KR101104402B1 - Method and Apparatus for Controlling Phase-Shift DC/DC Full-Bridge Converter - Google Patents

Abstract

The present invention relates to a phase shift control apparatus for controlling a DC-DC full-bridge converter and a method thereof.
According to an embodiment of the present invention, there is provided a phase shift control apparatus for controlling a DC-DC full-bridge converter, comprising: a comparison unit configured to compare a reference voltage with an output of the DC-DC full-bridge converter and output a difference value; A first square wave generator for generating a first square wave by receiving a reference periodic wave of a reference frequency for switching the DC-DC full-bridge converter; A first half wave generator for receiving the first square wave and generating a first half wave having an inverted phase of the first square wave; A phase shift filter unit receiving a filter input wave having the same frequency as the reference frequency and the difference value and generating a second square wave having a phase shift value corresponding to the magnitude of the difference value in comparison with the filter input wave; And a second half wave generator for receiving the second square wave and generating a second half wave having an inverted phase of the second square wave.

Description

Phase shift control device for controlling DC-DC full-bridge converter and its method {Method and Apparatus for Controlling Phase-Shift DC / DC Full-Bridge Converter}

Embodiments of the present invention relate to a phase shift control system and method for controlling a DC-DC full-bridge converter. More specifically, a phase shift control system for controlling the DC-DC full-bridge converter by simplifying the circuit and facilitating the control in generating the control signals of the forward leg switch and the ground leg switch of the DC-DC full-bridge converter. And to a method thereof.

With the development of today's industry, many industrial fields are demanding power converters with high power density and conversion efficiency. In particular, since the 1990s, the government's active policies have highlighted the importance of the high-speed rail industry. Accordingly, Korea has been able to develop independently by adopting the high-speed rail technology of advanced countries.

The next generation high-speed railway currently under development is a high-speed train with a target speed of 400 km / h and an operating speed of 350 km / h, and high efficiency, high performance and high density power converters are needed to realize this. Auxiliary power supplies for the next-generation high-speed railway consist of an AC / DC converter, a DC / AC static inverter, and a battery charger. Among these, the battery charger supplies stable power to a load requiring DC power. In general, phase shifting ZVS (zero voltage switching) full-bridge DC / DC converters used in battery chargers increase the leakage inductance of high-frequency transformers or insert inductances in series to ensure a stable ZVS operating range. Although this method can secure a stable ZVS operating range, it is difficult to obtain a desired output voltage by reducing the effective duty and decreasing the secondary voltage utilization rate of the high frequency converter. However, this problem can be solved by adding an auxiliary circuit to the converter.

However, when generating the control signal of the forward leg switch and the ground leg switch of a DC-DC full-bridge converter, the circuit is complicated and the circuit is replaced when the operating conditions of the converter change according to the conventional analog chips and peripheral circuits. And tuning is required, so it is difficult to change the phase shift filter function to suit the control purpose.

The embodiment of the present invention simplifies the circuit and facilitates control in generating the control signals of the forward leg switch and the ground leg switch of the DC-DC full-bridge converter to control the DC-DC full-bridge converter.

According to an embodiment of the present invention, a phase shift control system for controlling a DC-DC full-bridge converter, the phase shift control system comprising: a comparison unit for comparing a reference voltage and the output of the DC-DC full-bridge converter and outputting a difference value; A first square wave generator for generating a first square wave by receiving a reference periodic wave of a reference frequency for switching the DC-DC full-bridge converter; A first half wave generator for receiving the first square wave and generating a first half wave having an inverted phase of the first square wave; A phase shift filter unit receiving a filter input wave having the same frequency as the reference frequency and the difference value and generating a second square wave having a phase shift value corresponding to the magnitude of the difference value in comparison with the filter input wave; And a second half wave generator for receiving the second square wave and generating a second half wave having an inverted phase of the second square wave.

The phase shift control system further includes an A / D converter that receives the output of the DC-DC full-bridge converter and converts the digital value into a digital value, and the comparator compares the digital value with the reference voltage to determine the difference. You can print the value.

The filter input wave may be the first spherical file.

The phase shift control system includes: a first dead time generator configured to receive the first square wave and the first half-wave and generate an advance leg switch control signal having a dead time; And a second dead time generator configured to receive the second square wave and the second half-wave and generate a ground leg switch control signal having a dead time.

The phase shift filter may map the difference value to an operation reference frequency and obtain a phase shift value by applying the operation reference frequency as a variable to a transfer function for implementing a predetermined global pass filter.

The phase shift filter unit may include a storage unit configured to store the filter input wave value and the second square wave value for at least one period, and map the difference value to an operation reference frequency to filter the filter according to the magnitude of the operation reference frequency. An input wave, a value before one period of the filter input wave, and a value before one period of the second square wave are respectively converted as a function of the operation reference frequency, and the value before each period of the filter input wave and the filter input wave, respectively. And the second square wave may be generated by summing conversion values of a value before one cycle of the second square wave.

The operation reference frequency may have a minimum value when the difference value is less than or equal to a predetermined lower limit, and increase linearly as the difference value increases, and have a maximum value when the difference value is greater than or equal to a predetermined upper limit value.

In addition, according to another embodiment of the present invention, in the phase shift control method for controlling a DC-DC full-bridge converter, (a) by comparing the output voltage of the DC-DC full-bridge converter and the reference voltage to the difference value; Outputting; (b) receiving a reference periodic wave of a reference frequency for switching the DC-DC full-bridge converter to generate a first square wave; (c) generating a first half-wave having an inverted phase of the first square wave from the first square wave; (d) receiving a filter input wave having the same frequency as the switching period and the difference value, and generating a second square wave having a phase shift value according to the magnitude of the difference value compared to the filter input wave; And (e) receiving the second square wave to generate a second half wave having an inverted phase of the second square wave.

As described above, according to the embodiment of the present invention, the DC-DC full-bridge converter is simplified and easily controlled in generating the control signals of the forward leg switch and the ground leg switch of the DC-DC full-bridge converter. It is effective.

In addition, it is possible to simplify the control by converting and controlling the phase shift filter into an operation reference frequency so that the phase shift filter can be programmed as an equation and applied to a variable controlling the programmed equation without the circuit. The operation of the converter 200 can be simplified. If the operating conditions change during this time, circuit replacement and tuning are unnecessary, so that the phase shift filter function can be easily changed to suit the control purpose.

1 is a diagram illustrating a phase shift control system 100 for controlling a DC-DC full-bridge converter 200 according to an embodiment of the present invention.
2 is a diagram illustrating a circuit of a phase shift filter having an arbitrary phase shift value.
3 is a diagram illustrating a waveform input and output from a reference periodic wave to the output of the phase shift filter 108.
4 is a diagram illustrating output waveforms of the advanced leg gate signal (S1 gate signal, S3 gate signal) and ground leg gate signal (S2 gate signal, S4 gate signal) and the primary output voltage and output current of the converter 200. .
FIG. 5 is a diagram showing the voltage V _ch and the current I _ch applied to the capacitor C _h on the secondary side.
6 is a flowchart illustrating a phase shift control method of controlling a DC-DC full-bridge converter according to an embodiment of the present invention.
7 is a diagram illustrating a change in an operation reference frequency mapped according to a difference value.

Hereinafter, some embodiments of the present invention will be described in detail through exemplary drawings. In adding reference numerals to the components of each drawing, it should be noted that the same reference numerals are used to refer to the same components as much as possible even if displayed on different drawings. In describing the embodiments of the present invention, when it is determined that the detailed description of the related well-known configuration or function may obscure the gist of the present invention, the detailed description thereof will be omitted.

In addition, in describing the components of the embodiment of the present invention, terms such as first, second, A, B, (a), and (b) may be used. These terms are only for distinguishing the components from other components, and the nature, order or order of the components are not limited by the terms. If a component is described as being "connected", "coupled" or "connected" to another component, that component may be directly connected to or connected to that other component, but there may be another configuration between each component. It is to be understood that the elements may be "connected", "coupled" or "connected".

1 is a diagram illustrating a phase shift control system 100 for controlling a DC-DC full-bridge converter 200 according to an embodiment of the present invention.

As shown in FIG. 1, the phase shift control system 100 according to an exemplary embodiment of the present invention includes a comparator 102, a first square wave generator 104, a first half wave generator 106, and a phase shift filter. The unit 108 and the second half wave generator 110 is included. In some cases, the phase shift control system 100 further includes an A / D converter 112, a first dead time generator 114, a second dead time generator 116, and a gate drive 118. can do.

The comparator 102 compares the reference voltage with the output Vo of the DC-DC full-bridge converter 200 and outputs a difference value.

The first square wave generator 104 receives a reference periodic wave of a reference frequency for switching the DC-DC full-bridge converter 200 and converts it into a square wave.

The first half wave generator 106 receives the first square wave and generates a first half wave having an inverted phase of the first square wave.

The phase shift filter 108 receives the difference value from the filter input wave and the comparator 102 having the same frequency as the reference frequency, and compares the filter input wave with a second square wave having a phase shift value according to the magnitude of the difference value. Occurs.

The second half wave generator 110 receives the second square wave from the phase shift filter 108 and generates a second half wave having an inverted phase with respect to the second square wave.

The comparator 102 compares the reference voltage, which is a reference of the output Vo of the converter 200, with the output Vo of the DC-DC full-bridge converter 200, and outputs a difference value. The reference voltage is a value for comparing the output of the DC-DC full-bridge converter 200. If the difference value is positive, the phase shift control system 100 according to the embodiment of the present invention is a DC-DC full When the output of the bridge converter 200 is controlled in a decreasing direction, and the difference value is negative, the phase shift control system 100 according to an embodiment of the present invention is a DC-DC full-bridge converter 200. Control in the direction of increasing output.

In some embodiments, when the reference voltage is an analog value, the phase shift control system 100 directly receives the output of the DC-DC full-bridge converter 200. If the reference voltage is a digital value, the phase shift control system 100 may further include an A / D converter 112 that receives the output of the DC-DC full-bridge converter 200 and converts the digital value into a digital value. In this case, the comparator 102 compares the digital output value of the A / D converter 112 with a reference voltage having a digital value and outputs a difference value.

The first square wave generator 104 receives a reference periodic wave of a reference frequency for switching the DC-DC full-bridge converter 200 and converts it into a square wave. Here, the reference periodic wave may be in the form of a sine wave, but is not limited thereto. The reference square wave may be converted by the first square wave generator 104 into a square wave having the same frequency as that of the reference periodic wave.

The first half wave generator 106 receives the first square wave from the first square wave generator 104 and generates a first half wave having an inverted phase with respect to the first square wave. The first half wave generator 106 may be configured using an inverter (NOT gate) logic element.

The phase shift control system 100 of the present invention may further include a first dead time generator 114 for generating dead time of the first square wave (S1 control signal) and the first half-wave (S3 control signal). have. The first dead time generator 114 generates dead time for a predetermined time when the on / off operation between the first square wave and the switching elements S1 and S3 driven by the first half wave is toggled. will be.

When the on / off operation between the switch elements is toggled, although the gate signal is turned off, some time is required for the semiconductor switch element (for example, S1) to be actually turned off to have a high impedance state. For example, S3 is also turned on by the S3 control signal, and both switch elements are turned on, so that a short phenomenon occurs and the switch elements S1 and S3 may be damaged. Therefore, in order to prevent this, when the on / off operation between the switch elements is toggled, a dead time occurs in which both switch elements are turned off for a predetermined time, thereby preventing damage to the semiconductor switch element.

The first half wave generator 106 receives the first square wave generated by the first square wave generator 104 to generate the first half wave, thereby controlling the first square wave (S1 control signal) and the first half wave (S3). A pair of leading leg switch control signals are generated.

The phase shift filter 108 receives a difference value from the filter input wave and the comparator 102 having the same frequency as the switching reference frequency. Here, the filter input wave may be a square file generated by the first square wave generator 104 or a reference periodic file in the form of a sine wave. In the present embodiment, a description will be made assuming a square wave generated by the first square wave generator 104.

The phase shift filter 108 generates a second square wave having a phase shift value according to the magnitude of the difference value with respect to the filter input wave.

The phase shift filter unit 108 maps the difference value to the operation reference frequency, and applies the operation reference frequency mapped to the transfer function for implementing a predetermined global pass filter to the filter input wave, thereby applying the difference to the filter input wave. It is possible to obtain a second square wave having a phase shift value according to.

The phase shift filter 108 may be programmed to implement a transfer function having any phase shift global filter function.

2 is a diagram illustrating a circuit of a phase shift filter having an arbitrary phase shift value.

As illustrated in FIG. 2, the phase shift filter function of the phase shift filter 108 may be expressed as Equation 1 as an example of a transfer function having a single gain. In the present embodiment, the transfer function of Equation 1 is taken as an example, but is not limited thereto.

(Ω: switching frequency)

Equation 1 may be represented by Equation 2.

)(only,

)

Equation 2 can be expressed in the form of "A + jB", and can be expressed as Equation 3 by subtracting the denominator from the molecular angle, which can be adjusted by changing the gain to ω _c (operation reference frequency). Do.

)(only,

)

Here, the operation reference frequency may be set to have a minimum value when the difference value is less than or equal to a predetermined lower limit, and to increase the operation reference frequency proportionally as the difference value increases, and to set the operation reference frequency to have a maximum value when the difference value is greater than or equal to the predetermined upper limit value. For example, suppose on the circuit conditions of Fig. 2 that ω = 100 kHz, R = 100 kΩ, and C = 0.1 μF, if the difference value is 0, it is set to (ω _c = 100 kHz) and the difference value is +1. If it is above, it can be set to (ω _c = 200 kHz), and if the difference is less than -1, it can be set to (ω _c = 50 kHz) and set so that the difference varies linearly between +1 and -1. .

Therefore, if the difference value is +1, the phase shift value is 120 °, if the difference value is 0, the phase shift value is 90 °, and if the difference value is -1, the phase shift value is 60 °.

In order to generate the second square wave by controlling the phase shift filter function, the phase shift filter 108 may be performed through the following process.

Step 1: The transfer function of the phase shift filter is determined in the analog domain as shown in Equation 4.

(Tustin 변환)를 대입하여 수학식 5와 같이 Z 도메인에서 정리한다(단, T: 스위칭 주파수의 주기).Step 2:

(Tustin transform) is substituted in the Z domain as shown in Equation 5 (where T is the period of the switching frequency).

,

,

이다.)(only,

,

,

to be.)

관계를 이용하여 수학식 6과 같이 시간 도메인으로 옮긴다.Step 3:

The relationship is used to move to the time domain as shown in Equation 6.

As shown in Equation 6, the phase shift filter 108 maps the difference value to the operation reference frequency (ω _c ), and then filter input wave x (t) and filter input according to the magnitude of the operation reference frequency. A value before one cycle of the wave (x (tT)) and a value before one cycle of the second square wave (y (tT)) are respectively converted as a function of the operation reference frequency, and the converted value of the filter input wave (-(ω _c T-2) x (t) / (ω _c T + 2)), the converted value of the value one cycle before the filter input wave (here x (tT)) and the converted value of the value one cycle before the second square wave ( A second square wave as in Equation 6 may be generated by summing − (ω _c T-2) y (tT) / (ω _c T + 2)).

The phase shift filter unit 108 includes a storage unit 108a to store the value of the filter input wave for at least one recent period and the value of the second square wave for at least one recent period. Therefore, the phase shift filter 108 reads the value x (t-T) one cycle before the filter input wave and the value y (t-T) one cycle before the second square wave from the storage 108a.

The phase shift filter 108 may generate a second square wave to have a predetermined phase difference from the filter input wave when the input difference value is zero. This is to implement the zero voltage zero current switching of the converter 200, which is well known, and thus details thereof will be omitted.

The second half wave generator 110 receives the second square wave generated by the phase shift filter 108 to generate a second half wave, thereby generating a second square wave (S2 control signal) and a second half wave (S4 control signal). ), A pair of ground leg switch control signals are generated.

The phase shift control system 100 of the present invention may further include a second dead time generator 116 for generating a dead time of the ground leg switch control signal. The second dead time generator 116 is for generating a dead time for a predetermined time when the on / off operation between the switching elements S2 and S4 driven by the S2 control signal and the S4 control signal is toggled. .

Although the first dead time generating unit 114 and the second dead time generating unit 116 have been described as being separately configured, according to an exemplary embodiment, the first dead time generating unit 114 and the second dead time generating unit 114 may be configured as one circuit, but the present invention is not limited thereto. Do not.

The gate drive 118 includes an advance leg gate signal (S1 gate signal and an S3 gate signal) generated from the first dead time generator 114 and the second dead time generator 116, a ground leg gate signal (S2 gate signal, and the like. S4 gate signal) is received to generate forward leg drive signals G1 and G3 and ground leg drive signals G2 and G4 for driving the data of switches S1, S2, S3 and S4, respectively.

According to the switch driving of the gate drive 118, the on-time phase difference between the advanced leg switches S1 and S3 and the ground leg switches S2 and S4 is adjusted to control the output Vo of the converter 200.

3 is a diagram illustrating a waveform input and output from a reference periodic wave to the output of the phase shift filter 108.

When the reference periodic wave as shown in FIG. 3A is input to the first square wave generator 104, the first square wave generator 104 generates the first square wave as shown in FIG. 3B. When the difference value is input to the phase shift filter unit 108 from the first square wave and the comparator 102 as shown in FIG. 3B, the phase shift filter unit 108 receives the first square wave according to the magnitude of the difference value received. A waveform as shown in Fig. 3C having a phase difference with respect to the input wave) is generated. When a device that generates a square wave, such as an op-amp, is connected to the output of the phase shift filter 108, a switching waveform having a square wave shape as shown in FIG. 3D is generated. In general, the phase shift filter 108 may output a waveform as shown in FIG. 3D by using a square wave generator such as an op-amp.

As described above, the phase shift filter 108 and the second half wave generator 110 phase-adjust the ground leg switch control signal (S2 control signal and S4 control signal) to the advanced leg switch control signal (S1 control signal and S3). By changing the phase relative to the control signal), the DC-DC full-bridge converter 200 can obtain a desired output voltage.

4 is a diagram illustrating output waveforms of the advanced leg gate signal (S1 gate signal, S3 gate signal) and ground leg gate signal (S2 gate signal, S4 gate signal) and the primary output voltage and output current of the converter 200. .

FIG. 4A is a diagram illustrating one timing axis in order to compare timings of a pair of advanced leg gate signals (S1 gate signal and S3 gate signal), respectively.

As shown in FIG. 4A, the dead time is generated by the first dead time generator 114 in the fastening leg gate signal (S1 gate signal and S3 gate signal), and the dead time is between the S1 gate signal and the S3 gate signal waveform. An interval is set to prevent simultaneous conduction of switches S1 and S3.

4B is a diagram illustrating one timing axis in order to compare timings of a pair of ground leg gate signals (S2 gate signal and S4 gate signal), respectively.

As shown in FIG. 4B, the dead time is also generated by the second dead time generator 116 with respect to the ground leg gate signals (S2 gate signal and S4 gate signal), and thus a dead time between the S2 gate signal and the S4 gate signal waveform. The interval is set so as to prevent simultaneous conduction of switches S2 and S4.

4C illustrates the primary output voltage of the converter 200, and FIG. 4D illustrates the primary output current of the converter 200.

As shown in Fig. 4C, a positive output waveform of positive side occurs in a section in which S1 and S2 are on at the same time, and a negative one in a section in which S3 and S4 are on at the same time. A secondary output waveform is generated. By adjusting the phase difference between the advanced leg gate signal (S1 gate signal, S3 gate signal) and the ground leg gate signal (S2 gate signal, S4 gate signal) as described above, the sections in which S1 and S2 are simultaneously On and S3 and S4 The primary output voltage is controlled by adjusting the section at which both are on simultaneously. Therefore, the secondary output voltage and the output Vo of the converter 200 are controlled in proportion to the primary output voltage.

FIG. 5 is a diagram showing the voltage V _ch and the current I _ch applied to the capacitor C _h on the secondary side.

Fig. As shown in Figure 5, voltage (V _ch) is S1, S2 are simultaneously turned on (On) This section and S3, S4 is turned on (On) the interval voltage occurs, and the voltage (V _ch) in which at the same time is It is delivered to the output load.

6 is a flowchart illustrating a phase shift control method of controlling a DC-DC full-bridge converter according to an embodiment of the present invention.

As shown in FIG. 6, the method for controlling phase shift according to an embodiment of the present invention includes a difference value output step S602, a first square wave generation step S604, a first half wave generation step S606, a filter input wave and Differential value receiving step (S608), operation reference frequency mapping step (S610), second square wave generation step (S612), second half-wave generation step (S614), dead time generation step (S616) and switch gate drive step (618) ).

In the difference value output step S602, the difference value is output by comparing the output Vo of the DC-DC full-bridge converter with a reference voltage. In this case, when the output Vo of the DC-DC full-bridge converter has an analog value, it may be directly compared with the reference voltage (in this case, the reference voltage may also be an analog value), but the output Vo of the converter is A. After the / D conversion, the difference value may be output compared with the reference voltage (in this case, the reference voltage may also be a digital value).

In the first square wave generation step S604, a reference square wave of a reference frequency for switching the DC-DC full-bridge converter 200 is received to generate a first square wave.

In the first half wave generation step (S606), a first half wave is generated from the first square wave having the inverted phase of the first square wave.

In the filter input wave and difference value receiving step S608, the filter input wave and difference value output step S602 having the same frequency as the switching period of the converter 200 are received. Here, the filter input wave may be a first rectangular file.

In the operation reference frequency mapping step (S610), the received difference value is mapped to the operation reference frequency. Here, the operation reference frequency mapped may be set to have a minimum operation reference frequency value when the difference value is less than or equal to a predetermined lower limit, and to increase linearly as the difference value increases, and to have a maximum operation reference frequency value when the difference value is greater than or equal to the predetermined upper limit value. .

7 is a diagram illustrating a change in an operation reference frequency mapped according to a difference value.

FIG. 7 illustrates that the operation reference frequency increases in proportion to the difference value when the operation reference frequency increases linearly as the difference value increases, and does not necessarily increase linearly.

In the second square wave generation step (S612), a second square wave having a phase shift value according to the magnitude of the difference value is generated with respect to the filter input wave.

In the second square wave generation step S612, the filter input wave, the value before one cycle of the filter input wave, and the value before one cycle of the second square wave are respectively determined according to the magnitude of the operation reference frequency generated in the operation reference frequency mapping step S610. A second square wave is generated by converting as a function of the operation reference frequency and adding up the converted values of each filter input wave, one cycle before the filter input wave, and one cycle before the second square wave.

In the second half wave generation step (S614), a second square wave is received to generate a second half wave having an inverted phase of the second square wave.

In the dead time generating step (S616), the dead time between the first square wave (S1 control signal) and the first half wave (S3 control signal) and between the second square wave (S2 control signal) and the second half wave (S4 control signal) Will cause dead time.

In the switch gate drive operation 618, an advance leg gate signal (S1 gate signal and an S3 gate signal) and a ground leg gate signal (S2 gate) generated from the first dead time generator 114 and the second dead time generator 116 may be used. Signal and S4 gate signal) to generate the advance leg drive signals G1 and G3 and the ground leg drive signals G2 and G4 that drive the data of the switches S1, S2, S3 and S4, respectively.

According to the switch driving of the gate drive 118, the on-time phase difference between the advanced leg switches S1 and S3 and the ground leg switches S2 and S4 is adjusted to control the output Vo of the converter 200.

As described above, according to the embodiment of the present invention, the DC-DC full-bridge converter is simplified and easily controlled in generating the control signals of the forward leg switch and the ground leg switch of the DC-DC full-bridge converter. It is effective.

In addition, it is possible to simplify the control by converting and controlling the phase shift filter into an operation reference frequency so that the phase shift filter can be programmed as an equation and applied to a variable controlling the programmed equation without the circuit. The operation of the converter 200 can be simplified. If the operating conditions change during this time, circuit replacement and tuning are unnecessary, so that the phase shift filter function can be easily changed to suit the control purpose.

In the above description, all elements constituting the embodiments of the present invention are described as being combined or operating in combination, but the present invention is not necessarily limited to the embodiments. That is, all of the components may operate selectively in combination with one or more of them. In addition, although all of the components may be implemented in one independent hardware, each or all of the components may be selectively combined to perform some or all functions combined in one or a plurality of hardware. It may be implemented as a computer program having a. Codes and code segments constituting the computer program may be easily inferred by those skilled in the art. Such a computer program may be stored in a computer readable storage medium and read and executed by a computer, thereby implementing embodiments of the present invention. The storage medium of the computer program may include a magnetic recording medium, an optical recording medium, a carrier wave medium, and the like.

In addition, the terms "comprise", "comprise", or "having" described above mean that the corresponding component may be embedded unless otherwise stated, and thus, other components. It should be construed that it may further include other components rather than to exclude them. All terms, including technical and scientific terms, have the same meanings as commonly understood by one of ordinary skill in the art unless otherwise defined. Terms commonly used, such as terms defined in a dictionary, should be interpreted to coincide with the contextual meaning of the related art, and shall not be construed in an ideal or excessively formal sense unless explicitly defined in the present invention.

The foregoing description is merely illustrative of the technical idea of the present invention, and various changes and modifications may be made by those skilled in the art without departing from the essential characteristics of the present invention. Therefore, the embodiments disclosed in the present invention are not intended to limit the technical idea of the present invention but to describe the present invention, and the scope of the technical idea of the present invention is not limited by these embodiments. The protection scope of the present invention should be interpreted by the following claims, and all technical ideas within the equivalent scope should be interpreted as being included in the scope of the present invention.

100: phase shift control system
102: comparison unit
104: first square wave generator
106: first half wave generator
108: phase shift filter
108a: storage
110: second half wave generator
112: A / D converter
114: first dead time generator
116: second dead time generating unit
118: gate drive
200: converter

Claims (13)

In the phase shift control device for controlling a DC-DC full-bridge converter,
A comparator for comparing a reference voltage with an output of the DC-DC full-bridge converter and outputting a difference value;
A first square wave generator for generating a first square wave by receiving a reference periodic wave of a reference frequency for switching the DC-DC full-bridge converter;
A first half wave generator for receiving the first square wave and generating a first half wave having an inverted phase of the first square wave;
A phase shift filter unit receiving a filter input wave having the same frequency as the reference frequency and the difference value and generating a second square wave having a phase shift value corresponding to the magnitude of the difference value in comparison with the filter input wave; And
A second half wave generator for receiving the second square wave and generating a second half wave having an inverted phase of the second square wave;
Including,
The phase shift filter unit may include a storage unit configured to store the filter input wave value and the second square wave value for at least one period, and map the difference value to an operation reference frequency to filter the filter according to the magnitude of the operation reference frequency. An input wave, a value before one period of the filter input wave, and a value before one period of the second square wave are respectively converted as a function of the operation reference frequency, and the value before each period of the filter input wave and the filter input wave, respectively. And generating the second square wave by summing conversion values of a value before one cycle of the second square wave. The method of claim 1,
The phase shift control device,
And an A / D converter for receiving the output of the DC-DC full-bridge converter and converting it into a digital value.
And the comparator compares the digital value with the reference voltage and outputs the difference value. The method of claim 1,
And the filter input wave is the first square wave. The method of claim 1,
The phase shift control device,
A first dead time generator configured to receive the first square wave and the first half-wave and generate an advance leg switch control signal having a dead time; And
A second dead time generator for receiving the second square wave and the second half-wave and generating a ground leg switch control signal having a dead time;
Phase shift control apparatus further comprising a. In the phase shift control device for controlling a DC-DC full-bridge converter,
A comparator for comparing a reference voltage with an output of the DC-DC full-bridge converter and outputting a difference value;
A first square wave generator for generating a first square wave by receiving a reference periodic wave of a reference frequency for switching the DC-DC full-bridge converter;
A first half wave generator for receiving the first square wave and generating a first half wave having an inverted phase of the first square wave;
A phase shift filter unit receiving a filter input wave having the same frequency as the reference frequency and the difference value and generating a second square wave having a phase shift value corresponding to the magnitude of the difference value in comparison with the filter input wave; And
A second half wave generator for receiving the second square wave and generating a second half wave having an inverted phase of the second square wave;
Including,
The phase shift filter unit maps the difference value to an operation reference frequency and obtains a phase shift value by applying the operation reference frequency as a variable to a transfer function for implementing a predetermined global pass filter, and the operation reference frequency is the difference value. The phase shift control device having a minimum value below the predetermined lower limit and linearly increasing as the difference value increases, and having a maximum value when the difference value is above the predetermined upper limit value. delete The method of claim 1,
The operation reference frequency has a minimum value when the difference value is less than or equal to a predetermined lower limit, and increases linearly as the difference value increases, and has a maximum value when the difference value is greater than or equal to a predetermined upper limit value. In the phase shift control method for controlling a DC-DC full-bridge converter,
(a) comparing the output of the DC-DC full-bridge converter with a reference voltage and outputting a difference value;
(b) receiving a reference periodic wave of a reference frequency for switching the DC-DC full-bridge converter to generate a first square wave;
(c) generating a first half-wave having an inverted phase of the first square wave from the first square wave;
(d) receiving a filter input wave having the same frequency as the switching period and the difference value, and generating a second square wave having a phase shift value according to the magnitude of the difference value compared to the filter input wave; And
(e) receiving the second square wave and generating a second half wave having an inverted phase of the second square wave
Including,
In step (d),
The difference value is mapped to an operation reference frequency, and the filter input wave, a value before one cycle of the filter input wave, and a value before one cycle of the second square wave are functions of the operation reference frequency, respectively, according to the magnitude of the operation reference frequency. And converting according to the sum of the filter input wave, the value before one cycle of the filter input wave, and the value of one cycle before the second square wave, to generate the second square wave. Way. The method of claim 8,
In the step (a)
And outputting the difference value by A / D conversion of the output of the DC-DC full-bridge converter and comparing with the reference voltage. The method of claim 8,
And the filter input wave is the first square wave. In the phase shift control method for controlling a DC-DC full-bridge converter,
(a) comparing the output of the DC-DC full-bridge converter with a reference voltage and outputting a difference value;
(b) receiving a reference periodic wave of a reference frequency for switching the DC-DC full-bridge converter to generate a first square wave;
(c) generating a first half-wave having an inverted phase of the first square wave from the first square wave;
(d) receiving a filter input wave having the same frequency as the switching period and the difference value, and generating a second square wave having a phase shift value according to the magnitude of the difference value compared to the filter input wave; And
(e) receiving the second square wave and generating a second half wave having an inverted phase of the second square wave
Including,
In step (d),
A phase shift value is obtained by applying the operation reference frequency as a variable to a transfer function that maps the difference value to an operation reference frequency and implements a predetermined global pass filter, and the operation reference frequency is equal to or less than a predetermined lower limit value. And having a minimum value and linearly increasing as the difference value increases, and having a maximum value when the difference value is greater than or equal to a predetermined upper limit value. delete The method of claim 8,
And the operation reference frequency has a lowest value when the difference value is less than or equal to a predetermined lower limit, and increases linearly as the difference value increases, and has a maximum value when the difference value is greater than or equal to a predetermined upper limit value.

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