JP5364125B2 - Semiconductor device - Google Patents

Description

  The present invention relates to a semiconductor device that requires high speed and low power consumption, and more particularly to a technique that is effective when applied to a low power processor circuit used in a portable device.

  In recent years, high speed and low power consumption have been strongly demanded for semiconductor devices, particularly semiconductor devices such as processors.

In general, speeding up can be achieved by lowering the threshold voltage. As a method of lowering the threshold voltage, a method of applying a voltage to the substrate of the MOS transistor is known. For example, Non-Patent Document 1 (1996, IEEE, Journal of Solid-State Circuits, VOL. 31, No. 11, pages 1770 to 1779, “A 0.9-V, 150-MHz, 10-mW, 4 mm. ² , 2-D Discrete Cosine Transform Core Processor with Variable Threshold-Voltage-Voltage (VT) Scheme ") (see FIG. 2 in this document), applying a voltage to a CMOS substrate (well). The current capability is changed by changing the threshold voltage.

  However, if the threshold voltage is lowered for speeding up, the leakage current increases, which causes a problem that the power consumption increases.

  Therefore, in order to realize low power consumption at the same time as speeding up, a technique for reducing the threshold voltage and suppressing the increase in leakage current is required. As a technique for improving the current capability of the MOS transistor and simultaneously reducing the leakage current, there is a technique of changing the voltage applied to the back gate according to the operation state of the transistor. For example, a conductive light-shielding layer covered with an insulating film is formed in the lower layer of a thin film transistor that constitutes a pixel of a liquid crystal display device, and this is used as a back gate. By applying a voltage to this back gate, the current capability of the thin film transistor In other words, a configuration is known in which the current capability is increased when the signal voltage is written to the pixel and the leakage current is suppressed after the writing (see Japanese Patent Application Laid-Open No. 2000-131713).

  Alternatively, in a circuit using a bulk type MOS transistor, there is known a method for realizing high speed and low power consumption by controlling a voltage applied to a back gate during active and standby (Patent Document). 2).

JP 2000-131713 A JP-A-10-340998

“A 0.9-V, 150-MHz, 10-mW, 4 mm2, 2-D Discrete Cosine Transform Core Processor with Variable Threshold-Voltage (VT) Scheme“, Journal of Sol E E 19 VOL. 31, no. 11, p. 1770-1779

  However, the method of applying a bias to the substrate (well) generally increases the leakage current of the MOS transistor (for example, in the case of a 3 GHz PC processor composed of CMOS, the leakage current is 20 to 30 A per chip. Also become). That is, PN junctions exist between the source and drain terminals of each CMOS transistor and the substrate (well) terminal. For example, in an nMOS, the substrate is p-type and the source is n-type. In nMOS, a positive voltage is applied to the substrate (well) in order to lower the threshold value during operation. However, since the PN junction is turned on, the voltage range that can be applied is limited. In particular, this range becomes narrower as the temperature increases. In a low-power processor application, the value of the voltage that can be applied to the substrate (well) with respect to the source is limited to about 0.5 V at room temperature and about 0.2 V at a high temperature (eg 80 ° C.). This is less effective, and the current due to the PN junction is not small at this time, and it becomes difficult to meet the target specification. In addition, when switching between not only positive potentials but also 0 V and negative voltages, the change in threshold voltage with respect to the voltage applied to the substrate is small. For this reason, the voltage amplitude required to cause a desired threshold voltage change is large, and it is necessary to drive a large capacitor with this voltage amplitude.

  On the other hand, there is a method using the back gate described in Patent Document 1 described above for a device having an SOI structure that does not have a PN junction between the substrate and the source and drain. This method requires a circuit for controlling the voltage applied to the back gate of each device according to the operating state of the device. However, the element circuits that make up the system differ in the degree of demand for high speed and low power consumption depending on their functions, and the method of applying the back gate voltage to all devices that make up the circuit is: It is not effective for power consumption of the entire system. Even if a method of controlling the applied voltage according to each device is employed, there is a problem that the circuit configuration is complicated.

  Further, in the circuit using the bulk MOS transistor described above, there is a problem that a switch circuit for switching the voltage applied to the back gate is required separately.

  Accordingly, an object of the present invention is to provide a semiconductor device that achieves high speed and low power consumption by controlling the voltage applied to the back gate of the MOS device, thereby reducing the threshold voltage and suppressing the leakage current. Further, it is to provide a semiconductor device characterized in that each circuit constituting the system is selectively used according to its circuit function without increasing the circuit scale necessary for controlling the back gate. .

  An object of the present invention is to provide a first semiconductor layer formed on a semiconductor substrate via a buried oxide film, and a source region and a drain region formed in the first semiconductor layer and having a thickness of the first semiconductor layer. A channel region formed so as to be sandwiched between the source region and the drain region, a first gate formed on the first main surface side of the channel region, and a lower surface of the buried oxide film A fully-depleted SOI-MOS transistor having a second gate made of a conductive layer and an insulating isolation layer formed on the semiconductor substrate so as to surround the first semiconductor layer; A first MOS transistor electrically connected to a second gate; a second MOS transistor in which each of the first gate and the second gate is electrically controlled independently; Has can be achieved by a semiconductor device including a first circuit constituted by said first MOS transistor, and a second circuit composed of the second MOS transistor on said semiconductor substrate.

  In other words, a transistor characterized in that a buried oxide (BOX) layer is thin (for example, 30 nm or less) in a fully depleted (FD) SOI structure is used. As a result, the back gate with the BOX layer as a gate insulating film can be driven to dynamically take a high threshold state and a low threshold state. Since there is a BOX layer, there is no PN junction as in the conventional example, and no current due to this PN junction flows.

  The present invention is particularly characterized in that a MOS transistor having the back gate connected to the normal gate and a MOS transistor for independently driving the back gate and the normal gate are used in combination. In the latter MOS transistor, the back gates of the pMOS part are connected in common in the preset circuit block, and the back gates of the nMOS part are connected in common, and this terminal is connected to the activation of the circuit block (input signal). The state is controlled according to the logic operation based on the above and the output signal is being output. The former MOS transistor is also used as a circuit for driving a heavy load, a circuit for driving a back gate commonly connected in a circuit block using the latter MOS, and a switch MOS provided between the circuit block and a power source.

  As a result, the driving capability of the MOS transistor can be increased by driving the back gate to realize high speed, and in a state where the load is not charged / discharged, the back gate is driven in the reverse polarity to reduce the leakage current. be able to. Thus, both high speed and low power can be achieved.

  According to the present invention, high speed and low power consumption of a semiconductor device such as a low power processor can be realized while suppressing an increase in circuit scale and reducing an increase in the area of a semiconductor chip.

The figure which shows the 1st Example of this invention. The figure which shows the operation example of FIG. The figure which shows the cross-sectional example of pMOS. The figure which shows the cross-sectional example of nMOS. The figure which shows the example of a characteristic of nMOS. The figure which shows the example of a characteristic of nMOS when a gate and a back gate are connected. The figure which shows the 2nd Example of this invention. The figure which shows the example of a power supply voltage. The figure which shows the 3rd Example of this invention. The figure which shows the 4th Example of this invention. The figure which shows the 5th Example of this invention. The figure which shows the example of a top view of CMOS in this invention. Sectional drawing in the line of A-A1-A2-B2-B1-B shown to FIG. 12A. The figure which shows the cross-sectional example of CMOS. The figure which shows the cross-sectional example of CMOS. The figure which shows the cross-sectional example of CMOS. The figure which shows the 6th Example of this invention. The figure which shows the operation example of FIG. The figure which shows gate electrode material and gate insulating-film material. The figure which shows the 7th Example of this invention. The figure which shows the example of control of FIG. The figure which shows the circuit example SVC which detects the temperature change and dispersion | variation, and produces | generates the voltage which correct | amends this. The figure which shows the circuit example of VCA generator which comprises a part of FIG. 21A. The figure which shows the cross-sectional example of CMOS. The figure which shows the cross-sectional example of CMOS. The figure which shows the cross-sectional example of CMOS. The figure which shows the SRAM circuit example comprised by four transistors. The figure which shows the SRAM circuit example comprised by six transistors. The figure which shows the DRAM circuit example comprised by three transistors. The figure which shows the DRAM circuit example comprised by three transistors. The figure which shows the example of arrangement | positioning of a logic circuit and memory. The figure which shows the example of arrangement | positioning of a logic circuit and memory. The figure which shows the Example which mounts the circuit SVC which detects the temperature change and dispersion | variation, and generates the voltage which correct | amends this on the same chip | tip. FIG. 31B is a block arrangement diagram showing a configuration example of the SVC 1 in FIG. 31A. The figure which shows the structural example with a back gate. The figure which shows the structural example with a back gate. The figure which shows the structural example of PD-SOI.

Hereinafter, the present invention will be described in detail with reference to the drawings.
<Example 1>
FIG. 1 is a diagram showing a first embodiment of the invention.

    This circuit can be roughly divided into three blocks. First, DCL is a logic circuit block, BAC is a circuit for controlling the back gate of the DCL, and PFC is a circuit for driving an output terminal BO1 having a large load.

  In the DCL, a two-stage inverter circuit is taken as an example of the logic circuit here, and the input to this block is BI1 and the output is CO1. The power supply voltage is VCC and the ground voltage is VSC. C21 and C22 are inverter circuits, the input of C11 is BI1, the output of C11 is the input of C22, and the output of C22 is CO1. In this DCL logic circuit block, in the example of this figure, two stages of inverter circuits, the CMOS transistors constituting this logic circuit can be controlled from the outside (from outside this logic circuit block). It has the feature of including things. In this figure, in C21 and C22, the back gates of the pMOS transistors are combined into BGP, and the back gates of the nMOS are combined into BGN. Thereby, as will be described later, the voltage of the back gate can be changed according to the operation mode and operation state of the logic circuit block. By changing the back gate voltage, the threshold voltage of the nMOS and pMOS can be changed. For this reason, by changing the signal voltage generated in BGP and BGN, in the standby state, the back gate voltage is changed to create a high threshold voltage to reduce the leakage current. Can be changed to create a state in which the threshold voltage is low to increase the on-current and obtain a large driving current.

  BAC is a circuit for generating BGP and BGN. Here, CAC is constituted by two stages of inverters in which a gate and a back gate are directly connected. The power supply voltage is VCA and the ground voltage is VSA. BA1 is an input signal. By this signal, BGP and BGN are switched, whereby the state of the threshold voltage of the nMOS and pMOS included in the DCL can be changed.

  The PFC is a circuit for receiving the output CO1 of the logic circuit block DCL and driving BO1, which is a heavy load terminal such as a long wiring. In this figure, C3 is composed of one stage of inverters in which a gate and a back gate are directly connected, but the number of stages varies depending on the load of BO1. The power supply voltage is VCO and the ground voltage is VSO.

  In these three components, the potentials of the power supply voltages VCA, VCC, and VCO may be the same or different. Even in the case of the same potential, in an actual LSI chip layout, power supply wiring may be prepared independently for VCA, VCC, and VCO from a pad connected to an external power supply. VCA, VCC, and VCO are, for example, 1V. Further, although VSC, VSA, and VSO are ground voltages, they may be different from each other. Negative voltage can be taken.

  According to the present embodiment, since the threshold voltage states of the nMOS and pMOS in the DCL can be changed, the threshold voltage in the DCL can be selected according to the operating state of the DCL. . As a result, when speeding up is required, the threshold voltage can be set to a low absolute value, and the threshold voltage can be set high to keep the leak current low when the speed is low or in a standby state. In this way, high speed and low power can be achieved.

  FIG. 2 is a diagram for explaining an operation example of the configuration of FIG. BA1 is a signal for activating whether to activate DCL, that is, changing the state of DCL, and BGP and BGN are control signals to DCL generated by BA1. BI1 is an input signal to the logic circuit block DCL, and BO1 is a signal obtained by current amplification of the output CO1 of the DCL by the PFC. Here, it is assumed that the voltage level of BA1 when DCL is not activated is a low voltage level VSA, and the voltage level of BA1 when DCL is activated is a high voltage level VCA.

  In the initial state, when DCL is in a standby state, BA1 is VSA which is a low voltage level. Thereby, in BAC, the voltage level of BGP is VCA and the voltage level of BGN is VSA by the inverter in two stages. As a result, in the DCL, both the pMOS and nMOS MOS transistors have a high threshold voltage, and the leakage current can be kept low.

In order to activate DCL, first, BA1 is switched from the VSA level to the VCA level.
Thereby, in BAC, the signals of BGP and BGN are switched by the inverter in two stages. In the BGP that controls the back gate of the DCL pMOS, the high level VCA is switched to the low level VSA, and in the BGN that controls the nMOS back gate, the low level VSA is switched to the high level VCA. As a result, in the DCL, the threshold voltages of both the pMOS and nMOS are lowered, and a high speed operation is possible. Thereafter, a signal input from the BI1 to the DCL becomes a valid signal, and a logical operation is performed in the DCL in response to the input signal. In the example of FIG. 1, this logical operation consists of two stages of inverters. This is for ease of explanation, and of course, other logic circuits such as NAND and NOR may be used, and there may be a plurality of inputs BI1. The result of this logical operation is output to CO1 in FIG. 1, which increases the driving force in the output buffer PFC and becomes the output of BO1. As a means for generating BA1 to be input to the BAC, a circuit that is created outside the block of FIG. 1 and that controls various circuit blocks created by a circuit block before the circuit block of FIG. A block is prepared and generated here, and a circuit for monitoring the state of the input signal BA1 is provided to generate from this signal state. You may input from an external apparatus.

  When the logic operation of the DCL is finished and it is desired to deactivate it, BA1 is switched again to the voltage level of VSA. In response, BAC operates, BGP becomes VCA, and BGN becomes VSA. When this signal is input to the back gates of the DCL pMOS and nMOS, the threshold voltages of these MOS transistors become high again. As a result, the DCL becomes inactive again.

  By performing such an operation, in this embodiment, it is possible to realize high speed, low power, and low leakage current.

  Next, a structure example of a MOS transistor for performing such an operation is shown.

    FIG. 3 is a diagram illustrating a structural example of a pMOS. (A) shows a circuit diagram, (b) shows an example of a cross-sectional view, and names of terminals correspond to each other.

  In (b), p-sub is a substrate, its terminal is SB, STI is a trench-type insulating region (trench isolation region), and UTB is a buried oxide film. The thickness of the UTB is, for example, 10 to 20 nm. A MOS is formed on this UTB, S is a source terminal, G is a gate terminal, and D is a drain terminal, and these are p + region (source) and n region (channel formation) via silicide SC. Region), p + region (drain). This thickness is, for example, about 20 nm. There is an oxide film OX between the gate SC and the n region, which is a so-called MOS structure. This oxide film may be a so-called High-k film such as hafnium oxide. The gate is made of silicide, which is NiSi, for example. Other metal materials are also conceivable. There is an n region below the UTB, which is connected to the terminal BG. Therefore, as shown in the circuit diagram (a), the BG is connected to the n region of (b) via the capacitor using the UTB as an insulating film. This is a structure in which the second gate exists on the back surface of the MOS structure when this UTB is regarded as the second gate oxide film. Therefore, this gate is called a back gate. A configuration example of a circuit using this structure is shown in FIG. If the potential of p-sub is applied so that the voltage difference between the n region to which BG is connected and the p-sub to which SB which is the p region is connected is not forward, the voltage is applied to BG within this range. It is possible to change the threshold value of the MOS above the UTB. In such a structure, when the channel formation region has a thickness of about 20 nm in the above example, the semiconductor region (channel region) under the gate sandwiched between the source and the drain is completely depleted. Such a structure having a fully depleted channel region on the insulating film UTB is generally called an FD-SOI structure when the thickness of the UTB is not limited.

  FIG. 4 is a diagram showing a structural example of an nMOS. In the structural example of the pMOS in FIG. 3, since there are many common parts with the case where the p-type and n-type are interchanged, description of this part is omitted. However, a MOS is formed on the UTB, a gate made of silicide, n + It consists of a source and a drain made of silicide. In the example of FIG. 4, an n region is provided between the p region to which BG is connected and p-sub (terminal is SB), which is generally lighter in concentration but also p region, and is controlled by the terminal TW. I can do it. This is for electrically separating the p region to which the BG is connected and the p-sub which is the same p region. Since the potential of the terminal BG to which the BG is connected is changed as described with reference to FIGS. 1 and 2, even if these potentials are applied to the BG, electrical separation from the p-sub (SB) is not possible. A potential that can be realized by the reverse potential of the PN junction can be applied from TW. Although the pMOS of FIG. 3 and the nMOS of FIG. 4 are illustrated separately, the nMOS and the pMOS are actually formed in the same p-sub.

5 and 6 show an example in the case of applying a voltage to the back gate (BG).
5A is a circuit diagram, and FIG. 5B is the gate-source voltage VGS dependency of the drain current IDS when the voltage VBGS of the back gate BG is changed. From this (b), for example, when the current at the point where the gate-source voltage VGS is 0 V, that is, the leakage current in the off state, when the BG voltage VBGS is 0 V, the gate width is 10 per 1 micrometer. It can be seen that when the voltage VBGS is 1V, a large current of 3 digits or more flows while it is minus tenth power ampere. In addition, this figure is difficult to understand because the vertical axis is a logarithm, but the VGS is 1V, that is, about 20% in the on-state current, and the VBGS of 1V is larger than the case of VBGS of 0V. Thus, different currents can be taken by changing the back gate voltage VBG at the same gate-source voltage VGS. Therefore, as described with reference to FIGS. 1 and 2, in the circuit block DCL, a state with a small leakage current or a state with a large on-current can be created according to the state.

  FIG. 6 shows the dependence of the drain current IDS on the gate-source voltage VGS when the back gate and the gate are in direct contact with each other and only the gate G is driven as shown in the circuit diagram of FIG. In (b), the line A is the dependency at this time. The line B shows the time-dependent line when VBGS in Fig. 5 (b) is 1V, and the line C shows the time-dependent line when VBGS in Fig. 5 (b) is 0V. Thus, a small leakage current is realized when VGS is 0 V, that is, an off state, and a large on-current is realized when VGS is 1 V. As a result, as described with reference to FIGS. 1 and 2, high speed, low power, and low leakage current can be realized by using the circuit block BAC and the circuit block PFC.

  In the present invention, the BGs are independently controlled as shown in FIG. 5 in the logic circuit grouped like the DCL in FIG. In general, a system LSI is made up of many circuit blocks. However, not all circuit blocks are operating at all times, and the parts that operate temporally and spatially are part of many circuit blocks. This will change from moment to moment. Therefore, only the circuit block to be activated has a high on-current, and many non-activated circuit blocks have a very low off-current, thereby achieving high speed, low power, and low leakage. be able to. Furthermore, since the back gate is driven from outside this circuit block, the operation of this circuit block proceeds, so that each circuit in the DCL does not drive the back gate. Since the wiring is short inside the circuit block, the load driven by each circuit is almost determined by the gate capacitance. Therefore, it is important not to increase the gate capacitance, and this is achieved. On the other hand, the BAC in FIG. 1 is a circuit that determines whether to activate DCL, and the back gate must be driven in this circuit. In general, since activation is performed in a unit of time, it is sufficient that the BAC can be driven at the beginning and end of the activation. On the other hand, it is necessary to be able to accept a signal to shift to the activation state at any time. Therefore, the connection method shown in FIG. 6 is used because the control is simple. Since the PFC drives a large load, the influence of an increase in gate capacitance is reduced. Therefore, this also uses the method of FIG. 6 which is easy to control.

As described above, the first transistor using the FD-SOI having the thin box layer and connecting the gate and the back gate, and the second transistor that changes the voltage of the back gate from the other terminal during operation and standby. Were used in combination. As a result, in the logic circuit block, the second transistor is used in the logic circuit with a light load in the block, and the back gates are connected in common, and the gates can be controlled in accordance with the block activation. In addition, the first transistor is used in a circuit that performs this block activation and a logic circuit with a heavy load such as an output unit of the circuit block, and the back gate can be directly controlled by the gate input signal. As a result, high speed, low power, and low leakage can be achieved.
<Example 2>
Next, the DCL in FIG. 1 is a logic circuit block as described so far, and is activated and operated when necessary by the BAC. FIG. 7 shows another example.

  FIG. 7 shows the DCL including the NAND circuit C2 and the NOR circuit C3. In both cases, pMOS back gates are collectively referred to as BGP, and nMOS back gates are collectively referred to as BGN. The input is only BI1 from outside the DCL, but there may be other inputs. Although C2N1 and C3N1 are not shown in the figure, they are connected to the outputs of other circuits in the DCL, and this output signal is input. Here, the PFC has two stages of inverters. As in FIG. 1, BAC and PFC use a configuration in which a gate and a back gate are directly connected.

FIG. 8 shows an example of the power supply voltage. Case 1 is a case where a single power supply voltage is used (the ground voltage 0V is not counted as usual), and only a power supply voltage of 1V is used. That is, VCA, VCC, and VSC are 1V, and VSA, VSC, and VSO are 0V. At this time, SGP and SGN become a voltage of 0V or 1V. Even with such a simple voltage configuration, if the present invention is used, the threshold voltage can be changed as shown in FIG. 5 and FIG. The off-state current can be kept extremely small. As shown in FIGS. 3 and 4, the buried oxide film UTB has a thickness of 10 to 20 nm, and a fully depleted SOI MOS is used. The gate material is NiSi, for example. On the other hand, the on-current can be further increased and the off-current can be further decreased. This case is case 2. What is characteristic here is that VCA is set to 2V and VSA is set to -1V in the power supply of the BAC shown in FIGS. This increases the amplitude of the back gate. For example, in the case of an nMOS, the on-current increases by applying 2V instead of 1V to the back gate, and conversely, if −1V instead of 0V is applied to the back gate. The off current decreases. Although not shown here, the TW and SB voltages shown in FIGS. 3 and 4 also provide appropriate voltages.
<Example 3>
FIG. 9 shows an example of another logic circuit used for DCL. pc, carry, s0, s1, and sum are input / output signals. In both cases, the pMOS back gates are collectively connected to BGP, and the nMOS back gates are collectively connected to BGN. In this embodiment, a circuit indicated as GK is placed in some nodes. This is a latch circuit that holds a signal. This latch circuit is used to stably hold the signal level of the node connected during standby. In operation, the driving capability needs to be weak so as not to disturb the circuit that actually drives this node.
<Example 4>
Examples of this are shown in FIGS. The circuit has a configuration in which the outputs of each other are connected to the input. In this circuit, in the example of FIG. 10, the back gate is connected to the power source. That is, the pMOS is connected to VCC, and the nMOS is connected to VSC. With this connection, if the latch circuit has a driving capability that does not interfere with the operation of other circuits when the circuit block is activated, the back gate can be activated even when the circuit block is deactivated or in standby. Unlike other circuits connected to SGP and SGN, the drive capability does not drop. Further, according to the present embodiment shown in FIG. 11, it is possible to obtain a driving ability to firmly hold the level at the time of standby, and to change to a small driving force that does not disturb the operation of other circuits at the time of operation. is there. That is, the back gate of the pMOS is connected to the BGN, and the back gate of the nMOS is connected to the BGP in the reverse manner. With this connection, for example, taking an nMOS as an example, the on-current is small because the back gate is at a low level during operation, while on the other hand, a high voltage is applied to the back gate this time during standby. The current is large and will hold its voltage level firmly.

12A and 12B are diagrams showing examples of the CMOS structure in the present invention. 12A is a plan view, and FIG. 12B is a cross-sectional view taken along the line A-A1-A2-B2-B1-B. The nMOS and pMOS are formed on the p-sub with a structure described below, and both are separated by STI, which is a trench type insulating region. First, regarding the pMOS, the structure on the buried oxide film UTB is the same as the structure on the UTB shown in FIG. An n region is placed under the UTB and serves as a back gate. This back gate is taken out to the semiconductor surface via n +. The isolation region between the n + extraction region and the pMOS portion including UTB is SSTI, which is a trench type insulating region shallower than STI. In the nMOS portion, the structure on the buried oxide film UTB is the same as the structure on the UTB shown in FIG. A p region is placed under the UTB and serves as a back gate. This back gate is taken out to the semiconductor surface via p +. The isolation region between the p + extraction region and the nMOS portion including UTB is SSTI, which is a trench-type insulating region shallower than STI.
Further, a dn region that is an n-type semiconductor is provided to separate the p region under the UTB from the p-sub that is the same p-type semiconductor. This dn region is taken out to the semiconductor surface by an n region and an n + region arranged under the SSTI region. The STI separates the nMOS and the pMOS configured as described above. The dn region and the n region which is the back gate region of the pMOS are also separated. As a result, the threshold voltage can be changed according to the operation state of the circuit, and a high-speed, low power and low leakage current semiconductor device can be realized.

  13 and 14 are diagrams showing another example of the structure. Here, only the difference in structure from FIG. 12B is shown. In FIG. 13, the nMOS and the pMOS are separated from each other by the trench type insulating region STI in FIG. 12, but here, the trench type insulating region has a structure using only SSTI. For this purpose, in the nMOS, the entire back gate portion is covered with dn. In this way, in the region below the UTB, the nMOS dn and the pMOS n region can be separated by the p-sub that is the p region. The UTB and the part above the UTB can be separated by SSTI. Thus, the structure of the present invention can be realized without forming an STI. FIG. 14 shows an example in which the p region is formed when the p region used for the back gate region of the nMOS is formed between the dn of the nMOS and the n region of the pMOS. As a result, the nMOS and the pMOS can be arranged closer to each other.

  FIG. 15 is a diagram showing another example of the CMOS structure in the present invention. This has a structure in which the back gate portion and the p-sub are separated by a buried oxide film called TB. Therefore, in the nMOS, the back gate of the p region is formed under the UTB, and in the pMOS, the back gate of the n region is formed under the UTB. The p region back gate of the nMOS is the p + region, and the n region back gate of the pMOS is Extracted to the semiconductor surface in the n + region. It is not necessary to separate the nMOS p region back gate and the p-sub by providing an n region. According to this embodiment, the nMOS and the pMOS can be arranged closer to each other, and a semiconductor device with a small area can be realized.

  FIG. 16 is a diagram showing another configuration example of the present invention. The difference from the circuit configuration of FIGS. 1 and 4 is that there are a plurality (n) of circuit blocks in which BAC, DCL, and PFC are set, and these power supply terminals are combined and connected to the power supply by a switch indicated by AAC. This is the point. This AAC uses the MOS having the structure shown in FIG. 3 and the like, and connects the gate and the back gate. According to this configuration, a current required to operate a circuit block in which BAC, DCL, and PFC are set can be supplied by a MOS in which a gate and a back gate configuring AAC are connected, and standby Sometimes a very small leakage current can be obtained. This AAC control signal is DS. In FIG. 16, a part in which BAC, DCL, and PFC are set is called BLK, and there are n pieces. The n pieces are connected to one AAC, and this unit is called AREA. Signals for activating each BLK are AB1 to ABn.

  FIG. 17 is a diagram showing an operation example of the method of FIG. First, DS switches from high level to low level. As a result, the pMOS constituting the AAC is turned on as shown in FIG. As a result, the area named AREA and the power supply are connected and become active. This is called AREA ACTIVE. When this is completed, only the necessary part of AB1 to ABn is activated. FIG. 17 shows an example in which only AB1 is selected. AB1 changes from high level to low level, and the DCL MOS in BLK1 has a small threshold voltage, enabling high-speed operation. Thereafter, the signal of the input signal BI1 becomes valid, and the operation result is output to BO1. In order to deactivate this BLK, AB1 is returned to the high level again. As a result, the threshold voltage of the MOS in the DCL becomes high and enters a standby state (indicated as BLK Stand-by in the figure). In this state, the leakage current is small, but the voltage signal at each node is held. Therefore, when AB1 is switched again, it is possible to enter an operable state immediately. Thus, it is one of the features of the present invention to immediately enter the operating state and the activated state from the standby state and the inactivated state. In order to put the entire AREA in the standby state and inactive state, the DS may be switched again.

  FIG. 18 shows a gate electrode material and a gate oxide film material used in the MOS of the present invention. As an example, a structural example of nMOS is shown in FIG. As shown in (b). As an example of the material of the gate electrode SC, it is not necessary to limit to the salicide structure as shown in (a), and a metal gate material can be selected. This material is determined by the target threshold voltage value. The control is performed by the back gate around the threshold determined by the gate material. On the other hand, the gate oxide film mainly shows a material called a high-k film. In general, when a material as shown in this figure is used for the gate electrode, the threshold voltage is determined here, and it is said that the change in the threshold voltage is small by bringing in the High-k film. Goodness can be brought out.

  FIG. 19 is a diagram for explaining another embodiment of the present invention, and shows only a part of the BAC and DCL. What is characteristic in this embodiment is that the values of VCA and VSA can be changed according to operating temperature and manufacturing conditions. As a result, as shown in FIG. 20A, as the temperature increases, for example, VCA is higher and VSA is lower, so that the change in DCL characteristics due to temperature change can be reduced. Alternatively, the roughness is a threshold voltage determined by the gate electric material, but the value varies due to manufacturing variations. As shown in (b), a voltage for canceling this variation can be generated.

  FIG. 21A and FIG. 21B show an example circuit SVC that detects the temperature change and variation and generates a voltage for correcting the temperature change and variation. The MOS transistor inside the Vth detector is a MOS transistor having the structure of the present invention, and monitors the current flowing therethrough and generates a voltage determined by the resistance in the VDE. In this example, a band gap generator is used as a reference voltage, and this generated voltage is VBG. The resistance in the Vth detector and the size of the MOS are adjusted so that the VDE changes near the VBG. If the difference between VDE and VBG is detected by an amplifier, VCA can be generated so that a constant voltage can be obtained regardless of temperature and variation, and VSA is generated by VSA generator based on the change in VCA. can do.

  FIG. 22 shows an embodiment of the present invention for realizing a small area. Only changes from now on will be described in comparison with FIG. The feature of the embodiment of FIG. 22 is that an nMOS and a pMOS are created in dn, and the back gate is shared by the MOS and the pMOS. That is, the p region which is the back gate of the nMOS in FIG. 12 is also used as the back gate of the pMOS. As a result, the STI that separates the nMOS and the pMOS in FIG. 12 becomes unnecessary. This is effective when, for example, a memory cell or the like that requires a smaller area is formed.

FIG. 23 differs from FIG. 22 in that the n region which is the back gate of the pMOS in FIG. 12 is also used as the back gate of the nMOS. This is also effective when a memory cell or the like is created because a small area can be realized.

  FIG. 24 shows a configuration in which the p region which is the back gate of the nMOS and the p-sub region are not separated. This embodiment can be used first when it is desired to use, for example, a conventional bulk created layout data or circuit as it is. Second, since this structure can control the back gate of the pMOS, it can be used for an application in which the back gate is controlled only for the pMOS. This is effective in memory cells and pass gate logic.

25 to 28 show examples of memory cells.
FIG. 25 shows an example of an SRAM composed of four transistors Tr1, Tr2, Dr1, Dr2. The back gates of Tr1 and Tr2 are controlled by N1 and N2 which are internal nodes of the memory cell. B1 and B2 are bit lines for reading signals, and W1 is a word line. According to this configuration, the required threshold voltage of one of the transistors Tr1 and Tr2 can be set high and the other can be set low, and the power of this memory cell can be reduced.

  FIG. 26 shows an example of an SRAM composed of six transistors Tr1, Tr2, Ld1, Ld2, Dr1, and Dr2. The back gates of Ld1 and Dr1 are connected to the gates. Similarly, the back gates of Ld2 and Dr2 are connected to each other. Take the configuration connected to the gate. According to this configuration, the stability of the memory cell can be increased.

  FIG. 27 shows an embodiment in which the present invention is applied to a DRAM composed of three transistors. In FIG. 27, information is stored depending on whether or not the gate of M2 is charged. M1 is a transistor for writing information that stores and outputs charges at the gate of M2. The gate signal W1 of M1 is called a write word line, and B1 connected to the other of the source / drain terminals of M1 is called a write bit line. In M2, the current that can flow is different depending on the presence or absence of the gate charge, but this information is selectively read out by M3 connected in series with M2. The gate signal W2 of M3 is called a read word line, and B2 connected to the drain terminal of M3 is called a write bit line. In FIG. 27, the gate of M2 and the back gate are connected. As a result, in the state where the gate of M2 is charged, this voltage is high, so that the threshold voltage of M2 decreases and a large drain current of M2 can flow. On the other hand, in the state where there is no charge in the gate of M2, Since the voltage is low, the threshold voltage of M2 increases and only a small current can flow through M2. Therefore, the current difference due to the information difference can be increased compared to the state where this control is not performed.

  FIG. 28 shows another embodiment. Only the difference from the configuration of FIG. 27 will be described. In this embodiment, the gate and the back gate are connected also in M3 in addition to M2. As a result, a larger current can be taken at the time of reading. In general, M1 has only a small driving capability because M2 is a gate of M2 only, but M3 needs a large driving capability in order to read out a current. If the invention is not used, the size must be increased in order to pass a large current. This increases the memory cell area, which is not preferable.

  FIGS. 29 to 31A and 31B are examples showing combinations of the logic circuit method and the memory cell method described so far, and show what components are mounted on the chip of the semiconductor device. Here, only the portions necessary for the description are shown, but of course, other IO circuits, sensors, wireless, non-volatile memories, and the like are mounted as necessary.

  In FIG. 29, the back gate control is not performed for the logic circuit, but the back gate control is performed for the memory, and the memory cell using the four transistors as shown in FIG. 25 is used. The 4Tr SRAM is a memory part composed of memory cells using these four transistors, and the Logic w / o Back is a logic circuit part. Since the cross-sectional structure using this configuration can be simplified, the cost is reduced. That is, the structure of FIG. 23 is used for the memory portion, and the structure of FIG. 24 is used for the logic portion. These two structures are the same process.

  FIG. 30 shows an embodiment in which a back gate control method is included in the logic unit. The memory part (4TrSRAM) is equipped with a memory part (6TrSRAM) using a memory cell using six transistors as shown in FIG. In the logic circuit portion (Logic), a circuit for performing back gate control as shown in FIG. 1 is mounted. This 6TrSRAM can be used as a cache memory, and a 4TrSRAM with a small area can be used as a work memory (because the number of transistors is less than six), so that the performance of the entire semiconductor device can be improved. By using this embodiment, it is possible to mount a high-speed, low-power logic circuit as described in the previous embodiments and a memory essential for this operation with a low area and low power.

  FIG. 31A is an embodiment in which a plurality of circuits SVC that detect the temperature change and variation described in FIG. 21A and generate a voltage for correcting the temperature change are mounted on the same chip. Thus, by providing an SVC for each region or circuit configuration that can be regarded as uniform on the chip, finer control can be performed. In this example, the chip is divided into four areas, and VCA and VSA suitable for each are generated by the circuits shown in SVC1 to SVC4. For example, as shown in FIG. 31B, in SVC1, VCA1 and VSA1 are generated, and these voltages are supplied to BAC and DCL in this area as shown in the block arrangement example.

  An example of back gate control is shown in FIGS.

  FIG. 32 schematically shows the structure used in the present invention. A MOS having a source S, a drain D, a gate G1, and a gate oxide film OX is placed on the buried oxide film UTB to form an SOI structure, and a semiconductor portion of the substrate under the UTB is a back gate G2. Is. Here, the thickness of the gate oxide film OX is TOX, the thickness of the source S and drain D is TSOI, and the thickness of the buried oxide film UTB is TBOX, but TOX is different when a high-k film is used. Is 2 nm or less, TSOI is about 20 nm, and TBOX is about 10 to 20 nm.

  FIG. 33 shows another structure. In this structure, the back gate G2 is made of a conductive material similar to that of the gate G1. In this structure, it is necessary to prevent the positions of the back gate G2 and the gate G1 from being shifted vertically, but the back gate G2 can be formed with high accuracy.

  FIG. 34 shows an example of a structure having a thick TSOI called PD-SOI. This is called a partial depletion type. In this case, as shown in FIG. A potential is applied to G2 under the condition that the PN junction between the source S and the region under the gate is not turned on.

  DCL: logic circuit block, BAC: back gate control signal generation circuit block, PFC: output buffer circuit block, UTB: buried oxide film, OX: gate oxide film, STI: trench trench insulating region, SSTI: trench trench insulating region (Shallow than STI), TB... Buried oxide film (under UTB).

Claims (1)

A first circuit block and a second sub-circuit block including a first sub-circuit block and a second transistor including a first transistor,
A second circuit block and a fourth sub-circuit block including a third sub-circuit block and a fourth transistor including a third transistor,
And a first power source selection switch connected to said first and second circuit blocks,
Each of the previous SL first and the third transistor, a first semiconductor layer formed on a semiconductor substrate through a first buried oxide layer,
A first source region and a first drain region formed in the first semiconductor layer and having the same film thickness as the first semiconductor layer;
Said first first channel region is fully depleted region formed in the semiconductor region between the first source region and first drain region,
A first gate formed on a first main surface of the first channel region via a first gate insulating film;
A second gate formed of a conductive layer formed in contact with the bottom surface of the buried oxide film and electrically connected to the first gate;
And a first isolation layer formed on the semiconductor substrate so as to surround the first semiconductor layer,
Each of the previous SL second and said fourth transistor, and a second semiconductor layer formed on a semiconductor substrate via a second buried oxide layer,
A second source region and a second drain region formed in the second semiconductor layer and having the same film thickness as the second semiconductor layer;
A second channel region is fully depleted region formed in the second semiconductor region between the second source region and second drain region,
A third gate formed on the first main surface of the second channel region via a second gate insulating film;
A fourth gate made of a conductive layer formed in contact with the bottom surface of the second buried oxide film;
And a second isolation layer formed on the semiconductor substrate so as to surround the second semiconductor layer,
The output signal of the first sub-circuit block is input to the fourth gate of the second sub-circuit prior disposed block Symbol second transistor,
The output signal of the third sub-circuit block is input to the fourth gate of the fourth sub-circuit prior disposed block SL fourth transistor,
An input signal input to the third gate of each of the second and fourth transistors is the second signal of the second transistor disposed in the second sub-circuit block and the fourth sub-circuit block. It is independent from the input signal input to 4 gates,
The power supply voltage is applied to the first circuit block and the prior SL second circuit block via the first power supply selecting switch,
The semiconductor device, wherein the first power source selection switch is constituted by the first transistor.

Images