JP2003153543A - Power feeder, motor driver, and method of controlling power feeder - Google Patents

Abstract

PROBLEM TO BE SOLVED: To perform power supply stably by power factor improvement by reducing the loss covering the whole of the wide operation zone of load, thereby enabling the efficiency improvement, and to solve high frequency problem both in load and in power. SOLUTION: This power feeder is provided with a reactor whose one end is connected to an AC power source, and a bidirectionally conductive short circuit element which short-circuits/opens the AC power source via the reactor, and the short-circuit element is controlled, according to the quantity of load, in any mode of a no-power-factor-improvement mode where the short circuit action is not performed, a partial switching mode where the short circuit action is performed one time or a plurality of times in a half cycle of power by current open loop control, and a high frequency switching mode where the short circuit action is performed with high frequency by current feedback control.

Description

Detailed Description of the Invention

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention changes the control pattern of the short-circuiting means for short-circuiting or opening the AC power source according to the load, and improves the power factor in a wide operating range.
The present invention relates to a power supply device that converts an alternating current power source into a direct current with a high conversion efficiency and supplies it to a load, and an electric motor driven by this power device.

[0002]

2. Description of the Related Art As a power factor improving circuit for improving a power source power factor and reducing a harmonic component contained in an input current, there is a system disclosed in, for example, Japanese Patent Laid-Open No. 3-65056. The configuration of this method is a high power factor converter circuit that combines a short-circuit element that is short-circuited via a reactor for improving the power source power factor connected to an AC power source and a rectifier that rectifies AC to DC. By short-circuiting the AC power supply via the reactor, magnetic energy is stored in the reactor, and then by opening the short-circuit element, the stored energy in the reactor is transferred to the smoothing capacitor on the DC side. Therefore, the input current and the DC output voltage can be controlled by controlling the short circuit / open of the short-circuit element, and the power supply power factor is improved.

Further, a relay contact of a rectifier circuit switching switch for switching the rectification mode to the full-wave or double voltage rectification mode is provided, and the DC output voltage reference value Vdc is set according to the detected current value.
Set ^※, DC output voltage, i.e. the voltage between the terminals of the smoothing capacitor feedback controlled to be the reference value Vdc ^※, also, to be a sine wave shape current detected is synchronized to the AC power supply 1 high power factor The converter circuit is controlled by high frequency. Therefore, according to the detected current value, the relay contact is opened in the high load area to operate the high power factor converter circuit in the full-wave rectification mode.In the intermediate load area, the relay contact is short-circuited in the voltage doubler rectification mode. The high power factor converter circuit is stopped, and in the low load area, the DC output voltage is reduced by operating the high power factor converter circuit at a low step-up ratio so that the DC output voltage does not rise too much, or by stopping it completely. The power factor can be improved while controlling.

As another prior art, Japanese Patent Laid-Open No. 11-206
There is a system shown in Japanese Patent Publication No. 130. The configuration of this system is also similar to the above, and the magnetic energy of the reactor can be controlled, the input current and the DC output voltage can be controlled, and the power supply power factor is improved.

In this system, a controller for controlling a rectifier circuit switching switch and a short-circuit element controls the full-wave / double-voltage rectification mode according to the detected power consumption of the load or the input current or DC output voltage that can simulate the detected power consumption. The power factor improving function and the boosting function are realized by controlling the short-circuit start timing and the short-circuit time of the short-circuit element by an open loop.

The operation of the power factor correction circuit configured as described above is as follows. First, when the input current is small, the switch for rectifying circuit switching is turned off to select the full-wave rectifying mode, and at the same time, the short-circuit element is selected. The short-circuit operation is not performed, that is, the power factor is not corrected, and the DC output voltage of the power factor correction circuit is controlled to be small. Next, when the full-wave rectification mode is selected and the input current is a little large, the short-circuit start timing and short-circuit time of the short-circuit element are variably controlled to perform intermittent control to improve the power factor and reduce the DC output voltage Greatly control. Further, when the input current is large and the step-up ratio of the power factor correction circuit exceeds a predetermined value, the rectifier circuit switching switch is turned on to select the double voltage rectification mode, and
The short-circuit operation of the short-circuit element is not performed, that is, the power factor is not corrected, and the DC output voltage of the power factor correction circuit is largely controlled. Further, when the input current is larger and a larger DC output voltage is required in the state where the voltage doubler rectification mode is selected, the short-circuit start timing and the short-circuit time of the short-circuit element are variably controlled to improve the power factor. The DC output voltage is controlled more greatly.

As described above, JP-A-11-206130
In the technique of the publication, the rectifier circuit is controlled in the full-wave rectification mode or the voltage doubler rectification mode by turning on / off the rectifier circuit switching switch, and the DC output voltage of the power factor correction circuit is roughly divided into two stages. By dividing the divided area into two stages, one with no power factor improvement and the other with power factor improvement by short-circuit variable control in the open loop of the short-circuit element, a total of four stages of DC output voltage region is constructed. It is possible to improve the power factor on the high load side while expanding the output range of the DC output voltage.

Further, as still another conventional technique for improving the power source power factor and reducing the harmonic components contained in the input current,
For example, there is Japanese Patent No. 2140103. The configuration in this system corresponds to the configuration in which the relay contact is removed in the technique disclosed in Japanese Patent Laid-Open No. 3-65056. That is, there is provided a DC voltage control means for outputting a DC voltage control signal according to the deviation value between the DC output voltage reference value Vdc ^* set according to the load and the voltage across the terminals of the smoothing capacitor, and the DC voltage control means. Current reference calculation means for outputting a current reference signal from the product of the control signal from the control signal and the sine wave synchronizing signal synchronized with the AC power supply. By comparing this current reference signal with the AC side current of the rectifying element, the switch element is ON / OFF controlled at high frequency, and the DC output voltage is controlled to a desired value while controlling the AC input current in a sine wave shape. And
The power source power factor is set to approximately 1, and the generation of harmonics can be suppressed. Similarly, a power factor correction circuit is disclosed in Japanese Patent Laid-Open No. 2001
The technique disclosed in Japanese Patent Publication No. 145360 is also known.

[0009]

However, the above-mentioned conventional techniques, JP-A-3-65056, JP-A-11-206130, and JP2140103,
In Japanese Patent Laid-Open No. 2001-145360, etc., the control pattern of the short-circuit element is limited.
High frequency switching mode for feeding back current (Japanese Patent Laid-Open No. 3-65056, Japanese Patent No. 2140103)
No.) or a partial switching mode of current open loop control (Japanese Patent Laid-Open No. 11-206130), in order to avoid excessive boosting of the DC output voltage on the low load side, the short-circuit element is not operated and the power factor is not increased. Do not improve. Therefore, the waveform distortion of the input current is large on the low load side, the current containing many harmonic components flows through the reactor 2, and the reactor iron loss increases, which reduces the AC-DC conversion efficiency of the power factor correction circuit. Will end up.

Further, in the short-circuit control of the short-circuit element for improving the power factor in Japanese Unexamined Patent Publication No. 11-206130, the short-circuit start timing and the short-circuit time are controlled by an open loop, and the short-circuit is short-circuited for a certain period with respect to the power cycle. Since it is a partial switching system that operates, the power factor can be improved and the DC output voltage can be boosted, but its effect is small on the high load side where the amount of generated harmonics increases. Therefore, in order to obtain a sufficient power factor improvement effect, that is, the harmonic suppression ability, in the conventional technology with the tightening of harmonic regulations in the future, a reactor having a large inductance value is required, and therefore the AC / DC conversion efficiency is improved. This leads to problems such as deterioration, increase in circuit size, and cost. Also, when boosting the DC output voltage while suppressing the amount of harmonic generation to a certain level, the operation on the high load side becomes unstable or the stable operation on the high load side occurs because the boosting capacity is limited. If you think about it, the selection range of the load will be narrowed.

The present invention has been made to solve the above-mentioned problems, and it is possible to improve efficiency by reducing loss over the entire operating region of a wide load, and improve power factor to stabilize power supply. It is about going. The present invention provides a highly reliable and compact power supply device. Further, the present invention controls the electric power supplied to the electric motor to improve the efficiency of the entire apparatus, and solves the high frequency problem in both the load and the power supply.

[0012]

According to a first aspect of the present invention, there is provided a power supply device which rectifies an alternating current from an alternating current power source and converts the alternating current into a direct current, and a smoother which smoothes an output of the rectifier and supplies power to a load. Means, a reactor connected to the AC side or the DC side of the rectifier, and a short-circuit means for increasing or decreasing the voltage across the terminals of the smoothing means by short-circuiting or opening the AC power supply via the reactor and utilizing the electromagnetic energy storage effect of the reactor. And partial switching in which the short-circuiting operation of the short-circuiting means is performed once or a plurality of times in a half cycle of the power supply based on the supply information such as electric power or current supplied to the load connected between the terminals of the smoothing means or the information from the load. And a controller capable of switching between a high frequency switching mode and a high frequency switching mode performed at a high frequency.

A power supply device according to a second aspect of the present invention includes a rectifier circuit switching switch for switching the rectifier between a full-wave rectification mode and a voltage doubler rectification mode, and the controller is connected between terminals of the smoothing means. The rectifier circuit switching switch is controlled to the full-wave rectification mode or the voltage doubler rectification mode based on supply information such as electric power or current supplied to the load or information from the load.

According to a third aspect of the present invention, there is provided a power supply device for connecting a rectifier and a capacitor for double voltage rectification, and a switch for switching a rectifier circuit for switching the rectifier between a full wave rectification mode and a voltage doubler rectification mode. , The controller is configured to set the rectifier circuit switching switch to the full-wave rectification mode or the double-voltage rectification mode on the basis of supply information such as electric power or current supplied to the load connected between the terminals of the smoothing means or information from the load. To control.

A controller of a power supply apparatus according to a fourth aspect of the present invention controls a rectifier circuit changeover switch to a full-wave rectification mode when the load is light and to a voltage doubler rectification mode when the load is heavy.

According to a fifth aspect of the present invention, in the controller of the power supply device, two different thresholds are provided as the switching judgment standard of the rectifier circuit switching switch, and the larger one is used for turning on the rectifying circuit switching switch. , The smaller one is for turn-off, and the rectifier circuit changeover switch is controlled based on this.

According to a sixth aspect of the present invention, in the controller of the power supply device, the short-circuit means is a partial switching mode which is a current open loop control when the load is light and there is no need to boost the DC output voltage. When it is necessary to output the DC output voltage with a heavy and high step-up ratio, it is switched to the high frequency switching mode which is the current feedback control.

According to a seventh aspect of the present invention, in the controller, when the controller switches the rectifier circuit changeover switch from the full-wave rectification mode to the double voltage rectification mode, the DC output voltage from the rectifier changes to the double voltage rectification mode. The short-circuiting means is controlled so that the voltage value obtained after switching or the preset maximum DC output voltage value in the full-wave rectification mode can be obtained.

According to the eighth aspect of the present invention, in the controller, when the controller switches the rectifier circuit switching switch from the double voltage rectification mode to the full-wave rectification mode, the DC output voltage after switching to the full-wave rectification mode. The short-circuit means is controlled so that the voltage value becomes the voltage value in the voltage doubler rectification mode before the value is switched.

In the power supply device according to claim 9 of the present invention, the controller controls the rectifier circuit changeover switch and the short-circuit means so that the power supply power factor increases.

In the power supply device according to the tenth aspect of the present invention, the controller controls the rectifier circuit changeover switch and the short-circuit means so as to reduce the harmonic component contained in the input current.

According to the eleventh aspect of the present invention, the controller controls the rectifying circuit changeover switch and the short-circuit means so that the DC output voltage approaches the voltage value required by the load.

In the power supply device according to the twelfth aspect of the present invention, the short-circuiting means is a bidirectional conducting short-circuit element constituted by combining a diode bridge and a one-way conducting semiconductor switch.

According to a thirteenth aspect of the present invention, in the power supply device, the short-circuiting means is a bidirectional conducting short-circuit element composed by combining two or more unidirectionally conducting semiconductor switches so as to have mutually opposite polarities. .

In the power supply device according to claim 14 of the present invention, the short-circuit means is a plurality of switching elements provided between one end of the reactor and the DC side terminal of the rectifier.

In the power supply device according to the fifteenth aspect of the present invention, at least a part of the rectifying element forming the rectifier is formed of a high speed recovery diode.

According to the sixteenth aspect of the present invention, in the electric motor drive device, when the electric power supply device supplies electric power to the inverter and the electric motor, which are loads, the controller causes the rectifier circuit changeover switch to change the rotational speed command value of the electric motor. When it is small, it is controlled to full-wave rectification mode, when it is large, it is controlled to double-voltage rectification mode, or when the short-circuit means has a small motor rotation speed command value and little DC voltage boosting is required to drive the motor. In the partial switching mode, the control is performed in the high frequency switching mode when the rotation speed command value is large and it is necessary to output the DC voltage at a high step-up ratio for driving the electric motor.

According to a seventeenth aspect of the present invention, in the electric motor drive device, when the electric power supply device of the present invention supplies electric power to the direct current electric motor which is a load, the controller sets the rectifier circuit switching switch to the rotational speed command value of the direct current electric motor. If it is small, it is controlled to full-wave rectification mode, if it is large, it is controlled to double voltage rectification mode, or the short-circuiting means needs to boost the DC voltage to drive the DC motor because the rotation speed command value of the DC motor is small. If not, the control is performed in the partial switching mode, and in the high frequency switching mode when the rotation speed command value is large and it is necessary to output the DC voltage at a high step-up ratio for driving the DC motor.

A control method for a power supply device according to an eighteenth aspect of the present invention comprises a rectifier for rectifying an alternating current from an alternating current power source and converting it into a direct current, and smoothing means for smoothing an output of the rectifier and supplying electric power to a load. A reactor connected to the AC side or DC side of the rectifier, and a short-circuit means for short-circuiting or opening the AC power supply via the reactor and increasing or decreasing the terminal voltage of the smoothing means by utilizing the electromagnetic energy storage effect of the reactor, In the provided power supply device, a step of determining whether the load is large or small based on supply information such as electric power or current supplied to the load connected between the terminals of the smoothing means or information from the load; If it is judged to be small, the step of setting the partial switching mode in which the short-circuiting operation of the short-circuiting device is performed once or a plurality of times in a half cycle of the power supply
When it is determined that the load is large, a step of setting the high-frequency switching mode in which the short-circuiting operation of the short-circuiting unit is performed at high frequency is provided.

According to the nineteenth aspect of the present invention, in the method for controlling a power supply device, the short-circuiting operation of the short-circuiting means is such that the efficiency is improved depending on the load, and the harmonic component contained in the input current is predetermined. And a step of controlling the direction so that the value is within the value.

[0031]

BEST MODE FOR CARRYING OUT THE INVENTION Embodiment 1. 1 is a circuit configuration diagram showing an example of a first embodiment of the present invention, FIG. 2 is a configuration diagram of a switching circuit, FIG. 3 is an operation explanatory diagram of a switching circuit that performs short-circuiting a small number of times, and FIG. FIG. 5 is a circuit configuration diagram showing another circuit configuration of the switching circuit for performing the above. In the figure, 40 is a power factor correction circuit, 1 is an AC power supply which is a power supply for commercial use, 2
Is a reactor whose one end is connected to the AC power supply 1, 3 is a rectifier that rectifies the AC from the AC power supply 1 and converts it to DC, 6 is a smoothing capacitor that smoothes the DC output voltage of the rectifier 3, and 7 is a smoothing capacitor. A controller which is driven by being supplied with a DC voltage from 6, a bidirectional conducting short-circuit element 9 which is a switching circuit, and a control means 14 for controlling ON / OFF of the short-circuit element 9 and a load control means 15. , 11 is a power supply voltage detecting means, 12 is an input current detecting means, 16 is a diode bridge, 17 is a one-way conducting short-circuit element, 18 is a diode, and 19 is a backflow preventing rectifying element.

In the rectifier 3 which is a rectifier circuit, the two diodes 3a and 3c are excellent in the circuit configuration of the rectifier 3 so that the backflow from the smoothing capacitor 6 does not occur even when the short-circuit element 9 is operated at a high frequency. It is composed of a fast recovery diode that exhibits current cutoff characteristics. The fast recovery diode is not limited to 3a and 3c,
Instead of these, diodes 3b and 3d may be used, or 3a and 3b, or 3c and 3d, and similar effects can be obtained. Further, the number of fast recovery diodes is not limited to two, and three or all of the rectifiers 3 may be configured with fast recovery diodes, but in that case, the cost is increased.

The short-circuit element 9 as a switching circuit is
It has bidirectional conductivity, and is shown in FIG.
2, a diode bridge 16 and a unidirectional conducting short-circuit element 17 such as an IGBT or a bipolar transistor or a MOSFET, or, as shown in FIG. 2B, an IGBT or a bipolar transistor or a MOSF.
It is configured by combining a plurality of one-way conductive short-circuit elements 17 such as ET and diodes so as to have opposite polarities. With the configuration as shown in FIG. 2, the alternating current from the alternating current power source can be short-circuited. Note that the configuration of FIG. 2B can reduce the number of elements included in the current path when the one-way conductive short-circuit element 17 is on, that is, the conduction loss can be reduced, and thus the configuration of FIG. High efficiency can be realized.

The controller 10 can switch the operation pattern of the short-circuit element 9 between the high-frequency switching mode and the partial switching mode. The short-circuit element 9 can be set in the power factor no-correction mode, the partial switching mode, or the high-frequency switching mode. , Or to control either.

Here, the power factor no-correction mode, the partial switching mode, and the high frequency switching mode will be described. For convenience, the power supply voltage execution value of the AC power supply 1 is Vs, the instantaneous value is Vst, the inductance of the reactor 3 is L, the terminal voltage of the smoothing capacitor 6 is Vdc, and the reactor 3
The current flowing through is used as I below. The power supply voltage execution value Vs is a value preset by the power supply system, and is a value of Vs = 100V in the power supply 100V system and Vs = 200V in the power supply 200V system.

First, the power factor no-correction mode is a normal capacitor input type rectification mode in which the rectifier 3 does not operate the short-circuit element 9 at all. The short-circuit element 9 in FIG. 1 remains open, that is, since the input current flows only in the section where the AC voltage instantaneous value Vst is higher than the DC output voltage Vdc, the waveform distortion is large and many harmonics are generated. Including.

Next, in the partial switching mode, the short-circuit element 9 is set to 1 every half cycle of the power supply by the current open loop control.
The operation is to be turned on / off a plurality of times. This operation will be described with reference to FIG. In the figure,
(A) is a current path when the short-circuit element 9 is turned on / off,
(B) shows the power supply voltage, the input current, and the switch drive signal when the switching operation is performed once every half cycle of the power supply. First, when the short-circuit element 9 is turned on, the AC power supply 1 is short-circuited via the reactor 2 as shown in FIG. 3A, and the current I flows in the circuit composed of the AC power supply 1, the reactor 2 and the short-circuit element 9. , The magnetic energy of the reactor 2 is 1 / 2LI ²
Is accumulated. The stored energy is transferred to the smoothing capacitor 6 via the rectifier 3 at the same time when the short-circuit element 9 is turned off. By this series of operations, the input current as shown in FIG. 3B flows, the energization angle can be widened as compared with the power factor non-correction mode, and the power factor can be improved to some extent. Although the figure shows the case where the switching operation is performed only once in the half cycle of the power source, the number of times of switching may be any number. However, due to the current open loop control, when switching at a high frequency of several kHz or more, too much current flows in the circuit and the DC output voltage is boosted too much, which may lead to the destruction of the circuit. Therefore, in general, the switching operation in the partial switching mode is performed once every half cycle of the power supply or at a frequency of several k.
Multiple times up to Hz. In the partial switching mode, the energy accumulated in the reactor 2 can be controlled by controlling the short-circuit start time, the short-circuit time, and the number of short-circuits of the short-circuit element 9, and the DC output voltage Vdc is higher than that in the mode without power factor correction. It can be stepped up to a certain high value.

In the high frequency switching mode, the DC output voltage and the input current are feedback-controlled. As shown in FIG. 4, the switching frequency in the partial switching mode is set to several kHz or higher, and the DC output voltage is desired. Of the short circuit element 9 so that the input current approaches a sine wave synchronized with the power supply voltage.
It controls the off time. The current path when the short-circuit element 9 is turned on / off is the same as that shown in FIG.
This switching mode can improve the power factor to almost 1. Further, the boosting capability is higher than in the partial switching mode, and the DC output voltage Vdc can be steplessly controlled to any value higher than the voltage value in the power factor correction-free mode.

The operation of the controller 10 when controlling the input current and the DC output voltage in the circuit configuration of FIG. 1 will be described. In FIG. 1, reference numeral 11 is connected to both ends of the AC power supply 1, and is a power supply voltage zero cross point of a sine wave AC, or a power supply voltage peak point, or an arbitrary point of the power supply voltage, that is, an instantaneous value, or a sine wave AC of the power supply voltage. A power supply voltage detecting means for detecting a waveform, 12 is an input current detecting means for detecting an input current of the circuit by a shunt resistor or the like inserted in a current path of the AC power supply 1, and 13 is a DC output which is a terminal voltage of the smoothing capacitor 6. DC voltage detection means for detecting the voltage Vdc, and 15 is load control means for controlling the load.

Reference numeral 14 is a microcomputer having a storage means and a calculation means, and the like. The power supply voltage information from the power supply voltage detection means 11, the input current information from the input current detection means 12 and the DC voltage detection means 13 are supplied. The control means is a means for inputting the DC output voltage information and the command value Vdc ^{* of} a predetermined DC output voltage from the input port, and for issuing a signal for ON / OFF controlling the short-circuit element 9 in accordance with the input information. Here, the DC output voltage command value Vdc ^* is, for example, the amount of power consumption of the load that is directly detected, or a value suitable for the load state based on input current information or DC output voltage information that can simulate this, and controls the load. It is input by the load control means or external human power.

The control means 14 always outputs an OFF signal to the short-circuit element 9 when controlling the short-circuit element 9 in the power factor correction-free mode. As a result, the switching circuit 9 maintains the open state.

Further, when the short-circuit element 9 is controlled in the partial switching mode, the control means 14 uses the arbitrary timing of the power supply voltage information from the power supply voltage detection means 11, for example, a zero cross point as a reference point, as shown in FIG. As shown in b), the short-circuit element 9 is delayed from the reference point by the short-circuit start time.
The ON signal is output, and the control signal is output to the short-circuit element 9 so as to keep on for the short-circuit time. At this time, when the DC output voltage Vdc is smaller than the DC output voltage command value Vdc ^* , the microcomputer compares and calculates the voltage to delay the short circuit start time, or increase the short circuit time, or change the number of times of switching. When the DC output voltage Vdc is controlled to increase and the DC output voltage Vdc is larger than the command value Vdc ^* of the DC output voltage, the control is performed so as to be the opposite, so that the DC output voltage Vdc can be controlled to approach the command value Vdc ^* .

Further, the control means 14 drives the short-circuit element 9 at a high frequency.
When controlling in the wave switching mode, see Fig. 1.
The DC output voltage Vdc and the command value V of the DC output voltage
dc ^*Error amount ΔVdc from the power supply voltage detection means 11
A sine wave synchronized with the power supply voltage based on the power supply voltage information from
Input current command value is generated and input current detection means 12
Compare the input current information from the above with the input current command value, and
When the input current is smaller than the input current command value, the short-circuit element
The ON signal of the child 9 is output and the input current is greater than the input current command value.
When it is larger than the above, the OFF signal of the short-circuit element 9 is output.
It By repeating this series of operations at a high frequency,
, The input current approaches a sine wave, and the DC output voltage
Vdc is the command value Vdc^*Can be controlled.

Here, touching on the loss in the short-circuit means 9 of the power factor correction circuit, the loss in the short-circuit means 9 itself is higher in the high frequency switching mode than in the partial switching mode. The reason is that in the high frequency switching mode, the high speed switching operation is repeatedly performed, so that the switching loss in the short-circuit means 9 increases.

Therefore, in the control means 14, the DC output voltage command value V generated by the load control means based on the load state.
By controlling the short-circuiting means 9 as follows according to dc ^* , a highly efficient power factor correction circuit can be realized.
In the region where the command value Vdc ^* is large, that is, in the heavy load region where the input current is large and the harmonic current component is large, the iron loss in the reactor 2 and the rectifier 3 due to the harmonic component increases, and the power factor correction circuit 40 Since the loss ratio in the short-circuiting unit 9 becomes smaller than the total loss, under such conditions, the control unit 14 operates the short-circuiting unit 9 in the high frequency switching mode so as to suppress the loss due to the harmonic component. Harmonic components are reduced by making the input current waveform closer to a sine wave waveform. On the contrary, in the region where the command value Vdc ^* is small, that is, in the light load region where the input current is small and the harmonic current component is small, the loss ratio in the short-circuit means 9 is large relative to the total loss in the power factor correction circuit 40. Therefore, the control means 14 operates the short-circuit means 9 in the partial switching mode to reduce the switching loss so that the loss of the short-circuit means 9 itself becomes small.

As described above, in the example of the present embodiment, the control means 14 switches the operation pattern of the short-circuit means 9 according to the DC output voltage required by the load, so that the high efficiency of the power factor correction circuit is achieved in the entire load region. Can be realized. Also, in the heavy load region where the harmonic current component is large, the high frequency switching mode with high harmonic suppression capability is used, so the inductance value of the reactor 2 for clearing the harmonic regulation can be selected to a small value, and the circuit size can be reduced. Efficiency, cost reduction, and high efficiency. In addition, since a series of operations are performed with a reactor having a small inductance value, in the operating region where the boosting of the DC output voltage is not required so much, the reactor stored energy (1 / 2LI ² ) can be reduced, and therefore, the boosting amount of the DC output voltage can be suppressed to a small amount while improving the power factor, and the AC-DC conversion efficiency at low load can be improved.

In the above description, the short-circuit means 9 is provided on the AC side of the rectifier 3, but the short-circuit means 9 may be provided between the DC-side terminals of the rectifier 3 as shown in FIG. ,
As shown in FIG. 5B, not only the short-circuit means 9 but also the reactor 2 may be provided on the DC side. However, in these cases, it is necessary to provide the backflow prevention diode 19 between the short-circuit means 9 and the smoothing capacitor 6 so that the smoothing capacitor 6 is not short-circuited when the short-circuit means 9 is turned on. The operation of the circuit of FIG. 5 is the same as the operation described with reference to FIGS. 1 to 4, and the same effect can be obtained.

Further, although the load control means 15 for controlling the load is provided inside the controller 10 in the present embodiment, it may be provided outside the controller 10, and in this case as well, it depends on the power consumption of the load. DC output voltage command value Vd
The same effect can be obtained by configuring c ^* to be input from the load control means 15 to the controller 10.

FIG. 6 is a circuit diagram showing another circuit of the present invention. In FIG. 6, reference numeral 40 denotes a power factor correction circuit, 1
Is an AC power supply, 2 is a reactor whose one end is connected to the AC power supply 1, 3 is a rectifier that rectifies the AC power supply 1 and converts it into DC, 4 to 5 are capacitors for double voltage rectification, 6 is a rectifier 3
A smoothing capacitor for smoothing the DC output voltage of, a load 7 driven by the DC voltage supplied from the smoothing capacitor 6,
Reference numeral 8 is a rectifier circuit switching switch for switching the rectifier 3 to a full-wave rectification or voltage doubler rectification, 9 is a bidirectional short-circuit element, and 10 is a rectifier circuit switching switch 8 and a short-circuit element 9 is turned on / off. It is a controller that controls.

In the rectifier 3, the two diodes 3a and 3c of the rectifier 3 are arranged so that the backflow from the voltage doubler rectifying capacitors 4 to 5 or the smoothing capacitor 6 does not occur even if the short-circuit element 9 is operated at a high frequency. It is composed of a fast recovery diode that exhibits excellent current cutoff characteristics. Further, the fast recovery diode is not limited to 3a and 3c, and instead of these, the diodes 3b and 3d, or 3a and 3b, or 3c and 3d may be used as the fast recovery diode. The above diodes may be configured as fast recovery diodes.

Although not shown in the figure, the smoothing capacitor 6 can be functionally substituted by increasing the capacity of the voltage-doubler rectifying capacitors 4 to 5 connected in parallel, that is, The smoothing capacitor 6 can be omitted. In this case, the smoothing capacitor that outputs to the load is borne by the double voltage rectifying capacitor.

The rectifier circuit switching switch 8 is a bidirectional energizing element such as a relay or triac, or, as shown in FIG. 2A, a diode bridge 16 and a unidirectional energizing element such as an IGBT, a bipolar transistor or a MOSFET. The short-circuit element 17 or, as shown in FIG.
IGBT or bipolar transistor or MOSFET
A plurality of one-way conductive short-circuit elements 17 and diodes 18 and the like are combined so as to have opposite polarities. Note that the configuration of FIG. 2B can reduce the number of elements included in the current path when the one-way conductive short-circuit element 17 is on, that is, the conduction loss can be reduced, and thus the configuration of FIG. High efficiency can be realized.

The short-circuit element 9 as a switching circuit is
It has bidirectional conductivity, and is shown in FIG.
2, a diode bridge 16 and a unidirectional conducting short-circuit element 17 such as an IGBT or a bipolar transistor or MOSFET, or an IGBT or a bipolar transistor or MOSF as shown in FIG. 2B.
It is configured by combining a plurality of one-way conductive short-circuit elements 17 such as ET and diodes so as to have opposite polarities. Note that the configuration of FIG. 2B can reduce the number of elements included in the current path when the one-way conductive short-circuit element 17 is on, that is, the conduction loss can be reduced, and thus the configuration of FIG. High efficiency can be realized.

The controller 10 controls the full-wave rectification mode by turning off the rectifier circuit switching switch 8 or the double voltage rectification mode by turning it on. Further, the short-circuit element 9 is controlled to either the power factor correction-free mode, the partial switching mode, or the high frequency switching mode.

Here, the mode without power factor correction, the partial switching mode and the high frequency switching mode will be described. For convenience, the power supply voltage execution value of the AC power supply 1 is Vs, the instantaneous value is Vst, the inductance of the reactor 3 is L, the terminal voltage of the smoothing capacitor 6 is Vdc, and the reactor 3
The current flowing through is used as I below. The power supply voltage execution value Vs is a value preset by the power supply system, and is a value of Vs = 100V in the power supply 100V system and Vs = 200V in the power supply 200V system.

First, the non-power factor correction mode is a normal capacitor input type rectification mode in which the rectifier 3 does not operate the short-circuit element 9 at all. That is, the input current is
Since it flows only in the section where the AC voltage instantaneous value Vst is higher than the DC output voltage Vdc, the waveform distortion is large and many harmonics are included. At this time, the DC output voltage Vdc is √2 × V when the rectifier circuit changeover switch 8 is in the full-wave rectification mode.
s, 2√2 × Vs in the voltage doubler rectification mode.

Next, in the partial switching mode, the short-circuit element 9 is set to 1 every half cycle of the power supply by the current open loop control.
The operation is to be turned on / off a plurality of times. Although this operation has already been described, it will be described with reference to FIG. In the figure, (a) shows a current path when the short-circuit element 9 is turned on / off, and (b) shows a power supply voltage, an input current, and a switch drive signal when the switching operation is performed once in a half cycle of the power supply. First, when the short-circuit element 9 is turned on, FIG.
As shown in (a), the AC power supply 1 is short-circuited via the reactor 2, a current I flows in the circuit composed of the AC power supply 1, the reactor 2, and the short-circuit element 9, and magnetic energy 1 / 2LI ² is accumulated in the reactor 2. To be done. The stored energy is transferred to the voltage-doubler rectification capacitors 4 and 5 via the rectifier 3 at the same time when the short-circuit element 9 is turned off. By this series of operations, the input current as shown in FIG. 3B flows, the energization angle can be widened as compared with the power factor non-correction mode, and the power factor can be improved to some extent. Although the figure shows the case where the switching operation is performed only once in the half cycle of the power source, the number of times of switching may be any number. However, due to the current open loop control, when switching is performed at a high frequency of several kHz or more, overshooting cannot be suppressed and the DC output voltage is boosted too much, which may lead to circuit breakdown. Therefore, generally, the switching operation in the partial switching mode is performed once in a half cycle of the power supply or a plurality of times up to several kHz.
In the partial switching mode, by controlling the short circuit start time of the short circuit element 9, the short circuit time, and the number of short circuits,
The energy accumulated in the reactor 2 can be controlled, and the DC output voltage Vdc can be steplessly boosted to a certain value higher than that in the power factor correction-free mode.

In the high frequency switching mode, the DC output voltage and the input current are feedback-controlled. As shown in FIG. 4, the switching frequency in the partial switching mode is set to several kHz or higher, and the DC output voltage is desired. Of the short circuit element 9 so that the input current approaches a sine wave synchronized with the power supply voltage.
It controls the off time. The current path when the short-circuit element 9 is turned on / off is the same as that shown in FIG.
This switching mode can improve the power factor to almost 1. Further, the boosting capability is higher than in the partial switching mode, and the DC output voltage Vdc can be steplessly controlled to any value higher than the voltage value in the power factor correction-free mode.

The operation of the controller 10 in the case of controlling the input current and the DC output voltage with the configuration of FIG. 6 will be described. In FIG. 6, reference numeral 11 is connected to both ends of the AC power supply 1 and detects a power supply voltage zero-cross point of a sine wave AC, a power supply voltage peak point, an arbitrary point of the power supply voltage, or a sine wave AC waveform of the power supply voltage. Power supply voltage detecting means,
Reference numeral 12 is an input current detecting means which is inserted in a current path of the AC power supply 1 and detects an input current of the circuit, and 13 is a smoothing capacitor 6
DC voltage detecting means for detecting the DC output voltage Vdc, which is the terminal voltage of the, and load control means 15 for controlling the load.

Reference numeral 14 indicates the power supply voltage information from the power supply voltage detecting means 11, the input current information from the input current detecting means 12, the DC output voltage information from the DC voltage detecting means 13, and a predetermined DC output voltage. Command value Vdc ^* is input,
The control unit controls the rectifier circuit switching switch 8 according to the input information and controls the short-circuit element 9 to be turned on / off. Here, the DC output voltage command value Vdc ^* is, for example, the amount of power consumption of the load that is directly detected, or a value suitable for the load state based on input current information or DC output voltage information that can simulate this, and controls the load. It is input by the load control means or external human power.

When controlling the short-circuit element 9 in the power factor correction-free mode, the control means 14 always outputs an off signal to the short-circuit element 9. Further, when controlling the short-circuit element 9 in the partial switching mode, the control means 14 uses the arbitrary timing of the power supply voltage information from the power supply voltage detection means 11, for example, a zero cross point, as a reference point, as shown in FIG. As shown, the ON signal of the short-circuit element 9 is output after a delay of the short-circuit start time from the reference point, and the control signal is output to the short-circuit element 9 so that the short-circuit element 9 is kept on for the short-circuit time. At this time, when the DC output voltage Vdc is smaller than the DC output voltage command value Vdc ^* , the short circuit start time is delayed or
By controlling to increase the short-circuit time or increase the number of times of switching, and when the DC output voltage Vdc is larger than the command value Vdc ^* of the DC output voltage, the control is performed so as to be the opposite, thereby controlling the DC output voltage. Vdc is the command value V
It can be controlled to approach dc ^* .

FIG. 7 is a system configuration diagram for controlling the DC output voltage and the input current. When controlling the short-circuit element 9 in the high frequency switching mode, the control means 14 determines the error amount ΔVdc between the DC output voltage Vdc and the DC output voltage command value Vdc ^* , and the power supply voltage detection means, as shown in FIG. 7. A power supply voltage phase information from 11 is used to generate a sinusoidal input current command value synchronized with the power supply voltage, and the input current information from the input current detection means 12 is compared with the input current command value. When the input current is smaller than the input current command value, the ON signal of the short-circuit element 9 is output, and when the input current is larger than the input current command value, the short-circuit element 9 is output.
The off signal of is output. By repeating this series of operations at high frequency, the input current approaches a sine wave, and the DC output voltage Vdc can be controlled to the command value Vdc ^* .

Here, referring to the AC / DC conversion efficiency of the power factor correction circuit, the conversion efficiency decreases as the boost amount of the DC output voltage increases. The reason is that, as described in the control operation of the control means 14, as the boost amount of the DC output voltage is increased,
In order to control the stored energy of the reactor 2 to increase, that is, to delay the short-circuit start time to increase the short-circuit current, or to control the short-circuit time to be long or to increase the number of short-circuits, the short-circuit element 9 is set. This is because the amount of current flowing increases and the loss in the short-circuit element 9 increases.

Therefore, in the control means 14, if the rectifier circuit changeover switch 8 is controlled in accordance with the DC output voltage command value Vdc ^* desired by the load according to the operation flow shown in FIG. A power factor correction circuit that can be made small and that can perform boosting operation with low loss can be realized. FIG. 8 is a flowchart showing a relay control sequence in the control means 14. First, when this control is started, in step 21, the DC output voltage command value Vdc ^* suitable for the load state is input from the keyboard of the controller 10, the input switch, or the like by the load control means 15 or external human power. Next, in step 22, it is determined whether the input command value Vdc ^* is different from the previously input value. Here, when the command value Vdc ^* is different from the previous value, the process proceeds to step 23. If the command value Vdc ^* is equal to the previous value, the rectifying circuit changeover switch 8 is not switched, and the previous rectification mode is maintained, so the route for this determination is ended. If the command values are different, in step 23, the input DC output voltage command value Vdc is input.
^It is determined whether or not ^* is 2√2 times or more the power supply voltage execution value Vs which is predetermined by the power supply system. If the result of this determination is YES, the routine proceeds to step 24, where the rectifier circuit switching switch 8 is turned on and the double voltage rectification mode is selected. If the determination result in step 23 is NO, the process proceeds to step 25, the rectifier circuit switching switch 8 is turned off, and the full-wave rectification mode is selected.

In FIG. 8, the threshold value of the switching judgment reference of the rectifier circuit switching switch 8 in step 23 is set to a value that is 2√2 times the power supply voltage execution value Vs. Since there is a voltage drop in the diodes 3a to 3d or the reactor 2, a boosting effect due to switching of the short-circuit element 9, and the like, the threshold value may be the above value or the above value. Further, two different thresholds are provided, one having a larger value is for turning on the rectifier circuit switching switch 8 and the other having a smaller value is for turning off. By providing a difference, the DC output voltage command value Vdc ^* is It is possible to prevent chattering of the rectifier circuit changeover switch 8 when it fluctuates near the threshold value.

Next, the general operation of this system will be described with reference to FIG. Note that FIG. 9 is a diagram showing the power factor and the DC output voltage Vdc of the power factor correction circuit with respect to the power consumption of the load. First, when the power consumption of the load is 0, or when the load is extremely low such that the power consumption is almost equal to 0 (the power consumption is less than 10% of the allowable power consumption of the load), that is, the operation mode 1 in FIG.
In this case, the controller 10 controls the rectifier circuit switching switch 8 to the full-wave rectification mode and the short-circuit switch 9 to the power factor correction-free mode. As a result, the DC output voltage Vd
c is controlled to a low value of √2 × Vs.

Further, the power consumption of the load is slightly increased as compared with the operation mode 1, and the power consumption is 10 times the allowable power consumption of the load.
In the low load region of ˜30%, that is, in the operation mode 2 of FIG. 9, the controller 10 keeps the rectifier circuit switching switch 8 in the full-wave rectification mode and controls the short-circuit element 9 in the partial switching mode. . Therefore, the power factor can be controlled in the part indicated by the broken line in the figure, which is improved as compared with the mode without power factor correction, and the harmonic component contained in the input current can be reduced. Accordingly, iron loss in the reactor 2 can be suppressed. By making the amount of loss in the short-circuit element 9 associated with boosting smaller than the iron loss suppression amount, the conversion efficiency of the power factor correction circuit can be improved as compared to the power factor correction no mode. DC output voltage V
dc can also output the value in the broken line area.

During operation in the full-wave rectification mode, the power consumption of the load further increases, and the power consumption is 30 to 5 which is the allowable power amount of the load.
In the middle load region of 0%, that is, in the operation mode 3 of FIG. 9, the short-circuit element 9 is controlled in the high frequency switching mode. Therefore, the DC output voltage can be controlled without an upper limit as indicated by the shaded area in the figure, and is controlled to a desired arbitrary value suitable for the power consumption of the load. At this time, the power factor can be controlled to be approximately 1.

Next, the power consumption of the load further increases, and the DC output voltage command value Vdc ^* becomes the power supply voltage execution value Vs.
2√2 times or more of the high load region (the power consumption is 50 to 70% of the allowable power amount of the load), that is, in the operation mode 4 of FIG. 9, the rectifier circuit changeover switch 8 is doubled by the controller 10. It is switched to the voltage rectification mode. Further, the short-circuit element 9 is controlled in the partial switching mode, the power factor can be controlled in the part indicated by the broken line in the figure, and the DC output voltage is also 2√2 ×.
It is possible to output the value in the broken line region near Vs.

During operation in the voltage doubler rectification mode, the power consumption of the load further increases, and the power consumption is in an extremely high load region of 70% or more of the allowable power consumption of the load, that is, the operation mode 5 of FIG. In the case, the short-circuit element 9 is switched to the high frequency switching mode. Therefore, the DC output voltage can be boosted without an upper limit like the shaded area in the figure, and is controlled to an arbitrary value commensurate with the power consumption of the load, and the power factor is approximately 1 Therefore, the waveform distortion of the input current is improved. Therefore, in this operation mode, the ability to suppress harmonics is high, and since the DC output voltage is controlled by high-frequency switching from the voltage doubler rectification mode, the DC output voltage can be boosted while maintaining high AC-DC conversion efficiency.

A series of control sequences of the controller 10 will be described below with reference to the flowchart of FIG. First, as step 1, the power consumption of the load is obtained. Next, in step 2, the DC output voltage command value Vdc ^* suitable for the load state is input by the load control means or external human power. Further, in step 3, it is determined whether the input command value Vdc ^* is different from the previously input value. Here, when the command value Vdc ^* is different from the previous value, the process proceeds to step 4 and the command value Vdc ^*
Is equal to the previous value, the rectifier circuit selector switch 8
The previous operation mode is maintained without switching. In step 4, the input DC output voltage command value Vdc ^*
Is a power supply voltage execution value V that is predetermined by the power supply system
It is determined whether it is 2√2 times or more of s. If the determination result is false, the process proceeds to step 5 to turn off the rectifier circuit switching switch 8 and select the full-wave rectification mode. Further, the process proceeds to step 6, and it is determined what percentage of the allowable power amount of the load the power consumption amount obtained in step 1 is, and when the power consumption amount is 0 to 10% of the allowable power amount, it is in the extremely low load region. Proceeding from step 7 to step 8, the short-circuit element 9 is controlled in the mode without power factor correction. Note that this corresponds to the operation mode 1 in FIG. Further, in the low load region where the power consumption is 10 to 30% of the allowable power, the process proceeds from step 7 to step 9 to control the short-circuit element 9 in the partial switching mode. Note that this corresponds to the operation mode 2 in FIG. In addition, the amount of power consumption is 30 to the allowable amount of power.
When the intermediate load region is 50%, the process proceeds to step 10 to control the short-circuit element 9 in the high frequency switching mode. Note that this corresponds to the operation mode 3 in FIG.

When the result of the determination in step 4 is true, the process proceeds to step 11 to turn on the rectifier circuit switching switch 8 to select the double voltage rectification mode. Further, the process proceeds to step 12, and it is determined whether the power consumption amount obtained in step 1 is 70% or more of the allowable power amount of the load, and if the determination result is a high load region, the process proceeds to step 13. ,
The short-circuit element 9 is controlled in the partial switching mode. Note that this corresponds to the operation mode 4 in FIG. Further, in step 12, in the case of the extremely high load region where the determination result is true, the process proceeds to step 14 to control the short-circuit element 9 in the high frequency switching mode. Note that this corresponds to the operation mode 5 in FIG.

In the above description of the operation, the full-wave / double voltage rectification mode and the short-circuit element control mode are switched depending on the percentage of the allowable power consumption of the load. It is not limited to the numerical value, and may be set arbitrarily according to the operating conditions and the application. Further, in FIG. 10, the rectifying circuit switching is performed first, that is, the steps 5 to 11 following the steps 2 to 4 are placed after the step 1, and then the operation of switching the short-circuit elements of the steps 6 and below and the steps 12 and below is performed. Although the example has been described, the same operation and effect can be obtained even if the short-circuit element switching is performed first according to the conditions such as the load region and then the rectifying circuit switching is performed. Also, regardless of the presence or absence of a rectifier circuit changeover switch, that is, regardless of the configuration of the rectifier circuit, or regardless of the magnitude of the DC voltage, a short-circuit element depending on the power of the load or the rotation speed of the motor. It goes without saying that it is sufficient to drive only by switching.

As described above, according to the present invention, in the extremely high load region (operating mode 5 in FIG. 9) in which the amount of decrease in the DC output voltage and the amount of generated harmonics are the largest, the voltage doubler with high boosting capability and higher harmonic suppressing capability is obtained. Since the operation is performed in the rectification mode / high-frequency switching mode, unstable operation of the load due to insufficient DC output voltage can be avoided, and the range of load selection can be expanded. Further, the inductance value of the reactor 2 for clearing the harmonic regulation can be selected to be a small value, and the circuit can be downsized, the cost can be reduced, and the efficiency can be improved. In addition, since the series of operations of the operation modes 1 to 5 is performed with the reactor having a small inductance value, the short circuit element 9 controlled in the partial switching mode is used in the operation mode 2 or 4 in which the boosting of the DC output voltage is not required so much. The reactor stored energy (1 / 2LI ² ) at the time of short-circuit can be reduced, and therefore, the boost amount of the DC output voltage can be suppressed to a minute while improving the power factor, and the AC-DC conversion efficiency at low load is improved. be able to.

Further, the series of operation modes of the system is not limited to this, and for example, the operation mode configuration omitting the operation mode 1 or the operation mode configuration excluding the operation mode 3 or the operation mode It can be freely selected according to the load such as the operation mode configuration excluding the mode 4 or desired operation conditions, and the same effect can be obtained even under such use conditions.

Further, in the present invention, the load control means 15 for controlling the load is provided inside the controller 10. However, it may be provided outside the controller 10. In this case as well, a DC output according to the power consumption of the load is provided. The same effect can be obtained by configuring the voltage command value Vdc ^* to be input from the load control means 15 to the controller 10.

Further, in the present invention, the operation has been described according to the power consumption of the load, but any operation can be used as long as it can determine the load state. For example, the operation mode is switched according to the input current or the DC output voltage. Alternatively, the same effect can be obtained by switching the operation mode of the load.

For reference, the domestic regulatory class A (2004-) on harmonics currently under consideration is shown in FIG.
Shown in 1. In FIG. 11, n is the harmonic order, V _nom
Indicates the rated voltage of the device, and restrictions are set for harmonics up to the 40th order. In addition, [× (230 / V
_nom ]], V _nom is 220V, 230
This applies when the voltage is other than the V or 240V power supply system.
For a voltage of 220-240V, this table can be used as it is. Further, "odd harmonics" in the figure refers to harmonics whose frequency is an odd multiple of the power system, and similarly,
"Even harmonics" refers to harmonics whose frequencies are even multiples of the power system. From the figure, for example, 3 of 100V rated equipment
The regulation value of the second harmonic is 2.30 x (230/100) =
It is calculated as 5.29A. If it is attempted to satisfy this regulation value by the conventional technique, the reactor 2 becomes large in size, which causes deterioration of efficiency, increase in cost, and increase in size of the device.

The difference between the circuit configuration of FIG. 1 and the circuit configuration of FIG. 6 is that the rectifier 3 is connected in series with the DC side of the rectifier 3 so that the full-wave rectification mode and the voltage doubler rectification mode can be selected. 6 in that the double voltage rectifying capacitors 4 and 5 are provided, and the interconnection point of the double voltage rectifying capacitors 4 and 5 is connected to the AC side of the rectifier 3 via the rectifier circuit switching switch 8. In the circuit, the rectification mode can be switched according to the desired DC output voltage value of the load, which allows the DC output voltage to be output stably and efficiently over a wide range.

FIG. 12 is a circuit diagram showing another structure of the present invention. In FIG. 12, parts corresponding to those in FIG. 1 and the like are designated by the same reference numerals, and duplicate description thereof will be omitted. FIG. 12 shows the bidirectionally conductive short-circuit element 9 in FIG.
A pair of switching elements 20a and 20b using a semiconductor element such as a GBT, a bipolar transistor or a MOSFET is connected in parallel to one phase of the rectifier 3 to substitute it. In FIG. 12, 20a and 20b are a pair of switching elements substituting for the short-circuit element 9 in FIG. 1 and others, and these switching elements 20a, 20b.
Are respectively connected in parallel to the diodes 3a and 3c of the rectifier circuit 3, and the control signal from the controller 10 is applied to the gates thereof. Further, 19 is a backflow preventing rectifying element inserted between the rectifier 3 and the voltage doubling capacitors 4 to 5, and is a switching element 20a, 2
Double voltage rectification capacitors 4 to 5 due to short circuit operation of 0b
Alternatively, it is for preventing backflow from the smoothing capacitor 6 to the rectifier 3 side.

Next, the operation will be described. First, the AC power supply 1 is detected by the power supply voltage detection means 11 of the controller 10.
The voltage polarity of is detected. At this time, if the potential of one terminal a of the AC power supply 1 is higher than the potential of the other terminal b (this state is a positive polarity and the opposite state is a negative polarity), the control of the controller 10 is performed. The means 14 controls the switching element 20a to be turned off and the switching element 20b.
Allow only switching operation. Also, AC power supply 1
When the voltage polarity of is negative, the controller 10
The switching element 20b is controlled to be turned off, and the switching operation of only the switching element 20a is permitted. Here, the switching mode is assumed to be performed in the power factor no-correction mode, the partial switching mode, or the high frequency switching mode, as described above.

The difference in effect between the configurations of FIGS. 1 and 6 and the configuration of FIG. 12 is that the number of elements in the current path when the switching elements 20a and 20b are turned on can be reduced and the loss when the switching elements are turned on can be reduced. It is in. However, when the switching elements 20a and 20b are turned off, the number of elements in the current path increases more than in FIG. Therefore, under the operating condition in which the ON time of the switching element 20a or 20b becomes long, the circuit configuration has higher conversion efficiency than the configuration shown in FIG.

FIG. 13 is a circuit diagram showing another circuit configuration of the present invention. In FIG. 13, parts corresponding to those in FIG. 1 and the like are designated by the same reference numerals, and duplicate description thereof will be omitted. This circuit configuration is, for example, a switching element 20a ′ and 2 such as an IGBT or a bipolar transistor or a MOSFET.
0b 'is connected between the AC input terminal and the DC output terminal of the rectifier 3 on the low voltage side to replace the bidirectional conducting short-circuit element 9 in FIG. 1 and others. In FIG. 13, reference numerals 20a ′ and 20b ′ are a pair of switching elements substituting for the short-circuit element 9 of FIG. 1, and these switching elements 20a ′ and 20b ′ are connected to the diodes 3c and 3d of the rectifier circuit 3, respectively. They are connected in parallel, and a control signal from the controller 10 is applied to their gates. Further, 19 'is a switching element 20a', 20b 'between the rectifier 3 and the voltage doubler capacitor 4.
Is a backflow preventing rectifier element inserted between the double voltage capacitor 5 and the double voltage capacitor 5, and is for preventing short circuit of the double voltage capacitor 4-5 due to the short-circuit operation of the switching elements 20a ', 20b'. is there. However, when at least 3a of the rectifier 3 is composed of a high-speed recovery diode exhibiting excellent current cutoff characteristics, the backflow prevention rectifying element 19 ′ provided between the rectifier 3 and the voltage doubler capacitor 4 can be omitted. .

Next, the operation will be described. First, the controller 10 detects the voltage polarity of the AC power supply 1.
At this time, if the potential of one terminal a of the AC power supply 1 is higher than the potential of the other terminal b (this state is the positive polarity and the opposite state is the negative polarity), the controller 10
Controls the switching element 20a 'to be off and permits the switching operation of only the switching element 20b'. When the voltage polarity of the AC power supply 1 is negative,
The controller 10 controls the switching element 20b 'to be off, and permits the switching operation of only the switching element 20a'. Here, it is assumed that the switching is performed in the power factor no-correction mode, the partial switching mode, or the high frequency switching mode, as in the above description.

The difference of the effect of the configuration of FIG. 13 from the circuit configuration of FIG. 12 is that the rectifying element 3a is composed of a high speed recovery diode, and the backflow preventing rectifying element 19 provided between the voltage doubler capacitor 4 and the rectifier 3 is provided. By omitting the ', the number of backflow preventing rectifying elements 19 provided to prevent the voltage doubler rectifying capacitors 4 and 5 from being short-circuited when the switching elements 20a and 20b are turned on is reduced. There is something you can do.

Further, in the present invention, the example of the structure in which the reactor is provided on the AC side as shown in FIGS. 12 and 13 has been described, but the same applies when the reactor 2 is arranged on the DC side of the rectifier 3 as shown in FIG. The circuit operation and effect of are obtained. Furthermore, although not shown in the figure, the AC power supply is short-circuited via the reactor,
In the case of a circuit that improves power factor, whether the reactor and the short-circuit element are provided on the AC side or the DC side of the rectifier, the operation pattern of the short-circuit element is switched at high frequency according to the DC output voltage command value Vdc ^* desired by the load. By switching between the mode and the partial switching mode, the effects as described above can be obtained.

FIG. 15 is a circuit configuration diagram showing another configuration of the present invention. In the figure, parts corresponding to those in FIG. 1 and other parts are designated by the same reference numerals, and duplicate description thereof will be omitted. In the figure,
Reference numeral 21 is an inverter that is connected between both terminals of the smoothing capacitor 6 and that converts a DC voltage obtained between both terminals into an AC voltage; 22 is an electric motor driven by the inverter 21;
Reference numeral 23 is an inverter control means for controlling the inverter 21. The inverter control means 23 receives the rotation speed command value f ^* of the electric motor 22 and outputs a control signal to the inverter 21 so that the rotation speed of the electric motor 22 matches this.
Based on this control signal, the inverter 21 generates an AC voltage and drives the electric motor 22.

The difference between the configuration of FIG. 15 and the configuration described above is that the electric motor 22 is connected as the load 7 via the inverter 21 controlled by the inverter control means 23. As described above, the DC output voltage command value V
It is assumed that dc ^* is generated according to the power consumption of the load or the DC output voltage information and the input current information. However, in this configuration, the output of the electric motor 22 is proportional to the rotation speed, and therefore the power consumption of the load is reduced. The amount can be substituted by the rotation speed command value f ^* of the electric motor 22.

Even when the power consumption of the load of the power factor correction circuit is not substituted by the rotation speed command value f ^* of the electric motor 22, the load of the power factor correction circuit is set by using the set value in the inverter control means 23. It is possible to estimate the power consumption of. For example, a voltage command value applied to the electric motor 22 has the same effect. Further, the phase current value may be used as long as it is configured to detect the phase current of the electric motor 22, and the power consumption of the load can be easily obtained from the inverter control means 23.

As described above, when the load of the power factor correction circuit is the inverter, the power consumption of the load can be easily estimated from the set value such as the operation command value, and the DC output suitable for the power consumption of the load can be obtained. Since the DC output voltage is controlled based on the voltage command value Vdc ^* and the harmonic components contained in the input current are suppressed, the DC output voltage is not boosted unnecessarily, and the iron loss of the motor as well as the iron loss of the reactor can be reduced. A highly efficient drive device can be obtained. Further, since the circuit loss can be reduced, the output of the electric motor can be increased, so that the maximum rotation speed of the electric motor can be increased.

FIG. 16 is a circuit diagram showing another structure of the present invention. 16, parts corresponding to those in FIG. 1 and the like are designated by the same reference numerals, and duplicate description thereof will be omitted. In FIG. 16, 24 is connected between both terminals of the smoothing capacitor 6,
It is a DC motor driven by a DC voltage obtained between both terminals. The example of this configuration substantially corresponds to a form in which the inverter and the electric motor of FIG. 15 are replaced with a DC electric motor. Also in this case, the power consumption of the load is the DC motor 2
4 can be substituted by the rotational speed command value f ^※, as described above,
Since the DC output voltage is controlled to a value suitable for the power consumption of the load and the harmonic components contained in the input current are suppressed, the iron loss of the motor as well as the iron loss of the reactor can be reduced, and a highly efficient motor drive device can be obtained. . As described above, by downsizing the reactor of the power supply device that directly drives the DC motor, the combination of the power source and the motor can be freely selected, and the device with the highest efficiency can be selected.

In the above description of the circuit configuration, the input power is obtained from the power supply voltage detecting means 11 and the input current detecting means 12. Load information such as load power consumption, rotation speed when the load is a motor, load current, and switching duty of the inverter is obtained from the load control means 15. As described above, according to the present invention, the harmonic components contained in the input current are suppressed by the configurations of FIG. 1 and FIG. 6 and the like, and even on the high load side where the amount of generated harmonics is large, it is sufficient without increasing the reactor. It is possible to obtain a power factor correction circuit having high harmonic suppression capability and boosting capability and high AC / DC conversion efficiency.

The power factor correction circuit according to the circuit configuration of the present invention is
A reactor whose one end is connected to an AC power supply, a bidirectional short-circuit element that short-circuits / opens the AC power supply through this reactor, a rectifier that rectifies the voltage across the short-circuit element and converts it to DC, and a rectifier. Double voltage rectification capacitor that rectifies in the double voltage rectification mode, rectifier circuit switch that switches the rectifier between full-wave rectification mode and double voltage rectification mode, and a smoothing capacitor that smoothes the output of the rectifier and supplies power to the load. And the rectifier circuit switching switch is controlled to the full-wave rectification mode or the voltage doubler rectification mode according to the load state connected between both terminals of the smoothing capacitor, and the short-circuit element is not short-circuited. Mode or short-circuit operation is performed by current open loop control once or more times in a half cycle of the power supply. With a controller that controls in any of the high-frequency switching modes that perform high-frequency in the feedback loop, it is possible to improve the power supply power factor from light loads to heavy loads and stabilize a wide range of DC output voltage. In addition, a power factor correction circuit that can be efficiently supplied can be realized, and further, since the booster capability and the harmonic suppression capability are provided, the reactor can be downsized, and the circuit size and cost can be reduced.

The power factor correction circuit according to the circuit configuration of the present invention is
A reactor whose one end is connected to an AC power supply, a bidirectional short-circuit element that short-circuits / opens the AC power supply via the reactor, a rectifier that rectifies the voltage across the short-circuit element and converts it to DC, and a rectifier A voltage doubler rectifier that rectifies the voltage in the voltage rectifier mode and smoothes the output of the rectifier to supply power to the load; a rectifier circuit switch that switches the rectifier between a full-wave rectifier mode and a voltage doubler rectifier mode; Depending on the load state connected between the upper and lower terminals of the voltage rectifying capacitor, the rectifier circuit switching switch is controlled to the full-wave rectification mode or the double voltage rectification mode, and the short-circuit element is not short-circuited. No switching mode or short-circuit operation is performed by current open-loop control once or multiple times in a half cycle of the power supply. A controller for controlling at any mode of high-frequency switching mode of performing at a high frequency in readback control, since with a, there is no need to separately provide a smoothing capacitor, low cost can be realized in the circuit.
Further, it is possible to improve the power factor of the power source from light load to heavy load, and to realize a highly efficient power factor correction circuit having high boosting capability and harmonic suppression capability.

Since four of the four rectifying elements which constitute the rectifier of the power factor correction circuit according to the present invention are constituted by the high speed recovery diodes, the high frequency operation of the short-circuit element can be realized.

In the controller of the present invention, two different thresholds are provided as the switching judgment criteria of the rectifying circuit switching switch, the larger value is used for turning on the rectifying circuit switching switch, and the smaller value is used for turning off. Since the rectifying circuit switching switch is controlled based on the above, it is possible to prevent chattering of the rectifying circuit switching switch when the load changes in the vicinity of the threshold value, and it is possible to improve system reliability and device life.

When the load of the short-circuit element is light and there is almost no need to boost the DC output voltage, it is necessary to output the DC output voltage at the partial switching mode which is the current open loop control and the load is heavy and the boost ratio is high. In some cases, the high-frequency switching mode, which is the current feedback control, is used for control, so the power supply power factor is improved even at light loads, and a highly efficient power factor correction circuit with high boosting capability and harmonic suppression capability even at heavy loads. Can be realized.

When the rectifier circuit switching switch is switched from the full-wave rectification mode to the voltage doubler rectification mode, the voltage value obtained after the DC output voltage of the power factor correction circuit is switched to the voltage doubler rectification mode or a preset full-wave voltage. Since the short-circuit element is controlled so as to have the maximum DC output voltage in the rectification mode, it is possible to suppress voltage fluctuation when switching from full-wave rectification to double-voltage rectification.

When the rectifier circuit switching switch is switched from the double voltage rectification mode to the full-wave rectification mode, the DC output voltage value of the power factor correction circuit after switching to the full-wave rectification mode is in the double-voltage rectification mode before switching. Since the short-circuit element is controlled so that the voltage value becomes, the voltage fluctuation when switching from the double voltage rectification to the full-wave rectification can be suppressed.

Further, since the rectifier circuit changeover switch and the short-circuit element are controlled so that the power source power factor rises, the maximum output power can be improved and the AC-DC conversion efficiency in that state can be maximized. .

Further, since the rectifier circuit switching switch and the short-circuit element are controlled so as to reduce the harmonic component contained in the input current, the power source harmonic can be suppressed and the AC-DC conversion efficiency in that state can be maximized. Can be controlled.

Further, since the rectifier circuit changeover switch and the short-circuit element are controlled so that the DC output voltage approaches the voltage value required by the load, the DC output voltage can be controlled to a desired value and the circuit efficiency is lowered due to unnecessary boosting. Can be suppressed.

The load of the power factor correction circuit according to the configuration of the present invention is the inverter and the electric motor, and the controller controls the rectifier circuit changeover switch to be the full-wave rectification mode when the rotation speed command value of the electric motor is small and the load when the rotation speed command value of the motor is large. Is controlled in the double voltage rectification mode, and the short-circuit element is a current open loop control partial switching mode when the rotation speed command value of the motor is small and almost no boosting of the DC voltage is required to drive the motor. When the rotation speed command value is large and it is necessary to output the DC voltage at a high step-up ratio for driving the motor, the high-frequency switching mode that is the current feedback control is used to control the power factor correction circuit and load. It is possible to control the circuit efficiency of the inverter to the maximum, expand the selection range of the motor specifications, and increase the maximum rotation speed of the motor. It is possible.

The load of the power factor correction circuit according to the configuration of the present invention is a DC motor, and the controller uses a rectifier circuit changeover switch to set the full-wave rectification mode when the rotation speed command value of the DC motor is small and when it is large. Is controlled in the voltage doubler rectification mode, and the short-circuit element is the current open loop control when the DC motor rotation speed command value is small and almost no boosting of the DC voltage is required to drive the DC motor. Switching mode, when the rotation speed command value is large and it is necessary to output the DC voltage at a high step-up ratio for driving the DC motor, the high-frequency switching mode, which is the current feedback control, is used for control. It is possible to reduce the loss of the DC motor, which is the load, and to expand the selection range of DC motor specifications and increase the maximum rotation speed of the motor. That.

Further, since the short-circuit element is a bidirectional current-conducting short-circuit element formed by combining a diode bridge and a one-way current-conducting semiconductor switch, the short-circuit operation of the AC power supply can be realized inexpensively and effectively. Further, since the short-circuit element is a bidirectional current-conducting short-circuit element configured by combining two or more one-way current-conducting semiconductor switches so as to have mutually opposite polarities, it is possible to realize high efficiency of the short-circuit operation of the AC power supply. Further, since the short-circuit element is a plurality of switching elements provided between one end of the reactor and the DC side terminal of the rectifier, the element stress can be reduced and the life of the element can be extended.

[0106]

The power supply device according to claim 1 of the present invention includes a rectifier for rectifying an alternating current from an alternating current power source and converting it into a direct current, a smoothing means for smoothing an output of the rectifier and supplying power to a load, and a rectifier. Of the AC power supply or the DC power supply, and a short-circuit means for short-circuiting or opening the AC power supply via the reactor to increase / decrease the inter-terminal voltage of the smoothing means by utilizing the electromagnetic energy storage effect of the reactor, and a smoothing means. The short-circuiting operation of the short-circuiting means is performed once or several times in a half cycle of the power supply based on the information supplied from the load or the information such as the power or current supplied to the load connected between the terminals Since it has a controller that can switch to the high-frequency switching mode, it maintains a good power supply power factor over a wide load operating range from light loads to heavy loads. In state, it can suppress a harmonic component contained in the input current can be efficiently supplied device is obtained the power.

A power supply device according to a second aspect of the present invention comprises a rectifier circuit switching switch for switching the rectifier between a full-wave rectification mode and a voltage doubler rectification mode, and the controller is connected between terminals of the smoothing means. The rectifier circuit changeover switch is controlled in the full-wave rectification mode or the voltage doubler rectification mode based on the information supplied from the load or the power or current supplied to the load. And a device having a high boosting capability can be obtained.

A power supply device according to a third aspect of the present invention includes a rectifier circuit switching switch that connects a rectifier and a double voltage rectifying capacitor and switches the rectifier between a full-wave rectifying mode and a double voltage rectifying mode. , The controller is configured to set the rectifier circuit switching switch to the full-wave rectification mode or the double-voltage rectification mode on the basis of supply information such as electric power or current supplied to the load connected between the terminals of the smoothing means or information from the load. Therefore, a device having high boosting capability and high frequency suppressing capability with a simplified circuit can be obtained.

The controller of the power supply apparatus according to the fourth aspect of the present invention controls the rectifier circuit changeover switch to the full-wave rectification mode when the load is light and to the voltage doubler rectification mode when the load is heavy. A compact and efficient device can be obtained.

According to a fifth aspect of the present invention, in the controller of the power supply device, two different thresholds are provided as the switching judgment reference of the rectifying circuit switching switch, and the larger value is used for turning on the rectifying circuit switching switch. , The smaller one is used for turn-off, and the rectifier circuit switching switch is controlled based on this, so that a stable operation at the time of circuit switching and a highly reliable device in the long term can be obtained.

According to a sixth aspect of the present invention, in the controller of the power supply device, the short-circuit means is provided with the partial switching mode which is the current open loop control when the load is light and the DC output voltage need not be almost boosted. When it is necessary to output the DC output voltage with a heavy and high step-up ratio, it switches to the high-frequency switching mode, which is the current feedback control, so that the harmonics can be suppressed while maintaining the voltage required by the load. The device is obtained.

In the controller of the power supply apparatus according to the seventh aspect of the present invention, when the rectifier circuit switching switch is switched from the full-wave rectification mode to the voltage doubler rectification mode, the DC output voltage from the rectifier is switched to the voltage doubler rectification mode. Since the short-circuit means is controlled so that the voltage value obtained after the rectification mode is the maximum value or the DC output voltage value in the maximum full-wave rectification mode set in advance, the voltage fluctuation when switching the rectification mode can be suppressed and stable operation reliability can be obtained. Higher equipment can be obtained.

According to the eighth aspect of the present invention, in the controller of the power supply device, when the rectifier circuit switching switch is switched from the double voltage rectification mode to the full-wave rectification mode, the DC output voltage value after switching to the full-wave rectification mode. Since the short-circuit means is controlled so that the voltage value in the voltage doubler rectification mode before switching is set, the voltage fluctuation at the time of switching the rectification mode can be suppressed, and a stable operation with a good power factor can be obtained.

Since the controller of the power supply device according to the ninth aspect of the present invention controls the rectifier circuit changeover switch and the short-circuit means so that the power supply power factor rises, a device which can improve the maximum output and is efficient is provided. can get.

Since the controller of the power supply apparatus according to the tenth aspect of the present invention controls the rectifying circuit changeover switch and the short-circuit means so as to reduce the harmonic components contained in the input current, the harmonic suppression capability is high. A device with high AC-DC conversion efficiency can be obtained.

Since the controller of the power supply apparatus according to the eleventh aspect of the present invention controls the rectifying circuit changeover switch and the short-circuit means so that the DC output voltage approaches the voltage value required by the load, unnecessary operation is prevented. Therefore, a device with no waste in efficiency can be obtained.

Since the short-circuiting means of the power supply device according to claim 12 of the present invention is a bidirectional conducting short-circuit element constituted by combining a diode bridge and a one-way conducting semiconductor switch, it is inexpensive and compact. Efficiency can be obtained with the device.

Since the short-circuiting means of the power supply device according to the thirteenth aspect of the present invention is a bidirectional conducting short-circuit element constituted by combining two or more unidirectionally conducting semiconductor switches so as to have mutually opposite polarities. The short-circuit operation of the AC power supply can be efficiently performed.

Since the short-circuiting means of the power supply device according to claim 14 of the present invention is a plurality of switching elements provided between one end of the reactor and the DC side terminal of the rectifier, a long life of the parts is realized. it can.

In the power supply apparatus according to the fifteenth aspect of the present invention, at least a part of the rectifying element constituting the rectifier is constituted by the high speed recovery diode, so that a component for preventing backflow from the smoothing means should be added. It is possible to realize a high-frequency operation of the short-circuit element and obtain a small device.

According to the sixteenth aspect of the present invention, in the electric motor drive device, when the electric power supply device supplies electric power to the inverter and the electric motor, which are loads, the controller causes the rectifier circuit changeover switch to change the rotation speed command value of the electric motor. When it is small, it is controlled to full-wave rectification mode, when it is large, it is controlled to double-voltage rectification mode, or when the short-circuit means has a small motor rotation speed command value and little DC voltage boosting is required to drive the motor. In the partial switching mode, when the rotation speed command value is large and it is necessary to output the DC voltage with a high step-up ratio for driving the motor, the control is performed in the high frequency switching mode. Can be improved.

In the electric motor drive device according to claim 17 of the present invention, when the electric power supply device supplies electric power to the direct current electric motor which is a load, the controller causes the rectifier circuit changeover switch to change the rotation speed command value of the direct electric motor. If it is small, it is controlled to full-wave rectification mode, if it is large, it is controlled to double voltage rectification mode, or if the short-circuit means has a small rotation speed command value for the DC motor and it is almost necessary to boost the DC voltage to drive the DC motor. If not, it is controlled in the high frequency switching mode when the DC voltage is required to be output at a high step-up ratio to drive the DC motor with a partial switching mode and a large rotation speed command value. It can be reduced and the selection of DC motor specifications can be expanded.

The control method of the power supply device according to the eighteenth aspect of the present invention comprises a rectifier for rectifying the alternating current from the alternating current power source and converting it into a direct current, and a smoothing means for smoothing the output of the rectifier and supplying the power to the load. A reactor connected to the AC side or DC side of the rectifier, and a short-circuit means for short-circuiting or opening the AC power supply via the reactor and increasing or decreasing the terminal voltage of the smoothing means using the electromagnetic energy storage effect of the reactor, In the provided power supply device, a step of determining whether the load is large or small based on supply information such as electric power or current supplied to the load connected between the terminals of the smoothing means or information from the load; If it is judged to be small, the step of setting the partial switching mode in which the short-circuiting operation of the short-circuiting device is performed once or a plurality of times in a half cycle of the power supply,
When it is determined that the load is large, the step of setting the high-frequency switching mode in which the short-circuiting operation of the short-circuiting unit is performed at a high frequency is provided. Therefore, efficient control is possible over a wide range of the load.

According to the nineteenth aspect of the control method of the power supply apparatus of the present invention, the short-circuiting operation of the short-circuiting means tends to improve the efficiency depending on the load, and the harmonic component contained in the input current is predetermined. Since it has a step of controlling so that it falls within the value, the AC-DC conversion efficiency corresponding to the load can be increased.

[Brief description of drawings]

FIG. 1 is a circuit configuration diagram showing a first embodiment of the present invention.

FIG. 2 is a circuit diagram showing an example of a bidirectional conducting short-circuit element of the present invention.

FIG. 3 is a diagram showing partial switching mode operation of the short-circuit element of the present invention.

FIG. 4 is a diagram showing a high frequency switching mode operation of the short-circuit element of the present invention.

FIG. 5 is a circuit configuration diagram showing another circuit according to the first embodiment of the present invention.

FIG. 6 is a circuit configuration diagram showing another circuit according to the first embodiment of the present invention.

FIG. 7 is a system configuration diagram for controlling a DC output voltage and an input current according to the present invention.

FIG. 8 is a flowchart showing a switching control sequence of the rectifier circuit switching switch of the present invention.

FIG. 9 is an explanatory diagram showing a series of operation modes for the power consumption of the load of the system of the present invention.

FIG. 10 is a flowchart showing a switching control sequence of the rectifier circuit switching switch and the short-circuit element according to the present invention.

FIG. 11 is a diagram showing domestic regulation values regarding harmonics scheduled to be applied from 2004.

FIG. 12 is a circuit configuration diagram showing another circuit configuration according to the first embodiment of the present invention.

FIG. 13 is a circuit configuration diagram showing another circuit configuration according to the first embodiment of the present invention.

FIG. 14 is a circuit configuration diagram showing another circuit configuration according to the first embodiment of the present invention.

FIG. 15 is a circuit configuration diagram showing another circuit configuration according to the first embodiment of the present invention.

FIG. 16 is a circuit configuration diagram showing another circuit configuration according to the first embodiment of the present invention.

[Explanation of symbols]

1 AC power supply, 2 reactor, 3 rectifier, 4
〜5 times voltage rectification capacitor, 6 smoothing capacitor, 7 load, 8 rectifier circuit changeover switch, 9
Short-circuit element, 10 controller, 11 power supply voltage detection means, 12 input current detection means, 13 DC voltage detection means, 14 control means, 15 load control means,
16 diode bridge, 17 unidirectional conducting short circuit element, 18 diode, 19 backflow preventing rectifying element, 20 switching element, 21 inverter,
22 electric motor, 23 inverter control means, 24
DC motor, 40 power factor correction circuit.

Continued front page    (72) Inventor Mamoru Kawakubo             2-3 2-3 Marunouchi, Chiyoda-ku, Tokyo             Inside Ryo Electric Co., Ltd. F-term (reference) 5H006 AA01 AA02 BB05 CA01 CA07                       CB01 CB04 CB08 CC01 CC08                       DC02 DC05

Claims (19)

[Claims] 1. A rectifier for rectifying AC from an AC power source and converting it to DC, smoothing means for smoothing the output of the rectifier and supplying electric power to a load, and a reactor connected to the AC side or DC side of the rectifier. Connected between the terminals of the smoothing means and a short-circuiting means for increasing or decreasing the inter-terminal voltage of the smoothing means by utilizing the electromagnetic energy storage effect of the reactor by short-circuiting or opening the AC power supply via the reactor. And a high-frequency switching mode in which the short-circuiting operation of the short-circuiting device is performed once or a plurality of times in a half cycle of the power supply based on supply information such as electric power or current supplied to the load or information from the load. And a controller that can be switched to a power supply device. 2. A switch for switching a rectifier circuit for switching the rectifier between a full-wave rectification mode and a voltage doubler rectification mode, wherein the controller supplies power to a load connected between terminals of the smoothing means. 2. The power supply device according to claim 1, wherein the rectifier circuit switching switch is controlled to a full-wave rectification mode or a voltage doubler rectification mode based on supply information such as current or information from a load. 3. A rectifier circuit switching switch that connects the rectifier and a capacitor for double voltage rectification and switches the rectifier between a full-wave rectification mode and a voltage doubler rectification mode, wherein the controller includes the smoothing device. Characterized in that the rectifying circuit changeover switch is controlled to a full-wave rectification mode or a double voltage rectification mode based on supply information such as electric power or current supplied to a load connected between terminals of the means or information from the load. The power supply device according to claim 1. 4. The controller controls the rectifying circuit changeover switch in a full-wave rectification mode when the load is light and in a voltage doubler rectification mode when the load is heavy. The power supply device according to. 5. The controller provides two different thresholds as a switching judgment reference of the rectifier circuit changeover switch, a larger value is used for turning on the rectifier circuit changeover switch, and a smaller value is used for turnoff. The power supply device according to claim 2, wherein the rectifier circuit changeover switch is controlled based on this. 6. The controller includes the short-circuit means,
When the load is light and there is almost no need to boost the DC output voltage, partial switching mode is the current open loop control.When the load is heavy and the DC output voltage needs to be output at a high boost ratio, current feedback control is used. The power supply device according to claim 1, wherein the power supply device is switched to a certain high frequency switching mode. 7. The controller, when switching the rectifier circuit switching switch from a full-wave rectification mode to a voltage doubler rectification mode, a voltage value obtained after the DC output voltage from the rectifier is switched to the voltage doubler rectification mode. The power supply device according to any one of claims 2 to 6, wherein the short-circuit means is controlled so as to have a preset maximum DC output voltage value in the full-wave rectification mode. 8. The controller, when switching the rectifier circuit switching switch from a voltage doubler rectification mode to a full-wave rectification mode, a voltage doubler rectification mode after switching to the full-wave rectification mode and before switching the DC output voltage value. The power supply device according to any one of claims 2 to 7, wherein the short-circuiting means is controlled so that the voltage value of the power supply is equal to that of the power supply device. 9. The power supply device according to claim 2, wherein the controller controls the rectifier circuit changeover switch and the short-circuit means so that a power supply power factor increases. 10. The controller according to claim 2, wherein the controller controls the rectifying circuit changeover switch and the short-circuit means so as to reduce a harmonic component included in the input current. Power supply equipment. 11. The controller according to claim 2, wherein the controller controls the rectifying circuit changeover switch and the short-circuit element so that the DC output voltage approaches a voltage value required by a load. Power supply equipment. 12. The bidirectional conducting short-circuit element configured by combining a diode bridge and a unidirectional conducting semiconductor switch, as claimed in any one of claims 1 to 11. Power supply equipment. 13. The short-circuiting means is a bidirectional conducting short-circuit element configured by combining two or more unidirectionally conducting semiconductor switches so as to have mutually opposite polarities. The power supply device according to any one of 1. 14. The short-circuiting means is a plurality of switching elements provided between one end of the reactor and a DC side terminal of the rectifier, according to any one of claims 1 to 13. Power supply equipment. 15. The power supply device according to claim 1, wherein at least a part of the rectifying element forming the rectifier is formed of a fast recovery diode. 16. When the power supply apparatus according to any one of claims 1 to 15 supplies power to an inverter and an electric motor, which are loads, the controller causes the rectifier circuit switching switch to rotate at the rotational speed of the electric motor. When the command value is small, it is controlled to the full-wave rectification mode, and when it is large, it is controlled to the voltage doubler rectification mode. It is characterized by controlling in partial switching mode when it is rarely needed, and in high-frequency switching mode when it is necessary to output a DC voltage at a high step-up ratio to drive a motor because the rotation speed command value is large. Electric motor drive. 17. When the power supply apparatus according to any one of claims 1 to 15 supplies power to a DC motor that is a load, the controller causes the rectifier circuit changeover switch to rotate at a rotational speed of the DC motor. When the command value is small, it is controlled to the full-wave rectification mode, and when it is large, it is controlled to the voltage doubler rectification mode, or the short-circuit means controls the DC voltage to drive the DC motor because the DC motor rotation speed command value is small. When the boosting is rarely required, control is performed in the partial switching mode, and when the rotation speed command value is large and it is necessary to output the DC voltage at a high boosting ratio for driving the DC motor, control in the high frequency switching mode. A characteristic motor drive device. 18. A rectifier for rectifying AC from an AC power supply and converting it to DC, smoothing means for smoothing the output of the rectifier and supplying power to a load, and a reactor connected to the AC or DC side of the rectifier. And a short-circuiting unit that short-circuits or opens the AC power supply via the reactor and increases or decreases the inter-terminal voltage of the smoothing unit by utilizing the electromagnetic energy storage effect of the reactor, A step of determining whether the load is large or small based on supply information such as electric power or current supplied to the load connected between the terminals of the smoothing means or information from the load; The step of setting the partial switching mode in which the short-circuiting operation of the short-circuiting device is performed once or a plurality of times in a half cycle of the power supply; And a step of setting a high-frequency switching mode in which the short-circuiting operation of the short-circuiting means is performed at a high frequency. 19. The step of controlling the short-circuiting operation of the short-circuiting device so that the efficiency is improved depending on the load and the harmonic component contained in the input current is kept within a predetermined value. The method for controlling operation of the power supply device according to claim 18, wherein