CN217332839U

CN217332839U - Microwave detection device

Info

Publication number: CN217332839U
Application number: CN202220769731.2U
Authority: CN
Inventors: 邹高迪; 孙毅; 邹新; 邹明志
Original assignee: Shenzhen Merrytek Technology Co Ltd
Current assignee: Shenzhen Merrytek Technology Co Ltd
Priority date: 2022-01-25
Filing date: 2022-04-02
Publication date: 2022-08-30
Anticipated expiration: 2032-04-02
Also published as: CN114624695B; CN114624696A; CN217360292U; CN114624696B; CN217332841U; CN217332844U; CN114624695A; WO2023143104A1; CN217332838U; CN217820849U; CN116148833A; CN217820850U; CN114624697B; CN217332840U; CN114624697A; CN217332843U; CN217332842U; CN218331959U; CN217766842U; CN219811054U

Abstract

The utility model provides a microwave detection device, wherein microwave detection device is through the mode of accessing the echo signal of balanced differential signal form from microwave detection device's receiving antenna for electromagnetic interference in the environment exists with the common mode interference form in the echo signal and can restrain environmental interference in the transmission process of echo signal, so that in the successor, based on the further inhibition effect of the difference to single-ended processing step of echo signal to balanced differential signal form to common mode interference in the echo signal to balanced differential signal form, the echo signal of single-ended signal form free from environmental electromagnetic interference is output, and based on the mixing processing step of echo signal to single-ended signal form, the Doppler intermediate frequency signal is output, thereby improving Doppler intermediate frequency signal to move action, micro-motion with the human body, and feedback accuracy of activity characteristics corresponding to breathing and heartbeat movements.

Description

Microwave detection device

Technical Field

The utility model relates to a microwave detection field, in particular to microwave detection device based on doppler effect principle.

Background

With the development of the internet of things technology, the requirements of artificial intelligence, smart home and intelligent security technology on environment detection, particularly on detection accuracy of human existence, movement and micro motion are higher and higher, and accurate judgment basis can be provided for intelligent terminal equipment only by acquiring a stable enough detection result. The microwave detection technology based on the Doppler effect principle is used as a person and an object, and an important junction connected between the object and the object has unique advantages in behavior detection and existence detection technology, can detect moving objects such as action characteristics, movement characteristics and micro-movement characteristics of the person and even heartbeat and respiration characteristic information of the person under the condition of not invading the privacy of the person, and has wide application prospect. In particular, the respective microwave probe is fed by an excitation signal to emit a microwave beam corresponding to the frequency of said excitation signal into said target space, further forming a detection region in the target space, and receiving a reflected echo formed by the reflection of the microwave beam by the corresponding object in the detection region and transmitting an echo signal corresponding to the frequency of the reflected echo to a mixer detector unit, wherein the mix detection unit mixes the excitation signal and the echo signal to output a Doppler intermediate frequency signal corresponding to a frequency/phase difference between the excitation signal and the echo signal, wherein, based on the Doppler effect principle, when the object reflecting the microwave beam is in motion, the echo signal and the excitation signal have a certain frequency/phase difference, and the Doppler intermediate frequency signal presents corresponding amplitude fluctuation to feed back human body activity.

In an unlicensed ISM band defined by ITU-R (ITU radio communication Sector) for being opened to organizations such as industry, science and medicine, frequency bands applied to microwave detection mainly include limited frequency band resources such as 2.4Ghz, 5.8Ghz, 10.525Ghz, 24.125Gh, etc., and a corresponding microwave detector needs to observe a certain transmission power (generally, the transmission power is lower than 1W) to reduce interference to other radio devices when using the frequency bands, although the definition and permission of different frequency bands can standardize the use frequency bands of radio and reduce the probability of mutual interference between radio devices of different frequency bands, under the permission of limited frequency band resources, along with the high-speed development of the technology of internet of things, the radio use coverage rate corresponding to adjacent frequency bands or the same frequency band is increased at a high speed, such as an increasingly popular 5G wireless router, or the 5G frequency band is newly added on the basis of the duplex mode on the basis of the original 2.4G wireless router, so that the problem of mutual interference between radios in adjacent or same frequency bands is increasingly serious, and along with people-oriented intelligent competition, the requirement for accurately detecting human action characteristics including respiratory action and even heartbeat action is also rapidly increased. Therefore, the anti-interference performance is one of the factors that measure the accuracy of the corresponding microwave detection module, and under the circumstance that the problem of mutual interference between radios is becoming serious, the accuracy of the existing microwave detector is difficult to maintain, and not to mention, the requirement of accurate detection of human motion characteristics including breathing motion and even heartbeat motion is satisfied.

Further, since the boundary of the corresponding microwave beam is a gradient boundary where the radiation energy is attenuated to a certain degree and has non-determinacy, and since there is no effective control means for the electromagnetic radiation, i.e. shaping means for the gradient boundary of the corresponding microwave beam, which is mainly reflected in the lack of adjusting means for the beam angle of the microwave beam, the actual detection space covered by the microwave beam emitted by the corresponding microwave detector is difficult to be stably controlled, and further based on the reflection and penetration behavior of the microwave beam in different target detection spaces, the actual detection space of the existing microwave detector cannot be matched with the corresponding target detection space independently based on the adjustment for the beam angle of the microwave beam, so as to achieve a state where the target detection space outside the actual detection space cannot be effectively detected, and/or a state where there is environmental interference in the actual detection space outside the target detection space, the microwave detection method based on the Doppler effect principle comprises the steps of action interference, electromagnetic interference and self-excitation interference caused by an electromagnetic shielding environment, and solves the problems that the existing microwave detection technology based on the Doppler effect principle is poor in accuracy and/or poor in anti-interference performance, namely, because the boundary of a microwave beam is a gradient boundary of which the radiation energy is attenuated to a certain degree, a shaping means for the gradient boundary of the microwave beam is lacked, and based on the reflection and penetration characteristics of the microwave beam, the actual detection space of the existing microwave detector is difficult to match with the corresponding target detection space in actual application, and the defects that the existing microwave detector is limited in adaptability to different application scenes in actual application and has poor detection stability are caused.

In order to solve the above drawbacks, the conventional microwave detector mainly reduces the probability of mutual interference between antennas in the same frequency band by narrowing the frequency bandwidth of the antennas, and increases the amplitude difference of the corresponding effective signal relative to the interference signal in the doppler intermediate frequency signal by increasing the strength of the echo signal, so as to set and reduce the sensitivity of the microwave detection module with the corresponding threshold value of the doppler intermediate frequency signal on the amplitude value, thereby eliminating the environmental interference of the actual detection space outside the target detection space corresponding to the interference signal with a low amplitude value based on the reduction of the sensitivity. On one hand, although the probability of mutual interference between antennas in the same frequency band can be reduced by narrowing the frequency bandwidth of the antennas, based on the difference in the operating principle, antennas for communication purposes (such as antennas in a wireless router) are often designed to have a wider frequency bandwidth to meet the requirement of multi-channel communication, and narrowing the frequency bandwidth of the antennas of the microwave probe cannot ensure that the antennas of the existing microwave probe are not interfered by the antennas for communication purposes or do not cause interference to the antennas for communication purposes under the background that the coverage rate of radio use in adjacent frequency bands or the same frequency band is increased at a high speed; in addition, based on the corresponding relationship between the frequency bandwidth of the antenna and the structural form and size of the antenna, narrowing the frequency bandwidth of the antenna of the microwave detector can simultaneously form high-precision requirements on the structure and size of the antenna, and the corresponding high-precision requirements are more severe along with the improvement of the resonant frequency point of the antenna, so that additional cost burden is correspondingly generated. On the other hand, since the amplitude of the doppler intermediate frequency signal is related to the energy of the reflected echo and is also related to the size of the reflecting surface area in the environment, the size and the moving speed of the reflecting surface of the moving object and the distance between the microwave detection module, the reduction of the sensitivity of the microwave detector cannot accurately exclude the environmental interference and the motion interference of the actual detection space outside the target detection space, so that the detection of the target detection space is not stable and accurate; in addition, based on the high strength requirement of the existing microwave detector for the echo signal, the range adjustment for the actual detection space tends to have a higher electromagnetic radiation energy density in the target detection space while covering the corresponding target detection space, so that the existing microwave detector cannot avoid interference to the antenna for communication use in the target detection space based on the reduction of the sensitivity, and it is difficult to avoid interference to the antenna for communication use in the target detection space based on the reduction of the sensitivity in pursuit of the antenna for communication use for high signal strength.

SUMMERY OF THE UTILITY MODEL

An object of the utility model is to provide a microwave detection device, wherein microwave detection device's detection method has broken through the technical tendency that technical staff in the field tends to improve echo signal's intensity, and the antenna based on the communication usage pursues high signal strength's universality, through reducing microwave detection device's transmitting antenna's transmitting power's mode has reduced correspondingly the microwave beam with reflection echo's signal strength has reduced promptly the microwave beam with reflection echo's electromagnetic radiation energy density, and then can utilize communication device from the end in area to make an uproar the suppression mechanism, it is right to avoid causing the interference and can reduce or even remove communication device's in the installing environment installing position to microwave detection device in the restriction of corresponding installing environment.

Another object of the present invention is to provide a microwave detecting device, wherein the transmitting antenna of the microwave detecting device is provided with a transmitting antenna, the microwave beam is reduced in signal strength, so that the signal strength of the microwave beam is reduced and the microwave beam is in a state of weak signal form based on the fact that the microwave beam is far greater than the loss generated by the penetrating action of the masonry wall or glass to the masonry structure, the microwave beam is absorbed by the masonry wall or glass to the weak signal form to form a weak signal form, the microwave beam is defined in the adaptability of the gradient boundary of the microwave beam, the state of the space form of the target detecting space is not limited, and the effective detecting space of the microwave detecting device using the masonry wall or glass as the boundary can be matched with the target detecting space and matched with the target detecting space The adaptability of the microwave detection device to different target detection spaces in practical application is improved.

Another object of the present invention is to provide a microwave detecting device, wherein the microwave detecting device is provided with a plurality of reflecting actions, and the reflecting actions of the microwave beams are reflected by the reflecting actions of the microwave beams, so as to avoid the self-excited interference generated by the multiple reflecting actions.

Another object of the present invention is to provide a microwave detecting device, wherein through reducing microwave detecting device's transmitting antenna's transmitting power's mode, transmitting antenna's immunity is right transmitting antenna's frequency bandwidth's dependency is reduced, and it is right that the correspondence has been reduced transmitting antenna's required precision and be favorable to reducing transmitting antenna's manufacturing cost.

Another object of the present invention is to provide a microwave detecting device, wherein the reduction of the transmitting power of the transmitting antenna of the microwave detecting device is not aimed at adjusting the gradient boundary of the microwave beam in the conventional sense, and the state of the transmitting antenna of the microwave detecting device being excited to transmit the microwave beam is based on the principle that the coverage space of the microwave beam corresponds to the gain (dBd or dBi) of the transmitting antenna of the microwave detecting device and is not controlled by the transmitting power of the transmitting antenna, so as to reduce the electromagnetic radiation energy density of the microwave beam in the coverage space thereof by reducing the transmitting power of the transmitting antenna, so as to increase the ratio of the loss generated by the penetrating action of the microwave beam to the radiation energy of the microwave beam, thereby reducing the signal intensity of the microwave beam to be in a weak signal form, the microwave detection device has the advantages that the microwave beams in weak signal forms are absorbed by the concrete walls or glass of the masonry structure defining the target detection space, the concrete walls or glass of the masonry structure are used as boundaries to form adaptive definition of gradient boundaries of the microwave beams in weak signal forms, and therefore adaptability of the microwave detection device to different target detection spaces in practical application is improved.

Another object of the present invention is to provide a microwave detecting device, wherein the reduction of the transmitting power of the transmitting antenna of the microwave detecting device is not aimed at adjusting the gradient boundary of the microwave beam in the conventional sense, the transmitting antenna of the microwave detecting device is excited to transmit the state of the microwave beam, based on the principle that the coverage space range of the microwave beam corresponds to the gain (dBd or dBi) of the transmitting antenna of the microwave detecting device and is not controlled by the transmitting power of the transmitting antenna, the utility model reduces the electromagnetic radiation energy density of the microwave beam in the coverage space thereof to be suitable for being suppressed by the bottom noise suppressing mechanism of the corresponding communication device based on the microwave beam, thereby breaking through the weak signal form that the person skilled in the art tends to improve the strength of the echo signal and tends to the same condition that the microwave beam covers the corresponding target detecting space The technical trend of higher electromagnetic radiation energy density in the target detection space.

Another object of the present invention is to provide a microwave detecting device, wherein based on the theoretical recognition that the transmitting power (dBm) of the transmitting antenna of the microwave detecting device is equal to the signal source power (dBm) -the transmission line loss (dB) + the transmitting antenna gain (dBd or dBi), and experimental exploration and cognition of a background noise suppression mechanism of a communication device in the non-field, the utility model forms a weak signal form of the microwave beam by reducing the transmitting power of the transmitting antenna to be less than or equal to 0dBm, the energy density of the electromagnetic radiation corresponding to the microwave beam in the covered space approaches the gradient boundary in the traditional sense and the energy density of the electromagnetic radiation outside the gradient boundary, the reduction of the transmitting power of the transmitting antenna of the microwave detection device is therefore not aimed at adjusting the gradient boundaries in the conventional sense of the microwave beam.

Another object of the present invention is to provide a microwave detecting device, wherein the detecting method of the microwave detecting device includes improving the conversion efficiency of the transmitting antenna, so as to avoid the transmitting antenna cannot complete the initial polarization and cannot transmit correspondingly in the state where its transmitting power is reduced based on the dielectric loss of itself the technical obstacle of the microwave beam corresponds to the guarantee the stable transmitting state of the microwave beam is reduced the minimum transmitting power extreme value of the transmitting antenna, so as to reduce the transmitting power of the transmitting antenna to the state guarantee micro-signal form of the corresponding target transmitting power the stable transmitting of the microwave beam.

Another object of the present invention is to provide a microwave detecting apparatus, wherein the feeding is achieved by phase difference, the circular polarization of the transmitting antenna is reduced the minimum transmitting power extreme value of the transmitting antenna is ensured the stable transmitting state of the microwave beam is reduced the minimum transmitting power extreme value of the transmitting antenna is reduced the stable transmitting of the microwave beam is ensured the state of the transmitting power of the transmitting antenna to the target transmitting power.

Another object of the utility model is to provide a microwave detection device, wherein through the mode of difference feed transmitting antenna adopts the linear polarization form transmitting antenna's state, in transmitting antenna's linear polarization direction, it is right to realize transmitting antenna is greater than the difference feed that 90 differences, in order to reduce transmitting antenna reduces based on the loss that electric field coupling produced at initial polarization in-process transmitting antenna's minimum transmitting power extreme value, thereby reducing transmitting antenna's transmitting power to target transmitting power's state, the guarantee transmitting antenna is to the micro-signal form the stable transmission of microwave beam.

Another object of the utility model is to provide a microwave detection device, wherein reduce based on the mode of emitting antenna's self dielectric loss reduces emitting antenna's minimum transmitting power extreme value, microwave detection device adopts half-wave inflection formula directional microwave detection antenna as emitting antenna, with based on half-wave inflection formula directional microwave detection antenna uses the air to reduce as the structural feature of medium emitting antenna's self dielectric loss and reduction emitting antenna's minimum transmitting power extreme value, and based on half-wave inflection formula directional microwave detection antenna's high-gain characteristic further reduces emitting antenna's minimum transmitting power extreme value, thereby reducing emitting antenna's transmitting power to the state guarantee micro-signal form that is less than or equal to 0dBm or lower the stable transmission of microwave beam.

Another objective of the present invention is to provide a microwave detecting device, wherein the minimum transmitting power extreme value of the transmitting antenna is reduced based on the manner of reducing the self dielectric loss of the transmitting antenna, the microwave detecting device adopts a dual-fed differential antenna as the transmitting antenna, wherein the dual-fed differential antenna comprises a reference ground and two strip-shaped oscillators, wherein two ends of the two strip-shaped oscillators, which are connected to the excitation signal, are respectively the feeding ends of the two strip-shaped oscillators, the two strip-shaped oscillators extend from the same lateral space of the reference ground through the two feeding ends and respectively have a wavelength electrical length greater than or equal to 3/16 and less than or equal to 5/16, wherein the two strip-shaped oscillators respectively have a coupling section, wherein the end of the coupling section, which is close to the feeding end of the strip-shaped oscillator to which the coupling section belongs, is the proximal end of the coupling section, the two coupling sections extend in the dislocation opposite direction from the near end and have a dislocation distance which is greater than or equal to lambda/256 and less than or equal to lambda/6, namely, the distance from any point on one coupling section to the other coupling section is greater than or equal to lambda/256 and less than or equal to lambda/6, wherein lambda is a wavelength parameter corresponding to the frequency of the excitation signal, so that the double-ended feed type differential antenna is used as the transmitting antenna, the excitation signals with a difference of greater than 90 DEG are accessed to the two feeding ends of the two strip-shaped elements to be subjected to phase difference feeding, a polarization form tending to linear polarization is realized on the basis that the coupling between the two strip-shaped elements and the reference ground has a difference of greater than 90 DEG, and the coupling between the two coupling sections is formed on the basis that the two coupling sections extend in the dislocation opposite direction from the near end, and a common resonance frequency point is formed based on mutual coupling between the two coupling sections, namely, in a state that the double-feed differential antenna is used as the transmitting antenna to access excitation signals with a difference of more than 90 degrees at the two feeding ends of the two strip-shaped oscillators, differential feeding to the transmitting antenna is realized in a polarization direction of the transmitting antenna which tends to be linearly polarized, the minimum transmitting power extreme value of the transmitting antenna is reduced in a state of ensuring stable transmitting of the microwave beam, and further, stable transmitting of the microwave beam in a micro-signal form is ensured in a state of reducing the transmitting power of the transmitting antenna to a target transmitting power.

Another object of the present invention is to provide a microwave detecting device, wherein the state of the transmitting antenna is in a linear polarization state the polarization direction of the transmitting antenna is preferably based on the balanced differential feeding that the transmitting antenna tends to 180 ° phase difference, or the dual feed type differential antenna is adopted as the state of the transmitting antenna is preferably based on the balanced differential feeding that the transmitting antenna tends to 180 ° phase difference, and the minimum transmitting power extreme value of the transmitting antenna is reduced in the state of the stable transmission of the microwave beam, so as to reduce the transmitting power of the transmitting antenna to the state of less than or equal to 0dBm or lower to ensure the stable transmission of the microwave beam.

It is another object of the present invention to provide a microwave detecting device, wherein the microwave detecting device includes a differential feeding circuit, wherein the differential feeding circuit is provided in the form of discrete components and has a three-pole circuit handler provided as an MOS transistor or a triode, an inductor, a first resistor, a second resistor, a third resistor, a first capacitor, a second capacitor, an oscillation capacitor and a power connection terminal adapted to be connected to a corresponding power source, wherein the three-pole circuit handler has a first connection terminal corresponding to a collector electrode of the triode or a drain electrode of the MOS transistor, a second connection terminal corresponding to a base electrode of the triode or a gate electrode of the MOS transistor, and a third connection terminal corresponding to an emitter electrode of the triode or a source electrode of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit handler, the other end of the second resistor is connected to the power connection terminal via the inductor, and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit processor, and the other end of the third resistor is grounded, wherein one end of the oscillating capacitor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the oscillating capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor, and the other end of the first resistor is electrically connected between the inductor and the second resistor or to the power connection terminal, wherein two ends of the second capacitor are electrically connected to the first connection terminal and the third connection terminal of the three-pole circuit processor, respectively, the second resistor and the third resistor are set to be equal in resistance value, so that in the state that the differential feed circuit is connected to a corresponding power supply at the power supply connecting end, the excitation signal is output at two ends of the second capacitor in a balanced differential signal form with a phase difference approaching 180 degrees, and therefore phase difference feeding of the transmitting antenna approaching 180 degrees is achieved.

Another object of the present invention is to provide a microwave detecting device, wherein the microwave detecting device includes a differential feeding circuit, wherein the differential feeding circuit is configured in an integrated circuit form and has two opposite phase outputs, so that two opposite phase outputs output balanced differential signals with a phase difference of 180 ° to the excitation signals.

Another object of the present invention is to provide a microwave detecting device, wherein the detecting method of the microwave detecting device further includes improving the step of the accuracy of the echo signal, so that the intensity of the echo signal is based on the state that the transmitting power of the transmitting antenna is reduced, based on the improvement of the accuracy of the echo signal, the microwave detecting device is guaranteed to move the action, the fine motion action with the human body, and the accuracy and the stability of the detection and the detection of the respiration and the heartbeat corresponding movement characteristics.

Another object of the present invention is to provide a microwave detecting device, wherein the improvement step of the accuracy of the echo signal comprises accessing the receiving antenna of the microwave detecting device to the echo signal in the form of balanced differential signal, then the electromagnetic interference in the environment exists in the form of common mode interference in the echo signal, so that the echo signal in the form of differential signal can be suppressed in the receiving and transmitting processes, and in the subsequent process, the doppler intermediate frequency signal in the form of balanced differential signal is outputted based on the mixing processing step of the echo signal in the form of balanced differential signal, and the intermediate frequency doppler signal in the form of single-ended signal is outputted based on the differential-to-single-ended processing step of the doppler intermediate frequency signal in the form of balanced differential signal, so as to perform the mixing processing step of the echo signal in the form of balanced differential signal and/or to the form of balanced differential signal the doppler intermediate frequency signal A differential-to-single-ended processing step, which further suppresses common-mode interference in the echo signals and/or the doppler intermediate frequency signals in balanced differential signal form, outputs the doppler intermediate frequency signals in single-ended signal form free from environmental electromagnetic interference, thereby improving the feedback accuracy of the Doppler intermediate frequency signal to the activity characteristics corresponding to the human body movement action, the micro-motion action, the respiration action and the heartbeat action, the processing system of the balanced differential signal is constructed corresponding to the step of accessing the echo signal in the form of the balanced differential signal from the receiving antenna of the microwave detection device with micro transmitting power and the subsequent steps, the microwave detection device with micro transmitting power can ensure the movement action and the micro-movement action of the microwave detection device with the micro transmitting power with the human body, and the detection range and the detection accuracy and stability of the activity characteristics corresponding to the breathing and heartbeat actions.

Another object of the present invention is to provide a microwave detecting device, wherein the step of improving the accuracy of the echo signal includes the step of accessing the echo signal in a balanced differential signal form from a receiving antenna of the microwave detecting device, so that the electromagnetic interference in the environment exists in a common mode interference form in the echo signal, and thus can be suppressed during the receiving and transmitting processes of the echo signal in a differential signal form, and in the subsequent step, the echo signal in a single-ended signal form free from the environmental electromagnetic interference is outputted based on the further suppressing effect of the differential-to-single-ended processing step of the echo signal in a balanced differential signal form on the common mode interference in the echo signal in a balanced differential signal form, and the doppler intermediate frequency signal free from the environmental electromagnetic interference is outputted based on the mixing processing step of the echo signal in a single-ended signal form free from the environmental electromagnetic interference, the feedback accuracy of the Doppler intermediate frequency signal to the activity characteristics corresponding to the human body movement action, the micro-motion action and the respiration and heartbeat action is improved, and the detection range and the detection accuracy and stability of the microwave detection device with the micro-transmitting power to the activity characteristics corresponding to the human body movement action, the micro-motion action and the respiration and heartbeat action are guaranteed by a processing system of the balanced differential signal, which is constructed by the step of accessing the echo signal with the balanced differential signal form and the subsequent step, of the receiving antenna of the microwave detection device with the micro-transmitting power.

Another object of the present invention is to provide a microwave detecting device, wherein based on the balanced differential signal form, the differential to single-ended processing step of the doppler intermediate frequency signal is further suppressing the common-mode interference in the doppler intermediate frequency signal, or based on the balanced differential signal form, the differential to single-ended processing step of the echo signal is further suppressing the common-mode interference in the echo signal, the electromagnetic radiation interference in the environment is not present in the balanced differential signal form in the state received by the receiving antenna in the common-mode form, and can be effectively suppressed, including the electromagnetic radiation interference in the environment with the same frequency as the echo signal, so as to improve the frequency of the doppler intermediate frequency signal to move with the human body, Fine motion, and feedback accuracy of activity characteristics corresponding to respiration and heartbeat.

Another object of the present invention is to provide a microwave detecting device, wherein from microwave detecting device's receiving antenna inserts balanced differential signal form echo signal's step includes that two receiving feed points of receiving antenna are based on the phase shift step of the echo signal of one of them receiving feed point access to the state of arranging by the quadrature echo signal access balanced differential signal form echo signal, with based on quadrature form guarantee between two receiving feed points of receiving antenna certainly isolation between two receiving feed point access echo signal of receiving antenna corresponds the guarantee based on the phase shift step of the echo signal of one of them receiving feed point access to the balanced differential signal form echo signal's precision.

Another object of the present invention is to provide a microwave detecting device, wherein the receiving antenna of the microwave detecting device is connected to the balanced differential signal form in the step of the echo signal, two receiving feeding points of the receiving antenna are arranged in opposite phase, so that the receiving feeding points are connected to the balanced differential signal form in the echo signal.

Another object of the present invention is to provide a microwave detecting device, wherein the transmitting antenna and the receiving antenna of the microwave detecting device share the structural configuration of the reference ground is set up to facilitate the miniaturization design of the microwave detecting device.

Another object of the present invention is to provide a microwave detecting device, wherein the transmitting antenna and the receiving antenna are integrally disposed in a separated form, so as to ensure isolation between corresponding feeding points (ends) and guarantee the accuracy of the echo signal, and facilitate the miniaturization design of the microwave detecting device.

Another object of the present invention is to provide a microwave detecting device, wherein the transmitting antenna and the receiving antenna are integrally disposed in a receiving and transmitting integrated manner, so as to simplify the circuit design of the microwave detecting device and facilitate the miniaturization design of the microwave detecting device.

According to an aspect of the utility model, the utility model provides a microwave detection device, microwave detection device includes:

a transmitting antenna, wherein the transmitting antenna is set to transmit a microwave beam corresponding to a frequency of an excitation signal in a state of being fed by the excitation signal;

a receiving antenna, wherein the receiving antenna is configured in a planar patch antenna configuration and has a ground reference and a radiation source, wherein the radiation source is configured in a spaced apart manner from the ground reference, wherein the radiation source is configured in a unit radiation source configuration, and has a single number of radiation elements corresponding to the radiation source, wherein the radiation elements have two feeding points, wherein the two feeding points are arranged in opposite phases, and a connection line direction from one of the feeding points to a physical center point of the radiation element and a connection line direction from the other feeding point to the physical center point of the radiation element are coincident with each other, so as to output the echo signals in a balanced differential signal configuration at the two feeding points after receiving a reflected echo formed after the microwave beam is reflected by a corresponding object based on a structural state in which the two feeding points are arranged in opposite phases, the echo signal comprises a signal corresponding to a reflected echo formed by the microwave beam reflected by a corresponding object, and the electromagnetic interference in the environment exists in a common-mode interference form in the echo signal so as to suppress the environmental interference in the receiving and transmitting processes of the echo signal in a balanced differential signal form;

the differential-to-single-ended circuit is used for performing differential-to-single-ended processing on the echo signals in a balanced differential signal form so as to output echo signals in a single-ended signal form; and

a mixer circuit, wherein the mixer circuit is configured to perform a mixing process on the excitation signal and the echo signal in the form of a single-ended signal to output a doppler intermediate frequency signal in the form of a single-ended signal, so as to improve the accuracy of the doppler intermediate frequency signal in the form of a single-ended signal by improving the feedback accuracy of the echo signal in the form of a single-ended signal to the reflected echo based on the suppression effect of the conversion process from the echo signal in the form of a balanced differential signal to the echo signal in the form of a single-ended signal in the echo signal in the form of a balanced differential signal.

In an embodiment, the two feeding points of the radiating element of the receiving antenna are arranged to be point-symmetric with respect to a physical center of the radiating element.

In one embodiment, the radiating element is electrically connected to the reference ground at its physical center point.

In one embodiment, the radiating element has at least one group and/or at least one pair of grounding points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element at the physical central point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the zero potential point is equivalent to the physical central point of the radiating element and the reference ground are electrically connected.

In an embodiment, the transmitting antenna is configured in a planar patch antenna form and has a reference ground and a radiation source, wherein the radiation source is configured on one side of the reference ground in a state of being spaced apart from the reference ground, the radiation source is configured in a unit radiation source form, the radiation source has a single number of radiation elements, the radiation elements have two feeding points, the two feeding points are arranged in opposite phases, and a connection line direction from one of the feeding points to a physical center point of the radiation element and a connection line direction from the other feeding point to the physical center point of the radiation element are coincided oppositely, so that the two feeding points are connected with an excitation signal to realize feeding of the transmitting antenna.

In an embodiment, the transmitting antenna and the receiving antenna are integrally disposed in a transceiving separated manner based on a structural form sharing the reference ground, the transmitting antenna and the receiving antenna integrally disposed in the transceiving separated manner include one reference ground and one radiation source, the radiation source is disposed in a binary radiation source form and has two radiation elements, each radiation element has two feeding points, the two feeding points of each radiation element are arranged in an inverted phase, a connection direction of the two feeding points of each radiation element is taken as a polarization direction, the two radiation elements are arranged orthogonally, the polarization direction of one of the radiation elements is perpendicular to the polarization direction of the other radiation element, and thus, the two feeding points of one of the radiation elements are connected with an excitation signal to realize feeding of the transmitting antenna, and outputting the echo signals in a balanced differential signal form at the two feeding points of the other radiating element to correspondingly form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separation mode.

In an embodiment, the transmitting antenna and the receiving antenna are integrally disposed in a transceiving split manner based on a structural configuration sharing the reference ground and the radiation source, the transmitting antenna and the receiving antenna integrally disposed in a transceiving split manner include one reference ground and one radiation source, the radiation source is disposed in a unit radiation source configuration and has a single number of the radiating elements, the radiating elements have four feeding points, an included angle between a connecting line between any two adjacent feeding points and a physical central point of the radiating element in a direction around the physical central point of the radiating element is equal to 90 °, and a structural configuration in which two opposite feeding points are arranged in opposite phase is formed, so that two opposite feeding points of the radiating element access an excitation signal to realize feeding of the transmitting antenna, and outputting the echo signals in a balanced differential signal form at the other two opposite feed points, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separated form.

In one embodiment, the transmitting antenna and the receiving antenna are integrally arranged in a transceiving mode based on the structural configuration of sharing the reference ground and the radiation source, the transmitting antenna and the receiving antenna which are integrally arranged in a transceiving mode respectively comprise one reference ground and one radiation source, wherein the radiation source is arranged in a unit radiation source configuration with a single number of the radiating elements, wherein the radiating element has two feeding points, wherein the two feeding points are arranged in opposite phase, so that an excitation signal is switched in the two feeding points of the radiating element to realize feeding of the transmitting antenna, and the echo signals in a balanced differential signal form are output at the two feeding points, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving mode.

In an embodiment, the microwave detection device further includes at least one amplifying circuit adapted to amplify a signal in a differential signal form, wherein the amplifying circuit is disposed between the receiving antenna and the differential-to-single-ended circuit to amplify the echo signal in a balanced differential signal form output to the differential-to-single-ended circuit.

In an embodiment, the differential-to-single-ended circuit and the amplifying circuit are integrally arranged in a circuit form of an instrumentation amplifier.

Drawings

Fig. 1A is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to an embodiment of the present invention.

Fig. 1B is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 1C is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 2A is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 2B is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 3A is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 3B is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4A is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4B is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4C is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4D is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4E is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4F is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4G is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4H is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4I is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4J is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4K is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4L is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4M is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 4N is a schematic structural diagram of a transmitting antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 5A is a schematic structural diagram of a differential feed circuit of a microwave detection device according to an embodiment of the present invention.

Fig. 5B is a schematic structural diagram of a differential feed circuit of a microwave detecting device according to another embodiment of the present invention.

Fig. 6 is a schematic structural diagram of a differential oscillation circuit of a microwave detection device according to an embodiment of the present invention.

Fig. 7A is a schematic structural diagram of a microwave detection device according to an embodiment of the present invention.

Fig. 7B is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention.

Fig. 7C is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention.

Fig. 8A is a schematic structural diagram of a receiving antenna of a microwave detecting device according to an embodiment of the present invention.

Fig. 8B is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 8C is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 8D is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 9A is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 9B is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 9C is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 9D is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 9E is a schematic structural diagram of a receiving antenna of a microwave detecting device according to another embodiment of the present invention.

Fig. 10A is a schematic structural diagram illustrating a transmitting antenna and a receiving antenna of a microwave detecting device according to an embodiment of the present invention are integrally disposed.

Fig. 10B is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.

Fig. 10C is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.

Fig. 10D is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.

Fig. 10E is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.

Fig. 10F is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.

Fig. 10G is a schematic structural diagram illustrating a transmitting antenna and a receiving antenna of a microwave detecting device according to another embodiment of the present invention are integrally disposed.

Fig. 10H is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.

Fig. 10I is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.

Fig. 10J is a schematic structural diagram of a microwave detecting device according to another embodiment of the present invention, in which a transmitting antenna and a receiving antenna are integrally disposed.

Detailed Description

The following description is provided to disclose the invention so as to enable any person skilled in the art to practice the invention. The preferred embodiments in the following description are given by way of example only, and other obvious variations will occur to those skilled in the art. The basic principles of the invention, as defined in the following description, may be applied to other embodiments, variations, modifications, equivalents and other technical solutions without departing from the spirit and scope of the invention.

It will be understood by those skilled in the art that in the present disclosure, the terms "longitudinal," "lateral," "upper," "lower," "front," "rear," "left," "right," "vertical," "horizontal," "top," "bottom," "inner," "outer," and the like are used in a generic and descriptive sense only and not for purposes of limitation, as the terms are used in the description to indicate that the referenced device or element must have the specified orientation, be constructed and operated in the specified orientation, and not for the purposes of limitation.

It is understood that the terms "a" and "an" should be interpreted as meaning that a number of one element or element is one in one embodiment, while a number of other elements is one in another embodiment, and the terms "a" and "an" should not be interpreted as limiting the number.

The utility model provides a microwave detection device, wherein microwave detection device's detection method has broken through the technical tendency that technical staff in the field tends to improve corresponding echo signal's intensity, and antenna based on communication usage pursues high signal strength's universality, through reducing microwave detection device's transmitting antenna's transmitting power's mode has reduced correspondingly the signal strength of microwave beam and reflection echo has reduced promptly the microwave beam with reflection echo's electromagnetic radiation energy density, and then can utilize communication device from the end suppression mechanism of making an uproar in area, it is right to avoid causing the interference and can reduce or even remove communication device's in the installation position of installation environment corresponding microwave detection device's restriction in the installation position of corresponding installation environment.

The transmitting power of the transmitting antenna of the microwave detection device is reduced, the signal intensity corresponding to the microwave beam is reduced and the microwave beam is in a weak signal form, and the corresponding communication device in the environment can resist the interference of the microwave detection device based on a self-contained bottom noise suppression mechanism, so that the influence of the frequency bandwidth of the transmitting antenna of the microwave detection device is reduced for the interference capability of the microwave detection device on the corresponding communication device, namely the dependence of the immunity of the transmitting antenna on the narrowed frequency bandwidth is reduced, the precision requirement on the transmitting antenna is correspondingly reduced, and the production cost of the transmitting antenna is favorably reduced.

Meanwhile, since the signal intensity of the microwave beam is reduced, based on the characteristic that the loss generated by the penetration behavior of the microwave beam to the concrete wall or glass of the masonry structure is much larger than the loss generated by propagation in the space, in a state where the signal intensity of the microwave beam is reduced to be in a weak signal form, by absorption of the microwave beam in a weak signal form by a concrete wall or glass of a masonry structure defining a target detection space, i.e. an adaptive definition of the gradient boundaries of the microwave beam, which can form weak signal morphology, corresponding to a state in which the spatial morphology of the target detection space is not restricted, the effective detection space of the microwave detection device, which is bounded by the masonry-structured concrete wall or glass, can be matched with the corresponding target detection space, so that the adaptability of the microwave detection device to different target detection spaces in practical application is improved.

Further, since the signal intensity of the microwave beam is reduced to be in a weak signal form, the ratio of the loss generated based on the reflection behavior of the microwave beam to the radiation energy of the microwave beam is increased, so that the self-excited interference generated based on the multiple reflection behavior can be avoided.

That is, the transmitting power of the transmitting antenna of the microwave detecting device is reduced, and the signal strength of the corresponding microwave beam is reduced to be in a weak signal form, so that the strength of the corresponding echo signal is reduced, and thus the detecting method of the microwave detecting device breaks through the technical trend that a person skilled in the art tends to increase the strength of the corresponding echo signal to tend to have a higher electromagnetic radiation energy density in the target detecting space while the microwave beam covers the corresponding target detecting space, wherein the reduction of the transmitting power of the transmitting antenna of the microwave detecting device is not intended to adjust the gradient boundary in the conventional sense of the microwave beam, but is not intended to be based on the condition that the transmitting antenna of the microwave detecting device is excited to transmit the microwave beam, and the coverage space range of the microwave beam corresponds to the gain (dBd or dBi) of the transmitting antenna of the microwave detecting device without being affected by the transmitting power of the transmitting antenna The principle of rate control is realized by reducing the electromagnetic radiation energy density of the microwave beam in the coverage space of the microwave beam by reducing the transmitting power of the transmitting antenna to a weak signal form which is suitable for being suppressed by a corresponding communication device based on an own background noise suppression mechanism, thereby avoiding interference with the corresponding communication device, and increasing the ratio of the loss generated by the penetration action of the microwave beam to the radiation energy of the microwave beam, the absorption of said microwave beam in weak signal form by masonry-structured concrete walls or glass delimiting the target detection space can then be utilized, the masonry concrete wall or glass boundary forms an adaptive definition of the gradient boundary of the microwave beam of weak signal morphology, correspondingly, the adaptability of the microwave detection device to different target detection spaces in practical application is improved.

Further, based on the theoretical recognition that the transmitting power (dBm) of the transmitting antenna of the microwave detection apparatus is equal to the signal source power (dBm) -the transmission line loss (dB) + the transmitting antenna gain (dBd or dBi), and the experimental exploration recognition of the noise floor suppression mechanism of the communication apparatus not in the field, the detection method of the microwave detection apparatus is preferably characterized by feeding the transmitting antenna with a feeding power of less than 1mW to form a weak signal shape of the microwave beam, corresponding to the electromagnetic radiation energy density of the microwave beam in the coverage space thereof approaching the conventionally significant gradient boundary and the electromagnetic radiation energy density beyond the gradient boundary, in a manner of reducing the transmitting power of the transmitting antenna to a target transmitting power of 0dBm or less, such as in a manner of reducing the transmitting power of the transmitting antenna to a target transmitting power of-3 dBm or-6 dBm, the reduction of the transmitting power of the transmitting antenna of the microwave detection device is therefore not aimed at adjusting the gradient boundaries in the conventional sense of the microwave beam.

It can be understood that, due to the existence of the dielectric loss of the transmitting antenna itself, the conversion efficiency of the transmitting antenna may not reach 100%, and correspondingly, in the process that the transmitting power of the transmitting antenna is reduced, the transmitting antenna may not transmit the corresponding microwave beam when the transmitting power of the transmitting antenna is not reduced to the target transmitting power, that is, the initial polarization process cannot be completed based on the dielectric loss of the transmitting antenna itself. That is to say, the minimum transmitting power capable of guaranteeing the stable transmission of the microwave beam is the minimum transmitting power extreme value of the transmitting antenna, and in the state that the minimum transmitting power extreme value of the transmitting antenna is less than 0dBm, the specific type and structural configuration of the transmitting antenna are not limited, but based on the dielectric loss of the transmitting antenna, the transmitting antenna has a technical obstacle that the minimum transmitting power extreme value of the transmitting antenna may be greater than the target transmitting power and cannot be further reduced in the state of guaranteeing the stable transmission of the microwave beam. Based on this, microwave detecting device's detection method still includes the improvement transmitting antenna's conversion efficiency's method step, in order to avoid transmitting antenna can't accomplish initial polarization and can't transmit correspondingly in its transmitted power reduced state based on the dielectric loss of self the technical barrier of microwave beam corresponds the guarantee the state of the stable transmission of microwave beam reduces transmitting antenna's minimum transmitted power extreme value, in order to reduce transmitting antenna's transmitted power to the state guarantee micro-signal form the stable transmission of microwave beam.

Specifically, in the method step of improving the conversion efficiency of the transmitting antenna, the circularly polarized form of the transmitting antenna is implemented in a phase difference feeding manner to reduce the minimum transmitting power extremum of the transmitting antenna, or in a state where the transmitting antenna adopts a linearly polarized form, in a linear polarization direction of the transmitting antenna, in a phase difference feeding manner, differential feeding is implemented for the transmitting antenna with a phase difference larger than 90 ° so as to reduce the minimum transmitting power extremum of the transmitting antenna based on the loss generated by the electric field coupling effect in the initial polarization process of the transmitting antenna, thereby ensuring stable transmission of the microwave beam in a micro signal form by the transmitting antenna in a state of reducing the transmitting power of the transmitting antenna to a target transmitting power.

Accordingly, referring to fig. 1A to 1C of the drawings of the present disclosure, various embodiments of the transmitting antenna 10 for realizing a circular polarization state based on a phase difference feeding mode are illustrated, wherein the transmitting antenna 10 is exemplarily configured in a planar patch antenna configuration to have a reference ground 11 and a radiation source 12, and wherein the radiation source 12 is configured at a side of the reference ground 11 in a spaced state from the reference ground 11.

Corresponding to fig. 1A and 1B, the radiation source 12 is configured as a unit radiation source, and corresponding to the radiation source 12, the radiation element 12 has a single number of radiation elements 121, wherein corresponding to fig. 1A, the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are orthogonally arranged, and connecting lines between the two feeding points 1211 and a physical central point 1212 of the radiation element 121 are perpendicular to each other, so that excitation signals with 90 ° difference are accessed to the two feeding points 1211 of the radiation element 121 by means of phase difference feeding to realize a circular polarization configuration of the transmitting antenna 10; corresponding to fig. 1B, the radiation element 121 has at least three feeding points 1211, wherein each feeding point 1211 is arranged around the physical center point 1212 of the radiation element 121 at the same distance, and an angle between a connecting line between any two adjacent feeding points 1211 and the physical center point 1212 of the radiation element 121 is equal to 360 °/n corresponding to a direction around the physical center point 1212 of the radiation element 121, where n is the number of feeding points 1211 of the radiation element 121, so that in a manner of phase difference feeding, excitation signals with a phase difference of 360 °/n are sequentially inputted to the feeding points 1211 of the radiation element 121 in a direction around the physical center point 1212 of the radiation element 121 to realize a circular polarization state of the transmission antenna 10, in particular in the transmission antenna 10 illustrated in fig. 1B, the number of the feeding points 1211 of the radiation element 121 is 4, and an included angle between a connecting line between any two adjacent feeding points 1211 and the physical center point 1212 of the radiation element 121 is equal to 90 ° in a direction around the physical center point 1212 of the radiation element 121, so that excitation signals with a 90 ° difference are sequentially accessed to the feeding points 1211 of the radiation element 121 in a direction around the physical center point 1212 of the radiation element 121 in a phase difference feeding manner, so as to implement a circular polarization configuration of the transmitting antenna 10.

Corresponding to fig. 1C, the radiation source 12 is disposed in a multi-element radiation source configuration, and at least three radiation elements 121 are disposed corresponding to the radiation source 12, wherein each radiation element 121 has a feeding point 1211, and each radiation element 121 is circumferentially arranged such that, in a circumferential arrangement direction of the radiation elements 121, an angle between a connecting line between the feeding point 1211 and a physical central point 1212 of any two adjacent radiation elements 121 is equal to 360 °/m, where m is the number of the radiation elements 121, so that excitation signals with a difference of 360 °/m are sequentially connected to the feeding point 1211 of each radiation element 121 in the circumferential arrangement direction of the radiation elements 121 in a phase-difference feeding manner to achieve a circular polarization configuration of the transmitting antenna 10. Preferably, each of the radiation elements 121 further satisfies that, while an angle between a connecting line between the feeding point 1211 and the physical center point 1212 of any two adjacent radiation elements 121 is equal to 360 °/m when the circumferential arrangement direction of the radiation elements 121 is satisfied, the connecting line between the feeding point 1211 and the physical center point 1212 of the radiation element 121 intersects at a point, and distances from the feeding point 1211 of each radiation element 121 to the point are the same, or satisfies that the connecting line between the feeding point 1211 and the physical center point 1212 of each radiation element 121 intersects to form a regular polygon corresponding to the number of the radiation elements 121, and distances from the feeding point 1211 of each radiation element 121 to midpoints of the regular polygon are the same, specifically, in the transmitting antenna 10 illustrated in fig. 1C, the number of the radiation elements 121 is four, corresponding to the circumferential arrangement direction of the radiation elements 121, an included angle between a connecting line between the feeding point 1211 of any two adjacent radiating elements 121 and the physical center point 1212 thereof is equal to 90 °, and the connecting line between the feeding point 1211 of each radiating element 121 and the physical center point 1212 thereof intersects to form a regular quadrangle, and distances from the feeding point 1211 of each radiating element 121 to a midpoint of the regular quadrangle are the same. In this way, the circular polarization form of the transmitting antenna 10 is realized in a manner of being based on phase difference feeding, and the stability of the circular polarization form of the transmitting antenna 10 is guaranteed.

It is worth mentioning that, in the embodiments of the present invention, based on the difference of the feeding structure of the radiating element 121, the position of the corresponding feeding point 1211 is defined differently, particularly in a state that the radiating element 121 adopts a feeding structure of probe feeding or microstrip feeding (including microstrip angle feeding), the feeding point 1211 corresponds to a point on the radiating element 121 at which a feeding signal (including an excitation signal) is coupled, and a state of a feeding structure in which the radiating element 121 adopts an edge feed, the feeding point 1211 corresponds to a midpoint of an edge on the radiating element 121 that accesses a feeding signal (including an excitation signal) based on a coupling effect, in the description of the present invention, in a state where the transmitting antenna 10 is set in a planar patch antenna state, the description of the feeding point 1211 does not constitute a limitation on the feeding structure of the corresponding radiating element 121.

Furthermore, in some embodiments of the present invention, when the transmitting antenna 10 is configured in a planar patch antenna configuration, the same two feeding points 1211 connected to the same phase excitation signal on the radiating element 121, the central line of the connection line of the two feeding points 1211 passes through the structural state of the physical central point 1212 of the radiating element 121, which is equivalent to the feeding point 1211 at the central point of the connection line of the two feeding points 1211 in the description of the present invention, which is not limited by the present invention.

Preferably, in the embodiments of the present invention, the radiating element 121 is further configured to be directly and/or equivalently grounded at the physical center point 1212 thereof, and particularly, the structural state of the radiating element 121 configured to be directly grounded at the physical center point 1212 thereof is formed based on the electrical connection between the physical center point 1212 thereof and the ground reference 11 of the radiating element 121, and the structural state of the radiating element 121 configured to be equivalently grounded at the physical center point 1212 thereof is formed based on the electrical connection between at least one set and/or at least one pair of grounding points on the radiating element 121 and the ground reference 11, wherein the grounding points of the same set are located at the vertices of the same regular polygon with the physical center point 1212 of the radiating element 121 as the midpoint, and the grounding points of the same set are arranged at equal angles around the physical center point 1212 of the radiating element 121 in a state of equal distance from the physical center point 1212 of the radiating element 121, the same pair of grounding points are symmetrically distributed on the radiating element 121 about the physical center point 1212 of the radiating element 121, and the connecting line segment corresponding to the same pair of grounding points is centered about the physical center point 1212 of the radiating element 121, so that the impedance of the transmitting antenna 10 is reduced by forming a zero potential point at the physical center point 1212 of the radiating element 121 and a direct and/or equivalent connection with the reference ground 11, and the frequency bandwidth of the transmitting antenna 10 is narrowed at the expense of the improvement of the precision requirement of the transmitting antenna 10 in structure and size, thereby improving the immunity of the transmitting antenna 10, reducing the precision requirement of the transmitting antenna 10, and being beneficial to reducing the production cost of the transmitting antenna 10.

Further, referring to fig. 2A and 2B of the drawings of the present disclosure, different embodiments of implementing differential feeding for a phase difference of more than 90 ° to the transmitting antenna 10 in the linear polarization direction of the transmitting antenna 10 based on a phase difference feeding mode in a state that the transmitting antenna 10 adopts a linear polarization state are illustrated, wherein the transmitting antenna 10 is disposed in a planar patch antenna state and has a reference ground 11 and a radiation source 12, and the radiation source 12 is disposed at one side of the reference ground 11 in a state spaced apart from the reference ground 11.

Corresponding to fig. 2A, the radiation source 12 is configured in a unit radiation source configuration, and corresponding to the radiation source 12, there is a single number of radiation elements 121, where the radiation element 121 has two feeding points 1211, where the two feeding points 1211 are arranged in opposite phase, and a connection direction corresponding to one of the feeding points 1211 to a physical central point 1212 of the radiation element 121 coincides with a connection direction corresponding to the other of the feeding points 1211 to the physical central point 1212 of the radiation element 121, so that the radiation element 121 has a polarization configuration of linear polarization in a state where the feeding points 1211 access an excitation signal and has the connection direction of the two feeding points 1211 as the linear polarization direction, and thus in a manner of feeding by phase difference, a differential feeding to the transmission antenna 10 is realized in the linear polarization direction of the transmission antenna 10 in a state where the two feeding points 1211 access excitation signals having a phase difference of more than 90 °, so as to reduce the loss generated by the transmitting antenna 10 based on the electric field coupling effect in the initial polarization process and reduce the minimum transmitting power extreme value of the transmitting antenna 10, thereby ensuring the stable transmission of the microwave beam in the form of the micro signal by the transmitting antenna 10 in the state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.

Preferably, in this embodiment of the present invention, the two feeding points 1211 of the radiating element 121 are arranged symmetrically with respect to the physical center point 1212 of the radiating element 121, so that in a manner of feeding by phase difference, in a state that the two feeding points 1211 of the radiating element 121 access excitation signals with phase difference approaching 180 °, a balanced differential feeding to the transmitting antenna 10 is realized in the linear polarization direction of the transmitting antenna 10, so as to further reduce the loss generated by the transmitting antenna 10 based on the electric field coupling effect during the initial polarization process, so as to reduce the minimum transmitting power extreme value of the transmitting antenna 10, thereby ensuring stable transmission of the microwave beam in the form of micro-signal by the transmitting antenna 10 in a state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.

Corresponding to fig. 2B, the radiation source 12 is configured as a binary radiation source, and has two radiation elements 121 corresponding to the radiation source 12, wherein each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are arranged in opposite phase, and a connection direction of the feeding point 1211 of one of the radiation elements 121 to a physical central point 1212 is opposite to a connection direction of the feeding point 1211 of the other radiation element 121 to the physical central point, so that the two radiation elements 121 have a polarization state of linear polarization in a state that the two feeding points 1211 access an excitation signal and have a connection direction of the two feeding points 1211 as a linear polarization direction, and thus, in a manner of phase-difference feeding, the two feeding points 1211 of the two radiation elements 121 access an excitation signal with a phase difference of more than 90 ° to realize differential feeding to the transmission antenna 10 in the linear polarization direction of the transmission antenna 10, so as to reduce the loss generated by the transmitting antenna 10 based on the electric field coupling effect in the initial polarization process and reduce the minimum transmitting power extreme value of the transmitting antenna 10, thereby ensuring the stable transmission of the microwave beam in the form of the micro signal by the transmitting antenna 10 in the state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.

Preferably, in this embodiment of the present invention, two of the radiating elements 121 are arranged in a mirror image, so as to implement a balanced differential feeding to the transmitting antenna 10 in the linear polarization direction of the transmitting antenna 10 in a manner of feeding by phase difference in a state that two of the feeding points 1211 of the radiating elements 121 access excitation signals with phase difference approaching 180 °, so as to further reduce the loss generated by the transmitting antenna 10 based on the electric field coupling effect during the initial polarization process, thereby reducing the minimum transmitting power extreme value of the transmitting antenna 10, and thus ensuring stable transmission of the microwave beam in the form of micro-signals by the transmitting antenna 10 in a state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.

It is also worth mentioning that in both embodiments of the present invention, based on the difference in the feeding structure of the radiating element 121, the position of the corresponding feeding point 1211 is defined differently, particularly in a state that the radiating element 121 adopts a feeding structure of probe feeding or microstrip feeding (including microstrip angle feeding), the feeding point 1211 corresponds to a point on the radiating element 121 at which a feeding signal (including an excitation signal) is coupled, and a state of the feeding structure in which the radiating element 121 adopts an edge feed, the feeding point 1211 corresponds to a midpoint of an edge of the radiating element 121 which is coupled into a feeding signal (including an excitation signal) based on a coupling effect, in the description of the present invention, in a state where the transmitting antenna 10 is set in a planar patch antenna state, the description of the feeding point 1211 does not constitute a limitation on the feeding structure of the corresponding radiating element 121.

Further, the minimum transmitting power extreme value of the transmitting antenna 10 is reduced based on a manner of reducing the self dielectric loss of the transmitting antenna 10, the microwave detecting device adopts a half-wave folded-back directional microwave detecting antenna as the transmitting antenna 10, reduces the self dielectric loss of the transmitting antenna 10 based on the structural characteristic that the half-wave folded-back directional microwave detecting antenna takes air as a medium to reduce the minimum transmitting power extreme value of the transmitting antenna 10, and further reduces the minimum transmitting power extreme value of the transmitting antenna 10 based on the high-gain characteristic of the half-wave folded-back directional microwave detecting antenna, so as to ensure stable transmission of the microwave beam in the form of the micro signal in a state of reducing the transmitting power of the transmitting antenna 10 to the target transmitting power.

Referring to fig. 3A and 3B of the drawings of the present invention, the structures of the half-wave folded directional microwave detecting antenna 10A in the vertical structure and the horizontal structure are illustrated respectively.

Corresponding to fig. 3A, the half-wave folded directional microwave detecting antenna 10A of the vertical structure includes a ground reference 11A, a half-wave oscillator 12A and two power feeding lines 13A, wherein the half-wave oscillator 12A has a wavelength electrical length greater than or equal to 1/2 and less than or equal to 3/4 and has two coupling sections 121A, wherein each of the coupling sections 121A has a wavelength electrical length greater than or equal to 1/6, one end of each of the coupling sections 121A is a feeding end 1211A of the coupling section 121A, and the other ends of the coupling sections 121A are two ends of the half-wave oscillator 12A, wherein a distance between the feeding ends 1211A is less than or equal to λ/4, a distance between the two ends of the half-wave oscillator 12A is greater than or equal to λ/128 and less than or equal to λ/6, so as to connect two poles of an excitation signal or two excitation poles with a phase difference to the two feeding ends 1211A of the half-wave oscillator 12A respectively A signal feeding state in which both ends of the half-wave oscillator 12A can be coupled to each other with a phase difference therebetween, where λ is a wavelength parameter corresponding to the frequency of the excitation signal; wherein the half-wave vibrator 12A is spaced from the reference ground 11A in a state where a distance between both ends thereof and the reference ground 11A is λ/128 or more and λ/6 or less; the two feeding lines 13A are electrically connected to the corresponding feeding ends 1211A, respectively, so that in a state where the two feeding lines 13A are electrically coupled to the corresponding feeding circuits to receive two poles of excitation signals or receive excitation signals with a phase difference, the feeding ends 1211A are electrically connected to the feeding lines 13A in a state where the half-wave oscillator 12A is spaced from the ground reference 11A, and the feeding ends 1211A of the half-wave oscillator 12A feed the half-wave oscillator 12A.

Corresponding to fig. 3B, the half-wave folded-back directional microwave detecting antenna 10A of the horizontal type structure includes a ground reference 11A, a half-wave oscillator 12A and a feeding line 13A, wherein the half-wave oscillator 12A has a wavelength electrical length greater than or equal to 1/2 and less than or equal to 3/4, wherein the half-wave oscillator 12A is folded back to form a state where a distance between both ends thereof is greater than or equal to λ/128 and less than or equal to λ/6, wherein the half-wave oscillator 12A has a feeding point 121A, and a wavelength electrical length between the feeding point 121A and one end of the half-wave oscillator 12A along the half-wave oscillator 12A is less than or equal to 1/6, so that both ends of the half-wave oscillator 12A can be coupled to each other with a phase difference tending to reverse phase in a state where the half-wave oscillator 12A is fed by being connected to a corresponding excitation signal at the feeding point 121A, wherein λ is a wavelength parameter corresponding to a frequency of the excitation signal; wherein the half-wave vibrator 12A is spaced from the reference ground 11A in a state where a distance between both ends thereof and the reference ground 11A is equal to or greater than λ/128, and a distance between at least one end thereof and the reference ground 11A is equal to or less than λ/6; one end of the power feeding line 13A is electrically connected to the feeding point 121A of the half-wave oscillator 12A, wherein the power feeding line 13A has a wavelength electrical length greater than or equal to 1/128 and less than or equal to 1/4, so that when the power feeding line 13A is electrically coupled to the corresponding feeding circuit at the other end thereof and receives the excitation signal, the half-wave oscillator 12A is fed at the feeding point 121A of the half-wave oscillator 12A in a state where the feeding point and the half-wave oscillator 12A are electrically connected to each other via the power feeding line 13A and spaced from the reference ground 11A.

Further, refer to the utility model discloses a figure 4A to figure 4N of the description drawings are shown, based on reducing the mode of transmitting antenna 10's self dielectric loss, the combination is in order to right transmitting antenna 10's difference feed reduces transmitting antenna 10's minimum transmit power extreme value, the utility model discloses a double feed formula difference antenna 10B is further provided, with microwave detection device adopts double feed formula difference antenna 10B regards as transmitting antenna 10's state reduces transmitting antenna 10's minimum transmit power extreme value, with reducing transmitting antenna 10's transmit power to the state guarantee micro-signal form of target transmit power the stable transmission of microwave beam.

Corresponding to fig. 4A to 4N, the dual-feed differential antenna includes a reference ground 11B and two strip-shaped elements 12B, wherein two ends of the two strip-shaped elements 12B connected to excitation signals are respectively the feeding ends 121B of the two strip-shaped elements 12B, the two strip-shaped elements 12B extend from the two feeding ends 121B in the same lateral space of the reference ground 11B and respectively have a wavelength electrical length greater than or equal to 3/16 and less than or equal to 5/16, the two strip-shaped elements 12B respectively have a coupling section 122B, one end of the coupling section 122B close to the feeding end 121B of the strip-shaped element 12B to which the coupling section belongs is a proximal end of the coupling section 122B, the two coupling sections 122B extend from the proximal end in opposite directions, so that the dual-feed differential antenna 10B is used as the transmitting antenna 10, and the two strip-shaped ends 121B of the two strip-shaped elements 12B are connected to the two strip-shaped elements 12B with a large phase difference therebetween In a state of being fed by a phase difference of 90 ° excitation signals, a polarization state tending to linear polarization is realized based on that the coupling between the two strip-shaped oscillators 12B and the reference ground 11B has a phase difference larger than 90 °, the coupling between the two coupling sections 122B is formed based on a structural form in which the two coupling sections 122B extend from the near end in opposite directions, and a common resonant frequency point is formed based on mutual coupling between the two coupling sections 122B, that is, in a state of using the double-ended feed type differential antenna 10B as the transmitting antenna 10 to access excitation signals with a phase difference larger than 90 ° at the two feeding ends 121B of the two strip-shaped oscillators 12B, differential feeding to the transmitting antenna 10 is realized in a polarization direction tending to linear polarization of the transmitting antenna 10, and a minimum transmitting power extreme value of the transmitting antenna 10 is reduced in a state of guaranteeing stable transmission of the microwave beam, and further, the stable emission of the microwave beam in the form of a micro signal is ensured in a state of reducing the emission power of the emission antenna 10 to the target emission power.

Specifically, corresponding to fig. 4A, two of the strip-shaped oscillators 12B extend from two of the feeding terminals 121B in the same lateral spatial sequence of the reference ground 11B in a direction vertically away from the reference ground 11B, and extend toward each other at a position equidistant from the reference ground 11B to form the proximal ends of two of the coupling sections 122B at this position.

Corresponding to fig. 4B, two of the strip-shaped oscillators 12B extend from two of the feeding terminals 121B in the same lateral spatial order of the reference ground 11B in a direction vertically away from the reference ground 11B, extend toward each other at a position equidistant from the reference ground 11B to form the coupling section 122B, and extend in a direction vertically close to the reference ground 11B.

Corresponding to fig. 4C to 4N, the two coupling segments 122B extend from the proximal end in the offset direction and have an offset distance of λ/256 or more and λ/6 or less, i.e. the distance from any point on one coupling segment 122B to the other coupling segment 122B is λ/256 or more and λ/6 or less, where λ is a wavelength parameter corresponding to the frequency of the excitation signal.

Specifically, corresponding to fig. 4C to 4L, the two coupling sections 122B of the two strip-shaped oscillators 12B extend from the proximal ends toward each other in a mutually parallel offset direction.

Corresponding to fig. 4C, the two strip-shaped oscillators 12B extend in the direction away from the reference ground 11B vertically in the same lateral spatial order of the reference ground 11B from the two feeding terminals 121B, and extend in opposite directions parallel to each other at the same distance from the reference ground 11B, so as to form the proximal ends of the two coupling sections 122B at the same position.

Corresponding to fig. 4D, two of the strip-shaped oscillators 12B extend in the same lateral spatial sequence of the reference ground 11B from the two feeding terminals 121B in the direction vertically away from the reference ground 11B, extend in opposite directions at positions equidistant from the reference ground 11B in parallel offset directions to form the coupling sections 122B, and extend in the direction vertically close to the reference ground 11B.

Corresponding to fig. 4E, based on the structure of the dual-feed differential antenna illustrated in fig. 4D, one of the coupling sections 122B is electrically connected to the middle of the other coupling section 122B.

Corresponding to fig. 4F, the coupling section 122B has a change in cross-sectional area in the cross-sectional direction of the strip-shaped element 12B on the basis of the structure of the double-feed differential antenna illustrated in fig. 4D.

Corresponding to fig. 4G, two of the strip-shaped oscillators 12B extend in the direction perpendicular to and away from the reference ground 11B from the two feeding terminals 121B in the same lateral spatial order of the reference ground 11B, extend in the opposite directions parallel to each other in the offset direction at the positions equidistant from the reference ground 11B, extend in the direction perpendicular to and away from the reference ground 11B, and extend in the opposite directions parallel to each other in the offset direction at the positions equidistant from the reference ground 11B to form the coupling sections 122B.

Corresponding to fig. 4H, two of the strip-shaped oscillators 12B extend from two of the feeding terminals 121B in the same lateral spatial order of the reference ground 11B in the direction vertically away from the reference ground 11B, extend back to back in the mutually parallel offset directions at positions equidistant from the reference ground 11B, extend in the direction vertically away from the reference ground 11B, extend opposite in the mutually parallel offset directions at positions equidistant from the reference ground 11B to form the coupling sections 122B, and extend in the direction vertically close to the reference ground 11B.

Corresponding to fig. 4I, two of the strip-shaped oscillators 12B extend in the direction away from the reference ground 11B vertically in the same lateral spatial order of the reference ground 11B from the two feeding terminals 121B, extend in opposite directions parallel to each other at positions equidistant from the reference ground 11B to form the coupling sections 122B, extend in the direction approaching the reference ground 11B vertically, and extend in opposite directions parallel to each other again at positions equidistant from the reference ground 11B.

Corresponding to fig. 4J, the two strip-shaped oscillators 12B extend from the two feeding terminals 121B in the same lateral spatial order of the reference ground 11B in the direction away from the reference ground 11B, extend back to the opposite direction in parallel with the offset direction at the position equidistant from the reference ground 11B, extend in the direction away from the reference ground 11B in the perpendicular direction, extend toward each other in parallel with the offset direction at the position equidistant from the reference ground 11B to form the coupling section 122B, extend in the direction approaching the reference ground 11B in the perpendicular direction, and extend toward each other again in parallel with the offset direction at the position equidistant from the reference ground 11B.

Corresponding to fig. 4K, two of the strip-shaped oscillators 12B extend in the direction perpendicular to and away from the reference ground 11B from two of the feeding terminals 121B in the same lateral spatial order of the reference ground 11B, and extend in opposite directions in mutually parallel offset directions at different distances from the reference ground 11B to form the coupling sections 122B, wherein the lengths of the two coupling sections 122B are not limited to be the same.

Corresponding to fig. 4L, the two strip-shaped oscillators 12B extend from the two feeding terminals 121B in the same lateral space of the reference ground 11B in the direction perpendicular to and away from the reference ground 11B, are bent in order at positions equidistant from the reference ground 11B to extend in opposite directions in parallel to each other in the offset direction, are bent to extend in opposite directions in parallel to each other in the offset direction to form the coupling sections 122B, and are bent again to extend in opposite directions in parallel to each other in the offset direction.

Corresponding to fig. 4M and 4N, the two coupling sections 122B of the two strip-shaped oscillators 12B extend from the near end in opposite directions with a staggered arrangement. Specifically, corresponding to fig. 4M, the two strip-shaped oscillators 12B extend in the direction perpendicular to and away from the reference ground 11B from the two feeding terminals 121B in the same lateral space sequence of the reference ground 11B, and extend oppositely in the staggered direction of the opposite offset and away from the reference ground 11B at the same distance from the reference ground 11B to form the coupling section 122B. Corresponding to fig. 4N, the two strip-shaped oscillators 12B extend in the direction vertically away from the reference ground 11B in the same lateral spatial sequence of the reference ground 11B from the two feeding terminals 121B, extend in opposite directions away from the reference ground 11B at positions equidistant from the reference ground 11B to form the coupling sections 122B, and extend in the direction vertically away from the reference ground 11B at positions equidistant from the reference ground 11B.

It is worth mentioning that the dual-feed differential antenna has various structural forms, and when the end of the coupling segment 122B close to the feeding end 121B of the strip-shaped element 12B to which the coupling segment 122B belongs is the proximal end of the coupling segment 122B, in a state where the two coupling segments 122B extend from the proximal end in opposite directions, the extending direction of each coupling segment 122B is not limited to a fixed extending direction, that is, in some embodiments of the present invention, the two coupling segments 122B extend from the proximal end in dynamic opposite directions to form the coupling segment 122B in a curved shape, and similarly, the dual-feed differential antenna 10B can be used as the transmitting antenna 10 to be fed with excitation signals having a phase difference greater than 90 ° at the two feeding ends 121B of the two strip-shaped elements 12B for phase difference feeding, and the phase difference between the two strip-shaped elements 12B and the reference ground 11B tends to be equal to 90 ° Polarized polarization form, and based on two coupling section 122B from the near-end forms two in the structural style that the opposite direction extends coupling between the coupling section 122B to based on two mutual coupling between the coupling section 122B forms common resonance frequency point, the utility model discloses do not do the restriction to this.

Furthermore, in some embodiments of the present invention, the strip-shaped oscillator 12B is disposed in a microstrip line form carried on the circuit board, which is not limited by the present invention.

It should be noted that, in a state of the transmitting antenna 10 adopting a linear polarization form, preferably in a linear polarization or a polarization direction tending to the linear polarization of the transmitting antenna 10, based on feeding the transmitting antenna 10 tending to a phase difference of 180 °, a balanced differential feeding of the transmitting antenna 10 is implemented, so as to reduce a minimum transmitting power extreme value of the transmitting antenna 10 in a state of ensuring stable transmission of the microwave beam, thereby ensuring stable transmission of the microwave beam in a micro signal form in a state of reducing the transmitting power of the transmitting antenna 10 to a target transmitting power.

Based on this, the present invention further provides a differential feed circuit, which corresponds to some embodiments of the present invention, the microwave detecting device includes the differential feed circuit, wherein corresponding to fig. 5A and 5B, the differential feed circuit is set in a discrete component form, and the circuit structures of the differential feed circuit 20 of different embodiments are respectively illustrated.

Corresponding to fig. 5A and 5B, in this embodiment of the invention, the differential feed circuit has a three-pole circuit processor (corresponding to Q1 in the figure), an inductor (corresponding to L1 in the figure), a first resistor (corresponding to R1 in the figure), a second resistor (corresponding to R2 in the figure), a third resistor (corresponding to R3 in the figure), a first capacitor (corresponding to C1 in the figure), a second capacitor (corresponding to C2 in the figure), an oscillating capacitor (corresponding to C5 in the figure) and a power connection (corresponding to Vcc in the figure) adapted to access a corresponding power source, wherein the three-pole circuit processor has a first connection corresponding to the collector of the transistor or the drain of the MOS transistor, a second connection corresponding to the base of the transistor or the gate of the MOS transistor, and a third connection corresponding to the emitter of the transistor or the source of the MOS transistor, wherein one end of the second resistor is electrically connected to the first connection terminal of the three-pole circuit handler, the other end of the second resistor is connected to the power connection terminal via the inductor, and is grounded via the first capacitor, wherein one end of the third resistor is electrically connected to the third connection terminal of the three-pole circuit handler, the other end of the third resistor is grounded, wherein one end of the oscillation capacitor is electrically connected to the second connection terminal of the three-pole circuit handler, the other end of the oscillation capacitor is grounded, wherein one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit handler, the other end of the first resistor is electrically connected between the inductor and the second resistor corresponding to fig. 5A, or is electrically connected to the power connection terminal corresponding to fig. 5B, the two ends of the second capacitor are electrically connected to the first connection end and the third connection end of the three-pole circuit processor, respectively, wherein the second resistor and the third resistor are set to have equal resistance values, so that the excitation signal is output at the two ends of the second capacitor in a balanced differential signal form with a phase difference of approximately 180 degrees in a state that the differential feed circuit is connected to a corresponding power supply at the power supply connection end, and thus, the phase difference feed of approximately 180 degrees to the transmitting antenna is realized.

It is worth mentioning that the inductor functions to isolate ac and direct current to isolate the high frequency ac excitation signal from the power supply voltage signal, the first capacitor is a decoupling capacitor, can prevent the circuit from generating parasitic oscillation caused by a positive feedback path formed by a power supply and prevent the current fluctuation generated in the power supply circuit by the current size change of the front circuit and the back circuit from influencing the normal operation of the circuit, wherein, since one end of the first resistor is electrically connected to the second connection terminal of the three-pole circuit processor to provide a divided current to the second connection terminal of the three-pole circuit processor, the inductor does not participate in the voltage division, therefore, the other end of the first resistor may be electrically connected between the inductor and the second resistor corresponding to fig. 5A, or may be electrically connected to the power connection terminal corresponding to fig. 5B.

Further, in the two embodiments of the present invention, the differential feeding circuit further has a third capacitor (corresponding to C3 in the figure) and a fourth capacitor (corresponding to C4 in the figure), wherein the third capacitor and the fourth capacitor are electrically connected to two ends of the second capacitor respectively, so as to output the excitation signal in a balanced differential signal form with a phase difference approaching 180 ° through the third capacitor and the fourth capacitor, thereby realizing phase difference feeding of the transmitting antenna approaching 180 °.

It is worth mentioning that, corresponding to the differential feeding circuit illustrated in fig. 5A and 5B, in other embodiments of the present invention, the inductance may not be set, corresponding to one end of the second resistor electrically connected to the first connection end of the three-pole circuit processor, the other end of the second resistor electrically connected to the power connection end, and via the first capacitor grounded, one end of the first resistor electrically connected to the second connection end of the three-pole circuit processor, and the other end of the first resistor electrically connected to the power connection end.

Furthermore, it is worth mentioning that, in the embodiments of the present invention, the first capacitor, the second capacitor, the third capacitor, the fourth capacitor and the oscillating capacitor can be set in the actual circuit structure in the form of a microstrip distributed capacitor, which is not limited by the present invention.

Referring further to fig. 6 of the drawings accompanying the present application, a partial circuit structure of a differential feed circuit according to an embodiment of the present invention is illustrated, in which the differential feed circuit is configured in an integrated circuit form and outputs the excitation signal in a differential oscillation circuit in a balanced differential signal form with a phase difference of approximately 180 °.

Specifically, the differential oscillation circuit has two N-channel MOS transistors (corresponding to Q1 and Q2 in the figure), two P-channel MOS transistors (corresponding to Q3 and Q4 in the figure), an oscillation inductor (corresponding to L in the figure) and an oscillation capacitor (corresponding to C in the figure), wherein the sources of the two N-channel MOS transistors are electrically connected, the sources of the two P-channel MOS transistors are electrically connected, the drains of the two N-channel MOS transistors are electrically connected to the drains of different P-channel MOS transistors, respectively, so as to form a sequential connection relationship that the drain of one of the N-channel MOS transistors is electrically connected to the drain of one of the P-channel MOS transistors, the source of the P-channel MOS transistor is electrically connected to the source of the other P-channel MOS transistor, the drain of the other P-channel MOS transistor is electrically connected to the drain of the other N-channel MOS transistor, and the source of the other N-channel MOS transistor is electrically connected to the source of the previous N-channel MOS transistor, wherein, in the two N-channel MOS transistors, the gate of any one of the N-channel MOS transistors is electrically connected to the drain of the other N-channel MOS transistor, wherein, in the two P-channel MOS transistors, the gate of any one of the P-channel MOS transistors is electrically connected to the drain of the other P-channel MOS transistor, wherein, the two ends of the oscillation inductor are electrically connected to the drains of the different P-channel MOS transistors, respectively, and the two ends of the oscillation capacitor are electrically connected to the drains of the different P-channel MOS transistors and connected in parallel with the oscillation inductor, so that the oscillation and frequency selection are formed by the parallel resonant circuit composed of the oscillation inductor and the oscillation capacitor, and the two ends of the oscillation inductor and the two ends of the oscillation capacitor form electric signals with equal magnitude and opposite directions, so that one of the N-channel MOS transistors and the P-channel MOS transistor electrically connected to the gate of the N-channel MOS transistor can be conducted at the same time, the other N-channel MOS tube and the P-channel MOS tube electrically connected with the grid electrode of the N-channel MOS tube can be conducted at the same time at the other moment, so that the excitation signal is output at two ends of the oscillation inductor in a balanced differential signal form with a phase difference of 180 degrees.

With further reference to fig. 7A to 7C of the drawings accompanying the present invention, the differential feed circuit is configured in an integrated circuit form and outputs the state of the excitation signal in a balanced differential signal form with a phase difference approaching 180 ° in the differential oscillation circuit, and the structural block diagram of the microwave detection apparatus according to the different embodiments of the present invention is illustrated.

Wherein the differential feeding circuit comprises a low dropout linear regulator (corresponding to the internal LDO in the figure), the differential oscillating circuit, an oscillator (corresponding to the Osc in the figure), a phase-locked loop (corresponding to the PLL in the figure) and a logic control unit, wherein the low dropout linear regulator provides a constant voltage for the differential oscillating circuit in a powered state, wherein the oscillator is configured such that the logic control unit provides a basic clock signal and is externally configured with a quartz crystal oscillator or is integrally configured with an internal oscillating circuit, wherein the logic control unit is configured with a DSP, a MCU or a RAM and is electrically connected to the oscillating inductor of the differential oscillating circuit, wherein the phase-locked loop is electrically connected between the logic control unit and the differential oscillating circuit in a state of being externally configured or integrated with the logic control unit, based on the feedback of the excitation signal output by the differential oscillation circuit by the logic control unit, the frequency/phase of the excitation signal output by the differential oscillation circuit in a balanced differential signal form with a 180-degree difference at two ends of the oscillation inductor is calibrated, so that the stable output of the excitation signal in the balanced differential signal form by the differential feed circuit is ensured.

It is worth mentioning that, for the purpose of reducing the cost of the differential feeding circuit, in some embodiments of the present invention, the phase-locked loop may not be configured, that is, the logic control unit is electrically connected to the differential oscillating circuit, so as to control the stability of the frequency/phase of the excitation signal outputted from the differential oscillating circuit at two ends of the oscillating inductor in a balanced differential signal form with a 180 ° difference based on the feedback of the excitation signal outputted from the differential oscillating circuit.

Further, in the embodiments of the present invention, the differential feeding circuit further includes two amplifiers (corresponding to PA1 and PA2 directly led out from the differential oscillating circuit in the figure) for amplifying the excitation signal outputted from the differential oscillating circuit in a balanced differential signal form, wherein the logic control unit is electrically connected to the oscillating inductor of the differential oscillating circuit in a state of being electrically connected to at least one of the amplifiers to receive the feedback of the excitation signal outputted from the differential oscillating circuit by the amplifiers.

It is worth mentioning that in a state where the microwave beam is in a weak signal form due to the reduction of the transmitting power of the transmitting antenna, although the above-mentioned series of advantages are exhibited, since the strength of the corresponding echo signal is simultaneously reduced, in a state where there is ambient electromagnetic interference in the corresponding target detection space, the corresponding doppler intermediate frequency signal is more likely to be interfered by ambient electromagnetic radiation, and it is difficult to accurately feed back the motion characteristics corresponding to the human body movement motion, the inching motion, and the breathing and heartbeat motion. Based on this, correspond to the utility model discloses a figure 7A of the specification attached drawing is illustrated to figure 7C microwave detection device, corresponding microwave detection device's detection method further includes the method step of improving echo signal's precision, with echo signal's intensity is based on the state that the transmitting power of transmitting antenna (TX in the corresponding map) was reduced, based on the improvement of echo signal's precision, guarantees microwave detection device to the accuracy and the stability of the detection of the activity characteristics corresponding to human body movement, fine motion, and breathing and heartbeat action.

In particular, the method step of improving the accuracy of the echo signal includes a step of accessing the echo signal in a balanced differential signal form from a receiving antenna (corresponding to RX in the figure) of the microwave detection device, so that the electromagnetic interference in the environment exists in a common-mode interference form in the echo signal, and thus can be suppressed during the reception and transmission of the echo signal in a differential signal form, and subsequently, corresponding to fig. 7B and 7C, the doppler intermediate frequency signal in a balanced differential signal form is output based on a mixing processing step of the echo signal in a balanced differential signal form, and the doppler intermediate frequency signal in a single-ended signal form is output based on a differential-to-single-ended processing step of the doppler intermediate frequency signal in a balanced differential signal form, so as to perform a mixing processing step of the echo signal in a balanced differential signal form and/or a differential-to-single-ended processing step of the doppler intermediate frequency signal in a balanced differential signal form Further inhibiting the common-mode interference in the echo signal and/or the doppler intermediate frequency signal in the balanced differential signal form by the differential-to-single-ended processing step, for example, utilizing the characteristic of the common-mode interference that is in equal-amplitude asymmetry in the signal in the differential signal form with symmetric characteristics, and outputting the doppler intermediate frequency signal in the single-ended signal form free from environmental electromagnetic interference through the cancellation effect in the symmetry conversion and superposition processes of the amplitude-asymmetric common-mode interference by the differential-to-single-ended processing step based on the difference finding principle, so as to improve the feedback accuracy of the doppler intermediate frequency signal on the activity characteristics corresponding to the human body movement action, the micromotion action, and the respiration and heartbeat action; or in the subsequent, corresponding to fig. 7A, outputting the echo signal in the form of a single-ended signal free from environmental electromagnetic interference based on further suppressing common-mode interference in the echo signal in the form of a balanced differential signal by the step of processing the echo signal in the form of a differential-to-single-ended signal in the form of a balanced differential signal, and outputting the doppler intermediate frequency signal free from environmental electromagnetic interference based on the step of processing the echo signal in the form of a single-ended signal free from environmental electromagnetic interference by the step of mixing the echo signal in the form of a single-ended signal free from environmental electromagnetic interference, thereby improving the feedback accuracy of the doppler intermediate frequency signal on activity characteristics corresponding to human body movement, micromotion, and respiration and heartbeat, corresponding to the step of accessing the echo signal in the form of a balanced differential signal by the receiving antenna of the microwave detecting device based on the micro-transmitting power and the processing system of a balanced differential signal constructed in the subsequent steps, the microwave detection device for guaranteeing the micro-transmitting power can detect the activity characteristics corresponding to the movement action, the micro-movement action, the respiration action and the heartbeat action of the human body, and can ensure the accuracy and the stability of the detection.

It is worth mentioning that, since the echo signal is in a balanced differential signal form when accessed from the receiving antenna, the electromagnetic radiation interference in the environment exists in a common mode interference form in the echo signal, and can thus be suppressed during reception and transmission of said echo signals in the form of differential signals, namely, the echo signal contains a signal corresponding to a reflected echo formed by the reflection of the microwave beam emitted by the transmitting antenna by a corresponding object and an electromagnetic radiation interference signal existing in a common mode interference form, thus irrespective of whether it corresponds to figures 7B and 7C to output said doppler intermediate frequency signal in the form of a balanced differential signal in a subsequent processing step based on mixing said echo signal in the form of a balanced differential signal, and outputting the Doppler intermediate frequency signal in a single-ended signal form based on a differential-to-single-ended processing step of the Doppler intermediate frequency signal in a balanced differential signal form; or the echo signal in single-ended signal form, which is output in a subsequent differential-to-single-ended processing step based on the echo signal in balanced differential signal form, and the doppler intermediate frequency signal, which is output in a subsequent differential-to-single-ended processing step based on the echo signal in balanced differential signal form, wherein further suppression of common-mode interference in the echo signal and/or the doppler intermediate frequency signal in balanced differential signal form, which is based on the mixing processing step based on the echo signal in balanced differential signal form and/or the differential-to-single-ended processing step based on the doppler intermediate frequency signal in balanced differential signal form, which corresponds to fig. 7B and fig. 7C, or further suppression of common-mode interference in the echo signal in balanced differential signal form, which corresponds to fig. 7A, which is based on the differential-to-single-ended processing step based on the echo signal in balanced differential signal form, the Doppler intermediate frequency signal which is finally output is free from environmental electromagnetic interference, so that the feedback accuracy of the Doppler intermediate frequency signal to the activity characteristics corresponding to the movement action, the micro-movement action and the respiration and heartbeat actions of the human body can be improved, a processing system of the balance differential signal which is established in the step of the echo signal and the subsequent step is correspondingly accessed on the basis of the receiving antenna of the microwave detection device with micro-transmitting power, and the detection range and the detection accuracy and the detection stability of the microwave detection device with micro-transmitting power to the activity characteristics corresponding to the movement action, the micro-movement action and the respiration and heartbeat actions of the human body are guaranteed.

Correspondingly, the microwave detecting device further comprises a mixing circuit and a differential-to-single-ended circuit, wherein the mixing circuit is electrically connected between the differential oscillating circuit and the receiving antenna to output the doppler intermediate frequency signal in a single-ended signal form corresponding to the frequency/phase difference between the excitation signal and the echo signal based on the mixing process of the excitation signal and the echo signal in a single-ended signal form corresponding to fig. 7A, or output the doppler intermediate frequency signal in a differential signal form corresponding to the frequency/phase difference between the excitation signal and the echo signal based on the mixing process of the excitation signal and the echo signal in a balanced differential signal form corresponding to fig. 7B and 7C; accordingly, the differential to single-ended circuit is disposed between the receive antenna and the mixer circuit corresponding to FIG. 7A, outputting the echo signals in a single-ended signal form free from electromagnetic environment interference to the mixer circuit by performing differential-to-single-ended processing on the echo signals in a balanced differential signal form based on a difference-finding principle, or is arranged corresponding to fig. 7B and 7C to be electrically connected to the mixing circuit to receive the doppler intermediate frequency signal in differential signal form outputted from the mixing circuit and perform differential-to-single-ended processing on the doppler intermediate frequency signal in differential signal form based on the difference finding principle to output the doppler intermediate frequency signal in single-ended signal form free from electromagnetic environment interference, therefore, the feedback accuracy of the Doppler intermediate frequency signal to the activity characteristics corresponding to the human body movement action, the micro-motion action, the respiration action and the heartbeat action is improved.

Further, corresponding to fig. 7A, in a state where the mixing circuit is configured to output the doppler intermediate frequency signal in a single-ended signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal based on the mixing process of the echo signal in the excitation signal and the single-ended signal form, the microwave detecting apparatus optionally includes another differential to single-ended circuit, wherein the differential to single-ended circuit is configured between the differential oscillating circuit and the mixing circuit to output the excitation signal in a single-ended signal form free from electromagnetic environment interference to the mixing circuit based on the differential to single-ended process of the excitation signal in a differential signal form, so as to facilitate an improvement in accuracy of the doppler intermediate frequency signal in a single-ended signal form output from the mixing circuit, correspondingly secure the doppler intermediate frequency signal pair with a human body moving motion, Fine motion, and feedback accuracy of activity characteristics corresponding to respiration and heartbeat. That is, in a state where the differential-to-single-ended circuit is not set, the excitation signal in a single-ended signal form may be outputted to the mixer circuit by selecting a mode in which the excitation signal in a single-ended signal form is directly extracted from the differential oscillator circuit, which is not limited by the present invention.

It is worth mentioning that, based on the difference of the usage/transmission path of the signals extracted from the differential oscillating circuit, in some documents in the art, the names of the signals extracted from the corresponding oscillating circuit may be different, for example, in some documents in the art, the transmission object of the signals extracted from the corresponding oscillating circuit is an antenna for feeding the corresponding antenna is called an excitation signal, and the transmission object of the extracted signals is a mixer is called a local oscillation signal, the invention is not limited thereto, that is, in the description of the invention, the excitation signal extracted from the differential oscillating circuit and transmitted to the transmitting antenna and the excitation signal extracted from the differential oscillating circuit and transmitted to the mixer circuit are given the same names in order to facilitate understanding that the excitation signals are provided by the differential oscillating circuit, the designation of the excitation signal itself does not constitute a limitation of its use/transmission path.

Corresponding to fig. 7B and 7C, in a state where the mixing circuit is set to output the doppler intermediate frequency signal of a balanced differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal of a balanced differential signal form based on the mixing processing of the excitation signal and the echo signal of a balanced differential signal form, the mixer circuit illustrated in figure 7C may alternatively correspond to the integrated version of figure 7B arranged as two mixer circuits adapted for mixing processing of the excitation signal and the echo signal in a single ended signal form, outputting the Doppler intermediate frequency signal in a differential signal form corresponding to a frequency/phase difference between the excitation signal and the echo signal with a mixing process of the excitation signal and the echo signal based on the differential signal form by the mixing circuit.

It is understood that in some embodiments of the present invention, the mixing circuit may be optionally implemented as an integrated form of the mixing circuit and the differential to single-ended circuit corresponding to fig. 7A to 7C, and the mixing circuit may be configured to output the doppler intermediate frequency signal in a single-ended signal form in a state of accessing the echo signal and the excitation signal in a balanced differential signal form, including but not limited to outputting the doppler intermediate frequency signal in a single-ended signal form corresponding to fig. 7A based on a differential to single-ended processing of the echo signal in a balanced differential signal form and a mixing processing of the echo signal and the excitation signal in a single-ended signal form, or outputting the doppler intermediate frequency signal in a single-ended signal form based on a mixing processing of the echo signal and the excitation signal in a balanced differential signal form and a mixing processing of the single-ended doppler intermediate frequency signal in a balanced differential signal form corresponding to fig. 7B and 7C The doppler intermediate frequency signal is not limited in this regard.

Specifically, the signal based on the balanced differential signal form has two signals with equal amplitude and opposite phase relative to the reference potential and has a symmetrical characteristic, in some embodiments of the present invention, the differential to single-ended circuit is configured to perform the inverse phase processing on one of the two signals based on the signal with the differential signal form, and output the signal with the single-ended signal form after being superimposed with the other signal, so that the common-mode interference information in the signal with the balanced differential signal form can be suppressed or even eliminated by using the characteristic that the common-mode interference is equal amplitude and asymmetrical in the signal with the symmetrical characteristic in the signal with the differential signal form based on the differential to single-ended processing on the signal with the balanced differential signal form by the differential to single-ended circuit.

In these embodiments of the present invention, when the mixing circuit is implemented in a fully integrated manner corresponding to the mixing circuit and the differential-to-single-ended circuit in fig. 7A to 7C to implement that the mixing circuit outputs the doppler intermediate frequency signal in a single-ended signal form in a state of accessing the echo signal and the excitation signal in a balanced differential signal form, the mixing circuit may be further implemented to output the doppler intermediate frequency signal in a single-ended signal form sequentially based on an inversion process on one of two signals of the echo signal in a balanced differential signal form, a mixing process on the two signals respectively, and a superposition process on the two doppler intermediate frequency signals output by the mixing process, so as to suppress or even eliminate interference information generated by corresponding common-mode interference.

In other embodiments of the present invention, when the mixing circuit is implemented as a partially integrated form corresponding to the mixing circuit and the differential-to-single-ended circuit in fig. 7A to 7C, so as to output the doppler intermediate frequency signal in a single-ended signal form by the mixing circuit in a state of accessing the echo signal and the excitation signal in a balanced differential signal form, the mixing circuit may be implemented as a processing unit sequentially outputting the doppler intermediate frequency signal in a single-ended signal form based on an inversion process of one of two signals of the echo signal in a balanced differential signal form, and a processing unit respectively outputting the doppler intermediate frequency signal in a two-way single-ended signal form based on a mixing process of two signals, so as to be able to suppress or even eliminate interference information generated by corresponding common-mode interference based on a superposition process of the two doppler intermediate frequency signals, or generate interference information with an equal absolute value in a time domain relative to a reference potential value based on a digital conversion of the two doppler intermediate frequency signals And the two groups of numerical data with the same numerical value change trend are expressed by the digitalized characteristics of two groups of numerical values with the same absolute value and the opposite numerical value change trends respectively added to the two groups of numerical data on the time domain according to the common-mode interference, and the interference information generated based on the common-mode interference is inhibited or even eliminated by an algorithm for summing the two groups of numerical data or an algorithm for filtering the numerical data which do not conform to the same change trend through the comparison of the two groups of numerical data, so that the digitalized form of the Doppler intermediate frequency signal free from the electromagnetic environment interference is correspondingly obtained, and the feedback accuracy of the Doppler intermediate frequency signal on the activity characteristics corresponding to the movement action, the inching action and the respiration and heartbeat action of a human body is improved. Or the difference component generated based on the common-mode interference is eliminated through the difference or comparison of the two sets of numerical data after the corresponding operation processing, for example, the two sets of numerical data are independently processed based on the corresponding operation to obtain two sets of control data, and the difference component generated based on the common-mode interference is eliminated through the subsequent comparison and analysis based on the two sets of control data, so that an accurate control result is output.

It is worth mentioning that in some embodiments of the present invention, the step of processing the echo signal and/or the doppler intermediate frequency signal in the form of balanced differential signal is further included, for example, on the basis of the circuit structure illustrated in fig. 7A, a corresponding amplifying circuit adapted to amplify the signal in the form of differential signal is further disposed between the receiving antenna and the corresponding differential-to-single-ended circuit, so as to amplify and output the echo signal in the form of balanced differential signal to the differential-to-single-ended circuit, or on the basis of the circuit structures illustrated in fig. 7B and 7C, a corresponding amplifying circuit adapted to amplify the signal in the form of differential signal is further disposed between the receiving antenna and the frequency mixing circuit and/or between the frequency mixing circuit and the differential-to-single-ended circuit, so as to amplify and output the echo signal in the form of balanced differential signal to the frequency mixing circuit and/or amplify and output the signal in the form of differential signal The present invention is not limited to this, and preferably, the differential to single-ended circuit is configured with a circuit having electrical characteristics for amplifying signals in differential signal form, such as a circuit of a meter amplifier, so as to simultaneously implement amplification and single-ended conversion of signals in differential signal form, and is simple and easy.

In particular, in some embodiments of the present invention, the processing step of amplifying the echo signal and/or the doppler intermediate frequency signal in single-ended signal form is further included, for example, on the basis of the circuit structure illustrated in fig. 7A, a corresponding amplifying circuit adapted to amplify the signal in single-ended signal form is further disposed between the differential-to-single-ended circuit and the mixing circuit and/or at the output end of the mixing circuit, so as to amplify the echo signal in single-ended signal form to the mixing circuit and/or amplify the doppler intermediate frequency signal in single-ended signal form, or on the basis of the circuit structures illustrated in fig. 7B and 7C, a corresponding amplifying circuit adapted to amplify the signal in single-ended signal form is further disposed at the output end of the differential-to-single-ended circuit, so as to amplify the doppler intermediate frequency signal in single-ended signal form, the utility model discloses do not limit to this.

Further, in some embodiments of the present invention, the step of accessing the echo signal from the receiving antenna of the microwave detecting device to the balanced differential signal form includes accessing the echo signal of the balanced differential signal form based on a phase shifting step of the echo signal accessed from one of the receiving feeding points (ends) in a state where the two receiving feeding points (ends) of the receiving antenna are orthogonally arranged, so as to ensure isolation between the echo signals accessed from the two receiving feeding points (ends) of the receiving antenna based on the orthogonal form between the two receiving feeding points (ends) of the receiving antenna, and correspondingly ensure accuracy of the echo signal of the balanced differential signal form accessed based on the phase shifting step of the echo signal accessed from one of the receiving feeding points (ends).

Corresponding refer to the utility model discloses a figure 8A to figure 8D of the specification attached drawing show two receipt feed points (end) of receiving antenna are based on the phase shift step of the echo signal of receiving one of them feed point (end) access and insert balanced difference signal form echo signal, different embodiments the structural style of receiving antenna is illustrated, wherein based on the receiving and dispatching reciprocity characteristic of antenna, to the nomenclature of the reference numeral and the corresponding structure of receiving antenna follows in the description and the figure of the utility model the nomenclature of the reference numeral and the corresponding structure of transmitting antenna.

In both embodiments of the present invention, the receiving antenna 10 is exemplified by a planar patch antenna configuration having a reference ground 11 and a radiation source 12, corresponding to fig. 8A and 8B, wherein the radiation source 12 is disposed on a side of the reference ground 11 in a spaced state from the reference ground 11.

Specifically, corresponding to fig. 8A, the radiation source 12 is configured as a unit radiation source, and the radiation source 12 has a single number of radiation elements 121, wherein the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are orthogonally arranged, connecting lines between the two feeding points 1211 and a physical central point 1212 of the radiation element 121 are perpendicular to each other, one of the feeding points 1211 is electrically connected with a phase shifter, such as a microstrip line configured with a corresponding electrical length, so as to output the echo signal in a balanced differential signal form between one end of the phase shifter far from the feeding point 1211 and the other feeding point 1211 based on a phase shifting process of the phase shifter on the echo signal accessed from the feeding point 1211.

Corresponding to fig. 8B, the radiation source 12 is configured as a binary radiation source, and the radiation source 12 has two radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are orthogonally arranged, a connection direction of the feeding point 1211 to the physical central point 1212 of one of the radiation elements 121 is perpendicular to a connection direction of the feeding point 1211 to the physical central point 1212 of the other radiation element 121, and one of the feeding points 1211 is electrically connected with a phase shifter, such as a microstrip line configured with a corresponding electrical length, so as to output the echo signals in a balanced differential signal form between one end of the phase shifter far from the feeding point 1211 and the other feeding point 1211 based on a phase shifting process of the phase shifter on the echo signals accessed from the feeding point 1211.

Corresponding to fig. 8C and 8D, in both embodiments of the present invention, the receiving antenna is exemplified by the half-wave folded directional microwave detecting antenna 10A of the orthogonal polarization.

Specifically, corresponding to fig. 8C, the half-wave folded-back directional microwave detecting antenna 10A of the horizontal structure with orthogonal polarization of the receiving antenna is disposed, the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are orthogonally arranged, the extending direction of the half-wave folded-back directional microwave detecting antenna 10A is perpendicular to the height direction of the reference ground 11A, the extending direction of the two half-wave oscillators 12A is perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A, the feeding point 121A of one half-wave oscillator 12A is connected with a phase shifter via the feeding line 13A, such as a microstrip line disposed with a corresponding electrical length, to perform phase shift processing on the echo signal received from the feeding point 121A based on the phase shifter, the echo signal in the form of a balanced differential signal is output between one end of the phase shifter, which is far from the feeding point 121A, and the other feeding point 121A.

Corresponding to fig. 8D, the half-wave folded-back directional microwave detecting antenna 10A of the receiving antenna in the orthogonally polarized vertical structure is disposed, the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are orthogonally arranged, the extending directions of the two half-wave oscillators 12A in the vertical direction perpendicular to the reference ground 11A direction as the height direction of the half-wave folded-back directional microwave detecting antenna 10A are perpendicular to each other, the extending directions of the two half-wave oscillators 12A in the vertical direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A are perpendicular to each other, one of the feeding terminals 1211A of one of the half-wave oscillators 12A is connected with a phase shifter such as a microstrip line disposed with a corresponding electrical length based on the phase shift processing of the echo signal inputted from the feeding terminal 1211A by the phase shifter, the echo signal in a balanced differential signal form is output between one end of the phase shifter, which is far away from the feeding end 1211A, and one feeding end 1211A of the other half-wave oscillator 12A.

It is worth mentioning that in some preferred embodiments of the present invention, in the step of accessing the echo signal in the form of balanced differential signal from the receiving antenna of the microwave detecting device, two receiving feeding points of the receiving antenna are arranged in opposite phase to directly access the echo signal in the form of balanced differential signal from the two receiving feeding points.

Referring to fig. 9A to 9E of the drawings of the present invention, in a state where two receiving feeding points (ends) of the receiving antenna are arranged in opposite phases, the echo signals in a balanced differential signal form are directly accessed from the two receiving feeding points (ends), and the structural form of the receiving antenna in different embodiments is illustrated.

In both embodiments of the present invention, the receiving antenna 10 is exemplified by a planar patch antenna configuration having a reference ground 11 and a radiation source 12, corresponding to fig. 9A and 9B, wherein the radiation source 12 is disposed on a side of the reference ground 11 in a spaced state from the reference ground 11.

Specifically, corresponding to fig. 9A, the radiation source 12 is configured in a unit radiation source form, and the radiation source 12 has a single number of radiation elements 121, wherein the radiation element 121 has two feeding points 1211, wherein the two feeding points 1211 are arranged in opposite phases, and a connection direction from one of the feeding points 1211 to a physical center point 1212 of the radiation element 121 coincides with a connection direction from the other feeding point 1211 to the physical center point 1212 of the radiation element 121, so as to output the echo signals in a balanced differential signal form at the two feeding points 1211 based on a structural state that the two feeding points 1211 are arranged in opposite phases.

Preferably, in this embodiment of the present invention, the two feeding points 1211 of the radiating element 121 are arranged symmetrically with respect to the physical center point 1212 of the radiating element 121, so that the echo signals in a balanced differential signal form are output at the two feeding points 1211 with a phase difference of about 180 ° based on the two feeding points 1211 arranged in opposite phases and the equidistant configuration from the two feeding points 1211 to the physical center point 1212 of the radiating element 121.

Corresponding to fig. 9B, the radiation source 12 is configured in a binary radiation source form, and the radiation source 12 has two radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, wherein the two radiation elements 121 are arranged in opposite phases, and a connection line direction from the feeding point 1211 to a physical central point 1212 of one of the radiation elements 121 is opposite to a connection line direction from the feeding point 1211 to a physical central point of the other radiation element 121, so that the two feeding points 1211 output the echo signals in a balanced differential signal form based on a structural state that the two radiation elements 121 are arranged in opposite phases.

Preferably, in this embodiment of the present invention, two of the radiation elements 121 are arranged in a mirror image, so that the two feed points 1211 output the echo signals with a phase difference of about 180 ° and a balanced differential signal form at the two feed points 1211 based on the structure state that the two radiation elements 121 are arranged in opposite phases and the two feed points 1211 are equidistant from the physical center point 1212 of the radiation element 121 to which the two feed points belong.

Corresponding to fig. 9C and 9D, in the two embodiments of the present invention, the receiving antenna is exemplified by the half-wave folded directional microwave detecting antenna 10A polarized in reverse phase.

Specifically, corresponding to fig. 9C, the half-wave folded-back directional microwave detecting antenna 10A of the receiving antenna in a reverse-phase polarized horizontal structure is disposed, the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are arranged in reverse phase, and the two half-wave oscillators 12A are arranged in reverse phase corresponding to the direction perpendicular to the reference ground 11A as the height direction of the half-wave folded-back directional microwave detecting antenna 10A, and the extending direction of the two half-wave oscillators 12A from the feeding point 121A in the direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A is reversed, so as to output the echo signals in a balanced differential signal form at the two feeding points 121A based on the structural state that the two half-wave oscillators 12A are arranged in reverse phase.

Corresponding to fig. 9D, the half-wave folded-back directional microwave detecting antenna 10A of the receiving antenna in a vertical structure with reverse polarization is disposed, the half-wave elements 12A corresponding to the half-wave folded-back directional microwave detecting antenna 10A are arranged in reverse phase, i.e., in a direction perpendicular to the reference ground 11A as a height direction of the half-wave folded-back directional microwave detecting antenna 10A, the half-wave elements 12A are reversed from the two feeding terminals 1211A in an extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A, so as to output the echo signals in a balanced differential signal form at the two feeding terminals 1211A based on a structural state that the half-wave elements 12A are arranged in reverse phase.

Corresponding to fig. 9E, in this embodiment of the present invention, the receiving antenna is exemplified by the double-ended feeding differential antenna 10B, so that two coupling sections 122B extending from the near end in opposite directions based on two strip-shaped oscillators 12B can be coupled to each other to form a common structural characteristic of resonant frequency points, forming two strip-shaped oscillators 12B in a structural state of being arranged in opposite phases in polarization directions tending to linear polarization, and thus, when the double-ended feeding differential antenna 10B is used as a receiving antenna, the two feeding ends 121B directly output the echo signals in a balanced differential signal form.

It is worth mentioning that in other embodiments of the present invention, in a state that the microwave beam is in a weak signal form due to the transmitting power of the transmitting antenna being reduced to the target transmitting power, the doppler intermediate frequency signal pair is increased to move or slightly move with respect to the human body by increasing the strength of the echo signal, and the accuracy and stability of the feedback of the activity characteristics corresponding to the breathing and heartbeat movements, the respective transmit antennas allow to be set in an orthogonal polarization configuration, the radiation source is orthogonally arranged in a binary radiation source configuration corresponding to a state in which the transmitting antenna is arranged in a planar patch antenna configuration, namely, the radiation source is provided with two radiation elements, and the direction of a connecting line from the feeding point to a physical central point of one radiation element is opposite to and vertical to the direction of a connecting line from the feeding point to a physical central point of the other radiation element; and in the state that the transmitting antenna is set by the half-wave folded-back directional microwave detection antenna, the half-wave folded-back directional microwave detection antenna is set in an orthogonal polarization state, namely, the half-wave folded-back directional microwave detection antenna comprises two half-wave oscillators, wherein the two half-wave oscillators are orthogonally arranged, and correspondingly, the direction perpendicular to the reference ground direction is taken as the height direction of the half-wave folded-back directional microwave detection antenna, and the extending directions of the two half-wave oscillators perpendicular to the height direction of the half-wave folded-back directional microwave detection antenna are mutually perpendicular.

It should be noted that, in some embodiments of the present invention, different combinations of the transmitting antenna and the receiving antenna of the above embodiments can be integrally disposed in a form of separate transceiving or a form of combining transceiving in a structural form sharing the reference ground, thereby facilitating the miniaturization design of the microwave detecting apparatus.

For example, referring to fig. 10A to 10J of the drawings of the present invention, based on different combinations of the transmitting antenna and the receiving antenna according to the above embodiments, the transmitting antenna and the receiving antenna that are integrally provided in a transmission/reception separated form or a transmission/reception integrated form in a structural form that shares the reference ground are illustrated.

Corresponding to fig. 10A, based on the combination of the transmitting antenna illustrated in fig. 1A and the receiving antenna illustrated in fig. 8A, in the structural configuration that the transmitting antenna and the receiving antenna share the ground reference 11 and the radiation source 12, the integral structure of the transmitting antenna and the receiving antenna is illustrated, wherein the integral structure of the transmitting antenna and the receiving antenna has the ground reference 11 and the radiation source 12, wherein the radiation source 12 is disposed on one side of the ground reference 11 in a state of being spaced apart from the ground reference 11, wherein the radiation source 12 is disposed in a unit radiation source configuration, corresponding to the radiation source 12, having a single number of radiation elements 121, wherein the radiation elements 121 have four feeding points 1211, wherein an included angle between connecting lines between any two adjacent feeding points 1211 and a physical central point 1212 of the radiation element 121 in a direction around the physical central point 1212 of the radiation element 121 is equal to 90 °, the circularly polarized form of the transmitting antenna 10 is realized in a state of sequentially accessing excitation signals different by 90 ° to two adjacent ones of the feed points 1211 in a direction around a physical center point 1212 of the radiating element 121 by phase-difference feeding, and the echo signals in a form of balanced differential signals are output between one of the two feed points 1211 and an end of the phase shifter distant from the other feed point 1211 based on phase-shifting processing of the echo signals accessed from the one feed point 1211 by the phase shifter in a manner of accessing the phase shifter at the one feed point 1211 of the other two feed points 1211 by phase-difference feeding, so as to form an integral structure of the transmitting antenna and the receiving antenna in a transceiving separated form.

Corresponding to fig. 10B and 10C, based on the combination of the transmitting antenna illustrated in fig. 2A and the receiving antenna illustrated in fig. 9A, in a structural configuration in which the transmitting antenna and the receiving antenna share the reference ground 11, an integrated structure of the transmitting antenna and the receiving antenna of different embodiments is illustrated, wherein the integrated structure of the transmitting antenna and the receiving antenna has the reference ground 11 and the radiation source 12, wherein the radiation source 12 is disposed on one side of the reference ground 11 in a state of being spaced apart from the reference ground 11, wherein corresponding to fig. 10B, the radiation source 12 is disposed in a unit radiation source configuration, corresponding to the radiation source 12, having a single number of radiation elements 121, wherein the radiation elements 121 have four feeding points 1211, wherein in a direction around a physical center point 1212 of the radiation elements 121, an included angle between any two adjacent feeding points 1211 and a connecting line between the physical center points 1212 of the radiating elements 121 is equal to 90 °, and a structural state that the two opposite feeding points 1211 are arranged in opposite phase is correspondingly formed, so that differential feeding to the transmitting antenna 10 is realized in a state that the two opposite feeding points 1211 of the radiating elements 121 are connected to excitation signals with a phase difference larger than 90 °, and the echo signals in a balanced differential signal form are output from the two opposite feeding points 1211, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separated form; corresponding to fig. 10C, the radiation source 12 is configured as a binary radiation source, and has two radiation elements 121 corresponding to the radiation source 12, wherein each of the radiation elements 121 has two feeding points 1211, wherein the two feeding points 1211 of each of the radiation elements 121 are arranged in opposite phases, a connection direction from one of the feeding points 1211 to the physical central point 1212 of each of the radiation elements 121 coincides with a connection direction from the other of the feeding points 1211 to the physical central point 1212 thereof, so that a polarization direction of each of the radiation elements 121 corresponds to a connection direction of the two feeding points 1211 thereof, wherein the two radiation elements 121 are arranged orthogonally, and a polarization direction of one of the radiation elements 121 is perpendicular to a polarization direction of the other radiation element 121, such that differential feeding to the transmitting antenna 10 is realized in a manner of feeding by phase difference in a state in which the two feeding points 1211 of one of the radiation elements 121 are connected to excitation signals having a phase difference greater than 90 °, and outputting the echo signals in a balanced differential signal form at the two feeding points 1211 of the other radiating element 121, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separation mode.

Corresponding to fig. 10D, on the basis of the receiving antenna illustrated in fig. 8B, the transmitting antenna arranged in the orthogonal polarization state is combined for the purpose of improving the intensity of the echo signal, and the integral structure of the transmitting antenna and the receiving antenna is illustrated in the structural form that the transmitting antenna and the receiving antenna share the reference ground 11, wherein the integral structure of the transmitting antenna and the receiving antenna has the reference ground 11 and the radiation source 12, wherein the radiation source 12 is arranged on one side of the reference ground 11 in a state of being spaced apart from the reference ground 11, wherein the radiation source 12 is arranged in the quaternary radiation source state, corresponding to the radiation source 12, having four radiation elements 121, wherein each of the radiation elements 121 has a feeding point 1211, wherein each of the radiation elements 121 is arranged circumferentially and satisfies the circumferential arrangement direction of the radiation elements 121, the angle between the connection line between the feeding point 1211 of any two adjacent radiating elements 121 and the physical center point 1212 thereof is equal to 90 degrees, one of the feeding points 1211 is electrically connected to a phase shifter, so that the echo signals in a balanced differential signal form are output between one end of the phase shifter far from the feeding point 1211 and another feeding point 1211 adjacent to the feeding point 1211 in the circumferential arrangement direction of the radiating element 121 based on the phase shifting processing of the phase shifter on the echo signals accessed from the feeding point 1211, and in the state that the other two feeding points 1211 are connected with the excitation signal, based on the orthogonal polarization state of the two radiation elements 121 to which the two feeding points 1211 belong, the intensity of the echo signal is improved, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separated form.

Corresponding to fig. 10E, based on the combination of the transmitting antenna illustrated in fig. 2B and the receiving antenna illustrated in fig. 9B, a structure of the transmitting antenna and the receiving antenna integrated with each other is illustrated in a structural form in which the transmitting antenna and the receiving antenna share the ground reference 11, wherein the structure of the transmitting antenna and the receiving antenna integrated with each other has the ground reference 11 and the radiation source 12, the radiation source 12 is disposed on one side of the ground reference 11 in a state spaced apart from the ground reference 11, the radiation source 12 is disposed in a quaternary radiation source form, the radiation source 12 has four radiation elements 121, each radiation element 121 has a feeding point 1211, each radiation element 121 is circumferentially arranged and satisfies that, in a circumferential arrangement direction of the radiation elements 121, an included angle between a connecting line between the feeding point 1211 of any two adjacent radiation elements 121 and a physical central point 1212 thereof is equal to 90 Wherein, two feeding points 1211 of two radiation elements 121 opposite to each other in the circumferential direction of the radiation elements 121 are used as transmitting feeding points, through a phase difference feeding mode, the two feeding points 1211 are connected with excitation signals with a phase difference larger than 90 degrees to realize differential feeding to the transmitting antenna 10, and the other two feeding points 1211 output echo signals in a balanced differential signal form, so as to correspondingly form an integral structure of the transmitting antenna and the receiving antenna in a transceiving separation mode.

In particular, in the two embodiments of the present invention corresponding to fig. 10D and 10E, in the circumferential arrangement direction of the radiation elements 121, in two opposite radiation elements 121, the connection line from the feeding point 1211 to the physical central point 1212 of one radiation element 121 is staggered and opposite to the connection line from the feeding point 1211 to the physical central point 1212 of the other radiation element 121, and the feeding point 1211 and the connection line from the physical central point 1212 of each radiation element 121, which are correspondingly formed, intersect to form a regular quadrilateral structure, so as to facilitate reducing the radial area occupied by the arrangement of the radiation elements 121.

Corresponding to fig. 10F, on the basis of the receiving antenna illustrated in fig. 8C, the transmitting antenna provided in the orthogonal polarization form is combined, and in a structural form in which the transmitting antenna and the receiving antenna share the reference ground 11A, an integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the transmitting antenna and the receiving antenna are respectively provided in the half-wave folded-back directional microwave detecting antenna 10A of the orthogonal polarization horizontal structure, the half-wave folded-back directional microwave detecting antenna 10A includes four half-wave vibrators 12A, four of which are circumferentially arranged and satisfy a circumferential arrangement direction of the half-wave vibrators 12A, and any two adjacent half-wave vibrators 12A are orthogonally arranged corresponding to a height direction of the half-wave folded-back directional microwave detecting antenna 10A in a direction perpendicular to the reference ground 11A In the circumferential arrangement direction of the half-wave oscillators 12A, any two adjacent half-wave oscillators 12A are perpendicular to each other in the extending direction perpendicular to the height direction of the half-wave folded directional microwave detecting antenna 10A, wherein the feeding point 121A of one half-wave oscillator 12A is connected to a phase shifter via the feeding line 13A, so that the echo signal received from the feeding point 121A is output as a balanced differential signal between one end of the phase shifter remote from the feeding point 121A and another feeding point 121A adjacent to the feeding point 121A in the circumferential arrangement direction of the half-wave oscillator 12A based on the phase shift processing of the phase shifter, and in a state where the other two feeding points 121A are connected to an excitation signal, based on a structural form where the two half-wave oscillators 12A to which the two feeding points 121A belong are orthogonally arranged, and improving the strength of the echo signal so as to form an integral structure of the transmitting antenna and the receiving antenna in a transceiving separation mode.

Corresponding to fig. 10G, on the basis of the receiving antenna illustrated in fig. 9C, the transmitting antenna provided in a reverse polarization state is combined for the purpose of improving the accuracy of the echo signal, and the integrated structure of the transmitting antenna and the receiving antenna is illustrated in the structural form in which the transmitting antenna and the receiving antenna share the reference ground 11A, wherein the transmitting antenna and the receiving antenna are respectively provided in the half-wave folded-back type directional microwave detecting antenna 10A of a horizontal structure in reverse polarization, the corresponding half-wave folded-back type directional microwave detecting antenna 10A includes four half-wave vibrators 12A, wherein the four half-wave vibrators 12A are arranged in the circumferential direction and satisfy the circumferential arrangement direction of the half-wave vibrators 12A, and any two adjacent half-wave vibrators 12A are arranged orthogonally, corresponding to the high level of the half-wave folded-back type directional microwave detecting antenna 10A in the direction perpendicular to the reference ground 11A In the circumferential arrangement direction of the half-wave oscillators 12A, the extending directions of any two adjacent half-wave oscillators 12A in the direction perpendicular to the height direction of the half-wave backfolding type directional microwave detection antenna 10A are perpendicular to each other, wherein the two feeding points 121A of the two half-wave oscillators 12A opposite to the circumferential arrangement direction of the half-wave oscillators 12A are used as transmitting feeding points, differential feeding to the transmitting antenna is realized in a state that excitation signals with a phase difference larger than 90 ° are connected to the two feeding points 121A in a phase difference feeding manner, echo signals in a balanced differential signal form are output from the other two feeding points 121A, and an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separation form is correspondingly formed.

Corresponding to fig. 10H, on the basis of the receiving antenna illustrated in fig. 8D, the transmitting antenna configured in an orthogonal polarization form is combined, specifically, the receiving antenna is the transmitting antenna, and an integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the transmitting antenna and the receiving antenna are configured in the half-wave folded-back directional microwave detecting antenna 10A of a vertical structure of the same orthogonal polarization, the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, two half-wave oscillators 12A are orthogonally arranged, and an extending direction of the two half-wave oscillators 12A in a direction perpendicular to a height direction of the half-wave folded-back directional microwave detecting antenna 10A is perpendicular to a direction of the reference ground 11A, one of the feeding ends 1211A of one of the half-wave oscillators 12A is connected with a phase shifter through the feeding line 13A, so as to output the echo signal in a balanced differential signal form between one end of the phase shifter, which is far away from the feeding end 1211A of the half-wave oscillator 12A, and one of the feeding ends 1211A of the other half-wave oscillator 12A based on the phase shift processing of the echo signal accessed by the phase shifter, and improve the intensity of the echo signal based on the structural form that the two half-wave oscillators 12A to which the two feeding ends 1211A belong are orthogonally arranged in the state that the other two feeding ends 1211A are accessed with an excitation signal, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving integrated form.

Corresponding to fig. 10I, based on the combination of the transmitting antenna illustrated in fig. 3A and the receiving antenna illustrated in fig. 9D, in a structural form in which the transmitting antenna and the receiving antenna share the reference ground 11A, an integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the transmitting antenna and the receiving antenna are respectively disposed in the half-wave folded type directional microwave detection antenna 10A of a reverse-phase polarized vertical structure, the integrated structure corresponding to the transmitting antenna and the receiving antenna includes two half-wave oscillators 12A, wherein each of the half-wave oscillators 12A is arranged in reverse phase, and the two half-wave oscillators 12A are arranged orthogonally to each other, and corresponding to a height direction of the half-wave folded type directional microwave detection antenna 10A in a direction perpendicular to the reference ground 11A, each of the half-wave oscillators 12A is arranged in a height direction perpendicular to the half-wave folded type directional microwave detection antenna 10A from the two feeding terminals 1211A The extending directions of the two half-wave oscillators 12A are opposite, and the extending directions perpendicular to the height direction of the half-wave folded directional microwave detecting antenna 10A are perpendicular to each other, so that based on the structural state that each half-wave oscillator 12A is arranged in opposite phase, the two feeding ends 1211A of one half-wave oscillator 12A output the echo signals in a balanced differential signal form, and the two feeding ends 1211A of the other half-wave oscillator 12A are connected to excitation signals with a difference of more than 90 ° to realize differential feeding to the transmitting antenna, thereby forming an integrated structure of the transmitting antenna and the receiving antenna in a transmitting-receiving separation form.

In particular, in correspondence with the integrated structure of the transmitting antenna and the receiving antenna illustrated in fig. 10H and 10I, each half-wave element 12A is shifted from the two feeding terminals 1211A in the extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A, wherein the state in which the two half-wave elements 12A are orthogonally arranged corresponds to the structural form in which the four feeding terminals 1211A are located at the four vertex positions of the square having the connection line of the two feeding terminals 1211A of each half-wave element 12A as two diagonal lines, so as to maintain the state in which the distance between the two feeding terminals 1211A of each half-wave element 12A is equal to or less than λ/4 and the distance between the two ends of each half-wave element 12A is equal to or greater than λ/128 and equal to or less than λ/6, which is advantageous in the state in which the two half-wave elements 12A are orthogonally arranged, based on the structure form that the extending directions of the two feeding ends 1211A of the half-wave oscillators 12A in the direction perpendicular to the height direction of the half-wave folded directional microwave detecting antenna 10A are staggered and reversed, the stability of the integrated structure of the transmitting antenna and the receiving antenna under the corresponding volume limitation due to the too close distance between the feeding end 1211A of one half-wave oscillator 12A and the feeding end 1211A of the other half-wave oscillator 12A is avoided.

Corresponding to fig. 10J, on the basis of the receiving antenna illustrated in fig. 9E, based on the purpose of improving the accuracy of the echo signal, based on the transceiving reciprocity characteristic of the antenna, the receiving antenna is the transmitting antenna, and the integrated structure of the transmitting antenna and the receiving antenna is illustrated, wherein the receiving antenna is exemplified by the double-feed differential antenna 10B, and the two strip-shaped elements 12B are formed in a structure state in which the two strip-shaped elements 12B are arranged in opposite phases in the polarization direction tending to linear polarization based on the structural characteristic that the two coupling sections 122B of the two strip-shaped elements 12B extend in the opposite directions from the proximal end and can be coupled with each other to form a common resonant frequency point, so that the echo signal in a balanced differential signal form can be directly output at the two feeding ends 121B when the double-feed differential antenna 10B is used as the receiving antenna, and when the double-feed type differential antenna 10B is used as a transmitting antenna, the differential feed of the transmitting antenna is realized in the polarization direction of the transmitting antenna which tends to linear polarization by accessing the state of excitation signals with a phase difference larger than 90 degrees at the two feed ends 121B of the two strip-shaped oscillators 12B, so that an integrated structure of the transmitting antenna and the receiving antenna in a transceiving integrated mode is formed.

Corresponding to the above description, according to the present invention, the detection method of the microwave detection device comprises the following steps:

A. feeding the transmitting antenna with an excitation signal with a phase difference larger than 90 degrees in the polarization direction of the transmitting antenna tending to linear polarization by means of phase difference feeding so as to realize differential feeding of the transmitting antenna with the phase difference larger than 90 degrees;

B. accessing the echo signals with phase difference of 180 degrees and in a balanced differential signal form from the receiving antenna; and

C. outputting the Doppler intermediate frequency signal in a single-ended signal form with a frequency/phase difference between the excitation signal and the echo signal in a mixing processing step and a differential-to-single-ended processing step based on step (C1) or step (C2), wherein in the step (C1), the echo signal in a single-ended signal form is output based on the differential-to-single-ended processing of the echo signal in a balanced differential signal form by the differential-to-single-ended circuit, and the Doppler intermediate frequency signal in a single-ended signal form is output based on the mixing processing of the excitation signal and the echo signal in a single-ended signal form by the mixing circuit, wherein in the step (C2), the Doppler intermediate frequency signal in a balanced differential signal form is output based on the mixing processing of the excitation signal and the echo signal in a balanced differential signal form by the mixing circuit, and outputting the Doppler intermediate frequency signal in a single-ended signal form based on differential-to-single-ended processing of the Doppler intermediate frequency signal in a balanced differential signal form by the differential-to-single-ended circuit.

In some embodiments of the present invention, corresponding to fig. 2A, the transmitting antenna is configured with a ground reference 11 and a radiation source 12 in a planar patch antenna configuration, wherein the radiation source 12 is configured at one side of the ground reference 11 in a spaced manner from the ground reference 11, the radiation source 12 is configured in a unit radiation source configuration, the radiation source 12 has a single number of radiation elements 121, the radiation elements 121 have two feeding points 1211, wherein the two feeding points 1211 are arranged in opposite phases, a connection direction corresponding to a physical central point 1212 of the radiation element 121 from one of the feeding points 1211 coincides with a connection direction corresponding to a physical central point 1212 of the radiation element 121 from the other of the feeding points 1211, and the radiation element 121 has a polarization configuration of linear polarization in a state that the feeding points 1211 is connected to an excitation signal and uses the connection direction of the two feeding points 1211 as the linear polarization direction, in this way, in a manner of feeding by phase difference, in a state that the two feeding points 1211 of the radiating element 121 access the excitation signals with a phase difference larger than 90 °, the differential feeding to the transmitting antenna is realized in the linear polarization direction of the transmitting antenna.

In some embodiments of the present invention, corresponding to fig. 2B, the transmitting antenna is configured with a ground reference 11 and a radiation source 12 in a planar patch antenna configuration, wherein the radiation source 12 is configured at one side of the ground reference 11 in a spaced manner from the ground reference 11, the radiation source 12 is configured in a binary radiation source configuration, the radiation source 12 has two radiation elements 121, each of the radiation elements 121 has a feeding point 1211, the two radiation elements 121 are arranged in opposite phases, a connection direction from the feeding point 1211 to a physical central point 1212 of one of the radiation elements 121 is opposite to a connection direction from the feeding point 1211 to the physical central point of the other radiation element 121, and the two radiation elements 121 have a linear polarization configuration in a state that the two feeding points 1211 are connected to an excitation signal and a linear polarization direction from the connection direction of the two feeding points 1211, in this way, in a manner of feeding by phase difference, the differential feeding to the transmitting antenna is implemented in the linear polarization direction of the transmitting antenna in a state that the two feeding points 1211 of the two radiating elements 121 access the excitation signals with a phase difference greater than 90 °.

In some embodiments of the present invention, corresponding to fig. 3A, the transmitting antenna is configured as the half-wave folded directional microwave detecting antenna of a vertical structure, and includes a ground reference 11A, a half-wave oscillator 12A and two power feeding lines 13A, wherein the half-wave oscillator 12A has an electrical length equal to or greater than 1/2 and equal to or less than 3/4, and has two coupling sections 121A, wherein each of the coupling sections 121A has an electrical length equal to or greater than 1/6, one end of each of the coupling sections 121A is the feeding end 1211A of the coupling section 121A, and the other ends of the coupling sections 121A are two ends of the half-wave oscillator 12A, wherein the distance between the two feeding ends 1211A is equal to or less than λ/4, the distance between the two ends of the half-wave oscillator 12A is equal to or greater than λ/128 and equal to or less than λ/6, then, the half-wave oscillator 12A is in a state that two poles of an excitation signal or an excitation signal with a phase difference are respectively accessed to the two feeding ends 1211A to be fed, two ends of the half-wave oscillator 12A can form a phase difference to form a polarization state tending to linear polarization in a mutual coupling manner, and when the direction perpendicular to the reference ground 11A is the height direction of the half-wave folded directional microwave detecting antenna 10A, the extending direction of the half-wave oscillator 12A in the direction perpendicular to the height direction of the half-wave folded directional microwave detecting antenna 10A is a linear polarization direction, so that in a manner of feeding by a phase difference, differential feeding to the transmitting antenna is realized in the linear polarization direction of the transmitting antenna in a state that the two feeding ends 1211A of the half-wave oscillator are accessed to the excitation signal with a phase difference larger than 90 °.

In some embodiments of the present invention, the transmitting antenna is disposed corresponding to the half-wave folded-back directional microwave detecting antenna 10A of the horizontal structure in which the receiving antenna is polarized in reverse phase as illustrated in fig. 9C, and the half-wave folded-back directional microwave detecting antenna 10A includes two half-wave oscillators 12A, wherein the two half-wave oscillators 12A are arranged in reverse phase, corresponding to the height direction of the half-wave folded-back directional microwave detecting antenna 10A in the direction perpendicular to the reference ground 11A, the two half-wave oscillators 12A are reversed from the feeding point 121A in the extending direction perpendicular to the height direction of the half-wave folded-back directional microwave detecting antenna 10A, based on the structural state in which the two half-wave oscillators 12A are arranged in reverse phase, in the state in which the two feeding points 121A are fed with excitation signals having a phase difference, the two half-wave oscillators 12A can form a phase difference to form a polarization state tending to linear polarization in a mutual coupling manner, and when the direction perpendicular to the reference ground 11A is the height direction of the half-wave folded-back directional microwave detection antenna 10A, the extension direction of the half-wave oscillators 12A in the height direction perpendicular to the half-wave folded-back directional microwave detection antenna 10A is the linear polarization direction, so that differential feeding to the transmitting antenna is realized in the linear polarization direction of the transmitting antenna in a state that the two feeding points 121A are connected with excitation signals with a phase difference larger than 90 degrees in a phase difference feeding manner.

In some embodiments of the present invention, corresponding to fig. 4A to 4N, the transmitting antenna is configured as the dual-feed differential antenna, and the transmitting antenna includes a reference ground 11B and two strip-shaped oscillators 12B, wherein two ends of the two strip-shaped oscillators 12B, which are connected to the excitation signal, are respectively the feeding ends 121B of the two strip-shaped oscillators 12B, the two strip-shaped oscillators 12B extend from the two feeding ends 121B in the same lateral space of the reference ground 11B and respectively have a wavelength electrical length greater than or equal to 3/16 and less than or equal to 5/16, wherein the two strip-shaped oscillators 12B respectively have a coupling section 122B, wherein one end of the coupling section 122B, which is close to the feeding end 121B of the strip-shaped oscillator 12B to which the coupling section belongs, is a proximal end of the coupling section 122B, and the two coupling sections 122B extend from the proximal end in opposite directions, the two coupling sections 122B extend from the near end in opposite directions based on a structural form that the two coupling sections 122B extend from the near end, and a state that the two feeding ends 121B of the two strip-shaped oscillators 12B are connected with excitation signals with phase difference forms coupling between the two coupling sections 122B to form a polarization form tending to linear polarization, so that the two feeding ends 121B of the two strip-shaped oscillators 12B are connected with excitation signals with phase difference larger than 90 degrees in a phase difference feeding mode, and differential feeding of the transmitting antenna is realized in the polarization direction tending to linear polarization of the transmitting antenna.

In some embodiments of the present invention, wherein in the step (a), the transmitting power of the transmitting antenna is less than or equal to 0 dBm.

In accordance with another embodiment of the present invention, a detection method of a microwave detection device includes the following steps:

A. setting a transmit power of the transmit antenna at a target transmit power of less than or equal to 0dBm based on a corresponding parameter setting of an excitation signal;

C. outputting the Doppler intermediate frequency signal in a single-ended signal form with a frequency/phase difference between the excitation signal and the echo signal in a mixing processing step and a differential-to-single-ended processing step based on step (C1) or step (C2), wherein in the step (C1), the echo signal in a single-ended signal form is output based on the differential-to-single-ended processing of the echo signal in a balanced differential signal form by the differential-to-single-ended circuit, and the Doppler intermediate frequency signal in a single-ended signal form is output based on the mixing processing of the excitation signal and the echo signal in a single-ended signal form by the mixing circuit, wherein in the step (C2), the Doppler intermediate frequency signal in a balanced differential signal form is output based on the mixing processing of the excitation signal and the echo signal in a balanced differential signal form by the mixing circuit, and the Doppler intermediate frequency signal in a single-ended signal form is output based on the differential-to-single-ended processing of the Doppler intermediate frequency signal in a balanced differential signal form by the differential-to-single-ended circuit.

In some embodiments of the present invention, in the step (a), the circular polarization form of the transmitting antenna is implemented and the minimum transmitting power extreme value of the transmitting antenna is reduced by means of phase difference feeding.

In some embodiments of the present invention, in the step (a), in a manner of phase difference feeding, the polarization direction tending to linear polarization of the transmitting antenna feeds the transmitting antenna with an excitation signal greater than 90 ° phase difference, so as to implement differential feeding greater than 90 ° phase difference for the transmitting antenna.

In the description herein, references to the description of the term "one embodiment," "some embodiments," "an example," "a specific example," or "some examples," etc., mean that a particular feature, structure, material, or characteristic described in connection with the embodiment or example is included in at least one embodiment or example of the invention. In this specification, the terminology used in the description above is not necessarily meant to be the same embodiment or example. Furthermore, the particular features, structures, materials, or characteristics described may be combined in any suitable manner in any one or more embodiments or examples. Furthermore, various embodiments or examples and features of different embodiments or examples described in this specification can be combined and combined by one skilled in the art without contradiction.

It will be understood by those skilled in the art that the embodiments of the present invention as described above and shown in the drawings are given by way of example only and are not limiting of the present invention. The objects of the present invention have been fully and effectively accomplished. The functional and structural principles of the present invention have been shown and described in the embodiments without departing from the principles, embodiments of the present invention may have any deformation or modification.

Claims

1. Microwave detection device, its characterized in that includes:

a receiving antenna, wherein the receiving antenna is configured as a planar patch antenna and has a reference ground and a radiation source, wherein the radiation source is configured as a unit radiation source, the radiation source has a single number of radiation elements, the radiation elements have two feeding points, the two feeding points are arranged in opposite phases, a connection line direction from one of the feeding points to a physical center point of the radiation element and a connection line direction from the other feeding point to the physical center point of the radiation element are coincident with each other, so as to output echo signals in a balanced differential signal form at the two feeding points after receiving a reflected echo wave formed by the microwave beam reflected by a corresponding object based on a structural state that the two feeding points are arranged in opposite phases, the echo signal comprises a signal corresponding to a reflected echo formed by the microwave beam reflected by a corresponding object, and the electromagnetic interference in the environment exists in a common-mode interference form in the echo signal and can be suppressed in the receiving and transmitting processes of the echo signal with a balanced differential signal form;

2. The microwave detection apparatus according to claim 1, wherein the two feeding points of the radiating element of the receiving antenna are arranged to be symmetrical with respect to a physical center point of the radiating element.

3. A microwave detection apparatus as claimed in claim 2 wherein the radiating element is electrically connected to the reference ground at its physical centre point.

4. A microwave detection apparatus according to claim 3 wherein the radiating elements have at least one set and/or at least one pair of ground points electrically connected to the reference ground, wherein the grounding points of the same group are positioned at each vertex of the same regular polygon taking the physical central point of the radiating element as a midpoint, each grounding point corresponding to the grounding point in the same group is arranged around the physical central point of the radiation element at equal angles in a state of being equidistant from the physical central point of the radiation element, wherein the grounding points of the same pair are symmetrically distributed on the radiating element with the physical center point of the radiating element, the connecting line segment corresponding to the grounding point of the same pair takes the physical central point of the radiating element as a midpoint, and forms a zero potential point at the physical central point of the radiating element based on the electrical connection relationship between the grounding point and the reference ground, so that the connecting line segment is equivalent to the physical central point of the radiating element and the reference ground in electrical connection.

5. The microwave detecting device according to any one of claims 2 to 4, wherein the transmitting antenna is configured in a planar patch antenna configuration having a reference ground and a radiation source, wherein the radiation source is configured on one side of the reference ground in a state spaced apart from the reference ground, the radiation source is configured in a unit radiation source configuration having a single number of radiation elements corresponding to the radiation source, wherein the radiation elements have two feeding points, wherein the two feeding points are arranged in opposite phases, and a connection line direction from one of the feeding points to a physical central point of the radiation element and a connection line direction from the other feeding point to a physical central point of the radiation element are coincident with each other, so that the two feeding points are connected to an excitation signal to realize feeding of the transmitting antenna.

6. The microwave detecting device according to claim 5, wherein the transmitting antenna and the receiving antenna are integrally provided in a transceiving separated form based on a structural form sharing the reference ground, and the transmitting antenna and the receiving antenna integrally provided in the transceiving separated form include one reference ground and one radiation source, wherein the radiation source is provided in a binary radiation source form having two radiating elements, wherein each of the radiating elements has two feeding points, wherein the two feeding points of each of the radiating elements are arranged in an inverted phase, wherein a direction of a connection line of the two feeding points of each of the radiating elements is a polarization direction thereof, the two radiating elements are arranged orthogonally, and a polarization direction of one of the radiating elements is perpendicular to a polarization direction of the other of the radiating elements, so that the two feeding points of one of the radiating elements are connected to an excitation signal to realize feeding of the transmitting antenna, and outputting the echo signals in a balanced differential signal form at the two feeding points of the other radiating element to correspondingly form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separation mode.

7. The microwave detecting device according to claim 5, wherein the transmitting antenna and the receiving antenna are integrally disposed in a transceiving separated form based on a structural configuration that shares the reference ground and the radiation source, and the transmitting antenna and the receiving antenna that are integrally disposed in the transceiving separated form include one reference ground and one radiation source, wherein the radiation source is disposed in a unit radiation source form and has a single number of the radiating elements, wherein the radiating elements have four feeding points, wherein an angle between a connecting line between any two adjacent feeding points and a physical central point of the radiating element in a direction around the physical central point of the radiating element is equal to 90 °, and a structural state is formed in which the two opposite feeding points are arranged in opposite phases, so that an excitation signal is accessed to two opposite feeding points of the radiating element to realize feeding of the transmitting antenna, and outputting the echo signals in a balanced differential signal form at the other two opposite feeding points, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving separation mode.

8. The microwave detection apparatus according to claim 5, wherein the transmitting antenna and the receiving antenna are integrally provided in a transceive-united form based on a structural form of sharing the reference ground and the radiation source, the transmitting antenna and the receiving antenna integrally provided in a transceive-united manner include one of the reference ground and one of the radiation sources, wherein the radiation source is arranged in a unit radiation source configuration with a single number of the radiating elements, wherein the radiating element has two feeding points, wherein the two feeding points are arranged in opposite phase, so that an excitation signal is switched in the two feeding points of the radiating element to realize feeding of the transmitting antenna, and the echo signals in a balanced differential signal form are output at the two feeding points, so as to form an integrated structure of the transmitting antenna and the receiving antenna in a transceiving integrated mode.

9. The microwave detection device according to claim 5, wherein the microwave detection device further comprises at least one amplification circuit adapted to amplify signals in differential signal form, wherein the amplification circuit is disposed between the receiving antenna and the differential to single-ended circuit to amplify the echo signals in balanced differential signal form output to the differential to single-ended circuit.

10. The microwave detection device according to claim 9, wherein the differential-to-single-ended circuit and the amplification circuit are integrally provided in a circuit configuration of an instrumentation amplifier.