CN103458586A - Transconductance amplifier and LED constant current drive circuit - Google Patents
Transconductance amplifier and LED constant current drive circuit Download PDFInfo
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- CN103458586A CN103458586A CN2013104150963A CN201310415096A CN103458586A CN 103458586 A CN103458586 A CN 103458586A CN 2013104150963 A CN2013104150963 A CN 2013104150963A CN 201310415096 A CN201310415096 A CN 201310415096A CN 103458586 A CN103458586 A CN 103458586A
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Abstract
The invention provides a transconductance amplifier and an LED constant current drive circuit. The transconductance amplifier comprises a differential input stage circuit, a current transmitting circuit, an input switching network, a current transmitting switching network and a clock signal generator. The differential input stage circuit comprises a first voltage-to-current circuit and a second voltage-to-current circuit; the current transmitting circuit carries out transmission on currents output by the differential input stage circuit; the input switching network carries out switching on input positive input signals and input negative input signals, and thus the input positive input signals and the input negative input signals are made to be input to the input end of the first voltage-to-current circuit and the input end of the second voltage-to-current circuit alternatively; the current transmitting switching network carries out switching on the current transmitting paths of the current transmitting circuit, and thus output signals of the transconductance amplifier are made to be maintained in positive polarity with positive input signals and to be maintained in reversed polarity with negative input signals; the clock signal generator generates first clock signals, second clock signals, third clock signals and fourth clock signals, wherein the first clock signals, the second clock signals, the third clock signals and the fourth clock signals are non-overlapped signals in periodicity, the first cock signals are in phase reversal with the second clock signals, and the third clock signals are in phase reversal with the fourth clock signals. The transconductance amplifier and the LED constant current drive circuit can reduce detuning caused by matching of devices and packaging stress, and are beneficial to improving the conformance of circuits.
Description
Technical field
The present invention relates to the trsanscondutance amplifier technical field, relate in particular to a kind of trsanscondutance amplifier and LED constant-current drive circuit.
Background technology
With reference to figure 1, traditional step-down LED drive circuit mainly comprises: constant-current control circuit 100, sustained diode 1, inductance L 1, capacitor C 1, switching tube M1, sampling resistor Rcs.Wherein, the negative pole of sustained diode 1 is connected to positive pole and the power end Vin of load LED, and the positive pole of sustained diode 1 is connected to the first end of inductance L 1, and the second end of inductance L 1 is connected to the negative pole of load LED; Switching tube M1 is connected between inductance L 1 and sampling resistor Rcs, and this switching tube M1 is controlled by constant-current control circuit 100.
Wherein, constant-current control circuit 100 comprises: peak sampling hold circuit 106, and during power switch M1 conducting, sample streams is through the sampled voltage Vcs of peak current on sampling resistor Rcs of power switch; Output equivalent Current calculation circuit 105, calculate the output equivalent electric current according to the peak meter of the sampled voltage Vcs on sampling resistor Rcs; Trsanscondutance amplifier 101, do the error amplification to output equivalent electric current and fiducial value Vref1, and output error signal is to loop compensation end COMP; Loop compensation end COMP, this loop compensation end COMP can additional compensating element,, generally resistance, electric capacity connection in series-parallel, consists of, and by error signal, Vcomp carrys out control loop; Pwm signal generation circuit 102, receive error signal Vcomp, produce pwm signal to logic control circuit 103, the duty ratio of pwm signal is relevant to error signal Vcomp, and logic control circuit 103 produces pre-drive signal GT1 through drive circuit 104 driving power switch M1.
Wherein, the precision of output current and fiducial value Vref1, peak value sampling retention value are relevant, also relevant to the precision of trsanscondutance amplifier 101, and for the consistency of circuit, the precision of trsanscondutance amplifier 101 has conclusive effect.
With reference to figure 2, in traditional transconductance type error amplifier circuit, MOS transistor N1, N2 are as input to pipe, and resistance R 1 and resistance R 2 are used for widening the input range of linearity of error amplifier, if the input range of linearity is enough, resistance R 1 and resistance R 2 can be omitted.MOS transistor P1, P2, P3, P4, N4, N5 are as intergrade, and the mirror image delivered current, make output current Iout=Gm*(Vp-Vn), Iout is output current, Gm is mutual conductance, the magnitude of voltage that Vp is positive input signal, the magnitude of voltage that Vn is the negative input signal.Wherein, the size of mutual conductance Gm with as the MOS transistor N1 of input pipe, the size of N2, the size of resistance R 1 and resistance R 2, and the ratio that image current transmits is relevant.
The mismatch of trsanscondutance amplifier can cause actual value and the desired value generation deviation controlled.
Especially use in the LED drive circuit of trsanscondutance amplifier at LED drive circuit, for the consistency by circuit is carried out, with regard to requiring, the mutual conductance of circuit is done accurately, and reduced as far as possible the imbalance of circuit.But, due to the deviation in the processes manufacture process and encapsulation stress, can cause symmetrical input pipe, synistor and the image current of design to become mismatch, thereby cause the mutual conductance of side circuit no longer accurate, the imbalance of circuit obviously increases.In order to reduce this mismatch, generally need to cause all meetings the element of mismatch to do symmetrically as much as possible, comprise the Central Symmetry of domain, and strengthen the size of symmetric element, but can cause like this need to be larger chip area, also just increased the coupling cost.In addition, even use these measures, still can not well solve the impact that the problem that mismatch causes, especially mismatch are subject to encapsulation stress, the effect of the size of increasing symmetric element is also not obvious.
Summary of the invention
The technical problem to be solved in the present invention is to provide a kind of trsanscondutance amplifier and LED constant-current drive circuit, can reduce the trsanscondutance amplifier imbalance caused due to device matching and encapsulation stress, is conducive to improve the consistency of circuit.
For solving the problems of the technologies described above, the invention provides a kind of trsanscondutance amplifier, comprising:
The differential input stage circuit, comprise that the first voltage turns current circuit and second voltage turns current circuit;
Current transfer circuit, the electric current that described differential input stage circuit is exported is transmitted;
The input switch network, switched positive input signal and the negative input signal of input, makes described positive input signal and negative input signal alternately input to described the first voltage and turn the input that current circuit and second voltage turn current circuit;
The current delivery switching network, switched the current delivery path of described current transfer circuit, makes the output signal of described trsanscondutance amplifier and described positive input signal keep positive polarity, and keep reversed polarity with described negative input signal;
Clock-signal generator, described clock-signal generator produces periodically non-the first overlapping clock signal and second clock signal, this first clock signal and second clock signal inversion, this first clock signal and second clock signal are for controlling described input switch network and current delivery switching network, described clock-signal generator also produces periodically non-the 3rd overlapping clock signal and the 4th clock signal, the 3rd clock signal and the 4th clock signal are anti-phase, and the 3rd clock signal and the 4th clock signal are for controlling described current delivery switching network.
According to one embodiment of present invention, described input switch network comprises:
The first switch, its first end receives described negative input signal, and its second end connects the input that described the first voltage turns current circuit, and its control end receives described the first clock signal;
Second switch, its first end receives described positive input signal, and its second end connects the input that described the first voltage turns current circuit, and its control end receives described second clock signal;
The 3rd switch, its first end receives described positive input signal, and its second end connects the input that described second voltage turns current circuit, and its control end receives described the first clock signal;
The 4th switch, its first end receives described negative input signal, and its second end connects the input that described second voltage turns current circuit, and its control end receives described second clock signal.
According to one embodiment of present invention,
Described current transfer circuit comprises:
The first mirror current source, its input is connected with the output that described the first voltage turns current circuit;
The second mirror current source, its input is connected with the output that described second voltage turns current circuit;
The first mirror image tube;
The second mirror image pipe, its source electrode is connected with the source electrode of described first mirror image tube, and its grid is connected with the grid of described first mirror image tube;
Described current delivery switching network comprises:
The 5th switch, its first end connects the output of described the first mirror current source, and its second end connects the output of described trsanscondutance amplifier, and its control end receives described second clock signal;
The 6th switch, its first end connects the output of described the first mirror current source, and its control end receives described the first clock signal;
Minion is closed, and its first end connects the output of described the second mirror current source, and its second end connects the second end of described the 6th switch, and its control end receives described second clock signal;
The 8th switch, its first end connects the output of described the second mirror current source, and its second end connects the second end of described the 5th switch, and its control end receives described the first clock signal;
The 9th switch, its first end connects the second end that described minion is closed, and its second end connects the drain electrode of described first mirror image tube, and its control end receives described the 4th clock signal;
The tenth switch, its first end connects the second end of described minion pass and the grid of described first mirror image tube and the second mirror image pipe, and its second end connects the drain electrode of described the second mirror image pipe, and its control end receives described the 3rd clock signal;
The 11 switch, its first end connects the second end of described the 8th switch, and its second end connects the drain electrode of described first mirror image tube, and its control end receives described the 3rd clock signal;
Twelvemo is closed, and its first end connects the second end of described the 8th switch, and its second end connects the drain electrode of described the second mirror image pipe, and its control end receives described the 4th clock signal.
According to one embodiment of present invention, the duty ratio of described the first clock signal, second clock signal, the 3rd clock signal and the 4th clock signal is 0.5.
According to one embodiment of present invention, described the first voltage turns current circuit and comprises that the first difference input is to pipe, and described second voltage turns current circuit and comprises that the second difference input is to pipe.
According to one embodiment of present invention, described the first differential pair tube is connected with the first resistance, and described the second differential pair tube is connected with the second resistance.
According to one embodiment of present invention, described the first difference input is nmos pass transistor, NPN triode, PMOS transistor or PNP triode to pipe and the input of the second difference to pipe.
The present invention also provides a kind of LED constant-current drive circuit, comprises the described trsanscondutance amplifier of above any one.
According to one embodiment of present invention, this LED constant-current drive circuit comprises constant-current control circuit, transformer, switching tube, sampling resistor, fly-wheel diode and output capacitance, wherein,
The Same Name of Ends of the former limit winding of described transformer receives input voltage, the Same Name of Ends ground connection of the secondary winding of described transformer, and the different name end of the secondary winding of described transformer connects the positive pole of described fly-wheel diode;
The drain electrode of described switching tube connects the different name end of the former limit winding of described transformer, and the grid of described switching tube connects the output of described constant-current control circuit;
The first end of described sampling resistor connects the source electrode of described switching tube and the sampling input of described constant-current control circuit, the second end ground connection of described sampling resistor;
The first end of described output capacitance connects the negative pole of described fly-wheel diode, the second end ground connection of described output capacitance,
Described constant-current control circuit comprises:
Peak sampling hold circuit, its input connects the sampling input of described constant-current control circuit, and the sampled voltage on described sampling resistor is sampled;
Output equivalent Current calculation circuit, its input is connected with the output of described peak sampling hold circuit, according to described sampled voltage, calculates the output equivalent electric current, and output means the equivalent voltage of this output equivalent electric current;
The described trsanscondutance amplifier of above-mentioned any one, its first input end connects the output of described output equivalent Current calculation circuit, and its second input receives reference voltage, and described equivalent voltage and reference voltage are carried out to the error amplification;
Pwm signal generation circuit, its input connects the output of described trsanscondutance amplifier, according to the error signal of described trsanscondutance amplifier output, produces pwm signal, and the duty ratio of described pwm signal is regulated by described error signal;
Logic and driver circuitry, its input connects the output of described pwm signal generation circuit, and described pwm signal transfers to the grid of described switching tube via this logic and driver circuitry.
Compared with prior art, the present invention has the following advantages:
In the trsanscondutance amplifier of the embodiment of the present invention, adopt the input switch network by positive input signal and negative input signal alternately in other words periodically alternately input to two inputs of differential input stage circuit, and adopt the current delivery switching network to be switched the current delivery path of current transfer circuit, make the output signal of trsanscondutance amplifier and positive input signal remain positive polarity.On the one hand, because positive and negative input signal alternately inputs to two inputs of differential input stage circuit, therefore the first voltage of differential input stage inside circuit turns the imbalance that current circuit and second voltage turn between current circuit and can cancel out each other, and has greatly improved the consistency of circuit; On the other hand, because is alternately switching in the current delivery path, so in current transfer circuit, the imbalance between each device is also cancelled out each other, and is conducive to improve the consistency of circuit.
The accompanying drawing explanation
Fig. 1 is the electrical block diagram of a kind of LED drive circuit in prior art;
Fig. 2 is the electrical block diagram of a kind of trsanscondutance amplifier in prior art;
Fig. 3 is the electrical block diagram of the trsanscondutance amplifier of the embodiment of the present invention;
Fig. 4 is the oscillogram of the clock signal of the embodiment of the present invention;
Fig. 5 is the structural representation of the clock-signal generator of the embodiment of the present invention;
Fig. 6 is the electrical block diagram of the LED constant-current drive circuit of the embodiment of the present invention.
Embodiment
Below in conjunction with specific embodiments and the drawings, the invention will be further described, but should not limit the scope of the invention with this.
With reference to figure 3, the trsanscondutance amplifier of the present embodiment comprises: input switch network 200, differential input stage circuit 201, current transfer circuit, current delivery switching network and clock-signal generator.
Furthermore, differential input stage circuit 201 comprises that the first voltage turns current circuit and second voltage turns current circuit.In the present embodiment, the first voltage turns current circuit and comprises first resistance R 1 of the first difference input to pipe N1 and series connection with it, second voltage turns current circuit and comprises second resistance R 2 of the second difference input to pipe N2 and series connection with it, differential input stage circuit 201 is connected to ground via transistor N3, and the grid of transistor N3 receives bias voltage Vbias.Wherein, the first resistance R 1 and the second resistance R 2, for increasing the input range of linearity, are optional.The first difference input can be nmos pass transistor, NPN triode, PMOS transistor or PNP tri-machine pipes to pipe N1 and the input of the second difference to pipe N2, or can be also other suitable transistors.As a nonrestrictive example, in the example shown in Fig. 3, the first difference input is nmos pass transistor to pipe N1 and the input of the second difference to pipe N2.
The positive input signal Vp of 200 pairs of inputs of input switch network and negative input signal Vn carry out periodicity switching, make positive input signal Vp and negative input signal Vn alternately input to the first voltage and turn the input that current circuit and second voltage turn current circuit.It should be noted that, " just " and " bearing " in positive input signal Vp and negative input signal Vn be only for distinguishing the two-way input signal herein, and the polar relationship of the voltage of non-limiting two-way input signal or electric current, and the two can be for example positive voltage signal.
In the present embodiment, this input switch network 200 comprises switch S 1, switch S 2, switch S 3, switch S 4.Wherein, the first end of switch S 1 receives negative input signal Vn, and the second end connects the input (being specially in the present embodiment the grid of MOS transistor N1) that the first voltage turns current circuit, and its control end receives the first clock signal C H0; The first end of switch S 2 receives positive input signal Vp, and its second end connects the input (being specially in the present embodiment the grid of MOS transistor N1) that the first voltage turns current circuit, and its control end receives second clock signal CL0; The first end of switch S 3 receives positive input signal Vp, and its second end connects the input (being specially the grid of MOS transistor N2 in the present embodiment) that second voltage turns current circuit, and its control end receives the first clock signal C H0; The first end of switch S 4 receives negative input signal Vn, and its second end connects the input (being specially the grid of MOS transistor N2 in the present embodiment) that second voltage turns current circuit, and its control end receives second clock signal CL0.
Current transfer circuit is transmitted for the electric current to 201 outputs of differential input stage circuit, and in the present embodiment, this current transfer circuit comprises the first mirror current source 203, the second mirror current source 204, mirror image pipe N4 and mirror image pipe N5.Wherein, the input of the first mirror current source 203 is connected with the output that the first voltage turns current circuit; The input of the second mirror current source 204 is connected with the output that second voltage turns current circuit.As a nonrestrictive example, the first mirror current source 203 comprises mirror image pipe P1 and mirror image pipe P2; The second mirror current source 204 comprises mirror image pipe P3 and mirror image pipe P4.
It will be appreciated by those skilled in the art that above-mentioned each mirror current source 203,204 can adopt the MOS transistor transmission, also can adopt the triode transmission, can also use amplifier architecture to realize transmitting.
The current delivery switching network comprises: switching network 202, switching network 205 and mirror image pipe switch unit 207, and wherein, switching network 202 comprises switch S 5 and switch S 6; Switching network 205 comprises switch S 7 and S8; Mirror image pipe switch unit 207 comprises switch S 9, switch S 10, switch S 11 and switch S 12; The current mirror relation of 207 couples of mirror image pipe N4 of this mirror image pipe switch unit and mirror image pipe N5 replaces switching, switching state comprises following two kinds: by mirror image pipe N4, be passed to mirror image pipe N5, and be passed to mirror image pipe N4 by mirror image pipe N5, that is to say, under different clock signals is controlled, mirror image pipe N4 and N5 will form mirror current source, and the current mirror relation of the mirror current source formed is also done periodically switching under the control of clock signal.
Furthermore, the first end of switch S 5 connects the output of the first mirror current source 203, and the second end of switch S 5 connects the output of trsanscondutance amplifier, and the control end of switch S 5 receives second clock signal CL0; The first end of switch S 6 connects the output of the first mirror current source 103, and the control end of switch S 6 receives the first clock signal C H0; The first end of switch S 7 connects the output of the second mirror current source 204, the second end of the second end connecting valve S6 of switch S 7, and the control end of switch S 7 receives second clock signal CL0; The first end of switch S 8 connects the output of the second mirror current source 204, the second end of the second end connecting valve S5 of switch S 8, and the control end of switch S 8 receives the first clock signal C H0; The second end of the first end connecting valve S7 of switch S 9, the second end of switch S 9 connects the drain terminal of mirror image pipe N4, and the control end of switch S 9 receives the 4th clock signal C L1; The second end of the first end connecting valve S7 of switch S 10, the second end of switch S 10 connects the drain terminal of mirror image pipe N5, and the control end of switch S 10 receives the 3rd clock signal C H1; The second end of the first end connecting valve S8 of switch S 11, the second end of switch S 11 connects the drain terminal of mirror image pipe N4, and the control end of switch S 11 receives the 3rd clock signal C H1; The second end of the first termination switch S 8 of switch S 12, the second end of switch S 12 connects the drain terminal of mirror image pipe N5, and the control end of switch S 12 receives the 4th clock signal C L1; The grid of mirror image pipe N4 and mirror image pipe N5 is connected and is connected to the second end of switch S 7, the source electrode of mirror image pipe N4 and mirror image pipe N5 link together (for example can ground connection).
In conjunction with Fig. 3 to Fig. 5, the first clock signal C H0, second clock signal CL0, the 3rd clock signal C H1 and the 4th clock signal C L1 can be produced by clock-signal generator 220 simultaneously.This first clock signal C H0 and second clock signal CL0 are periodically, inverting each other and non-overlapping; The 3rd clock signal C H1 and the 4th clock signal C L1 are also periodically, inverting each other and non-overlapping.This clock-signal generator 220 can adopt any suitable structure in prior art to realize.Preferably, this first clock signal C H0, second clock signal CL0, the 3rd clock signal C H1 and the 4th clock signal C L1 can be the square-wave signal of duty ratio 0.5.
As a nonrestrictive example, when as second clock signal CL0, for logic is high, the first clock signal C H0 is logic low, switch S 2, S4, S5, the S7 conducting, switch S 1, S3, S6, S8 disconnects, the first input end of trsanscondutance amplifier meets negative input signal Vn, the second input termination positive input signal Vp of trsanscondutance amplifier, the output of negative input signal Vn and trsanscondutance amplifier is reversed polarity, be that negative input signal Vn adds the lower voltage that conference causes output, the output signal of the output of positive input signal Vp and trsanscondutance amplifier is positive polarity, be that positive input signal Vp adds the voltage rising that conference causes output.
When second clock signal CL0 is that logic low and the first clock signal C H0 are when to be logic high, switch S 1, S3, S6, the S8 conducting, switch S 2, S4, S5, S7 disconnects, the first input end of trsanscondutance amplifier meets positive input signal Vp, the second input termination negative input signal Vn of trsanscondutance amplifier, the output signal of the output of negative input signal Vn and trsanscondutance amplifier still is reversed polarity, be that negative input signal Vn adds the lower voltage that conference causes output, the output signal of the output of positive input signal Vp and trsanscondutance amplifier still is positive polarity, be that positive input signal Vp adds the voltage rising that conference causes output.
Like this, under second clock signal CL0 and the first clock signal C H0 control, the transitive relation of switch current transfer circuit in the input signal received by the input at the switching trsanscondutance amplifier, remain output and the negative input signal Vn reversed polarity of mutual conductance error amplifier, keep output and the positive input signal Vp positive polarity of trsanscondutance amplifier.
While being low at the 4th clock signal C L1 for high the 3rd clock signal C H1, switch S 9, S12 conducting, switch S 10, S11 turn-off, and current mirror is passed to mirror image pipe N5 by mirror image pipe N4; While being high at the 4th clock signal C L1 for low the 3rd clock signal C H1, switch S 9, S12 turn-off, switch S 10, S11 conducting, current mirror is passed to mirror image pipe N4 by mirror image pipe N5, can effectively reduce thus the imbalance that the mismatch due to mirror image pipe N4 and mirror image pipe N5 causes.
Due under clock signal C L0 and CH0 control, mirror image pipe P1 and mirror image pipe P2, mirror image pipe P3 and mirror image pipe P4 are fixedly connected on the difference input drain terminal and the difference of pipe N1 are inputted to the drain terminal to pipe N2, when the difference input receives positive input signal Vp and negative input signal Vn to managing N1 and difference input in turn to pipe N2, mirror image pipe P1 and P2, the electric current of mirror image pipe P3 and P4 is also in turn corresponding to flowing through the electric current of difference input to pipe N1 and N2, according to top identical analysis, mirror image pipe P1 and P2, the clock signal C L0 that the mismatch of mirror image pipe P3 and P4 is also 0.5 in duty ratio and CH0 are eliminated under controlling, therefore, for mirror image pipe P1 and P2, mirror image pipe P3 and P4 do not need to adopt the way of similar mirror image pipe N4 and N5, do not need to carry out the switching of current mirror relation yet.
In trsanscondutance amplifier, the size of current Iout of output is expressed as: Iout=Gm*(Vp-Vn), and the wherein mutual conductance of Gm for setting, the magnitude of voltage that Vp is positive input signal, the magnitude of voltage that Vn is the negative input signal.The correlative factor of the size of mutual conductance Gm has: the difference input is inputted the size to pipe N2, the size of resistance R 1 and resistance R 2, mirror image pipe P1 and mirror image pipe P2 size, mirror image pipe P3 and mirror image pipe P4 size, mirror image pipe N4 and mirror image pipe N5 size to pipe N1 and difference.
When requiring mutual conductance Gm precision higher, need the difference input to input the symmetry to pipe N2, resistance R 1 and resistance R 2 symmetries, mirror image pipe P1 and mirror image pipe P2 symmetry, mirror image pipe P3 and mirror image pipe P4 symmetry, mirror image pipe N4 and mirror image pipe N5 symmetry to pipe N1 and difference.Above symmetrical device in fact can not be accomplished full symmetric, can have imbalance, thereby can cause the imbalance of amplifier.When the trsanscondutance amplifier of imbalance is controlled as loop, can cause the reduction of control precision, affect the consistency of circuit.For example, for constant voltage, controlling is constant voltage generation deviation, and for constant current, controlling is constant current generation deviation, for permanent power, is firm power generation deviation, etc.
Suppose, the differential input stage circuit mismatch of trsanscondutance amplifier causes under identical positive input signal Vp, negative input signal Vn, flows through the difference input electric current of managing N1 is greater than and flows through the electric current of difference input to pipe N2.When adopting that periodically non-overlapping a pair of inversion clock signal CL0 and CH0 control switching, because the difference input of trsanscondutance amplifier receives positive input signal Vp and negative input signal Vn in turn to pipe N1 and N2.When negative input signal Vn transfers to the difference input to pipe N1, the electric current that negative input signal Vn is corresponding is relatively large; When positive input signal Vp is connected to the difference input to pipe N1, the electric current that positive input signal Vp is corresponding is relatively large.If it is 0.5 that the duty ratio of second clock signal CL0 and the first clock signal C H0 is set, in whole one-period, the imbalance of the electric current that the negative input signal Vn caused due to the differential input stage circuit and positive input signal Vp are corresponding will be repealed by implication, and greatly improve the consistency of circuit.
From above scheme, the major function of differential input stage circuit 201 is that voltage transitions is become to electric current, and the major function of current transfer circuit is transmitted electric current, therefore, can replace differential input stage circuit 201 by the voltage transitions electric current structure of any appropriate format, can replace current transfer circuit by the current delivery structure of any appropriate format, include but not limited to various current-mirror structure.
With reference to figure 6, Fig. 6 shows the LED constant-current drive circuit of the present embodiment, comprising: constant-current control circuit 900, transformer T1, switching tube M1, sampling resistor Rcs, sustained diode 2, output capacitance Cbulk.Wherein, the Same Name of Ends of the former limit winding L 2 of transformer T1 receives input voltage vin, and the different name end of the secondary winding L 3 of transformer T1 connects the positive pole of sustained diode 2, the Same Name of Ends ground connection of secondary winding L 3; The drain electrode of switching tube M1 connects the different name end of former limit winding L 2, and the grid of switching tube M1 connects the output of constant-current control circuit 900; The source electrode of the first end connecting valve pipe M1 of sampling resistor Rcs and the sampling input of constant-current control circuit 900, the second end ground connection of sampling resistor Rcs; The first end of output capacitance Cbulk connects the negative pole of sustained diode 2, the second end ground connection of output capacitance Cbulk.It should be noted that, " ground connection " refers to and is connected to conventional ground herein, and non-floating ground.
Furthermore, constant-current control circuit 900 comprises: trsanscondutance amplifier 901, pwm signal generation circuit 902, logic and driver circuitry 903, output equivalent Current calculation circuit 904 and peak sampling hold circuit 905.。
Wherein, the input of peak sampling hold circuit 905 connects the sampling input of constant-current control circuit 900, and the sampled voltage on sampling resistor Rcs is sampled; The input of output equivalent Current calculation circuit 904 is connected with the output of peak sampling hold circuit 905, and the sampled voltage obtained according to employing calculates the output equivalent electric current, and output means the equivalent voltage of this output equivalent electric current; The first input end of trsanscondutance amplifier 901 connects the output of output equivalent Current calculation circuit 904, and its second input receives reference voltage Vref 1, and equivalent voltage and reference voltage Vref 1 are carried out to the error amplification; The input of pwm signal generation circuit 902 connects the output of trsanscondutance amplifier 901, according to the error signal of trsanscondutance amplifier 901 outputs, produces pwm signal GT1, and the duty ratio of this pwm signal GT1 is regulated by above-mentioned error signal; The input of logic and driver circuitry 903 connects the output of pwm signal generation circuit 902, pwm signal GT1 obtains driving signal GT after processing via this logic and driver circuitry 903, this driving signal GT transfers to the grid of switching tube M1, in order to the turn-on and turn-off of control switch pipe M1.
In addition, this constant-current control circuit 900 can also have compensation port COMP, and this compensation port COMP is connected with the output of trsanscondutance amplifier 901 and the input of pwm signal generation circuit 902.This compensation port COMP can external compensating element,, for example, by resistance, capacitances in series or be formed in parallel.
The structure of the trsanscondutance amplifier 901 in Fig. 6 is the transconductance amplifier circuit structure shown in Fig. 3, no longer elaborates here.Because trsanscondutance amplifier 901 adopts input switch networks and the current delivery switching network bang path of switched differential input stage circuit and mirror current source in turn, therefore can significantly improve the consistency of output current.
It will be appreciated by those skilled in the art that Fig. 6 is only signal, in fact, the trsanscondutance amplifier structure of the present embodiment can be applied in any LED drive circuit that comprises trsanscondutance amplifier.
The above, be only preferred embodiment of the present invention, not the present invention done to any pro forma restriction.Therefore, every content that does not break away from technical solution of the present invention, just according to technical spirit of the present invention to any simple modification made for any of the above embodiments, the conversion that is equal to, all still belong in the protection range of technical solution of the present invention.
Claims (9)
1. a trsanscondutance amplifier, is characterized in that, comprising:
The differential input stage circuit, comprise that the first voltage turns current circuit and second voltage turns current circuit;
Current transfer circuit, the electric current that described differential input stage circuit is exported is transmitted;
The input switch network, switched positive input signal and the negative input signal of input, makes described positive input signal and negative input signal alternately input to described the first voltage and turn the input that current circuit and second voltage turn current circuit;
The current delivery switching network, switched the current delivery path of described current transfer circuit, makes the output signal of described trsanscondutance amplifier and described positive input signal keep positive polarity, and keep reversed polarity with described negative input signal;
Clock-signal generator, produce periodically non-the first overlapping clock signal and second clock signal, this first clock signal and second clock signal inversion, this first clock signal and second clock signal are for controlling described input switch network and current delivery switching network, described clock-signal generator also produces periodically non-the 3rd overlapping clock signal and the 4th clock signal, the 3rd clock signal and the 4th clock signal are anti-phase, and the 3rd clock signal and the 4th clock signal are for controlling described current delivery switching network.
2. trsanscondutance amplifier according to claim 1, is characterized in that, described input switch network comprises:
The first switch, its first end receives described negative input signal, and its second end connects the input that described the first voltage turns current circuit, and its control end receives described the first clock signal;
Second switch, its first end receives described positive input signal, and its second end connects the input that described the first voltage turns current circuit, and its control end receives described second clock signal;
The 3rd switch, its first end receives described positive input signal, and its second end connects the input that described second voltage turns current circuit, and its control end receives described the first clock signal;
The 4th switch, its first end receives described negative input signal, and its second end connects the input that described second voltage turns current circuit, and its control end receives described second clock signal.
3. trsanscondutance amplifier according to claim 1, is characterized in that,
Described current transfer circuit comprises:
The first mirror current source, its input is connected with the output that described the first voltage turns current circuit;
The second mirror current source, its input is connected with the output that described second voltage turns current circuit;
The first mirror image tube;
The second mirror image pipe, its source electrode is connected with the source electrode of described first mirror image tube, and its grid is connected with the grid of described first mirror image tube;
Described current delivery switching network comprises:
The 5th switch, its first end connects the output of described the first mirror current source, and its second end connects the output of described trsanscondutance amplifier, and its control end receives described second clock signal;
The 6th switch, its first end connects the output of described the first mirror current source, and its control end receives described the first clock signal;
Minion is closed, and its first end connects the output of described the second mirror current source, and its second end connects the second end of described the 6th switch, and its control end receives described second clock signal;
The 8th switch, its first end connects the output of described the second mirror current source, and its second end connects the second end of described the 5th switch, and its control end receives described the first clock signal;
The 9th switch, its first end connects the second end that described minion is closed, and its second end connects the drain electrode of described first mirror image tube, and its control end receives described the 4th clock signal;
The tenth switch, its first end connects the second end of described minion pass and the grid of described first mirror image tube and the second mirror image pipe, and its second end connects the drain electrode of described the second mirror image pipe, and its control end receives described the 3rd clock signal;
The 11 switch, its first end connects the second end of described the 8th switch, and its second end connects the drain electrode of described first mirror image tube, and its control end receives described the 3rd clock signal;
Twelvemo is closed, and its first end connects the second end of described the 8th switch, and its second end connects the drain electrode of described the second mirror image pipe, and its control end receives described the 4th clock signal.
4. trsanscondutance amplifier according to claim 1, is characterized in that, the duty ratio of described the first clock signal, second clock signal, the 3rd clock signal and the 4th clock signal is 0.5.
5. trsanscondutance amplifier according to claim 1, is characterized in that, described the first voltage turns current circuit and comprises that the first difference input is to pipe, and described second voltage turns current circuit and comprises that the second difference input is to pipe.
6. trsanscondutance amplifier according to claim 5, is characterized in that, described the first differential pair tube is connected with the first resistance, and described the second differential pair tube is connected with the second resistance.
7. trsanscondutance amplifier according to claim 5, is characterized in that, described the first difference input is nmos pass transistor, NPN triode, PMOS transistor or PNP triode to pipe and the input of the second difference to pipe.
8. a LED constant-current drive circuit, is characterized in that, comprises the described trsanscondutance amplifier of any one in claim 1 to 7.
9. LED constant-current drive circuit according to claim 8, is characterized in that, described LED constant-current drive circuit comprises constant-current control circuit, transformer, switching tube, sampling resistor, fly-wheel diode and output capacitance, wherein,
The Same Name of Ends of the former limit winding of described transformer receives input voltage, the Same Name of Ends ground connection of the secondary winding of described transformer, and the different name end of the secondary winding of described transformer connects the positive pole of described fly-wheel diode;
The drain electrode of described switching tube connects the different name end of the former limit winding of described transformer, and the grid of described switching tube connects the output of described constant-current control circuit;
The first end of described sampling resistor connects the source electrode of described switching tube and the sampling input of described constant-current control circuit, the second end ground connection of described sampling resistor;
The first end of described output capacitance connects the negative pole of described fly-wheel diode, the second end ground connection of described output capacitance,
Described constant-current control circuit comprises:
Peak sampling hold circuit, its input connects the sampling input of described constant-current control circuit, and the sampled voltage on described sampling resistor is sampled;
Output equivalent Current calculation circuit, its input is connected with the output of described peak sampling hold circuit, according to described sampled voltage, calculates the output equivalent electric current, and output means the equivalent voltage of this output equivalent electric current;
The described trsanscondutance amplifier of any one in claim 1 to 7, its first input end connects the output of described output equivalent Current calculation circuit, and its second input receives reference voltage, and described equivalent voltage and reference voltage are carried out to the error amplification;
Pwm signal generation circuit, its input connects the output of described trsanscondutance amplifier, according to the error signal of described trsanscondutance amplifier output, produces pwm signal, and the duty ratio of described pwm signal is regulated by described error signal;
Logic and driver circuitry, its input connects the output of described pwm signal generation circuit, and described pwm signal transfers to the grid of described switching tube via this logic and driver circuitry.
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Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104238614A (en) * | 2014-09-03 | 2014-12-24 | 李倩 | Reference voltage circuit |
| CN109275233A (en) * | 2018-11-12 | 2019-01-25 | 厦门芯达茂微电子有限公司 | Determine power LED driver |
| CN111867183A (en) * | 2019-04-08 | 2020-10-30 | 华润矽威科技（上海）有限公司 | LED drive circuit, power frequency square wave signal sampling circuit and method |
| CN113014074A (en) * | 2021-02-25 | 2021-06-22 | 杭州士兰微电子股份有限公司 | Constant current control circuit, constant current drive circuit and constant current control method |
| CN113114179A (en) * | 2021-03-18 | 2021-07-13 | 杭州士兰微电子股份有限公司 | Comparator circuit, constant current control circuit and constant current drive circuit |
| CN113473671A (en) * | 2021-07-28 | 2021-10-01 | 上海晶丰明源半导体股份有限公司 | Control circuit for constant current type drive circuit and constant current type drive circuit |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101313468A (en) * | 2005-11-21 | 2008-11-26 | 松下电器产业株式会社 | Fully differential comparator and fully differential amplifier |
| CN101394163A (en) * | 2008-10-09 | 2009-03-25 | 捷顶微电子（上海）有限公司 | Signal conditioning circuit and dual sampling-hold circuit applying the conditioning method |
| CN101930706A (en) * | 2009-06-25 | 2010-12-29 | 索尼公司 | Signal-line driving circuit, display apparatus and electronic apparatus |
| WO2013021873A1 (en) * | 2011-08-05 | 2013-02-14 | シャープ株式会社 | Display drive circuit, display device and method for driving display drive circuit |
| CN203504817U (en) * | 2013-09-12 | 2014-03-26 | 杭州士兰微电子股份有限公司 | Transconductance amplifier and LED constant current drive circuit |
-
2013
- 2013-09-12 CN CN201310415096.3A patent/CN103458586B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101313468A (en) * | 2005-11-21 | 2008-11-26 | 松下电器产业株式会社 | Fully differential comparator and fully differential amplifier |
| CN101394163A (en) * | 2008-10-09 | 2009-03-25 | 捷顶微电子（上海）有限公司 | Signal conditioning circuit and dual sampling-hold circuit applying the conditioning method |
| CN101930706A (en) * | 2009-06-25 | 2010-12-29 | 索尼公司 | Signal-line driving circuit, display apparatus and electronic apparatus |
| WO2013021873A1 (en) * | 2011-08-05 | 2013-02-14 | シャープ株式会社 | Display drive circuit, display device and method for driving display drive circuit |
| CN203504817U (en) * | 2013-09-12 | 2014-03-26 | 杭州士兰微电子股份有限公司 | Transconductance amplifier and LED constant current drive circuit |
Cited By (9)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN104238614A (en) * | 2014-09-03 | 2014-12-24 | 李倩 | Reference voltage circuit |
| CN109275233A (en) * | 2018-11-12 | 2019-01-25 | 厦门芯达茂微电子有限公司 | Determine power LED driver |
| CN109275233B (en) * | 2018-11-12 | 2024-04-23 | 厦门芯达茂微电子有限公司 | Constant-power LED driver |
| CN111867183A (en) * | 2019-04-08 | 2020-10-30 | 华润矽威科技（上海）有限公司 | LED drive circuit, power frequency square wave signal sampling circuit and method |
| CN113014074A (en) * | 2021-02-25 | 2021-06-22 | 杭州士兰微电子股份有限公司 | Constant current control circuit, constant current drive circuit and constant current control method |
| CN113014074B (en) * | 2021-02-25 | 2022-07-29 | 杭州士兰微电子股份有限公司 | Constant current control circuit, constant current drive circuit and constant current control method |
| CN113114179A (en) * | 2021-03-18 | 2021-07-13 | 杭州士兰微电子股份有限公司 | Comparator circuit, constant current control circuit and constant current drive circuit |
| CN113473671A (en) * | 2021-07-28 | 2021-10-01 | 上海晶丰明源半导体股份有限公司 | Control circuit for constant current type drive circuit and constant current type drive circuit |
| US11839002B2 (en) | 2021-07-28 | 2023-12-05 | Shanghai Bright Power Semiconductor Co., Ltd. | Control circuit for constant-current drive circuit and constant-current drive circuit |
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