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Search Results (227)

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17 pages, 15611 KiB  
Article
A Reading Range- and Frequency-Reconfigurable Antenna for Near-Field and Far-Field UHF RFID Applications
by Chenyang Song and Zhipeng Wu
Sensors 2025, 25(2), 408; https://doi.org/10.3390/s25020408 - 11 Jan 2025
Viewed by 488
Abstract
In radio frequency identification (RFID), differences in spectrum policies and tag misreading in different countries are the two main issues that limit its application. To solve these problems, this article proposes a composite right/left-handed transmission line (CRLH-TL)-based reconfigurable antenna for ultra-high frequency near-field [...] Read more.
In radio frequency identification (RFID), differences in spectrum policies and tag misreading in different countries are the two main issues that limit its application. To solve these problems, this article proposes a composite right/left-handed transmission line (CRLH-TL)-based reconfigurable antenna for ultra-high frequency near-field and far-field RFID reader applications. The CRLH-TL is achieved using a periodically capacitive gap-loaded parallel plate line. By deploying the CRLH-TL operating at zeroth-order resonance, a loop antenna with in-phase radiating current is obtained, which contributes to a strong and uniform H-field and a horizontally polarized omnidirectional radiation pattern. By introducing additional tunable components, frequency and reading range reconfigurabilities are enabled. The frequency tuning range is from 833 MHz to 979 MHz, which covers the worldwide UHF RFID band. Moreover, each operation mode has a narrow frequency band, which means it can operate without violating different countries’ radio frequency policy and reduce the design difficulty of designing multiple versions of a reader. Both the near-field interrogation zone and maximum far-field reading distance of the antenna are adjustable. The near-field interrogation zone is 400 mm × 400 mm × 50 mm and can be further confined. The tuning range for far-field reading distance is from 2.71 m to 0.35 m. Full article
(This article belongs to the Special Issue RFID and Zero-Power Backscatter Sensors)
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Figure 1
<p>The equivalent circuit of the CRLH transmission line.</p>
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<p>(<b>a</b>) Periodically capacitive gap-loaded parallel plate line; (<b>b</b>) equivalent circuit of capacitive-loaded parallel plate line; (<b>c</b>) simulated and analyzed S<sub>21</sub>.</p>
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<p>The proposed CRLH-TL loop antenna: (<b>a</b>) top view; (<b>b</b>) bottom view; (<b>c</b>) single unit.</p>
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<p>The impedance diagram of the ZPSL loop antenna: (<b>a</b>) resistance with varying width; (<b>b</b>) reactance with varying width; (<b>c</b>) resistance with varying radius; (<b>d</b>) reactance with varying radius; (<b>e</b>) resistance with varying arc angle; (<b>f</b>) reactance with varying arc angle.</p>
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<p>The impedance diagram of the ZPSL loop antenna: (<b>a</b>) resistance with varying width; (<b>b</b>) reactance with varying width; (<b>c</b>) resistance with varying radius; (<b>d</b>) reactance with varying radius; (<b>e</b>) resistance with varying arc angle; (<b>f</b>) reactance with varying arc angle.</p>
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<p>Simulated surface current of the designed CRLH-TL loop antenna at ZOR.</p>
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<p>Fabricated CRLH-TL antenna.</p>
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<p>Simulated and measured S<sub>11</sub> values of the proposed CRLH-TL loop antenna.</p>
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<p>Simulated and measured far-field gain of the proposed CRLH-TL loop antenna: (<b>a</b>) E-plane; (<b>b</b>) H-plane.</p>
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<p>The proposed reconfigurable CRLH-TL loop antenna: (<b>a</b>) top view; (<b>b</b>) bottom view; (<b>c</b>) single unit; (<b>d</b>) equivalent circuit.</p>
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<p>Surface current distribution of the proposed reconfigurable antenna.</p>
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<p>Simulated and measured S11 of the proposed reconfigurable antenna in different operation modes.</p>
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<p>Simulated vertical H-field (|H<sub>Z</sub>|) distributions on the X-Y plane and X-Z plane at different reading distances of the proposed reconfigurable antenna.</p>
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<p>Simulated and measured far-field gain of the reconfigurable antenna at 866.5 MHz: (<b>a</b>) E-plane; (<b>b</b>) H-plane.</p>
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<p>(<b>a</b>) Prototyped reconfigurable CRLH-TL loop antenna; (<b>b</b>) experiment setup.</p>
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<p>Gain and maximum reading distance of the designed reconfigurable antenna.</p>
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<p>Near-field tag detection rate of the proposed reconfigurable antenna.</p>
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<p>Near-field tag detection zone at different reading heights.</p>
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20 pages, 7167 KiB  
Article
Accelerating Deep Learning-Based Morphological Biometric Recognition with Field-Programmable Gate Arrays
by Nourhan Zayed, Nahed Tawfik, Mervat M. A. Mahmoud, Ahmed Fawzy, Young-Im Cho and Mohamed S. Abdallah
AI 2025, 6(1), 8; https://doi.org/10.3390/ai6010008 - 9 Jan 2025
Viewed by 627
Abstract
Convolutional neural networks (CNNs) are increasingly recognized as an important and potent artificial intelligence approach, widely employed in many computer vision applications, such as facial recognition. Their importance resides in their capacity to acquire hierarchical features, which is essential for recognizing complex patterns. [...] Read more.
Convolutional neural networks (CNNs) are increasingly recognized as an important and potent artificial intelligence approach, widely employed in many computer vision applications, such as facial recognition. Their importance resides in their capacity to acquire hierarchical features, which is essential for recognizing complex patterns. Nevertheless, the intricate architectural design of CNNs leads to significant computing requirements. To tackle these issues, it is essential to construct a system based on field-programmable gate arrays (FPGAs) to speed up CNNs. FPGAs provide fast development capabilities, energy efficiency, decreased latency, and advanced reconfigurability. A facial recognition solution by leveraging deep learning and subsequently deploying it on an FPGA platform is suggested. The system detects whether a person has the necessary authorization to enter/access a place. The FPGA is responsible for processing this system with utmost security and without any internet connectivity. Various facial recognition networks are accomplished, including AlexNet, ResNet, and VGG-16 networks. The findings of the proposed method prove that the GoogLeNet network is the best fit due to its lower computational resource requirements, speed, and accuracy. The system was deployed on three hardware kits to appraise the performance of different programming approaches in terms of accuracy, latency, cost, and power consumption. The software programming on the Raspberry Pi-3B kit had a recognition accuracy of around 70–75% and relied on a stable internet connection for processing. This dependency on internet connectivity increases bandwidth consumption and fails to meet the required security criteria, contrary to ZYBO-Z7 board hardware programming. Nevertheless, the hardware/software co-design on the PYNQ-Z2 board achieved an accuracy rate of 85% to 87%. It operates independently of an internet connection, making it a standalone system and saving costs. Full article
(This article belongs to the Special Issue Artificial Intelligence-Based Image Processing and Computer Vision)
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<p>AT &amp; T dataset (downloaded from <a href="https://www.kaggle.com/datasets/kasikrit/att-database-of-faces" target="_blank">https://www.kaggle.com/datasets/kasikrit/att-database-of-faces</a>; accessed on 13 October 2024).</p>
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<p>PYNQ-Z2.</p>
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<p>Zybo Z7-20 Zynq-7000 SoC development board.</p>
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<p>Raspberry Pi 3 Model B.</p>
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<p>OV7670 camera module.</p>
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<p>A flowchart of the proposed model.</p>
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<p>Top level block diagram. The light blue block (3) is a regular IP, while blue blocks (1, 2, and 4) are hierarchy blocks, grouping IP blocks together. Block no. 1, named camera_in, is the original data producer. It groups together the IP blocks needed to decode image data coming from the camera and to format it to suit our needs. Block no. 2, named video_out, is the ultimate data consumer. It groups IP blocks doing DVI encoding, so that the image data can be displayed on a monitor. We are going to look at these two hierarchy blocks later. Block no. 3 is an actual IP, named axi_vdma. It is a Xilinx IP with the full name AXI Video Direct Memory Access. VDMA sits in the middle of the video data flow, and its central role makes it an interesting addition. It is needed to decouple two incompatible video interfaces, the image sensor’s MIPI CSI-2 and the monitor’s DVI.</p>
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<p>The hierarchy of the control block, which illustrates, the input, output, and control interfaces modelled in C/C++.</p>
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<p>AlexNet accuracy.</p>
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<p>AlexNet loss.</p>
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<p>ResNet18 accuracy.</p>
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<p>ResNet18 loss.</p>
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<p>Accuracy of the VGG16 network.</p>
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<p>Loss curve of the VGG16 network.</p>
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<p>GoogLeNet accuracy.</p>
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<p>GoogLeNet loss curve.</p>
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22 pages, 315 KiB  
Article
Globalization and the Fallout of the COVID-19 Pandemic
by Pascal L. Ghazalian
World 2025, 6(1), 4; https://doi.org/10.3390/world6010004 - 1 Jan 2025
Viewed by 863
Abstract
The COVID-19 pandemic has significantly impacted globalization by disrupting the course of international economic integration, reducing interpersonal interaction and communication, and lessening the significance of global governance and political interactions. This unprecedented event has altered global supply chains, MNEs’ operations and FDI, and [...] Read more.
The COVID-19 pandemic has significantly impacted globalization by disrupting the course of international economic integration, reducing interpersonal interaction and communication, and lessening the significance of global governance and political interactions. This unprecedented event has altered global supply chains, MNEs’ operations and FDI, and trade patterns, and it has favored protectionist and border policies. Meanwhile, travel restrictions and social-distancing measures reduced human mobility and hindered intercultural exchanges. This study explores the short-term and long-term effects of the COVID-19 pandemic on economic globalization while also reflecting on its implications for social and political globalization. The analysis underlines that the COVID-19 pandemic has encouraged many governments to assess their strategies vis-à-vis globalization by seeking a certain equilibrium between global engagement, regional retreat, and national seclusion. Despite the adverse implications, some positive outcomes have emerged via the COVID-19-induced digital transformation and the reconfiguration of the global supply chains to improve resilience against future exogenous shocks. This pandemic exposed the shortcomings of the current global system and emphasized the necessity for a post-COVID-19 “re-designed” globalization to mitigate anti-globalization sentiments and expand benefits across countries/geo-economic regions and different segments of society. Full article
17 pages, 4791 KiB  
Article
Photoreconfigurable Metasurface for Independent Full-Space Control of Terahertz Waves
by Zhengxuan Jiang, Guowen Ding, Xinyao Luo and Shenyun Wang
Sensors 2025, 25(1), 119; https://doi.org/10.3390/s25010119 - 27 Dec 2024
Viewed by 728
Abstract
We present a novel photoreconfigurable metasurface designed for independent and efficient control of electromagnetic waves with identical incident polarization and frequency across the entire spatial domain. The proposed metasurface features a three-layer architecture: a top layer incorporating a gold circular split ring resonator [...] Read more.
We present a novel photoreconfigurable metasurface designed for independent and efficient control of electromagnetic waves with identical incident polarization and frequency across the entire spatial domain. The proposed metasurface features a three-layer architecture: a top layer incorporating a gold circular split ring resonator (CSRR) filled with perovskite material and dual C-shaped perovskite resonators; a middle layer of polyimide dielectric; and a bottom layer comprising a perovskite substrate with an oppositely oriented circular split ring resonator filled with gold. By modulating the intensity of a laser beam, we achieve autonomous manipulation of incident circularly polarized terahertz waves in both transmission and reflection modes. Simulation results demonstrate that the metasurface achieves a cross-polarized transmission coefficient of 0.82 without laser illumination and a co-polarization reflection coefficient of 0.8 under laser illumination. Leveraging the geometric phase principle, adjustments to the rotational orientation of the reverse split ring and dual C-shaped perovskite structures enable independent control of transmission and reflection phases. Furthermore, the proposed metasurface induces a +1 order orbital angular momentum in transmission and +2 order in reflection, facilitating beam deflection through metasurface convolution principles. Imaging using metasurface digital imaging technology showcases patterns “NUIST” in reflection and “LOONG” in transmission, illustrating the metasurface design principles via the proposed metasurface. The proposed metasurface’s capability for full-space control and reconfigurability presents promising applications in advanced imaging systems, dynamic beam steering, and tunable terahertz devices, highlighting its potential for future technological advancements. Full article
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<p>(<b>a</b>) OAM Mode 1 in transmission mode under high laser beam illumination for Metasurface I. (<b>b</b>) OAM Mode 2 in reflection mode without laser beam illumination for Metasurface I. (<b>c</b>) Holographic imaging with high laser beam illumination, generating a holographic image of the letters “NUIST” in reflection mode for Metasurface II. (<b>d</b>) Holographic imaging without laser beam illumination, generating a holographic image of the letters “LOONG” in transmission mode for Metasurface II.</p>
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<p>(<b>a</b>) Schematic of the proposed three-layer metasurface. (<b>b</b>) Top layer with CSRR and dual <span class="html-italic">C</span>-shaped resonators. (<b>c</b>) Bottom layer with circular split ring resonator.</p>
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<p>(<b>a</b>) Phase of co-polarized reflection coefficients (<span class="html-italic">r<sub>xx</sub></span> and <span class="html-italic">r<sub>yy</sub></span>) and co-polarized transmission coefficients (<span class="html-italic">t<sub>xx</sub></span> and <span class="html-italic">t<sub>yy</sub></span>) under laser beam illumination. (<b>b</b>) Phase of co-polarized reflection coefficients (<span class="html-italic">r<sub>xx</sub></span> and <span class="html-italic">r<sub>yy</sub></span>) and co-polarized transmission coefficients (<span class="html-italic">t<sub>xx</sub></span> and <span class="html-italic">t<sub>yy</sub></span>) without laser beam illumination. (<b>c</b>) Amplitude of co-polarized transmission coefficients (<span class="html-italic">t<sub>xx</sub></span> and <span class="html-italic">t<sub>yy</sub></span>) and co-polarized transmission coefficients (<span class="html-italic">t<sub>xx</sub></span> and <span class="html-italic">t<sub>yy</sub></span>) under laser beam illumination. (<b>d</b>) Amplitude of co-polarized transmission coefficients (<span class="html-italic">t<sub>xx</sub></span> and <span class="html-italic">t<sub>yy</sub></span>) and co-polarized transmission coefficients (<span class="html-italic">t<sub>xx</sub></span> and <span class="html-italic">t<sub>yy</sub></span>) without laser beam illumination.</p>
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<p>(<b>a</b>) Reflection amplitude and transmission amplitude at different rotation angles when unit is under laser beam illumination. (<b>b</b>) Transmission amplitude and reflection amplitude at different rotation angles when unit is without laser beam illumination. (<b>c</b>) Reflection phase at different rotation angles when unit is under laser beam illumination. (<b>d</b>) Transmission phase at different rotation angles when unit is without laser beam illumination.</p>
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<p>(<b>a</b>) Surface current distribution on the top layer under strong laser beam illumination, showing time-varying current distribution within the period. (<b>b</b>) Surface current distribution on the bottom layer under strong laser beam illumination, showing time-varying current distribution within the period. (<b>c</b>) Surface current distribution on the top layer without laser beam illumination, showing time-varying current distribution within the period. (<b>d</b>) Surface current distribution on the bottom layer without laser beam illumination, showing time-varying current distribution within the period.</p>
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<p>(<b>a</b>) Phase gradients along the +<span class="html-italic">x</span> direction. (<b>b</b>) Phase gradients along the −<span class="html-italic">x</span> direction. (<b>c</b>) Far-field distribution of a +1 order vortex beam deflected by 30° in the +<span class="html-italic">x</span> direction under strong laser beam illumination. (<b>d</b>) Far-field distribution of a −2 order vortex beam deflected by 30° in the −<span class="html-italic">x</span> direction without laser beam illumination. (<b>e</b>) Planar electric field intensity and phase distribution of the +1 order vortex beam under strong laser beam illumination, perpendicular to the 30° direction. (<b>f</b>) Planar electric field intensity and phase distribution of the −2 order vortex beam without laser beam illumination, perpendicular to the −30° direction.</p>
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<p>(<b>a</b>) Target images: “Zhu” in reflection mode, “Long” in transmission mode. (<b>b</b>) Phase distribution for holographic images, with phase changes from 0° to 360°. (<b>c</b>) Metasurface design layout with 50 × 50 unit structures in top and bottom layers. (<b>d</b>) Simulation results under different laser beam illumination: “Zhu” in reflection mode under laser beam illumination; “Long” in transmission mode without laser beam illumination.</p>
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<p>(<b>a</b>) Target images in reflection mode. (<b>b</b>) Phase distribution for reflection mode calculated using the GS algorithm. (<b>c</b>) Reproduced image of “NUIST” in reflection mode. (<b>d</b>) Target images in transmission mode. (<b>e</b>) Phase distribution for transmission mode calculated using the GS algorithm. (<b>f</b>) Reproduced image of “LOOGN” in transmission mode.</p>
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<p>(<b>a</b>) Near-field imaging results. (<b>b</b>) Far-field electric field distribution in reflection mode. (<b>c</b>) Far-field electric field distribution in transmission mode.</p>
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29 pages, 1433 KiB  
Article
Sparse Convolution FPGA Accelerator Based on Multi-Bank Hash Selection
by Jia Xu, Han Pu and Dong Wang
Micromachines 2025, 16(1), 22; https://doi.org/10.3390/mi16010022 - 27 Dec 2024
Viewed by 555
Abstract
Reconfigurable processor-based acceleration of deep convolutional neural network (DCNN) algorithms has emerged as a widely adopted technique, with particular attention on sparse neural network acceleration as an active research area. However, many computing devices that claim high computational power still struggle to execute [...] Read more.
Reconfigurable processor-based acceleration of deep convolutional neural network (DCNN) algorithms has emerged as a widely adopted technique, with particular attention on sparse neural network acceleration as an active research area. However, many computing devices that claim high computational power still struggle to execute neural network algorithms with optimal efficiency, low latency, and minimal power consumption. Consequently, there remains significant potential for further exploration into improving the efficiency, latency, and power consumption of neural network accelerators across diverse computational scenarios. This paper investigates three key techniques for hardware acceleration of sparse neural networks. The main contributions are as follows: (1) Most neural network inference tasks are typically executed on general-purpose computing devices, which often fail to deliver high energy efficiency and are not well-suited for accelerating sparse convolutional models. In this work, we propose a specialized computational circuit for the convolutional operations of sparse neural networks. This circuit is designed to detect and eliminate the computational effort associated with zero values in the sparse convolutional kernels, thereby enhancing energy efficiency. (2) The data access patterns in convolutional neural networks introduce significant pressure on the high-latency off-chip memory access process. Due to issues such as data discontinuity, the data reading unit often fails to fully exploit the available bandwidth during off-chip read and write operations. In this paper, we analyze bandwidth utilization in the context of convolutional accelerator data handling and propose a strategy to improve off-chip access efficiency. Specifically, we leverage a compiler optimization plugin developed for Vitis HLS, which automatically identifies and optimizes on-chip bandwidth utilization. (3) In coefficient-based accelerators, the synchronous operation of individual computational units can significantly hinder efficiency. Previous approaches have achieved asynchronous convolution by designing separate memory units for each computational unit; however, this method consumes a substantial amount of on-chip memory resources. To address this issue, we propose a shared feature map cache design for asynchronous convolution in the accelerators presented in this paper. This design resolves address access conflicts when multiple computational units concurrently access a set of caches by utilizing a hash-based address indexing algorithm. Moreover, the shared cache architecture reduces data redundancy and conserves on-chip resources. Using the optimized accelerator, we successfully executed ResNet50 inference on an Intel Arria 10 1150GX FPGA, achieving a throughput of 497 GOPS, or an equivalent computational power of 1579 GOPS, with a power consumption of only 22 watts. Full article
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<p>TPU architecture diagram, subfigure (<b>a</b>) illustrates the overall TPU architecture design. (<b>b</b>) illustrates the structure of the compute unit in each PE. [<a href="#B21-micromachines-16-00022" class="html-bibr">21</a>].</p>
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<p>Illustration of how sparse convolution is conducted.</p>
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<p>The overall architecture of proposed accelerator.</p>
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<p>Channel non-zero number(workload) in VGG16.</p>
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<p>Channel work balance over PE.</p>
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<p>Bank execute order intra PE.</p>
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<p>Prefetch window parallelism scheme.</p>
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<p>Intra channel array partitioning scheme.</p>
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<p>Synchronization scheme of parallel convolution tasks.</p>
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<p>Serialization of partial sum based on streaming.</p>
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<p>Sliding-window based fetching approach of Feature Map data.</p>
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<p>Multiple bank R/W design.</p>
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<p>Overall architecture of hash shared memory execution diagram.</p>
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<p>Data structure of stored weight file.</p>
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<p>Weight encoding scheme.</p>
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<p>Data format of quantization table.</p>
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<p>DSE of the shared memory bank selection.</p>
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<p>DSE of the design parameters. (<b>a</b>) shows the DSPs usage over <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> </semantics></math> after floorplanning. And the roofline limited by device is marked as dotted line. (<b>b</b>) shows the wall time of network reference over <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> </semantics></math>. The optimum design is marked in a red star. (<b>c</b>) shows the ALUTs usage with the increase of the parallel. and (<b>d</b>) shows the on-chip RAMs usage over <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>i</mi> <mi>n</mi> </mrow> </msub> </semantics></math>, and the optimum design is found by the elimination of device resource, marked in red star.</p>
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<p>Efficiency of different kernel and Feature Map size.</p>
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<p>Comparision of the measured time, theoretic time, and efficiency.</p>
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<p>Roofline Model data point.</p>
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31 pages, 49053 KiB  
Article
The Baroque Religious Architecture of Paredes de Coura, Portugal, and the Transformation of the Territory
by Fátima Matos Silva and Carlos Gouveia da Silva
Religions 2024, 15(12), 1563; https://doi.org/10.3390/rel15121563 - 21 Dec 2024
Viewed by 921
Abstract
This study explores the intricate relationship between Baroque religious architecture and the transformation of the territory in Paredes de Coura, Portugal. Between the second half of the 17th century and the first half of the 19th century, Paredes de Coura, located in northern [...] Read more.
This study explores the intricate relationship between Baroque religious architecture and the transformation of the territory in Paredes de Coura, Portugal. Between the second half of the 17th century and the first half of the 19th century, Paredes de Coura, located in northern Portugal, gradually transformed its religious spaces and buildings. Parish communities and private initiatives, driven by a deep religious motivation and favourable conjuncture factors, rebuilt, enlarged, and built dozens of chapels and churches from scratch, mostly in Baroque configuration but with differentiating characteristics. This process gradually gave the rural landscape a unique singularity, i.e., a transformation of significant cultural and historical importance. Numerous artisans constructed these buildings and filled their interior spaces with works of sacred art, mainly carved altars, originating primarily from Paredes de Coura and Alto-Minho municipalities. This systematic study, based on the analysis of contemporary documentation of religious buildings and extensive fieldwork, ensures the thoroughness and reliability of our research and aims to disseminate the data related to this process, presenting an overall reading of religious architecture and seeking to understand the reasons which were at the base of the construction of such a large number of temples in the municipality of Paredes de Coura during this period that changed the territory. This also highlights how Baroque religious architecture was a product of artistic and spiritual ambitions and a powerful agent of territorial reconfiguration, affecting settlement patterns, infrastructure, and social hierarchy. The legacy of these transformations continues to influence the region’s cultural landscape today. Full article
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<p>Location of the municipality of Paredes de Coura in Portugal and the Iberian Peninsula. Source: Cartography by Helena Albuquerque, based on CAOP (Carta Administrativa Oficial de Portugal (<a href="#B16-religions-15-01563" class="html-bibr">Direção-Geral do Território 2023</a>) and (<a href="#B38-religions-15-01563" class="html-bibr">Sevdari and Marmullaku 2023</a>)).</p>
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<p>Quantitative distribution by the parish of the churches and chapels of the municipality of Paredes de Coura. Source: authors.</p>
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<p>Location of the 15 chapel churches, of which there is documentation—contracts for the obligation of work. Cartography by Helena Albuquerque, based on CAOP (Carta Administrativa Oficial de Portugal (<a href="#B16-religions-15-01563" class="html-bibr">Direção-Geral do Território 2023</a>)).</p>
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<p>Chronology of documentary references—work obligation contracts. Source: authors.</p>
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<p>Bell towers with a bulbous top from Divino Espírito Santo Chapel. Source: authors.</p>
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<p>Bell tower with a bulbous top from <span class="html-italic">Ecce Homo</span> Chapel. Source: authors.</p>
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<p>Bell tower with a bulbous top from Linhares Church. Source: authors.</p>
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<p>Nossa Senhora do Amparo Chapel in Romarigães. Source: authors.</p>
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<p>Nossa Senhora do Rosário Chapel in Linhares. Source: authors.</p>
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<p>Pelmet to adorn the cruise arch in Ferreira Church. Source: authors.</p>
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<p>Baroque altar: Bico Church, Joanine style. Source: authors.</p>
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<p>Baroque altar: Cristelo Church, national style. Source: authors.</p>
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<p>Baroque altar: Mozelos Church, national style and Joanino superior finish. Source: authors.</p>
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<p>Rococo Altar: Our Lady of Pain of the Infesta Church. Source: authors.</p>
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<p>Rococo Altar: Our Lady of the Rosary, Agualonga Church. Source: authors.</p>
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<p>Rococo Altars: High Altar, Agualonga Church. Source: authors.</p>
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<p>Altarpiece of D. Maria’s period from Ecce Homo Chapel. Source: authors.</p>
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<p>Altarpiece of D. Maria’s period from Infesta Churche. Source: authors.</p>
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<p>Altarpiece of D. Maria’s period from Formariz Church. Source: authors.</p>
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<p>Altarpiece of the Ferreira Church. Source: authors.</p>
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<p>Altarpiece of S. Caetano Chapel, in Agualonga. Source: authors.</p>
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<p>Altarpiece of the S. Pedro Chapel, in Insalde. Source: authors.</p>
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<p>Detail of the Altarpiece and S. Pedro Chapel, in Insalde. Source: authors.</p>
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<p>Façade of the Nossa Senhora da Conceição Chapel in Ferreira. Source: authors.</p>
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<p>Altarpiece of the Nossa Senhora da Conceição Chapel in Ferreira. Source: authors.</p>
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<p>Pulpit of the Nossa Senhora da Conceição Chapel in Ferreira. Source: authors.</p>
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<p>Imaginary Baroque of the 18th century: Nossa Senhora da Cabeça. Source: authors.</p>
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<p>Imaginary Baroque of the 18th century: Nª Sª das Dores. Source: authors.</p>
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<p>Imaginary Baroque of the 18th century: Santa Ana Mestra. Source: authors.</p>
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27 pages, 10850 KiB  
Article
Modal Analysis with Asymptotic Strips Boundary Conditions of Skewed Helical Gratings on Dielectric Pipes as Cylindrical Metasurfaces for Multi-Beam Holographic Rod Antennas
by Malcolm Ng Mou Kehn, Ting-Wei Lin and Wei-Chuan Chen
Sensors 2024, 24(24), 8119; https://doi.org/10.3390/s24248119 - 19 Dec 2024
Viewed by 420
Abstract
A core dielectric cylindrical rod wrapped in a dielectric circular pipe whose outer surface is enclosed by a helical conducting strip grating that is skewed along the axial direction is herein analyzed using the asymptotic strip boundary conditions along with classical vector potential [...] Read more.
A core dielectric cylindrical rod wrapped in a dielectric circular pipe whose outer surface is enclosed by a helical conducting strip grating that is skewed along the axial direction is herein analyzed using the asymptotic strip boundary conditions along with classical vector potential analysis. Targeted for use as a cylindrical holographic antenna, the resultant field solutions facilitate the aperture integration of the equivalent cylindrical surface currents to obtain the radiated far fields. As each rod section of a certain skew angle exhibits a distinct modal attribute; this topology allows for the distribution of the cylindrical surface impedance via the effective refractive index to be modulated, as in gradient-index (GRIN) materials. Beam steering can also be achieved by altering the skew angle via mechanical sliding motion while leaving the cylindrical structure itself unchanged, as opposed to impractically reconfiguring the geometrical and material parameters of the latter to attain each new beam direction. The results computed by the program code based on the proposed technique in terms of the modal dispersion and radiation patterns are compared with simulations by a software solver. Manufactured prototypes are measured, and experimentally acquired dispersion diagrams and radiation patterns are favorably compared with theoretical predictions. Full article
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Figure 1

Figure 1
<p>Perspective schematic view of skewed helical conducting strip-grating printed on outer surface of dielectric pipe wrapped over core dielectric rod.</p>
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<p>Lateral view of helical conducting strip-grating with skew angle Φ printed on outer surface of dielectric pipe with outer radius <span class="html-italic">b</span> and of medium (<span class="html-italic">ε<sub>out</sub></span>, <span class="html-italic">μ<sub>out</sub></span>) wrapped over core dielectric rod with radius <span class="html-italic">a</span> and of medium (<span class="html-italic">ε<sub>in</sub></span>, <span class="html-italic">μ<sub>in</sub></span>). Axes showing coordinate transformation as shown.</p>
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<p>Modal dispersion diagrams for <span class="html-italic">m</span> = 1, <span class="html-italic">a</span> = 3 mm, <span class="html-italic">b</span> = 6 mm, (<span class="html-italic">μ<sub>in</sub></span>, <span class="html-italic">ε<sub>in</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 2.2<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>out</sub></span>, <span class="html-italic">ε<sub>out</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 3.8<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>ext</sub></span>, <span class="html-italic">ε<sub>ext</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, <span class="html-italic">ε</span><sub>0</sub>), computed by presented ASBC-based analysis and simulated by CST, for (<b>a</b>) Φ = 5°, (<b>b</b>) Φ = 10°, (<b>c</b>) Φ = 15°, (<b>d</b>) Φ = 20°, (<b>e</b>) Φ = 25°, (<b>f</b>) Φ = 30°, (<b>g</b>) Φ = 35°, (<b>h</b>) Φ = 40°.</p>
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<p>Modal dispersion diagrams for <span class="html-italic">m</span> = 1, <span class="html-italic">a</span> = 3 mm, <span class="html-italic">b</span> = 6 mm, (<span class="html-italic">μ<sub>in</sub></span>, <span class="html-italic">ε<sub>in</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 2.2<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>out</sub></span>, <span class="html-italic">ε<sub>out</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 3.8<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>ext</sub></span>, <span class="html-italic">ε<sub>ext</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, <span class="html-italic">ε</span><sub>0</sub>), for various Φ (5°, 10°, 20°, and 30°), (<b>a</b>) computed by code according to ASBC-based analysis, and (<b>b</b>) simulated by CST.</p>
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<p>Modal dispersion diagrams for <span class="html-italic">a</span> = 1 mm, <span class="html-italic">b</span> = 10 mm, (<span class="html-italic">μ<sub>in</sub></span>, <span class="html-italic">ε<sub>in</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 2<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>out</sub></span>, <span class="html-italic">ε<sub>out</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 2.25<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>ext</sub></span>, <span class="html-italic">ε<sub>ext</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, <span class="html-italic">ε</span><sub>0</sub>), Φ = 1°, computed by presented ASBC-based analysis (asterisk markers) and by likewise ASBC-based method for treating corresponding conventional transverse circumferential metal circular strip grated rod (dot markers), as well as simulated by CST (circle markers).</p>
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<p>Real and imaginary parts of eigenvector coefficients: (<b>a</b>) <span class="html-italic">C</span><sub>13</sub>, (<b>b</b>) <span class="html-italic">C</span><sub>14</sub>, and (<b>c</b>) <span class="html-italic">C</span><sub>15</sub>, plotted versus effective refractive index <span class="html-italic">n<sub>eff</sub></span> = <span class="html-italic">β<sub>z</sub><sup>univ</sup></span>/<span class="html-italic">k</span><sub>0</sub>, each pertaining to a Φ. Original solved ones of (14) given by circle markers, and reconstructed by polynomial curve-fitting with degree <span class="html-italic">N</span> = 6 (crosses), as of (58), for <span class="html-italic">m</span> = 1, <span class="html-italic">f<sub>reson</sub></span> = 14 GHz, <span class="html-italic">a</span> = 3 mm, <span class="html-italic">b</span> = 6 mm, (<span class="html-italic">μ<sub>in</sub></span>, <span class="html-italic">ε<sub>in</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 2.2<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>out</sub></span>, <span class="html-italic">ε<sub>out</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 3.8<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>ext</sub></span>, <span class="html-italic">ε<sub>ext</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, <span class="html-italic">ε</span><sub>0</sub>).</p>
Full article ">Figure 7
<p>Normalized real and imaginary parts of surface impedance tensor elements: (<b>a</b>) Re(<span class="html-italic">Z<sub>ϕϕ</sub></span>), (<b>b</b>) Im(<span class="html-italic">Z<sub>ϕϕ</sub></span>), (<b>c</b>) Re(<span class="html-italic">Z<sub>ϕz</sub></span>), (<b>d</b>) Im(<span class="html-italic">Z<sub>ϕz</sub></span>), (<b>e</b>) Re(<span class="html-italic">Z<sub>zϕ</sub></span>), (<b>f</b>) Im(<span class="html-italic">Z<sub>zϕ</sub></span>), (<b>g</b>) Re(<span class="html-italic">Z<sub>zz</sub></span>), (<b>h</b>) Im(<span class="html-italic">Z<sub>zz</sub></span>), contour plotted versus effective refractive index <span class="html-italic">n<sub>eff</sub></span> = <span class="html-italic">β<sub>z</sub><sup>univ</sup></span>/<span class="html-italic">k</span><sub>0</sub> and <span class="html-italic">z</span>, for single TE beam towards <span class="html-italic">θ</span><sub>0<span class="html-italic">e</span></sub> = 60°, rod length of 300 mm, with <span class="html-italic">m</span> = 1, <span class="html-italic">f<sub>reson</sub></span> = 14 GHz, <span class="html-italic">a</span> = 3 mm, <span class="html-italic">b</span> = 6 mm, (<span class="html-italic">μ<sub>in</sub></span>, <span class="html-italic">ε<sub>in</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 2.2<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>out</sub></span>, <span class="html-italic">ε<sub>out</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 3.8<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>ext</sub></span>, <span class="html-italic">ε<sub>ext</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, <span class="html-italic">ε</span><sub>0</sub>).</p>
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<p>Contour plot of base-10 logarithm, log<sub>10</sub>|<span class="html-italic">F</span>(<span class="html-italic">n<sub>eff</sub></span>, <span class="html-italic">z</span>)|, of LHS function of characteristic equation in (59), versus <span class="html-italic">n<sub>eff</sub></span> and <span class="html-italic">z</span>, for dual beam case of <span class="html-italic">θ</span><sub>0<span class="html-italic">m</span></sub> = 40° (TM) and <span class="html-italic">θ</span><sub>0<span class="html-italic">e</span></sub> = 65° (TE), with rod length of 300 mm, with <span class="html-italic">m</span> = 1, <span class="html-italic">f<sub>reson</sub></span> = 14 GHz, <span class="html-italic">a</span> = 3 mm, <span class="html-italic">b</span> = 6 mm, (<span class="html-italic">μ<sub>in</sub></span>, <span class="html-italic">ε<sub>in</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 2.2<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>out</sub></span>, <span class="html-italic">ε<sub>out</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 3.8<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>ext</sub></span>, <span class="html-italic">ε<sub>ext</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, <span class="html-italic">ε</span><sub>0</sub>); (<b>a</b>) planar top view, and (<b>b</b>) perspective view.</p>
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<p>Polynomially curve-fitted graph of <span class="html-italic">n<sub>eff</sub></span> vs. <span class="html-italic">X<sub>TM</sub></span> according to (64).</p>
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<p>Graph of <span class="html-italic">n<sub>eff</sub></span> vs. skew angle Φ.</p>
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<p>Graph of <span class="html-italic">n<sub>eff</sub></span> vs. <span class="html-italic">z</span> according to (65).</p>
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<p>Graph of Φ vs. <span class="html-italic">z</span>.</p>
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<p>Radiation patterns of holographic rod antenna designed to radiate a single TM-polarized main beam towards <span class="html-italic">θ</span><sub>0<span class="html-italic">m</span></sub> = 60°, obtained by both solvers, with co-polar <span class="html-italic">E<sub>θ</sub></span> and cross-polar <span class="html-italic">E<sub>ϕ</sub></span> components separately plotted. Schematic of rod antenna shown inset. Maximum directivity = 8.241 dBi, |S<sub>11</sub>| = −14.7324 dB, realized gain = 8.0924 dBi. Radiation efficiency is −3.577 dB.</p>
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<p>Radiation pattern of holographic rod antenna designed to radiate a single TE-polarized main beam towards <span class="html-italic">θ</span><sub>0<span class="html-italic">m</span></sub> = 40° (realize 38°), obtained by both solvers, with co-polar <span class="html-italic">E<sub>ϕ</sub></span> and cross-polar <span class="html-italic">E<sub>θ</sub></span> components separately plotted. Schematic of rod antenna shown inset. Maximum directivity = 7.215 dBi, |S<sub>11</sub>| = −15.65 dB, realized gain = 7.0948 dBi. Radiation efficiency is −3.1724 dB.</p>
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<p>Radiation patterns of holographic rod antenna designed to radiate two TM-polarized beams towards <span class="html-italic">θ</span><sub>0<span class="html-italic">m</span>1</sub> = 35° and <span class="html-italic">θ</span><sub>0<span class="html-italic">m</span>2</sub> = 50°, obtained by both solvers, with co-polar <span class="html-italic">E<sub>θ</sub></span> and cross-polar <span class="html-italic">E<sub>ϕ</sub></span> components separately plotted. Schematic of rod antenna shown above the graph. Maximum directivities towards these two respective beam directions are 7.3 dBi and 6.8 dBi, |S<sub>11</sub>| = −18.1257 dB, respective realized gains = 7.23 dBi and 6.734 dBi. Radiation efficiency is −3.766 dB.</p>
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<p>Radiation patterns of holographic rod antenna designed to radiate two TE-polarized beams towards <span class="html-italic">θ</span><sub>0<span class="html-italic">e</span>1</sub> = 40° and <span class="html-italic">θ</span><sub>0<span class="html-italic">e</span>2</sub> = 60°, obtained by both solvers, with co-polar <span class="html-italic">E<sub>ϕ</sub></span> and cross-polar <span class="html-italic">E<sub>θ</sub></span> components separately plotted. Maximum directivities towards these two respective beam directions are 7.1055 dBi and 6.179 dBi, |S<sub>11</sub>| = −15.1757 dB, respective realized gains = 6.9716 dBi and 6.0452 dBi. Radiation efficiency is −2.507 dB.</p>
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<p>Contour plot of normalized surface wave modal wavenumber <span class="html-italic">β<sub>z</sub></span>/<span class="html-italic">k</span><sub>0</sub> at 14 GHz of spiral-grated rod with <span class="html-italic">a</span> = 3 mm, <span class="html-italic">b</span> = 6 mm, Φ = 29°, against relative permittivities (<span class="html-italic">ε<sub>in</sub></span>/<span class="html-italic">ε</span><sub>0</sub>, <span class="html-italic">ε<sub>out</sub></span>/<span class="html-italic">ε</span><sub>0</sub>).</p>
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<p>Photographs of the two manufactured prototypes of skewed helical copper wire gratings wound on dielectric pipe sheathed over core dielectric rod (the latter invisible); skew angles (<b>a</b>) 20° and (<b>b</b>) 30°. Close-up shot in (<b>c</b>) of grooves with appropriate tilt angles cut into rod surface for wire to be slotted firmly in place.</p>
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<p>(<b>a</b>) Schematic of the measurement setup, and (<b>b</b>) photograph of actual experimental scenario for measuring modal dispersion comprising a feed horn antenna and a coaxial probe connected respectively to ports 1 and 2 of a vector network analyzer (not included in the photograph).</p>
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<p>Measured modal dispersion traces of two manufactured helically grated rods of different skew angles compared with theoretical ones predicted by ASBC-based analysis and CST simulations as indicated in legends, both for <span class="html-italic">a</span> = 3 mm, <span class="html-italic">b</span> = 6 mm, (<span class="html-italic">μ<sub>in</sub></span>, <span class="html-italic">ε<sub>in</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 2.1<span class="html-italic">ε</span><sub>0</sub> ≈ 2.2<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>out</sub></span>, <span class="html-italic">ε<sub>out</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 3.8<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>ext</sub></span>, <span class="html-italic">ε<sub>ext</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, <span class="html-italic">ε</span><sub>0</sub>), for (<b>a</b>) Φ = 20°, and (<b>b</b>) Φ = 30°.</p>
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<p>Photographs of experimental setup in an anechoic chamber for measurements of far-field radiation patterns of the manufactured rods; (<b>a</b>) overall view of chamber showing feed horn and AUT (grated rod) on rotating platform at near end and receiving horn at far end, and (<b>b</b>) closed-up view of grated rod fed by feed horn.</p>
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<p>Measured normalized far-field radiation patterns of Φ = 30° rod for <span class="html-italic">a</span> = 3 mm, <span class="html-italic">b</span> = 6 mm, (<span class="html-italic">μ<sub>in</sub></span>, <span class="html-italic">ε<sub>in</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 2.1<span class="html-italic">ε</span><sub>0</sub> ≈ 2.2<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>out</sub></span>, <span class="html-italic">ε<sub>out</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 3.8<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>ext</sub></span>, <span class="html-italic">ε<sub>ext</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, <span class="html-italic">ε</span><sub>0</sub>), at (<b>a</b>) 13 GHz and (<b>b</b>) 14 GHz.</p>
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<p>Measured normalized far-field radiation patterns of Φ = 20° rod for <span class="html-italic">a</span> = 3 mm, <span class="html-italic">b</span> = 6 mm, (<span class="html-italic">μ<sub>in</sub></span>, <span class="html-italic">ε<sub>in</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 2.1<span class="html-italic">ε</span><sub>0</sub> ≈ 2.2<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>out</sub></span>, <span class="html-italic">ε<sub>out</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, 3.8<span class="html-italic">ε</span><sub>0</sub>), (<span class="html-italic">μ<sub>ext</sub></span>, <span class="html-italic">ε<sub>ext</sub></span>) = (<span class="html-italic">μ</span><sub>0</sub>, <span class="html-italic">ε</span><sub>0</sub>), at (<b>a</b>) 15 GHz and (<b>b</b>) 16 GHz.</p>
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<p>Measured normalized far-field radiation patterns of two holographic rod antennas, designed to radiate (<b>a</b>) a single beam towards <span class="html-italic">θ</span><sub>0<span class="html-italic">m</span></sub> = 60°, and (<b>b</b>) double beams towards <span class="html-italic">θ</span><sub>0<span class="html-italic">e</span>1</sub> = 40° and <span class="html-italic">θ</span><sub>0<span class="html-italic">e</span>2</sub> = 60°, both compared with computed ones.</p>
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13 pages, 5193 KiB  
Article
Reconfigurable Multifunctional Metasurfaces for Full-Space Electromagnetic Wave Front Control
by Shunlan Zhang, Weiping Cao, Jiao Wang, Tiesheng Wu, Yiying Wang, Yanxia Wang and Dongsheng Zhou
Micromachines 2024, 15(11), 1282; https://doi.org/10.3390/mi15111282 - 22 Oct 2024
Viewed by 848
Abstract
In order to implement multiple electromagnetic (EM) wave front control, a reconfigurable multifunctional metasurface (RMM) has been investigated in this paper. It can meet the requirements for 6G communication systems. Considering the full-space working modes simultaneously, both reflection and transmission modes, the flexible [...] Read more.
In order to implement multiple electromagnetic (EM) wave front control, a reconfigurable multifunctional metasurface (RMM) has been investigated in this paper. It can meet the requirements for 6G communication systems. Considering the full-space working modes simultaneously, both reflection and transmission modes, the flexible transmission-reflection-integrated RMM with p-i-n diodes and anisotropic structures is proposed. By introducing a 45°-inclined H-shaped AS and grating-like micro-structure, the polarization conversion of linear to circular polarization (LP-to-CP) is achieved with good angular stability, in the transmission mode from top to bottom. Meanwhile, reflection beam patterns can be tuned by switching four p-i-n diodes to achieve a 1-bit reflection phase, which are embedded in the bottom of unit cells. To demonstrate the multiple reconfigurable abilities of RMMs to regulate EM waves, the RMMs working in polarization conversion mode, transmitted mode, reflected mode, and transmission-reflection-integrated mode are designed and simulated. Furthermore, by encoding two proper reflection sequences with 13×13 elements, reflection beam patterns with two beams and four beams can be achieved, respectively. The simulation results are consistent with the theoretical method. The suggested metasurface is helpful for radar and wireless communications because of its compact size, simple construction, angular stability, and multi-functionality. Full article
(This article belongs to the Special Issue Recent Advances in Electromagnetic Devices)
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Figure 1

Figure 1
<p>The schematic diagram of the suggested RMM working for full-space.</p>
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<p>The RMM unit cell structure. (<b>a</b>) Schematic of the unit cell; (<b>b</b>–<b>f</b>) structures of five metal patterns from 1 to 5.</p>
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<p>Analogous circuit of p-i-n diodes in different states: (<b>a</b>) ON state, (<b>b</b>) OFF state.</p>
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<p>The electric field along the x-axis splitting into the u and v components, where the right-hand coordinate system is assumed, and the z axis is directed towards the reader.</p>
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<p>Simulated co-polarized and cross-polarized transmission magnitudes and phase differences under the <span class="html-italic">x</span>-polarized EM wave in the ON state.</p>
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<p>Simulated co-polarized and cross-polarized transmission magnitudes and phase differences under the <span class="html-italic">x</span>-polarized EM wave in the OFF state.</p>
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<p>Simulated co- and cross-polarization transmission magnitudes and phase differences for different incident angles under the <span class="html-italic">x</span>-polarized EM waves in the ON state.</p>
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<p>Simulated co- and cross-polarization transmission magnitudes and phase differences for different incident angles under the <span class="html-italic">x</span>-polarized EM waves in the OFF state.</p>
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<p>Simulated reflection coefficients of the presented MS in the ON and OFF states: (<b>a</b>) reflection coefficient; (<b>b</b>) reflection phase and reflection phase differences between p-i-n diode ON and OFF states.</p>
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<p>Simulated reflection magnitudes and phases for different incident angles <math display="inline"><semantics> <mrow> <mi>θ</mi> </mrow> </semantics></math> in the ON states under the y-polarized wave from bottom to top: (<b>a</b>) magnitudes, (<b>b</b>) phases.</p>
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<p>Simulated reflection magnitudes and phases for different incident angles <math display="inline"><semantics> <mrow> <mi>θ</mi> </mrow> </semantics></math> in the OFF states under the y-polarized wave from bottom to top: (<b>a</b>) magnitudes, (<b>b</b>) phases.</p>
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<p>Schematic illustration of 0001111…… coding MSs under the y-normal illumination from bottom to top with dual-beam pattern: (<b>a</b>) coding phase profile, (<b>b</b>) simulated 3D far-field patterns.</p>
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<p>Schematic illustration of chess-board periodic coding metasurface under the y-normal illumination with quad-beam pattern: (<b>a</b>) coding phase profile, (<b>b</b>) simulated 3D far-field patterns.</p>
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13 pages, 1599 KiB  
Article
Exploring Diversification Strategies among Italian Farms
by Concetta Cardillo, Luca Bartoli, Marcello De Rosa, Martina Francescone, Margherita Masi, Hanae Sahir and Yari Vecchio
Sustainability 2024, 16(20), 8856; https://doi.org/10.3390/su16208856 - 13 Oct 2024
Cited by 1 | Viewed by 999
Abstract
The multifunctionality model is receiving more and more attention from policymakers as a result of recent initiatives to build more resilient and sustainable food systems as well as the potential for increased farm revenue. This paper explores the role of multifunctional farming in [...] Read more.
The multifunctionality model is receiving more and more attention from policymakers as a result of recent initiatives to build more resilient and sustainable food systems as well as the potential for increased farm revenue. This paper explores the role of multifunctional farming in the Italian agriculture viewed through the lens of an entrepreneurial strategy grounded on-farm diversification. Farm diversification strategies, which broaden the farm’s traditional boundaries to include additional activities at the farm level, help the evolution towards multifunctionality. A policy-driven transition towards multifunctional farming has been noticed in Italy during the past few decades, which has prompted a strategic reconfiguration of the farm’s business models. Drawing on the identified activity of portfolio diversification, this study provides an overview of the analyzed 49,429 Italian farms, by articulating diversification strategies into four entrepreneurial activities, which are related to on/off-farm/farm-related or farm-diverse diversification strategies. This article has attempted to verify the presence of farm types that responded to portfolio diversification management strategies through the use of a cluster analysis on data from the general census of Italian agriculture. Supporting new patterns in the adoption of business models focused on multifunctionality should be considered in European rural development policies. Full article
(This article belongs to the Section Sustainable Management)
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Figure 1
<p>Own interpretation of Vik and McElwee’s research [<a href="#B28-sustainability-16-08856" class="html-bibr">28</a>].</p>
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<p>Number of farms per region.</p>
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<p>Distribution of farms for RDP area. Own interpretation of data from Italian census of agriculture.</p>
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<p>Number of farms per UAA. Own interpretation of data from Italian census of agriculture.</p>
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<p>Positioning diversification strategies according to the cluster analysis. Own interpretation based on the application of the framework of Vik and McElwee [<a href="#B28-sustainability-16-08856" class="html-bibr">28</a>].</p>
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15 pages, 20922 KiB  
Article
A Versatile Shared-Aperture Antenna for Vehicle Communications
by Mingtang Li, Yihong Su, Wenxin Zhang and Xianqi Lin
Electronics 2024, 13(20), 4009; https://doi.org/10.3390/electronics13204009 - 12 Oct 2024
Viewed by 817
Abstract
This communication introduces a versatile, multi-service, shared-aperture antenna system for multiple vehicle applications. The design comprises three antenna elements: a rotatable microstrip antenna for global positioning system (GPS) communication, a cross-dipole circularly polarized antenna for satellite communication in the S-band, and a pattern [...] Read more.
This communication introduces a versatile, multi-service, shared-aperture antenna system for multiple vehicle applications. The design comprises three antenna elements: a rotatable microstrip antenna for global positioning system (GPS) communication, a cross-dipole circularly polarized antenna for satellite communication in the S-band, and a pattern reconfigurable antenna for V2V (vehicle-to-vehicle) communication. These antennas collectively support GPS, satellite communication (Satcom), and V2V communication in a single, shared-aperture design. This shared-aperture antenna system offers cost savings and occupies less space compared to using separate antennas for each service. The microstrip antenna covers the 1575 MHz frequency band used for GPS communication. The cross-dipole circularly polarized antenna provides continuous wideband coverage for S-band satellite communication. The pattern reconfigurable antenna, tailored for the specific application scenario, covers the 5.9 GHz V2V working frequency band (5.855–5.925 GHz). Practical testing and simulation results confirm the effectiveness of this antenna system for the intended applications. In summary, the microstrip antenna has a bandwidth of 1.565–1.578 GHz and a realized gain of 7 dBi with radiation efficiency of 81%, the cross-dipole antenna has a bandwidth of 2.2–3.8 GHz (53.3%) and a realized gain of 8.3 dBi with radiation efficiency of 90%, and the pattern reconfigurable antenna has a 5.8–6 GHz bandwidth and a realized gain of 3.7 dBi with radiation efficiency of 85%, and the isolation between antennas with different frequencies is 25 dB, 20 dB, and 30 dB in three frequency bands. Full article
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<p>Vehicular communication network diagram.</p>
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<p>Configuration of tri-band shared-aperture antenna. (<b>a</b>) Perspective view; (<b>b</b>) top view; (<b>c</b>) bottom view.</p>
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<p>Comparison of the distribution and array spacing of two shared-aperture arrays.</p>
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<p>Geometry of proposed microstrip antenna.</p>
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<p>Reflection coefficient and realized gain of microstrip antenna.</p>
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<p>Geometry of proposed cross dipole antenna. (<b>a</b>) Top view; (<b>b</b>) side view.</p>
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<p>Wide beam principle of proposed cross dipole.</p>
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<p>Current distribution of antenna at 3 GHz.</p>
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<p>Geometry of proposed pattern reconfigurable antenna. (<b>a</b>) Top view; (<b>b</b>) bottom view.</p>
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<p>Equivalent circuit of BAP70-03. (<b>a</b>) PIN on; (<b>b</b>) PIN off.</p>
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<p>The S11 and realized gain results of proposed pattern reconfigurable antenna.</p>
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<p>The prototype, the test environment, and the port definition.</p>
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<p>The antenna test architecture.</p>
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<p>Simulated and measured reflection coefficient of (<b>a</b>) microstrip antenna; (<b>b</b>) cross-dipole antenna; (<b>c</b>) pattern reconfigurable antenna.</p>
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<p>Simulated and measured iso-frequency port isolation at (<b>a</b>) GPS L1 band; (<b>b</b>) S band; (<b>c</b>) V2V band.</p>
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<p>Radiation performance of microstrip antenna. (<b>a</b>) Radiation pattern; (<b>b</b>) axial ratio.</p>
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<p>Radiation pattern of cross dipoles at (<b>a</b>) 2 GHz, (<b>b</b>) 3 GHz, and (<b>c</b>) 4 GHz.</p>
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<p>Simulated and measured radiation pattern of pattern reconfigurable antenna. (<b>a</b>) state 1. (<b>b</b>) state 2. (<b>c</b>) state 3. (<b>d</b>) state 4.</p>
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<p>Comparison of the distribution and array spacing of two shared-aperture arrays.</p>
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<p>(<b>a</b>) The schematic diagram of antenna installation on a car. (<b>b</b>) Horizontal radiation pattern of pattern reconfigurable antenna. (<b>c</b>) Vertical radiation pattern of pattern reconfigurable antenna.</p>
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23 pages, 9813 KiB  
Review
Overview of Reconfigurable Antenna Systems for IoT Devices
by Elena García, Aurora Andújar and Jaume Anguera
Electronics 2024, 13(20), 3988; https://doi.org/10.3390/electronics13203988 - 10 Oct 2024
Viewed by 1852
Abstract
The proliferation of Internet of Things (IoT) devices, such as trackers and sensors, necessitates a delicate balance between device miniaturization and performance. This extends to the antenna system, which must be both efficient and multiband operational while fitting within space-constrained electronic enclosures. Traditional [...] Read more.
The proliferation of Internet of Things (IoT) devices, such as trackers and sensors, necessitates a delicate balance between device miniaturization and performance. This extends to the antenna system, which must be both efficient and multiband operational while fitting within space-constrained electronic enclosures. Traditional antennas, however, struggle to meet these miniaturization demands. Reconfigurable antennas have emerged as a promising solution for adapting their frequency, radiation pattern, or polarization in response to changing requirements, making them ideal for IoT applications. Among various reconfiguration techniques (electrical, mechanical, optical, and material-based), electrical reconfiguration reigns supreme for IoT applications. Its suitability for compact devices, cost-effectiveness, and relative simplicity make it the preferred choice. This paper reviews various approaches to realizing IoT reconfigurable antennas, with a focus on electrical reconfiguration techniques. It categorizes these techniques based on their implementation, including PIN diodes, digital tunable capacitors (DTCs), varactor diodes, and RF switches. It also explores the challenges associated with the development and characterization of IoT reconfigurable antennas, evaluates the strengths and limitations of existing methods, and identifies open challenges for future research. Importantly, the growing trend towards smaller IoT devices has led to the development of antenna boosters. These components, combined with advanced reconfiguration techniques, offer new opportunities for enhancing antenna performance while maintaining a compact footprint. Full article
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<p>Number of reconfigurable antenna papers published. Data obtained from scientific databases [<a href="#B22-electronics-13-03988" class="html-bibr">22</a>,<a href="#B23-electronics-13-03988" class="html-bibr">23</a>], using the following keywords: antenna, IoT, reconfigurable, and tunable/tuneable.</p>
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<p>Schematic of reconfigurable antenna techniques, with a focus on those relevant to the IoT, which will be discussed in detail.</p>
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<p>Design of a reconfigurable 41 mm × 44 mm antenna with a PIN diode [<a href="#B53-electronics-13-03988" class="html-bibr">53</a>].</p>
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<p>PIN diode’s lumped elements in (<b>a</b>) on state (<b>b</b>) off state presented in [<a href="#B53-electronics-13-03988" class="html-bibr">53</a>].</p>
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<p>Detailed biasing circuit [<a href="#B53-electronics-13-03988" class="html-bibr">53</a>]. Lp represents the choke inductors, creating a high impedance for the operation frequencies. Cb represents the DB blocks, allowing the DC circuit to connect only to the VCC, the LP, the PIN diode, the Lp, and the ground.</p>
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<p>S<sub>11</sub> parameter of the antenna with the PIN diode [<a href="#B53-electronics-13-03988" class="html-bibr">53</a>].</p>
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<p>S<sub>11</sub> of the different states of the DCT with the antenna in [<a href="#B68-electronics-13-03988" class="html-bibr">68</a>].</p>
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<p>Antenna geometry with a DTC [<a href="#B70-electronics-13-03988" class="html-bibr">70</a>].</p>
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<p>Equivalent circuit of the antenna [<a href="#B70-electronics-13-03988" class="html-bibr">70</a>].</p>
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<p>Measured reflection coefficient of the antenna proposed in [<a href="#B70-electronics-13-03988" class="html-bibr">70</a>].</p>
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<p>Prototype of the reconfigurable antenna [<a href="#B74-electronics-13-03988" class="html-bibr">74</a>].</p>
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<p>The varactor diode equivalent circuit [<a href="#B75-electronics-13-03988" class="html-bibr">75</a>].</p>
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<p>Feed and short pins connected to printed lines with all the components for the reconfiguration [<a href="#B74-electronics-13-03988" class="html-bibr">74</a>].</p>
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<p>S<sub>11</sub> parameter of the reconfigurable antenna for C1 = 60 pF and C2 from 8 to 60 pF and for C1 from 8 to 60 pF and C2 = 60 pF [<a href="#B74-electronics-13-03988" class="html-bibr">74</a>].</p>
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<p>Configuration of the proposed antenna: (<b>a</b>) 3D view, and (<b>b</b>) top view. The detail DC bias circuit and circuit model of the varactor is displayed in the inset. [<a href="#B76-electronics-13-03988" class="html-bibr">76</a>].</p>
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<p>Measured and simulated S<sub>11</sub> of the different states [<a href="#B76-electronics-13-03988" class="html-bibr">76</a>].</p>
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<p>The configuration of the SP4T switch [<a href="#B95-electronics-13-03988" class="html-bibr">95</a>].</p>
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<p>Measured reflection coefficient results of the antenna at different states [<a href="#B95-electronics-13-03988" class="html-bibr">95</a>].</p>
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<p>PCB with antenna booster element in clearance area for cellular and GPS operation [<a href="#B57-electronics-13-03988" class="html-bibr">57</a>].</p>
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<p>Reconfigurable antenna architecture with matching network system for multiband operation [<a href="#B57-electronics-13-03988" class="html-bibr">57</a>].</p>
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<p>S<sub>11</sub> for states covering the desired frequency bands [<a href="#B57-electronics-13-03988" class="html-bibr">57</a>].</p>
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<p>Prototype of the reconfigurable architecture integrating an antenna booster element [<a href="#B98-electronics-13-03988" class="html-bibr">98</a>].</p>
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<p>RF SP4T switch architecture with all matching networks and an antenna booster element [<a href="#B98-electronics-13-03988" class="html-bibr">98</a>].</p>
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<p>Measured S<sub>11</sub> of the states when using the scheme shown in <a href="#electronics-13-03988-f022" class="html-fig">Figure 22</a> and <a href="#electronics-13-03988-f023" class="html-fig">Figure 23</a> [<a href="#B98-electronics-13-03988" class="html-bibr">98</a>].</p>
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<p>Thingy 91 X by Nordic Semiconductor [<a href="#B102-electronics-13-03988" class="html-bibr">102</a>], a multi-sensor cellular IoT prototyping platform in the market integrating antenna booster technology from Ignion [<a href="#B103-electronics-13-03988" class="html-bibr">103</a>].</p>
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<p>Measured radiation patterns showing the realized gain at 800 MHz (on the left) and 2 GHz (on the right) [<a href="#B98-electronics-13-03988" class="html-bibr">98</a>]. Radiation patterns are quasi-isotropic, which is convenient when the direction of the incoming signal is not known.</p>
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<p>Percentage of types of reconfiguration used based on publications in the IoT antenna domain.</p>
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21 pages, 2956 KiB  
Article
Ageing-Related Changes to H3K4me3, H3K27ac, and H3K27me3 in Purified Mouse Neurons
by Brandon Signal, Andrew J. Phipps, Katherine A. Giles, Shannon N. Huskins, Timothy R. Mercer, Mark D. Robinson, Adele Woodhouse and Phillippa C. Taberlay
Cells 2024, 13(16), 1393; https://doi.org/10.3390/cells13161393 - 21 Aug 2024
Viewed by 2414
Abstract
Neurons are central to lifelong learning and memory, but ageing disrupts their morphology and function, leading to cognitive decline. Although epigenetic mechanisms are known to play crucial roles in learning and memory, neuron-specific genome-wide epigenetic maps into old age remain scarce, often being [...] Read more.
Neurons are central to lifelong learning and memory, but ageing disrupts their morphology and function, leading to cognitive decline. Although epigenetic mechanisms are known to play crucial roles in learning and memory, neuron-specific genome-wide epigenetic maps into old age remain scarce, often being limited to whole-brain homogenates and confounded by glial cells. Here, we mapped H3K4me3, H3K27ac, and H3K27me3 in mouse neurons across their lifespan. This revealed stable H3K4me3 and global losses of H3K27ac and H3K27me3 into old age. We observed patterns of synaptic function gene deactivation, regulated through the loss of the active mark H3K27ac, but not H3K4me3. Alongside this, embryonic development loci lost repressive H3K27me3 in old age. This suggests a loss of a highly refined neuronal cellular identity linked to global chromatin reconfiguration. Collectively, these findings indicate a key role for epigenetic regulation in neurons that is inextricably linked with ageing. Full article
(This article belongs to the Section Cellular Aging)
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<p>Genome-wide epigenome maps of ageing neurons. (<b>A</b>–<b>D</b>) Schematic of experimental design and analysis for this study, including (<b>A</b>) timeline of mouse lifespan and data points collected for this study, (<b>B</b>) FANS collection using NeuN+ cells, (<b>C</b>) chromatin immunoprecipitation, and (<b>D</b>) sequencing. (<b>E</b>) Enrichment of neuron-specific epigenetic signals in ageing neurons. Proportion of cell-specific gene promoters from single-cell RNA-SEQ data from Ximerakis et al. (2019) [<a href="#B31-cells-13-01393" class="html-bibr">31</a>] with H3K4me3 and H3K27ac ChIP reads ≥ 2 RPKM, and mean H3K27me3 cell-specific gene body RPKM. Number of genes used is given in brackets after cell type. (<b>F</b>) PCA plots for genome-wide (10 kb binned) ChIP-Seq signal of H3K27ac (blue), H3K4me3 (green), and H3K27me3 (pink) in neurons.</p>
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<p>Novel H3K27ac peaks occur in synaptic-signalling-related genomic regions. (<b>A</b>) Identification of novel H3K27ac peaks that do not overlap with any of the ChromHMM enhancers, H3K27ac peaks, or snATAC peaks. Novel peaks were classed based on their genomic location, with introns being the most frequent. (<b>B</b>) Enrichment of the top 20 GO biological process terms in novel H3K27ac peaks. (<b>C</b>) HOMER de novo motif enrichment in novel H3K27ac peaks. (<b>D</b>) Neuronal H3K27ac ChIP-Seq signal in a novel peak within an intron of the synaptic signalling gene <span class="html-italic">Prkn</span>. Complementary H3K4me3 and H3K27me3 profiles are shown in <a href="#app1-cells-13-01393" class="html-app">Figure S16</a>.</p>
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<p>Differential H3K27ac occupancy in ageing neurons. (<b>A</b>) A csaw analysis with the glmQLFTest test identified regions of differential H3K27ac occupancy in ageing neurons from mice aged 3 months (<span class="html-italic">n</span> = 4), 12 months (<span class="html-italic">n</span> = 2), and 24 months (<span class="html-italic">n</span> = 2). (<b>B</b>) Region of H3K27ac gain in the first intron of <span class="html-italic">Zswim6</span> between 12 and 24 months. ENCODE postnatal enhancer regions are shown in yellow/gold. (<b>C</b>) Differential H3K27ac peak’s closest annotated genomic feature. Significant (<span class="html-italic">p</span> hypergeometric &lt; 0.05) over- and underrepresentations are indicated by red and black triangles, respectively. (<b>D</b>) Enrichment of the top 10 GO biological process terms for each age comparison and direction of change. (<b>E</b>) Overlap of all differential peak regions in the 3-month vs. 12-month comparisons and 3-month vs. 24-month comparisons. (<b>F</b>) Example regions of H3K27ac signal, showing a loss between 3 and 12 months (<span class="html-italic">Disc1</span>; <b>top</b>) and between 3 and 24 months (<span class="html-italic">Sorbs2</span>; <b>bottom</b>). ENCODE postnatal enhancer regions are shown in yellow/gold. Complementary H3K4me3 and H3K27me3 profiles are found in <a href="#app1-cells-13-01393" class="html-app">Figure S17</a>.</p>
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<p>Differential H3K4me3 occupancy in ageing neurons. (<b>A</b>) A csaw analysis with the glmQLFTest test identified a single region (<span class="html-italic">Igf2bp1</span>) of differential H3K4me3 occupancy in ageing neurons from mice aged 3 months (<span class="html-italic">n</span> = 4), 12 months (<span class="html-italic">n</span> = 2), and 24 months (<span class="html-italic">n</span> = 3). (<b>B</b>) Region of H3K4me3 loss in the <span class="html-italic">Igf2bp1</span> intron between 3 months and 24 months. ENCODE postnatal enhancer regions are shown in yellow/gold. Complementary H3K27ac and H3K27me3 profiles are shown in <a href="#app1-cells-13-01393" class="html-app">Figure S21</a>.</p>
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<p>Differential H3K27me3 occupancy in ageing neurons. (<b>A</b>) Differential H3K27me3 peak locations for the 3-month (<span class="html-italic">n</span> = 3) to 24-month (<span class="html-italic">n</span> = 2) csaw analysis with the glmQLFTest. Left: closest annotated genomic feature. Right: Overlap of promoter peaks with CpG islands. Promoter overlapping peaks were defined as those overlapping the region 5 kb upstream (i.e., “promoter_extended” and “promoter”) to 1 kb downstream from the TSS (top schematic). Significant (<span class="html-italic">p</span> hypergeometric &lt; 0.05) over- and underrepresentations are indicated by red and black triangles, respectively. (<b>B</b>) Enrichment of the top 10 GO biological process (top) and molecular function (bottom) terms for significant peaks in the 3-month to 24-month csaw analysis. (<b>C</b>) Example region of H3K27me signal, showing a loss between 3 and 24 months upstream of the embryonic development gene En1 promoter. ENCODE postnatal enhancer regions are shown in yellow/gold. (<b>D</b>) Differential signal of H3K27me3 at the E14.5 brain mouse superenhancer region (light blue). Regions of significant change in H3K27me3 ChIP-Seq signal are highlighted in pink. Complementary H3K27ac and H3K4me3 profiles are shown in <a href="#app1-cells-13-01393" class="html-app">Figures S21 and S24</a>.</p>
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18 pages, 2362 KiB  
Article
Engineering the Rhizosphere Microbiome with Plant Growth Promoting Bacteria for Modulation of the Plant Metabolome
by Maria J. Ferreira, Ana C. S. Veríssimo, Diana C. G. A. Pinto, Isabel N. Sierra-Garcia, Camille E. Granada, Javier Cremades, Helena Silva and Ângela Cunha
Plants 2024, 13(16), 2309; https://doi.org/10.3390/plants13162309 - 20 Aug 2024
Cited by 1 | Viewed by 2250
Abstract
Plant-growth-promoting bacteria (PGPB) have beneficial effects on plants. They can promote growth and enhance plant defense against abiotic stress and disease, and these effects are associated with changes in the plant metabolite profile. The research problem addressed in this study was the impact [...] Read more.
Plant-growth-promoting bacteria (PGPB) have beneficial effects on plants. They can promote growth and enhance plant defense against abiotic stress and disease, and these effects are associated with changes in the plant metabolite profile. The research problem addressed in this study was the impact of inoculation with PGPB on the metabolite profile of Salicornia europaea L. across controlled and field conditions. Salicornia europaea seeds, inoculated with Brevibacterium casei EB3 and Pseudomonas oryzihabitans RL18, were grown in controlled laboratory experiments and in a natural field setting. The metabolite composition of the aboveground tissues was analyzed using GC–MS and UHPLC–MS. PGPB inoculation promoted a reconfiguration in plant metabolism in both environments. Under controlled laboratory conditions, inoculation contributed to increased biomass production and the reinforcement of immune responses by significantly increasing the levels of unsaturated fatty acids, sugars, citric acid, acetic acid, chlorogenic acids, and quercetin. In field conditions, the inoculated plants exhibited a distinct phytochemical profile, with increased glucose, fructose, and phenolic compounds, especially hydroxybenzoic acid, quercetin, and apigenin, alongside decreased unsaturated fatty acids, suggesting higher stress levels. The metabolic response shifted from growth enhancement to stress resistance in the latter context. As a common pattern to both laboratory and field conditions, biopriming induced metabolic reprogramming towards the expression of apigenin, quercetin, formononetin, caffeic acid, and caffeoylquinic acid, metabolites that enhance the plant’s tolerance to abiotic and biotic stress. This study unveils the intricate metabolic adaptations of Salicornia europaea under controlled and field conditions, highlighting PGPB’s potential to redesign the metabolite profile of the plant. Elevated-stress-related metabolites may fortify plant defense mechanisms, laying the groundwork for stress-resistant crop development through PGPB-based inoculants, especially in saline agriculture. Full article
(This article belongs to the Special Issue Beneficial Effects of Bacteria on Plants)
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<p>Phytochemical profile of non-inoculated and inoculated <span class="html-italic">Salicornia europaea</span> in controlled conditions (microcosm experiments), according to chemical families of compounds detected with GC–MS and UHPLC–MS. NI—non-inoculated plants; EB3 + RL18—plants inoculated with <span class="html-italic">Brevibacterium casei</span> EB3 and <span class="html-italic">Pseudomonas oryzihabitans</span> RL18. The columns represent the average of 3 biological replicates, and the error bars correspond to the standard error. The data obtained were compared by <span class="html-italic">t</span>-test (sugar acids, saturated fatty acids, alcohols, amides, and phenolic acids) or the Mann–Whitney test (unsaturated fatty acids, sterols, sugars, and flavonoids); significant differences are indicated by * (<span class="html-italic">p</span> &lt; 0.05), ** (<span class="html-italic">p</span> = 0.004) and *** (<span class="html-italic">p</span> = 0.002) between the non-inoculated control and the test.</p>
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<p>Response of <span class="html-italic">Salicornia europaea</span> secondary metabolism to inoculation with PGPB <span class="html-italic">Brevibacterium casei</span> EB3 and <span class="html-italic">Pseudomonas oryzihabitans</span> RL18 under controlled microcosm conditions. Fold changes are expressed as Log<sub>2</sub> ((EB3 + RL18)/NI). (<b>A</b>)—Carboxylic acids; (<b>B</b>)—Sugar acids; (<b>C</b>)—Sterols; (<b>D</b>)—Fatty acids; (<b>E</b>)—Alcohols; (<b>F</b>)—Amides; (<b>G</b>)—Sugars; (<b>H</b>)—Phenolic compounds.</p>
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<p>Phytochemical profile of non-inoculated and inoculated <span class="html-italic">Salicornia europaea</span> under field conditions, according to chemical families of compounds detected with GC–MS and UHPLC–MS. NI—non-inoculated plants; EB3 + RL18—plants inoculated with <span class="html-italic">Brevibacterium casei</span> EB3 and <span class="html-italic">Pseudomonas oryzihabitans</span> RL18. The columns represent the average of 3 biological replicates, and the error bars correspond to the standard error. The data obtained were compared by <span class="html-italic">t</span>-test (carboxylic acids, sugar acids, and amides) and the Mann–Whitney U test (saturated and unsaturated fatty acids, sterols, alcohols, and sugars); significant differences are indicated by * (<span class="html-italic">p</span> &lt; 0.05), ** (<span class="html-italic">p</span> = 0.004) and *** (<span class="html-italic">p</span> = 0.002) between the control and the test.</p>
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<p>Response of <span class="html-italic">Salicornia europaea</span> secondary metabolism to inoculation with PGPB <span class="html-italic">Brevibacterium casei</span> EB3 and <span class="html-italic">Pseudomonas oryzihabitans</span> RL18 under field conditions. Fold changes are expressed as Log<sub>2</sub> ((EB3 + RL18)/NI). (<b>A</b>)—Carboxylic acids; (<b>B</b>)—Sugar acids; (<b>C</b>)—Sterols; (<b>D</b>)—Fatty acids; (<b>E</b>)—Alcohols; (<b>F</b>)—Amides; (<b>G</b>)—Sugars; (<b>H</b>)—Phenolic compounds.</p>
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<p>Principal component analysis (PCA) of (<b>A</b>) the microcosm experiment and (<b>B</b>) the field experiment. Changes in the metabolite composition of <span class="html-italic">Salicornia europaea</span> plants inoculated with <span class="html-italic">Brevibacterium casei</span> EB3 and <span class="html-italic">Pseudomonas oryzihabitans</span> RL18 (EB3 + RL18, gray stars) versus the corresponding non-inoculated controls (NI, black asterisks). Each symbol corresponds to an individual analyzed plant.</p>
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18 pages, 2685 KiB  
Article
Reconfigurable Robotic Exercising Companion
by W. K. R. Sachinthana, I. D. Wijegunawardana, S. M. Bhagya P. Samarakoon, M. A. Viraj J. Muthugala and Mohan Rajesh Elara
Appl. Sci. 2024, 14(16), 7249; https://doi.org/10.3390/app14167249 - 17 Aug 2024
Viewed by 695
Abstract
Regular exercise plays a crucial role in promoting overall well-being in today’s lifestyle. However, individuals often find it challenging to properly execute exercises, including maintaining correct postures and appropriate movement speeds. Robotic companions have emerged as potential solutions to assist and motivate users [...] Read more.
Regular exercise plays a crucial role in promoting overall well-being in today’s lifestyle. However, individuals often find it challenging to properly execute exercises, including maintaining correct postures and appropriate movement speeds. Robotic companions have emerged as potential solutions to assist and motivate users during exercise sessions. This research paper proposes a novel robot companion designed for exercise scenarios using a reconfigurable robot. In contrast to existing non-reconfigurable robotic companions, the use of a reconfigurable robot provides added flexibility in generating emotions. The system incorporates a module that utilizes fuzzy logic to evaluate the correctness of exercise performance based on posture variations and movement speeds. The robot generates emotions and provides feedback to users based on the exercise correctness score. The robot expresses emotions through reconfigurations, motion patterns, and variations in robot speed. This emotion-based feedback could be helpful for creating engaging and interactive exercise experiences. Apart from emotion generation, the robot utilizes vocal cues as feedback. Experimental results validate the effectiveness of the proposed system in evaluating exercise correctness and demonstrating meaningful emotion transitions. The findings of this work contribute to the development of innovative robotic companions for improving exercise adherence and overall well-being. Full article
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<p>Overview of the system.</p>
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<p>(<b>a</b>) Smorphi robot platform. (<b>b</b>) Robot shape configurations.</p>
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<p>Human body joint extraction: (<b>a</b>) 33 joint positions identified by Mediapipe Pose, and (<b>b</b>) body joints corresponding to derive <math display="inline"><semantics> <msub> <mi>θ</mi> <mi>i</mi> </msub> </semantics></math>.</p>
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<p>Membership function of the fuzzy logic module developed for evaluating the correctness of exercises. (<b>a</b>): the input membership function for <span class="html-italic">D</span>, (<b>b</b>): the input membership function for <span class="html-italic">S</span>, and (<b>c</b>): the output membership function.</p>
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<p>Emotion space model configured for the proposed system.</p>
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<p>Smorphi configurations with labeled top for emotion expression. (<b>a</b>): happy expression with O shape and (<b>b</b>): sad expression with S shape.</p>
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<p>Experimental setup. (<b>a</b>): Hardware setup with a user. (<b>b</b>): A user performing normal squats. (<b>c</b>): A user performing sumo squats.</p>
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<p>Normal squat experiment correctness evaluation results.</p>
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<p>Normal squat experiment emotion expression results.</p>
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<p>Normal squat correct posture variation.</p>
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<p>Normal squat wrong posture variation.</p>
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<p>Sumo squat correct posture variation.</p>
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<p>Sumo squat experiment correctness evaluation results.</p>
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<p>Sumo squat experiment emotion expression results.</p>
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19 pages, 1303 KiB  
Article
Natural Language Processing for Hardware Security: Case of Hardware Trojan Detection in FPGAs
by Jaya Dofe, Wafi Danesh, Vaishnavi More and Aaditya Chaudhari
Cryptography 2024, 8(3), 36; https://doi.org/10.3390/cryptography8030036 - 8 Aug 2024
Cited by 1 | Viewed by 2195
Abstract
Field-programmable gate arrays (FPGAs) offer the inherent ability to reconfigure at runtime, making them ideal for applications such as data centers, cloud computing, and edge computing. This reconfiguration, often achieved through remote access, enables efficient resource utilization but also introduces critical security vulnerabilities. [...] Read more.
Field-programmable gate arrays (FPGAs) offer the inherent ability to reconfigure at runtime, making them ideal for applications such as data centers, cloud computing, and edge computing. This reconfiguration, often achieved through remote access, enables efficient resource utilization but also introduces critical security vulnerabilities. An adversary could exploit this access to insert a dormant hardware trojan (HT) into the configuration bitstream, bypassing conventional security and verification measures. To address this security threat, we propose a supervised learning approach using deep recurrent neural networks (RNNs) for HT detection within FPGA configuration bitstreams. We explore two RNN architectures: basic RNN and long short-term memory (LSTM) networks. Our proposed method analyzes bitstream patterns, to identify anomalies indicative of malicious modifications. We evaluated the effectiveness on ISCAS 85 benchmark circuits of varying sizes and topologies, implemented on a Xilinx Artix-7 FPGA. The experimental results revealed that the basic RNN model showed lower accuracy in identifying HT-compromised bitstreams for most circuits. In contrast, the LSTM model achieved a significantly higher average accuracy of 93.5%. These results demonstrate that the LSTM model is more successful for HT detection in FPGA bitstreams. This research paves the way for using RNN architectures for HT detection in FPGAs, eliminating the need for time-consuming and resource-intensive reverse engineering or performance-degrading bitstream conversions. Full article
(This article belongs to the Special Issue Emerging Topics in Hardware Security)
Show Figures

Figure 1

Figure 1
<p>Concept of a bitstream protocol stack for Xilinx 7 series FPGAs.</p>
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<p>Xilinx configuration file formats. (Note: For (1), (2), (3) please refer to [<a href="#B22-cryptography-08-00036" class="html-bibr">22</a>]).</p>
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<p>Steps in 7-series FPGA configuration.</p>
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<p>Type 1 packet header format for Xilinx 7-series FPGA.</p>
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<p>Opcode for Type 1 packet header.</p>
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<p>Type 2 packet header format for Xilinx 7-series FPGA.</p>
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<p>Frame address register description.</p>
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<p>Conventional RNN architecture.</p>
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<p>Hidden layer for conventional RNN.</p>
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<p>Cell for LSTM architecture.</p>
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<p>The .<span class="html-italic">bit</span> file format.</p>
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<p>Data preprocessing algorithm.</p>
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<p>Training RNN models on preprocessed bitstreams.</p>
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<p>Training and validation accuracy over training epochs for RNN with step size 16.</p>
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<p>Training and validation accuracy over training epochs for LSTM with step size 16.</p>
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<p>Step size and accuracy trends for LSTM.</p>
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<p>Example of latched RO.</p>
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<p>Training and validation accuracy vs. step size for c17 benchmark.</p>
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<p>Comparison of c17 performance metrics for step sizes 8 and 16.</p>
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