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WO2024045797A1 - 非隔离谐振变换器 - Google Patents

非隔离谐振变换器 Download PDF

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Publication number
WO2024045797A1
WO2024045797A1 PCT/CN2023/102031 CN2023102031W WO2024045797A1 WO 2024045797 A1 WO2024045797 A1 WO 2024045797A1 CN 2023102031 W CN2023102031 W CN 2023102031W WO 2024045797 A1 WO2024045797 A1 WO 2024045797A1
Authority
WO
WIPO (PCT)
Prior art keywords
resonant
inductor
transformer
unit
switch unit
Prior art date
Application number
PCT/CN2023/102031
Other languages
English (en)
French (fr)
Inventor
李斌
李培永
李奇峰
杨鑫
周远平
乔宗标
Original Assignee
上海英联电子系统有限公司
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by 上海英联电子系统有限公司 filed Critical 上海英联电子系统有限公司
Publication of WO2024045797A1 publication Critical patent/WO2024045797A1/zh

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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/01—Resonant DC/DC converters
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/22—Conversion of DC power input into DC power output with intermediate conversion into AC
    • H02M3/24—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters
    • H02M3/28—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC
    • H02M3/325—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/3353—Conversion of DC power input into DC power output with intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate AC using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having at least two simultaneously operating switches on the input side, e.g. "double forward" or "double (switched) flyback" converter
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

Definitions

  • the present invention relates to the field of power supply technology, and in particular, to a non-isolated resonant converter.
  • the 48V bus is used to power server boards.
  • the power supply architecture gradually replaces the traditional architecture of the 12V bus; this 48V architecture usually converts the AC grid power into a 48V DC bus through the AC power supply, and then converts the 48V to 12V by the DCDC power supply, and then converts the 12V to what each chipset requires.
  • Various voltages as low as 0.6V are used to power the chipset.
  • Switchched Tank Converters STC
  • STC switched Energy storage converter non-isolated resonant converter
  • This converter is cascaded through a multi-stage resonant circuit, which can realize soft switching of all switching devices, and the stress of the switching devices is effectively controlled through the series connection of the switching devices and the output voltage clamping, so that the efficiency of the converter is at a lower level.
  • the cost has been very effectively improved, making this circuit a hot spot in the research field.
  • this circuit also has two inherent shortcomings: first, the converter is a resonant scheme of a switched capacitor circuit, the relationship between the input and output voltages is a fixed transformation ratio, and voltage regulation cannot be performed, which greatly limits the application of the converter, especially in After several leading companies successively shifted their server power supply solutions to 12V voltage controllable, the attention of this circuit began to decline; in addition, there are many switching devices and complex control. The series connection of multiple switching devices makes the driving scheme and auxiliary source design complex. Without In the case of a dedicated analog controller, the implementation and cost of the circuit are pushed up, which also limits the application of the circuit to a certain extent. between this Later, the buck converter circuit as shown in Figure 7 attracted attention again.
  • This circuit added a series capacitor to the traditional buck converter circuit. Due to the existence of this capacitor, the duty cycle of the converter can be expanded and the polarity can be increased. It greatly reduces the voltage ripple in front of the output filter inductor and improves the working conditions of the filter inductor, allowing the converter to lower the switching frequency, reduce switching losses, and improve efficiency. At the same time, the circuit structure of the converter is simpler than that of the STC circuit. , reducing the design difficulty. This circuit is a relatively optimized solution for current non-isolated 48V to 12V applications. The only drawback to this circuit is the hard switching. Since the switching device is in a hard switching condition during operation, it limits the increase in the switching frequency of the converter to a certain extent, which limits the module from further improving the power density of the power module.
  • the purpose of the present invention is to provide a non-isolated resonant converter to reduce control difficulty and cost.
  • the non-isolated resonant converter of the present invention includes a first resonant bridge, a second resonant bridge, a freewheeling tube unit, a resonant network, an autotransformer, a load and an output capacitor.
  • the autotransformer includes The first transformer inductor, the second transformer inductor and the third transformer inductor.
  • the resonant network and the first transformer inductor are connected in series to form a transformer resonant unit.
  • the first end of the transformer resonant unit is connected to the first resonant bridge.
  • the second end of the transformer resonant unit is connected to the second resonant bridge, the same-name end of the second transformer inductor is connected to the different-name end of the third transformer inductor, one end of the output capacitor, One end of the load is connected, the opposite end of the second transformer inductor is connected to the first resonant bridge and the freewheeling tube unit, the same end of the third transformer inductor is connected to the second resonant bridge and The freewheeling tube unit is connected, the first resonant bridge and the second resonant bridge are also connected to the positive electrode of the power supply, and the freewheeling tube unit is connected to the other end of the output capacitor and the other end of the load.
  • the first resonant bridge is used to connect the first end of the transformer resonant unit with the positive electrode of the power supply or the freewheeling tube
  • the second resonant bridge is used to connect the second end of the transformer resonant unit.
  • the freewheeling tube is used to connect the opposite end of the second transformer inductor or the same end of the third transformer inductor to the other end of the load, where , the number of turns of the first transformer inductor is greater than or equal to 0.
  • the beneficial effect of the non-isolated resonant converter is that it includes a first resonant bridge, a second resonant bridge, a freewheeling tube unit, a resonant network, an autotransformer, a load and an output capacitor.
  • the autotransformer includes a first transformer inductor. , the second transformer inductor and the third transformer inductor, the circuit is simple, the control is simple and easy, and the cost is low.
  • the first resonant bridge includes a first switch unit and a third switch unit, the first terminal of the first switch unit is connected to the positive pole of the power supply, and the second terminal of the first switch unit is connected to the third switch unit.
  • the first end of the three switch units is connected, and the second end of the third switch unit is connected to the opposite end of the second transformer inductor.
  • both the first switch unit and the third switch unit are controllable switching devices.
  • the second resonant bridge includes a second switching unit and a fourth switching unit, so The first end of the second switch unit is connected to the positive electrode of the power supply, the second end of the second switch unit is connected to the first end of the fourth switch unit, and the second end of the fourth switch unit is connected to the The same terminal of the third transformer inductor is connected.
  • both the second switch unit and the fourth switch unit are controllable switching devices.
  • the freewheeling tube unit includes a fifth switching unit and a sixth switching unit.
  • the first end of the fifth switching unit is connected to the opposite end of the second transformer inductor.
  • the fifth switching unit The second end of the sixth switching unit is connected to the other end of the load, the first end of the sixth switching unit is connected to the same end of the third transformer inductor, and the second end of the sixth switching unit is connected to the end of the load. Connect the other end.
  • both the fifth switching unit and the sixth switching unit are uncontrollable switching devices or controllable switching devices.
  • controllable switching device includes a metal oxide semiconductor field effect transistor, an insulated gate bipolar transistor, a gallium nitride transistor, a silicon carbide MOS transistor, and a first combined switching unit, and the first combined switching unit is a triode. combination with diodes.
  • the uncontrollable switching device includes a diode and a second combined switch unit
  • the second combined switch unit includes a diode and a metal oxide semiconductor field effect transistor, an insulated gate bipolar transistor, a gallium nitride transistor, and a silicon carbide Any combination of MOS tubes.
  • the resonant network includes a first resonant inductor and a resonant capacitor, and the first resonant inductor, the resonant capacitor and the first transformer inductor are connected in series.
  • the resonant network further includes a resistor, the resistor is connected to the first resonant circuit
  • the inductor, the resonant capacitor and the first transformer inductor are connected in series.
  • the autotransformer further includes a second resonant inductor.
  • the second resonant inductor When the number of turns of the first transformer inductor is greater than 0, the second resonant inductor is connected in parallel with the first transformer inductor.
  • the first transformer inductor has When the number of turns of the transformer inductor is equal to 0, the second resonant inductor is connected in parallel with the second transformer inductor.
  • the first transformer inductor when the number of turns of the first transformer inductor is greater than 0, the first transformer inductor includes at least one sub-transformer inductor, and the sub-transformer inductors are connected in series.
  • Figure 1 is a circuit schematic diagram of a non-isolated resonant converter in some embodiments of the present invention
  • Figure 2 is a schematic circuit diagram of a non-isolated resonant converter in some embodiments of the present invention
  • Figure 3 is a schematic circuit diagram of a non-isolated resonant converter in other embodiments of the present invention.
  • Figure 4 is a schematic circuit diagram of a non-isolated resonant converter in some embodiments of the present invention.
  • Figure 5 is a timing diagram of the non-isolated resonant converter shown in Figure 1 in some embodiments of the present invention
  • Figure 6 is a circuit schematic diagram of an STC non-isolated resonant converter in the prior art
  • FIG. 7 is a circuit schematic diagram of a buck conversion circuit in the prior art.
  • the non-isolated resonant converter 100 includes a first resonant bridge 101, a second resonant bridge 102, a freewheeling tube unit 103, a resonant network 104, an autotransformer 105, a load Ro and an output capacitor Co.
  • the coupling transformer 105 includes a first transformer inductor N1, a second transformer inductor N2 and a third transformer inductor N3, wherein the number of turns of the first transformer inductor N1 is greater than 0.
  • the resonant network and the first transformer inductor are connected in series to form a transformer resonant unit.
  • the first end of the transformer resonant unit is connected to the first resonant bridge, and the second end of the transformer resonant unit is connected to the first resonant bridge.
  • the end is connected to the second resonant bridge, the same-name end of the second transformer inductor is connected to the opposite-name end of the third transformer inductor, one end of the output capacitor, and one end of the load.
  • the second transformer inductor The opposite end of the inductor is connected to the first resonant bridge and the freewheeling tube unit, the same end of the third transformer inductor is connected to the second resonant bridge and the freewheeling tube unit, the first resonant The bridge and the second resonant bridge are also connected to the positive electrode of the power supply, and the freewheeling tube unit is connected to the other side of the output capacitor.
  • the first resonant bridge is used to connect the first end of the transformer resonant unit with the positive electrode of the power supply or the freewheeling tube
  • the second resonant bridge is used to connect The second end of the transformer resonant unit is connected to the positive electrode of the power supply or the freewheeling tube.
  • the freewheeling tube is used to connect the different-named end of the second transformer inductor or the same-named end of the third transformer inductor. The other end of the load is connected.
  • the first resonant bridge includes a first switch unit and a third switch unit, the first terminal of the first switch unit is connected to the positive pole of the power supply, and the second terminal of the first switch unit is connected to the The first end of the third switch unit is connected, and the second end of the third switch unit is connected to the opposite end of the second transformer inductor.
  • the second resonant bridge includes a second switch unit and a fourth switch unit, a first terminal of the second switch unit is connected to the positive pole of the power supply, and a second terminal of the second switch unit is connected to the The first end of the fourth switching unit is connected, and the second end of the fourth switching unit is connected to the same end of the third transformer inductor.
  • the freewheeling tube unit includes a fifth switch unit and a sixth switch unit.
  • the first end of the fifth switch unit is connected to the opposite end of the second transformer inductor.
  • the fifth switch The second end of the unit is connected to the other end of the load, the first end of the sixth switching unit is connected to the same end of the third transformer inductor, and the second end of the sixth switching unit is connected to the load. the other end of the connection. .
  • the first switch unit, the second switch unit, the third switch unit and the fourth switch unit are controllable switching devices
  • the fifth switch unit and the sixth switch unit are controllable switching devices.
  • the switching units are all uncontrollable switching devices or controllable switching devices.
  • the controllable switching device includes a metal oxide semiconductor field effect transistor, an insulated gate bipolar transistor, a gallium nitride transistor, a silicon carbide MOS transistor, and a first combined switch unit.
  • the first combined switch unit is a combination of a triode and a diode.
  • the uncontrollable switching device includes a diode and a second combined switch unit.
  • the second combined switch unit includes a diode and a metal oxide semi-field effect transistor, an insulated gate bipolar transistor, a gallium nitride transistor, or a silicon carbide MOS transistor. Any combination.
  • the first switching unit is a first NMOS transistor S1
  • the second switching unit is a second NMOS transistor S2
  • the third switching unit is a third NMOS transistor S3
  • the fourth switching unit is The fourth NMOS transistor S4
  • the fifth switching unit is the fifth NMOS transistor S5
  • the sixth switching unit is the sixth NMOS transistor S6.
  • the drain of the first NMOS transistor S1 is connected to the positive electrode of the power supply, the source of the first NMOS transistor S1 is connected to the drain of the third NMOS transistor S3, and the drain of the third NMOS transistor S3 is connected.
  • the source is connected to the opposite terminal of the second transformer inductor N2.
  • the drain of the second NMOS transistor S2 is connected to the positive electrode of the power supply, the source of the second NMOS transistor S2 is connected to the drain of the fourth NMOS transistor S4, and the drain of the fourth NMOS transistor S4 is connected.
  • the source is connected to the same terminal of the third transformer inductor N3.
  • the drain of the fifth NMOS transistor S5 is connected to the opposite end of the second transformer inductor N2, and the source of the fifth NMOS transistor S5 is connected to the other end of the load Ro and the output
  • the other end of the capacitor Co and the source of the sixth NMOS transistor S6 are connected to ground, and the drain of the sixth NMOS transistor S6 is connected to the same terminal of the third transformer inductor N3.
  • the gate of the first NMOS transistor is connected to the first control signal
  • the gate of the second NMOS transistor is connected to the second control signal
  • the gate of the third NMOS transistor is connected to the third control signal.
  • the gate of the fourth NMOS transistor is connected to the fourth control signal
  • the gate of the fifth NMOS transistor is connected to the fifth control signal
  • the gate of the sixth NMOS transistor is connected to the sixth control signal.
  • the resonant network includes a first resonant inductor and a resonant capacitor, and the first resonant inductor, the resonant capacitor and the first transformer inductor are connected in series.
  • the resonant network further includes a resistor, the resistor is connected in series with the first resonant inductor, the resonant capacitor, and the first transformer inductor.
  • the resonant network 104 includes a first resonant inductor Lr and a resonant capacitor Cr.
  • One end of the resonant capacitor Cr is connected to the source of the first NMOS transistor S1, and the other end of the resonant capacitor Cr is connected to the source of the first NMOS transistor S1.
  • One end of the first resonant inductor Lr is connected, the other end of the first resonant inductor Lr is connected to the same-name end of the first transformer inductor N1, and the opposite-name end of the first transformer inductor N1 is connected to the second NMOS
  • the source of tube S2 is connected.
  • the autotransformer further includes a second resonant inductor.
  • the second resonant inductor When the number of turns of the first transformer inductor is greater than 0, the second resonant inductor is connected in parallel with the first transformer inductor.
  • the second resonant inductor When the number of turns of a transformer inductor is equal to 0, the second resonant inductor is connected in parallel with the second transformer inductor.
  • the second resonant inductor is an independent inductor or a magnetizing inductor of the transformer.
  • the A transformer inductor when the number of turns of the first transformer inductor is greater than 0, the A transformer inductor includes at least one sub-transformer inductor, and the sub-transformer inductors are connected in series.
  • one end of the second resonant inductor Lm is connected to the same-name end of the first transformer inductor N1, and the other end of the second resonant inductor Lm is connected to the opposite-name end of the first transformer inductor N1.
  • FIG. 2 is a schematic circuit diagram of a non-isolated resonant converter in some embodiments of the present invention.
  • the difference between Figure 2 and Figure 1 is that the number of turns of the first transformer inductor N1 is equal to 0, that is, the other end of the first resonant inductor Lr is directly connected to the source of the second NMOS transistor S2, so The second resonant inductor Lm is connected in parallel with the second transformer inductor N2, that is, one end of the second resonant inductor Lm is connected to the opposite end of the second transformer inductor N2, and the other end of the second resonant inductor Lm Connect to the same end of the second transformer inductor N2.
  • FIG. 3 is a schematic circuit diagram of a non-isolated resonant converter in other embodiments of the present invention.
  • the difference between Figure 3 and Figure 1 is that both the fifth NMOS transistor S5 and the sixth NMOS transistor S6 are replaced with diodes.
  • FIG. 4 is a schematic circuit diagram of a non-isolated resonant converter in some embodiments of the present invention.
  • the difference between Figure 4 and Figure 2 is that both the fifth NMOS transistor S5 and the sixth NMOS transistor S6 are replaced with diodes.
  • FIG. 5 is a timing diagram of the non-isolated resonant converter shown in FIG. 1 in some embodiments of the present invention.
  • S 1 represents the first control signal
  • S 2 represents the second control signal
  • S 3 represents the third control signal
  • S 4 represents the fourth control signal
  • S 5 represents the fifth control signal
  • S 6 represents the sixth control signal
  • I Lr represents the current flowing through the first resonant inductor
  • I Lm represents the current flowing through the second resonant inductor
  • IN NS1 represents the current flowing through the first transformer inductor
  • V DS represents the current flowing through the first transformer inductor.
  • the first NMOS transistor S1, the fourth NMOS transistor S4 and the fifth NMOS transistor S5 are turned on, and the second NMOS transistor S2 and the third NMOS transistor S2 are turned on.
  • the transistor S3 and the sixth NMOS transistor S6 are turned off, and the turns ratio of the first transformer inductor Lr, the second transformer inductor N2 and the third transformer inductor N3 is n:1:1, n is greater than 0 , therefore, the voltage at both ends after the first resonant inductor Lr and the resonant capacitor Cr are connected in series is the resonant voltage, and the resonant voltage is equal to the difference between the power supply voltage V in and (n+2) times the output voltage Vo. Under the excitation of the resonant voltage, the current I Lr flowing through the first resonant inductor Lr rises according to the sinusoidal resonance and then decreases at resonance.
  • the current I Lm flowing through the second resonant inductor Lm is n times the output voltage Vo. Linearly increases under the action of One end flows into the first transformer inductor N1 through the same-name terminal of the first transformer inductor N1, and flows into the third transformer inductor N3 through the same-name terminal of the third transformer inductor N3.
  • the second transformer inductor N3 will induce (n+1) times the current flowing through the first transformer inductor N1, and flow out from the same terminal of the second transformer inductor N2 and flow into the output capacitor Co
  • One end of that is, the current flowing through the second transformer inductor N2 and the current flowing through the third transformer inductor N3 jointly charge the output capacitor Co, and the total current is (n+2) times flowing through the third transformer inductor N3.
  • the current of a transformer inductor N1 and the current flowing through the second resonant inductor N2 sum of currents.
  • the first NMOS transistor S1, the fourth NMOS transistor S4 and the fifth NMOS transistor S5 are turned off, and the first resonant inductor Lr and the resonant capacitor Cr are connected.
  • the direction of the current will not change suddenly.
  • the direction of the current on the first resonant inductor Lr is positive, which will charge the junction capacitance of the first NMOS transistor S1 and the junction capacitance of the fourth NMOS transistor S4.
  • the junction capacitance of the second NMOS transistor S2 and the junction capacitance of the third NMOS transistor S3 is discharged, and the current that charges the junction capacitance of the first NMOS transistor S1 and the fourth NMOS transistor S4 still flows in.
  • the current induced in the second transformer inductor N2 still flows from the same-name terminal of the third transformer inductor N3 through the different-name terminal. Therefore, although the fifth NMOS transistor S5 is turned off, the current still flows through the fifth NMOS transistor S5.
  • the body diode of the NMOS transistor S5, and the current flowing through the body diode of the fifth NMOS transistor S5 is (n+1) times the current flowing through the first transformer inductor N1, and the junction of the second NMOS transistor S2.
  • the current still flows into the second transformer N2 inductor from the opposite end of the second transformer inductor N2, and the current flowing through the second transformer inductor N2 is 2 times the difference between the current flowing through the first resonant inductor Lr and the current flowing through the second resonant inductor Lm.
  • the second NMOS transistor S2 and the third NMOS transistor S3 are 0 voltage conduction.
  • the body diode of the second NMOS transistor S2, the body diode of the third NMOS transistor S3, and the body diode of the fifth NMOS transistor S5 are conductive.
  • the resonant voltage at both ends is equal to the sum of the power supply voltage V in and n times the output voltage Vo.
  • the first resonant inductor Lr flows through and the current of the resonant capacitor Cr drops rapidly, and the current flowing into the first transformer inductor N1 is equal to the difference between the current flowing through the first resonant inductor Lr and the current flowing through the second resonant inductor Lm , when the current flowing through the first resonant inductor Lr is equal to the current flowing through the second resonant inductor Lm, the current flowing through the second transformer inductor N2 drops to 0, and at this time, the current flowing through the first resonant inductor Lm All the current of the resonant inductor Lr flows through the body diode of the fifth NMOS transistor S5, and the resonance state of the circuit remains unchanged.
  • the current flowing through the first resonant inductor Lr and the resonant capacitor Cr is at the resonant voltage.
  • the effect of The current part of the second resonant inductor Lm flows into the opposite terminal of the first transformer inductor N1, and the second transformer inductor N2 induces a current and flows out from the opposite terminal.
  • the second resonant inductor N2 The inductance value is relatively large. During this period, the current change on the second resonant inductor Lm is ignored.
  • the current on the first resonant inductor Lr decreases, the current flowing into the opposite end of the first transformer inductor N1 gradually increases. , the current induced by the second transformer inductor N2 gradually increases.
  • the current flowing through the third NMOS transistor S3 is the current flowing through the first resonant inductor Lr, and at the same time, the current flowing through the third resonant inductor Lr.
  • the sum of the current flowing through the body diode of the fifth NMOS transistor S5 and the current flowing through the second transformer inductor N2, as the current flowing through the second transformer inductor N2 gradually increases, the current flowing through the fifth NMOS transistor S5 The current gradually becomes smaller until time t2, when the current flowing through the fifth NMOS transistor S5 drops to 0, and the current flowing out of the opposite end of the second transformer inductor N2 is equal to the current flowing through the first resonant inductor Lr. , the fifth NMOS transistor S5 is turned off.
  • the fifth NMOS transistor S5 has just turned off, and the voltages across the source and drain of the fifth NMOS transistor S5 are 0. Therefore, the fifth NMOS transistor S5
  • the resonant voltage at both ends is equal to the sum of the power supply voltage V in and n times the output voltage Vo.
  • the first resonant inductor Lr and the resonant capacitor Cr flow through the first resonant inductor Lr and the resonant capacitor Cr.
  • the current of the resonant capacitor Cr decreases rapidly, the current flowing into the opposite terminal of the first transformer inductor N1 increases, the current flowing out of the opposite terminal of the second transformer inductor N2 increases accordingly, and the current flowing through the second transformer inductor N2
  • the junction capacitance of the fifth NMOS transistor S5 is greater than the current flowing through the first transformer inductor N1, and the current flowing through the second transformer inductor N2 is greater than the current flowing through the first transformer inductor N1. charge so that the source and drain of the fifth NMOS transistor S5 The voltage across the terminals increases.
  • the junction capacitance of the sixth NMOS transistor S6 begins to discharge, and the voltage across the source and drain of the sixth NMOS transistor S6 begins to decrease.
  • the first After the resonant inductor Lr and the resonant capacitor Cr are connected in series, the resonant voltage at both ends gradually decreases. Until time t3, the voltage at the source and drain of the sixth NMOS transistor S6 drops to 0. The body diode is turned on, clamping the voltage across the source and drain of the sixth NMOS transistor S6 at 0.
  • the resonant voltage at both ends of the first resonant inductor Lr and the resonant capacitor Cr gradually decreases until the resonant voltage at both ends of the first resonant inductor Lr and the resonant capacitor Cr is connected in series at time t3.
  • the sixth NMOS transistor S6 is clamped to the difference between the power supply voltage Vin and (n+2) times the output voltage Vo. At this time, the sixth NMOS transistor S6 is turned on at 0 voltage.
  • the resonant voltage at both ends after the first resonant inductor Lr and the resonant capacitor Cr are connected in series is between the power supply voltage V in and (n+2) times the output voltage Vo.
  • the output voltage Vo increases linearly under the action of the output voltage Vo.
  • the sine wave current on the first resonant inductor Lr flows through the second NMOS transistor S2, flows into the opposite terminal of the first transformer inductor N1, flows through the The third NMOS transistor S3 flows into the opposite end of the second transformer inductor N2 and outputs it to one end of the output capacitor Co. Since the current of the first transformer inductor N1 and the current of the second transformer inductor N2 are both determined by The opposite end flows in. According to the working principle of the autotransformer, the third transformer inductor N3 induces (n+1) times the electric current flowing through the first transformer inductor N1.
  • the output capacitor Co flows and flows out from the opposite terminal, and together with the current of the first transformer inductor N1 and the current of the second transformer inductor N2, flows into one end of the output capacitor Co, that is, the current flowing through the second transformer inductor N2 Together with the current flowing through the third transformer inductor N3, the output capacitor Co is charged.
  • the total current is (n+2) times the current flowing through the first transformer inductor N1 and the current flowing through the second resonance.
  • the switching frequency of the non-isolated resonant converter is higher than the resonant frequency of the first resonant inductor and the first two capacitors, or the switching frequency of the non-isolated resonant converter is lower than the first resonant capacitor.
  • the resonant frequency of the resonant inductor and the first and second capacitors, each switching unit adopts a controllable switching device or an uncontrollable switching device, and the working characteristic path changes slightly. Workers in the field can deduce the specific working mode, which will not be discussed here. Go into details.
  • the turn-on and turn-off of the first NMOS transistor, the second NMOS transistor, the third NMOS transistor and the fourth NMOS transistor cause the first resonant inductor and the resonant capacitor to It works in resonance with the second resonant inductor to form a resonant current.
  • the resonant current flows into the first transformer inductor and simultaneously flows into the second transformer inductor or the third transformer inductor, and flows into the third transformer where no current flows.
  • An induction film is formed in the inductor or the second transformer inductor, and through the freewheeling effect of the fifth NMOS tube or the sixth NMOS tube, the current flows from the same terminal of the second NMOS tube and the third NMOS tube.
  • the ends of the tubes with the same name flow out at the same time, so that the total current injected into one end of the output capacitor and one end of the load is proportionally distributed to the second transformer inductor and the third transformer inductor, reducing the current on the transformer inductor.
  • Valid values For example, the resonant current formed by the resonant operation of the first resonant inductor, the resonant capacitor and the second resonant inductor flows into the same-name terminal of the first transformer inductor. At this time, the current flows into the same-name terminal of the third transformer inductor.
  • a current is induced in the second transformer inductor and passes through the The current flowing out of the same terminal of the second transformer inductor and the sum of the resonant currents of the first resonant inductor, the resonant capacitor and the second resonant inductor flow into the output capacitor.
  • one end and one end of the load converting the input DC voltage into the output voltage.
  • the output voltage can be adjusted Adjustment; by adjusting the turns ratio of the autotransformer, the output voltage can be changed, thereby achieving non-isolation, input-output voltage conversion at high efficiency; utilizing the relationship between voltage and current in the autotransformer, the autotransformer current can be reduced The effective value of , improves the efficiency of the non-isolated resonant converter.

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Abstract

本发明提供了一种非隔离谐振变换器，包括第一谐振桥、第二谐振桥、续流管单元、谐振网络、自耦变压器、负载和输出电容，所述自耦变压器包括第一变压器电感、第二变压器电感和第三变压器电感，电路简单，控制简单易行，成本低。

Description

非隔离谐振变换器
本申请要求申请日为2022年08月30日，申请号为2022110493809，发明名称为“非隔离谐振变换器”的中国专利申请的优先权。上述申请的内容以引用方式被包含于此。
技术领域
本发明涉及电源技术领域，尤其涉及一种非隔离谐振变换器。
背景技术
近年来随着计算量的提高，服务器单板卡的电能需求越来越大，尤其随着机架式服务器的广泛使用，直流供电总线的电流越来越大，采用48V总线为服务器板卡供电的电源架构逐渐取代了12V总线的传统架构；这种48V架构通常是通过交流电源将交流电网电源转化为48V直流总线，再由DCDC电源将48V转换为12V，12V再转换为各芯片组所需的低至0.6V的各种电压为芯片组进行供电，也有一些方案是直接将48V直接转化为1V左右CPU core电压为CPU供电。由于服务器系统中除各芯片组需要低至0.6V的低压供电外，还有许多12V负载，如风扇和内存等，48V转12V后再由12V转为电压为芯片组供电的方式逐渐成为主流。
一方面服务器市场的体量巨大，成本压力高；另一方面全球范围的节能降耗要求越来越高，这就使得低成本、高效能的48V转12V成为电力电子领域的一个非常重要的研究方向，许多研究资源进入到 这个领域，并且很多研究成果陆续呈现。得到最广泛应用的有两个技术方向：一个方向是在传统通讯领域中广泛应用的48V转12V模块电源基础上不断优化设计。这个方向近年来不断有新的产品推出，功率密度和效率也逐年提高；各头部企业大多采用隔离的半桥或全桥硬开关电路，少部分采用隔离的半桥或全桥LLC非隔离谐振变换器电路；为达到更高的效率和功率密度，此发展方向不断的增加PCB板的层数和铜厚，不断优化隔离变压器设计，选择性能更优异的功率MOS管，这带来的后果是不断推高产品的成本，加长开发周期，提高设计难度和对技术人员的技术要求，使得该方向的发展到了一个瓶颈，很难在性能和价格之间继续平衡发展。另一个方向是非隔离48V转12V应用，并首先推出了对应的开关储能变换器非隔离谐振变换器(Switched Tank Converters，STC)，如图6所示。这个变换器通过多级谐振电路级联，可以实现所有开关器件的软开关，且开关器件的应力通过开关器件串联和输出电压钳位的方式，得到有效的控制，使得变换器的效率在较低的成本上得到非常有效的提升使得该电路一度成为研究领域的热点。不过这个电路同样存在两个先天的不足：首先变换器为开关电容电路的一个谐振方案，输入输出电压的关系为固定变比，不能进行调压，极大的限制了变换器的应用，尤其在几个头部企业相继将其服务器电源方案转向12V电压可控后，这个电路的关注度开始下降；此外，开关器件多、控制复杂，多开关器件串联使驱动方案、辅助源设计复杂，在没有专用模拟控制器的情况下使电路的实现和成本被推高，也在一定程度上限制了电路的应用。在这之 后，如图7所示的降压式变换电路再次得到关注，该电路在传统降压式变换电路中增加了串联电容，由于该电容的存在，使得变换器的占空比可以展开，并极大减小了输出滤波电感前的电压脉动，改善了滤波电感的工作条件，使得变换器可降低开关频率，减小开关损耗，提升效率，同时变换器的电路结构同STC电路相比也要简单，降低了设计难度。该电路是当前非隔离48V转12V应用中较为优化的方案。该电路唯一的缺点是硬开关。由于开关器件在工作中处于硬开关条件，一定程度上限制了变换器的开关频率的提高，这就限制了模块进一步提升电源模块的功率密度。
因此，有必要提供一种新型的非隔离谐振变换器以解决现有技术中存在的上述问题。
发明内容
本发明的目的在于提供一种非隔离谐振变换器，降低控制难度和成本。
为实现上述目的，本发明的所述非隔离谐振变换器，包括第一谐振桥、第二谐振桥、续流管单元、谐振网络、自耦变压器、负载和输出电容，所述自耦变压器包括第一变压器电感、第二变压器电感和第三变压器电感，所述谐振网络和所述第一变压器电感串联后以构成变压器谐振单元，所述变压器谐振单元的第一端与所述第一谐振桥连接，所述变压器谐振单元的第二端与所述第二谐振桥连接，所述第二变压器电感的同名端与所述第三变压器电感的异名端、所述输出电容一端、 所述负载的一端连接，所述第二变压器电感的异名端与所述第一谐振桥和所述续流管单元连接，所述第三变压器电感的同名端与所述第二谐振桥和所述续流管单元连接，所述第一谐振桥和所述第二谐振桥还与电源的正极连接，所述续流管单元与所述输出电容的另一端、所述负载的另一端连接并接地，所述第一谐振桥用于将所述变压器谐振单元的第一端与电源的正极或所述续流管连通，所述第二谐振桥用于将所述变压器谐振单元的第二端与电源的正极或所述续流管连通，所述续流管用于将所述第二变压器电感的异名端或所述第三变压器电感的同名端与所述负载的另一端连通，其中，所述第一变压器电感的匝数大于或等于0。
所述非隔离谐振变换器的有益效果在于：包括第一谐振桥、第二谐振桥、续流管单元、谐振网络、自耦变压器、负载和输出电容，所述自耦变压器包括第一变压器电感、第二变压器电感和第三变压器电感，电路简单，控制简单易行，成本低。
可选地，所述第一谐振桥包括第一开关单元和第三开关单元，所述第一开关单元的第一端接电源的正极，所述第一开关单元的第二端与所述第三开关单元的第一端连接，所述第三开关单元的第二端与所述第二变压器电感的异名端连接。
可选地，所述第一开关单元和所述第三开关单元均为可控开关器件。
可选地，所述第二谐振桥包括第二开关单元和第四开关单元，所 述第二开关单元的第一端接电源的正极，所述第二开关单元的第二端与所述第四开关单元的第一端连接，所述第四开关单元的第二端与所述第三变压器电感的同名端连接。
可选地，所述第二开关单元和所述第四开关单元均为可控开关器件。
可选地，所述续流管单元包括第五开关单元和第六开关单元，所述第五开关单元的第一端与所述第二变压器电感的异名端连接，所述第五开关单元的第二端与所述负载的另一端连接，所述第六开关单元的第一端与所述第三变压器电感的同名端连接，所述第六开关单元的第二端与所述负载的另一端连接。
可选地，所述第五开关单元和所述第六开关单元均为不可控开关器件或可控开关器件。
可选地，所述可控开关器件包括金氧半场效晶体管、绝缘栅双极型晶体管、氮化镓晶体管、碳化硅MOS管以及第一组合开关单元，所述第一组合开关单元为三极管与二极管的组合。
可选地，所述不可控开关器件包括二极管和第二组合开关单元，所述第二组合开关单元包括二极管与金氧半场效晶体管、绝缘栅双极型晶体管、氮化镓晶体管、碳化硅MOS管中任意一个的组合。
可选地，所述谐振网络包括第一谐振电感和谐振电容，所述第一谐振电感、所述谐振电容和所述第一变压器电感串联。
可选地，所述谐振网络还包括电阻，所述电阻与所述第一谐振电 感、所述谐振电容、所述第一变压器电感串联。
可选地，所述自耦变压器还包括第二谐振电感，当所述第一变压器电感的匝数大于0时，所述第二谐振电感与所述第一变压器电感并联，当所述第一变压器电感的匝数等于0时，所述第二谐振电感与所述第二变压器电感并联。
可选地，当所述第一变压器电感的匝数大于0时，所述第一变压器电感包括至少一个子变压器电感，所述子变压器电感之间串联。
附图说明
图1为本发明一些实施例中非隔离谐振变换器的电路示意图；
图2为本发明又一些实施例中非隔离谐振变换器的电路示意图；
图3为本发明另一些实施例中非隔离谐振变换器的电路示意图；
图4为本发明再一些实施例中非隔离谐振变换器的电路示意图；
图5为本发明一些实施例中图1所示非隔离谐振变换器的时序图；
图6为现有技术中一种STC非隔离谐振变换器的电路示意图；
图7为现有技术中一种降压式变换电路的电路示意图。
具体实施方式
为使本发明的目的、技术方案和优点更加清楚，下面将结合本发 明的附图，对本发明实施例中的技术方案进行清楚、完整地描述，显然，所描述的实施例是本发明的一部分实施例，而不是全部的实施例。基于本发明中的实施例，本领域普通技术人员在没有作出创造性劳动前提下所获得的所有其他实施例，都属于本发明保护的范围。除非另外定义，此处使用的技术术语或者科学术语应当为本发明所属领域内具有一般技能的人士所理解的通常意义。本文中使用的“包括”等类似的词语意指出现该词前面的元件或者物件涵盖出现在该词后面列举的元件或者物件及其等同，而不排除其他元件或者物件。
针对现有技术存在的问题，本发明的实施例提供了一种非隔离谐振变换器。参照图1，所述非隔离谐振变换器100包括第一谐振桥101、第二谐振桥102、续流管单元103、谐振网络104、自耦变压器105、负载Ro和输出电容Co，所述自耦变压器105包括第一变压器电感N1、第二变压器电感N2和第三变压器电感N3，其中，所述第一变压器电感N1的匝数大于0。
一些实施例中，所述谐振网络和所述第一变压器电感串联后以构成变压器谐振单元，所述变压器谐振单元的第一端与所述第一谐振桥连接，所述变压器谐振单元的第二端与所述第二谐振桥连接，所述第二变压器电感的同名端与所述第三变压器电感的异名端、所述输出电容一端、所述负载的一端连接，所述第二变压器电感的异名端与所述第一谐振桥和所述续流管单元连接，所述第三变压器电感的同名端与所述第二谐振桥和所述续流管单元连接，所述第一谐振桥和所述第二谐振桥还与电源的正极连接，所述续流管单元与所述输出电容的另一 端、所述负载的另一端连接并接地，所述第一谐振桥用于将所述变压器谐振单元的第一端与电源的正极或所述续流管连通，所述第二谐振桥用于将所述变压器谐振单元的第二端与电源的正极或所述续流管连通，所述续流管用于将所述第二变压器电感的异名端或所述第三变压器电感的同名端与所述负载的另一端连通。
一些实施例中，所述第一谐振桥包括第一开关单元和第三开关单元，所述第一开关单元的第一端接电源的正极，所述第一开关单元的第二端与所述第三开关单元的第一端连接，所述第三开关单元的第二端与所述第二变压器电感的异名端连接。
一些实施例中，所述第二谐振桥包括第二开关单元和第四开关单元，所述第二开关单元的第一端接电源的正极，所述第二开关单元的第二端与所述第四开关单元的第一端连接，所述第四开关单元的第二端与所述第三变压器电感的同名端连接。
一些实施例中，所述续流管单元包括第五开关单元和第六开关单元，所述第五开关单元的第一端与所述第二变压器电感的异名端连接，所述第五开关单元的第二端与所述负载的另一端连接，所述第六开关单元的第一端与所述第三变压器电感的同名端连接，所述第六开关单元的第二端与所述负载的另一端连接。。
一些实施例中，所述第一开关单元、所述第二开关单元、所述第三开关单元和所述第四开关单元均为可控开关器件，所述第五开关单元和所述第六开关单元均为不可控开关器件或可控开关器件。具体地， 所述可控开关器件包括金氧半场效晶体管、绝缘栅双极型晶体管、氮化镓晶体管、碳化硅MOS管以及第一组合开关单元，所述第一组合开关单元为三极管与二极管的组合，所述不可控开关器件包括二极管和第二组合开关单元，所述第二组合开关单元包括二极管与金氧半场效晶体管、绝缘栅双极型晶体管、氮化镓晶体管、碳化硅MOS管中任意一个的组合。
参照图1，所述第一开关单元为第一NMOS管S1，所述第二开关单元为第二NMOS管S2，所述第三开关单元为第三NMOS管S3，所述第四开关单元为第四NMOS管S4，所述第五开关单元为第五NMOS管S5，所述第六开关单元为第六NMOS管S6。
参照图1，所述第一NMOS管S1的漏极接电源的正极，所述第一NMOS管S1的源极与所述第三NMOS管S3的漏极连接，所述第三NMOS管S3的源极与所述第二变压器电感N2的异名端连接。
参照图1，所述第二NMOS管S2的漏极接电源的正极，所述第二NMOS管S2的源极与所述第四NMOS管S4的漏极连接，所述第四NMOS管S4的源极与所述第三变压器电感N3的同名端连接。
参照图1，所述第五NMOS管S5的漏极与所述第二变压器电感N2的异名端连接，所述第五NMOS管S5的源极与所述负载Ro的另一端、所述输出电容Co的另一端、所述第六NMOS管S6的源极连接后接地，所述第六NMOS管S6的漏极与所述第三变压器电感N3的同名端连接。
一些实施例中，所述第一NMOS管的栅极接第一控制信号，所述第二NMOS管的栅极接第二控制信号，所述第三NMOS管的栅极接第三控制信号，所述第四NMOS管的栅极接第四控制信号，所述第五NMOS管的栅极接第五控制信号，所述第六NMOS管的栅极接第六控制信号。
一些实施例中，所述谐振网络包括第一谐振电感和谐振电容，所述第一谐振电感、所述谐振电容和所述第一变压器电感串联。
又一些实施例中，所述谐振网络还包括电阻，所述电阻与所述第一谐振电感、所述谐振电容、所述第一变压器电感串联。
参照图1，所述谐振网络104包括第一谐振电感Lr和谐振电容Cr，所述谐振电容Cr的一端与所述第一NMOS管S1的源极连接，所述谐振电容Cr的另一端与所述第一谐振电感Lr的一端连接，所述第一谐振电感Lr的另一端与所述第一变压器电感N1的同名端连接，所述第一变压器电感N1的异名端与所述第二NMOS管S2的源极连接。
一些实施例中，所述自耦变压器还包括第二谐振电感，当所述第一变压器电感的匝数大于0时，所述第二谐振电感与所述第一变压器电感并联，当所述第一变压器电感的匝数等于0时，所述第二谐振电感与所述第二变压器电感并联。其中，所述第二谐振电感为独立电感或所述变压器的激磁电感。
一些实施例中，当所述第一变压器电感的匝数大于0时，所述第 一变压器电感包括至少一个子变压器电感，所述子变压器电感之间串联。
参照图1，所述第二谐振电感Lm的一端与所述第一变压器电感N1的同名端连接，所述第二谐振电感Lm的另一端与所述第一变压器电感N1的异名端连接。
图2为本发明又一些实施例中非隔离谐振变换器的电路示意图。图2与图1的区别在于：所述第一变压器电感N1的匝数等于0，即相当于所述第一谐振电感Lr的另一端直接与所述第二NMOS管S2的源极连接，所述第二谐振电感Lm与所述第二变压器电感N2并联，即所述第二谐振电感Lm的一端与所述第二变压器电感N2的异名端连接，所述第二谐振电感Lm的另一端与所述第二变压器电感N2的同名端连接。
图3为本发明另一些实施例中非隔离谐振变换器的电路示意图。图3与图1的区别在于：将所述第五NMOS管S5和所述第六NMOS管S6均替换为二极管。
图4为本发明再一些实施例中非隔离谐振变换器的电路示意图。图4与图2的区别在于：将所述第五NMOS管S5和所述第六NMOS管S6均替换为二极管。
图5为本发明一些实施例中图1所示非隔离谐振变换器的时序图。参照图1和图5，S1表示所述第一控制信号，S2表示第二控制信号，S3表示第三控制信号，S4表示第四控制信号，S5表示第五控制信号， S6表示第六控制信号，ILr表示流经第一谐振电感的电流，ILm表示流经第二谐振电感的电流，INS1表示流经所述第一变压器电感的电流，VDS表示所述第三NMOS管源极和漏极两端的电压。
参照图1和图5，t0时刻之前，所述第一NMOS管S1、所述第四NMOS管S4和所述第五NMOS管S5导通，所述第二NMOS管S2、所述第三NMOS管S3和所述第六NMOS管S6关断，所述第一变压器电感Lr、所述第二变压器电感N2和所述第三变压器电感N3的匝数比为n：1:1，n大于0，因此，所述第一谐振电感Lr和所述谐振电容Cr串联后两端的电压为谐振电压，所述谐振电压等于电源电压Vin与(n+2)倍输出电压Vo的差值，在所述谐振电压的激励下，流经所述第一谐振电感Lr的电流ILr按正弦谐振上升后在谐振下降，流经所述第二谐振电感Lm的电流ILm在n倍所述输出电压Vo的作用下线性增加，所述第一谐振电感Lr中的正弦波电流流经所述第一变压器电感N1、所述第四NMOS管S4和所述第三变压器电感N3到所述输出电容Co的一端，且经所述第一变压器电感N1的同名端流入所述第一变压器电感N1，经所述第三变压器电感N3的同名端流入所述第三变压器电感N3，根据自耦变压器的工作原理，所述第二变压器电感N3将感应出(n+1)倍流经所述第一变压器电感N1的电流，并由所述第二变压器电感N2的同名端流出，流入到所述输出电容Co的一端，即流经所述第二变压器电感N2的电流和流经所述第三变压器电感N3的电流共同对所述输出电容Co充电，总电流为(n+2)倍流经所述第一变压器电感N1的电流与流经所述第二谐振电感N2的 电流之和。
参照图1和图5，t0时刻，所述第一NMOS管S1、所述第四NMOS管S4和所述第五NMOS管S5关断，所述第一谐振电感Lr和所述谐振电容Cr上的电流方向不会突变，此时，所述第一谐振电感Lr上的电流方向为正，将对所述第一NMOS管S1的结电容和所述第四NMOS管S4的结电容充电，同时对所述第二NMOS管S2的结电容和所述第三NMOS管S3的结电容放电，对所述第一NMOS管S1的结电容和所述第四NMOS管S4结电容充电的电流仍然流入所述第三变压器电感N3的同名端，所述第二变压器电感N2中感应出电流仍然由异名端流入，故所述第五NMOS管S5虽然关断，但电流仍然流经所述第五NMOS管S5的体二极管，且流经所述第五NMOS管S5的体二极管的电流为(n+1)倍流经所述第一变压器电感N1的电流、所述第二NMOS管S2的结电容放电电流、所述第三NMOS管S3结电容放电电流之和。
参照图1和图5，t0～t1时刻，由于结电容容量很小，可以认为在此阶段，所述第一NMOS管源极和漏极两端的电压线性上升，所述第四NMOS管S4源极和漏极两端的电压线性上升，所述第二NMOS管S2源极和漏极两端的电压线性下降，所述第三NMOS管S3源极和漏极两端两端的电压线性下降；在所述第二NMOS管S2源极和漏极两端的电压以及所述第三NMOS管S3源极和漏极两端的电压下降到0后，所述第二NMOS管S2的体二极管和所述第三NMOS管S3的体二极管导通，将所述第二NMOS管S2源极和漏极两端的电压以 及所述第三NMOS管S3源极和漏极两端的电压钳位在0，同时将所述第四NMOS管S4源极和漏极两端的电压钳位在输入电压Vin与2倍所述输出电压Vo之间的差值；由于无充电电流流经所述第四NMOS管S4，流经所述第三NMOS管S3的电流下降到0，此时流经所述第一谐振电感Lr的电流大于流经所述第二谐振电感Lm的电流，电流仍由所述第二变压器电感N2的异名端流入所述第二变压器N2电感，且流经所述第二变压器电感N2的电流是流经所述第一谐振电感Lr的电流与流经所述第二谐振电感Lm的电流之间的差值的2倍，此时所述第二NMOS管S2和所述第三NMOS管S3为0电压导通。
参照图1和图5，t1～t2时刻，所述第二NMOS管S2的体二极管、所述第三NMOS管S3的体二极管和所述第五NMOS管S5的体二极管导通，所述第一谐振电感Lr和所述谐振电容Cr串联后两端的谐振电压等于电源电压Vin与n倍所述输出电压Vo之和，在所述谐振电压的作用下，流经所述第一谐振电感Lr和所述谐振电容Cr的电流迅速下降，流入所述第一变压器电感N1的电流等于流经所述第一谐振电感Lr的电流与流经所述第二谐振电感Lm的电流之间的差值，当流经所述第一谐振电感Lr的电流等于流经所述第二谐振电感Lm的电流时，流经所述第二变压器电感N2的电流下降到0，此时流经所述第一谐振电感Lr的电流全部经所述第五NMOS管S5的体二极管流过，电路的谐振状态不变，故流经所述第一谐振电感Lr和所述谐振电容Cr的电流在所述谐振电压的作用迅速下降，此时流经所述第一谐振电感Lr的电流小于流经所述第二谐振电感Lm的电流，流经 所述第二谐振电感Lm的电流部分流入所述第一变压器电感N1的异名端，所述第二变压器电感N2感应出电流并由异名端流出，而考虑到所述第二谐振电感N2的电感值比较大，在此期间忽略所述第二谐振电感Lm上的电流变化，随所述第一谐振电感Lr上的电流下降，流入所述第一变压器电感N1异名端的电流逐渐增大，所述第二变压器电感N2感应出的电流逐渐增大，此时，流经所述第三NMOS管S3的电流为流经所述第一谐振电感Lr的电流，同时是流经所述第五NMOS管S5体二极管的电流与流经所述第二变压器电感N2的电流之和，随着流经所述第二变压器电感N2的电流逐渐增大，流经所述第五NMOS管S5的电流逐渐变小，直至t2时刻，流经所述第五NMOS管S5的电流下降到0，所述第二变压器电感N2异名端流出的电流与流经所述第一谐振电感Lr的电流相等，所述第五NMOS管S5关断。
参照图1和图5，t2～t3时刻，在t2时刻，所述第五NMOS管S5刚刚关断，所述第五NMOS管S5源极和漏极两端的电压为0，因此，所述第一谐振电感Lr和所述谐振电容Cr串联后两端的谐振电压等于电源电压Vin与n倍所述输出电压Vo之和，在谐振电压的作用下，流经所述第一谐振电感Lr和所述谐振电容Cr的电流迅速下降，流入所述第一变压器电感N1异名端的电流增加，流出所述第二变压器电感N2异名端的电流随之增加，流经所述第二变压器电感N2的电流大于流经所述第一变压器电感N1的电流，且流经所述第二变压器电感N2的电流大于流经所述第一变压器电感N1的电流的部分对所述第五NMOS管S5的结电容充电，使所述第五NMOS管S5源极和漏 极两端电压升高，根据自耦变压器的耦合关系，所述第六NMOS管S6的结电容开始放电，所述第六NMOS管S6源极和漏极两端电压开始下降，所述第一谐振电感Lr和所述谐振电容Cr串联后两端的谐振电压逐渐减小，直至t3时刻，所述第六NMOS管S6源极和漏极两端的电压下降到0，所述第六NMOS管S6的体二极管导通，将所述第六NMOS管S6源极和漏极两端的电压钳位在0。在此过程中，所述第一谐振电感Lr和所述谐振电容Cr串联后两端的谐振电压逐渐减小，直至t3时刻所述第一谐振电感Lr和所述谐振电容Cr串联后两端的谐振电压被所述第六NMOS管S6钳位在电源电压Vin与(n+2)倍所述输出电压Vo之间的差值，此时所述第六NMOS管S6为0电压导通。
参照图1和图5，t3时刻之后，所述第一谐振电感Lr和所述谐振电容Cr串联后两端的谐振电压为电源电压Vin与(n+2)倍所述输出电压Vo之间的差值，在谐振电压的激励下，所述第一谐振电感Lr和所述谐振电容Cr上的电流先按正弦谐振上升后再谐振下降，流经所述第二谐振电感Lm的电流在n倍所述输出电压Vo的作用下线性增加，所述第一谐振电感Lr上的正弦波电流流经所述第二NMOS管S2、流入所述第一变压器电感N1的异名端、流经所述第三NMOS管S3、流入所述第二变压器电感N2的异名端输出到所述输出电容Co的一端，由于所述第一变压器电感N1的电流和所述第二变压器电感N2的电流均由异名端流入，根据自耦变压器的工作原理，所述第三变压器电感N3感应出(n+1)倍流经所述第一变压器电感N1的电 流并由异名端流出，与所述第一变压器电感N1的电流、所述第二变压器电感N2的电流共同流入所述输出电容Co的一端，即流经所述第二变压器电感N2的电流和流经所述第三变压器电感N3的电流共同对所述输出电容Co充电，总电流为(n+2)倍流流经所述第一变压器电感N1的电流与流经所述第二谐振电感Lm上的电流之和。后续流程为重复流程，原理相同，在此不再详细赘述。
本申请中，所述非隔离谐振变换器的开关频率高于所述第一谐振电感和所述第一二电容的谐振频率，或所述非隔离谐振变换器的开关频率低于所述第一谐振电感和所述第一二电容的谐振频率，各开关单元采用可控开关器件或不可控开关器件，工作特征路略有变化，本领域工作人员能够推导出具体的工作方式，在此不再详细赘述。
本申请中，所述第一NMOS管、所述第二NMOS管、所述第三NMOS管和所述第四NMOS管的导通和关断，使所述第一谐振电感、所述谐振电容和所述第二谐振电感谐振工作形成谐振电流，谐振电流流入所述第一变压器电感的同时流入所述第二变压器电感或所述第三变压器电感，并在未流入电流的所述第三变压器电感或所述第二变压器电感中形成感应电影，通过所述第五NMOS管或所述第六NMOS管的续流作用，使电流从所述第二NMOS管的同名端和所述第三NMOS管的同名端同时流出，实现将注入所述输出电容的一端、所述负载的一端的总电流按比例分配在所述第二变压器电感和所述第三变压器电感，减少了变压器电感上电流的有效值。例如，所述第一谐振电感、所述谐振电容和所述第二谐振电感谐振工作形成的谐振电流 流入所述第一变压器电感的同名端，此时此电流流入所述第三变压器电感的同名端，经过自耦变压器的耦合作用，在所述第二变压器电感的中感应出电流并经所述第二变压器电感的同名端流出，所述第二变压器电感的同名端流出的电流与所述第一谐振电感、所述谐振电容和所述第二谐振电感的谐振电流之和流入所述输出电容的一端和所述负载的一端，将输入直流电压转换为输出电压。
利用所述第一谐振电感、所述谐振电容和所述第二谐振电感的谐振工作，可以实现全部开关单元的软开关；通过调整所述非隔离谐振变换器的开关频率，可以实现输出电压的调整；通过调整所述自耦变压器的匝比，能够改变输出电压，进而能够在高效率下实现非隔离，输入输出的电压转换；利用自耦变压器中电压电流的关系，减少了自耦变压器电流的有效值，提高了所述非隔离谐振变换器的效率。
虽然在上文中详细说明了本发明的实施方式，但是对于本领域的技术人员来说显而易见的是，能够对这些实施方式进行各种修改和变化。但是，应理解，这种修改和变化都属于权利要求书中所述的本发明的范围和精神之内。而且，在此说明的本发明可有其它的实施方式，并且可通过多种方式实施或实现。

Claims (13)

  1. 一种非隔离谐振变换器，其特征在于，包括第一谐振桥、第二谐振桥、续流管单元、谐振网络、自耦变压器、负载和输出电容，所述自耦变压器包括第一变压器电感、第二变压器电感和第三变压器电感，所述谐振网络和所述第一变压器电感串联后以构成变压器谐振单元，所述变压器谐振单元的第一端与所述第一谐振桥连接，所述变压器谐振单元的第二端与所述第二谐振桥连接，所述第二变压器电感的同名端与所述第三变压器电感的异名端、所述输出电容一端、所述负载的一端连接，所述第二变压器电感的异名端与所述第一谐振桥和所述续流管单元连接，所述第三变压器电感的同名端与所述第二谐振桥和所述续流管单元连接，所述第一谐振桥和所述第二谐振桥还与电源的正极连接，所述续流管单元与所述输出电容的另一端、所述负载的另一端连接并接地，所述第一谐振桥用于将所述变压器谐振单元的第一端与电源的正极或所述续流管连通，所述第二谐振桥用于将所述变压器谐振单元的第二端与电源的正极或所述续流管连通，所述续流管用于将所述第二变压器电感的异名端或所述第三变压器电感的同名端与所述负载的另一端连通，其中，所述第一变压器电感的匝数大于或等于0。
  2. 根据权利要求1所述的非隔离谐振变换器，其特征在于，所述第一谐振桥包括第一开关单元和第三开关单元，所述第一开关单元的第一端接电源的正极，所述第一开关单元的第二端与所述第三开关单元的第一端连接，所述第三开关单元的第二端与所述第二变压器电感 的异名端连接。
  3. 根据权利要求2所述的非隔离谐振变换器，其特征在于，所述第一开关单元和所述第三开关单元均为可控开关器件。
  4. 根据权利要求1所述的非隔离谐振变换器，其特征在于，所述第二谐振桥包括第二开关单元和第四开关单元，所述第二开关单元的第一端接电源的正极，所述第二开关单元的第二端与所述第四开关单元的第一端连接，所述第四开关单元的第二端与所述第三变压器电感的同名端连接。
  5. 根据权利要求4所述的非隔离谐振变换器，其特征在于，所述第二开关单元和所述第四开关单元均为可控开关器件。
  6. 根据权利要求1所述的非隔离谐振变换器，其特征在于，所述续流管单元包括第五开关单元和第六开关单元，所述第五开关单元的第一端与所述第二变压器电感的异名端连接，所述第五开关单元的第二端与所述负载的另一端连接，所述第六开关单元的第一端与所述第三变压器电感的同名端连接，所述第六开关单元的第二端与所述负载的另一端连接。
  7. 根据权利要求6所述的非隔离谐振变换器，其特征在于，所述第五开关单元和所述第六开关单元均为不可控开关器件或可控开关器件。
  8. 根据权利要求3、5或7所述的非隔离谐振变换器，其特征在于，所述可控开关器件包括金氧半场效晶体管、绝缘栅双极型晶体管、氮化镓晶体管、碳化硅MOS管以及第一组合开关单元，所述第一组合开关单元为三极管与二极管的组合。
  9. 根据权利要求7所述的非隔离谐振变换器，其特征在于，所述不可控开关器件包括二极管和第二组合开关单元，所述第二组合开关单元包括二极管与金氧半场效晶体管、绝缘栅双极型晶体管、氮化镓晶体管、碳化硅MOS管中任意一个的组合。
  10. 根据权利要求1所述的非隔离谐振变换器，其特征在于，所述谐振网络包括第一谐振电感和谐振电容，所述第一谐振电感、所述谐振电容和所述第一变压器电感串联。
  11. 根据权利要求10所述的非隔离谐振变换器，其特征在于，所述谐振网络还包括电阻，所述电阻与所述第一谐振电感、所述谐振电容、所述第一变压器电感串联。
  12. 根据权利要求1所述的非隔离谐振变换器，其特征在于，所述自耦变压器还包括第二谐振电感，当所述第一变压器电感的匝数大于0时，所述第二谐振电感与所述第一变压器电感并联，当所述第一变压器电感的匝数等于0时，所述第二谐振电感与所述第二变压器电感并联。
  13. 根据权利要求1所述的非隔离谐振变换器，其特征在于，当 所述第一变压器电感的匝数大于0时，所述第一变压器电感包括至少一个子变压器电感，所述子变压器电感之间串联。
PCT/CN2023/102031 2022-08-30 2023-06-25 非隔离谐振变换器 WO2024045797A1 (zh)

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