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WO2022166941A1 - 超宽带天线及天线阵列 - Google Patents

超宽带天线及天线阵列 Download PDF

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Publication number
WO2022166941A1
WO2022166941A1 PCT/CN2022/075333 CN2022075333W WO2022166941A1 WO 2022166941 A1 WO2022166941 A1 WO 2022166941A1 CN 2022075333 W CN2022075333 W CN 2022075333W WO 2022166941 A1 WO2022166941 A1 WO 2022166941A1
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WO
WIPO (PCT)
Prior art keywords
ultra
metal
sub
wideband antenna
metal structural
Prior art date
Application number
PCT/CN2022/075333
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English (en)
French (fr)
Inventor
商进
杨杰钧
Original Assignee
上海安费诺永亿通讯电子有限公司
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Publication of WO2022166941A1 publication Critical patent/WO2022166941A1/zh

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    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/36—Structural form of radiating elements, e.g. cone, spiral, umbrella; Particular materials used therewith
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/48—Earthing means; Earth screens; Counterpoises
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q1/00—Details of, or arrangements associated with, antennas
    • H01Q1/50—Structural association of antennas with earthing switches, lead-in devices or lightning protectors
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/0006—Particular feeding systems
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/20—Arrays of individually energised antenna units similarly polarised and spaced apart the units being spaced along or adjacent to a curvilinear path

Definitions

  • the invention relates to the design field of ultra-wideband antenna structures, in particular to an ultra-wideband antenna and an antenna array.
  • GNSS systems mainly include well-known navigation systems such as GPS in the United States, Galileo in Europe, GLONASS in Russia and Beidou system in China. wave (RHCP).
  • the SDARS system is the abbreviation of satellite digital audio broadcasting service, its frequency band is 2.32G-2.345G, and the circularly polarized wave used is left-hand circularly polarized wave (LHCP).
  • the design of a circularly polarized antenna that includes both GNSS and SDARS bands is currently a difficult problem because the two frequency bands are far apart, or only part of the GNSS frequency band (such as 1.56G-1.6 G) and SDARS band.
  • the idea of separating the two and designing them independently is mainly adopted, which increases the space size of the antenna system design.
  • the current GNSS and SDARS antennas mostly use high-cost ceramic material-based patch antennas. Under the condition of the same size, the use of low-cost low-dielectric constant materials has also become a requirement.
  • millimeter wave band is a highlight.
  • the current millimeter wave bands are mainly concentrated in 24.5G-29.5G (such as n257, n258 and n261) and 37.5G-42.5G (such as n260).
  • millimeter-wave antennas mostly use array design and spatially orthogonal dual-polarized wave modes.
  • how to design an ultra-wideband dual-polarized antenna that includes the above bands and modes at the same time becomes a difficult problem.
  • the object of the present invention is to provide an ultra-wideband antenna and an antenna array for solving the miniaturization of ultra-wideband antennas in the satellite communication and navigation field and/or mobile communication field in the prior art limitations, etc.
  • the present invention provides an ultra-wideband antenna
  • the ultra-wideband antenna includes: a reference ground metal plate, 4 identical sub-metal structural units and 4 feed structures;
  • Each of the sub-metal structural units includes: a first metal structural member extending in a horizontal direction, two second metal structural members extending in a vertical direction and spaced apart, and two metal structural members of the second metal structural member One end is directly connected to the first metal structure, the other end of one second metal structure is connected to the reference ground metal plate, and the other end of the other second metal structure is connected to the reference ground A said feeding structure is added between the metal plates;
  • the absolute value of the feed phase difference between the two feed structures of the two adjacent metal sub-structure units is 90°, so that the ultra-wideband antenna radiates left-handed circularly polarized waves or right-handed circularly polarized waves. circularly polarized waves.
  • the ultra-wideband antenna that radiates right-hand circularly polarized waves is a GNSS antenna
  • the ultra-wideband antenna that radiates left-handed circularly polarized waves is an SDARS antenna.
  • the feed network includes two 5-port microwave networks, and the output/input port of each of the 5-port microwave networks is connected to the UWB.
  • the absolute values of the differences of the transmission phases of the four input/output ports connected to the antenna are 0°, 80° ⁇ 100°, 170° ⁇ 190°, and 260° ⁇ 280°, respectively.
  • the microwave network is a 4-phase coupler or a functional network composed of inductive and capacitive components.
  • the microwave network is a functional network formed by a microstrip line or a stripline design.
  • the feed network includes a synthesis or power division function network.
  • the synthesis or power division functional network consists of microstrip lines or strip lines with matching branches.
  • the shape of the first metal structure is a shape with a curvature and/or a bend
  • the shape of the second metal structure is a shape with a curvature and/or a bend
  • the width of one end of the first metal structural member close to the circumferential center position gradually decreases along the radial direction of the first metal structural member in the direction of the center position.
  • the four first metal structural members form a propeller-like structure that rotates clockwise or counterclockwise.
  • one end of the first metal structural member close to the circumferential center position is provided in a trapezoidal shape.
  • the second metal structure is cylindrical.
  • the ultra-wideband antenna further includes a third metal structure member, and the third metal structure member is disposed on the reference ground metal plate and is electrically connected to it, and plays the role of impedance matching.
  • the third metal structural member is respectively disposed on the peripheral side and/or the center of the peripheral direction of the four sub-metal structural units.
  • the number of the third metal structural members disposed on the peripheral side of each of the sub-metal structural units is one or two.
  • the shape of the third metal structure is a cube.
  • the ultra-wideband antenna further includes a metal wall, the four sub-metal structural units are located in a metal cavity structure formed by the metal wall and the reference ground metal plate, and the metal wall is connected to the metal wall.
  • a parasitic unit is provided on one side of the second metal structural member to which the feed structure is added, and the parasitic unit is directly connected to the reference ground metal plate and Extending along the vertical direction and in an inverted L shape, the parasitic unit is coupled with the second metal structure to excite a new resonance frequency.
  • the present invention also provides an ultra-wideband antenna array, wherein the ultra-wideband antenna array includes any one of the above-mentioned ultra-wideband antennas, and the ultra-wideband antennas are arranged in an array.
  • the ultra-wideband antenna array is a one-dimensional antenna array, wherein the absolute value of the included angle between the central axis of the sub-antenna of each of the ultra-wideband antennas and the arrangement direction of the one-dimensional antenna array is 45. °.
  • the present invention of the present invention provides an ultra-wideband antenna and an antenna array.
  • 4 sub-metal structural units arranged at equal intervals of 90° along the circumferential direction are arranged, and by aligning the two oppositely arranged sub-metal structural units
  • the metal structure unit applies a differential feed with a phase difference of 180°, and at the same time, the four sub-metal structure units have a coupling effect, which changes the electric field distribution at the circumferential center position of each group of sub-antennas, and excites a new low-frequency resonance mode , forming an ultra-wideband antenna, and when one group of sub-antennas is excited, the other group of sub-antennas acts as a parasitic unit structure through coupling, which has the effect of widening the low-frequency bandwidth.
  • the current is parallel to the excitation current, which increases the overall radiation effective area of the UWB antenna and increases the radiation gain without affecting the isolation of the two sub-antennas.
  • the electrical connection between the plurality of second metal structures and the reference ground metal plate not only reduces the resonance size of the ultra-wideband antenna, but also compensates for the capacitive effect of the plurality of first metal structures due to its inductive effect, thereby increasing the The effect of antenna bandwidth.
  • FIG. 1 is a schematic structural diagram of an ultra-wideband antenna of the present invention, wherein the first metal structure has a trapezoidal portion.
  • FIG. 2 is a schematic structural diagram of the ultra-wideband antenna of the present invention, wherein the second metal structure has a bent portion.
  • FIG. 3 is a schematic structural diagram of the ultra-wideband antenna of the present invention, wherein, in each sub-metal structural unit, a parasitic unit is provided on one side of the second metal structural member to which the feeding structure is added.
  • Fig. 4 is a schematic diagram of a partial structure of the ultra-wideband antenna according to the first embodiment of the present invention, and the figure shows a sub-metal structural unit.
  • FIG. 5 is a schematic structural diagram of the UWB antenna according to the first embodiment of the present invention, wherein four first metal structural members, such as the dotted frame A in the figure, form a propeller-like structure.
  • FIG. 6 shows simulated return loss diagrams of the GNSS antenna and the SDARS antenna in the ultra-wideband antenna according to the first embodiment of the present invention.
  • FIG. 7 shows a simulated total efficiency diagram of the GNSS antenna and the SDARS antenna in the ultra-wideband antenna according to the first embodiment of the present invention.
  • FIG. 8 shows a simulated gain and direction diagram of the center frequency of the L2 frequency band of the GNSS antenna in the ultra-wideband antenna according to the first embodiment of the present invention at the x-z plane.
  • FIG. 9 shows the simulated gain and direction diagram of the center frequency of the L1 frequency band of the GNSS antenna in the ultra-wideband antenna according to the first embodiment of the present invention at the x-z plane.
  • FIG. 10 shows the simulated gain and direction diagram of the frequency band center frequency of the SDARS antenna in the ultra-wideband antenna according to the first embodiment of the present invention at the x-z plane.
  • FIG. 11 shows a simulated axial ratio performance diagram of the GNSS antenna and the SDARS antenna in the ultra-wideband antenna according to the first embodiment of the present invention.
  • FIG. 12 is a schematic diagram of a feeding network of an ultra-wideband antenna according to Embodiment 1 of the present invention.
  • FIG. 13 is a schematic diagram showing the actual structure of the feeding network of the ultra-wideband antenna according to the first embodiment of the present invention.
  • FIG. 14 shows a simulation loss diagram of the transmission line of the feeder network in the GNSS antenna frequency band and the SDARS antenna frequency band in the ultra-wideband antenna according to the first embodiment of the present invention.
  • FIG. 15 shows a simulated transmission phase characteristic diagram of the transmission line of the feeder network in the SDARS antenna frequency band in the ultra-wideband antenna according to the first embodiment of the present invention.
  • FIG. 16 shows a simulated transmission phase characteristic diagram of the transmission line of the feeder network in the frequency band of the GNSS antenna in the ultra-wideband antenna according to the first embodiment of the present invention.
  • FIG. 17 shows a system simulation return loss diagram of the GNSS antenna and the SDARS antenna in the ultra-wideband antenna according to the first embodiment of the present invention combined with the corresponding feed network.
  • FIG. 18 is a diagram showing the total efficiency of the system simulation after the GNSS antenna and the SDARS antenna in the ultra-wideband antenna according to the first embodiment of the present invention are combined with the corresponding feed network.
  • FIG. 19 shows the simulated gain and direction diagram of the L2 frequency band center frequency of the GNSS antenna in the x-z plane in the system after the GNSS antenna and the SDARS antenna in the ultra-wideband antenna according to the first embodiment of the present invention are combined with the corresponding feed network.
  • Figure 20 shows the simulation gain and the directional diagram of the L1 frequency band center frequency of the GNSS antenna at the x-z plane in the system after the GNSS antenna and the SDARS antenna in the ultra-wideband antenna according to the first embodiment of the present invention are combined with the corresponding feed network.
  • 21 shows the simulated gain and direction diagram of the frequency band center frequency of the SDARS antenna in the x-z plane in the system after the GNSS antenna and the SDARS antenna in the ultra-wideband antenna according to the first embodiment of the present invention are combined with the corresponding feed network.
  • FIG. 22 shows a system simulation axial ratio performance diagram of the GNSS antenna and the SDARS antenna in the ultra-wideband antenna according to the first embodiment of the present invention combined with the corresponding feeding network.
  • FIG. 23 is a schematic diagram of a partial structure of the ultra-wideband antenna according to the second embodiment of the present invention, and the figure shows a sub-metal structural unit.
  • FIG. 24 is a schematic structural diagram of the ultra-wideband antenna according to the second embodiment of the present invention, wherein two sub-metal structural units arranged opposite to each other form a group of sub-antennas.
  • FIG. 25 shows a simulated return loss diagram of the ultra-wideband antenna in its frequency band according to the second embodiment of the present invention.
  • FIG. 26 shows a simulated total efficiency diagram of the ultra-wideband antenna in its frequency band according to the second embodiment of the present invention.
  • FIG. 27 shows a simulation gain performance diagram of the ultra-wideband antenna in its frequency band according to the second embodiment of the present invention.
  • FIG. 28 is a schematic structural diagram of an ultra-wideband antenna array according to Embodiment 2 of the present invention.
  • FIG. 29 is a schematic diagram showing the structure of the ultra-wideband antenna array simulated in the simulated metal structure of the mobile phone according to the second embodiment of the present invention.
  • FIG. 30 is a graph showing the isolation between the UWB antennas in the UWB antenna array of FIG. 29 .
  • Fig. 31 shows the total efficiency of the UWB antenna array in Fig. 29 when the frequency is 28G and the array scanning angle of the UWB antenna array is in the range of 0° to 60°.
  • Fig. 32 shows the total efficiency of the UWB antenna array in Fig. 29 when the frequency is 39G and the array scanning angle of the UWB antenna array is in the range of 0° to 60°.
  • Figure 33 shows the gain performance graph of the UWB antenna array when the array is scanned when the frequency is 28G in Figure 29 .
  • Fig. 34 shows the gain performance graph of the UWB antenna array when the array is scanned when the frequency is 39G in Fig. 29 .
  • the present invention provides an ultra-wideband antenna
  • the ultra-wideband antenna includes: a reference ground metal plate 10 , four identical sub-metal structural units 11 and four feed structures 12 ;
  • Each of the sub-metal structural units 11 includes: a first metal structural member 111 extending in a horizontal direction, two second metal structural members 112 extending in a vertical direction and arranged at intervals, and two of the second metal structural members 112 .
  • One end of the structural member 112 is directly connected to the first metal structural member 111
  • the other end of one of the second metal structural members 112 is connected to the reference ground metal plate 10
  • One of the feeding structures 12 is added between the other end of the reference ground metal plate 10 and the reference ground metal plate 10;
  • the electrical structure 12 applies differential feeds that are 180° out of phase.
  • sub-metal structural units 11 arranged at equal intervals of 90° in the circumferential direction are provided, and by applying differential feeding with a phase difference of 180° to the two oppositely arranged sub-metal structural units 11, at the same time, the four There is a coupling effect between the sub-metal structural units 11, which changes the electric field distribution at the circumferential center position of each group of sub-antennas 13, excites a new low-frequency resonance mode, and forms an ultra-wideband antenna, and when a group of sub-antennas 13 is excited When , another group of sub-antennas 13 acts as a parasitic unit structure through coupling, which has the effect of widening the low frequency bandwidth.
  • the two groups of sub-antennas are not affected.
  • the overall radiation effective area of the ultra-wideband antenna is increased, and the radiation gain is increased.
  • the electrical connection between the plurality of second metal structures 112 and the reference ground metal plate 10 not only reduces the resonance size of the ultra-wideband antenna, but also compensates for the capacitive effect of the plurality of first metal structures 111 due to its inductive effect. Play the role of increasing the antenna bandwidth.
  • the first metal structure 111 extends in the horizontal direction, which means that the overall trend of the first metal structure 111 is toward the horizontal direction, so the present invention does not limit the first metal structure
  • the shape of the member 111 can be as long as its overall trend is along the horizontal direction.
  • the first metal structural member 111 may be a completely horizontal shape (as shown in 1), or may have an arc along the vertical direction. , and may have this curvature in part, such as the trapezoid portion 114 in FIG. 2 or the entire first metal structure 111 with this curvature, or the first metal structure 111 may be provided with bends in the vertical direction.
  • the second metal structural member 112 extends in the vertical direction, which means that the overall trend of the second metal structural member 112 is towards the vertical direction, and the present invention does not limit the size of the second metal structural member 112 shape, as long as the overall trend is along the vertical direction, for example, the second metal structure 112 may be a completely vertical shape (as shown in FIG. 1 ), or may have an arc along the horizontal direction , and may be part of the radian or the entire first metal structure 111 has the radian, or the second metal structure 112 is provided with a bend in the horizontal direction, such as the bending portion 113 in FIG. 2 .
  • the spacing between the two sub-metal structural units 11 of the two groups of the sub-antennas 13 can be adjusted according to actual needs, and can be set to be the same (as shown in FIG. 1 ) or different according to needs.
  • the width of one end of the first metal structural member 111 close to the circumferential center position along the radial direction of the first metal structural member 111 toward the central position gradually decreases
  • one end of the first metal structural member 111 close to the circumferential center position is set in a trapezoid shape, such as the trapezoid portion 114 in FIG. 1 to FIG. 3 , as shown in FIG.
  • the vertical direction has an arc. Setting the end of the first metal structural member 111 close to the circumferential center position to gradually reduce the width can effectively shorten the distance between the four sub-metal structural units 11 , thereby improving the coupling effect between the four sub-metal structural units 11 .
  • the end of the first metal structural member 111 close to the circumferential center position can also be set to another shape, so as to shorten the distance between the four sub-metal structural units 11 .
  • the four first metal structural members 111 form a propeller-like structure that rotates clockwise or counterclockwise.
  • the shape of the second metal structure 112 is not limited, for example, it may be a flat sheet-like structure or a column-like structure. As shown in FIG. 5 , preferably, the second metal structural member 112 has a cylindrical structure, so as to facilitate process production.
  • the absolute value of the feed phase difference between the two feed structures 12 of the two adjacent sub-metal structure units 11 can be set to be 90°, that is, the two groups of the sub
  • the absolute value of the feed phase difference between the adjacent two sub-metal structural units 11 in the antenna 13 is set to 90°, so that the ultra-wideband antenna radiates left-handed circularly polarized waves or right-handed circularly polarized waves, which is a left-handed circularly polarized wave.
  • the integration of polarized antenna and right-hand circularly polarized antenna is possible. Based on this structure, as shown in FIG. 12 and FIG.
  • a feeder network 14 can be designed, and the feeder network 14 includes two 5-port 142 microwave networks 141 , each of which has an output/input port of the microwave network 141 .
  • the absolute values of the differences of the transmission phases of the four input/output ports connected to the UWB antenna are respectively 0°, 80° ⁇ 100°, 170° ⁇ 190°, and 260° ⁇ 280°.
  • the feed network also includes a synthesis or power division function network 144 to realize signal synthesis or power division.
  • the synthesis or power division function network 144 consists of a microstrip line or strip with a matching branch 143. form line.
  • the microwave network 141 may be any existing functional network that can synthesize linearly polarized signals into circularly polarized signals or divide circularly polarized signals into linearly polarized signals.
  • the microwave network 141 may be a 4-phase coupler or a functional network composed of inductive and capacitive components, or a functional network composed of a microstrip line or a stripline design, which is not limited herein.
  • the UWB antenna further includes a third metal structural member 15 , and the third metal structural member 15 is disposed on the reference ground metal plate 10 and is electrically connected to it for impedance matching. effect.
  • the parameters such as the shape and the setting position of the third metal structural member 15 are not limited here, and are specifically designed according to the actual situation according to the effect of impedance matching that needs to be achieved.
  • the third metal structural member 15 can be respectively disposed on the circumferential side and/or the circumferential center position of the four sub-metal structural units 11 , that is, the third metal structural member 15 can be arranged only on the peripheral sides of the four sub-metal structural units 11 respectively, or only in the center of the circumferential direction, or can be arranged on the peripheral sides and the four sub-metal structural units 11 at the same time. the circumferential center position. It should be noted here that the shape of the third metal structural member 15 disposed at the center position and the shape of the third metal structural member 15 disposed on the peripheral side of the sub-metal structural unit 11 are determined according to specific impedance matching requirements.
  • the arrangement can be the same or different; preferably, the number of the third metal structural members 15 arranged on the peripheral side of each sub-metal structural unit 11 can be 1 or 2;
  • the positional relationship between the third metal structural member 15 on the peripheral side of the sub-metal structural unit 11 and its corresponding sub-metal structural unit 11 is the same, that is, each of the sub-metal structural units 11 and the first metal structural unit on the peripheral side thereof are the same.
  • the positional relationship among the three metal structural members 15 is the same; further, when the number of the third metal structural members 15 disposed on the peripheral side of each sub-metal structural unit 11 is one, then there are four of the sub-metallic structural members 15 .
  • the four third metal structural members 15 on the peripheral side of the structural unit 11 are third metal structural members 15 of the same structure and have the same positional relationship with the corresponding third metal structural members 15 .
  • the structures of the two third metal structural members 15 may be the same or different, but four of the sub-metallic
  • the two third metal structural members 15 on the peripheral side of the structural unit 11 are two third metal structural members 15 of the same structure and have the same positional relationship with the corresponding third metal structural members 15 . As shown in FIG. 23 and FIG.
  • the UWB antenna may further include a metal wall 16 , and the four sub-metal structural units 11 are located in a structure formed by the metal wall 16 and the reference ground metal plate 10 .
  • the metal wall 16 is electrically or non-electrically connected to the reference ground metal plate 10 .
  • a parasitic unit 115 is provided on the side of the second metal structural member 112 to which the feeding structure 12 is added, and the parasitic unit 115 It is directly connected to the reference ground metal plate 10 and extends in the vertical direction, and has an inverted L shape, that is, the parasitic unit 115 includes a vertical part in the vertical direction and a horizontal part in the horizontal direction.
  • the second metal structure 112 (here the second metal structure 112 refers to the second metal structure 112 added to the feed structure 12 ) couples to excite a new resonant frequency, so as to widen the bandwidth of the ultra-wideband antenna .
  • an ultra-wideband antenna array can also be formed, so that the ultra-wideband antennas are arranged in an array.
  • This embodiment can realize the ultra-wideband antenna with GNSS L1, L2 and SDARS functions.
  • the GNSS L1 (1.56G-1.605G) frequency band, L2 (1.2G-1.26G) frequency band can be realized at the same time.
  • the integration degree and space utilization rate of the system are improved; at the same time, different from the traditional design method of using high-cost and high-dielectric-constant ceramics as the dielectric material for the traditional patch antenna, this embodiment adopts the same antenna size under the condition of keeping the same size.
  • the low-cost, low-dielectric constant of 4 plastic material also meets the requirements of the low-frequency 1.2G frequency band, and indirectly realizes the miniaturization function.
  • the size of the reference ground metal plate 10 is 7cm*7cm.
  • the ultra-wideband antenna further includes a medium 18, the medium 18 covers the four sub-metal structural units 11, and the material of the medium 18 is a plastic material with a dielectric constant of 4, or other materials with a low dielectric constant. , there is no limit here, the size is 6.2cm*6.2cm*1.1cm.
  • each sub-metal structural unit 11 rotates around the circumferential direction every time. 90° all overlap with the other three sub-metal structural units 11 .
  • One of the second metal structural members 112 is a copper cylinder with a diameter of 5 mm and a height of 1.1 cm, and is directly connected to the first metal structural member 111 through the medium 18 made of plastic, and the lower end is connected to the reference ground metal plate 10;
  • the second metal structural member 112 is a vertical sheet-like structure, and is directly electrically connected to the first metal structural member 111 .
  • the feeding point of the feeding structure 12 is applied to the connection between the other second metal structural member 112 and the reference ground metal plate 10 . between.
  • Differential feeds with a difference of 180° are applied to the feed points of the feed structures 12 of the two sub-metal structural units 11 arranged oppositely.
  • the phases of the four feeding structures 12 differ by 90° in the clockwise direction, that is, the phases in the clockwise direction are 0°, 90°, 180°, and 270°
  • the UWB antenna receives right-handed circular polarization. (RHCP) waves, used for GNSS communications.
  • RVCP right-handed circular polarization.
  • LHCP left-handed circular polarization
  • each third metal structure 15 is electrically connected to the reference ground metal plate 10, which plays the role of adjusting impedance matching.
  • the shape of the third metal structural member 15 is designed as a cube.
  • the simulated S-parameters and simulated total efficiency diagrams of the UWB antenna are shown.
  • the efficiency of the GNSS L1 band is in the range of -1.8 to -2dB;
  • the efficiency of the GNSS L2 band is in the range of -0.7 to -0.9dB;
  • the efficiency of the SDARS band is in the range of -1.6 to 1.95dB.
  • the simulated gain and direction diagrams of the GNSS antenna and the SDARS antenna on the x-z plane (for the coordinate system, please refer to the three-dimensional rectangular coordinate system in Figure 5).
  • the maximum gain of the right-hand circularly polarized wave in the zenith azimuth is 3.29dBi; at the center frequency of the GNSS L1 frequency band at 1.575G, the maximum gain of the right-hand circularly polarized wave in the zenith azimuth is 3.79dBi;
  • the center frequency of the SDARS band is 2.332G, and the maximum gain of the left-handed circularly polarized wave in the zenith azimuth is 6.58dBi.
  • the gain performance meets the requirements for practical use.
  • the axial ratio of the GNSS RHCP wave and the SDARS LHCP has a good performance, which is close to 0dB in the simulation, and from -50° to 50°, the axial ratio The values are all below 2dB.
  • the second metal structural member 112 of each sub-metal structural unit 11 is connected to the bottom of the reference ground metal plate 10 through the metal structure.
  • the feeding network 14 is electrically connected.
  • the feed network structure and the connection with the sub-metal structural unit, that is, the feed network is isolated from the sub-metal structural unit by the reference ground metal plate, is conducive to the isolation of the antenna and the feed network 14 and reduces mutual interference.
  • the feeding network 14 is divided into two paths through the duplexer structure (ie, the power division function network 144 ), and the first transmission line path is 145-1 , 145-2, 145-3, 145-4, the second transmission line path is 146-1, 146-2, 146-3, 146-4, the first transmission line path merges with the microwave network 141 in the lower right corner, this implementation
  • the microwave network 141 is selected as a four-phase coupler, which is used to receive the left-handed polarized signal of the SDARS frequency band; the second transmission line path converges on the microwave network 141 in the upper left corner.
  • the microwave network 141 is selected as a four-phase coupler, with to receive right-handed polarized signals in the GNSS band.
  • Four-phase couplers use existing microwave devices on the market.
  • each branch of the feeding network has a high consistency, thus ensuring the axial ratio characteristic of the circularly polarized antenna.
  • Figures 17 to 22 show the overall system simulation effects of the ultra-wideband antenna and the feed network in combination with this embodiment.
  • the return loss of the GNSS antenna and SDARS antenna frequency band is below -15dB, and the total efficiency is basically above -3dB
  • Figure 19 and Figure 20 are the pattern and gain performance of the GNSS antenna RHCP
  • Figure 21 The pattern and gain performance of the SDARS antenna LHCP, the gain performance is above 2dBi, which basically meets the actual needs
  • Figure 22 shows the axial ratio performance of the GNSS antenna RHCP and the SDARS antenna LHCP, between -50° and 50°, the AR axis The ratio is below 5dB, showing good axial ratio performance.
  • the ultra-wideband antenna of this embodiment is used for the ultra-wideband millimeter-wave antenna of the all-metal frame terminal user equipment.
  • the antenna array formed by the ultra-wideband antenna of this embodiment as a unit realizes the design of a 5G millimeter-wave array antenna in a metal frame environment, and reaches 26G ⁇ 29.5G, 37G ⁇ 42.5G ultra-wide frequency band requirements for dual polarization.
  • the antenna further includes a metal wall 16 and a medium 18.
  • the four sub-metal structural units 11 are located in a metal cavity structure 17 formed by a reference ground metal plate 10 and a metal wall 16.
  • the metal wall 16 is electrically or non-electrically connected to the reference ground metal plate 10.
  • the material of the medium 18 is PTFE with a low dielectric constant of 2 and a tangent loss of 0.003.
  • the size of the medium 18 is 4.5mm*4.5mm*1.1 mm, filling the metal cavity structure 17 .
  • each sub-metal structural unit 11 is rotated by 90° around the circumferential direction to overlap with the other three sub-metal structural units 11 .
  • One of the second metal structural members 112 is a metal column with a diameter of 0.2 mm and a height of 1.1 mm, which is directly connected to the first metal structural member 111 through the medium 18, and the lower end is connected to the reference ground metal plate 10;
  • the metal structure 112 is a vertical sheet-like structure and is directly electrically connected to the first metal structure 111 .
  • the feeding point of the feeding structure 12 is applied between another second metal structure 112 and the reference ground metal plate 10 .
  • the feed points of the feeding structure 12 of the two sub-metal structural units 11 arranged opposite to each other are applied with differential feeding with a difference of 180°, and constitute the sub-antenna 13 (as shown in FIG. 24 ).
  • the four sub-metal structural units 11 form two groups of sub-antennas.
  • the antenna 13 and the two groups of sub-antennas 13 are in an orthogonal relationship in space, and are used to realize the radiation of dual polarized waves.
  • Phi is the angle between the geometric center axis of the two sub-antennas 13 and the x-axis direction in FIG. 24 .
  • the simulated S-parameters and simulated total efficiency diagrams of the ultra-wideband millimeter-wave antenna of this embodiment are shown.
  • the efficiency is above -2dB in the 26G-29.5G frequency band and the 37G-42.5G frequency band.
  • FIG. 27 the gain performance diagram of the ultra-wideband millimeter-wave antenna of this embodiment is shown.
  • the 37G ⁇ 42.5G frequency band reaches above 6dBi, which has a good gain performance.
  • the above-mentioned ultra-wideband antenna 21 is used as a unit to form a 1*4 one-dimensional ultra-wideband antenna array 20 , wherein the middle of the sub-antenna 13 of each of the ultra-wideband antennas 21
  • the absolute value of the included angle between the axis and the arrangement direction of the one-dimensional antenna array is 45°, as well as its simulation performance in the simulated metal structure 19 of the mobile phone.
  • the mobile phone simulated metal structure 19 of 140mm*70mm*5.4mm is used to simulate the size of the mobile phone
  • the one-dimensional ultra-wideband antenna array 20 is embedded in the frame of the mobile phone simulated metal structure 19
  • the array scanning angle of the 1*4 one-dimensional ultra-wideband antenna array 20 is in the range of 0° to 60°, and the overall efficiency diagram of the one-dimensional ultra-wideband antenna array 20 is horizontal in the figure.
  • the coordinate axis angle is the angle between the z-y plane and the z-axis in Fig. 29, that is, the angle between the antenna and the front direction of the antenna array during angular scanning.
  • the scanning angle of the array is in the range of 0° to 60°
  • the total efficiency of the antenna array is basically above 50%.
  • the scanning angle of the array is in the range of 0° to 60°, and the total efficiency of the antenna array is basically above 60%.
  • Fig. 33 and Fig. 34 it is the gain performance diagram of the 1*4 one-dimensional ultra-wideband antenna array 20 during angle scanning.
  • the array scanning angle is in the range of 0° ⁇ 45°
  • the peak value difference of the gain value remains within 1.5dBi, which is basically stable.
  • Figure 34 for 39G, although the peak value of the gain value fluctuates greatly (due to the side lobe effect), the peak value is above 10dBi, which has a good gain performance.
  • the present invention provides an ultra-wideband antenna and an antenna array.
  • four sub-metal structural units arranged at equal intervals of 90° in the circumferential direction are arranged, and two metal sub-structure units arranged opposite to each other are arranged by The unit applies a differential feed with a phase difference of 180°, and at the same time, there is a coupling effect between the four sub-metal structural units, which changes the electric field distribution at the circumferential center position of each group of sub-antennas, and excites a new low-frequency resonance mode.
  • Ultra-wideband antenna and when one group of sub-antennas is excited, the other group of sub-antennas acts as a parasitic unit structure through coupling, which has the effect of broadening the low-frequency bandwidth.
  • the excitation current is parallel, which increases the overall radiation effective area of the ultra-wideband antenna and increases the radiation gain without affecting the isolation of the two sub-antennas.
  • the electrical connection between the plurality of second metal structures and the reference ground metal plate not only reduces the resonant size of the ultra-wideband antenna, but also compensates for the capacitive effect of the plurality of first metal structures due to its inductive effect, thereby increasing the The effect of antenna bandwidth. Therefore, the present invention effectively overcomes various shortcomings in the prior art and has high industrial utilization value.

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Abstract

本发明提供一种超宽带天线及天线阵列，包括：参考地金属板、设置于其上的4个相同子金属结构单元且沿周向等间隔90°设置及4个馈电结构；子金属结构单元包括：1个沿水平方向延伸的第一金属结构件、2个沿竖直方向延伸的第二金属结构件，2个第二金属结构件与第一金属结构件直接连接，1个第二金属结构件与参考地金属板连接，另一个第二金属结构件与参考地金属板之间加入一馈电结构。设置4个沿周向等间隔90°设置的子金属结构单元以及多个接地点的加入，并通过对相对设置的两子金属结构单元施加相位差为180°的差分馈电，同时使4个子金属结构单元之间具有耦合作用，形成超宽带天线；另外，还使辐射增益、天线带宽增加，同时达到小型化效果。

Description

超宽带天线及天线阵列 技术领域
本发明涉及超宽带天线结构的设计领域，特别是涉及一种超宽带天线及天线阵列。
背景技术
随着通信频段的不断扩充以及系统内各种功能模块集成度的提高，对小型化宽带天线的需求越来越高，同时设计也变得越来越有挑战性。
例如在卫星通信与导航领域，同为通过圆极化波通信的GNSS系统与SDARS系统常被放在一起讨论。GNSS系统主要有有名的导航系统有美国的GPS，欧洲的Galileo，俄罗斯的GLONASS以及中国的北斗系统等，其频段集中在1.1G-1.6G，所使用的圆极化波为右旋圆极化波(RHCP)。SDARS系统是卫星数字音频广播业务的简称，其频段为2.32G-2.345G，所使用的圆极化波为左旋圆极化波(LHCP)。当把两者集成在一个天线设计时，由于两者频段相隔较远，同时包含GNSS与SDARS频段的圆极化天线设计是目前一个难题，或者只能取GNSS中的部分频段(如1.56G-1.6G)与SDARS频段。目前为了覆盖GNSS与SDARS的频段，主要采用两者分开，各自独立设计的思路，这就增加了天线系统设计的空间尺寸。同时目前的GNSS与SDARS天线多使用高成本的陶瓷材料为主的贴片天线，在同等尺寸条件下，使用低成本的低介电常数材料也成为一种需求。
例如在5G(第5代移动通信技术)的应用中，毫米波波段的引入是一大亮点。目前毫米波的波段主要集中在24.5G-29.5G(如n257，n258和n261)以及37.5G-42.5G(如n260)。同时为了达到覆盖率以及增益的要求，毫米波天线多采用阵列设计以及空间正交的双极化波模式。在终端设备的开发中，如何设计同时包含如上波段与模式的超宽带双极化天线成为一个难题。
发明内容
鉴于以上所述现有技术的缺点，本发明的目的在于提供一种超宽带天线及天线阵列，用于解决现有技术中在卫星通信与导航领域和/或移动通信领域内超宽带天线小型化受限等的问题。
为实现上述目的及其他相关目的，本发明提供一种超宽带天线，所述超宽带天线包括：参考地金属板、4个相同的子金属结构单元及4个馈电结构；
4个相同的所述子金属结构单元设置于所述参考地金属板上，且4个相同的所述子金属 结构单元沿周向等间隔90°设置；
每个所述子金属结构单元包括：1个沿水平方向延伸的第一金属结构件、2个沿竖直方向延伸且间隔设置的第二金属结构件，2个所述第二金属结构件的一端与所述第一金属结构件直接连接，1个所述第二金属结构件的另一端与所述参考地金属板连接，另一个所述第二金属结构件的另一端与所述参考地金属板之间加入一个所述馈电结构；
每个所述子金属结构单元与其余3个所述子金属结构单元之间具有耦合作用；
相对设置的2个所述子金属结构单元组成一组子天线，4个所述子金属结构单元组成2组所述子天线，每组所述子天线的2个所述馈电结构施加相位差为180°的差分馈电。
可选地，相邻2个所述子金属结构单元的2个所述馈电结构之间馈电相位差的绝对值为90°，使所述超宽带天线辐射左旋圆极化波或右旋圆极化波。
可选地，辐射右旋圆极化波的所述超宽带天线为GNSS天线，辐射左旋圆极化波的所述超宽带天线为SDARS天线。
可选地，4个所述馈电结构连接于一个馈电网络，所述馈电网络中包含2个5端口微波网络，每个所述5端口微波网络的输出/输入端口与所述超宽带天线连接的4个输入/输出端口的传输相位的差值的绝对值分别为0°、80°～100°、170°～190°及260°～280°。
可选地，所述微波网络为4相耦合器或由电感及电容元器件设计构成的功能网络。
可选地，所述微波网络为由微带线或带状线设计构成的功能网络。
可选地，所述馈电网络中包含合成或功分功能网络。
可选地，所述合成或功分功能网络由带有匹配枝节的微带线或带状线构成。
可选地，所述第一金属结构件的形状为具有弧度和/或弯折的形状，所述第二金属结构件的形状为具有弧度和/或弯折的形状。
可选地，所述第一金属结构件靠近所述周向中心位置的一端沿所述第一金属结构件的径向指向所述中心位置方向的宽度逐渐减小。
可选地，4个所述第一金属结构件构成沿顺时针方向旋转或逆时针方向旋转的类螺旋桨状结构。
可选地，所述第一金属结构件靠近周向中心位置的一端设置为梯形形状。
可选地，所述第二金属结构件为圆柱状。
可选地，所述超宽带天线还包括第三金属结构件，所述第三金属结构件设置于所述参考地金属板上并与其电连接，起到阻抗匹配的作用。
可选地，所述第三金属结构件分别设置于4个所述子金属结构单元的周侧和/或所述周向 的中心位置。
可选地，设置于每个所述子金属结构单元周侧的所述第三金属结构件的数量为1个或2个。
可选地，所述第三金属结构件的形状为立方体。
可选地，所述超宽带天线还包括金属壁，4个所述子金属结构单元位于由所述金属壁及所述参考地金属板构成的金属腔体结构内，所述金属壁与所述参考地金属板之间电连接或非电连接。
可选地，每个所述子金属结构单元中，加入所述馈电结构的所述第二金属结构件的一侧设置有寄生单元，所述寄生单元与所述参考地金属板直接连接且沿竖直方向延伸，呈倒L形，该寄生单元与该第二金属结构件耦合激发出新的谐振频率。
本发明还提供一种超宽带天线阵列，所述超宽带天线阵列包括如上所述的任意一项的超宽带天线，且所述超宽带天线呈阵列排布。
可选地，所述超宽带天线阵列为一维天线阵列，其中，每个所述超宽带天线的所述子天线的中轴线与该一维天线阵列的排列方向的夹角的绝对值为45°。
如上所述，本发明的本发明提供一种超宽带天线及天线阵列，本发明提出的结构，设置4个沿周向等间隔90°设置的子金属结构单元，并通过对相对设置的2个子金属结构单元施加相位差为180°的差分馈电，同时使4个子金属结构单元之间具有耦合作用，改变了每组子天线的周向中心位置处的电场分布，激发了新的低频谐振模式，形成超宽带天线，且当一组子天线被激励时，另一组子天线通过耦合作用，作为寄生单元结构，起到了拓宽低频带宽的效果，同时由于寄生单元结构上电流的流动，且寄生电流与激励电流平行，在不影响两组子天线隔离度的情况下，增加了超宽带天线整体的辐射有效面积，使辐射增益增大。另外，通过多个第二金属结构件与参考地金属板的电连接，既缩小了超宽带天线的谐振尺寸，又因其电感效应补偿了多个第一金属结构件的电容效应，起到增加天线带宽的作用。
附图说明
图1显示为本发明的超宽带天线的结构示意图，其中，第一金属结构件具有梯形部。
图2显示为本发明的超宽带天线的结构示意图，其中，第二金属结构件具有弯折部。
图3显示为本发明的超宽带天线的结构示意图，其中，每个子金属结构单元中，加入馈电结构的第二金属结构件的一侧设置有寄生单元。
图4显示为本发明的实施例一的超宽带天线的局部结构示意图，图中示出了一个子金属 结构单元。
图5显示为本发明的实施例一的超宽带天线的结构示意图，其中，4个第一金属结构件，如图中虚线框A，构成类螺旋桨状结构。
图6显示为本发明的实施例一的超宽带天线中的GNSS天线及SDARS天线的仿真回波损耗图。
图7显示为本发明的实施例一的超宽带天线中的GNSS天线及SDARS天线的仿真总效率图。
图8显示为本发明的实施例一的超宽带天线中的GNSS天线的L2频段中心频率处在x-z平面的仿真增益与方向图。
图9显示为本发明的实施例一的超宽带天线中的GNSS天线的L1频段中心频率处在x-z平面的仿真增益与方向图。
图10显示为本发明的实施例一的超宽带天线中的SDARS天线的频段中心频率处在x-z平面的仿真增益与方向图。
图11显示为本发明的实施例一的超宽带天线中的GNSS天线及SDARS天线的仿真轴比性能图。
图12显示为本发明的实施例一的超宽带天线的馈电网络示意图。
图13显示为本发明的实施例一的超宽带天线的馈电网络实际结构示意图。
图14显示为在本发明的实施例一的超宽带天线中的GNSS天线频段及SDARS天线频段，馈电网络传输线的仿真损耗图。
图15显示为在本发明的实施例一的超宽带天线中的SDARS天线频段，馈电网络传输线的仿真传输相位特性图。
图16显示为在本发明的实施例一的超宽带天线中的GNSS天线频段，馈电网络传输线的仿真传输相位特性图。
图17显示为本发明的实施例一的超宽带天线中的GNSS天线及SDARS天线结合相应的馈电网络后的系统仿真回波损耗图。
图18显示为本发明的实施例一的超宽带天线中的GNSS天线及SDARS天线结合相应的馈电网络后的系统仿真的总效率图。
图19显示为本发明的实施例一的超宽带天线中的GNSS天线及SDARS天线结合相应的馈电网络后的系统中GNSS天线的L2频段中心频率处在x-z平面的仿真增益与方向图。
图20显示为本发明的实施例一的超宽带天线中的GNSS天线及SDARS天线结合相应的 馈电网络后的系统中GNSS天线的L1频段中心频率处在x-z平面的仿真增益与方向图。
图21显示为本发明的实施例一的超宽带天线中的GNSS天线及SDARS天线结合相应的馈电网络后的系统中SDARS天线的频段中心频率处在x-z平面的仿真增益与方向图。
图22显示为本发明的实施例一的超宽带天线中的GNSS天线及SDARS天线结合相应的馈电网络后的系统仿真轴比性能图。
图23显示为本发明的实施例二的超宽带天线的局部结构示意图，图中示出了一个子金属结构单元。
图24显示为本发明的实施例二的超宽带天线的结构示意图，其中，相对设置的2个子金属结构单元组成一组子天线。
图25显示为本发明的实施例二的超宽带天线在其频段内的仿真回波损耗图。
图26显示为本发明的实施例二的超宽带天线在其频段内的仿真总效率图。
图27显示为本发明的实施例二的超宽带天线在其频段内的仿真增益性能图。
图28显示为本发明的实施例二的超宽带天线阵列的结构示意图。
图29显示为本发明的实施例二的超宽带天线阵列模拟于手机模拟金属结构中的结构示意图。
图30显示为图29中超宽带天线阵列中各超宽带天线之间的隔离度图。
图31显示为图29中，频率为28G时，超宽带天线阵列的阵列扫描角度在0°～60°的范围内，超宽带天线阵列的总效率图。
图32显示为图29中，频率为39G时，超宽带天线阵列的阵列扫描角度在0°～60°的范围内，超宽带天线阵列的总效率图。
图33显示为图29中，频率为28G时，超宽带天线阵列在阵列扫描时的增益性能图。
图34显示为图29中，频率为39G时，超宽带天线阵列在阵列扫描时的增益性能图。
元件标号说明
10                     参考地金属板
11                     子金属结构单元
111                    第一金属结构件
112                    第二金属结构件
113                    弯折部
114                    梯形部
115                         寄生单元
12                          馈电结构
13                          子天线
14                          馈电网络
141                         5端口微波网络
142                         端口
143                         匹配枝节
144                         合成或功分功能网络
145-1、145-2、145-3、145-4  第一传输线路经
146-1、146-2、146-3、146-4  第二传输线路径
15                          第三金属结构件
16                          金属壁
17                          金属腔体结构
18                          介质
19                          模拟手机金属结构
20                          一维超宽带天线阵列
21                          超宽带天线
具体实施方式
以下通过特定的具体实例说明本发明的实施方式，本领域技术人员可由本说明书所揭露的内容轻易地了解本发明的其他优点与功效。本发明还可以通过另外不同的具体实施方式加以实施或应用，本说明书中的各项细节也可以基于不同观点与应用，在没有背离本发明的精神下进行各种修饰或改变。
请参考图1至图32。需要说明的是，本实施例中所提供的图示仅以示意方式说明本发明的基本构想，遂图示中仅显示与本发明中有关的组件而非按照实际实施时的组件数目、形状及尺寸绘制，其实际实施时各组件的型态、数量及比例可为一种随意的改变，且其组件布局型态也可能更为复杂。
如图1所示，本发明提供一种超宽带天线，所述超宽带天线包括：参考地金属板10、4个相同的子金属结构单元11及4个馈电结构12；
4个相同的所述子金属结构单元11设置于所述参考地金属板10上，且4个相同的所述 子金属结构单元11沿周向等间隔90°设置；
每个所述子金属结构单元11包括：1个沿水平方向延伸的第一金属结构件111、2个沿竖直方向延伸且间隔设置的第二金属结构件112，2个所述第二金属结构件112的一端与所述第一金属结构件111直接连接，1个所述第二金属结构件112的另一端与所述参考地金属板10连接，另一个所述第二金属结构件112的另一端与所述参考地金属板10之间加入一个所述馈电结构12；
每个所述子金属结构单元11与其余3个所述子金属结构单元11之间具有耦合作用，具体地为每个所述子金属结构单元11与其余3个所述子金属结构单元11之间通过所述第一金属结构件111的距离、形状等结构参数而发生耦合作用；
相对设置的2个所述子金属结构单元11组成一组子天线13，4个所述子金属结构单元11组成2组所述子天线13，每组所述子天线13的2个所述馈电结构12施加相位差为180°的差分馈电。
本发明提出的结构，设置4个沿周向等间隔90°设置的子金属结构单元11，并通过对相对设置的2个子金属结构单元11施加相位差为180°的差分馈电，同时使4个子金属结构单元11之间具有耦合作用，改变了每组子天线13的周向中心位置处的电场分布，激发了新的低频谐振模式，形成超宽带天线，且当一组子天线13被激励时，另一组子天线13通过耦合作用，作为寄生单元结构，起到了拓宽低频带宽的效果，同时由于寄生单元结构上电流的流动，且寄生电流与激励电流平行，在不影响两组子天线13隔离度的情况下，增加了超宽带天线整体的辐射有效面积，使辐射增益增大。另外，通过多个第二金属结构件112与参考地金属板10的电连接，既缩小了超宽带天线的谐振尺寸，又因其电感效应补偿了多个第一金属结构件111的电容效应，起到增加天线带宽的作用。这里需要说明的是，所述第一金属结构件111沿水平方向延伸，指的是所述第一金属结构件111的整体走势是朝着水平方向，所以本发明不限制所述第一金属结构件111的形状，只要满足其整体走势是沿水平方向即可，例如，所述第一金属结构件111可以是完全水平的形状(如1所示)、也可以是具有沿竖直方向的弧度，且可以是部分具有该弧度，如图2中的梯形部114或整个第一金属结构件111具有该弧度、也可以是第一金属结构件111上设置有沿竖直方向的弯折。所述第二金属结构件112沿竖直方向延伸，指的是所述第二金属结构件112的整体走势是朝着竖直方向，所述本发明不限制所述第二金属结构件112的形状，只要满足其整体走势是沿着竖直方向即可，例如，所述第二金属结构件112可以是完全竖直的形状(如图1所示)、也可以是具有沿水平方向的弧度，且可以是部分具有该弧度或整个第一金属结构件111具有该弧度、也可以是第二金属结 构件112上设置有沿水平方向的弯折，如图2中的弯折部113。
2组所述子天线13的2个子金属结构单元11之间的间距可以根据实际需要进行调整，可以根据需要设置为相同(如图1所示)，也可以设置为不同。
如图1至图3所示，作为示例，所述第一金属结构件111靠近所述周向中心位置的一端沿所述第一金属结构件111的径向指向该中心位置方向的宽度逐渐减小；较佳地，所述第一金属结构件111靠近周向中心位置的一端设置为梯形形状，例如图1至图3中的梯形部114，如图2所示，所述梯形部114沿竖直方向具有弧度。将所述第一金属结构件111靠近周向中心位置的一端设置为宽度逐渐减小，可有效缩短四个子金属结构单元11之间的距离，从而提高4个子金属结构单元11之间的耦合效果。由此也可知，还可将所述第一金属结构件111靠近周向中心位置的一端设置为其它形状，以缩短四个子金属结构单元11之间的距离。进一步的，作为一较佳示例，如图5所示，4个所述第一金属结构件111构成沿顺时针方向旋转或逆时针方向旋转的类螺旋桨状结构。
不限制所述第二金属结构件112的形状，例如可以是扁平的片状结构，也可以是柱状结构。如图5所示，优选所述第二金属结构件112为圆柱状结构，以便于工艺生产。
如图5所示，作为示例，可设置相邻2个所述子金属结构单元11的2个所述馈电结构12之间馈电相位差的绝对值为90°，即将2组所述子天线13中相邻的两个子金属结构单元11的馈电相位差的绝对值设置为90°，从而使所述超宽带天线辐射左旋圆极化波或右旋圆极化波，以为左旋圆极化天线及右旋圆极化天线的集成提供可能。基于此结构，如图12及图13所示，可设计一馈电网络14，所述馈电网络14中包含2个5端口142微波网络141，每个所述微波网络141的输出/输入端口与所述超宽带天线连接的4个输入/输出端口的传输相位的差值的绝对值分别为0°、80°～100°、170°～190°及260°～280°。所述馈电网络中还包含合成或功分功能网络144，以实现对信号的合成或功分，作为示例，所述合成或功分功能网络144由带有匹配枝节143的微带线或带状线构成。
作为示例，所述微波网络141可以是现有任意可将线极化信号合成为圆极化信号或将圆极化信号功分为线极化信号的功能网络。例如，所述微波网络141可以为4相耦合器或由电感及电容元器件设计构成的功能网络，也可为由微带线或带状线设计构成的功能网络，在此不做限制。
如图5所示，作为示例，所述超宽带天线还包括第三金属结构件15，所述第三金属结构件15设置于所述参考地金属板10上并与其电连接，起到阻抗匹配的作用。这里不限制所述第三金属结构件15的形状及设置位置等参数，具体依据其需要达到的阻抗匹配的作用根据实 际情况进行设计。在本实施例中，可将所述第三金属结构件15分别设置于4个所述子金属结构单元11的周侧和/或所述周向的中心位置，即所述第三金属结构件15可仅分别设置于4个所述子金属结构单元11的周侧，也可仅设置于所述周向的中心位置，也可同时设置于4个所述子金属结构单元11的周侧及所述周向的中心位置。这里需要说明的是设置于中心位置的所述第三金属结构件15的形状与设置于所述子金属结构单元11周侧的所述第三金属结构件15的形状根据具体的阻抗匹配要求进行设置，可以相同也可以不相同；较佳地，设置于每个子金属结构单元11周侧的所述第三金属结构件15的数量可以是1个或2个；更进一步地，设置于所述子金属结构单元11周侧的所述第三金属结构件15与其对应的所述子金属结构单元11之间的位置关系相同，即每个所述子金属结构单元11与其周侧的所述第三金属结构件15之间的位置关系相同；再进一步地，当设置于每个子金属结构单元11周侧的所述第三金属结构件15的数量是1个时，则4个所述子金属结构单元11周侧的4个所述第三金属结构件15为相同结构的第三金属结构件15且与对应的第三金属结构件15之间的位置关系也相同，当设置于每个子金属结构单元11周侧的所述第三金属结构件15的数量是2个时，该2个第三金属结构件15的结构可以是相同的也可以是不相同的，但4个所述子金属结构单元11周侧的2个第三金属结构件15为相同结构的2个第三金属结构件15且与对应的第三金属结构件15之间的位置关系也相同。如图23及图24所示，作为示例，所述超宽带天线还可包括金属壁16，4个所述子金属结构单元11位于由所述金属壁16及所述参考地金属板10构成的金属腔体结构17内，所述金属壁16与所述参考地金属板10之间电连接或非电连接。
如图3所示，作为示例，每个所述子金属结构单元11中，加入所述馈电结构12的所述第二金属结构件112的一侧设置有寄生单元115，所述寄生单元115与所述参考地金属板10直接连接且沿竖直方向延伸，呈倒L形，即该寄生单元115包括沿竖直方向的竖直部及沿水平方向的水平部，该寄生单元115与该第二金属结构件112(这里的第二金属结构件112指的是加入所述馈电结构12的所述第二金属结构件112)耦合激发出新的谐振频率，以拓宽超宽带天线的带宽。
基于上述超宽带天线还可形成超宽带天线阵列，以使所述超宽带天线呈阵列排布。
下面将结合具体的附图及相应的实施例对本发明的超宽带天线及天线阵列进行详细描述，显然，所描述的实施例仅仅是本发明一部分实施例，而不是全部的实施例。基于本发明的实施例，本领域一般技术人员在没有做出创造性劳动的前提下所获得的所有其他实施例，都属于本发明保护的范围。
实施例1
本实施例可实现GNSS L1，L2与SDARS功能的超宽带天线，通过本实施例的超小型化宽带天线设置，同时实现了GNSS L1(1.56G～1.605G)频段，L2(1.2G～1.26G)频段的右旋圆极化波天线功能以及SDARS 2.32G～2.45G频段的左旋圆极化波接收功能。提高了系统的集成度以及空间利用率；同时，不同于传统的贴片天线采用高成本，高介电常数的陶瓷作为介质材料的设计方法，本实施例在保持同样天线尺寸的情况下采用了低成本，低介电常数为4的塑料材质，同样达到了低频1.2G频段的要求，间接实现了小型化功能。
如图4及图5所示，本实施例的超宽带天线中，参考地金属板10的尺寸为7cm*7cm。超宽带天线还包括介质18，所述介质18包覆4个所述子金属结构单元11，所述介质18的材料采用介电常数为4的塑料材质，也可为其他低介电常数的材料，在此不做限制，尺寸为6.2cm*6.2cm*1.1cm。
4个相同的子金属结构单元11沿顺时针方向旋转构成类螺旋桨状结构，且4个子金属结构单元11沿周向等间隔90°设置的同时，每个子金属结构单元11绕着周向每旋转90°均与其他3个子金属结构单元11重合。其中一个第二金属结构件112为铜圆柱，直径5mm、高度1.1cm，穿过塑料材质的所述介质18与第一金属结构件111直接连接，下端连接所述参考地金属板10；另一个第二金属结构件112为竖直的片状结构，与第一金属结构件111直接电连接，馈电结构12的馈电点施加于另一个第二金属结构件112与参考地金属板10之间。
相对设置的两个子金属结构单元11的馈电结构12的馈电点施加相差180°的差分馈电。当4个所述馈电结构12沿顺时针方向相位依次相差90°，即沿顺时针方向相位依次为0°、90°、180°、270°，则此超宽带天线接收右旋圆极化(RHCP)波，用于GNSS通信。当4个所述馈电结构12沿逆时针方向相位依次相差90°，即沿逆时针方向相位依次为0°、90°、180°、270°，则此超宽带天线接收左旋圆极化(LHCP)波，用于SDARS通信。
在参考地金属板10的四个边角上放置了尺寸为7mm*7mm*5mm的四个第三金属结构件15，相当于四个第三金属结构件15分别设置于4个子金属结构单元11的一侧，每个第三金属结构件15与参考地金属板10电连接，起到了调节阻抗匹配的作用。在本实施例中，将第三金属结构件15的形状设计为立方体。
如图6及图7所示，为超宽带天线的仿真S参数及仿真总效率图。GNSS L1频段的效率在-1.8～-2dB区间；GNSS L2频段的效率在-0.7～-0.9dB区间；SDARS频段的效率在-1.6～1.95dB区间。如图8至图10所示，为GNSS天线与SDARS天线在x-z plane(坐标系请参考图5中的三维直角坐标系)的仿真增益与方向图。在GNSS L2频段中心频率处1.235G，zenith方位的右旋圆极化波最大增益为3.29dBi；在GNSS L1频段中心频率处1.575G，zenith方位的右 旋圆极化最大增益为3.79dBi；在SDARS频段中心频率处2.332G，zenith方位的左旋圆极化波最大增益为6.58dBi。增益性能满足实际使用上的要求。
由于本实施例的超宽带天线的对称性，如图11所示，GNSS RHCP波与SDARS LHCP的轴比都有不错性能，在仿真中都接近0dB，且从-50°～50°，轴比数值都在2dB以下。
如图12所示，为针对本实施例的超宽带天线设计的馈电网络14，实际设计中，每个子金属结构单元11的第二金属结构件112会通过金属结构与参考地金属板10下面的馈电网络14进行电连接。这种馈电网络结构以及与子金属结构单元的连接方式，即馈电网络通过参考地金属板与子金属结构单元隔离开，有利于天线与馈电网络14的隔离，减少互相干扰。如图12所示，馈电网络14在接收到每个子金属结构单元11的信号后，经过双工器结构(即功分功能网络144)分为两路，第一传输线路路径为145-1、145-2、145-3、145-4，第二传输线路径为146-1、146-2、146-3、146-4，第一传输线路路径汇合于右下角的微波网络141，本实施例选择微波网络141为四相耦合器，用来接收SDARS频段的左旋极化信号；第二传输线路路径汇合于左上角的微波网络141，本实施例选择微波网络141为四相耦合器，用来接收GNSS频段的右旋极化信号。四相耦合器使用市场上现有的微波器件。
如图13所示，根据图12的馈电网络设计，提出了如图13所示的双层PCB馈电网络结构，PCB长宽尺寸为8cm*8cm，介质材料采用了Rogers的Dk＝4，Df＝0.003的PTFE陶瓷材料，介质厚度为2mm。因为馈电网络沿着对角线B对称设计，所以我们只列出145-1、145-4，146-1、146-4的仿真结构来验证本馈电网络设计。
仿真结果如图14至图16所示，在图14中，在GNSS天线与SDARS天线频段，传输线的损耗基本都在1dB以下，且差值在0.2dB以内；在图15中，在SDARS天线频段内，145-1、145-4的传输相位特性保持在3°以内；在图16中，在GNSS天线的L1，L2频段内，146-1、146-4的传输相位特性保持在10°以内。不管是幅度特性还是相位特性，此馈电网络的各个支路都有着较高的一致性，从而保证了圆极化天线的轴比特性。
结合本实施例的超宽带天线及馈电网络的整体的系统仿真效果如图17至图22所示。在图17及图18中，GNSS天线与SDARS天线频段回波损耗都在-15dB以下，总效率基本都在-3dB以上；图19及图20为GNSS天线RHCP的方向图与增益性能，图21为SDARS天线LHCP的方向图与增益性能，增益性能都在2dBi以上，基本满足实际需求；图22为GNSS天线RHCP与SDARS天线LHCP的轴比性能，在-50°～50°之间，AR轴比都在5dB以下，显示了不错的轴比性能。
实施例2
本实施例的超宽带天线用于全金属边框终端用户设备的超宽带毫米波天线。如今全金属边框手机已经成为主流，以本实施例的超宽带天线为单元所构成的天线阵列，实现了在金属边框环境中5G毫米波阵列天线的设计，同时达到了26G～29.5G，37G～42.5G超宽频段下的双极化的要求。如图23及图24所示，天线还包括金属壁16、介质18，4个所述子金属结构单元11位于由参考地金属板10与金属壁16构成的金属腔体结构17内，金属壁16与参考地金属板10之间电连接或非电连接，介质18的材料采用低介电常数为2，正切损耗为0.003的低损耗材料PTFE，介质18的尺寸为4.5mm*4.5mm*1.1mm，填充满于金属腔体结构17内。
4个子金属结构单元11沿周向等间隔90°设置的同时，每个子金属结构单元11绕着周向每旋转90°均与其他3个子金属结构单元11重合。其中一个第二金属结构件112为金属柱，直径0.2mm、高度1.1mm，穿过所述介质18与第一金属结构件111直接连接，下端连接所述参考地金属板10；另一个第二金属结构件112为竖直的片状结构，与第一金属结构件111直接电连接，馈电结构12的馈电点施加于另一个第二金属结构件112与参考地金属板10之间。
相对设置的两个子金属结构单元11的馈电结构12的馈电点施加相差180°的差分馈电，且构成子天线13(如图24所示)，4个子金属结构单元11组成2组子天线13，2组子天线13在空间上呈正交关系，用来实现双极化波的辐射。其中，沿上下方向的子天线13辐射phi＝45°方向极化波，沿左右方向的子天线13辐射phi＝-45°方向极化波。Phi为图24中，2个子天线13的几何中轴线与x轴方向夹角。
如图25及图26所示，为本实施例的超宽带毫米波天线的仿真S参数及仿真总效率图。对于phi＝±45°极化子天线，在26G～29.5G频段与37G～42.5G频段效率都在在-2dB以上。如图27所示，为本实施例的超宽带毫米波天线的增益性能图。在26G～29.5G频段与37G～42.5G频段，phi＝±45°极化子天线13的增益都在4.5dBi以上，37G～42.5G频段达到了6dBi以上，有着不错的增益性能。
如图28及图29所示，接下来以上述超宽带天线21为单元构成1*4的一维超宽带天线阵列20，其中，每个所述超宽带天线21的所述子天线13的中轴线与该一维天线阵列的排列方向的夹角的绝对值为45°，以及其在手机模拟金属结构19中的仿真性能。图28及图29中，沿左上角至右下角方向的子天线13构成了1*4的天线阵列，用于phi＝45°方向极化波辐射；沿右上角至左下角方向的子天线13构成了1*4的天线阵列，与沿左上角至右下角方向的子天线13正交，用于phi＝-45°方向极化波辐射。实施例中使用140mm*70mm*5.4mm的手机模拟金属结构19来模拟手机尺寸，一维超宽带天线阵列20嵌在手机模拟金属结构19的边框之 内，phi＝±45°极化阵列沿着Y轴对称。
如图30所示，为1*4的一维超宽带天线阵列20中各超宽带天线21之间的隔离度图，由于对称关系，phi＝±45°极化阵列性能相同，只列出phi＝45°方向极化阵列各超宽带天线21之间的隔离度结果，超宽带天线21之间的隔离度都超过-15dB，有着不错的隔离特性。
如图31及图32所示，为1*4的一维超宽带天线阵列20的阵列扫描角度在0°～60°的范围内，一维超宽带天线阵列20的总效率图，图中水平坐标轴angle为图29中z-y plane中与z轴的夹角，即天线在角度扫描时与天线阵列正前面方向的夹角。在图31中，频率为28G时，阵列扫描角度在0°～60°的范围内，天线阵列的总效率基本在50％以上。在图32中，频率为39G时，阵列扫描角度在0°～60°的范围内，天线阵列的总效率基本在60％以上。
如图33及图34所示，为1*4的一维超宽带天线阵列20在角度扫描时的增益性能图，图33中，对于28G时，阵列扫描角度在0°～45°的范围内，增益值峰值差值保持在1.5dBi内，基本稳定。在图34中，对于39G时，虽然增益值峰值变化浮动较大(由于旁瓣效应)，但是峰值都在10dBi以上，有着不错的增益性能。
综上所述，本发明提供一种超宽带天线及天线阵列，本发明提出的结构，设置4个沿周向等间隔90°设置的子金属结构单元，并通过对相对设置的2个子金属结构单元施加相位差为180°的差分馈电，同时使4个子金属结构单元之间具有耦合作用，改变了每组子天线的周向中心位置处的电场分布，激发了新的低频谐振模式，形成超宽带天线，且当一组子天线被激励时，另一组子天线通过耦合作用，作为寄生单元结构，起到了拓宽低频带宽的效果，同时由于寄生单元结构上电流的流动，且寄生电流与激励电流平行，在不影响两组子天线隔离度的情况下，增加了超宽带天线整体的辐射有效面积，使辐射增益增大。另外，通过多个第二金属结构件与参考地金属板的电连接，既缩小了超宽带天线的谐振尺寸，又因其电感效应补偿了多个第一金属结构件的电容效应，起到增加天线带宽的作用。所以，本发明有效克服了现有技术中的种种缺点而具高度产业利用价值。
上述实施例仅例示性说明本发明的原理及其功效，而非用于限制本发明。任何熟悉此技术的人士皆可在不违背本发明的精神及范畴下，对上述实施例进行修饰或改变。因此，举凡所属技术领域中具有通常知识者在未脱离本发明所揭示的精神与技术思想下所完成的一切等效修饰或改变，仍应由本发明的权利要求所涵盖。

Claims (21)

  1. 一种超宽带天线，其特征在于，所述超宽带天线包括：参考地金属板、4个相同的子金属结构单元及4个馈电结构；
    4个相同的所述子金属结构单元设置于所述参考地金属板上，且4个相同的所述子金属结构单元沿周向等间隔90°设置；
    每个所述子金属结构单元包括：1个沿水平方向延伸的第一金属结构件、2个沿竖直方向延伸且间隔设置的第二金属结构件，2个所述第二金属结构件的一端与所述第一金属结构件直接连接，1个所述第二金属结构件的另一端与所述参考地金属板连接，另一个所述第二金属结构件的另一端与所述参考地金属板之间加入一个所述馈电结构；
    每个所述子金属结构单元与其余3个所述子金属结构单元之间具有耦合作用；相对设置的2个所述子金属结构单元组成一组子天线，4个所述子金属结构单元组成2组所述子天线，每组所述子天线的2个所述馈电结构施加相位差为180°的差分馈电。
  2. 根据权利要求1所述的超宽带天线，其特征在于：相邻2个所述子金属结构单元的2个所述馈电结构之间馈电相位差的绝对值为90°，使所述超宽带天线辐射左旋圆极化波或右旋圆极化波。
  3. 根据权利要求2所述的超宽带天线，其特征在于：辐射右旋圆极化波的所述超宽带天线为GNSS天线，辐射左旋圆极化波的所述超宽带天线为SDARS天线。
  4. 根据权利要求2所述的超宽带天线，其特征在于：4个所述馈电结构连接于一个馈电网络，所述馈电网络中包含2个5端口微波网络，每个所述5端口微波网络的输出/输入端口与所述超宽带天线连接的4个输入/输出端口的传输相位的差值的绝对值分别为0°、80°～100°、170°～190°及260°～280°。
  5. 根据权利要求4所述的超宽带天线，其特征在于：所述微波网络为4相耦合器或由电感及电容元器件设计构成的功能网络。
  6. 根据权利要求4所述的超宽带天线，其特征在于：所述微波网络为由微带线或带状线设计构成的功能网络。
  7. 根据权利要求4所述的超宽带天线，其特征在于：所述馈电网络中包含合成或功分功能网络。
  8. 根据权利要求7所述的超宽带天线，其特征在于：所述合成或功分功能网络由带有匹配枝节的微带线或带状线构成。
  9. 根据权利要求1所述的超宽带天线，其特征在于：所述第一金属结构件的形状为具有弧度和/或弯折的形状，所述第二金属结构件的形状为具有弧度和/或弯折的形状。
  10. 根据权利要求1或9所述的超宽带天线，其特征在于：所述第一金属结构件靠近所述周向中心位置的一端沿所述第一金属结构件的径向指向所述中心位置方向的宽度逐渐减小。
  11. 根据权利要求10所述的超宽带天线，其特征在于：4个所述第一金属结构件构成沿顺时针方向旋转或逆时针方向旋转的类螺旋桨状结构。
  12. 根据权利要求10所述的超宽带天线，其特征在于：所述第一金属结构件靠近周向中心位置的一端设置为梯形形状。
  13. 根据权利要求1所述的超宽带天线，其特征在于：所述第二金属结构件为圆柱状。
  14. 根据权利要求1所述的超宽带天线，其特征在于，所述超宽带天线还包括第三金属结构件，所述第三金属结构件设置于所述参考地金属板上并与其电连接，起到阻抗匹配的作用。
  15. 根据权利要求14所述的超宽带天线，其特征在于：所述第三金属结构件分别设置于4个所述子金属结构单元的周侧和/或所述周向的中心位置。
  16. 根据权利要求15所述的超宽带天线，其特征在于：设置于每个所述子金属结构单元周侧的所述第三金属结构件的数量为1个或2个。
  17. 根据权利要求14所述的超宽带天线，其特征在于：所述第三金属结构件的形状为立方体。
  18. 根据权利要求1所述的超宽带天线，其特征在于，所述超宽带天线还包括金属壁，4个所述子金属结构单元位于由所述金属壁及所述参考地金属板构成的金属腔体结构内，所述金属壁与所述参考地金属板之间电连接或非电连接。
  19. 根据权利要求1所述的超宽带天线，其特征在于：每个所述子金属结构单元中，加入所述馈电结构的所述第二金属结构件的一侧设置有寄生单元，所述寄生单元与所述参考地金属板直接连接且沿竖直方向延伸，呈倒L形，该寄生单元与该第二金属结构件耦合激发出新的谐振频率。
  20. 一种超宽带天线阵列，其特征在于，所述超宽带天线阵列包括如权利要求1至19中任意一项所述的超宽带天线，且所述超宽带天线呈阵列排布。
  21. 根据权利要求20所述的超宽带天线阵列，其特征在于：所述超宽带天线阵列为一维天线阵列，其中，每个所述超宽带天线的所述子天线的中轴线与该一维天线阵列的排列方向的夹角的绝对值为45°。
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