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WO2016150245A1 - 一种dc/dc转换器 - Google Patents

一种dc/dc转换器 Download PDF

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Publication number
WO2016150245A1
WO2016150245A1 PCT/CN2016/071517 CN2016071517W WO2016150245A1 WO 2016150245 A1 WO2016150245 A1 WO 2016150245A1 CN 2016071517 W CN2016071517 W CN 2016071517W WO 2016150245 A1 WO2016150245 A1 WO 2016150245A1
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WO
WIPO (PCT)
Prior art keywords
switch
switch tube
circuit
rectifying
rectification
Prior art date
Application number
PCT/CN2016/071517
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English (en)
French (fr)
Inventor
王跃斌
宋栋梁
崔荣明
Original Assignee
深圳市皓文电子有限公司
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Publication date
Application filed by 深圳市皓文电子有限公司 filed Critical 深圳市皓文电子有限公司
Publication of WO2016150245A1 publication Critical patent/WO2016150245A1/zh

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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
    • H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
    • H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
    • H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
    • H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/33569—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements
    • H02M3/33576—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer
    • H02M3/33592—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only having several active switching elements having at least one active switching element at the secondary side of an isolation transformer having a synchronous rectifier circuit or a synchronous freewheeling circuit at the secondary side of an isolation transformer
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/14—Arrangements for reducing ripples from dc input or output
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
    • H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
    • H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
    • H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
    • H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
    • H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation

Definitions

  • This invention relates to power supplies and, more particularly, to a DC/DC converter.
  • the resonant network is applied to the power conversion circuit, which can effectively reduce the switching loss and noise of the circuit, reduce the electromagnetic interference, reduce the voltage and current pressure of the device, improve the switching frequency, improve the efficiency, reduce the volume weight, and improve the power for the converter. Density creates good conditions.
  • the widely used LLC resonant topology adopts PFM control in the control method, that is, the switching frequency is changed, which makes the design of the control method complicated; when using PFM control, the transformer needs to be designed according to the lowest operating frequency, and the design of the transformer itself is complicated.
  • the parameters are difficult to optimize; in the synchronous rectification circuit, the synchronous rectification drive circuit is complicated due to the variable frequency control; the LLC resonant topology output usually adopts capacitive filtering, and the capacitor bears the resonant ripple current, which is not only large in loss, but also has serious heat generation and large output ripple. . Therefore, it is necessary to seek a circuit or a combination of a circuit and a control method not only to realize the soft switching of the switching tube in a wide load range, but also to simplify the design of the transformer and the secondary side synchronous rectification driving.
  • the technical problem to be solved by the present invention is to provide a method for the above-mentioned resonant network of the prior art, which is complicated in control mode, cannot optimize the transformer design, has difficulty in designing the secondary side synchronous rectification drive control, and has large output ripple.
  • the control method is simple, the transformer can optimize the design, the synchronous rectification drive control circuit is simple in design, and the output ripple current is small, a DC/DC converter.
  • the technical solution adopted by the present invention to solve the technical problem is to construct a DC/DC converter including an inverter unit, a resonance unit, a high frequency transformer and a rectification and filtering unit;
  • the inverter unit includes a half bridge circuit in an asymmetry a complementary pulse width modulated control signal or a full bridge circuit converts a DC input into a square wave under constant frequency phase shift control;
  • the resonant unit obtains a square wave of its output by the inverter unit and causes Resonating and transmitting it to the primary side of the high-frequency transformer;
  • the rectifying and filtering unit adopts double current rectification, full-wave rectification or full-bridge rectification and converts the alternating current waveform on the secondary side of the high-frequency transformer by LC filtering Switch to DC output.
  • the inverter unit includes a half bridge circuit composed of a first controlled switch tube and a second controlled switch tube, and one end of the DC input sequentially passes through the two switch ends of the first switch tube and the second switch tube.
  • the two switch ends are connected to the other end of the DC input;
  • the two switch tubes are respectively controlled by their asymmetric, complementary pulse width modulation signals input from the control terminal;
  • the control end of the first switch tube a pulse width of the upper control signal determines a pulse width of the output square wave of the inverter unit;
  • the resonance unit is obtained by a connection point of the first switch tube and the second switch tube, and one end or the other end of the DC input The square wave output by the inverter unit.
  • a period of the control signal input by the control ends of the first switch tube and the second switch tube is a set length, and when the duty ratio of the control signal of the first controlled switch is D, the first The duty ratio of the control signal of the two controlled switches is 1-D; the two control signals are respectively advanced or delayed by a set width at their adjacent high and low level switching positions to form a dead zone of the set width to prevent The two switching tubes are simultaneously turned on.
  • the inverter unit includes a full bridge inverter circuit adopting constant frequency phase shift control;
  • the full bridge inverter circuit includes a first half composed of a first controlled switch tube and a second controlled switch tube a bridge circuit and a second half bridge circuit composed of a third controlled switch tube and a fourth controlled switch tube; one end of the DC input is sequentially connected to the DC input through the two switch ends of the first switch tube and the second switch tube The other end; the one end of the DC input is also connected to the other end of the DC input of the third switch tube and the fourth switch tube;
  • the two switch tubes of one half bridge circuit are respectively input by the control end thereof, and each has A pulse-width modulated signal having a 50% duty cycle and a phase difference of 180 degrees controls its switching; there is a setting between control signals of two controlled switching transistors in the two half-bridge circuits at their topological diagonal positions a phase difference or a phase shift angle, the set phase difference determining a pulse width of the output square wave of the inverter unit; the resonance unit being
  • one half bridge The control signals of the two controlled switches in the circuit have equal pulse widths, each having a 50% duty cycle and a phase difference of 180 degrees, and the two control signals are advanced or delayed by one at their adjacent high and low level switching positions, respectively.
  • the width is set to form a dead zone of the set width to prevent the two switches from being turned on at the same time.
  • the resonant unit includes a resonant inductor, a first resonant capacitor, and a second resonant capacitor, and the resonant inductor and the first resonant capacitor are connected in series with the primary side of the high-frequency transformer in an output of the inverter unit
  • the second resonant capacitor is connected to the primary or secondary side of the high-frequency transformer or the sum of the parallel capacitors of the primary and secondary sides
  • the resonant inductor is an independent inductor Or the leakage inductance of the transformer or the sum of the two
  • the second resonant capacitor is a separate capacitor or a rectifier switch parasitic capacitance or a parallel equivalent equivalent of the two.
  • the primary side of the high frequency transformer is one winding
  • the secondary side is one or more windings.
  • the rectifying and filtering circuit includes a rectifying portion and a filtering portion; the rectifying portion includes a rectifying device, and when rectifying and rectifying, the rectifying device is a diode using a common anode or a common cathode current doubler rectifying circuit or adopting The MOSFET of the synchronous rectification circuit; the filtering part is an LC combined filter circuit.
  • the rectifying and filtering circuit includes a rectifying portion and a filtering portion; the rectifying portion includes a rectifying device, and the rectifying device is a diode using a common anode or a common cathode rectifying circuit when full-wave or full-bridge rectification;
  • the filtering part is an LC combined filter circuit.
  • a DC/DC converter embodying the present invention has the following beneficial effects: since the inverter unit uses an asymmetric, complementary PWM drive signal to control the conduction and turn-off of its controlled switch tube, and at the same time, the resonant capacitor in the resonant unit It is connected to the high-frequency transformer. Therefore, the soft switching of the switching tube can be realized in a wide load range, thereby reducing switching loss and EMI, making the filter circuit easy to design. At the same time, the parasitic parameters of the high-frequency transformer will be used as the resonant element, eliminating the pair.
  • the rectification and filtering unit adopts double current rectification, full-wave rectification or full-bridge rectification plus LC combined filtering, so that its rectifier diodes are naturally commutated without reverse recovery problem. Due to the presence of the resonant unit, the power switch tube is at zero Turning on or off under voltage or zero current conditions realizes soft switching of the power switch tube and improves conversion efficiency.
  • FIG. 1 is a schematic structural view of a DC/DC converter in an embodiment of a DC/DC converter according to the present invention
  • FIG. 2 is a schematic structural view of a half bridge asymmetric control in the embodiment
  • Figure 3 is a schematic view of the driving waveform of Figure 2;
  • Figure 4 is a waveform diagram at two points of AB in Figure 2;
  • FIG. 5 is a schematic structural diagram of a phase-shifted full bridge using constant frequency control in the embodiment
  • FIG. 6 is a schematic diagram of driving waveforms of the inverter unit of FIG. 5;
  • Figure 7 is a waveform diagram of two points of AB in Figure 5;
  • Figure 8 is a waveform diagram of the rectifier diode of Figure 5.
  • Figure 9 is a schematic view showing a modified structure of the DC/DC converter of Figure 2;
  • Figure 10 is a schematic view showing a modified structure of the DC/DC converter of Figure 5;
  • 11-20 are respectively schematic structural diagrams of a rectifying and filtering unit in an embodiment of the present invention.
  • 21 is a schematic diagram showing a modified structure of an LC circuit in a rectifying and filtering unit according to an embodiment of the present invention.
  • FIG. 22 is a schematic diagram showing another modified structure of an LC circuit in a rectifying and filtering unit according to an embodiment of the present invention.
  • the DC/DC converter includes an inverter unit, a resonance unit, a high frequency transformer, and a rectification filtering unit;
  • the complementary input pulse width modulation (PWM) control signal converts the DC input into a square wave; and the resonant unit obtains the square wave of its output by the above-mentioned inverter unit and resonates it, and the resonant unit includes the parallel connection
  • the resonant capacitor on the high-frequency transformer is described; the rectifying and filtering unit adopts double current rectification, full-wave rectification or full-bridge rectification and converts the alternating current waveform on the secondary side of the high-frequency transformer into a direct current output by LC filtering.
  • Fig. 2 is a circuit diagram showing the structure of a half bridge as an inverter unit in the present invention.
  • the inverter unit includes Q 1 and Q 2 and its accessory elements
  • the resonance unit includes L r , C s and C p
  • the rectification filtering unit includes D 1 , D 2 , L f1 , L f2 and C o
  • the high frequency transformer is T 1
  • the resonant capacitor is the capacitors C s and C p in FIG. 2; in FIG.
  • the above inverter unit comprises a first controlled switch Q 1 and a second controlled switch Q 2
  • the first half bridge circuit one end of the DC input is sequentially connected to the other end of the DC input through the two switch ends of the first controlled switch Q 1 and the two switch ends of the second controlled switch Q 2
  • the controlled switch is a MOS transistor, the two switch ends of which are their source and drain, respectively, and the control end thereof is the gate of the MOS tube; the two controlled switches are respectively input by their control terminals, asymmetrical,
  • the complementary pulse width adjustment control signal controls its switch; that is, a control signal or a drive signal is applied to the gates of the first controlled switch Q 1 and the second controlled switch Q 2 described above to control the source and drain thereof.
  • the pulse width of the control signal on the control end of the first switch Q 1 determines the output of the inverter unit
  • the pulse width of the square wave also determines the magnitude of the DC power output of the converter; the resonant unit obtains the output of the inverter unit from the connection point of the first controlled switch Q 1 and the second controlled switch Q 2 and the other end of the DC input.
  • the square wave that is, the square wave output from the inverter unit is obtained from two points A and B in Fig. 2 .
  • T S is the total pulse width of the driving signal, and the pulse width of any one of the control signals cannot be equal to 1/2, that is, the two control signals cannot be symmetric.
  • V in is the input side DC power supply; the first controlled switch Q 1 and the second controlled switch Q 2 (including the internal parasitic diode and parasitic inductance of the switch) Forming a half bridge; the series resonant inductor L r , the first resonant capacitor C s and the second resonant capacitor C p constitute an LCC resonant network; T 1 is a high frequency transformer whose primary side is connected in parallel to both ends of the second resonant capacitor C p The secondary side is connected to the current doubler rectification topology; the current doubler rectification topology is composed of fast recovery diodes D 1 and D 2 , output filter inductors L f1 and L f2 , and an output filter capacitor C o ; R L is a load.
  • the DC input V in is connected to an asymmetric half-bridge topology consisting of a first controlled switch Q 1 and a second controlled switch Q 2 , and the PWM drive signal controls the complementary conduction of the two controlled switches and remains There is a certain dead zone (see Figure 3) to avoid straight-through.
  • a square wave voltage is generated between the drain and source of the second controlled switch Q 2 (two points A and B in Figure 2).
  • the voltage or current flowing through the LCC resonant loop is a sine wave or a quasi-sinusoidal wave, causing the first controlled switch Q 1 and the second controlled switch Q 2 to be turned on under zero voltage conditions.
  • the sinusoidal voltage on the primary side (primary side) of the transformer is coupled to the secondary side (secondary side).
  • the voltage is still sinusoidal.
  • the secondary side sinusoidal voltage is connected to the load R L through the current doubler rectifier circuit, and the rectifier diodes D 1 and D 2 are realized. Natural commutation.
  • the PWM drive signal is shown in Figure 3.
  • the square wave voltage V AB applied by the inverter unit to the LCC resonant network is as shown in FIG.
  • the asymmetry or the asymmetry means that the pulse widths of the two driving signals (ie, the width of the effective level) are unequal; and the complementary refers to the high level of the two driving signals.
  • the partial addition (including the previously set dead zone or isolation region at the level of the two drive signal level shifting) is equal to the total width of the drive pulse.
  • Fig. 2 shows the structure of the inverter unit in some cases in the present invention, and in other cases in the present invention, the above-mentioned inverter unit may also be constituted by two half bridges. Referring to FIG. 5, in FIG. 5, except that the structure and control signals of the inverter unit and the square wave output end are different from those of FIG. 2, the remaining components are substantially the same as those of FIG. In FIG.
  • the inverter unit includes a first half bridge circuit composed of a first controlled switch Q 1 and a second controlled switch Q 2 and is composed of a third controlled switch Q 3 and a fourth controlled switch Q 4 a second half bridge circuit; one end of the DC input is sequentially connected to the DC through the two switch ends of the first switch Q 1 and the third switch Q 3 and the two switch ends of the second switch Q 3 and the fourth switch Q 4 The other end of the input; in other words, the two half bridges are connected in parallel at both ends of the DC input; in the half bridge circuit, the two switch tubes are respectively input by their control terminals, each having a 50% duty ratio and having a phase difference of 180 The pulse width modulation control signal controls its switch; the two half bridge circuits are combined to form a full bridge circuit, which is provided between the control signals of the two controlled switches located at the top diagonal position of the full bridge circuit.
  • a predetermined phase difference or phase shift angle determines a pulse width of the output square wave of the inverter unit; adjusting the phase difference or the phase shift angle can adjust a DC level of the DC/DC converter output.
  • the resonant unit obtains a square wave output by the inverter unit by a connection point of the first controlled switch Q 1 and the second controlled switch Q 2 and a connection point of the third controlled switch Q 3 and the fourth controlled switch Q 4 . See points A and B in Figure 5. In FIG.
  • the control signals of the two controlled switches in one half bridge circuit have the same pulse width and phase difference of 180 degrees, and the two control signals are in the same
  • the adjacent positions are respectively advanced or delayed by a set width to form a dead zone of the set width to prevent the two switch tubes from being simultaneously turned on; and in the combined topology formed by the first half bridge circuit and the second half bridge circuit
  • the control signals between the controlled switches of the diagonal position (for example, between Q 3 and Q 2 in Figure 5 or between Q 1 and Q 4 ) differ by a set phase difference, ie there is a shift
  • the phase angle is adjusted by adjusting the phase shift angle to adjust the pulse width of the output of the full bridge inverter circuit. See Figure 6 for the drive signal in Figure 5.
  • V in is the input side of the DC power supply; controlled switch Q 1 ⁇ Q 4 (internal switch comprises a parasitic diode and a parasitic inductance) consisting of two half-bridge phase shift controlled switch Q 1 And Q 2 is the first half bridge, the phase of the driving signal is ahead of the second half bridge; the controlled switches Q 3 and Q 4 are the second half bridge, the phase lag of the driving signal and the driving signal of the first half bridge
  • the resonant unit also includes a series resonant inductor L r , a first resonant capacitor C s and a second resonant capacitor C p to form an LCC resonant network; T 1 is a high frequency transformer, and the primary side (primary side) is connected in parallel to the second resonant capacitor C p both ends of the secondary side (secondary side) contact times rectifier topology; Doubler rectifier topology of fast recovery diode D 1 and D 2, L f1 and output filter inductor L f2
  • a positive and negative alternating pulse square wave (see FIG. 7) is generated between the two points A and B in FIG. 5, and applied to the LCC resonant network.
  • the voltage or current flowing through the LCC resonant tank is a sinusoidal or quasi-sinusoidal wave that causes the controlled switches Q 1 -Q 4 to turn "on” and "off” under zero or zero current conditions.
  • the primary side sinusoidal voltage of the transformer is coupled to the secondary side and the voltage is still sinusoidal.
  • the secondary side sinusoidal voltage is connected to the load R L through the current doubler rectifier circuit, and the rectifier diodes D 1 and D 2 realize natural commutation.
  • PWM1 ⁇ PWM4 signal to drive the power switch Q 1 -Q 4 is, PWM controlled drive switches in half-bridge is turned on and a signal complementary to leave some dead avoid shoot-through; diagonal There is a phase shift angle between the PWM drive signals at the position of the switch, and the power adjustment is performed by controlling the phase shift angle.
  • the square wave voltage V AB applied to the LCC resonant network is as shown in FIG.
  • the voltage waveforms V D1 and V D1 of the rectifier diodes D 1 and D 2 are as shown in FIG.
  • the resonance unit thereof includes the resonance inductance L r , the first resonance capacitance C s , and the second resonance capacitance C p , wherein the (series) resonant inductor L r and the first resonant capacitor C s are connected in series with the primary side of the high-frequency transformer and connected to the two terminals of the output square wave of the inverter unit, and the second resonant capacitor C p is connected in parallel On the primary or secondary side of the high frequency transformer.
  • the second resonant capacitor is connected to the secondary side of the high frequency transformer, refer to FIG. 9 and FIG.
  • the second resonant capacitor when the inverter unit is a half bridge circuit, the second resonant capacitor is connected to the high frequency variable voltage secondary side.
  • the circuit at this time, the second resonant capacitor includes not only C p ' but also the parasitic capacitance of the rectifying device; and FIG. 10 is when the inverter unit is a full-bridge circuit, and the second resonant capacitor is connected to the high-frequency transformer The secondary side of the circuit (at this time, the second resonant capacitor also includes the parasitic capacitance of the rectifying device).
  • the rectifying and filtering unit includes two rectifying switches, two rectifying switches and a high frequency transformer, which are respectively connected to one end of the high frequency transformer, and the other switch end is connected to the common potential end.
  • a switch end connected at both ends of the secondary side is connected together as a positive output end of the DC output of the rectifying and filtering unit;
  • a DC negative output end of the rectifying and filtering unit is the common potential end;
  • the rectifying switch comprises a cathode and a high The diode connected to the secondary side of the frequency transformer (see Figure 2, Figure 5, Figure 9, and Figure 10) or the MOS tube (see Figure 13 and Figure 14).
  • the rectifying and filtering unit may be a bridge rectifying circuit whose input end is at both ends of the high frequency transformer, and the rectifying and filtering unit of the bridge rectifying circuit includes a diode (refer to FIG. 15). ) or a controlled MOS tube (see Figure 16).
  • the rectifying and filtering unit may also be a full-wave rectifying circuit, and the rectifying and filtering unit of the full-wave rectifying circuit includes a diode (see FIGS. 17 and 19) or a controlled MOS tube (see FIGS. 18 and 20).
  • the rectifying and filtering unit further comprises a filtering module, wherein the filtering module comprises a filter inductor (L f1 , L f2 ) and a filter capacitor C o ; wherein the filter inductor (L f1 , L f2 ) is connected in series with the DC The output capacitor and the negative terminal of the rectifier diode or the positive output of the bridge rectifier, the filter capacitor C o is connected between the DC positive output terminal and the negative output terminal. It is worth mentioning that in bridge rectification, the above two filter inductors can also be combined into one.
  • FIGS. 11 to 20 show a derivative circuit of the rectifying and filtering unit in the present invention, that is, in any of the cases of the present invention, the rectifying and filtering unit can adopt any one of Figs. 11 to 20.
  • the current doubler rectification circuit has two forms, and FIG. 2, FIG. 5, FIG. 9, FIG. 10, FIG. 12, and FIG. 13 are one of the circuit forms, and FIGS. 11 and 14 are Another circuit form; Fig. 2, Fig. 5, Fig. 9, Fig. 10, Fig. 11 and Fig. 12 are diode rectified, Fig. 13 and Fig. 14 are synchronous rectification; Fig. 15 is a diode rectified full bridge rectification circuit, Fig. 16 It is a full-bridge rectifier circuit using synchronous rectification; Figures 17 and 19 are full-wave rectification circuits using diode rectification, and Figures 18 and 20 are full-wave rectification circuits using synchronous rectification.
  • Fig. 21 and Fig. 22 respectively show two kinds of deformed structures which may exist in the LC circuit in the rectifying and filtering unit of the present invention.
  • an inductor that is usually connected in series with the filter capacitor is split into two and connected in series in the loop at both ends of the filter capacitor; and in FIG. 22, the inductor and the capacitor, which were originally one, are separately split.
  • the first LC filter circuit is connected between the output of the DC output and the ground
  • the second LC filter circuit It is connected to both ends of the filter capacitor of the first LC filter circuit, and the load is connected to both ends of the filter capacitor of the second LC filter circuit.
  • This will split the inductor or capacitor well. It is possible to reduce the inductance value or capacitance value of a single component, thereby reducing the volume of a single component, and being able to adapt to space or cost sensitive situations.
  • the respective units constituting the DC/DC converter in the above various cases including the inverter unit, the rectifying and filtering unit, the resonating unit, and the rectifying and filtering unit, are not limited to the above description.
  • a person skilled in the art can also make a reasonable combination, transformation or modification of the composition of each unit or the connection between the units according to common knowledge in the art.

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  • Dc-Dc Converters (AREA)

Abstract

一种DC/DC转换器，包括逆变单元、谐振单元、高频变压器和整流滤波单元。逆变单元包括在不对称、互补的脉冲宽度调制的控制信号作用下的半桥电路或在恒频移相控制下的全桥电路，其将直流输入转换为方波。谐振单元从逆变单元取得其输出的方波并使其谐振。谐振单元包括谐振电感、第一谐振电容和第二谐振电容。整流滤波单元为倍流整流、全波整流或全桥整流方式与各类LC滤波的组合，其将高频变压器的副边上的交流波形转换为直流输出。该DC/DC转换器控制方式简单、输出纹波小、转换效率高、变压器设计简单。

Description

一种DC/DC转换器 技术领域
本发明涉及电源，更具体地说，涉及一种DC/DC转换器。
背景技术
一般来讲，谐振网络应用于功率变换电路，能有效降低电路的开关损耗和噪声、降低电磁干扰、降低器件的电压和电流压力，为变换器提高开关频率、提高效率、降低体积重量、提高功率密度创造良好的条件。目前应用较广泛的LLC谐振拓扑在控制方法上均采用PFM控制，即开关频率是变化的，这使得其控制方法设计复杂；采用PFM控制时，变压器需要按照最低工作频率设计，变压器本身设计复杂，参数难以优化；在采用同步整流电路中也因变频控制导致同步整流驱动线路复杂；LLC谐振拓扑输出通常采用电容滤波，电容上承担谐振纹波电流，不仅损耗大，发热严重，输出纹波也大。因此，需要寻求一种电路或电路与控制方式的组合不仅能够实现宽负载范围内实现开关管的软开关，而且能够简化变压器和副边同步整流驱动的设计。
发明内容
本发明要解决的技术问题在于，针对现有技术的上述谐振网络用于变换器时控制方式复杂、变压器设计无法优化、副边同步整流驱动控制设计困难、输出纹波大的缺陷，提供一种控制方式简单、变压器能够优化设计、同步整流驱动控制电路设计简单、输出纹波电流小的一种DC/DC转换器。
本发明解决其技术问题所采用的技术方案是：构造一种DC/DC转换器，包括逆变单元、谐振单元、高频变压器和整流滤波单元；所述逆变单元包括半桥电路在不对称、互补的脉冲宽度调制的控制信号作用下或全桥电路在恒频移相控制下，将直流输入转换为方波；所述谐振单元由所述逆变单元取得其输出的方波并使其谐振，并将其传输到所述高频变压器原边；所述整流滤波单元采用倍流整流、全波整流或全桥整流并通过LC滤波将所述高频变压器的副边上的交流波形转 换为直流输出。
更进一步地，所述逆变单元包括由第一受控开关管和第二受控开关管组成的半桥电路，直流输入的一端依次通过第一开关管的两个开关端和第二开关管的两个开关端连接到直流输入的另一端；所述两个开关管分别由其控制端输入的、不对称的、互补的脉冲宽度调制信号控制其开关；所述第一开关管的控制端上的控制信号的脉冲宽度决定所述逆变单元输出方波的脉冲宽度；所述谐振单元由所述第一开关管和第二开关管的连接点以及所述直流输入一端或另一端取得所述逆变单元输出的方波。
更进一步地，所述第一开关管和第二开关管控制端输入的控制信号的周期为设定长度，在所述第一受控开关的控制信号的占空比为D时，所述第二受控开关的控制信号的占空比为1-D；所述两个控制信号在其相邻的高低电平转换位置分别提前或延迟一个设定宽度，形成设定宽度的死区以防止所述两个开关管同时导通。
更进一步地，所述逆变单元包括采用恒频移相控制的全桥逆变电路；所述全桥逆变电路包括由第一受控开关管和第二受控开关管组成的第一半桥电路以及由第三受控开关管和第四受控开关管组成的第二半桥电路；直流输入的一端依次通过第一开关管和第二开关管的两个开关端连接到直流输入的另一端；直流输入的一端还依次第三开关管和第四开关管的两个开关端连接到直流输入的另一端；一个半桥电路中两个开关管分别由其控制端输入的、各自具有50％占空比且相位相差180度的脉冲调宽调制信号控制其开关；所述两个半桥电路中位于其拓扑对角线位置的两个受控开关管的控制信号之间具有设定的相位差或移相角，所述设定的相位差决定所述逆变单元输出方波的脉冲宽度；所述谐振单元由所述第一开关管和第二开关管的连接点以及所述第三开关管和第四开关管的连接点取得所述逆变单元输出的方波。
更进一步地，在所述第一半桥电路和第二半桥电路中，一个半桥 电路中两个受控开关的控制信号的脉冲宽度相等、各自具有50％占空比且相位相差180度，且所述两个控制信号在其相邻的高低电平转换位置分别提前或延迟一个设定宽度，形成设定宽度的死区以防止所述两个开关管同时导通。
更进一步地，所述谐振单元包括谐振电感、第一谐振电容和第二谐振电容，所述谐振电感和第一谐振电容串联后与所述高频变压器原边串接在所述逆变单元输出方波的两个端子上，所述第二谐振电容并接在所述高频变压器的原边或副边上或为所述原、副边并接电容之和；所述谐振电感为独立电感或变压器之漏感或所述两者之和；所述第二谐振电容为独立电容或整流开关管寄生电容或所述两者的并联的等效电容。
更进一步地，所述高频变压器原边为一个绕组，副边为一个或一个以上绕组。
更进一步地，所述整流滤波电路包括整流部分和滤波部分；所述整流部分包括整流器件，在倍流整流时，所述整流器件为采用共阳极或共阴极倍流整流电路的二极管或为采用同步整流电路的MOSFET；其滤波部分为LC组合滤波电路。
更进一步地，所述整流滤波电路包括整流部分和滤波部分；所述整流部分包括整流器件，在全波或全桥整流时，所述整流器件为采用共阳极或共阴极整流电路的二极管；其滤波部分为LC组合滤波电路。
实施本发明的一种DC/DC转换器，具有以下有益效果：由于逆变单元采用不对称的、互补的PWM驱动信号控制其受控开关管的导通和截止，同时，谐振单元中谐振电容连接在高频变压器上，因此，可以在宽负载范围实现开关管的软开关，从而减少开关损耗和EMI，使得滤波电路易于设计，同时，高频变压器寄生参数将作为谐振元件,消除了其对电路的不利影响；此外，整流滤波单元采用倍流整流、全波整流或全桥整流加上LC组合滤波的方式，使得其整流二极管自然换流,没有反向恢复问题。由于谐振单元的存在，使得功率开关管在零 电压或零电流条件下导通或关断,实现了功率开关管的软开关，提高了变换效率。
附图说明
图1是本发明一种DC/DC转换器实施例中DC/DC转换器的结构示意图；
图2是所述实施例中采用半桥不对称控制时的结构示意图；
图3是图2中驱动波形示意图；
图4是图2中AB两点上的波形图；
图5是所述实施例中采用恒频控制移相全桥的结构示意图；
图6是图5中逆变单元的驱动波形示意图；
图7是图5中AB两点的波形图；
图8是图5中整流二极管上的波形图；
图9是图2中DC/DC变换器的一种变形结构示意图；
图10是图5中DC/DC变换器的一种变形结构示意图；
图11-20分别是本发明实施例中整流滤波单元的变形结构示意图；
图21是本发明实施例中整流滤波单元中LC电路的一种变形结构示意图；
图22是本发明实施例中整流滤波单元中LC电路的另一种变形结构示意图。
具体实施方式
下面将结合附图对本发明实施例作进一步说明。
如图1所示，在本发明一种DC/DC转换器的实施例中，该DC/DC转换器包括逆变单元、谐振单元、高频变压器和整流滤波单元；上述逆变单元在不对称的、互补的脉冲宽度调制(PWM)的控制信号作用下，将直流输入转换为方波；而谐振单元由上述逆变单元取得其输出的方波并使其谐振，谐振单元包括并接在所述高频变压器上的谐振电容；整流滤波单元采用倍流整流、全波整流或全桥整流并通过LC滤 波将所述高频变压器的副边上的交流波形转换为直流输出。图2是本发明中采用一个半桥作为逆变单元时的电路结构示意图。在图2中，逆变单元包括Q1和Q2及其附属元件，谐振单元包括Lr、Cs和Cp，整流滤波单元包括D1、D2、Lf1、Lf2和Co，高频变压器是T1，而谐振电容在图2中是电容Cs和Cp；在图2中，上述逆变单元包括由第一受控开关Q1和第二受控开关Q2组成的第一半桥电路，直流输入的一端依次通过第一受控开关Q1的两个开关端和第二受控开关Q2的两个开关端连接到直流输入的另一端；在本发明中，受控开关是MOS管，其两个开关端分别是其源极和漏极，其控制端是该MOS管的栅极；上述两个受控开关分别由其控制端输入的、不对称的、互补的脉冲调宽控制信号控制其开关；也就是说，控制信号或驱动信号施加在上述第一受控开关Q1和第二受控开关Q2的栅极，控制其源极和漏极的接通或断开；其中，第一开关Q1的控制端上的控制信号的脉冲宽度决定该逆变单元输出方波的脉冲宽度，也决定了该转换器输出直流功率的大小；谐振单元由第一受控开关Q1和第二受控开关Q2的连接点以及直流输入的另一端取得逆变单元输出的方波，即由图2中的A、B两点取得逆变单元输出的方波。在本发明中，图2中的两个受控开关的控制信号(驱动信号)的总的脉冲宽度(即脉冲周期)是相同的，但是这两个控制信号的有效电平(即控制受控开关导通的电平)出现位置是不同的，具体来讲是不对称且互补的；换句话说，这两个信号的高电平或低电平的持续时间是不相等的，且这两个信号的高电平的持续时间相加等于总的脉冲周期，其低电平持续时间相加也等于总的脉冲周期。这两个信号之间的关系是：在第一受控开关Q1的控制信号的占空比为D时，第二受控开关Q2的控制信号的占空比为1-D；且所述两个控制信号在其相邻位置分别提前或延迟一个设定宽度，形成设定宽度的死区以防止两个受控开关同时导通。请参见图3，图3中，TS是驱动信号的总的脉冲宽度，任何一个控制信号的脉冲宽度不能等于1/2，即两个控制信号不能对称。
总之，在图2中的DC/DC变换器电路中，Vin为输入侧直流电源；第一受控开关Q1和第二受控开关Q2(包含开关管的内部寄生二极管和寄生电感)组成半桥；串联谐振电感Lr、第一谐振电容Cs和第二谐振电容Cp组成LCC谐振网络；T1为高频变压器，其原边侧并联到第二谐振电容Cp的两端，其副边侧接倍流整流拓扑；倍流整流拓扑由快恢复二极管D1和D2、输出滤波电感Lf1和Lf2以及输出滤波电容Co组成；RL为负载。
在图2中，直流输入Vin接入由第一受控开关Q1和第二受控开关Q2组成的不对称半桥拓扑，PWM驱动信号控制两个受控开关管互补导通并留有一定的死区(请参见图3)避免直通，通过控制占空比调节功率，在第二受控开关Q2漏源极之间(图2中的A、B两点)产生方波电压，施加于LCC谐振网络，流过LCC谐振回路的电压或电流为正弦波或准正弦波，使第一受控开关Q1和第二受控开关Q2在零电压条件下导通。变压器一次侧(原边侧)正弦电压耦合到二次侧(副边侧)电压仍然为正弦电压，二次侧正弦电压通过倍流整流电路输出接负载RL，整流二极管D1和D2实现自然换流。该PWM驱动信号如图3所示。逆变单元施加于LCC谐振网络的方波电压VAB如图4所示。
值得一提的是，在本发明中，不对称或非对称是指两个驱动信号的脉冲宽度(即有效电平的宽度)是不相等的；而互补是指两个驱动信号的高电平部分相加(包括事先设置的、位于两个驱动信号电平转换位置处的死区或隔离区)等于驱动脉冲的总的宽度。
图2示出了本发明中一些情况下的逆变单元的结构，而在本发明中的另外一些情况下，上述逆变单元也可以由两个半桥构成。请参见图5，在图5中，除了逆变单元的结构及控制信号、方波输出端与图2不同之外，其余部件大致与图2相同。在图5中，逆变单元包括由第一受控开关Q1和第二受控开关Q2组成的第一半桥电路以及由第三受控开关Q3和第四受控开关Q4组成的第二半桥电路；直流输入的一端分别依次通过第一开关Q1和第三开关Q3的两个开关端以及第二开 关Q3和第四开关Q4的两个开关端连接到直流输入的另一端；换句话说，上述两个半桥并联在直流输入的两端；一个半桥电路中两个开关管分别由其控制端输入的、各自具有50％占空比且相位相差180度的脉冲宽度调制控制信号控制其开关；两个半桥电路组合在一起形成一个全桥电路，位于该全桥电路的拓扑对角线位置的两个受控开关管的控制信号之间具有设定的相位差或移相角，该设定的相位差决定所述逆变单元输出方波的脉冲宽度；调节这个相位差或移相角就能够调节该DC/DC变换器输出的直流电平。谐振单元由第一受控开关Q1和第二受控开关Q2的连接点以及第三受控开关Q3和第四受控开关Q4的连接点取得逆变单元输出的方波，请参见图5中的A、B两点。在图5中，在第一半桥电路和第二半桥电路中，一个半桥电路中两个受控开关的控制信号的脉冲宽度相等、相位相差180度，且该两个控制信号在其相邻位置分别提前或延迟一个设定宽度，形成设定宽度的死区以防止两个开关管同时导通；而在上述第一半桥电路和第二半桥电路所形成的组合的拓扑中，对角线位置的受控开关之间(例如，图5中的Q3和Q2之间或Q1和Q4之间)的控制信号之间相差一个设定的相位差，即存在一个移相角，通过调节该移相角来调节所述全桥逆变电路输出的脉冲宽度。关于图5中的驱动信号，请参见图6。
同样地，在图5中，Vin为输入侧直流电源；受控开关Q1～Q4(包含开关管的内部寄生二极管和寄生电感)组成移相的两个半桥，受控开关Q1和Q2为第一半桥，其驱动信号的相位超前于第二半桥；受控开关Q3和Q4为第二半桥，其驱动信号的相位滞后与上述第一半桥的驱动信号；谐振单元同样包括串联谐振电感Lr、第一谐振电容Cs和第二谐振电容Cp组成LCC谐振网络；T1为高频变压器，一次侧(原边)并联到第二谐振电容Cp的两端，二次侧(副边)接倍流整流拓扑；倍流整流拓扑由快恢复二极管D1和D2、输出滤波电感Lf1和Lf2以及输出滤波电容Co组成；RL为负载。值得一提的是，在本发明中，上述高频变压器的原边仅包括一个绕组，而其副边则可以包括一个以上的绕组。
在图5中，通过移相PWM控制受控开关Q1-Q4，在图5中的A、B两点间产生正负交替脉冲方波(请参见图7)，施加于LCC谐振网络，流过LCC谐振回路的电压或电流为正弦波或准正弦波，使受控开关Q1-Q4在零电压或零电流条件下导通和关断。变压器一次侧正弦电压耦合到副边侧电压仍然为正弦波形，二次侧正弦电压通过倍流整流电路输出接负载RL，整流二极管D1和D2实现自然换流。如图6所示，PWM1～PWM4为功率开关管Q1-Q4的驱动信号，各半桥内的受控开关的PWM驱动信号互补导通并留有一定的死区避免直通；对角线位置上的开关管PWM驱动信号间存在移相角，通过控制移相角进行功率调整。施加于LCC谐振网络的方波电压VAB如图7所示。整流二极管D1和D2的电压波形VD1和VD1如图8所示。
如上所述，在本发明中，在图2和图5中示出的两种情况中的任何一种中，其谐振单元均包括谐振电感Lr、第一谐振电容Cs和第二谐振电容Cp，其中，(串联)谐振电感Lr和第一谐振电容Cs串联后与高频变压器原边串接在逆变单元输出方波的两个端子上，第二谐振电容Cp并接在所述高频变压器的原边或副边上。关于第二谐振电容连接在高频变压器副边上的例子，请参见图9和图10；其中，图9是逆变单元为半桥电路时，第二谐振电容连接在高频变压副边的电路(此时，第二谐振电容不仅包括了Cp’，还包括了整流器件的寄生电容)；而图10是逆变单元为全桥电路时，第二谐振电容连接在高频变压副边的电路(此时，第二谐振电容同样包括了整流器件的寄生电容)。
此外，在发明中，整流滤波单元包括一个开关端分别连接在所述高频变压器副边两端，另一个开关端连接在公共电位端上的两个整流开关，两个整流开关与高频变压器副边两端连接的开关端并接在一起作为所述整流滤波单元的直流输出的正输出端；整流滤波单元的直流负输出端是所述公共电位端；其中，整流开关包括其阴极与高频变压器副边连接的二极管(请参见图2、图5、图9和图10)或MOS管(请参见图13和图14)。
在本发明中的另外一些情况下，上述整流滤波单元也可以是其输入端是所述高频变压器副边两端的桥式整流电路，桥式整流电路的整流滤波单元包括二极管(请参见图15)或受控的MOS管(请参见图16)。上述整流滤波单元还可以是全波整流电路，全波整流电路的整流滤波单元包括二极管(请参见图17和图19)或受控的MOS管(请参见图18和图20)。
在上述任何一种情况中，整流滤波单元还包括滤波模块，滤波模块包括滤波电感(Lf1、Lf2)和滤波电容Co；其中，滤波电感(Lf1、Lf2)串接在直流正输出端和整流二极管负端之间或桥式整流的正输出端上，滤波电容Co并接在直流正输出端和负输出端之间。值得一提的是，在桥式整流中，上述两个滤波电感也可以合并为一个。
图11到图20示出了本发明中整流滤波单元的衍生电路，也就是说，在本发明的任何一种情况下，整流滤波单元都可以采用图11到图20中的任何一种形式。对图11到图20的简要描述如下：倍流整流电路有两种形式，图2、图5、图9、图10、图12和图13是其中一种电路形式，图11和图14是另一种电路形式；图2、图5、图9、图10、图11和图12采用二极管整流，图13和图14采用同步整流；图15是采用二极管整流的全桥整流电路，图16是采用同步整流的全桥整流电路；图17和图19是采用二极管整流的全波整流电路，图18和图20是采用同步整流的全波整流电路。
此外，图21和图22分别给出了本发明中整流滤波单元中的LC电路可能存在的两种变形结构。在图21中，将通常与滤波电容串联的一个电感拆分为两个，并分别串联在滤波电容两端的回路中；而图22中，将原先分别是一个的电感和电容，分别拆分为两个，每个电感和电容之间还是串联的方式连接，这样得到两节单独的LC滤波电路，第一节LC滤波电路连接在直流输出的输出端和地之间，第二节LC滤波电路并接在第一节LC滤波电路的滤波电容两端，而负载并接在第二节LC滤波电路的滤波电容两端。这样将电感或电容拆分的好 处是可以减小单个元件的电感值或电容值，从而减小单个元件的体积，能够适应对空间或成本敏感的场合。
值得一提的是，在本发明中，上述各种情况下组成DC/DC变换器的各个单元，包括逆变单元、整流滤波单元、谐振单元以及整流滤波单元，并不仅仅局限于上述说明。本领域技术人员还可以依据本领域的公知常识对上述各单元的构成或各单元之间的连接进行合理的组合、变换或修改。
以上所述实施例仅表达了本发明的几种实施方式，其描述较为具体和详细，但并不能因此而理解为对本发明专利范围的限制。应当指出的是，对于本领域的普通技术人员来说，在不脱离本发明构思的前提下，还可以做出若干变形和改进，这些都属于本发明的保护范围。因此，本发明专利的保护范围应以所附权利要求为准。

Claims (9)

  1. 一种DC/DC转换器，其特征在于，包括逆变单元、谐振单元、高频变压器和整流滤波单元；所述逆变单元包括半桥电路在不对称、互补的脉冲宽度调制的控制信号作用下或全桥电路在恒频移相控制下，将直流输入转换为方波；所述谐振单元由所述逆变单元取得其输出的方波并使其谐振，并将其传输到所述高频变压器原边；所述整流滤波单元采用倍流整流、全波整流或全桥整流并通过LC滤波将所述高频变压器的副边上的交流波形转换为直流输出。
  2. 根据权利要求1所述的DC/DC转换器，其特征在于，所述逆变单元包括由第一受控开关管和第二受控开关管组成的半桥电路，直流输入的一端依次通过第一开关管的两个开关端和第二开关管的两个开关端连接到直流输入的另一端；所述两个开关管分别由其控制端输入的、不对称的、互补的脉冲宽度调制信号控制其开关；所述第一开关管的控制端上的控制信号的脉冲宽度决定所述逆变单元输出方波的脉冲宽度；所述谐振单元由所述第一开关管和第二开关管的连接点以及所述直流输入一端或另一端取得所述逆变单元输出的方波。
  3. 根据权利要求2所述的DC/DC转换器，其特征在于，所述第一开关管和第二开关管控制端输入的控制信号的周期为设定长度，在所述第一受控开关的控制信号的占空比为D时，所述第二受控开关的控制信号的占空比为1-D；所述两个控制信号在其相邻的高低电平转换位置分别提前或延迟一个设定宽度，形成设定宽度的死区以防止所述两个开关管同时导通。
  4. 根据权利要求1所述的DC/DC转换器，其特征在于，所述逆变单元包括采用恒频移相控制的全桥逆变电路；所述全桥逆变电路包括由第一受控开关管和第二受控开关管组成的第一半桥电路以及由第三受控开关管和第四受控开关管组成的第二半桥电路；直流输入的一端依次通过第一开关管和第二开关管的两个开关端连接到直流输入的另一端；直流输入的一端还依次第三开关管和第四开关管的两个 开关端连接到直流输入的另一端；一个半桥电路中两个开关管分别由其控制端输入的、各自具有50％占空比且相位相差180度的脉冲调宽调制信号控制其开关；所述两个半桥电路中位于其拓扑对角线位置的两个受控开关管的控制信号之间具有设定的相位差或移相角，所述设定的相位差决定所述逆变单元输出方波的脉冲宽度；所述谐振单元由所述第一开关管和第二开关管的连接点以及所述第三开关管和第四开关管的连接点取得所述逆变单元输出的方波。
  5. 根据权利要求4所述的DC/DC转换器，其特征在于，在所述第一半桥电路和第二半桥电路中，一个半桥电路中两个受控开关的控制信号的脉冲宽度相等、各自具有50％占空比且相位相差180度，且所述两个控制信号在其相邻的高低电平转换位置分别提前或延迟一个设定宽度，形成设定宽度的死区以防止所述两个开关管同时导通。
  6. 根据权利要求1所述的DC/DC转换器，其特征在于，所述谐振单元包括谐振电感、第一谐振电容和第二谐振电容，所述谐振电感和第一谐振电容串联后与所述高频变压器原边串接在所述逆变单元输出方波的两个端子上，所述第二谐振电容并接在所述高频变压器的原边或副边上或为所述原、副边并接电容之和；所述谐振电感为独立电感或变压器之漏感或所述两者之和；所述第二谐振电容为独立电容或整流开关管寄生电容或所述两者的并联的等效电容。
  7. 根据权利要求1所述的DC/DC转换器，其特征在于，所述高频变压器原边为一个绕组，副边为一个或一个以上绕组。
  8. 根据权利要求7所述的DC/DC转换器，其特征在于，所述整流滤波电路包括整流部分和滤波部分；所述整流部分包括整流器件，在倍流整流时，所述整流器件为采用共阳极或共阴极倍流整流电路的二极管或为采用同步整流电路的MOSFET；其滤波部分为LC组合滤波电路。
  9. 根据权利要求7所述的DC/DC转换器，其特征在于，所述整流滤波电路包括整流部分和滤波部分；所述整流部分包括整流器件， 在全波整流时，所述整流器件为采用共阳极或共阴极整流电路的二极管；其滤波部分为LC组合滤波电路。
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