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WO2005094352A2 - Antenne multifaisceau - Google Patents

Antenne multifaisceau Download PDF

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Publication number
WO2005094352A2
WO2005094352A2 PCT/US2005/010596 US2005010596W WO2005094352A2 WO 2005094352 A2 WO2005094352 A2 WO 2005094352A2 US 2005010596 W US2005010596 W US 2005010596W WO 2005094352 A2 WO2005094352 A2 WO 2005094352A2
Authority
WO
WIPO (PCT)
Prior art keywords
antenna
dielectric substrate
recited
beam antenna
edge
Prior art date
Application number
PCT/US2005/010596
Other languages
English (en)
Other versions
WO2005094352A3 (fr
Inventor
Gabriel M. Rebeiz
James P. Ebling
Bernhard Schoenlinner
Original Assignee
Automotive Systems Laboratory, Inc.
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Automotive Systems Laboratory, Inc. filed Critical Automotive Systems Laboratory, Inc.
Priority to EP05730876A priority Critical patent/EP1738432A4/fr
Priority to JP2007505280A priority patent/JP2008503904A/ja
Publication of WO2005094352A2 publication Critical patent/WO2005094352A2/fr
Publication of WO2005094352A3 publication Critical patent/WO2005094352A3/fr

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Classifications

    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q13/00—Waveguide horns or mouths; Slot antennas; Leaky-waveguide antennas; Equivalent structures causing radiation along the transmission path of a guided wave
    • H01Q13/08—Radiating ends of two-conductor microwave transmission lines, e.g. of coaxial lines, of microstrip lines
    • H01Q13/085—Slot-line radiating ends
    • H—ELECTRICITY
    • H01—ELECTRIC ELEMENTS
    • H01Q—ANTENNAS, i.e. RADIO AERIALS
    • H01Q21/00—Antenna arrays or systems
    • H01Q21/06—Arrays of individually energised antenna units similarly polarised and spaced apart
    • H01Q21/20—Arrays of individually energised antenna units similarly polarised and spaced apart the units being spaced along or adjacent to a curvilinear path

Definitions

  • FIG. 1 illustrates a top plan view of a first embodiment of a multi-beam antenna
  • FIG. 2 illustrates a side cross-sectional view of the embodiment of FIG. 1
  • FIG. 3 illustrates a top plan view of an embodiment of a multi-beam antenna
  • FIGS. 4a-4f illustrate various embodiments of tapered slot antenna elements
  • FIG. 5 illustrates a tapered slot antenna element and an associated coordinate system
  • FIG. 6 illustrates a junction where a microstrip line is adapted to couple to a slotline feeding a tapered slot antenna
  • FIG. 7 illustrates a bottom view of the embodiment of the multi-beam antenna illustrated in FIG. 3 interfaced to an associated feed network
  • FIG. 1 illustrates a top plan view of a first embodiment of a multi-beam antenna
  • FIG. 2 illustrates a side cross-sectional view of the embodiment of FIG. 1
  • FIG. 3 illustrates a top plan view of an embodiment of a multi-beam antenna
  • FIGS. 4a-4f illustrate various
  • FIG. 8 illustrates a bottom view of the embodiment of the multi-beam antenna illustrated in FIG. 3 with associated receiver circuitry
  • FIG. 9 illustrates a detailed view of the receiver circuitry for the embodiment illustrated in FIG. 8
  • FIG. 10 illustrates an antenna gain pattern for the multi-beam antenna illustrated in FIGS. 3 and 8
  • FIG. 11a illustrates an isometric view of an embodiment of a multi-beam antenna incorporating a bi-conical reflector
  • FIG. lib illustrates a cross-sectional view of the embodiment of a multi-beam antenna illustrated in FIG. 11a incorporating a bi-conical reflector
  • FIG. 12a illustrates a top plan view of an embodiment of a multi-beam antenna incorporating a conformal cylindrical dielectric lens
  • FIG. 11a illustrates an isometric view of an embodiment of a multi-beam antenna incorporating a bi-conical reflector
  • FIG. lib illustrates a cross-sectional view of the embodiment of a multi-beam antenna illustrated in FIG. 11
  • FIG. 12b illustrates a cross-sectional view of the embodiment of a multi-beam antenna illustrated in FIG. 12a incorporating a circular cylindrical lens
  • FIG. 13a illustrates a top plan view of an embodiment of a multi-beam antenna incorporating a planar lens
  • FIG. 13b illustrates a cross-sectional view of the embodiment of a multi-beam antenna illustrated in FIG. 13a incorporating a planar lens
  • FIG. 14 illustrates a first side of a planar discrete lens array
  • FIG. 15 illustrates a block diagram of a discrete lens array
  • FIG. 16 illustrates a plot of delay as a function of transverse location on the planar discrete array of FIG. 15;
  • FIG. 17 illustrates a fragmentary cross sectional isometric view of an embodiment of a discrete lens antenna element
  • FIG. 18 illustrates an isometric view of the discrete lens antenna element illustrated in FIG. 17, isolated from associated dielectric substrates
  • FIG. 19a illustrates a top plan view of an embodiment of a multi-beam antenna incorporating a dipole antenna adapted to cooperate with an associated corner reflector
  • FIG. 19b illustrates a cross-sectional view of the embodiment of a multi-beam antenna illustrated in FIG. 19a incorporating a dipole antenna and an associated corner reflector
  • FIGS. 20a and 20b illustrate a Yagi-Uda antenna element with a first embodiment of an associated feed circuit
  • FIG. 21 illustrates the operation of the Yagi-Uda antenna element illustrated in FIGS. 20a and 20b in cooperation with a dielectric lens having a circular profile
  • FIG. 22 illustrates a Yagi-Uda antenna element with a second embodiment of an associated feed circuit
  • FIG. 23 illustrates an embodiment of a mulit-beam antenna incorporating a plurality of Yagi-Uda antenna elements on a concave edge of a dielectric substrate
  • FIG. 24 illustrates an embodiment of a mulit-beam antenna incorporating a plurality of Yagi-Uda antenna elements on a concave edge of a dielectric substrate, in cooperation with an at least partially spherical dielectric lens
  • FIG. 25a and 25b illustrate an embodiment of a mulit-beam antenna incorporating a plurality of endfire antenna elements on a concave edge of a dielectric substrate, in cooperation with an associated bi-conical reflector;
  • FIG. 26 illustrates a circular multi-beam antenna;
  • FIGS. 27a and 27b illustrate a first non-planar embodiment of a multi-beam antenna;
  • FIGS. 28a and 28b illustrate a second non-planar embodiment of a multi-beam antenna.
  • a multi-beam antenna 10 comprises a dielectric substrate 12 having a convex profile 14 — e.g. circular, semi -circular, quasi-circular, elliptical, or some other profile shape as may be required — with a plurality of endfire antenna elements 16 etched into a first conductive layer 18.1 on the first side 20.1 of the dielectric substrate 12.
  • a convex profile 14 e.g. circular, semi -circular, quasi-circular, elliptical, or some other profile shape as may be required — with a plurality of endfire antenna elements 16 etched into a first conductive layer 18.1 on the first side 20.1 of the dielectric substrate 12.
  • the plurality of endfire antenna elements 16 are adapted to radiate a corresponding plurality of beams of electromagnetic energy 21 radially outwards from the convex profile 14 of the dielectric substrate 12, or to receive a corresponding plurality of beams of electromagnetic energy 21 propagating towards the convex profile 14 of the dielectric substrate 12.
  • the endfire antenna elements 16 are illustrated as abutting the convex profile 14.
  • the dielectric substrate 12 is, for example, a material with relatively low loss at an operating frequency, for example, DUROID ® , a TEFLON ® containing material, a ceramic material, or a composite material such as an epoxy/fiberglass composite.
  • the dielectric substrate 12 comprises a dielectric 12.1 of a circuit board 22, for example, a printed or flexible circuit 22.1 comprising at least one conductive layer 18 adhered to the dielectric substrate 12, from which the endfire antenna elements 16 and other associated circuit traces 24 are formed, for example, by subtractive technology, for example, chemical or ion etching, or stamping; or additive techniques, for example, deposition, bonding or lamination.
  • the multi-beam antenna 10 illustrated in FIGS. 3, 7 and 8 was fabricated on an RT/DUROID ® 5880 substrate with a copper layer of 17 micrometers thickness on either side with a fabrication process using a one-mask process with one lithography step.
  • An endfire antenna element 16 may, for example, comprise either a Yagi-Uda antenna, a coplanar horn antenna (also known as a tapered slot antenna), a Vivaldi antenna, a tapered dielectric rod, a slot antenna, a dipole antenna, or a helical antenna, each of which is capable of being formed on the dielectric substrate 12, for example, from a printed or flexible circuit 22.1, for example, by subtractive technology, for example, chemical or ion etching, or stamping; or additive techniques, for example, deposition, bonding or lamination.
  • the endfire antenna element 16 could also comprise a monopole antenna, for example, a monopole antenna element oriented either in-plane or out-of-plane with respect to the dielectric substrate 12. Furthermore, the endfire antenna elements 16 may be used for transmitting, receiving or both. For example, the embodiments illustrated in FIGS. 1 and 3 incorporate tapered-slot antennas 16.1 as the associated endfire antenna elements 16. The tapered-slot antenna
  • 16.1 is a surface-wave traveling-wave antenna, which generally allows wider band operation in comparison with resonant structures, such as dipole or Yagi-Uda antennas.
  • the directivity of a traveling-wave antenna depends mostly upon length and relatively little on its aperture.
  • the aperture is typically larger than a half free space wavelength to provide for proper radiation and low reflection.
  • the input impedance becomes mismatched with respect to that of an associated slotline feed and considerable reflections may occur. Longer antennas generally provide for increased directivity. Traveling-wave antennas generally are substantially less susceptible to mutual coupling than resonant antennas, which makes it possible to place them in close proximity to each other without substantially disturbing the radiation pattern of the associated multi- beam antenna 10.
  • the tapered-slot antenna 16.1 comprises a slot in a conductive ground plane supported by a dielectric substrate 12.
  • the width of the slot increases gradually in a certain fashion from the location of the feed to the location of interface with free space. As the width of the slot increases, the characteristic impedance increases as well, thus providing a smooth transition to the free space characteristic impedance of 120 times pi Ohms.
  • FTSA Fermi tapered slot antenna
  • LTSA linearly tapered slot antenna
  • Nivaldi exponentially tapered slot antenna Nivaldi exponentially tapered slot antenna
  • the tapered-slot antenna 16.1 exhibits an E-field polarization that is in the plane of the tapered-slot antenna 16.1.
  • These different types of tapered-slot antennas 16.1 exhibit corresponding different radiation patterns, also depending on the length and aperture of the slot and the supporting substrate. Generally, for the same substrate with the same length and aperture, the beamwidth is smallest for the CWSA, followed by the LTSA, and then the Nivaldi.
  • the sidelobes are highest for the CWSA, followed by the LTSA, and then the Nivaldi.
  • the Nivaldi has theoretically the largest bandwidth due to its exponential structure.
  • the BLTSA exhibits a wider -3 dB beamwidth than the LTSA and the cross-polarization in the D-plane (diagonal plane) is about 2 dB lower compared to LTSA and CWSA.
  • the DETSA has a smaller -3 dB beamwidth than the Nivaldi, but the sidelobe level is higher, although for higher frequency, the sidelobes can be suppressed.
  • the DETSA gives an additional degree of freedom in design especially with regard to parasitic effects due to packaging.
  • the FTSA exhibits very low and the most symmetrical sidelobe level in E and H-plane and the - 3 dB beamwidth is larger than the BLTSA.
  • the multi-beam antenna 10 may further comprise at least one transmission line 26 on the dielectric substrate 12 operatively connected to a corresponding at least one feed port 28 of a corresponding at least one of the plurality of endfire antenna elements 16 for feeding a signal thereto or receiving a signal therefrom.
  • the at least one transmission line 26 may comprise either a stripline, a microstrip line, an inverted microstrip line, a slotline, an image line, an insulated image line, a tapped image line, a coplanar stripline, or a coplanar waveguide line formed on the dielectric substrate 12, for example, of a printed or flexible circuit 22.1, for example, by subtractive technology, for example, chemical or ion etching, or stamping; or additive techniques, for example, deposition, bonding or lamination.
  • the slotlines 30 are terminated with at a terminus 32 on the first side 20.1 of the dielectric substrate 12, proximate to which the slotlines 30 is electromagnetically coupled at a coupling location 33 to a microstrip line 34 on the opposite or second side 20.2 of the dielectric substrate 12, wherein the first conductive layer 18.1 on the first side 20.1 of the dielectric substrate 12 constitutes an associated conductive ground layer 38 of the microstrip line 34, and the conductor 40 of the microstrip line 34 is formed from a second conductive layer 18.2 on the second side 20.2 of the dielectric substrate 12. Referring to FIGS.
  • a transition between the microstrip line 34 and the slotline 30 is formed by etching the slotline 30 into the conductive ground layer 38 of the microstrip line 34 and is crossed by the conductor 40 of the microstrip line 34 oriented substantially perpendicular to the axis of the slotline 30, as is illustrated in detail in FIG. 6.
  • a transition distance of about one wavelength provides matching the 50 Ohm impedance of the microstrip line 34 to the 100 Ohm impedance of the slotline 30.
  • the coupling of the fields between the microstrip line 34 and slotline 30 occurs through an associated magnetic field, and is strongest when the intersection of the conductor 40 and slotline 30 occurs proximate to a short circuit of the microstrip line 34 — where the current therein is a maximum ⁇ and an open circuit of the slotline 30. Because short circuits in a microstrip line 34 require via holes, it is easier to terminate the microstrip line 34 in an open circuit a quarter guided wavelength from the transition intersection, where quarter guided wavelength is that of the microstrip line 34. A quarter-wave radial stub 41 can provide for relatively wider bandwidth. An open circuit in the slotline 30 is created by truncating the conductive ground layer 38, which is generally impractical.
  • the slotline 30 is terminated with a short circuit and recessed from the intersection by a quarter guided wavelength of the slotline 30.
  • the bandwidth can be increased by realizing the quarter- wave termination in a circular disc aperture 42, which is an approximation of an open circuit of a slotline 30.
  • the open-circuit behavior improves with increasing radius of the circular disc aperture 42.
  • the circular disc aperture 42 behaves like a resonator.
  • the circular disc aperture 42 is capacitive in nature, and behaves as an open circuit provided that the operating frequency is higher than the resonance frequency of the circular disc aperture 42 resonator.
  • the multi-beam antenna 10 may further comprise a switching network 44 having at least one first port 46 and a plurality of second ports 48, wherein the at least one first port 46 is operatively connected — for example, via at least one above described transmission line 26 — to a corporate antenna feed port 50, and each second port 48 of the plurality of second ports 48 is connected ⁇ for example, via at least one transmission line 26 — to a respective feed port 28 of a different endfire antenna element 16 of the plurality of endfire antenna elements 16.
  • the switching network 44 further comprises at least one control port 52 for controlling which second ports 48 are connected to the at least one first port 46 at a given time.
  • the switching network 44 may, for example, comprise either a plurality of micro-mechanical switches, PIN diode switches, transistor switches, or a combination thereof, and may, for example, be operatively connected to the dielectric substrate 12, for example, by surface mount to an associated conductive layer 18 of a printed or flexible circuit 22.1, inboard of the endfire antenna elements 16.
  • the switching network 44 may be located proximate to the center 53 of the radius R of curvature of the dielectric substrate 12 so as to be proximate to the associated coupling locations 33 of the associated microstrip lines 34.
  • the switching network 48 if used, need not be collocated on a common dielectric substrate 16, but can be separately located, as, for example, may be useful for relatively lower frequency applications, for example, 1- 20 GHz.
  • a feed signal 54 applied to the corporate antenna feed port 50 is either blocked — for example, by an open circuit, by reflection or by absorption, — or switched to the associated feed port 28 of one or more endfire antenna elements 16, via one or more associated transmission lines 44, by the switching network 44, responsive to a control signal 60 applied to the control port 52.
  • the feed signal 54 may either comprise a single signal common to each endfire antenna element 16, or a plurality of signals associated with different endfire antenna elements 16.
  • Each endfire antenna element 16 to which the feed signal 54 is applied launches an associated electromagnetic wave into space.
  • the associated beams of electromagnetic energy 21 launched by different endfire antenna elements 16 propagate in different associated directions 58.
  • the various beams of electromagnetic energy 21 may be generated individually at different times so as to provide for a scanned beam of electromagnetic energy 21. Alternatively, two or more beams of electromagnetic energy 21 may be generated simultaneously.
  • different endfire antenna elements 16 may be driven by different frequencies that, for example, are either directly switched to the respective endfire antenna elements 16, or switched via an associated switching network 44 having a plurality of first ports 46, at least some of which are each connected to different feed signals 54.
  • the multi-beam antenna 10 may be adapted so that the respective signals are associated with the respective endfire antenna elements 16 in a one-to-one relationship, thereby precluding the need for an associated switching network 44.
  • each endfire antenna element 16 can be operatively connected to an associated signal through an associated processing element.
  • the respective endfire antenna elements 16 are used to receive electromagnetic energy, and the corresponding processing elements comprise detectors.
  • the respective endfire antenna elements 16 are used to both transmit and receive electromagnetic energy, and the respective processing elements comprise transmit/receive modules or transceivers. For example, referring to FIGS.
  • a multi-beam antenna 10 is adapted with a plurality of detectors 60 for detecting signals received by associated endfire antenna elements 16 of the multi-beam antenna 10, for example, to provide for making associated radiation pattern measurements.
  • Each detector 60 comprises a planar silicon Schottky diode 60.1 mounted with an electrically conductive epoxy across a gap 62 in the microstrip line 34. For higher sensitivity, the diode 60.1 is DC-biased. Two quarter wavelength-stub filters 63 provide for maximizing the current at the location of the diode 60.1 detector 60 while preventing leakage into the DC-path.
  • FIG. 10 illustrates an E-plane radiation pattern for the multi-beam antenna 10 illustrated in FIGS. 3 and 8, configured as a receiving antenna.
  • the tapered-slot endfire antenna elements 16.1 provide for relatively narrow individual E-plane beam widths, but inherently exhibit relatively wider H-plane beam widths, of the associated beams of electromagnetic energy 21.
  • the H-plane beam width may be reduced, and the directivity of the multi-beam antenna 10 may be increased, by sandwiching the above-described multi- beam antenna 10 within a bi-conical reflector 64, so as to provide for a horn-like antenna in the H-plane.
  • the opening angle between the opposing faces 65 of the bi-conic reflector is about 50 degrees and the lateral dimensions coincide with that of the dielectric substrate 12.
  • the measured radiation patterns in E-plane of this embodiment exhibited a -3 dB beamwidth of 26 degrees and the cross-over of adjacent beams occurs at the -2.5 dB level.
  • the sidelobe level was about -6 dB, and compared to the array without a reflector, the depth of the nulls between main beam and sidelobes was substantially increased.
  • the —3 and —10 dB beamwidths were 35 degrees and 68 degrees respectively, respectively, and the sidelobe level was below -20 dB.
  • the presence of the bi- conical reflector 64 increased the measured gain by 10 percent. Although the improvement in gain is relatively small, e.g.
  • the bi-conical reflector 64 is beneficial to the H-plane radiation pattern.
  • the H-plane beam width may be reduced, and the directivity of the multi- beam antenna 10 may be increased, by using a conformal cylindrical dielectric lens 66 which is bent along its cylindrical axis so as to conform to the convex profile 14 of the dielectric substrate 12, so as to provide for focusing in the H-plane without substantially affecting the E-plane radiation pattern.
  • the conformal cylindrical dielectric lens 66 could be constructed from either RexoliteTM, TeflonTM, polyethylene, or polystyrene; or a plurality of different materials having different refractive indices.
  • the conformal cylindrical dielectric lens 66 could have a piano-cylindrical cross-section, rather than the circular cross-section as illustrated in FIG. 12b.
  • the conformal cylindrical dielectric lens 66 may be adapted to also act as a radome so as to provide for protecting the multi-beam antenna 10.2 from the adverse environmental elements (e.g. rain or snow) and factors, or contamination (e.g. dirt). Referring to FIGS.
  • the H-plane beam width may be reduced, and the directivity of the multi- beam antenna 10 may be increased, by using a planar lens 68, the planar surface of which is oriented normal to the dielectric substrate 12 and — in a direction normal to the surface of the planar surface ⁇ is adapted to conform to the convex profile 14 of the dielectric substrate 12.
  • the planar lens 68 would comprise a plurality of first patch antennas 70.1 on one side of an associated dielectric substrate 72 of the planar lens 68 that are connected via associated delay elements 74, e.g.
  • the delay lines 76 can be constructed by forming meandering paths of appropriate length using printed circuit technology.
  • a cylindrical lens array is described by D. Popovic and Z. Popovic in "Mutlibeam Antennas with Polarization and Angle Diversity", IEEE Transactions on Antennas and Propagation, Vol. 50, No. 5, May 2002, which is incorporated herein by reference.
  • the patch antennas 70.1, 70.2 comprise conductive surfaces on the dielectric substrate 72
  • the delay element 76 coupling the patch antennas 70.1, 70.2 of the first 80 and second 82 sides of the planar lens 68 comprise delay lines 76, e.g. microstrip or stipline structures, that are located adjacent to the associated patch antennas 70.1, 70.2 on the underlying dielectric substrate 72.
  • the first ends 84.1 of the delay lines 76 are connected to the corresponding patch antennas 70.1, 70.2, and the second ends 84.2 of the delay lines 76 are interconnected to one another with a conductive path, for example, with a conductive via 86 though the dielectric substrate 72.
  • FIG. 14 illustrates the delay lines 76 arranged so as to provide for feeding the associated first 70.1 and second 70.2 sets of patch antennas at the same relative locations. Referring to Fig. 15, each patch antenna 70.1 on the first side 80 of the planar lens
  • a signal responsive thereto is coupled via ⁇ and delayed by — the delay line 76 to the corresponding patch antenna 70.2, 70.1, e.g. the second patch antenna 70.2, wherein the amount of delay by the delay line 76 is dependent upon the location of the corresponding patch antennas 70.1, 70.2 on the respective first 80 and second 82 sides of the planar lens 68.
  • the signal coupled to the second patch antenna 70.2 is then radiated thereby from the second side 82 of the planar lens 68.
  • the planar lens 68 comprises a plurality of lens elements 88, wherein each lens element 88 comprises a first patch antenna element 70.1 operatively coupled to a corresponding second patch antenna element 70.2 via at least one delay line 76, wherein the first 70.1 and second 70.2 patch antenna elements are substantially opposed to one another on opposite sides of the planar lens 68.
  • the amount of delay caused by the associated delay lines 76 is made dependent upon the location of the associated patch antenna 102 in the planar lens 68, and, for example, is set by the length of the associated delay lines 76, as illustrated by the configuration illustrated in FIG. 14, so as to emulate the phase properties of a convex electromagnetic lens 12, e.g. a conformal cylindrical dielectric lens 66.
  • the shape of the delay profile illustrated in FIG. 16 can be of various configurations, for example, 1) uniform for all radial directions, thereby emulating a spherical lens; 2) adapted to incorporate an azimuthal dependence, e.g. so as to emulate an elliptical lens; 3) adapted to provide for focusing in one direction only, e.g. in the elevation plane of the multi-beam antenna 10.6, e.g. so as to emulate a conformal cylindrical dielectric lens 66, or 4) adapted to direct the associated radiation pattern either above or below the plane of the associated multi-beam antenna 10.3, e.g. so as to mitigate against reflections from the ground, i.e. clutter.
  • a lens element 88 of the planar lens 68 illustrated in FIG. 14 comprises first 70.1 and second 70.2 patch antenna elements on the outer surfaces of a core assembly 90 comprising first 72.1 and second 72.2 dielectric substrates surrounding a conductive ground plane 92 sandwiched therebetween.
  • the combination of the first 76.1 and second 76.2 delay lines interconnected by the conductive via 86 constitutes the associated delay line 76 of the lens element 88, and the amount of delay of the delay line 76 is generally responsive to the cumulative circumferential lengths of the associated first 76.1 and second 76.2 delay lines.
  • the dielectric substrate 12 with a plurality of associated endfire antenna elements 16 is combined with associated out-of-plane reflectors 96 above and below the dielectric substrate 12, in addition to any that are etched into the dielectric substrate 12 itself, so as to provide for improved the radiation patterns of the etched endfire antenna elements 16.
  • a dipole antenna 16.2 and an associated reflector portion 98 can be etched in at least one conductive layer 18 of the dielectric substrate 12.
  • a Yagi-Uda element could used instead of the dipole antenna 16.2.
  • the etched reflector portion 98 can also be extended away from the dielectric substrate 12 to form a planar corner reflector 100 , e.g. by attaching relatively thin conductive plates 102 to the associated first 18.1 and second 18.2 conductive layers, e.g. using solder or conductive epoxy. For example, this would be similar to the metallic enclosures currently used to limit electromagnetic emissions and susceptibility on circuit boards.
  • the reflectors 96 could also be made of solid pieces that span across all of the endfire antenna elements 16 on the dielectric substrate 12 with a common shape, such as for the bi-conical reflector 64 described hereinabove. Referring to FIGS.
  • a Yagi-Uda antenna 16.3 may be used as an endfire antenna element 16 of a multi-beam antenna 10, as described in "A 24-GHz High-Gain Yagi-Uda Antenna Array" by P.R. Grajek, B. Schoenlinner and G.M. Rebeiz in Transactions on Antennas and Propagation, May, 2004, which is incorporated herein by reference.
  • a Yagi-Uda antenna 16.3 incorporates a dipole element 104, two forward director elements 106 on the first side 20.1 of the dielectric substrate 12 - e.g.
  • the dimensions are then scaled to compensate for the affects of the DUROID ® substrate, e.g.
  • the feed gap S was limited to a width of 0.15 mm due to the resolution of the etching process.
  • the Yagi- Uda antenna 16.3 is fed with a microstrip line 34 coupled to a coplanar stripline 112 coupled to the Yagi-Uda antenna 16.3.
  • a new quasi-yagi antenna for planar active antenna arrays by W. R. Deal, N. Kaneda, J. Sor, Y. Qian and T. Itoh in IEEE Trans. Microwave Theory Tech., Vol. 48, No. 6, pp.
  • the transition between the microstrip line 34 and the coplanar stripline 112 is provided by splitting the primary microstrip line 34 into two separate coplanar stripline 112, one of which incorporates a balun 114 comprising a meanderline 116 of sufficient length to cause a 180 degree phase shift, so as to provide for exciting a quasi-TEM mode along the balanced coplanar striplines 112 connected to the dipole element 104.
  • a quarter-wave transformer section 118 between the microstrip line 34 and the coplanar striplines 112 provides for matching the impedance of the coplanar stripline 112 / Yagi-Uda antenna 16.3 to that of the microstrip line 34.
  • the input impedance is affected by the gap spacing Sm of the measnerline 116 through mutual coupling in the balun 114, and by the proximity S T of the meanderline 116 to the edge 120 of the associated ground plane 122, wherein fringing effects can occur if the meanderline 116 of the is too close to the edge 120.
  • the directivity of a Yagi-Uda antenna 16.3 can be substantially increased with an associated dielectric lens 124, for example, a dielectric lens 124 with a circular shape, e.g.
  • the Yagi-Uda antenna 16.3 is used as a receiving antenna in cooperation with a second embodiment of an associated feed circuit 128, wherein a detector 60 is operatively coupled across the coplanar striplines 112 from the associated dipole element 104, and ⁇ g/4 open-stubs 130 are operatively coupled to each coplanar stripline 112 at a distance of ⁇ g/4 from the detector 60, which provides for an an RF open circuit at the detector 60, and which provides for a detected signal at nodes 132 operatively coupled to the associated coplanar striplines 112 beyond the ⁇ g/4 open-stubs 130.
  • a multi-beam antenna 10.5 comprises a dielectric substrate 12 having a concave profile 134 — e.g. circular, semicircular, quasi-circular, elliptical, or some other profile shape as may be required — with a plurality of endfire antenna elements 16, for example, Yagi-Uda antennas 16.3 constructed in accordance with the embodiment illustrated in FIGS. 20a and 20b, with a second embodiment of the feed circuit 128 as illustrated in FIG. 22, so as to provide for receiving beams of electromagnetic energy 21 from a plurality of associated different directions corresponding to the different azimuthal directions of the associated endfire antenna elements 16 arranged along the edge 136 of the concave profile 134.
  • a concave profile 134 e.g. circular, semicircular, quasi-circular, elliptical, or some other profile shape as may be required — with a plurality of endfire antenna elements 16, for example, Yagi-Uda antennas 16.3 constructed in accordance with the embodiment illustrated in FIGS.
  • the embodiment of the multi-beam antenna 10.5 illustrated in FIG. 23 comprises an 11 - element array of Yagi-Uda antennas 16.3 that are evenly spaced with an angular separation of 18.7 degrees so as to provide for an associated -6 dB beam cross-over.
  • the multi-beam antenna 10.5 of the sixth aspect for example, as illustrated in FIG.
  • the multi-beam antenna 10.5 of the sixth aspect is adapted to cooperate with a concave bi-conical reflector 140, so as to provide for reducing the associated beam width in the H-plane, for example, as disclosed hereinabove in accordance with the embodiment illustrated in FIGS. 11a and lib.
  • the multi-beam antenna 10 comprises a dielectric substrate 12 with a convex profile 14, for example, a circular, quasi-circular or elliptical profile, wherein an associated plurality endfire antenna elements 16 etched into a first conductive layer 18.1 on the first side 20.1 of the dielectric substrate 12 are distributed around the edge 142 of the dielectric substrate 12 so as to provide for omni-directional operation.
  • a convex profile 14 for example, a circular, quasi-circular or elliptical profile
  • the plurality of endfire antenna elements 16 are adapted to radiate a corresponding plurality of beams of electromagnetic energy 21 radially outwards from the convex profile 14 of the dielectric substrate 12, or to receive a corresponding plurality of beams of electromagnetic energy 21 propagating towards the convex profile 14 of the dielectric substrate 12.
  • the endfire antenna elements 16 are arranged so that the associated radiation patterns intersect one another at power levels ranging from -2 dB to -6 dB, depending upon the particular application.
  • the number of endfire antenna elements 16 would depend upon the associated beamwidths and the associated extent of total angular coverall required, which can range from the minimum azimuthal extent covered by two adjacent endfire antenna elements 16 to 360 degrees for full omni-directional coverage.
  • the switching network 44 is fabricated using either a single integrated circuit or a plurality of integrated circuits, for example, a 1 :2 switch followed by two 1:4 switches.
  • the switching network 44 may comprise either GaAs P-I-N diodes, Si P-I-N diodes, GaAs MESFET transistors, or RF MEMS switches, the latter of which may provide for higher isolation and lower insertion loss.
  • the associated transmission line 26 may be adapted to beneficially reduce the electromagnetic coupling between different transmission lines 26, for example by using either vertical co-axial feed transmission lines 26, coplanar-waveguide transmission lines 26, suspended stripline transmission lines 26, or microstrip transmission lines 26. Otherwise, coupling between the associated transmission lines 26 can degrade the associated radiation patterns of the associated endfire antenna elements 16 so as to cause a resulting ripple in the associated main-lobes and increased associated sidelobe levels thereof.
  • An associated radar unit can be located directly behind the switch matrix on either the same dielectric substrate 12 (or on a different substrate), so as to provide for reduced size and cost of an associated radar system. The resulting omni-directional radar system could be located on top of a vehicle so as to provide full azimuthal coverage with a single associated multi-beam antenna 10.
  • the dielectric substrate 12 can be angled in the vertical direction, either upward or downward in elevation, for example, so as to provide for eliminating or reducing associated ground reflections, also known as clutter.
  • the dielectric substrate 12 of a multi-beam antenna 10 with a convex profile 14 may be provided with a conical shape so that each of the associated endfire antenna elements 16 is oriented with an elevation angle towards the associated axis 144 of the conical surface 146, for example, so as to provide for orienting the associated directivity of the associated endfire antenna elements 16 upwards in elevation.
  • the dielectric substrate 12 of a multi-beam antenna 10 with a concave profile 134 may be provided with a conical shape so that each of the associated endfire antenna elements 16 is oriented with an elevation angle towards the associated axis 144 of the conical surface 146, for example, so as to provide for orienting the associated directivity of the associated endfire antenna elements 16 upwards in elevation. Accordingly, the dielectric substrate 12 of the multi- beam antenna 10 need not be planar.
  • the multi-beam antenna 10 provides for a relatively wide field-of-view, and is suitable for a variety of applications.
  • the multi-beam antenna 10 provides for a relatively inexpensive, relatively compact, relatively low-profile, and relatively wide field-of-view, electronically scanned antenna for automotive applications, including, but not limited to, automotive radar for forward, side, and rear impact protection, stop and go cruise control, parking aid, and blind spot monitoring.
  • the multi-beam antenna 10 can be used for point-to-point communications systems and point-to-multi -point communication systems, over a wide range of frequencies for which the endfire antenna elements 16 may be designed to radiate, for example, 1 to 200 GHz.
  • the multi- beam antenna 10 may be configured for either mono-static or bi-static operation.

Landscapes

  • Variable-Direction Aerials And Aerial Arrays (AREA)
  • Aerials With Secondary Devices (AREA)
  • Waveguide Aerials (AREA)

Abstract

Une pluralité d'éléments d'antenne (16, 16.1, 16.2, 16.3) sur un substrat diélectrique (12) sont conçues pour lancer et recevoir des ondes électromagnétiques (21) à destination et en provenance d'une direction sensiblement à distance d'un bord convexe (14) ou concave (134) de ce substrat diélectrique (12), au moins deux de ces éléments d'antenne (16, 16.1, 16.2, 16.3) fonctionnant dans différentes directions (58). Les lignes de fente (26) d'antenne à rayonnement longitudinal à fente en cône (16.1) dans une première couche conductrice (18.1) d'un premier côté (20.1) du substrat diélectrique (12) sont couplées à des lignes microbande (34) d'une seconde couche conductrice (18.2) du second côté (20.2) du substrat diélectrique (12). Un réflecteur biconique (64,140) de lentille diélectrique cylindrique conforme (66) ou de lentille plane (68) améliore le diagramme de rayonnement de plan H. Des éléments d'antenne dipôle (16.2) ou des éléments d'antenne Yagi-Uda (16.3) sur la couche conductrice (18.1) du substrat diélectrique (12) peuvent être utilisés en coopération avec des éléments réflechissant associés (96, 98, 108), seuls ou en combinaison avec un réflecteur en coin (100) de plaques conductrices (102) fixé sur les couches conductrices (18.1, 18.2) à proximité des éléments d'antenne à faisceau longitudinal(16, 16.2, 16.3).
PCT/US2005/010596 2004-03-26 2005-03-28 Antenne multifaisceau WO2005094352A2 (fr)

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JP2007505280A JP2008503904A (ja) 2004-03-26 2005-03-28 マルチビームアンテナ

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DE102017209242A1 (de) 2017-05-31 2018-12-06 Volkswagen Aktiengesellschaft Bikonische Antennenvorrichtung für ein Kraftfahrzeug sowie Kraftfahrzeug
CN109950707A (zh) * 2019-04-15 2019-06-28 西安电子科技大学 一种圆锥共形端射阵列天线
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US9595767B2 (en) 2008-03-11 2017-03-14 Intel Corporation Wireless antenna array system architecture and methods to achieve 3D beam coverage
US10096891B2 (en) 2008-03-11 2018-10-09 Intel Corporation Wireless antenna array system architecture and methods to achieve 3D beam coverage
US11276918B2 (en) 2008-03-11 2022-03-15 Intel Corporation Wireless antenna array system architecture and methods to achieve 3D beam coverage
GB2509112A (en) * 2012-12-20 2014-06-25 Canon Kk Antenna system electromagnetic lens arrangement
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US9397407B2 (en) 2012-12-20 2016-07-19 Canon Kabushiki Kaisha Antenna system
WO2014118494A1 (fr) * 2013-02-01 2014-08-07 Cambridge Communications Systems Limited Agencement d'antennes d'un nœud sans fil
JP2016513386A (ja) * 2013-02-01 2016-05-12 ケンブリッジ コミュニケーション システムズ リミテッド 無線ノードのアンテナ配列
DE102017209242B4 (de) 2017-05-31 2019-09-05 Volkswagen Aktiengesellschaft Bikonische Antennenvorrichtung für ein Kraftfahrzeug sowie Kraftfahrzeug
DE102017209242A1 (de) 2017-05-31 2018-12-06 Volkswagen Aktiengesellschaft Bikonische Antennenvorrichtung für ein Kraftfahrzeug sowie Kraftfahrzeug
US10985471B2 (en) 2017-11-27 2021-04-20 Panasonic Intellectual Property Management Co., Ltd. Radar device
US10804615B2 (en) 2017-11-27 2020-10-13 Panasonic Intellectual Property Management Co., Ltd. Radar device
US10833415B2 (en) 2019-04-11 2020-11-10 The Boeing Company Radio frequency circuit board with microstrip-to-waveguide transition
CN109950707A (zh) * 2019-04-15 2019-06-28 西安电子科技大学 一种圆锥共形端射阵列天线
CN109950707B (zh) * 2019-04-15 2020-09-04 西安电子科技大学 一种圆锥共形端射阵列天线
US11942688B2 (en) 2019-04-26 2024-03-26 Battelle Memorial Institute Conformal/omni-directional differential segmented aperture
WO2020220055A1 (fr) * 2019-04-26 2020-10-29 Battelle Memorial Institute Ouverture segmentée différentielle conforme/omnidirectionnelle
US11605899B2 (en) 2019-04-26 2023-03-14 Battelle Memorial Institute Conformal/omni-directional differential segmented aperture
US11177548B1 (en) 2020-05-04 2021-11-16 The Boeing Company Electromagnetic wave concentration
CN112510358A (zh) * 2020-11-25 2021-03-16 大连理工大学 一种紧密型交叉梳状天线及汽车雷达
CN112510358B (zh) * 2020-11-25 2022-03-29 大连理工大学 一种紧密型交叉梳状天线及汽车雷达
WO2023155196A1 (fr) * 2022-02-21 2023-08-24 京东方科技集团股份有限公司 Antenne et dispositif électronique

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WO2005094352A3 (fr) 2007-02-15
EP1738432A2 (fr) 2007-01-03
EP1738432A4 (fr) 2007-09-05
JP2008503904A (ja) 2008-02-07

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