WO2001087020A1

WO2001087020A1 - Universal ballast control circuit

Info

Publication number: WO2001087020A1
Application number: PCT/CA2000/000462
Authority: WO
Inventors: Alexei Bogdan; Marc Oliver Hoffknecht
Original assignee: Lumion Corporation
Priority date: 2000-04-27
Filing date: 2000-04-27
Publication date: 2001-11-15
Also published as: AU4736100A

Abstract

A universal ballast control circuit allows a universal ballast to accommodate a gas discharge lamp within a relatively wide wattage range using a low-speed microcontroller. The control circuit drives the ballast to start, run and dim a particular lamp type by providing a control voltage signal to a conventional inverter MOSFET driver to effect dynamic and selective changes in the duty cycle and the frequency of the inverter signal. The present invention allows for the control circuit to be powered by a power supply signal either derived from an half-bridge MOSFET driver, extracted from a boost inductor of the boost converter or generated by an appropriately configured dedicated miniature switch mode power supply. Finally, control circuit can be utilized to drive PFC circuity in a feedback configuration to regulate the level of boost converter output voltage signal.

Description

Title: UNIVERSAL BALLAST CONTROL CIRCUIT

FIELD OF THE INVENTION

The present invention relates generally to lighting ballasts and in particular to a universal ballast control circuit for controlling the operation of a wide range of gas discharge lamp types.

BACKGROUND OF THE INVENTION

Significant improvements in programmable microcontrollers over the past five years as well as the existence of dimming systems which use complex algorithms have caused most major electronic ballast companies to develop microcontroller driven electronic ballasts. These electronic ballasts typically use microcontrollers to adjust the characteristics of the inverter voltage signal to accommodate a wide variety of lamps and /or to provide dimming functionality. Specifically, by changing the frequency or duty cycle of the inverter voltage signal, these electronic ballasts are able to start, run and dim a wide variety of gas discharge lamps.

Some electronic ballasts such as the one disclosed by United States Patent No. 5,039,921 to Kakitani uses a central processing unit (CPU) to control the frequency of the inverter voltage signal to change lamp voltage. The Kakitani patent describes a ballast which can be adapted to light and drive various types of gas discharge lamps according to each lamp's individual rating. The control circuit employs the CPU to detect the rating of the discharge lamp based on the lamp's starting voltage and to retrieve stored lamp loading data from memory relating to the type of discharge lamp detected. The oscillating frequency of the inverter circuit voltage signal is then adjusted so that the ballast produces a power voltage signal suited to the particular discharge lamp.

Other electronic ballasts such as the one disclosed by United Stated Patent No. 5,569,984 to Holtstag use a microprocessor to control the switching frequency and the pulse width of the inverter voltage signal provided to a particular lamp to avoid strong acoustic resonances or arc instabilities. The microprocessor evaluates deviation of electrical lamp parameters to detect arc instabilities and adjusts the frequency and pulse width in response. Accordingly, the ballast can operate HID lamps of different types, wattages and manufacturers over a broad frequency range despite the occurrence of acoustic resonance /arc instabilities among these lamps.

In order to achieve acceptable levels of accuracy in running and dimming a wide variety of gas-discharge lamps, it is necessary to be able to produce a wide variety of inverter voltage signals which requires a high resolution of control signals. Low-speed microcontrollers cannot provide the necessary degree of control to run a lamp within a ballast having conventional inverter signal frequencies. In order to achieve the desired operation of a typical ballast, expensive high-speed microcontrollers must be used which severely limits mass production and consumption of microcontroller-based electronic ballasts due to the cost of such high-speed microcontrollers.

Further, since microcontrollers provide discreet output, when digital output levels are provided to a lamp, sudden incremental changes in the lumen output are produced. These discrete "steps" in light intensity are visible to users and are unacceptable in commercial and residential environments. Even when the microcontroller is programmed to dim a lamp in relatively small increments, dimming a lamp using a digital signal still results in visible steps. Finally, in order to provide sufficient power supply to the microcontroller, either a drop-down resistor or a dedicated off-line power supply circuitry is used. The problem with using a simple voltage-drop resistor is that the heat and high frequency noise which are generated are very difficult to suppress. On the other hand, a separate off-line power supply adds substantial expense to the product.

Thus, there is a need for a universal lighting ballast control circuit which can produce a wide range of different control signals to start, run and dim a wide variety of gas-discharge lamp types using an inexpensive low-speed microcontroller, which can modulate illumination levels on a continuously variable basis and which provides power to the microcontroller without conventionally known power supply problems and associated expense.

BRIEF SUMMARY OF THE INVENTION

It is therefore an object of the present invention in one aspect to provide a universal ballast control circuit for use with a power circuit coupled to an AC source for outputting a high frequency AC signal and a coupling circuit coupled to the power circuit for applying the AC signal to any one of a plurality of gas discharge lamp types, said control circuit comprising:

(a) a generator for generating a periodic analog voltage signal having a first waveform; (b) a source for generating a first DC voltage signal having a second waveform;

(c) a controller for controlling the frequency of the periodic analog voltage signal; and

(d) a processor for processing said first DC voltage signal and said periodic analog voltage signal to generate a control voltage signal for varying the frequency and duty cycle of the AC signal, the frequency and duty cycle of said control voltage signal being dependent on said first and second waveforms. In a second aspect, the present invention provides a universal ballast control circuit for use with a power circuit coupled to an AC source for outputting a high frequency AC signal and a coupling circuit coupled to the power circuit for applying the AC signal to any one of a plurality of gas discharge lamp types, said control circuit comprising: (a) a generator for generating a periodic analog voltage signal having a first waveform;

(b) a controller for controlling the shape of said first waveform; and

(c) a comparator for comparing the periodic analog voltage signal with at least one DC voltage and for generating a control voltage signal for varying the duty cycle and frequency of the AC signal.

In a third aspect, the present invention provides a method of powering any one of a plurality of gas discharge lamp types, each lamp type having a predetermined set of lamp characteristics, said method comprising the steps of:

(a) producing a high frequency AC signal;

(b) applying the AC signal to the lamp;

(c) generating a periodic analog voltage signal having a first waveform;

(d) generating a DC voltage signal having a second waveform;

(e) controlling the frequency of the periodic analog voltage signal;

(f) controlling the magnitude of the DC voltage signal; (g) varying the duty cycle and frequency of the AC signal based on a comparison of the first and second waveforms.

In a fifth aspect, the present invention provides a method of powering any one of a plurality of gas discharge lamp types, each lamp type having a predetermined set of lamp characteristics, said method comprising the steps of:

(a) producing a high frequency AC signal;

(b) applying the AC signal to the lamp;

(c) generating a periodic analog voltage signal having a first waveform; (d) controlling the shape of the first waveform;

(e) varying the duty cycle and frequency of the AC signal based on a comparison of first waveform and at least one DC threshold voltage. It also an object of the present invention to provide a method of controlling the output voltage of a boost converter of a gas-discharge lighting ballast, said method comprising the steps of:

(a) applying a DC signal to a power switch to produce a boost converter output voltage;

(b) generating a periodic AC voltage signal;

(c) varying the waveform characteristics of the periodic AC voltage signal to form a modulated periodic AC voltage signal;

(d) comparing the modulated periodic AC voltage signal with the boost converter output voltage; and

(e) applying the result to the power switch to change the output voltage of the boost converter.

Further objects and advantages of the invention will appear from the following description, taken together with the accompanying drawings.

BRIEF DESCRIPTION OF THE DRAWINGS In the accompanying drawings:

Fig. 1 is a block diagram of a typical prior art microcontroller-based electronic lighting ballast;

Fig. 2 is a block diagram of the present invention; Fig. 3 is a waveform timing diagram showing the control voltage signal V_c which is produced when a DC voltage signal V_D is compared with a periodic voltage signal V_P in the present invention;

Fig. 4A is a circuit diagram of the digital-to-analog converter of the present invention;

Fig. 4B is another circuit implementation of the digital-to-analog converter of the present invention;

Fig. 5 is a circuit diagram of an implementation of the control circuit of the present invention in which the microcontroller and two digital-to- analog converters provide DC signals Noci ^anc^ V_DC2 which are used to vary the duty cycle and frequency of the control voltage signal N_c;

Fig. 6 is another implementation of the control circuit in which two DC voltage signals V_DC1 ^an N_DC2 ^are used to control the duty cycle and the frequency of the control voltage signal N_c by controlling the rate of charging and discharging of capacitor C_τ;

Fig. 7 A is a waveform timing diagram showing the periodic voltage signal N_P and control voltage signal N_c of Fig. 6; Fig. 7B is a waveform timing diagram showing the DC voltage signal N_DC1 of Fig. 6;

Fig. 7C is a waveform timing diagram showing the DC voltage signal V_Dc2 °f Fig- 6;

Fig. 8 is a circuit diagram illustrating how the microcontroller can be powered using a half-bridge driver;

Fig. 9 is a circuit diagram illustrating how the microcontroller can be powered using a boost inductor;

Fig. 10 is a circuit diagram illustrating how the microcontroller can be powered using a miniature switch mode power supply; Fig. 11 is a circuit diagram of the control circuit of the present invention for achieving power factor correction.

DETAILED DESCRIPTION OF PREFERRED EMBODIMENTS

Reference is first made to Fig. 1, which shows a prior art microcontroller-based electronic ballast 10. As is conventionally known, ballast 10 includes a bridge rectifier 12, a boost converter 14, an inverter 16, resonance network 18, and a microcontroller 20. Ballast 10 is used to power a lamp 22 as is conventionally known.

Bridge rectifier 12 is coupled to a typical AC power line voltage of

110-120 Volts. A rectifier consisting of diodes provides a full-wave rectified DC voltage of about 160 Volts across its output. Bridge rectifier 12 may also include an EMI filter for insulating the power lines from interference generated by ballast 10.

Boost converter 14 is coupled to the output of bridge rectifier 12 and is used to boost and control the input DC voltage provided by bridge rectifier 12 such that appropriate power is provided to lamp 22. Boost converter 14 provides regulated voltage to inverter 16.

Inverter 16 is a voltage-fed half-bridge DC-AC inverter which is used to convert the input DC voltage received from boost converter 14 into high frequency AC voltage. Half-bridge inverter 16 typically includes a half-bridge MOSFET driver 17 and MOSFET transistors Q_A and Q_B at its output, although many other implementations are possible (i.e. using bipolar transistors). MOSFET driver 17 is typically implemented using an integrated circuit such as IR2104 manufactured by International Rectifier. Transistors Q_A and Q_B produce an inverter voltage signal which is a high frequency generally square wave signal, as is familiar to those skilled in the art. The high frequency signal generated by transistors Q_A and Q_B is applied to resonance network 18.

Resonance network 18 is directly coupled to lamp 22 and is commonly used to avoid the necessity of an output transformer. Resonance network 18 typically includes an LCC network of capacitors and inductors which provides waveshaping and current limiting to produce a substantial sinusoidal lamp current for lamp 22. Ballast designers choose an optimal inverter frequency and optimal values of LCC circuit inductance and capacitance to create proper currents and voltages across the lamp as well as to produce an economical ballast configuration. The LCC network also functions as an igniter to ignite the lamp upon initial application of power to ballast 10.

Microcontroller 20 is used to control the operating frequency or duty cycle of the inverter voltage signal. In order for ballast 10 to properly operate lamp 22, ballast 10 must be able to produce certain voltage and current characteristics which are suited to a lamp's particular characteristics. When lamp 22 has been struck and is in full operation, its running voltage must be within its manufacturer's specified range. Typically, ballast 10 would be designed to provide a voltage between 35 and 130 volts (rms) for running operation of lamp 22. Particular voltages must be provided across the filaments of lamp 22 during the course of lamp operation. Further, the current flowing through lamp 22 must also be such that lamp 22 can be safely run. Finally, a sufficient striking (or ignition) voltage must be applied to lamp 22, such that the pressurized gas ignites into plasma form and forms a plasma thread. The provision of all of these voltage and current characteristics is accomplished by controlling the operation of half-bridge MOSFET driver 17 which in turn drives transistors Q_T1 and Q_I2 of inverter 16. By controlling the duration and frequency that transistors Qn and Q_I2 are conductive, microcontroller 20 can ensure that ballast 110 provides the proper striking, running and dimming of lamp 22.

However, in order for ballast 10 to provide the above discussed circuit conditions, microcontroller 20 must operate at a high-speed to produce a sufficient number of control levels. If microcontroller operates at too low a speed, then ballast 10 will not be able to accurately provide the various current and voltage characteristics which are necessary for proper running and dimming of lamp 22. As an illustration, consider a typical low-speed 8-pin microcontroller such as the PIC12C508 from Microchip Technology. If this microcontroller 20 is configured to directly drive the output half-bridge inverter 16 of ballast 10, it will result in inaccurate operation of ballast 10. The nominal frequency of the PIC12C508 microcontroller 20 is 4 MHz, a typical value for this slower class of microcontrollers.

Since an instruction can only be acted on by microcontroller 20 once every four timing cycles, the command cycle time T_c for this device would be:

Accordingly, every 1 μsec a digital voltage level can be provided to inverter 16 to change the current and voltage characteristics of resonance network 18. Typically, fluorescent electronic ballasts operate in a frequency range between 20 kHz to 60 kHz. For a ballast having an operating frequency of 40 kHz, the duration of the half-cycle pulse T_{1 2} of the inverter voltage is:

T. ,, = x — = 12.5 μsec

^{1 2} 40 x l0³ 2 *^*

Accordingly, in order to adjust the duty cycle or the frequency of the inverter voltage signal, there are only be 12 steps in which to do so. The overall accuracy of such control circuitry is approximately 8.3%. This accuracy becomes worse when the full range of 50/50 duty cycle oscillation cannot be used. When the duty cycle is 20/80 or even 10/90, the driving accuracy of the control circuitry will only be about 50-80% which is unacceptable for proper operation of ballast 10.

Consequently, it is necessary to use high-speed microcontrollers which run at speeds of between 20 MHz to 40 MHz to properly control the operation of typical ballasts running at frequencies between 20 kHz to 60 kHz. Such microcontrollers are typically priced at between US$5 to US$10 each, which prohibits cost-effective production of ballast 10. Further, when the frequency of the digital output pulses produced by high-speed microcontrollers 20 is changed, sudden incremental changes in the lumen output of lamp 22 result which are visually perceived as light intensity "steps". For example, even when microcontroller 20 is programmed to dim lamp 22 using 128 light intensity steps, the inventor has found that visible steps still occur. Reference is now made to Figs. 2 and 3, which show an improved microcontroller-based programmable ballast 110 which includes a control circuit 126, according to a preferred embodiment of the invention. Control circuit 126 is designed to utilize a relatively inexpensive microcontroller 120 to control the inverter voltage signal to start, run and dim a wide range of lamp types. Common elements between ballast 110 and the prior art ballast 10 will be denoted by the same numerals with one hundred added thereto.

Accordingly, ballast 110 includes a bridge rectifier 112, a boost converter 114, an inverter 116, resonance network 118, a microcontroller 120 as previously discussed. Ballast 110 also comprises control circuit 126 which uses a low-speed microcontroller 120 for proper operation of ballast

110.

Control circuit 126 provides an analog control voltage signal V_c to half-bridge MOSFET driver 117 which in turn drives MOSFET transistors Q_A and Q_B. Control circuit 126 comprises microcontroller 120 periodic signal generator 128, a digital-to-analog (D/A) converter 130 and a comparator 132.

Microcontroller 120 of the present invention can be a conventional low-cost microprocessor such as PIC12C508 from Microchip Technology. Microcontroller 120 generates digital voltage signals V_D1 and V_D2 which are input into control circuit 126.

Periodic voltage signal generator 128 receives digital voltage signal V_D2 from microcontroller 120 and generates a periodic voltage signal V_P. While any periodic voltage signal can be used within control circuit 126, the inventor has determined that a sawtooth waveform is preferable as a sawtooth generator can be implemented by a simple and low cost circuit. For example, a conventional timer integrated circuit (e.g. a 555 timer circuit or an IR5155 oscillator circuit) configured with appropriate resistive and capacitor elements attached to various pin inputs and outputs generates a sawtooth waveform, as is conventionally known and as will be discussed.

D/A converter 130 converts the digital voltage signal V_D1 produced by microcontroller 120 into an analog voltage signal V_Dcι- D/A converter 130 is preferably implemented using an integrating capacitor , either a series or parallel connected resistor Rj and an appropriately oriented diode D_j as shown in Figs. 4A and 4B, to form a conventional integrator circuit. It has been determined that it is preferable to use the circuits of Fig. 4A and 4B instead of conventionally available D/A integrated circuits to ensure that a wide range of analog signals can be produced cost effectively.

Referring back to Figs. 2 and 3, comparator 132 is a general-purpose comparator integrated circuit such as the LM393 integrated circuit manufactured by Linear Technology. As shown, the DC voltage signal V_{D 1} being output by the D/A converter 130 is provided to the positive input of comparator 132 and the periodic voltage signal V_P is provided to the negative input of comparator 132. Comparator 132 produces a control voltage signal V_c waveform having a duty cycle DC and a frequency f_c as shown in Fig. 3.

Control voltage duty cycle DC^ is dependant on the comparative values of the DC voltage signal V_DC1 and the periodic voltage signal V_P. It will be seen from Fig. 3 that when periodic voltage V_P exceeds V_Dci_/ control voltage V_c goes high and while periodic voltage V_P is less than DC voltage signal V_DC1, control voltage V_c goes low. Accordingly, control voltage duty cycle DC_C can be varied by adjusting the value of the DC voltage signal V_{D 1} or by changing the digital voltage signal V_D1 generated by microcontroller 120.

Further, as can be seen from Fig. 3, the control voltage frequency f _c is equivalent to the frequency of the periodic voltage signal V_P. Accordingly, the control voltage frequency f_c can be varied by controlling the frequency of the periodic voltage signal V_P. One way of accomplishing this is by using the DC voltage signal V_DC2 from microcontroller 120 to control the current source of the periodic voltage signal generator 128 as will be discussed below.

Fig. 5 shows one possible circuit implementation of control circuit 126 in which both the control voltage duty cycle DC_C and the control voltage frequency f are varied using a periodic voltage signal generator 128, a controller 129, and a comparator 132. Controller 129 includes microcontroller 120 and D/A converters

D/A_α and D/A₂. Microcontroller 120 outputs two separate digital control voltages V_D1 and V_D2 into D/A converters D/Aj and D/A₂, respectively which in turn convert them into DC voltage signals V_DC1 and Nrj_>c₂- D voltage signal V_DC1 is input into the positive input of comparator 132 and DC voltage signal V_{D 2} is used to control the current source of the periodic voltage signal generator 128. By varying DC voltage signal V_Dci_/ it is possible to control the control voltage duty cycle DC_C being output by comparator 132 as previously described. By varying the DC voltage signal V_DC2, it is possible to control the control voltage frequency f , as will be discussed.

Periodic voltage signal generator 128 generates a sawtooth waveform using timer IC_T, resistors Rj and R₂, capacitor C_τ, and transistor Q_x. Timer IC_T is a conventional timer integrated circuit such as a 555 timer circuit or an IR5155 oscillator circuit. RESET (pin 4) and VCC (pin 8) are connected to running voltage V_DD. TRIGGER (pin 2), THRESHOLD (pin 6) and DISCHARGE (pin 7) of timer IC_T are coupled at node A to a grounded timing capacitor C_τ. Transistor Qj has its collector connected to node A and its emitter connected to voltage V_cc through resistor R_α. Accordingly, periodic voltage signal V_P having a sawtooth waveform is generated at the collector of transistor as is conventionally known. The current source comprising resistor R_j and transistor Q₁ powered by voltage V_cc serves to stabilize the charge current on capacitor C_τ.

When the periodic voltage signal V_P THRESHOLD (pin 6) rises above 2/3 V_DD, timer IC_T shorts capacitor C_τ to ground at DISCHARGE (pin 7) through its internal discharge transistor. When the periodic voltage signal V_P at THRESHOLD (pin 6) falls below 1 /3 V_DD, the internal discharge transistor in timer IC_T is disabled and capacitor C_τ begins to recharge from V_cc through resistor R₁ and transistor Q_:. In this way, timer IC_T can be configured to operate as an astable multivibrator such that a periodic voltage signal V_P is produced across capacitor C_τ. Since the current flowing through transistor Q_x is controlled by DC voltage signal V_DC2 it i^s possible to control the frequency of the periodic voltage signal V_P by appropriately varying DC signal N_DC2- Transistor Q₂ operates as a linear modulating amplifier since Q₁ is always biased in its active region. Accordingly, as DC voltage signal V_DC2 i^s increased, the current flowing through transistor Q₁ is increased (i.e. impedance of transistor Q₁ is decreased) and capacitor C_τ will charge at a faster rate. Thus, the set-point of 2/3 N_DD ^w ϋ be reached more quickly causing the frequency of periodic voltage signal N_P to increase which in turn will increase the control voltage frequency f^. Since the current source comprising resistor R_lf transistor Q₁ voltage V_c can be considered to operate as a variable impedance having a linear characteristic when V_DC2 is applied to the base of Q the duty cycle of the control voltage signal V_c will not be affected by changes in DC signal V_Dc₂.

Further, by changing the value of DC voltage signal V_Dci_/ it is possible to change the control voltage duty cycle DC_C in a continuous manner. If the integrator capacitor C_j of D/A converter D/A_α is large, a wide range of DC voltage signals V_c , each having a unique DC threshold voltage, can be generated for comparison with periodic voltages V_P. As DC voltage signal V_DC1 is reduced, the duty cycle of control voltage V_c increases and as DC voltage signal V_Dcι increases, the duty cycle of control voltage V_c decreases. It should be noted that the frequency of control voltage V_c will not change as DC voltage signal V_DC1 is varied. Consequently, it is possible for microcontroller 120 and control circuit 126 to generate a wide range of control voltages V_c, each with a unique frequency f_c and duty cycle DC_C.

Fig. 6 shows an alternative circuit implementation of control circuit 126 which uses microcontroller 120 to independently control the control signal duty cycle DC and the control signal frequency f_c of control voltage signal V_c with digital voltage signals V_D1 and V_D2. Control circuit 126 comprises controller 129, timer circuit IC_T, transistors Q_x and Q₂, resistor R and timing capacitor C_τ.

Controller 129 comprises microcontroller 120 and two D/A converters D/A_α and D/A₂. D/A converters D/Aj and D/A convert digital voltage signals V_Dι and V_D from microcontroller 120 into DC voltage signals V_DC1 and V_{D 2/} respectively. Each DC voltage signal V_Dcι and V_DC2 controls the operation of transistors Q₁ and Q₂, respectively, to vary the duty cycle and frequency of periodic voltage signal V_P as will be described.

Timer IC_T is a conventional timer (e.g. a 555 timer) powered by voltage V_DD and utilized as a simple oscillator in the present circuit. The schematic and written description of the 555 timer circuit provided by "Microelectronic Circuits" Third Edition by Adel Sedra and Kenneth C. Smith (at pages 875 to 880) is hereby incorporated by reference. Timer IC_T compares the periodic voltage signal V_P at THRESHOLD (pin 6) with two internally generated threshold voltages namely 1/3 V_DD ^and 2/3 V_DD- THRESHOLD (pin 6) of timer IC_T is connected to the common collector junction of transistors and Q₂ and to ground through timer capacitor C_τ. OUTPUT (pin 3) of timer IC_T produces the control voltage V_c of control circuit 126. As will be explained, due to the charging and discharging of timer capacitor C_τ, a periodic voltage signal V_P with a triangular-type waveform is generated at the common collector junction. When periodic voltage signal V_P is greater than 2/3 N_DD at THRESHOLD (pin 6), internal circuitry of timer IC_T will cause OUTPUT (pin 3) to go high. When periodic voltage signal N_P is lower than 1/3 N_DD ^at THRESHOLD (pin 6), internal circuitry of timer IC_T will cause OUTPUT (pin 3) will go low. In this way, control voltage signal N_c is controlled by the voltage characteristics (i.e. duty cycle and frequency) of periodic voltage signal N_P.

Transistors Qj and Q are coupled to ground through timing capacitor C_τ and to the output of control circuit 126 through resistor Rj. Transistors Q_: and Q₂ are controlled by DC voltage signals Noci ^and V_Dc_.2> respectively. Resistor Rj and control voltage signal V act as either a current source for transistor Q_α or a current sink for transistor Q₂, depending on the polarity of control voltage signal V_c. Specifically, the collectors of transistors Q_x and Q₂ are coupled to the ground through capacitor C_τ and the emitters of transistors Qj and Q₂ are coupled to the output of control circuit 126 through resistor Rj. The bases of transistors and Q₂ are coupled to the DC voltage signal outputs of D/A converters D/Aj and D/A₂. Accordingly, transistors Q₁ and Q₂ operate as amplifiers when they are biased in their active region by control voltage signal V_c through resistor R₁ and their impedance values can be controlled by DC voltage signals V_Dcι and V_DC2, respectively as is conventionally known.

Thus, the control voltage signal V_c produced at OUTPUT (pin 3) of timer IC_T, is controlled by the combined operation and relative impedance of transistors Q₁ and Q₂. When OUTPUT (pin 3) of timer IC_T is high, timer capacitor C_τ will charge through resistor R₁ and transistor Q₁ until periodic voltage signal V_P reaches 2/3 V_DD. When periodic voltage signal V_P at THRESHOLD (pin 6) is 2/3 V_DD, timer IC_T will force OUTPUT (pin 3) low and capacitor C_τ will begin discharging through transistor Q and resistor R_:. Once periodic voltage signal V_P at THRESHOLD (pin 6) decreases to 1/3 V_DD, OUTPUT (pin 3) will be driven high and capacitor C_τ will start charging through transistor Q₁ again. It should be noted that transistors Q_τ and Q₂ will never conduct simultaneously, as transistor Q- is only on when OUTPUT (pin 3) at timer ICT is high and transistor Q₂ is only on when OUTPUT of timer ICT is low.

Capacitor C_τ will charge or discharge at a rate based on the relative impedances of transistors Q₁ and Q₂. That is, if the impedance of transistor Q_x is low, capacitor C_τ will charge at a higher rate than if the impedance of transistor Q_x is high. Similarly if the impedance of transistor Q₂ is high, capacitor C_τ will discharge slower than if the impedance of transistor Q is low. That is, the duty cycle and the frequency of the periodic voltage signal V_P waveform are determined by the direction and rate of current that flows through timer capacitor C_τ. As the characteristics of periodic voltage V_P are changed by DC voltage signals V_DC1 and V_DC2, periodic voltage signal V_P at THRESHOLD (pin 6) reaches 2/3 V_DD and 1/3V_DD voltage levels at various times which alters the waveform characteristics of control voltage signal V_c at OUTPUT (pin 3) of timer IC_T. Thus, by modifying the characteristics of periodic voltage signal V_P, it is possible to control the pulse duration and pause duration of the high and low signals produced by OUTPUT (pin 3) of timer IC_T and accordingly the duty cycle and frequency of control voltage V can be controlled.

As an illustration of how a control voltage signal V_c is generated by the circuit of Fig. 6, a typical periodic voltage signal V_P produced at the common collector junction of transistors C^ and Q₂ is shown in Fig. 7A. When DC voltage signal V_DC1 as shown in Fig. 7B is applied to the base of transistor Q_: and DC voltage signal V_DC as shown in Fig. 7C is applied to the base of transistor Q₂, the control voltage signal V_c as shown superimposed on periodic voltage signal V_P in Fig. 7A results. Specifically, when DC voltage signal V_DC1 is at DC level A (Fig. 7B), periodic voltage signal V_P causes control voltage signal V at OUTPUT (pin 3) of timer IC_T to have a pulse duration of X₁ and a pause duration Y_j as shown. When DC voltage signal V_Dcι i^s increased to DC level B (Fig. 7B), increased current flows through transistor Q_x when capacitor C_τ is charging and thus capacitor C_τ is charged at an increased rate. This causes control voltage signal V_c to have a pulse duration X₂ (Fig. 7A) which is less than the initial pulse duration, as shown. Similarly, when DC voltage signal V_DC2 (Fig. 7C) is increased from DC level A' to B^', increased current flows through transistor Q₂ when capacitor C_τ is discharging and thus capacitor C_τ is discharged at an increased rate. This results in a shorter pause duration Y₂, as shown.

In this way, a low-speed microcontroller 120 can provide sufficient digital voltage signals which can be converted into a wide variety of analog signals that can individually control the charge time and discharge time of timing capacitor C_τ. In this way, it is possible to control the duration of the pulses for the control voltage signal V_c and the pauses between the pulses to an extremely high degree of resolution. Thus both the control signal duty cycle DC_C and the control signal frequency fc can be independently controlled to a wide degree by a relatively low-speed microcontroller 120. Further, since the control voltage signals V_c are analog, it is possible to modulate illumination levels on a continuously variable basis.

Another aspect of the present invention relates to the ability to power microcontroller 120 within a conventional ballast 110 without the conventional disadvantages. Typical microcontroller-based ballasts power microcontroller and other associated control circuity components either through a drop-down resistor which' causes problems associated with heat and high frequency noise or by using a dedicated off-line power supply circuitry which is costly. Accordingly, it is desirable to provide a clean high frequency power signal that can be easily filtered and converted to DC voltage sufficient to power the microcontroller 120 and associated control circuitry 126 without the associated problems As illustrated in Fig. 8, the present invention provides power signal

P_s to microcontroller 120 by extracting energy from half-bridge MOSFET driver 117 using a conventionally known bootstrap power supply 142. As has been discussed, inverter 116 contains a MOSFET driver 117 which drives transistors Q_A and Q_B from a HIGHSIDE MOSFET SIGNAL OUTPUT (pin 11) and a LOWSIDE MOSFET SIGNAL OUTPUT (pin 7). Bootstrap power supply 142 is connected to bootstrap output (pin 12) and FLOATING GROUND POINT (pin 9) of MOSFET driver 117. FLOATING GROUND POINT is connected to the common node of transistors Q_A and Q_B. POWER SUPPLY (pin 1) of MOSFET driver 117 is fed to the input of bridge rectifier 112 through resistor R_BR. Bootstrap power supply 142 provides power signal P_s to microcontroller 120 through reverse- connected diode D_B3 and capacitor C_B and through forward-connected diode D_B1, as is conventionally known. Bootstrap power supply 142 comprises diodes D_B1, D_B2, resistor R_B and capacitors C_B1 and C_B2 as is conventionally known.

Fig. 9 shows an alternative way of providing microcontroller 120 with a power supply signal P_s, namely by extracting power from a boost inductor L_B of boost converter 114. Boost converter 114 typically comprises boost inductor L_B, a PFC MOSFET transistor Q_PPc ^a bulk capacitor C_B, diode D_P3 and PFC control circuity 143.

Diode D_P3 acts as a uni-directional switch. When diode D_P3 is forward biased (and MOSFET Q_PPc is open), current flowing through boost inductor L_B from bridge rectifier 112 will charge bulk capacitor C_B to an output voltage level. Diode D_P3 prevents bulk capacitor C_B from discharging through MOSFET P_PPc (if closed) or through boost inductor L_B. This allows bulk capacitor C_B to be charged or "boosted" to exceed the AC input voltage applied to ballast 110, as is conventionally known.

Power adaption circuit 144 is shown comprising diodes D_P1, D_P2, D_P4, resistors R_P1 and R_P2, and capacitor C_P. Diode D_P1, D_P4 and resistor R_P1 are connected in series to secondary winding of boost inductor L_B such that current flows to microcontroller 120. Schottky diode D_P2 is reverse- connected to ensure a stable voltage drop at the node between resistor R_P1 and forward-connected diode D_P4. Power supply signal P_s is provided to microcontroller 120 from the common node between resistor R_P2 and capacitor C_P. Capacitor C_P is used to smooth power signal P_s and resistor R_P is used as a "start-up" resistor to ensure that capacitor C_P undergoes several start-up charging cycles when ballast is started.

Finally, as shown in Fig. 10 microcontroller 120 can be powered by a power supply signal P_s which is generated by a dedicated miniature switch mode power supply 146 appropriately configured as is conventionally known. Switch mode power supply 146 can be restricted to producing between 2 to 3 watts and is a reliable but somewhat expensive alternative to the previous alternatives. Switch mode power supply 146 can be any commercially available miniature switch mode power supply 146, such as a TOP210 three terminal off-line PWM switch integrated circuit manufactured by Power Integrations, Inc. as will be assumed for the following discussion.

Switch mode power supply 146 can be configured to provide power supply signal P_s using transformer T_lx diodes D_P1._P4, capacitors C_P1 and C_P2, and resistor R_P as shown. The primary winding of transformer Tj receives the high voltage DC signal from bridge rectifier 112 and the other side of the primary is driven by the integrated high-voltage MOSFET within power supply 146. Specifically, power supply signal P_s is determined by the voltage across CONTROL (pin 4) of power supply 146, the voltage drops of diode D_P4 and D_P3, and the turns ratio between the bias winding and output windings of transformer T_x. Other output voltages can be produced by adjusting the turns ratios of transformer T₁. Diodes D_P1 and D_P2 clamp the voltage spike caused by transformer leakage to a safe value and reduce ringing at DRAIN (pin 5) of power supply 146. The power secondary winding is rectified and filtered by diode D_P4 and capacitor C_P1 to create power supply signal P_s. The voltage waveform across bias winding is rectified and filtered by diode D_P3, resistor R_P and capacitor C_P2 to create a bias voltage to power supply 146. Capacitor C_P2 also filters internal MOSFET gate drive charge current spikes on the CONTROL pin, determines the auto-restart frequency, and together with R_P, compensates the control loop.

Now referring to Fig. 11, another aspect of the present invention is shown whereby a voltage stabilization feedback circuit 150 is used to regulate the level of boost converter 114 output voltage signal Nouτ- A conventional method of creating power factor correction (PFC) circuity for electronic ballasts is by using boost converter circuity. However, it is usually impossible to adjust output voltage of the PFC circuity when the lamp load changes, during the course of dimming and when input voltage is varied.

Generally, the output voltage signal V₀uτ ° boost converter 114 driven in continuous current mode and with constant frequency and supplied with an input voltage signal V_IN can be described as follows:

V

V ^v ouτ = ₍₁ _ ^w _D)

where D is the duty cycle of the operational voltage. However, less well recognized is that by changing frequency within a continuous current mode of operation, output voltage signal V₀uτ ^can be adjusted within certain limits. The expression for output voltage signal V_QUT versus switching frequency F can be defined as follows:

where t₀ is the switch on-time and t_0FF is the switch off-time which in turn can be defined as follows:

t ^lON =

where POUT is the output power, L is the inductance of the boost inductor, η is the efficiency, V_IN is the input voltage and K is the input voltage form coefficient, as is conventionally understood. By rearranging these relations, output voltage signal V₀TJT ^can be written as follows:

V V

Thus, when output power PouT' efficiency of the inverter η, boost inductance L, and input voltage signal N_ΪΝ are fixed, the relationship between output voltage signal Nouτ ^anc^ frequency F has a hyperbolic character. Taking these principles into account, the inventor has determined that it is possible to adjust boost converter output voltage signal Nouτ using microcontroller 120 and a voltage stabilizing feedback circuit 150.

Specifically, feedback circuit 150 comprises capacitors C_F1._F3, diodes D_F1._F2, resistors R^y, 555 timer circuit IC_T, comparator 132, and transistors FI-F2- S previously discussed, diode D_F1, capacitor C_F1 and resistor R_F1 are configured to form a simple D/A converter 130 which serves to convert a digital signal N_D produced by microcontroller 120 to a DC signal V_Dc- DC signal V_DC is used to control the current source of the periodic generator 128 by triggering transistor Q_F1 which has its emitter connected to voltage signal N_DD through resistor R_F3 and to ground through capacitor C_F2. Also as previously discussed, the collector of transistor Q_P1 is coupled to TRIGGER (pin 2), THRESHOLD (pin 6) and DISCHARGE (pin 7) of 555 timer circuit IC_T to produce periodic voltage signal N_P as previously described in detail in respect of Fig. 5. The periodic voltage signal N_P is input into the negative terminal of comparator 132.

Further, the voltage output of the boost converter 114 Nouτ is applied through diode D_F2, capacitor C_F3 and across voltage divider comprising resistors R_F6 and R_F7 into the positive terminal of comparator 132. The power factor correction signal V_PF produced by comparator 132 is used to control the output voltage signal V₀uτ produced by boost converter 114 by controlling the operation of PFC MOSFET transistor Q_PFc- Specifically, power factor correction signal V_PFC is used to control the current source comprising transistor Q_F2 and resistor R_F5 driven by voltage V_Dr Thus, by appropriately varying the duty cycle of the PFC voltage signal being applied to transistor Q_PF in such a feedback configuration it is possible to stabilize the output of boost converter 114, as is conventionally understood.

As before, microcontroller 120 controls the frequency of power factor correction signal V_PFC by controlling the current source connected to timer IC_T. Further, the duty cycle of PFC signal V_PFC is determined by the difference between boost converter output voltage signal Nouτ ^an(^ the voltage signal V_P and varies itself to maintain output voltage when either the input voltage or the output load fluctuate. By changing the frequency and duty cycle of the periodic voltage signal V_P, the PFC signal V_PFC supplied to transistor Q_PFc can regulate the output voltage Nouτ °f boost converter 114. Accordingly, a relatively low-speed microcontroller 120 can achieve stabilization of the boost converter 114.

In use, control circuit 126 of ballast 110 utilizes a low-speed microcontroller 120 to successfully control the operation of MOSFET driver 117 of a conventional inverter circuit 116 using a control voltage Nc- Control circuit 126 can vary the duty cycle DC_C and control voltage frequency f _c of a control voltage signal N_c to a high degree of resolution. Control circuit 126 generates a periodic voltage signal N_P and modulates the periodic voltage V_P so that certain DC levels are detected at differing frequencies. These DC levels are used to generate the control voltage V_cby either comparing the periodic voltage signal V_P with an analog DC signal through a comparator to produce control voltage V_c or by passing the periodic voltage signal V_P through a timer IC_T to suitably trigger THRESHOLD (pin 6) of timer IC_T to generate control voltage V_c at OUTPUT (pin 3) of timer IC_T.

Further, the present invention allows for control circuit 126 to be powered using a number of convenient power sources within a conventional ballast 110. First, microcontroller 120 can be powered by a power supply signal P_s derived from half-bridge MOSFET driver 117 of inverter 116, using a conventionally known bootstrap power supply 142. Second, microcontroller 120 can be powered by a power supply signal P_s which is extracted from a boost inductor L_B (Fig. 11) of boost converter 114. Finally, as microcontroller 120 can be powered by a power supply signal P_s generated by a appropriately configured dedicated miniature switch mode power supply 146, such as a TOP210 three terminal off-line PWM switch integrated circuit manufactured by Power Integrations, Inc. Control circuit 126 can also be applied to stabilize the level of boost converter 114 output voltage signal VQUT by providing a feedback control signal V_PFC to the PFC MOSFET Q_PFc- Microcontroller 120 is used to control the frequency and duty cycle of power factor correction signal V_PFC by controlling the frequency and duty cycle of the periodic voltage signal V_P and comparing the periodic voltage signal V_P to the output voltage Nouτ to determine a proper feedback control voltage signal V_PFC.

Accordingly, the present invention provides a universal lighting ballast control circuit which generates a wide range of different control signals to start, run and dim a wide variety of gas-discharge lamp types using an inexpensive low-speed microcontroller. By providing a high number of continuously variable control signals, the present invention can eliminate visible steps of light intensity which would otherwise occur when dimming a lamp. Further, the microcontroller can be powered within a typical ballast without conventionally known power supply problems and associated expenses. Finally, the present invention can be used to regulate the boost converter output voltage to control and stabilize the operation of the power factor correction circuitry.

As will be apparent to persons skilled in the art, various modifications and adaptations of the structure described above are possible without departure from the present invention, the scope of which is defined in the appended claims.

Claims

WE CLAIM:

1. A universal ballast control circuit for use with a power circuit coupled to an AC source for outputting a high frequency AC signal and a coupling circuit coupled to the power circuit for applying the AC signal to any one of a plurality of gas discharge lamp types, said control circuit comprising:

(a) a generator for generating a periodic analog voltage signal having a first waveform;

(b) a source for generating a first DC voltage signal having a second waveform;

(d) a processor for processing said first DC voltage signal and said periodic analog voltage signal to generate a control voltage signal for varying the frequency and duty cycle of the AC signal, the frequency and duty cycle of said control voltage signal being dependent on said first and second waveforms.

2. The universal ballast control circuit of claim 1, wherein the source comprises a microcontroller and a first digital-to-analog converter coupled to the microcontroller for generating said first DC voltage signal for controlling the magnitude of the first DC voltage signal.

3. The universal ballast control circuit of claim 1, wherein the controller comprises a microcontroller and a second digital-to-analog converter coupled to the microcontroller for generating a second DC voltage signal for controlling the frequency of the periodic analog voltage signal.

4. The universal ballast control circuit of claim 1, wherein the processor comprises a comparator circuit for comparing said first waveform with said second waveform.

5. The universal ballast control circuit of claim 4, wherein the comparator circuit generates a first voltage level when the first waveform is less than the second waveform and generating a second voltage level when the first waveform is greater than the second waveform.

6. The universal ballast control circuit of claim 1, wherein the generator comprises a timer circuit coupled to a current source and a capacitor such that a sawtooth voltage signal is produced across the capacitor.

7. The universal ballast control circuit of claim 1, wherein the controller comprises a microcontroller and first and second digital-to- analog converters coupled to the microcontroller for generating first and second DC control voltage signals.

8. The universal ballast control circuit of claim 7, wherein the generator comprises a capacitor coupled to a current source and a current sink such that the capacitor charges with current in accordance with said first DC control voltage signal applied to the current source and the capacitor discharges current in accordance with said second DC control voltage signal applied to the current sink such that said periodic analog voltage signal is generated across the capacitor and such that the shape of said first waveform is controlled by said first and second DC control voltage signals.

9. The universal ballast control circuit of claim 1, wherein the source comprises a timer circuit which internally generates said first DC voltage signal and a second DC voltage signal having a third waveform.

10. The universal ballast control circuit of claim 9, wherein the processor comprises said timer circuit for comparing said first waveform with said second waveform and for comparing said first waveform with said third waveform.

11. The universal ballast control circuit of claim 10, wherein said timer circuit generates a first voltage level when the first waveform rises above said second waveform and a second voltage level when the first waveform falls below said third waveform.

12. The universal ballast control circuit of claim 2 or 7, wherein said microcontroller is a low speed microcontroller having a processing speed of up to 8 megahertz.

13. The universal ballast control circuit of claim 2 or 7, wherein the power circuit comprises a half-bridge output to provide operational power to said microcontroller.

14. The universal ballast control circuit of claim 2 or 7, wherein the power circuit comprises a boost inductor to provide operational power to said microcontroller.

15. The universal ballast control circuit of claim 2 or 7, wherein the power circuit comprises a dedicated miniature switch mode power supply to provide operational power to said microcontroller.

16. A universal ballast control circuit for use with a power circuit coupled to an AC source for outputting a high frequency AC signal and a coupling circuit coupled to the power circuit for applying the AC signal to any one of a plurality of gas discharge lamp types, said control circuit comprising: (a) a generator for generating a periodic analog voltage signal having a first waveform;

(b) a controller for controlling the shape of said first waveform; and (c) a comparator for comparing the periodic analog voltage signal with at least one DC voltage and for generating a control voltage signal for varying the duty cycle and frequency of the AC signal.

17. The universal ballast control circuit of claim 16, wherein the controller comprises a microcontroller and first and second digital-to- analog converters coupled to the microcontroller for generating first and second DC control voltage signals.

18. The universal ballast control circuit of claim 17, wherein the generator comprises a capacitor coupled to a current source and a current sink such that the capacitor charges with current in accordance with said first DC control voltage signal applied to the current source and the capacitor discharges current in accordance with said second DC control voltage signal applied to the current sink such that said periodic analog voltage signal is generated across the capacitor and such that the shape of said first waveform is controlled by said first and second DC control voltage signals.

19. The universal ballast control circuit of claim 16, wherein the comparator comprises an oscillator circuit for generating first and second DC voltages, for comparing said first waveform with first and second DC voltages, and for generating a first voltage level when the first waveform rises above said first DC voltage and a second voltage level when the first waveform drops below said second DC voltage.

20. The universal ballast control circuit of claim 17 wherein said microcontroller is a low speed microcontroller having a processing speed of up to 8 megahertz.

21. A method of powering any one of a plurality of gas discharge lamp types, each lamp type having a predetermined set of lamp characteristics, said method comprising the steps of:

(a) producing a high frequency AC signal;

(b) applying the AC signal to the lamp;

(c) generating a periodic analog voltage signal having a first waveform; (d) generating a DC voltage signal having a second waveform;

(e) controlling the frequency of the periodic analog voltage signal;

(f) controlling the magnitude of the DC voltage signal;

(g) varying the duty cycle and frequency of the AC signal based on a comparison of the first and second waveforms.

22. A method of powering any one of a plurality of gas discharge lamp types, each lamp type having a predetermined set of lamp characteristics, said method comprising the steps of:

(a) producing a high frequency AC signal; (b) applying the AC signal to the lamp;

(c) generating a periodic analog voltage signal having a first waveform;

(d) controlling the shape of the first waveform;

(e) varying the duty cycle and frequency of the AC signal based on a comparison of first waveform and at least one DC threshold voltage.

23. A method of controlling the output voltage of a boost converter of a gas-discharge lighting ballast, said method comprising the steps of: (a) applying a DC signal to a power switch to produce a boost converter output voltage;

(b) generating a periodic analog voltage signal having a first waveform; (c) controlling the frequency of the periodic analog voltage signal and the magnitude of the DC voltage signal;

(d) comparing the first waveform with the boost converter output voltage; and