[go: up one dir, main page]
More Web Proxy on the site http://driver.im/

TW200945953A - Phase-control dimming electronic ballast system and the control method thereof - Google Patents

Phase-control dimming electronic ballast system and the control method thereof Download PDF

Info

Publication number
TW200945953A
TW200945953A TW097114441A TW97114441A TW200945953A TW 200945953 A TW200945953 A TW 200945953A TW 097114441 A TW097114441 A TW 097114441A TW 97114441 A TW97114441 A TW 97114441A TW 200945953 A TW200945953 A TW 200945953A
Authority
TW
Taiwan
Prior art keywords
phase
voltage
switch
lamp
converter
Prior art date
Application number
TW097114441A
Other languages
Chinese (zh)
Inventor
Yu-Kai Chen
yong-jun Wu
Wen-Yang Wang
jin-xiong Zhang
Original Assignee
Fego Prec Ind Co Ltd
Priority date (The priority date is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the date listed.)
Filing date
Publication date
Application filed by Fego Prec Ind Co Ltd filed Critical Fego Prec Ind Co Ltd
Priority to TW097114441A priority Critical patent/TW200945953A/en
Priority to US12/216,656 priority patent/US20090261744A1/en
Publication of TW200945953A publication Critical patent/TW200945953A/en

Links

Classifications

    • HELECTRICITY
    • H05ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05BELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14Circuit arrangements
    • H05B41/36Controlling
    • H05B41/38Controlling the intensity of light
    • H05B41/39Controlling the intensity of light continuously
    • H05B41/392Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor
    • H05B41/3921Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations
    • H05B41/3925Controlling the intensity of light continuously using semiconductor devices, e.g. thyristor with possibility of light intensity variations by frequency variation

Landscapes

  • Discharge-Lamp Control Circuits And Pulse- Feed Circuits (AREA)
  • Circuit Arrangements For Discharge Lamps (AREA)

Abstract

A phase-control dimming electronic ballast system and the control method thereof, wherein the system includes a phase controller, a converter, an inverter and a system controller. Moreover, the system controller senses a firing angle from the phase controller, and adjusts the output voltage of the converter and the switching frequency of the inverter to achieve the operation of dimming.

Description

200945953 九、發明說明: 【發明所屬之技術領域】 一錄係關於1相位調光控制系統及其方法,尤指 控制系統及控制方法Γ 觸發角’而達到線性調光的 【先前技術】 由於現在人們對照明的需求不再尸 β 足,同時還要可隨著枣产 先線疋否充 ❿ 冑境场同’來調整所需光線的明 、能源浪費’因此發展可調光的照明系 期。第:A 光方式包括有調頻、調壓及調責任週 調光f子安定轉構示意®。第一 β 架構示意圖。第― 週先電子安定器_示意圖。第— = 電子安定器架構示意圖。 Η為TRIAC相位调光 ® ϋ目調頻、調壓、調責任週_方式需額外配 〇 f2相i細咖制線路,如調頻控制器1G、調壓控制器 任週期調變控制器14。前述中,觸 S =調=14都會根據一調光峨而控制 二早開關SrS2的切換’以對燈管[卿進行調光 罐調光訊號sl,以控制—電力轉㈣ϋ 《造__擔。料,在輸人炫=周 無須增::dTmc,而採用調相方式進行,先’則 200945953 播严、、㈣,,為科㈣疋相§普遍的,而且均使用於白 必:的Si普然而,白熾燈泡發光效率低,造成許多不 、,、/費,因此,白熾燈泡逐漸將由日光燈取代。 泡大於日光燈為4體放電燈,其發光機制與白熾燈 將产嘴力2 ’自熾燈泡只要在燈絲上有微小電壓電流即可 ❻ 氣體原子;光二燈是依靠燈管内部汞 放電燈時,產生先子而發S,在點免氣體 以使燈管點 Μ有高電壓方驗汞氣㈣子解離, 冗,廷南電壓有時需高達數百伏至千伏以上。 白熾二閘流體元件觀C在照明控制應用上,使用 為負i:A=?有燈泡纽發光問題’而㈣日光燈 過少,銓㈢閘^體元件丁以舵的觸發角(iiHngangle) ι^ϋλ;二t至燈官的電壓不夠高而遭遇燈管點不亮、調光 粑圍不大及X相低落的問題。 亮度較無問題: 泡如同電阻性負載’故控制燈泡 搭配傳統安定圍廣且可線性變化。但如果曰光燈 a本概认使用’操作在低頻60Hz或50Hz電源下, 重的5變、,阻性’燈管電流不是正弦波’且有嚴 度,調光性能會流體元件麗C實際的導通角 將會閘流體元件TRIAC相位控制日光燈發光, 時,日光产技下問題’ L閘流體元件TRIAC在較大觸發角 3饩技無法起動。2.功率因數低、調光範圍不大。 3.燈目調光變化為非線性,不容易調至所⑽亮度。4.在 200945953 低壳度時,會有調光線性度不佳及無零電壓切換的特性。 【發明内容】 有鑑於此,本發明提供一種相位調光控制系統及其方 法,其係在相位控制器之後採用一轉換器(c〇nverter')、 一換流器(Inverter)及一單晶片控制器來解決或改善前 述閘流體元件TRIAC相位控制日光燈發光所面臨到的問 題0200945953 IX. Description of the invention: [Technical field to which the invention pertains] One recording system relates to a 1-phase dimming control system and its method, especially a control system and a control method 触发 a firing angle 'to achieve linear dimming. People's demand for lighting is no longer sacred, but at the same time, it can be filled with the first line of the jujube. The embarrassing field is the same as 'to adjust the light and energy waste of the required light', thus developing a dimmable lighting system. . The first: A light mode includes frequency modulation, voltage regulation and duty cycle. Schematic diagram of the first β structure. The first - week first electronic ballast _ schematic. No. — = Schematic diagram of the electronic ballast architecture. Η TRIAC phase dimming ® 调 FM, voltage regulation, duty cycle _ mode requires additional 〇 f2 phase i fine coffee circuit, such as FM controller 1G, voltage regulator controller cycle controller 14. In the foregoing, the touch S = tune = 14 will control the switching of the early switch SrS2 according to a dimming ' 'to the lamp tube [Qing dimming tank dimming signal sl, to control - power transfer (four) ϋ . Material, in the loss of people = week does not need to increase:: dTmc, and the use of phase modulation, first 'then 200945953 broadcast strict,, (four), for the section (four) 疋 phase § universal, and are used in the white must: Si However, incandescent bulbs have low luminous efficiency, causing many inconveniences, and/or fees. Therefore, incandescent bulbs will gradually be replaced by fluorescent lamps. The bubble is larger than the fluorescent lamp for the 4-body discharge lamp, and the illumination mechanism and the incandescent lamp will produce the mouth force. 2 The self-illuminating bulb can be used as long as there is a small voltage current on the filament; the light two lamp is dependent on the internal mercury discharge lamp of the lamp tube. Produce the first son and send S, at the point of the gas to make the lamp point high voltage test mercury gas (four) sub-dissociation, redundant, the Tinnan voltage sometimes needs to be hundreds of volts to more than a thousand volts. The incandescent two-gate fluid component view C is used for lighting control applications, using negative i: A=? There is a bulb illuminating problem' and (4) the fluorescent lamp is too small, and the 触发(3) gate body component is rudder firing angle (iiHngangle) ι^ϋλ The voltage of the lamp is not high enough, and the problem that the lamp point is not bright, the dimming circle is not large, and the X phase is low is encountered. The brightness is less problematic: the bubble is like a resistive load, so the control bulb is matched with the traditional stability and can be linearly changed. However, if the Xenon lamp a is used to operate under the low frequency 60Hz or 50Hz power supply, the heavy 5 change, the resistive 'lamp current is not sine wave' and there is strictness, the dimming performance will be the fluid component Li C actual The conduction angle will illuminate the TRIAC phase control fluorescent lamp, when the solar energy production problem TRI's TRI fluid element TRIAC can not start at a larger firing angle. 2. The power factor is low and the dimming range is not large. 3. The dimming change of the lamp is nonlinear, and it is not easy to adjust to the brightness of (10). 4. In the low shell of 200945953, there will be characteristics of poor dimming linearity and zero voltage switching. SUMMARY OF THE INVENTION In view of this, the present invention provides a phase dimming control system and method thereof, which employs a converter (c〇nverter'), an inverter (Inverter), and a single chip after the phase controller. The controller solves or improves the problem faced by the aforementioned thyristor element TRIAC phase control fluorescent lamp illumination

一本發明的相位調光控制系統,用以線性調整一燈管的 ^度,其包括有-相位控制器、一單晶月控制器、—整流 ί 1Γ轉換器及—換流器。其中,相位控制11根據一相位 調整一交流電壓的大小。單晶片控制器耦接於 ^工'盜’用以檢測相位觸發角,並且根 角 ?,整流該交流電壓,以;二=相= 於簡信號, 壓成為—直流鏈電壓。換流器^ 於^曰片控制盗、轉換器及燈管,係受控於高頻待,= 調頻/式調變直流鏈電壓成為—管電壓給燈“二 吞周變2流鍵電壓的大】矛=、士 、 夫》 時’係採用 制,以擴大調域岐調先控 調光線性衫佳或開關 或調壓,所造成 地控制責任週期和切換頻率,還可m問題。另外,適當 了進-步:ίϊ的詳細說明皆為示範性質,是為 j逗步說明本發明的申諸直 只疋马 他目的與優點,將在後續的^圍。而有關本發明的其 便躓的5兒明與圖示加以闞述。 200945953 【實施方式】 請參考第二圖,為本發明的相位調光控制 意圖。本發明的相位調光控制系統2用以線性調整—^ Lamp 0¾光度,相位調光控儀統2包財 2。、-整流器22、一轉換器24、一換流 = 控制器28。 早曰日片 復參考第二圖,相位控制器2〇包括—可 二流體元件丁RIAC,其中相位控制器2〇利用調整可變電 R,以改變閘流體元件TRIA C觸發一交流電壓v 週期的相位觸發角α,進而根據相 = 電壓-的大小。同時,整流灣接於 係攸相位控制器20取得調整後的交流電壓, 士 電壓VaC進行整流操作,用以輸出-輸入電壓Vln。另^ 早曰0曰以制器28輕接於相位控制器2〇 , 〇檢測出相位觸發角α,並且根據該 ;:, PWM信號S1與—高頻信號%。 Μα輸出― 復參考第二圖,轉換器24耦接於單晶片於 ^器22,係從單晶片控制器28接收簡信=。= 於PWM信號S1,而以調壓方式調變輸入電壓: =二直流鏈? Vdc。另外,換流器%減於單晶片控 f、轉換》24及燈fLamp,其中,換流H26從單Γ ^制器28接收高頻信號S2,並且受控於高鮮=日日 =調頻方式調變直流鏈電屋Vdc成 : ,吏用。另外,單晶片控制 鳴器,,並於相位觸發角α大於:η二蜂 制蜂鳴器29動作,以提仲& 」角(未“不)^控 料吨供燈管Lamp亮度達到最低段時的 200945953 響聲警告。 參考第三圖,為本發明的相位控制器電路示竟 位控制器20包括了可變電阻VR、閘流體元件TRI^ =件_及電容c。相位控制器2G主要是利用調^ 吏電阻的電阻值大小’以改變閘流體元件TRIAC於交漭 電屢,每半週期的相位觸發角α,以達成電壓控制 中’若負載呈顧性,其輸出波形如第四圖所示 ς 控制盗20輪出的平均電壓Vavg可由公式(1)算出: 在公式(1)中,Vm為交流電壓Vac的峰值電壓。另 相位控制^§ 2〇輪出的平均電壓Vavg與相 係曲線可由第五圖所示。由第五圖可以看出,;目 24〇輸出的平均電壓Vavg會隨相位觸發角α的不同而改 變,因此’可利用相位控制器20來達到調壓調光的功能。 復參考第二圖,轉換器24可以為一返馳式轉換器A phase dimming control system for linearly adjusting a degree of a lamp includes a phase-phase controller, a single crystal month controller, a rectifying converter, and an inverter. The phase control 11 adjusts the magnitude of an alternating voltage according to a phase. The single-chip controller is coupled to the 'spoof' to detect the phase firing angle, and the root angle ?, rectifies the alternating voltage, and the second = phase = the simple signal, the voltage becomes the DC link voltage. Inverter ^ control the thief, converter and lamp, is controlled by high frequency to wait, = FM / type modulation DC link voltage becomes - tube voltage to the lamp "two swallowing cycle 2 flow key voltage Large] spear =, Shi, husband" when the system is adopted to expand the adjustment of the domain, the first control dimming linear shirt is good or switch or voltage regulation, resulting in control responsibility cycle and switching frequency, but also m problem. The appropriate step-by-step: 详细 ϊ detailed descriptions are exemplary, is to explain the purpose and advantages of the invention for the purpose of j, and will be in the follow-up Please refer to the second figure for the phase dimming control intent of the present invention. The phase dimming control system 2 of the present invention is used for linear adjustment - ^ Lamp 03⁄4 Luminosity, phase dimming control system 2 Bao Cai 2, - rectifier 22, a converter 24, a commutation = controller 28. As early as the day after the second reference to the second picture, the phase controller 2 〇 includes - two Fluid element DRI, wherein the phase controller 2 uses the variable power R to change the thyristor The body component TERA C triggers the phase trigger angle α of an alternating voltage v cycle, and further according to the phase = voltage -. At the same time, the rectifier bank is connected to the system phase controller 20 to obtain the adjusted AC voltage, and the voltage VaC is rectified. For outputting - input voltage Vln. Another ^ early 0曰 to controller 28 is connected to phase controller 2〇, 〇 detects phase firing angle α, and according to this;:, PWM signal S1 and – high frequency signal Μα Output - Referring to the second figure, the converter 24 is coupled to the single-chip device 22, receiving a short message from the single-chip controller 28 === PWM signal S1, and modulating the input in a voltage-regulating manner Voltage: = two DC chains? Vdc. In addition, the inverter % is reduced to the single chip control f, the conversion "24" and the lamp fLamp, wherein the commutation H26 receives the high frequency signal S2 from the single controller 28 and is controlled In the high fresh = day = frequency modulation mode DC link electric house Vdc into:, use. In addition, the single-chip control sounder, and the phase trigger angle α is greater than: η two bee buzzer 29 action,提中& 角" (not "not" ^ control material ton for the lamp to reach the lowest point of the lamp 200945953 Sounding warning. Referring to the third figure, the phase controller circuit of the present invention shows that the position controller 20 includes a variable resistor VR, a thyristor element TRI^=piece_ and a capacitor c. The phase controller 2G mainly utilizes the adjustment ^ The resistance value of the 吏 resistor is 'to change the thyristor element TRIAC at the crossover frequency, and the phase trigger angle α is obtained every half cycle to achieve voltage control. If the load is considered, the output waveform is as shown in the fourth figure.平均 The average voltage Vavg of the control robber 20 is calculated by the formula (1): In the formula (1), Vm is the peak voltage of the AC voltage Vac. The average voltage Vavg and the phase curve of the phase control ^§ 2〇 can be shown in the fifth figure. As can be seen from the fifth figure, the average voltage Vavg of the output of the target 24V varies with the phase firing angle α, so that the phase controller 20 can be used to achieve the function of voltage regulation and dimming. Referring back to the second figure, the converter 24 can be a flyback converter

(Flyback Converter)或一昇壓轉換器(Β〇〇3ΐ Converter)。轉換器24經由整流器22耦接在相位控制器 20的後級,係具有電阻特性。轉換器24從整流器22取^ 輸入電壓Vin,以提供穩定的直流鏈電壓Vdc。另外,當相 位控制器20的相位觸發角α為〇時轉換器24操作在不連 續導通模式(DCM Mode)以作為功率因數校正的用途,其 輪入電壓Vin與直流鏈電壓Vdc的關係如下公式(2)所示: ..(2) 200945953(Flyback Converter) or a boost converter (Β〇〇3ΐ Converter). Converter 24 is coupled to the subsequent stage of phase controller 20 via rectifier 22 and has resistive characteristics. Converter 24 takes input voltage Vin from rectifier 22 to provide a stable DC link voltage Vdc. In addition, when the phase trigger angle α of the phase controller 20 is 〇, the converter 24 operates in the discontinuous conduction mode (DCM Mode) for power factor correction, and the relationship between the wheel-in voltage Vin and the DC link voltage Vdc is as follows. (2) shown: ..(2) 200945953

在公式⑵中,D為轉換器24的功率開關qi的責 期(duty cycle),Lm為轉換器24的電感值,了 24的功率開關Sl的切換週期,RL為轉換器2 = 電阻值。 文双貝m ❹ Ο 雖然相位控制益20可以單獨執行調光的功能,但、 從第五圖中可以觀察得知,相位控制器2 〇所輪 一^ 壓Vavg並非隨相位觸發角α呈現線性的變化。因此,=電 使調光有線性的變化,可以透過控制轉換器24輸出的y 鏈電壓Vdc,使其舆相位觸發角α成比例關係,如 ^In equation (2), D is the duty cycle of the power switch qi of the converter 24, Lm is the inductance value of the converter 24, the switching period of the power switch S1 of 24, and RL is the converter 2 = resistance value. Wen Shuangbei m ❹ Ο Although the phase control benefit 20 can perform the dimming function separately, it can be observed from the fifth figure that the phase controller 2 〇VVg does not appear linear with the phase trigger angle α. The change. Therefore, the = dimming has a linear change, and the y-chain voltage Vdc outputted by the converter 24 can be controlled to have a proportional relationship with the phase-trigger angle α, such as ^

V ...(3)V ...(3)

直流=:而==管角::大:產生較低' 由轉換器24在燈管Lamp起°故’可; 的功率開_大轉換器、 於點亮燈管L_。 為^直流鏈電壓Vdc,W 配合第二圖,參考第丄 管之等效電路示意圖。本發明圖的換 並聯連接。如第1 =式串聯譜振換流器託與燈管Lan ^PL -τ-,,、圖所不,燈管電壓Vump、電流I—及:^ 羊P—可由下列公式⑷至(6)得知: (4)200945953 ^Lamp~ κ (if)2 \2 + (fs)2 L UJ ) {f〇QJ v — LampDC =: and == tube angle:: large: produces a lower power converter _ large converter from the lamp 24 at the lamp Lamp; and illuminates the lamp tube L_. For the DC link voltage Vdc, W with the second diagram, refer to the equivalent circuit diagram of the second tube. The parallel connection of the Figure of the present invention. For example, the 1st-type series-spectral converter converter and the lamp Lan ^PL -τ-,,, the figure, the lamp voltage Vump, the current I- and: ^ sheep P - can be given by the following formulas (4) to (6) Learned: (4)200945953 ^Lamp~ κ (if)2 \2 + (fs)2 L UJ ) {f〇QJ v — Lamp

D 八 LampD 八 Lamp

.(5) ...(6) 在公式(4)-(6)中,Vs為方波電壓(± Vdc/2)的均方根 值,fs為換流器26的切換頻率,RumP為燈管Lamp等效電 阻,特性阻抗,自然頻率,其中,Lr為諧振電感值, Cr為諧振電容值。 由公式(4)至公式(6)可得知,燈管功率Pl_與直流鏈 電壓Vdc或換流器26的切換頻率fs有關係,如第七圖或 第八圖所示(模擬燈管採用OSRAMT8-32W的燈管),其關係 式為(PLamP (Vdc,fs)),如此,可以藉由調整直流鏈電壓Vdc 的大小或調整換流器26的切換頻率fs來改變燈管功率 PLamp ’以達到调光的功能。 同時,若以方波電壓(± Vdc/2)的均方根值Vs作為參 考相位,則諧振網路的電流iLr之相位0可由公式(7)表 示:(5) (6) In equations (4)-(6), Vs is the root mean square value of the square wave voltage (±Vdc/2), fs is the switching frequency of the inverter 26, and RumP is Lamp Lamp equivalent resistance, characteristic impedance, natural frequency, where Lr is the resonant inductance value and Cr is the resonant capacitance value. It can be known from formula (4) to formula (6) that the lamp power Pl_ is related to the DC link voltage Vdc or the switching frequency fs of the inverter 26, as shown in the seventh or eighth figure (analog lamp) The lamp of OSRAMT8-32W is used, and the relationship is (PLamP (Vdc, fs)). Thus, the lamp power PLamp can be changed by adjusting the magnitude of the DC link voltage Vdc or adjusting the switching frequency fs of the inverter 26. 'To achieve the function of dimming. Meanwhile, if the rms value Vs of the square wave voltage (± Vdc/2) is taken as the reference phase, the phase 0 of the current iLr of the resonant network can be expressed by the formula (7):

fs Li fsQ f〇Q { f〇 fsQ f〇 ...(7) 由於燈管Lamp的等效電阻Rump值會隨燈管功率Pump 不同而改變,且為負電阻特性,故在調光過程中諧振電流 11 200945953 iLr的相位Θ會改變,装中,批 流鏈電壓Vdc或換流器洸的# 流iLr的相位0與直 圖或第十圖所示。° 、1、頻率fs的關係,如第九 圖,單晶片控制器28從相位控制器20檢 s 並且根據相位觸發^輸_4 S1給轉換斋24,以控制轉換器 。就 ^進而調變直流鍵概的電壓力= =位觸發角。輸出高頻信號S2給; 率:一切換“ =::24中的功率開 力率開關Q2、Q3具有零電壓切換的特性。 ’ =考第二圖’當本發明的相位調 ΐϋΓΙΙΤ讀相位觸發角α,進而輸出―初― =.S1給轉換器24,轉換器24以調壓方式調變 , ❹ f νιη,—初始直流鏈電壓Vdc,約_。 控制器28再送出預熱之高頻訊仏二早日日 = 調變初始直流鏈二二 間,約1秒;Γ:5: ::P進行預熱。燈管Lamp經預‘時 給Hi 送出起動之高頻訊號S2 電壓他,以料彳換流1126調變初始直流鏈 卞供-啟動#電壓給燈管_進行點亮。 位觸ΐί 再次檢測輸入電壓Vin的相 頻訊遽S2。合適的剛訊號幻控制轉換器%產生適當: 12 200945953 直流鏈電壓Vdc。而合適的高頻 切換,用轉細的直_==^器26的 管L卿使用,進而達到線性調先的目的成《給麼 根據前述,本發_相位調光㈣錢 先將直流鏈電壓Vdc升壓i Α $ μ ^夸, θ ι至300ν,再使換流器26工作, 疋使不S此%輸入電壓Vin的相位觸發角α j 保燈管—點亮,並避免因燈管L_無法^ =Fs Li fsQ f〇Q { f〇fsQ f〇...(7) Since the equivalent resistance Rump value of the lamp Lamp changes with the lamp power pump and is negative resistance, it is in the dimming process. The phase Θ of the resonant current 11 200945953 iLr will change, loading, the batch chain voltage Vdc or the phase 0 of the current stream iLr of the converter 与 is shown in the figure or the tenth figure. The relationship between ° and 1, frequency fs, as in the ninth diagram, the single-chip controller 28 checks s from the phase controller 20 and converts the conversion 24 according to the phase trigger _4 S1 to control the converter. Then ^ adjusts the voltage of the DC key to the voltage = = bit firing angle. Output high frequency signal S2 to; rate: one switch "=::24 power opening rate switch Q2, Q3 has zero voltage switching characteristics. ' = test second picture 'When the phase of the invention is tuned to read phase trigger Angle α, and then output "initial" =.S1 to converter 24, converter 24 is modulated by voltage regulation, ❹ f νιη, - initial DC link voltage Vdc, about _. Controller 28 sends preheated high frequency Newsletter 2 early = Modification of the initial DC link 22, about 1 second; Γ: 5: ::P for preheating. Lamp Lamp is pre-sent to Hi to send the starting high frequency signal S2 voltage to him彳Commutation 1126 Modulates the initial DC link 卞Supply-start# voltage to the lamp _ to illuminate. Bit ΐ ί Detects the phase frequency signal S2 of the input voltage Vin again. The appropriate sigma control converter % generates appropriate: 12 200945953 DC link voltage Vdc. And the appropriate high-frequency switching, using the thin-lined _==^ 26 tube L Qing, and then achieve the purpose of linear tuning first, according to the above, the hair _ phase adjustment Light (4) money first boosts the DC link voltage Vdc i Α $ μ ^ boast, θ ι to 300 ν, and then the inverter 26 Do, do not S this % input voltage Vin phase firing angle α j to ensure that the lamp - light, and avoid because the lamp L_ can not ^ =

Ο 統2有:生故障之虞。在本發明的系統2操作過 二晶片控制器28同時也會檢測系統2中各電路單元, 保護等。 心故障_、過電壓保護、過電流 復^弟七圖與第九圖,當直流鏈電壓·降低時, ΪΓΓ:Ρ=:降,但諧振電流iLr的相位θ有增加 勢同k,翏考弟十圖,提高換流器26的切換頻率fs ΐ流iLr的相位Θ更為落後’這正可彌補直流 ,電壓Vdc降低時的缺撼。另外,參考第八圖,增加換流 瘭26的切換頻率fs將會使燈管功率ρ^ρ降低,但在很大 的頻率變動範圍裡(如45kHz〜64kHz),燈管功率變化 不多’因此實際燈管Lamp的亮度變化較不明顯。此時搭配 直流鏈電壓Vdc調降,則有較好的線性調光效果。 為使燈管Lamp在調光時有較線性及明顯的變化,以 達舒適調光目的,同時避免過高的損失。本發明的相位調 光控制方法係採用調壓及調頻方法合併使用,當調光時, 檢測此時輸入電壓Vin的相位觸發角〇:,並且依據相位觸 發角α:的大小,線性比例地改變直流鏈電壓Vdc,且同時 緣性調整換流器26的切換頻率fs’以調變直流鏈電壓Vdc 13 200945953 成為官電壓VLamP給燈管Lamp,進而線性調整燈管Lamp的 光度。 參考第十一A圖,為本發明的燈管功率與直流鏈電壓 =關係曲線示意圖。參考第十一 B圖,為本發明的諧振電 ,的相位與直流鏈電壓的關係曲線示意圖。其中,Afs為 每降低IV的直流鏈電壓Vdc,換流器之切換頻率fs的增 加量,且么化1</^32<^化3<4化4<么仕5。 ❹ ❹ 本發明的相位調光控制系統2採用調壓及調頻合併使 用,行5周光,此方式雖然具有互補作用,但從第十一 A圖 與第十-B®所示’本發明的相位調光控制⑽2在調光 蚪,,須有適當的△ f s,才能達到最佳化的操作。頻率的 改變里Afs較大易造成燈管功率非線性變化,反之,若△ fs較小燈管功率p—的變化雖較為雜化,但頻率增加所 =諧振電流lLr相位Θ的落後f ’卻無法克服直流鏈電 斤造成諧振電流iLr相位θ的增加量。因此,本發 明調光控制系統2 f依據所要調光 料—B財,挑選合適轉作曲線,以獲= 率最佳改料可#作最佳範圍或頻 -個控制系統及其方法’實際製 調光’以驗證本發明所提之論述 燈管功率的_〜10%,相彳 ^中燈吕調先範圍 圍:45。翁,昇壓轉的相位觸發角〇可控-圍《。當直流鏈電壓變化' fs設定在侧2,此時Sf蝴作。每降,_:= 14 200945953 電壓Vdc,切換頻率fs增加30Ηζ(Δ fs=30V)。 請參考第十二圖,為本發明的燈管功率與直流鏈電壓 的實測關係曲線示意圖。從第十二圖可以看出,同時採用 調壓及調頻調光的方法,在燈管調光過程有良好的線性關 係,很容易調至任一亮度。同時,第十三A圖為本發明的 燈管操作在滿載時,換流器26的功率開關Q2、Q3的電壓 VDS與電流IDS的量測波形示意圖。第十三B圖為本發明 的燈管操作在輕載時,換流器26的功率開關Q2、Q3的電 壓VDS與電流IDS的量測波形示意圖。根據第十三A圖與 第十三B圖所示,不論在滿載或輕載,換流器26中的諧振 網路(Lr、Cr)都成電感性,且功率開關 Q2、Q3具有零電 壓切換(ZVS)的特性,因此在調光的過程都有較高的效率。 參考第十四圖,為本發明結合轉換器與換流器的單級 架構示意圖。在第十四圖中,結合返驰式轉換器與半橋式 串聯諳振換流器的單級架構3,係根據第二圖中兩級架構 的返馳式轉換器24與半橋式串聯諧振換流器26經過電路 簡化的原則所產生的電路架構。該單級架構3包括有一變 壓器Tr、一返驰二極體D5、一第一開關Q2、一第二開關 Q3、一 LC諧振網路30、一第一電容C3及一第二電容C4。 其中,變壓器Tr具有一次側繞組P1與一二次側繞組P2, 且該一次侧繞組P1用以接收輸入電壓Vin。返馳二極體D5 耦接於變壓器Tr的二次侧繞組P2。第一開關Q2的第一端 透過反馳二極體D5耦接於變壓器Tr的二次側繞組P2,且 第一開關Q2的第二端透過一二極體D6耦接於該變壓器Tr 的一次側繞組P1。第二開關Q3耦接於變壓器Tr的二次側 繞組P2〇LC諧振網路30耦接於第一開關Q2、第二開關Q3 15 200945953 及燈管Lamp。第一電容C3搞 — 網路30。第二電容; 開關Q2與LC諧振 ;30 〇 _接於第二開_與IX譜振網路 另外第十五圖,為本發明另一6士人 的單級架構示意圖。在第十五圖中的單。=器舆=器 了昇壓式轉換器(未標 ^構4,係簡化 衍生出來的單級架構器%所 一第二開關q3、_儲能、、一匕括有第一開關Q2、 ❹-電容及-第二電容C4'”一,第 路、-第 於第-開關Q2。儲能電感L的第一耗接 接於第,關二二 之中間點。:LC諧振網路4〇耦接於 市刪㈧ Q3之中間點以及燈管Lamp。第—電容;A 一 f二開關 Q2與LC:諧振網路40。第二電容 H = LC諧振網路4〇。 设%弟一開關Q3與 綜上所述’本發明的相位調光控詞 ❹ ^係採用調變直流物和換流器的切換頻 光控制,以擴大調光範圍及避免只 頻、成 或開關無賴购 ,、可订H另外,適當地控制責任週期和切換頻 作為功率雜的校正,Μ述控制和調變及系 機制及控制電路數位化,整合成—精緻的系統複雜的控制 按,以上所述,僅為本發明最佳之具體實施例,惟本 發明之特徵並不侷限於此’任何熟悉該項技藝者在本發明 之領域内,可輕易思及之變化或修飾,皆可涵蓋在以;本 16 200945953 案之專利範圍。 【圖式簡單說明】 弟'一 A圖為調頻調光電子安定益架構不意圖, 第一B圖調壓調光電子安定器架構示意圖; 第一C圖調責任週期調光電子安定器架構示意圖; 第一 D圖為TRIAC相位調光電子安定器架構示意圖; 第二圖為本發明的相位調光控制系統方塊示意圖 第三圖為本發明的相位控制器電路示意圖; 第四圖為本發明的輸入電壓波形示意圖’; 第五圖為本發明的平均電壓與相位觸發角關係示意 圖; 第六圖為本發明的換流器並聯燈管之等校電路示意 圖; 第七圖為本發明的燈管功率與直流鏈電壓關係示意 圖; 第八亂為本發明的燈管功率與換流器的切換頻率關 係不意圖, 第九圖為本發明的諧振電流相位與直流鏈電壓關係 不意圖, 第十圖為本發明的諳振電流相位與換流器的切換頻 率關係示意圖; 第十一 A圖為本發明的燈管功率與直流鏈電壓的關係 曲線不意圖, 第十一 B圖為本發明的諳振電流的相位與直流鏈電壓 的關係曲線示意圖; 17 200945953 第十二圖為本發明的燈管功率與直流鏈電壓的實測 關係曲線不意圖_, 第十三A圖為本發明滿載時功率開關的電壓與電流的 量測波形示意圖; 第十三B圖為本發明輕載時功率開關的電壓與電流的 量測波形示意圖; 第十四圖為本發明結合轉換器與換流器的單級架構 不意圖,及 〇 第十五圖為本發明另一結合轉換器與換流器的單.級 架構不意圖。 【主要元件符號說明】 習知:Ο 2 2 has: 生 fault. When the system 2 of the present invention operates the two-chip controller 28, it also detects each circuit unit in the system 2, protection, and the like. Heart failure_, overvoltage protection, overcurrent recovery, and the seventh and ninth diagrams, when the DC link voltage decreases, ΪΓΓ:Ρ=: drop, but the phase θ of the resonant current iLr increases with the same k, In the tenth figure, the switching frequency fs of the inverter 26 is increased, and the phase Θ of the turbulent flow iLr is further lags behind. This can compensate for the shortage of DC and the decrease of the voltage Vdc. In addition, referring to the eighth figure, increasing the switching frequency fs of the commutating port 26 will lower the lamp power ρ^ρ, but in a large frequency variation range (such as 45 kHz to 64 kHz), the lamp power does not change much' Therefore, the brightness change of the actual lamp Lamp is less obvious. At this time, with the DC link voltage Vdc down, there is a better linear dimming effect. In order to make the lamp Lamp have a more linear and obvious change during dimming, it can achieve the purpose of comfortable dimming while avoiding excessive loss. The phase dimming control method of the present invention uses a combination of voltage regulation and frequency modulation methods. When dimming, the phase trigger angle 〇 of the input voltage Vin at this time is detected, and linearly proportionally changes according to the magnitude of the phase trigger angle α: The DC link voltage Vdc is adjusted at the same time to adjust the switching frequency fs' of the inverter 26 to modulate the DC link voltage Vdc 13 200945953 to become the official voltage VLamP to the lamp Lamp, thereby linearly adjusting the illuminance of the lamp Lamp. Referring to FIG. 11A, it is a schematic diagram of the relationship between the lamp power and the DC link voltage of the present invention. Referring to FIG. 11B, it is a schematic diagram showing the relationship between the phase of the resonant electric current and the DC link voltage of the present invention. Wherein, Afs is the DC link voltage Vdc for each IV reduction, and the switching frequency fs of the inverter is increased, and the change 1</^32<^3<4<4<4<相位 ❹ The phase dimming control system 2 of the present invention uses a combination of voltage regulation and frequency modulation, and performs 5 weeks of light. Although this method has complementary functions, the invention of the present invention is shown in FIG. 11A and FIG. The phase dimming control (10) 2 must have an appropriate Δ fs in the dimming mode to achieve an optimized operation. In the change of frequency, the Afs is large, which may cause the lamp power to change nonlinearly. On the contrary, if the change of the lamp power p- is smaller than △ fs, the frequency increases, and the resonant current lLr phase Θ is backward. It is impossible to overcome the increase in the phase θ of the resonant current iLr caused by the DC link. Therefore, the dimming control system 2 f of the present invention selects a suitable conversion curve according to the desired dimming material, and obtains the optimal conversion rate for the optimal range or frequency control system and its method. To adjust the light' to verify the power of the lamp of the present invention is _~10%, and the phase of the lamp is in the range of 45. Weng, the phase-triggered angle of the boosting turn can be controlled - around. When the DC link voltage changes 'fs' is set to side 2, then Sf is butterflyd. Every drop, _:= 14 200945953 Voltage Vdc, switching frequency fs increased by 30 Ηζ (Δ fs = 30V). Please refer to the twelfth figure, which is a schematic diagram showing the relationship between the lamp power and the DC link voltage of the present invention. It can be seen from the twelfth figure that the method of voltage regulation and frequency modulation dimming has a good linear relationship in the lamp dimming process, and it is easy to adjust to any brightness. Meanwhile, Fig. 13A is a schematic diagram showing the measurement waveforms of the voltage VDS and the current IDS of the power switches Q2 and Q3 of the inverter 26 when the lamp operation of the present invention is at full load. Fig. 13B is a schematic diagram showing the measurement waveforms of the voltage VDS and the current IDS of the power switches Q2 and Q3 of the inverter 26 when the lamp of the present invention is operated at a light load. According to the thirteenth Ath and thirteenth B, the resonant network (Lr, Cr) in the inverter 26 is inductive, whether at full load or light load, and the power switches Q2, Q3 have zero voltage. Switching (ZVS) characteristics, therefore, has a high efficiency in the dimming process. Referring to Fig. 14, a schematic diagram of a single stage architecture combining a converter and an inverter according to the present invention. In the fourteenth figure, the single-stage architecture 3 combining the flyback converter and the half-bridge series resonant converter is connected in series with the half bridge according to the two-stage architecture of the flyback converter 24 in the second figure. The resonant converter 26 is circuit-generated by the principle of circuit simplification. The single-stage architecture 3 includes a transformer Tr, a flyback diode D5, a first switch Q2, a second switch Q3, an LC resonant network 30, a first capacitor C3, and a second capacitor C4. The transformer Tr has a primary side winding P1 and a secondary side winding P2, and the primary side winding P1 is for receiving the input voltage Vin. The flyback diode D5 is coupled to the secondary side winding P2 of the transformer Tr. The first end of the first switch Q2 is coupled to the secondary side winding P2 of the transformer Tr through the reverse polarity diode D5, and the second end of the first switch Q2 is coupled to the transformer Tr through a diode D6. Side winding P1. The second switch Q3 is coupled to the secondary side winding P2 of the transformer Tr. The LC resonant network 30 is coupled to the first switch Q2, the second switch Q3 15 200945953, and the lamp Lamp. The first capacitor C3 engages with the network 30. The second capacitor; the switch Q2 resonates with the LC; 30 〇 _ is connected to the second open_and IX spectral network. The fifteenth figure is a schematic diagram of a single-stage architecture of another 6-person of the present invention. The single in the fifteenth figure. = 舆 = device boost converter (not standard 4, is a simplified single-stage architecture, a second switch q3, _ energy storage, including a first switch Q2, ❹ - Capacitor and - second capacitor C4'" one, the first path, - the first switch - Q2. The first consumption of the energy storage inductor L is connected to the middle point of the second and second two. LC resonant network 4 It is coupled to the middle point of the city (8) Q3 and the lamp Lamp. The first capacitor, the A-f switch Q2 and the LC: the resonant network 40. The second capacitor H = the LC resonant network 4〇. Q3 and the above-mentioned 'phase dimming control word ❹ ^ adopts switching frequency control of modulated DC and inverter to expand the dimming range and avoid the frequency, formation or switch rogue purchase, In addition, the duty cycle and the switching frequency are appropriately controlled as the correction of the power miscellaneous, the control and modulation and the mechanism and the digitalization of the control circuit are described, and the integrated control is integrated into a sophisticated system. It is a preferred embodiment of the invention, but the features of the invention are not limited to the invention of any one skilled in the art. In the field, changes or modifications that can be easily thought of can be covered in the patent scope of this 16th 200945953 case. [Simple description of the picture] The brother's picture is the intention of the FM dimming electronic stability system. B is a schematic diagram of the structure of the voltage regulating electronic ballast; the first C diagram is a schematic diagram of the duty cycle dimming electronic ballast; the first D is a schematic diagram of the TRIAC phase dimming electronic ballast; the second figure is the phase of the invention The third diagram of the dimming control system is a schematic diagram of the phase controller circuit of the present invention; the fourth diagram is a schematic diagram of the input voltage waveform of the present invention; and the fifth diagram is a schematic diagram of the relationship between the average voltage and the phase firing angle of the present invention; The figure is a schematic diagram of the equal circuit of the inverter parallel lamp of the present invention; the seventh figure is a schematic diagram of the relationship between the lamp power and the DC link voltage of the present invention; the eighth disorder is the switching of the lamp power and the converter of the present invention The frequency relationship is not intended. The ninth figure is not intended to relate the resonant current phase to the DC link voltage. The tenth figure is the resonant current phase and commutation of the present invention. Schematic diagram of the switching frequency relationship; FIG. 11A is a schematic diagram of the relationship between the lamp power and the DC link voltage of the present invention, and FIG. 11B is a schematic diagram showing the relationship between the phase of the shimmering current and the DC link voltage of the present invention. 17 200945953 The twelfth figure is a schematic diagram of the measured relationship between the lamp power and the DC link voltage of the present invention. FIG. 13A is a schematic diagram of the measurement waveform of the voltage and current of the power switch at the full load of the present invention; The three-B diagram is a schematic diagram of the measurement waveforms of the voltage and current of the power switch at the time of light load of the present invention; the fourteenth figure is not intended to combine the single-stage architecture of the converter and the converter, and the fifteenth figure is Another single stage architecture incorporating a converter and an inverter is not intended. [Main component symbol description] Convention:

調頻控制器10 電力轉換器11 調壓控制器12 責任週期調變控制器14 ❹ 輸入交流電源AC 閘流體元件TRIAC 調光訊號SL 功率開關S1、S2 本發明: 相位調光控制系統2 相位控制器20 整流器22 18 200945953 轉換器24 換流器26 單晶片控制器28 蜂鳴器29 交流電壓Vac PWM信號S1 高頻信號S2 燈管Lamp ❹ 輸入電壓Vin 直流鏈電壓Vdc 管電壓Vl_ 功率開關Ql、Q2、Q3FM Controller 10 Power Converter 11 Voltage Regulator 12 Duty Cycle Modulation Controller 14 ❹ Input AC Power AC Gate Fluid Element TRIAC Dimming Signal SL Power Switch S1, S2 The present invention: Phase Dimming Control System 2 Phase Controller 20 Rectifier 22 18 200945953 Converter 24 Inverter 26 Single Chip Controller 28 Buzzer 29 AC Voltage Vac PWM Signal S1 High Frequency Signal S2 Lamp Lamp ❹ Input Voltage Vin DC Link Voltage Vdc Tube Voltage Vl_ Power Switch Ql, Q2 Q3

可變電阻VR 相位觸發角αVariable resistance VR phase firing angle α

閘流體元件TRIACBrake fluid element TRIAC

_ 燈管電壓VumP ❿ 電流I Lamp 方波電壓(± Vdc/2)的均方根值Vs 燈管等效電阻RumP 譜振電感值Lr 諧振電容值Cr 諳振網路的電流iLr 結合返馳式轉換器與半橋式串聯諧振換流器的單級 架構3 19 200945953 變壓器Tr 返馳二極體D5 第一開關Q2 第二開關Q3 LC諧振網路30、40 ^ 第一電容C3 第二電容C4 結合昇壓式轉換器與半橋式串聯諧振換流器的單級 ❹ 架構4_ Lamp voltage VumP 电流 Current I Lamp Square-wave voltage of the square wave voltage (± Vdc/2) Vs Lamp equivalent resistance RumP Spectrum inductance value Lr Resonant capacitance value Cr Current of the oscillation network iLr Combined with the flyback Single-stage architecture of converter and half-bridge series resonant converter 3 19 200945953 Transformer Tr Reversing diode D5 First switch Q2 Second switch Q3 LC resonant network 30, 40 ^ First capacitor C3 Second capacitor C4 Single stage 结合 architecture with a boost converter and a half-bridge series resonant converter 4

儲能電感L 20Energy storage inductor L 20

Claims (1)

200945953 十、申請專利範圍: L产種絲控制系統n線性調整—螢光燈管的光 :據一相位觸發角,以調整—交流電 一相位控制器, 壓的大小; -::曰:二控制器’耦接於該相位控制器,該單晶片控 ❹ ❹ =讀測該相位觸發角,並且根據該相位觸發角輸 一出二醫信號與一高頻信號; 角輸 ,机器_接於該相位控制器,該整流器整流該交 〜電壓,以及輸出一輸入電壓; ^換°°耦接於該單晶片控制器與該整流器,該轉 ί Ξ受控於該P WM信號,係以調壓方式調變該輸入 电堅成為一直流鍵電壓;及 器’輕接於該單晶片控制器、該轉換器及該燈 吕,該換流器受控於該高頻錢,細翻方式調 變該直流鏈電壓成為一管電壓給該燈管。 2. 如申請專·圍第丨項观之相_光控㈣統,其中 該相位控制器包括一可變電阻與一 TRIAC,其中該相位 =器利,調整該可變電阻值,以改變該TRuc觸發該 父>二電壓每半職㈣相賴發肖,或錢控之方式配 合單晶片來控制其相位觸發角。 3. 如申請專利範圍第i項所述之相位調光控制系統,其中 該換流1§為-半橋式串餐振換流器,該半橋式串聯讀 振換流器並聯於該燈管。 4. 如申請專利範圍第3項所述之相位調光控制系統,其中 21 200945953 該轉換器為一返馳式轉換器。 5. 如申請專利範圍第3項所述之相位調光控制系統,其中 該轉換器為一昇壓轉換器。 6. 如申請專利範圍第1項所述之相位調光控制系統,其中 該單晶片控制器耦接一蜂鳴器,並於該相位觸發角大於 一臨界角時控制該蜂鳴器動作。 7. 如申請專利範圍第1項所述之相位調光控制系統,其中 該PWM信號控制該轉換器中功率開關的責任週期,以調 變該直流鏈電壓的大小。 8. 如申請專利範圍第7項所述之相位調光控制系統,其中 該功率開關具有零電壓切換的特性。 9. 如申請專利範圍第1項所述之相位調光控制系統,其中 該高頻信號控制該換流器中功率開關的切換頻率,以調 變該燈管電廛的大小。 10. —種相位調光控制方法,用以線性調整一燈管的光度, 包括: 根據輸入電壓的一相位觸發角,以調壓方式調變輸入 電壓成為一直流鏈電壓;及 根據該相位觸發角,以調頻方式調變該直流鏈電壓成 為一管電壓,用以線性調整該燈管的光度。 11. 如申請專利範圍第10項所述之相位調光控制方法,在 根據輸入電壓的一相位觸發角,以調壓方式調變輸入電 壓成為一直流鏈電壓步驟之前,進一步包括有: 根據輸入電壓的一初始相位觸發角,以調壓方式調變 該輸入電壓成為一初始直流鏈電壓; 22 200945953 根據該初始相位觸發角,以調頻方式調變初始直流鏈 電壓成為一預熱管電壓,用以預熱該燈管;及 經一預熱時間,再以調頻方式調變初始直流鏈電壓成 為一啟動管電壓,用以點亮該燈管。 12. 如申請專利範圍第4項所述之相位調光控制系統,其中 該半橋式串聯諧振換流器與該返驰式轉換器組成一單 級架構,該單級架構包括: 一變壓器,具有一次側繞組與一二次側繞組,該一次 0 側繞組接收該輸入電壓; 一返驰二極體,耦接於該變壓蒸的二次側繞組; 一第一開關,其第一端透過該反驰二極體耦接於該變 壓器的二次側繞組,該第一開關的第二端透過一二 極體耦接於該該變壓器的一次侧繞組; 一第二開關,耦接於該變壓器的二次側繞組; 一 LC諧振網路,耦接於該第一開關、該第二開關及 該燈管; ❹ 一第一電容,耦接於該第一開關與該LC諧振網路;. 及 一第二電容,耦接於該第二開關與該LC諧振網路。 13. 如申請專利範圍第5項所述之相位調光控制系統,其中 該半橋式串聯諧振換流器與該昇壓轉換器組成一單級 架構,該單級架構包括: 一第一開關; 一第二開關,串聯耦接於該第一開關; 一儲能電感,其第一端接收該輸入電壓,其第二端耦 23 200945953 接於該第一開關與該第二開關之中間點; 一 LC諧振網路,耦接於該第一開關與該第二開關之 中間點,以及該燈管; 一第一電容,耦接於該第一開關與該IX諧振網路; 及 一第二電容,耦接於該第二開關與該LC諧振網路。 ❹ 24200945953 X. Patent application scope: L production silk control system n linear adjustment - fluorescent tube light: according to a phase trigger angle, to adjust - AC one phase controller, the size of the pressure; -:: 曰: two control The device is coupled to the phase controller, the single chip control ❹ 读 = reading the phase firing angle, and outputting a second medical signal and a high frequency signal according to the phase firing angle; the angular transmission, the machine _ is connected to the a phase controller that rectifies the AC voltage and outputs an input voltage; is coupled to the single chip controller and the rectifier, and the voltage is controlled by the P WM signal to regulate voltage Modulating the input power into a constant current key voltage; the device is lightly connected to the single-chip controller, the converter and the lamp, and the converter is controlled by the high-frequency money, and the fine-tuning mode is modulated. The DC link voltage becomes a tube voltage to the lamp. 2. If you apply for the · 丨 观 _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ _ The TRuc triggers the parent > two voltages each half (four) depends on the hair, or the money control method with a single chip to control its phase firing angle. 3. The phase dimming control system according to claim i, wherein the commutation 1 § is a half bridge type series vibration converter, the half bridge series read vibration converter is connected in parallel to the lamp tube. 4. The phase dimming control system according to claim 3, wherein 21 200945953 the converter is a flyback converter. 5. The phase dimming control system of claim 3, wherein the converter is a boost converter. 6. The phase dimming control system of claim 1, wherein the single chip controller is coupled to a buzzer and controls the buzzer to operate when the phase trigger angle is greater than a critical angle. 7. The phase dimming control system of claim 1, wherein the PWM signal controls a duty cycle of the power switch in the converter to modulate the magnitude of the DC link voltage. 8. The phase dimming control system of claim 7, wherein the power switch has a zero voltage switching characteristic. 9. The phase dimming control system of claim 1, wherein the high frequency signal controls a switching frequency of the power switch in the inverter to modulate the size of the lamp. 10. A phase dimming control method for linearly adjusting the luminosity of a lamp, comprising: modulating an input voltage into a constant current chain voltage according to a phase trigger angle of the input voltage; and triggering according to the phase The angle is modulated by the frequency modulation to become a tube voltage for linearly adjusting the luminosity of the tube. 11. The phase dimming control method according to claim 10, before the step of adjusting the input voltage according to the input voltage to a constant current chain voltage step according to a phase trigger angle of the input voltage, further comprising: according to the input An initial phase firing angle of the voltage, the input voltage is modulated to become an initial DC link voltage by voltage regulation; 22 200945953 According to the initial phase firing angle, the initial DC link voltage is modulated by frequency modulation to become a preheating tube voltage, To preheat the lamp; and after a warm-up time, the initial DC link voltage is modulated by a frequency modulation method to become a starting pipe voltage for lighting the lamp. 12. The phase dimming control system of claim 4, wherein the half bridge series resonant converter and the flyback converter form a single stage architecture, the single stage architecture comprising: a transformer, Having a primary side winding and a secondary side winding, the primary 0 side winding receives the input voltage; a returning diode coupled to the transformer secondary side winding; a first switch, the first end thereof The second end of the first switch is coupled to the primary side winding of the transformer through a diode; the second switch is coupled to the second side winding of the transformer a secondary side winding of the transformer; an LC resonant network coupled to the first switch, the second switch, and the lamp; ❹ a first capacitor coupled to the first switch and the LC resonant network And a second capacitor coupled to the second switch and the LC resonant network. 13. The phase dimming control system of claim 5, wherein the half bridge series resonant converter and the boost converter form a single stage architecture, the single stage architecture comprising: a first switch a second switch coupled in series with the first switch; a first phase of the energy storage inductor receiving the input voltage, the second end coupling 23 200945953 being connected to an intermediate point between the first switch and the second switch An LC resonant network coupled between the first switch and the second switch, and the lamp; a first capacitor coupled to the first switch and the IX resonant network; The second capacitor is coupled to the second switch and the LC resonant network. ❹ 24
TW097114441A 2008-04-21 2008-04-21 Phase-control dimming electronic ballast system and the control method thereof TW200945953A (en)

Priority Applications (2)

Application Number Priority Date Filing Date Title
TW097114441A TW200945953A (en) 2008-04-21 2008-04-21 Phase-control dimming electronic ballast system and the control method thereof
US12/216,656 US20090261744A1 (en) 2008-04-21 2008-07-09 Phase-control dimming electronic ballast system and control method thereof

Applications Claiming Priority (1)

Application Number Priority Date Filing Date Title
TW097114441A TW200945953A (en) 2008-04-21 2008-04-21 Phase-control dimming electronic ballast system and the control method thereof

Publications (1)

Publication Number Publication Date
TW200945953A true TW200945953A (en) 2009-11-01

Family

ID=41200559

Family Applications (1)

Application Number Title Priority Date Filing Date
TW097114441A TW200945953A (en) 2008-04-21 2008-04-21 Phase-control dimming electronic ballast system and the control method thereof

Country Status (2)

Country Link
US (1) US20090261744A1 (en)
TW (1) TW200945953A (en)

Families Citing this family (12)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
US8102167B2 (en) * 2008-03-25 2012-01-24 Microsemi Corporation Phase-cut dimming circuit
US8233298B2 (en) * 2008-06-05 2012-07-31 Delta Electronics, Inc. Power factor correction rectifier that operates efficiently over a range of input voltage conditions
TW201038141A (en) * 2009-04-01 2010-10-16 chong-yuan Cai Non-flickering dimming device for non-resistive light-emitting load
CN102083254B (en) * 2009-11-30 2013-09-18 成都芯源系统有限公司 WLED driving circuit and driving method suitable for three-terminal controlled silicon dimmer
KR20120115400A (en) 2010-02-12 2012-10-17 마벨 월드 트레이드 리미티드 Dimmer circuit for electronic loads
TW201206248A (en) * 2010-03-25 2012-02-01 Koninkl Philips Electronics Nv Method and apparatus for increasing dimming range of solid state lighting fixtures
CN101835314B (en) * 2010-05-19 2013-12-04 成都芯源系统有限公司 LED drive circuit with dimming function and lamp
WO2012112750A1 (en) 2011-02-17 2012-08-23 Marvell World Trade Ltd. Triac dimmer detection
EP2749130B1 (en) 2011-10-14 2018-01-10 Philips Lighting Holding B.V. System and method for controlling dimming of solid state lighting device
TWI597930B (en) * 2015-02-06 2017-09-01 Use to change the conduction angle as the control command of the control device
US11050380B2 (en) 2017-12-14 2021-06-29 Haier Us Appliance Solutions, Inc. Phase control of DC bus in appliances
CN112737377B (en) * 2020-12-30 2022-06-28 江苏东方四通科技股份有限公司 Power controller capable of continuously and stably outputting power

Family Cites Families (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
JPS5919639B2 (en) * 1979-09-28 1984-05-08 東芝ライテック株式会社 discharge lamp lighting device
US6043611A (en) * 1997-04-10 2000-03-28 Philips Electronics North America Corporation Dimmable compact fluorescent lamp
EP1164819B1 (en) * 2000-06-15 2004-02-11 City University of Hong Kong Dimmable electronic ballast
US6597127B2 (en) * 2000-09-29 2003-07-22 Matsushita Electric Industrial Co., Ltd. Discharge lamp operating apparatus, self-ballasted discharge lamp, dimmer and illumination kit for dimming
US6603274B2 (en) * 2001-04-02 2003-08-05 International Rectifier Corporation Dimming ballast for compact fluorescent lamps
US7304439B2 (en) * 2001-09-06 2007-12-04 E. Energy Technology Limited Phase-controlled dimmable electronic ballasts for fluorescent lamps with very wide dimming range
US7888886B2 (en) * 2005-05-10 2011-02-15 Koninklijke Philips Electronics N.V. Universal line voltage dimming method and system

Also Published As

Publication number Publication date
US20090261744A1 (en) 2009-10-22

Similar Documents

Publication Publication Date Title
TW200945953A (en) Phase-control dimming electronic ballast system and the control method thereof
TWI384898B (en) Dimmable led driving circuit
JP3945681B2 (en) Lighting device
US20020113556A1 (en) Self-oscillating electronic discharge lamp ballast with dimming control
TWI516033B (en) Pulse-width modulation control device
US8427064B2 (en) Electronic ballast circuit for fluorescent lamps
CN104822216B (en) Small-power HID lamp driving circuit
CN107567130A (en) Power supply circuit and apply its LED drive circuit
TWI442826B (en) Driving circuit system for gas discharge lamp and the control method thereof
US7477021B2 (en) Non-discontinuous neon power supply with high power factor
CN105554956A (en) Light emitting diode (LED) lamp lighting system based on pulse width modulation (PWM) dimming
CN104822208B (en) The reduction voltage circuit of small-power HID lamp driving circuit
CN205378285U (en) LED lamp lighting system based on PWM adjusts luminance
CN1937876A (en) High voltage discharge lamp lighting device and illumination apparatus
CN201854491U (en) Metal halogen lamp electronic ballast
JP5069573B2 (en) High pressure discharge lamp lighting device, lighting fixture
Cheng et al. A digitally wireless dimmable lighting system for two-area fluorescent lamps
TWI459854B (en) A white LED (WLED) drive circuit and driving method for three - terminal controllable silicon dimmer
CN208739455U (en) LED touch dimmer temperature driving power
CN100594755C (en) Preheating method of Electronic lighting device fluorescent lamp
TWI446835B (en) Resonant capacitor adjusting element and current preheating ballast using the same
CN206559675U (en) A kind of LED dimming driving circuits
TWM341806U (en) Driver power supply for LED (light emitting diode) lighting with high efficiency and capable of being cascaded
Chang et al. A novel design of U-shaped CCFL in T8 tube to replace traditional fluorescent lamp
CN206790730U (en) LED adjusting control circuit