KR20220060457A - Display apparatus - Google Patents

Abstract

Provided is a display apparatus capable of improving color reproduction with respect to an input image signal. The display device comprises: a display panel including a pixel array in which a pixel composed of a plurality of inorganic light emitting elements is arranged in a plurality of row lines and a sub-pixel circuit provided for each of the inorganic light emitting elements and providing a driving current to the inorganic light emitting elements; and a driving unit for setting an image data voltage to the sub-pixel circuits of the display panel in order of the row line during a data setting period and driving the sub-pixel circuits to provide the driving current to the inorganic light emitting elements in order of the row line based on a sweep signal and the image data voltage during the light emitting period. The sub-pixel circuits comprise: a capacitor having one end to which the sweep signal is applied; and a first driving transistor connected to the other end of the capacitor, receiving the sweep signal through the capacitor in a light emitting section, and controlling a time during which the driving current is provided to the inorganic light emitting elements on the basis of the sweep signal. The drive unit applies a first voltage to the one end of the capacitor separately from the sweep signal in the data setting period.

Description

display device {DISPLAY APPARATUS}

The present disclosure relates to a display device, and more particularly, to a display device including a pixel array formed of a self-luminous element.

Conventionally, in a display panel in which an inorganic light emitting device such as a red LED (Light Emitting Diode), a green LED, or a blue LED (hereinafter, LED refers to an inorganic light emitting device) is driven as a sub-pixel, PAM (Pulse Amplitude Modulation) driving The gradation of sub-pixels was expressed through the method.

In this case, depending on the magnitude of the driving current, not only the gray level of the emitted light but also the wavelength changes, so that the color reproducibility of the image is reduced. 1 shows a change in wavelength according to the magnitude of a driving current flowing through a blue LED, a green LED, and a red LED.

Accordingly, development of a driving method of a self-luminous display panel capable of improving color reproducibility is required. In this case, power consumption, luminance uniformity, horizontal crosstalk, etc. need to be considered together.

An object of the present disclosure is to provide a display device that provides improved color reproducibility with respect to an input image signal, and a method of driving the same.

Another object of the present disclosure is to provide a display device including a sub-pixel circuit capable of driving an inorganic light emitting device more efficiently and stably, and a method of driving the same.

Another object of the present disclosure is to provide a display device including a driving circuit suitable for high-density integration by optimizing the design of various circuits for driving an inorganic light emitting device, and a driving method thereof.

Another object of the present disclosure is to provide a display device capable of solving a problem of a decrease in luminance uniformity due to a threshold voltage or mobility deviation of a driving transistor, and a driving method thereof.

Another object of the present disclosure is to provide a display device capable of reducing power consumption when driving a display panel and a driving method thereof.

Another object of the present disclosure is to provide a display device capable of compensating for an effect of a driving voltage drop that is different for each position of a display panel on a data voltage setting process, and a driving method thereof.

Another object of the present disclosure is to provide a display device having improved luminance non-uniformity and horizontal crosstalk caused by a sweep rod, and a method of driving the same.

A display device according to an embodiment of the present disclosure for achieving the above object is provided with a pixel array in which pixels composed of a plurality of inorganic light emitting devices are arranged in a plurality of row lines, and each of the plurality of inorganic light emitting devices, A display panel including a sub-pixel circuit providing a driving current to the inorganic light emitting device, and during a data setting period for each row line, image data voltages are set in the sub-pixel circuits of the display panel in a row line order, During the light emitting period, the sub-pixel circuits are driven so that the driving current is sequentially provided to the inorganic light emitting devices of the pixel array based on a sweep signal sweeping from a first voltage to a second voltage and the set image data voltage in a row line order. wherein one end of the sub-pixel circuit is connected to a capacitor to which the sweep signal is applied, and the other end of the capacitor, and receives the sweep signal through the capacitor in the light emitting section, and the sweep and a first driving transistor for controlling a time period during which the driving current is supplied to the inorganic light emitting device based on a signal, wherein the driving unit applies the first voltage separately from the sweep signal in the data setting period. It is applied to one end of the capacitor.

In addition, the driving unit is provided for each row line, a sweep driver circuit for applying the sweep signal to one end of the capacitor, and a power IC for providing the first voltage applied separately from the sweep signal to the display panel may include

In addition, the image data voltage includes a constant current source data voltage and a pulse width modulation (PWM) data voltage, the sub-pixel circuit includes a second driving transistor, and a magnitude is based on the constant current source data voltage. A PWM circuit including a constant current source circuit providing a driving current of may include

In addition, the constant current source circuit, in the data setting period, sets a third voltage based on the constant current source data voltage and a threshold voltage of the second driving transistor to the gate terminal of the second driving transistor, the PWM circuit , in the data setting period, while the first voltage is applied to one end of the capacitor, a fourth voltage based on the PWM data voltage and a threshold voltage of the first driving transistor is applied to the gate terminal of the first driving transistor. can be set.

In addition, the constant current source circuit provides a driving current of a magnitude based on the third voltage to the inorganic light emitting device in the light emitting section, and the PWM circuit provides the fourth voltage in the light emitting section according to the sweep signal. A time period during which the driving current is provided to the inorganic light emitting device may be controlled based on a voltage of the gate terminal of the first driving transistor that is changed from the voltage.

In addition, the sub-pixel circuits are driven in the order of the data setting period and the plurality of light emitting periods for each row line, and the driving unit may generate a driving current corresponding to the set image data voltage in each of the plurality of light emitting periods in the row line. The sub-pixel circuits of the row line may be driven to be provided to the inorganic light emitting devices of the .

In addition, currents flowing through the first driving transistor and the second driving transistor included in the sub-pixel circuit are sensed, respectively, based on a specific voltage applied to the sub-pixel circuit, and sensing data corresponding to the sensed current is obtained. It may include a sensing unit that outputs, and a correction unit correcting the constant current source data voltage and the PWM data voltage applied to the sub-pixel circuit based on the sensed data.

In the data setting period, the driver sets the image data voltage in the row line order in the sub-pixel circuits based on a first driving voltage, and in the light emission period, a second driving voltage and the first driving voltage The sub-pixel circuits may be driven so that the driving current is provided to the inorganic light emitting devices of the pixel array in the order of a row line based on a voltage.

The display device may further include a storage unit configured to store data for compensating for a drop of the driving voltage for each position of the display panel according to the driving current, wherein the compensating unit comprises: the sub-pixel circuit based on the sensing data and the stored data The constant current source data voltage and the PWM data voltage applied to may be corrected.

Meanwhile, in a display device according to another exemplary embodiment of the present disclosure, a pixel array in which pixels including a plurality of inorganic light emitting devices are disposed on a plurality of row lines, and each of the plurality of inorganic light emitting devices are provided, and a driving current is applied to the inorganic light emitting device. A display panel including a sub-pixel circuit provided as a device, and during a data setting period, image data voltages are set in the sub-pixel circuits of the display panel in a row line order, and during a light-emitting period, a first voltage to a second voltage and a driver for driving the sub-pixel circuits such that the driving current is sequentially provided to the inorganic light emitting devices of the pixel array based on a sweep signal sweeping to . , a capacitor, and a first driving transistor connected to one end of the capacitor and configured to control a time during which the driving current is provided to the inorganic light emitting device based on the sweep signal applied to the light emitting section, the first driving transistor comprising: The driver may apply the first voltage to the other terminal of the capacitor separately from the sweep signal.

In addition, the driving unit is provided for each row line, a sweep driver circuit for applying the sweep signal to the first driving transistor, and a power for providing the first voltage applied separately from the sweep signal to the display panel IC may be included.

In addition, the image data voltage includes a constant current source data voltage and a pulse width modulation (PWM) data voltage, the sub-pixel circuit includes a second driving transistor, and a magnitude is based on the constant current source data voltage. A PWM circuit including a constant current source circuit providing a driving current of may include

In addition, the constant current source circuit, in the data setting period, sets a third voltage based on the constant current source data voltage and a threshold voltage of the second driving transistor to the gate terminal of the second driving transistor, the PWM circuit , in the data setting period, while the first voltage is applied to one end of the capacitor, a fourth voltage based on the PWM data voltage and a threshold voltage of the first driving transistor is applied to the gate terminal of the first driving transistor. can be set.

In addition, the constant current source circuit provides a driving current of a magnitude based on the third voltage to the inorganic light emitting device in the light emission period, and the PWM circuit changes according to the sweep signal in the light emission period A time period during which the driving current is provided to the inorganic light emitting device may be controlled based on a voltage difference between the source terminal and the gate terminal of the first driving transistor.

In addition, the sub-pixel circuits are driven in the order of the data setting period and the plurality of light emitting periods for each row line, and the driving unit may generate a driving current corresponding to the set image data voltage in each of the plurality of light emitting periods in the row line. The sub-pixel circuits of the row line may be driven to be provided to the inorganic light emitting devices of the .

In addition, currents flowing through the first driving transistor and the second driving transistor included in the sub-pixel circuit are sensed, respectively, based on a specific voltage applied to the sub-pixel circuit, and sensing data corresponding to the sensed current is obtained. It may include a sensing unit that outputs, and a correction unit correcting the constant current source data voltage and the PWM data voltage applied to the sub-pixel circuit based on the sensed data.

In the data setting period, the driver sets the image data voltage in the row line order in the sub-pixel circuits based on a first driving voltage, and in the light emission period, a second driving voltage and the first driving voltage The sub-pixel circuits may be driven so that the driving current is provided to the inorganic light emitting devices of the pixel array in the order of a row line based on a voltage.

The display device may further include a storage unit configured to store data for compensating for a drop of the driving voltage for each position of the display panel according to the driving current, wherein the compensating unit is applied to the sub-pixel circuit based on the sensed data and the stored data It is possible to correct the constant current source data voltage and the PWM data voltage.

According to various embodiments of the present disclosure as described above, it is possible to prevent the wavelength of the light emitted by the inorganic light emitting device from being changed according to the gray level.

In addition, it is possible to easily compensate for unevenness that may appear in an image due to a difference in threshold voltage and mobility between driving transistors. In addition, color correction becomes easy.

In addition, even when a large-area display panel is configured by combining module-type display panels or when a single large-sized display panel is configured, it is possible to more easily compensate for spots and color correction.

In addition, power consumption when driving the display panel can be reduced.

In addition, it is possible to compensate for the influence of a drop of the driving voltage that is different for each position of the display panel on the data voltage setting process.

In addition, it is possible to design a more optimized driving circuit, and it is possible to stably and efficiently drive the inorganic light emitting device.

In addition, it is possible to improve luminance non-uniformity and horizontal crosstalk caused by the sweep rod.

1 is a graph showing the wavelength change according to the magnitude of the driving current flowing through a blue LED, a green LED, and a red LED;
2 is a view for explaining a pixel structure of a display device according to an embodiment of the present disclosure;
3A is a conceptual diagram illustrating a driving method of a conventional display panel;
3B is a conceptual diagram illustrating a driving method of a display panel according to an embodiment of the present disclosure;
4 is a block diagram illustrating a configuration of a display device according to an embodiment of the present disclosure;
5 is a view for explaining a progressive driving method of a display panel according to an embodiment of the present disclosure;
6 is a detailed block diagram showing the configuration of an apparatus according to an embodiment of the present disclosure;
7A is a block diagram of a sub-pixel circuit according to an embodiment of the present disclosure;
7B is a detailed circuit diagram of a sub-pixel circuit according to an embodiment of the present disclosure;
7C is a timing diagram for the gate signals described above in FIG. 7B;
7D is a timing diagram of various signals for driving a display panel including the sub-pixel circuit of FIG. 7B during one image frame period;
8A is a view for explaining luminance non-uniformity and horizontal crosstalk that may occur due to a sweep rod;
8B is a view for explaining the luminance non-uniformity and horizontal crosstalk phenomenon that may occur due to the sweep rod;
8C is a diagram illustrating a high voltage (SW_VGH) of a sweep signal according to an embodiment of the present disclosure;
9A is a view for explaining an embodiment of the present disclosure in which a low voltage SW_VGL of a sweep signal is applied to an X node;
9B is a diagram illustrating a low voltage SW_VGL of a sweep signal according to an embodiment of the present disclosure;
10A is a detailed circuit diagram of a sub-pixel circuit according to an embodiment of the present disclosure;
10B is a timing diagram of various signals for driving a display panel including the sub-pixel circuit of FIG. 10A during one image frame period;
11 is a block diagram illustrating a configuration of a display device according to an embodiment of the present disclosure;
12 is a detailed block diagram of a display device according to an embodiment of the present disclosure;
13A is a diagram illustrating an implementation example of a sensing unit according to an embodiment of the present disclosure;
13B is a diagram illustrating an implementation example of a sensing unit according to another embodiment of the present disclosure;
14A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to an embodiment of the present disclosure;
14B is a driving timing diagram of the sub-pixel circuit shown in FIG. 14A;
15A is a diagram for explaining luminance non-uniformity and horizontal crosstalk that may occur due to a sweep load in a sub-pixel circuit to which an external compensation method is applied;
15B is a diagram for explaining luminance non-uniformity and horizontal crosstalk that may occur due to a sweep load in a sub-pixel circuit to which an external compensation method is applied;
15C is a diagram illustrating a high voltage SW_VGH of a sweep signal according to an embodiment of the present disclosure;
16A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to another embodiment of the present disclosure;
16B is a driving timing diagram of the sub-pixel circuit shown in FIG. 16A;
17A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to another embodiment of the present disclosure;
17B is a driving timing diagram of the sub-pixel circuit shown in FIG. 17A;
18A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to another embodiment of the present disclosure;
18B is a driving timing diagram of the sub-pixel circuit shown in FIG. 18A;
19A is a view for explaining an embodiment of connecting a low voltage (SW_VGL) input of a sweep signal to an X node;
19B is a view for explaining an embodiment of connecting a low voltage (SW_VGL) input of a sweep signal to an X node;
20A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to an embodiment of the present disclosure;
20B is a timing diagram of various signals for driving a display panel including the sub-pixel circuit of FIG. 20A during one image frame period;
21A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to another embodiment of the present disclosure;
Fig. 21B is a timing diagram of various signals for driving the sub-pixel circuit of Fig. 21A;
22A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to another embodiment of the present disclosure;
22B is a driving timing diagram of the sub-pixel circuit shown in FIG. 22A;
23A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to another embodiment of the present disclosure;
23B is a driving timing diagram of the sub-pixel circuit shown in FIG. 23A;
24A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to an embodiment of the present disclosure;
24B is a driving timing diagram of the sub-pixel circuit shown in FIG. 24A;
25A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to another embodiment of the present disclosure;
25B is a driving timing diagram of the sub-pixel circuit shown in FIG. 25A;
26A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to another embodiment of the present disclosure;
26B is a driving timing diagram of the sub-pixel circuit shown in FIG. 26A;
27A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to another embodiment of the present disclosure;
27B is a driving timing diagram of the sub-pixel circuit shown in FIG. 27A;
28A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to an embodiment of the present disclosure;
28B is a driving timing diagram of the sub-pixel circuit shown in FIG. 28A;
29A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to another embodiment of the present disclosure;
29B is a timing diagram of various signals for driving the sub-pixel circuit of FIG. 29A;
30A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to another embodiment of the present disclosure;
30B is a driving timing diagram of the sub-pixel circuit shown in FIG. 30A;
31A is a detailed circuit diagram of a sub-pixel circuit and a sensing unit according to another embodiment of the present disclosure;
31B is a driving timing diagram of the sub-pixel circuit shown in FIG. 31A;
32A is a cross-sectional view of a display panel according to an embodiment of the present disclosure;
32B is a cross-sectional view of a display panel according to another embodiment of the present disclosure, and
32C is a plan view of a TFT layer according to an embodiment of the present disclosure.

In describing the present disclosure, if it is determined that a detailed description of a related known technology may unnecessarily obscure the subject matter of the present disclosure, the detailed description thereof will be omitted. In addition, redundant description of the same configuration will be omitted as much as possible.

The suffix "part" for the components used in the following description is given or mixed in consideration of only the ease of writing the specification, and does not have a meaning or role distinct from each other by itself.

Terms used in the present disclosure are used to describe embodiments, and are not intended to limit and/or limit the present disclosure. The singular expression includes the plural expression unless the context clearly dictates otherwise.

In the present disclosure, terms such as 'comprise' or 'have' are intended to designate that a feature, number, step, operation, component, part, or combination thereof described in the specification exists, but one or more other features It should be understood that this does not preclude the existence or addition of numbers, steps, operations, components, parts, or combinations thereof.

As used in the present disclosure, expressions such as “first,” “second,” “first,” or “second,” may modify various elements, regardless of order and/or importance, and refer to one element. It is used only to distinguish it from other components, and does not limit the components.

A component (eg, a first component) is "coupled with/to (operatively or communicatively)" to another component (eg, a second component); When referring to "connected to", it will be understood that the certain element may be directly connected to the other element or may be connected through another element (eg, a third element).

On the other hand, when it is referred to as being “directly connected” or “directly connected” to a component (eg, a first component (eg, a second component)), between the component and the other component It may be understood that other components (eg, a third component) do not exist in the .

Unless otherwise defined, terms used in the embodiments of the present disclosure may be interpreted as meanings commonly known to those of ordinary skill in the art.

Hereinafter, various embodiments of the present disclosure will be described in detail with reference to the accompanying drawings.

2 is a view for explaining a pixel structure of a display panel according to an embodiment of the present disclosure.

Referring to FIG. 2 , the display panel 100 includes a plurality of pixels 10 disposed (or arranged) in a matrix form, that is, a pixel array.

The pixel array includes a plurality of row lines or a plurality of column lines. In some cases, the row line may be called a horizontal line, a scan line, or a gate line, and the column line may be called a vertical line or a data line.

Alternatively, in some cases, the terms row line, column line, horizontal line, and vertical line are used as terms to refer to a line on a pixel array, and the terms scan line, gate line, and data line are a display panel through which data or signals are transmitted. It may be used as a term to refer to an actual wiring on (100).

Meanwhile, each pixel 10 of the pixel array has three types: a red (R) sub-pixel 20-1, a green (G) sub-pixel 20-2, and a blue (B) sub-pixel 20-3. may include sub-pixels of

In this case, each pixel 10 may include a plurality of inorganic light emitting devices constituting the sub-pixels 20 - 1 , 20 - 2 , and 20 - 3 .

For example, each pixel 10 has an R inorganic light emitting element constituting the R subpixel 20-1, a G inorganic light emitting element constituting the G subpixel 20-2, and a B subpixel 20- 3) may include three types of inorganic light emitting devices such as B inorganic light emitting devices.

Alternatively, each pixel 10 may include three blue inorganic light emitting devices. In this case, color filters for implementing R, G, and B colors may be provided on each inorganic light emitting device. In this case, the color filter may be a quantum dot (QD) color filter, but is not limited thereto.

Meanwhile, although not shown, a sub-pixel circuit for driving the inorganic light emitting device may be provided for each inorganic light emitting device in the display panel 100 .

In this case, each sub-pixel circuit may provide a driving current to the inorganic light emitting device based on the applied image data voltage.

Specifically, the image data voltage includes a constant current generator data voltage and a pulse width modulation (PWM) data voltage. Each sub-pixel circuit may express a grayscale of an image by providing a driving current having a magnitude corresponding to the constant current source data voltage to the inorganic light emitting device for a time corresponding to the PWM data voltage. Details on this will be described later.

Meanwhile, the sub-pixel circuits included in each row line of the display panel 100 may be driven in the order of “setting (or programming) an image data voltage” and “providing a driving current based on the set PWM data voltage”.

In this case, according to an embodiment of the present disclosure, the sub-pixel circuits included in each row line of the display panel 100 may be sequentially driven in the row line order.

For example, an operation of setting image data voltages of sub-pixel circuits included in one row line (eg, a first row line) and a sub-pixel included in a next row line (eg, a second row line) The operation of setting the image data voltage of the circuits may be sequentially performed in the row line order. In addition, an operation of providing a driving current to the sub-pixel circuits included in the one row line and an operation of providing a driving current to the sub-pixel circuits included in the next row line may also be sequentially performed in the order of the row line.

Meanwhile, in FIG. 2 , it is exemplified that the sub-pixels 20 - 1 to 20 - 3 are arranged in an inverted L-shape in one pixel area. However, the embodiment is not limited thereto, and the R, G, and B sub-pixels 20 - 1 to 20 - 3 may be arranged in a line in the pixel area or may be arranged in various forms according to the embodiment.

In addition, in FIG. 2 , a case in which three types of sub-pixels constitute one pixel has been described as an example. However, according to an embodiment, four types of sub-pixels such as R, G, B, and W (white) may constitute one pixel, or any number of different sub-pixels may constitute one pixel. .

3A is a conceptual diagram illustrating a conventional driving method of a display panel, and FIG. 3B is a conceptual diagram illustrating a driving method of a display panel according to an embodiment of the present disclosure.

3A and 3B show a method of driving a display panel for one image frame time. Also, in FIGS. 3A and 3B , a vertical axis indicates a row line, and a horizontal axis indicates time. In addition, the data setting period indicates a driving period of the display panel 100 in which image data voltages are set to sub-pixel circuits included in each row line, and the light emission period includes sub-pixel circuits included in each row line; A driving section of the display panel 100 in which a driving current is provided to the inorganic light emitting device based on the set image data voltage is shown. The inorganic light emitting devices emit light according to the driving current within the light emitting section.

Referring to FIG. 3A , in the related art, it can be seen that, after the image data voltage is set for all the row lines of the display panel, the light emitting period is collectively progressed.

In this case, since the entire row line of the display panel simultaneously emits light during the light emission period, a high peak current is required, and accordingly, there is a problem in that the peak power consumption required for the product is increased. When the peak power consumption increases, the capacity of a power supply device, such as a switched mode power supply (SMPS) mounted on a product, increases, so that the cost increases and the volume increases, which causes design restrictions.

On the other hand, according to an embodiment of the present disclosure, as shown in FIG. 3B , the data setting section and the light-emitting section (specifically, a plurality of light-emitting sections) of each row line sequentially proceed in the row line order. you can see Hereinafter, the driving method as shown in FIG. 3B will be referred to as a “progressive driving method” to distinguish it from the batch driving method of FIG. 3A .

In the case of the progressive driving method, since the number of row lines simultaneously emitting light is reduced, the amount of peak current required is lower than that of the prior art, and thus, peak power consumption can be reduced.

As described above, according to various embodiments of the present disclosure, it is possible to prevent a phenomenon in which the wavelength of light emitted from the inorganic light emitting device changes according to the gray level by PWM driving the inorganic light emitting device in an active matrix (AM) method. In addition, instantaneous peak power consumption may be reduced by driving the display panel 100 so that the sub-pixels sequentially emit light in row line order.

Meanwhile, a sub-pixel circuit that provides a driving current to the inorganic light emitting device includes a driving transistor. The driving transistor is a key component that determines the operation of the sub-pixel circuit. Theoretically, electrical characteristics such as the threshold voltage (Vth) or mobility (μ) of the driving transistor are mutually exclusive between the sub-pixel circuits of the display panel 100 . should be the same

However, the threshold voltage (Vth) and mobility (μ) of the actual driving transistor may vary for each sub-pixel circuit due to various factors such as process deviations or changes over time, and these deviations cause image quality deterioration. need to be compensated.

Hereinafter, an internal compensation method for compensating for the electrical characteristic deviation of the driving transistor based on the configuration of the sub-pixel circuit, and an external compensation for compensating for the electrical characteristic deviation of the driving transistor by correcting the image data voltage based on the current flowing through the driving transistor By dividing by the method, various embodiments of the present disclosure will be described.

First, various embodiments of a display device to which an internal compensation method is applied to a deviation in electrical characteristics of a driving transistor will be described with reference to FIGS. 4 to 10B .

4 is a block diagram illustrating a configuration of a display apparatus according to an embodiment of the present disclosure. According to FIG. 4 , the display apparatus 1000 includes a display panel 100 and a driving unit 500 .

The driving unit 500 drives the display panel 100 . Specifically, the driver 500 may drive the display panel 100 by providing various control signals, data signals, driving voltages, and the like to the display panel 100 .

As described above, according to an embodiment of the present disclosure, the display panel 100 may be driven in the order of row lines. To this end, the driver 500 may include a gate driver for driving the pixels on the pixel array in a row line unit.

Also, the driver 500 may include a source driver (or data driver) for providing a PWM data voltage to each pixel (or each sub-pixel) of the display panel 100 .

Also, the driver 500 may include a DeMUX circuit for selecting each of the plurality of sub-pixels 20 - 1 to 20 - 3 included in one pixel 10 .

In addition, the driving unit 500 includes various DC voltages (eg, a first driving voltage (VDD_PAM), a second driving voltage (VDD_PWM) to be described later), a ground voltage (VSS), a test voltage, a Vset voltage, etc.) or a constant current A power IC (or a driving voltage providing circuit) for providing the raw data voltage, the high voltage (SW_VGH) of the sweep signal, and the low voltage (SW_VGL) of the sweep signal to each sub-pixel circuit included in the display panel 100 is provided. may include

In addition, the driving unit 500 may include a clock signal providing circuit for providing various clock signals to the gate driver or data driver, and providing a sweep signal for providing a sweep signal (or sweep voltage), which will be described later, to the sub-pixel circuit. circuit (or sweep driver).

Meanwhile, at least some of the various circuits of the above-described driving unit 500 are implemented in a separate chip form and mounted on an external printed circuit board (PCB) together with a timing controller (TCON), and film on glass (FOG) wiring. may be connected to sub-pixel circuits formed in the TFT layer of the display panel 100 through

Alternatively, at least some of the various circuits of the above-described driving unit 500 are implemented in a separate chip form and disposed on a film in the form of a COF (Chip On Film), and the display panel ( 100) may be connected to the sub-pixel circuits formed in the TFT layer.

Alternatively, at least some of the various circuits of the above-described driving unit 500 are implemented in a separate chip form and arranged in a COG (Chip On Glass) form (that is, the rear surface of the glass substrate (to be described later) of the display panel 100 ). (arranged on the surface opposite to the surface on which the TFT layer is formed with respect to the glass substrate) and may be connected to the sub-pixel circuits formed on the TFT layer of the display panel 100 through a connection line.

Alternatively, at least some of the various circuits of the above-described driver 500 may be formed in the TFT layer together with the sub-pixel circuits formed in the TFT layer in the display panel 100 to be connected to the sub-pixel circuits.

For example, among the various circuits of the above-described driver 500 , a gate driver, a sweep signal providing circuit, and a demux circuit are formed in the TFT layer of the display panel 100 , and the data driver is a glass substrate of the display panel 100 . The power IC, the clock signal providing circuit, and the timing controller (TCON) may be disposed on an external printed circuit board (PCB), but are not limited thereto.

In particular, the driving unit 500 may drive the display panel 100 in a progressive driving manner. To this end, the driver 500 sets the image data voltages in the row line order in the sub-pixel circuits of the display panel 100 during the data setting period, and during the light emission period, based on the sweep signal and the set image data voltage. The sub-pixel circuits may be driven so that the pixels of the pixel array emit light in a row-line order.

The display panel 100 includes the pixel array as described above with reference to FIG. 2 , and may display an image corresponding to an applied image data voltage.

Each sub-pixel circuit included in the display panel 100 provides a driving current whose magnitude and driving time (or pulse width) are controlled based on the applied image data voltage to the corresponding inorganic light emitting device. can

The inorganic light emitting devices constituting the pixel array emit light according to a driving current provided from a corresponding sub-pixel circuit, and thus an image may be displayed on the display panel 100 .

5 is a view for explaining a progressive driving method of the display panel 100 according to an embodiment of the present disclosure.

5 conceptually illustrates a driving method of the display panel 100 for two consecutive image frames. In FIG. 5 , the vertical axis indicates a row line, the horizontal axis indicates time, reference number 60 indicates an image frame period, and reference number 65 indicates a blanking period.

Meanwhile, in FIG. 5 , the display panel 100 is composed of 270 row lines, and 7 light emitting sections 62-1 to 62-7 are performed based on the image data voltage set in the data setting section 61 . cite as an example However, it goes without saying that the number of row lines or the number of times of the light emitting period are not limited thereto.

Specifically, referring to FIG. 5 , it can be seen that for one image frame, one data setting section 61 and a plurality of light-emitting sections 62-1 to 62-7 are performed for each row line.

During the data setting period 61 , an image data voltage may be set in the sub-pixel circuits included in each row line. Also, in each of the plurality of light emitting sections 62-1 to 62-7, the sub-pixel circuits included in each row line may provide a driving current to the inorganic light emitting device based on the set image data voltage.

To this end, the driving unit 500 generates a control signal (hereinafter, referred to as a scan signal) for setting the image data voltage during the data setting period 61. For example, VST(n) and SP(n), which will be described later included) may be applied to the sub-pixel circuits of each row line.

In addition, the driving unit 500 includes a control signal (hereinafter, referred to as an emission signal) for controlling the driving current providing operation during the plurality of light emission periods 62-1 to 62-7. SET(n) and Emi_PWM to be described later (n), Emi_PAM(n), and Sweep(n)) may be applied to the sub-pixel circuits of each row line.

On the other hand, referring to FIG. 5 , it can be seen that the data setting section 61 and each light emitting section 62-1 to 62-7 sequentially proceed in the order of row lines for all row lines of the display panel 100 . can

To this end, the driver 500 may apply the scan signal to the sub-pixel circuits in the order of row lines from the first row line to the last row line of the display panel 100 . Also, the driver 500 may apply the emission signal to the sub-pixel circuits in the order of row lines from the first row line to the last row line of the display panel 100 .

Meanwhile, as shown in FIG. 5 , the first light emission section 62-1 of each row line is temporally continuous with the data setting section 61, and each of the plurality of light emission sections 62-1 to 62-7 It can be seen that has a preset time interval.

In this case, the number of light emitting sections performed in each row line for one image frame and a preset time interval between light emitting sections may be set based on the size of the display panel 100 and/or the shutter speed of the camera. . However, the present invention is not limited thereto.

In general, since the shutter speed of the camera is several times faster than one image frame time, when the display panel 100 is driven so that one light emission section from the first row line to the last row line proceeds in the row line order during one image frame time , the image displayed on the display panel 100 taken by the camera may be distorted.

Therefore, according to an embodiment of the present disclosure, the display panel 100 is driven so that a plurality of light emitting sections proceed with a preset time interval during one image frame time, but the preset time interval is set based on the speed of the camera By doing so, even if the display panel 100 is photographed at any moment, the image displayed on the display panel 100 taken by the camera may not be distorted.

Meanwhile, in FIG. 5 , a blanking interval 65 indicates a time interval between consecutive image frame periods 60 to which valid image data is not applied. Referring to FIG. 5 , it can be seen that the data setting period 61 is not included in the blanking period 65 . Accordingly, the image data voltage is not applied to the display panel 100 during the blankin period 65 .

Apart from the fact that the image data voltage is not applied during the blanking period 65 as described above, the inorganic light emitting devices may emit light even in a portion of the blanking period 65 according to an embodiment. Referring to arrows included in the time period indicated by reference numeral 66 in FIG. 5 , it can be seen that the light emission period of some row lines proceeds even within the blanking period 65 .

Also, in the blankine section 65 , a non-emission section 67 in which all inorganic light emitting devices of the display panel 100 do not emit light may exist. Since no current flows in the display panel 100 in the non-light-emitting section 67 , an operation such as detecting a failure of the display panel 100 may be performed.

6 is a detailed block diagram illustrating the configuration of the apparatus 1000 according to an embodiment of the present disclosure. In the description of FIG. 6 , a description of the content overlapping with the above in FIG. 4 will be omitted.

Referring to FIG. 6 , a display apparatus 1000 includes a display panel 100 including a sub-pixel circuit 110 and an inorganic light emitting device 120 , and a driver 500 .

As will be described later, the display panel 100 may have a structure in which the sub-pixel circuit 110 is formed on a glass substrate and the inorganic light emitting device 120 is disposed on the sub-pixel circuit 110, but is limited thereto. it is not going to be Meanwhile, in FIG. 6 , only one sub-pixel related configuration included in the display panel 100 is illustrated for convenience of explanation, but the sub-pixel circuit 110 and the inorganic light emitting device 120 for each sub-pixel of the display panel 100 are illustrated. is of course provided.

The inorganic light emitting device 120 may be mounted on the sub-pixel circuit 110 to be electrically connected to the sub-pixel circuit 110 , and may emit light based on a driving current provided from the sub-pixel circuit 110 .

The inorganic light emitting device 120 constitutes the sub-pixels 20 - 1 to 20 - 3 of the display panel 100 , and there may be a plurality of types according to the color of the emitted light. For example, the inorganic light emitting device 120 includes a red (R) inorganic light emitting device that emits red light, a green (G) inorganic light emitting device that emits green light, and a blue (R) inorganic light emitting device that emits blue light. B) There may be inorganic light emitting devices.

Accordingly, the type of the aforementioned sub-pixel may be determined according to the type of the inorganic light emitting device 120 . That is, the R inorganic light emitting device constitutes the R sub-pixel 20-1, the G inorganic light emitting device constitutes the G sub-pixel 20-2, and the B inorganic light emitting device constitutes the B sub-pixel 20-3. can

Here, the inorganic light emitting device 120 means a light emitting device manufactured using an inorganic material, which is different from an organic light emitting diode (OLED) manufactured using an organic material.

In particular, according to an embodiment of the present disclosure, the inorganic light emitting device 120 may be a micro light emitting diode (micro LED or μLED) having a size of 100 micrometers (μm) or less.

A display panel in which each sub-pixel is implemented as a micro LED is called a micro LED display panel. The micro LED display panel is one of the flat panel display panels, and is composed of a plurality of inorganic light emitting diodes (inorganic LEDs), each of which is 100 micrometers or less. Micro LED display panels offer better contrast, response time and energy efficiency compared to liquid crystal display (LCD) panels that require a backlight. On the other hand, both organic light emitting diodes (OLEDs) and micro LEDs have good energy efficiency, but micro LEDs provide better performance than OLEDs in terms of brightness, luminous efficiency, and lifespan.

The inorganic light emitting device 120 may express grayscale values of different brightness according to the magnitude of the driving current provided from the sub-pixel circuit 110 or the pulse width of the driving current. Here, the pulse width of the driving current may be referred to as a duty ratio of the driving current or a driving time of the driving current.

For example, the inorganic light emitting device 120 may express a brighter gray value as the driving current increases. In addition, the inorganic light emitting device 120 may express a brighter grayscale value as the pulse width of the driving current is longer (ie, the duty ratio is higher or the driving time is longer).

The sub-pixel circuit 110 provides a driving current to the inorganic light emitting device 120 .

Specifically, the sub-pixel circuit 110 includes an image data voltage (eg, a constant current source data voltage, a PWM data voltage) and a driving voltage (eg, a first driving voltage and a second driving voltage) applied from the driving unit 500 . Voltage and ground voltage) and various control signals (eg, scan signals, emission signals), and the like, may provide a driving current whose magnitude and driving time are controlled to the inorganic light emitting device 120 .

That is, the sub-pixel circuit 110 may drive the inorganic light emitting device 120 by PAM (Pulse Amplified Modulation) and/or PWM (Pulse Width Modulation).

To this end, the sub-pixel circuit 110 includes a constant current generator circuit 111 for providing a constant current having a size based on the constant current source data voltage to the inorganic light emitting device 120, and a PWM data voltage based on the A PWM circuit 112 for controlling the time when the constant current is provided to the inorganic light emitting device 120 may be included. Here, the constant current provided to the inorganic light emitting device 120 becomes the aforementioned driving current.

Meanwhile, according to an embodiment of the present disclosure, the same constant current source data voltage may be applied to all constant current source circuits 111 of the display panel 100 . Accordingly, since a driving current (ie, a constant current) of the same size is provided to all the inorganic light emitting devices 120 of the display panel 100 , the problem of a change in the wavelength of the LED due to a change in the size of the driving current can be solved.

According to an embodiment, the same constant current source data voltage may be applied to the constant current source circuits 111 of the display panel 100 for each type of sub-pixel. That is, since characteristics may be different depending on the type of the inorganic light emitting device 120 , constant current source data voltages of different sizes may be applied to different types of sub-pixel circuits. Also in this case, the same constant current source data voltage is applied to the same type of sub-pixel circuits.

A PWM data voltage corresponding to a gray level value of each sub-pixel may be applied to each PWM circuit 112 of the display panel 100 . Accordingly, the driving time of the driving current (ie, constant current) provided to the inorganic light emitting device 120 of each sub-pixel through the PWM circuit 112 may be controlled. Accordingly, the gradation of the image may be expressed.

Meanwhile, according to an embodiment of the present disclosure, the display apparatus 1000 includes a wearable device, a portable device, a handheld device, and various electronic products or electric devices requiring a display as a single unit. can be applied to products.

Also, according to an embodiment of the present disclosure, the display apparatus 1000 may be one display module. In this case, a plurality of display modules are combined or assembled to form one small display product such as a monitor for a personal computer or a TV, or one large display such as a digital signage or an electronic display. You can configure products.

On the other hand, when a plurality of display modules are combined to form one display device, the same constant current source data voltage is applied to the sub-pixel circuits included in one display panel 100 as described above, but the other display panel ( Of course, constant current source data voltages of different sizes may be applied to the sub-pixel circuits included in FIG. 100 . Accordingly, when a plurality of display modules are combined to form one display device, a brightness deviation or a color deviation between display modules that may occur may be compensated for by adjusting the constant current source data voltage.

7A is a block diagram of a sub-pixel circuit 110 according to an embodiment of the present disclosure. Referring to FIG. 7A , the sub-pixel circuit 110 includes a constant current source circuit 111 , a PWM circuit 112 , a first switching transistor T17 and a second switching transistor T18 .

The constant current source circuit 111 includes a first driving transistor T16, and generates a constant current having a constant magnitude based on a voltage applied between the source terminal and the gate terminal of the first driving transistor T16 to the inorganic light emitting device ( 120) is provided.

Specifically, when the constant current source data voltage is applied from the driver 500 (specifically, the data driver) in the data setting period, the constant current source circuit 111 is a constant current source in which the threshold voltage of the first driving transistor T16 is compensated. A data voltage may be applied to the gate terminal B of the first driving transistor T16 .

A deviation of the threshold voltage Vth may exist between the first driving transistors T16 included in the sub-pixel circuits of the display panel 100 . In this case, even when the same constant current source data voltage is applied to the constant current source circuit 111 of each sub-pixel, a driving current having a different magnitude by the difference in the threshold voltage of the first driving transistor T16 is provided to the inorganic light emitting device 120 . and it appears as a stain on the image. Accordingly, the threshold voltage deviation of the first driving transistors T16 included in the display panel 100 needs to be compensated for.

To this end, the constant current source circuit 111 includes an internal compensation unit 11 . Specifically, when the constant current source data voltage is applied, the constant current source circuit 111 generates a first voltage based on the constant current source data voltage and the threshold voltage of the first driving transistor T16 through the internal compensation unit 11 . It may be applied to the gate terminal B of the first driving transistor T16.

Thereafter, in the light emission period, the constant current source circuit 111 operates based on the first driving voltage applied to the source terminal of the first driving transistor T16 and the first voltage applied to the gate terminal of the first driving transistor T16. A constant current of a magnitude may be provided to the inorganic light emitting device 120 through the first driving transistor T16 turned on.

Accordingly, the constant current source circuit 111 may provide a driving current having a magnitude corresponding to the applied constant current source data voltage to the inorganic light emitting device 120 irrespective of the threshold voltage deviation of the first driving transistors T16 . be able to

Meanwhile, as shown in FIG. 7A , the first switching transistor T17 has a source terminal connected to the drain terminal of the first driving transistor T16 and a drain terminal connected to the source terminal of the second switching transistor T18 . do. In addition, the second switching transistor T18 has a source terminal connected to a drain terminal of the first switching transistor T17 and a drain terminal connected to an anode terminal of the inorganic light emitting device 120 . Accordingly, as shown in FIG. 7A , a constant current is provided to the inorganic light emitting device 120 in a state in which the first switching transistor T17 and the second switching transistor T18 are turned on.

The PWM circuit 112 includes the second driving transistor T6 , and controls the on/off operation of the first switching transistor T17 to control the time for which a constant current flows through the inorganic light emitting device 120 .

Specifically, when the PWM data voltage is applied from the driver 500 (specifically, the data driver) during the data setting period, the PWM circuit 112 generates the PWM data voltage for which the threshold voltage of the second driving transistor T6 is compensated. It can be set to the gate terminal A of the second driving transistor T6.

Since the above-described problem due to the threshold voltage deviation between the first driving transistors T16 may also occur with respect to the second driving transistors T6 , the PWM circuit 112 also includes the internal compensation unit 12 . can be seen doing

When the PWM data voltage is applied, the PWM circuit 112 generates a second voltage based on the PWM data voltage and the threshold voltage of the second driving transistor T6 through the internal compensation unit 12 to the second driving transistor T6 . It can be set to the gate terminal (A) of

Thereafter, when the second driving transistor T6 is turned on based on the sweep signal applied during the emission period, the PWM circuit 112 applies a second driving voltage to the gate terminal of the first switching transistor T17 to perform the first switching. By turning off the transistor T17 , the time for which the constant current flows through the inorganic light emitting device 120 may be controlled.

At this time, in the second driving transistor T6 , the second voltage set at the gate terminal is changed according to the sweep signal applied to the PWM circuit 112 , and the voltage between the gate terminal and the source terminal of the second driving transistor T6 is changed. When the threshold voltage of the second driving transistor T6 is reached, it is turned on.

Here, the sweep signal is transmitted from the driver 500 (specifically, the sweep voltage providing circuit or the sweep driver) to the sub-pixel circuit 110 to change the voltage of the gate terminal of the second driving transistor T6 during the light emission period. As an applied signal, it may be a voltage signal sweeping between two different voltages. For example, the sweep signal may be a signal that linearly changes between two voltages, such as a triangular wave, but is not limited thereto.

Accordingly, the PWM circuit 112 may allow the constant current to flow through the inorganic light emitting device 120 for a time corresponding to the applied PWM data voltage, regardless of the threshold voltage deviation of the second driving transistors T6 . there is.

Meanwhile, the PWM circuit 112 includes a reset unit 13 . The reset unit 13 is configured to forcibly turn on the first switching transistor T17 . As described above, in order for a constant current to flow through the inorganic light emitting device 120 and the inorganic light emitting device 120 to emit light, the first switching transistor T17 must be turned on. To this end, through the operation of the reset unit 13 , the first switching transistor T17 may be turned on at the start time of each of the plurality of light emitting periods.

The second switching transistor T18 is turned on/off according to the emission signal Emi_PAM(n), as will be described later. The on/off timing of the second switching transistor T18 is related to the implementation of the black gradation, which will be described in detail later.

On the other hand, a resistance component is present in the display panel 100 . Accordingly, an IR drop occurs when a driving current flows in the light emitting section, which causes a drop in the driving voltage. As will be described later, since the driving voltage also serves as a reference when setting the constant current source data voltage, a drop in the driving voltage interferes with the accurate setting of the constant current source data voltage.

Specifically, in various embodiments of the present disclosure, as described above, the data setting section and the light emitting section proceed in the row line order, so that while the sub-pixel circuits of some row lines of the display panel 100 operate in the light emitting section, Sub-pixel circuits of other row lines operate in the data setting period.

Accordingly, when the same driving voltage applied through one wire is applied to the constant current source circuit 111 irrespective of the driving period of the display panel 100 , the driving voltage drops due to the sub-pixel circuits operating in the light emitting period. affects the constant current source data voltage setting operation of the sub-pixel circuits operating in the data setting period.

In order to overcome such a problem, in various embodiments of the present disclosure, a separate driving voltage applied through a separate wire is applied to the constant current source circuit 111 in the data setting section and the light emission section, respectively.

In the example of FIG. 7A , the second driving voltage VDD_PWM is applied to the constant current source circuit 111 in the data setting period, and the first driving voltage VDD_PAM is applied to the constant current source circuit 111 in the light emission period. Accordingly, even if a voltage drop occurs in the first driving voltage due to the sub-pixel circuits operating in the light-emitting period, a separate second driving voltage independent of the driving current is applied to the sub-pixel circuits operating in the data setting period. It becomes possible to set a stable constant current source data voltage.

Meanwhile, as shown in FIG. 7A , the second driving voltage is applied to the PWM circuit 112 during the emission period and is also used as a voltage to turn off the first switching transistor T17 .

7B is a detailed circuit diagram of the sub-pixel circuit 110 according to an embodiment of the present disclosure. Referring to FIG. 7B , the sub-pixel circuit 110 includes a constant current source circuit 111 , a PWM circuit 112 , a first switching transistor T17 , a second switching transistor T18 , a transistor T9 , and a transistor ( T10) and a transistor T19.

In this case, the PWM circuit 112 includes an internal compensation unit 12 and a reset unit 13 , and the constant current source circuit 111 includes an internal compensation unit 11 .

Meanwhile, the transistor T9 and the transistor T10 are circuit configurations for applying the second driving voltage VDD_PWM to the constant current source circuit 112 in the data setting period.

The transistor T19 is connected between the anode terminal and the cathode terminal of the inorganic light emitting device 120 . The transistor T19 may be used for different purposes before and after the inorganic light emitting device 120 is mounted on a TFT layer to be described later and electrically connected to the sub-pixel circuit 110 .

For example, before the inorganic light emitting device 120 and the sub-pixel circuit 110 are connected to each other, the transistor T19 may be turned on according to the control signal TEST to check whether the sub-pixel circuit 110 is abnormal. there is. In addition, after the inorganic light emitting device 120 and the sub-pixel circuit 110 are connected to each other, the transistor T19 is controlled to discharge the charge remaining in the junction capacitance of the inorganic light emitting device 120 as shown in FIG. 7B . It may be turned on according to a signal (Test).

In FIG. 7B , VDD_PAM is a first driving voltage (eg, + 10 [V]), VDD_PWM is a second driving voltage (eg, + 10 [V]), and VSS is a ground voltage (eg, + 10 [V]). , 0 [V]), and Vset represents a low voltage (eg, -3 [V]) for turning on the first switching transistor T17. The VDD_PAM, VDD_PWM, VSS, Vset, and Test voltages may be provided from the aforementioned power IC, but are not limited thereto.

VST(n) is a scan applied to the sub-pixel circuit 110 to initialize the voltages of node A (gate terminal of second driving transistor T6) and node B (gate terminal of first driving transistor T16) indicates a signal.

SP(n) represents a scan signal applied to the sub-pixel circuit 110 to set (or program) an image data voltage (ie, a PWM data voltage, a constant current source data voltage).

SET(n) represents an emission signal applied to the reset unit 13 of the PWM circuit 112 to turn on the first switching transistor T17.

Emi_PWM(n) turns on the transistor T5 to apply the second driving voltage VDD_PWM to the PWM circuit 112 , and turns on the transistor T15 and T12 to apply the first driving voltage VDD_PAM as a constant current An emission signal to be applied to the original circuit 111 is shown.

Sweep(n) represents a sweep signal. According to an embodiment of the present disclosure, the sweep signal may be a voltage signal that linearly changes between two different voltages, but is not limited thereto. Meanwhile, the sweep signal may be repeatedly applied in the same form for each emission section.

Emi_PAM(n) represents an emission signal for turning on the second switching transistor T18.

In the above signals, n represents the nth row line. As described above, the driver 500 drives the display panel 110 for each row line (or scan line or gate line), and thus the above-described control signals VST(n), SP(n), SET( n), Emi_PWM(n), Sweep(n), and Emi_PAM(n)) are identical to all sub-pixel circuits 110 included in the n-th row line in the same order as shown in FIG. 7C , which will be described later. can be authorized

Meanwhile, the aforementioned control signals (scan signals and emission signals) may be applied from the gate driver and may be referred to as gate signals.

Vsig(m)_R/G/B represents a PWM data voltage for each of R, G, and B sub-pixels of a pixel included in the m-th column line. Since the above-described gate signals are signals for the n-th row line, Vsig(m)_R/G/B shown in FIG. 7B is PWM applied to the pixel disposed at the intersection of the n-th row line and the m-th column line. Data voltages (specifically, PWM data voltages for each of the time division multiplexed R, G, and B sub-pixels) are indicated.

In this case, Vsig(m)_R/G/B may be applied from the data driver. In addition, as for Vsig(m)_R/G/B, a voltage between, for example, +10 [V] (black) to +15 [V] (full white) may be used, but is not limited thereto.

Meanwhile, since the sub-pixel circuit 110 shown in FIG. 7B shows the sub-pixel circuit 110 corresponding to any one of the R, G, and B sub-pixels (eg, the R sub-pixel), From among the time division multiplexed PWM data voltages, only the PWM data voltage for the R sub-pixel is selected and applied to the sub-pixel circuit 110 through a demux circuit (not shown).

VPAM_R/G/B represents a constant current source data voltage for each of R, G, and B sub-pixels included in the display panel 100 . As described above, the same constant current source data voltage may be applied to the display panel 100 .

However, the same constant current source data voltage means that the same constant current source data voltage is applied to the same type of sub-pixels included in the display panel 100, and This does not mean that the same constant current source data voltage must be applied to all sub-pixels. Since the R, G, and B sub-pixels may have different characteristics depending on the type of the sub-pixel, the constant current source data voltage may vary according to the type of the sub-pixel. Even in this case, the same constant current source data voltage may be applied to the same type of sub-pixel regardless of a column line or a row line.

Meanwhile, according to an embodiment of the present disclosure, the constant current source data voltage may not be applied from the data driver like the PWM data voltage, but may be directly applied from the power IC for each sub-pixel type.

That is, since the same constant current source data voltage may be applied to the same type of sub-pixel regardless of the column line or the row line, a DC voltage may be used as the constant current source data voltage. Accordingly, for example, three types of DC voltages (eg, +5.1 [V], +4.8 [V], +5.0 [V]) corresponding to each of the R, G, and B sub-pixels are the driving voltages. The circuit may be individually and directly applied to each of the R, G, and B sub-pixel circuits of the display panel 100 . In this case, in order to apply the constant current source data voltage to the sub-pixel circuit 110 , a demux circuit as well as a data driver is not required.

Meanwhile, according to an embodiment, when using the same constant current source data voltage for different types of sub-pixels exhibits a better characteristic, the same constant current source data voltage may be applied to different types of sub-pixels. Of course.

FIG. 7C is a timing diagram for the gate signals described above with reference to FIG. 7B .

Among the gate signals shown in FIG. 7C , VST(n) and SP(n)(①) are related to the data setting operation of the sub-pixel circuit 110 and may be called a scan signal to be distinguished from the emission signal. . Also, among the gate signals shown in FIG. 7C , Emi_PWM(n), SET(n), Emi_PAM(n), and Sweep(n)(②) are related to the light emitting operation of the sub-pixel circuit 110, and thus the emission signal can be called

As described above, according to an embodiment of the present disclosure, for one image frame, the data setting section is performed once, and the light emission section is performed a plurality of times. Accordingly, the driving unit 500 applies the scan signals (①) to each row line of the display panel 100 once in a row line order for one image frame, and applies the emission signals (②) to the display panel It is applied to each row line of (100) a plurality of times in the order of the row line.

7D is a timing diagram of various signals for driving the display panel 100 including the sub-pixel circuit of FIG. 7B during one image frame period. In FIG. 7D , a case in which the display panel 100 includes 270 row lines is exemplified.

As shown in reference numbers n-①, n+1-① to 270-①, the scan signals (VST(n), SP(n)) for the data setting operation are each row sequentially for one frame time. It can be applied once per line.

In addition, as shown in reference numbers n-②, n+1-② to 270-②, emission signals Emi_PWM(n), SET(n), Emi_PAM(n) and Sweep(n) for light-emitting operation ) may be applied to each row line a plurality of times.

Hereinafter, a detailed operation of the sub-pixel circuit 110 will be described with reference to FIGS. 7B and 7D together.

When the data setting period starts in each row line, the driver 500 first drives the first driving transistor T16 included in the constant current source circuit 111 and the second driving transistor T6 included in the PWM circuit 112 . turns on To this end, the driver 500 applies a low voltage (eg, -3 [V]) to the sub-pixel circuit 110 through the VST(n) signal.

Referring to FIG. 7B , when a low voltage is applied to the gate terminal (hereinafter referred to as node A) of the second driving transistor T6 through the transistor T2 turned on according to the VST(n) signal, the second driving Transistor T6 is turned on. In addition, when a low voltage is applied to the gate terminal (hereinafter, referred to as a B node) of the first driving transistor T16 through the transistor T11 turned on according to the VST(n) signal, the first driving transistor T16 is coming

Meanwhile, when a low voltage (eg, -3 [V]) is applied to the sub-pixel circuit 110 through the VST(n) signal, the transistor T10 is also turned on. (hereinafter referred to as a second driving voltage (eg, +10 [V]). A voltage is applied to the other end of the capacitor C2 having one end connected to the B node. In this case, the second driving voltage becomes a reference potential for setting the constant current source data voltage to be performed according to the SP(n) signal.

In the data setting period, when the first driving transistor T16 and the second driving transistor T6 are turned on through the VST(n) signal, the driving unit 500 inputs the data voltage to the A node and the B node, respectively. To this end, the driver 500 applies a low voltage to the sub-pixel circuit 110 through the SP(n) signal.

When a low voltage is applied to the sub-pixel circuit 110 through the SP(n) signal, the transistors T3 and T4 of the PWM circuit 112 are turned on. Accordingly, the PWM data voltage from the data signal line Vsig(m)_R/G/B is applied to the node A through the on transistor T3, the on-state second driving transistor T6, and the on transistor T4. can be authorized

At this time, at node A, the PWM data voltage applied from the driver 500 (specifically, the data driver) is not set as it is, but the PWM data voltage for which the threshold voltage of the second driving transistor T6 is compensated (that is, A voltage obtained by adding the PWM data voltage and the threshold voltage of the second driving transistor T6) is set.

Specifically, when the transistor T3 and the transistor T4 are turned on according to the SP(n) signal, the PWM data voltage applied to the source terminal of the transistor T3 is input to the internal compensation unit 12 . At this time, since the second driving transistor T6 is fully turned on through the VST(n) signal, the input PWM data voltage is applied to the transistor T3 and the second driving transistor T6. and the transistor T4 are sequentially passed through, and the input is started to the node A. That is, the voltage at node A starts to rise from the low voltage.

However, the voltage of node A does not rise to the input PWM data voltage, but rises only to a voltage corresponding to the sum of the PWM data voltage and the threshold voltage of the second driving transistor T6. This is because the voltage of node A is sufficiently low (eg, -3 [V]) at the time when the PWM data voltage starts to be input to the internal compensation circuit 12 so that the second driving transistor T6 is completely turned- Since it is fully turned on, sufficient current flows and the voltage at node A smoothly rises. However, as the voltage at node A increases, the voltage difference between the gate terminal (node A) and the source terminal of the second driving transistor T6 is reduced, the flow of current is reduced, and eventually, when the voltage difference between the gate terminal and the source terminal of the second driving transistor T6 reaches the threshold voltage of the second driving transistor T6, the second driving transistor T6 is off and the flow of current stops.

That is, since the PWM data voltage is applied to the source terminal of the second driving transistor T6 through the turned-on transistor T3 , the voltage of the node A is limited to the sum of the PWM data voltage and the threshold voltage of the second driving transistor T6 . this will rise

Meanwhile, when a low voltage is applied to the sub-pixel circuit 110 through the SP(n) signal line, the transistors T13 and T14 of the constant current source circuit 111 are also turned on. Accordingly, the constant current source data voltage may be applied to the node B from the data signal line VPAM_R/G/B through the on transistor T13 , the first driving transistor T16 in the on state, and the on transistor T14 . there is.

At this time, the constant current source data voltage applied from the driver 500 (specifically, the power IC) is not set at the node B as it is, but for the same reason as described above in the description of the node A, the first driving transistor T16 ), the constant current source data voltage (ie, the sum of the constant current source data voltage and the threshold voltage of the first driving transistor T16) is set.

Meanwhile, when a low voltage is applied to the sub-pixel circuit 110 through the SP(n) signal line, the transistor T9 is also turned on, and the second driving voltage VDD_PWM is transferred to the capacitor C2 through the turned-on transistor T9. ), the reference potential with respect to the constant current source data voltage (specifically, the sum of the constant current source data voltage and the threshold voltage of the first driving transistor T16) set at the node B is maintained as it is.

Meanwhile, in the above description, the PWM data voltage may be higher than the second driving voltage VDD_PWM. Accordingly, in a state in which the PWM data voltage is set at node A, the second driving transistor T6 maintains an off state. Also, the constant current source data voltage may be lower than the second driving voltage VDD_PWM. Accordingly, in a state in which the constant current source data voltage is set at node B, the first driving transistor T16 maintains an on state.

When the setting of each data voltage in the constant current source circuit 111 and the PWM circuit 112 is completed, the driving unit 500 first turns on the first switching transistor T17 in order to make the inorganic light emitting device 120 emit light. . To this end, the driving unit 500 applies a low voltage to the reset unit 13 (specifically, the transistor T8 of the reset unit 13 ) through the SET(n) signal.

When a low voltage is applied to the transistor T8 along the SET(n) signal line, the Vset voltage is charged to the capacitor C3 through the turned-on transistor T8. As described above, since Vset is a low voltage (for example, -3 [V]), when the Vset voltage is charged in the capacitor C3, the gate terminal of the first switching transistor T17 (hereinafter referred to as a C node) .), a low voltage is applied to turn on the first switching transistor T17.

Meanwhile, since the reset unit 13 operates independently of the remaining circuit components until the low voltage is applied through the Emi_PWM(n) signal line, the low voltage applied through the SET(n) signal line may It may be applied earlier than the time point shown in FIG. 7C or FIG. 7D.

When the first switching transistor T17 is turned on, the driver 500 emits light from the inorganic light emitting device 120 based on the voltages set at the A node and the B node. To this end, the driver 500 applies a low voltage to the sub-pixel circuit 110 through the Emi_PWM(n) and Emi_PAM(n) signal lines, and applies a sweep voltage to the sub-pixel circuit 110 through the Sweep(n) signal line. ) is approved.

First, the operation of the constant current source circuit 111 according to signals applied from the driver 500 during the light emission period will be described as follows.

The constant current source circuit 111 provides a constant current to the inorganic light emitting device 120 based on the voltage set at the B node.

Specifically, since a low voltage is applied to the gate terminal through the Emi_PWM(n) and Emi_PAM(n) signal lines during the emission period, the transistor T15 and the second switching transistor T18 are turned on.

Meanwhile, as described above, the first switching transistor T17 is in an on state according to the SET(n) signal.

In addition, as described above, in a state in which the sum of the constant current source data voltage (eg, +5 [V]) and the threshold voltage of the first driving transistor T16 is applied to the B node, the Emi_PWM(n) signal is Since VDD_PAM (hereinafter, referred to as a first driving voltage (eg, +10 [V])) is applied to the source terminal of the first driving transistor T16 through the turned-on transistor T15, the first driving transistor A voltage less than the threshold voltage of the first driving transistor T16 is applied between the gate terminal and the source terminal of T16, so that the first driving transistor T16 is also turned on. (For reference, in the case of a PMOSFET, a threshold voltage is applied. The voltage has a negative value, and is turned on when a voltage less than the threshold voltage is applied between the gate terminal and the source terminal, and turned off when a voltage exceeding the threshold voltage is applied.)

Accordingly, the first driving voltage is applied to the anode terminal of the inorganic light emitting device 120 through the turned-on transistor T15 , the first driving transistor T16 , the first switching transistor T17 , and the second switching transistor T18 . A potential difference exceeding the forward voltage Vf is generated at both ends of the inorganic light emitting device 120 . Accordingly, a driving current (ie, a constant current) flows through the inorganic light emitting device 120 and the inorganic light emitting device 120 starts to emit light. In this case, the magnitude of the driving current (ie, the constant current) for emitting the inorganic light emitting device 120 has a magnitude corresponding to the constant current source data voltage.

Meanwhile, since a driving current must be provided to the inorganic light emitting device 120 in the emission period, the driving voltage applied to the constant current source circuit 111 is changed from the second driving voltage VDD_PWM to the first driving voltage VDD_PAM. . Referring to FIG. 7B , when a low voltage is applied to the transistors T12 and T15 according to the Emi_PWM(n) signal, the first driving voltage VDD_PAM is applied to the capacitor through the turned-on transistors T12 and T15. It can be seen that the application is applied to the other end of (C2).

In this case, as described above, a voltage drop may occur in the first driving voltage due to an IR drop generated while a driving current flows to the inorganic light emitting device 120 . However, even when a voltage drop occurs in the first driving voltage, the voltage between the gate terminal and the source terminal of the first driving transistor T16 remains constant regardless of the voltage drop amount (ie, IR drop amount) of the first driving voltage. It remains the same as the set voltage. This is because even if the voltage applied to the other end of the capacitor C2 is changed to any voltage, the voltage of the B node is also changed by being coupled through the capacitor C2 by the amount of change.

Accordingly, according to embodiments of the present disclosure, since the second driving voltage without a voltage drop is applied to the constant current source circuit 111 in the data setting period, the correct constant current source data voltage is constant regardless of the voltage drop of the first driving voltage. It may be set in the original circuit 111 .

In addition, although the first driving voltage having a voltage drop is applied to the constant current source circuit 111 in the light emitting period, the constant current source circuit 111 normally operates in the light emitting period regardless of the voltage drop of the first driving voltage for the same reason as described above. You can see that it works.

Next, the operation of the PWM circuit 112 according to the signals applied from the driving unit 500 during the light emission period will be described as follows.

The PWM circuit 112 controls the light emission time of the inorganic light emitting device 120 based on the voltage set at the node A. Specifically, the PWM circuit 112 controls the off operation of the first switching transistor T17 based on the voltage set at the node A, so that the constant current provided by the constant current source circuit 111 to the inorganic light emitting device 120 is converted into an inorganic Time flowing through the light emitting device 120 may be controlled.

As described above, when the constant current source circuit 111 provides a constant current to the inorganic light emitting device 120 , the inorganic light emitting device 120 starts to emit light.

At this time, referring to FIG. 7B , even when the transistors T5 and T7 are turned on according to the Emi_PWM(n) signal, the second driving transistor T6 is turned off while the PWM data voltage is set as described above. Therefore, the second driving voltage VDD_PWM is not applied to the C node. Accordingly, the first switching transistor T17 continuously maintains an on state according to the SET(n) signal as described above, and the constant current provided by the constant current source circuit 111 may flow through the inorganic light emitting device 120 .

Specifically, when the transistor T5 is turned on according to the Emi_PWM(n) signal, the second driving voltage VDD_PWM is applied to the source terminal of the second driving transistor T6 through the turned-on transistor T5.

For example, as described above, when a voltage between +10 [V] (black) and +15 [V] (full white) is used as the PWM data voltage, the threshold voltage of the second driving transistor T6 is -1 Assuming [V], a voltage between +9 [V] (black) and +14 [V] (full white) is set at node A during the data setting period.

Thereafter, when a second driving voltage (eg, +10 [V]) is applied to the source terminal of the second driving transistor T6 according to the Emi_PWM(n) signal, the gate terminal of the second driving transistor T3 and The voltage between the source terminals is equal to or greater than the threshold voltage (-1 [V]) of the second driving transistor T3 (-1 [V] to +4 [V]).

Accordingly, when the second driving voltage is applied to the source terminal of the second driving transistor T6 (ie, low according to the Emi_PWM(n) signal), unless the PWM data voltage corresponding to the black grayscale is set in the A node. When a voltage is applied to the sub-pixel circuit 110), the second driving transistor T6 maintains an off state, and as long as the second driving transistor T6 maintains an off state, the first switching transistor T17 Since the on state is maintained, the inorganic light emitting device 120 maintains light emission. (On the other hand, when the PWM data voltage corresponding to the black gray level is set at the node A, when the second driving voltage is applied to the source terminal of the second driving transistor T6, the second driving transistor T6 is immediately turned on. .)

However, the voltage at the node A is changed according to the sweep signal Sweep(n) so that the voltage between the gate terminal and the source terminal of the second driving transistor T6 is reduced to the threshold voltage of the second driving transistor T6 (−1 [V]). ) or less, the second driving transistor T6 is turned on, and the second driving voltage VDD_PWM, for example, +10 [V]) is applied to the C node, so that the first switching transistor T17 is turned off. . Accordingly, the constant current no longer flows through the inorganic light emitting device 120 , and the inorganic light emitting device 120 stops emitting light.

Specifically, referring to FIG. 7C or 7D , while a low voltage is applied to the sub-pixel circuit 110 according to the Emi_PWM(n) signal, a sweep signal Sweep(n) that changes linearly, that is, a high voltage (for example, , +15 [V]) to a low voltage (eg, +10 [V]), it can be seen that the sweep voltage linearly decreasing is applied to the sub-pixel circuit 110 .

Since the voltage change of the sweep signal is coupled to the A node through the capacitor C1, the voltage of the A node also changes according to the sweep signal.

When the voltage at node A decreases according to the sweep signal and becomes a voltage corresponding to the sum of the second driving voltage and the threshold voltage of the second driving transistor T6 (ie, the gate terminal and the source of the second driving transistor T6 ) When the voltage between the terminals becomes less than or equal to the threshold voltage of the second driving transistor T6), the second driving transistor T3 is turned on.

Accordingly, a second driving voltage, which is a high voltage, is applied to the C node, that is, the gate terminal of the first switching transistor T17 through the on transistor T5, the second driving transistor T6, and the transistor T7, 1 The switching transistor T17 is turned off.

In this way, the PWM circuit 112 may control the light emission time of the inorganic light emitting device 120 based on the voltage set at the node A.

Meanwhile, when the application of the low voltage through the Emi_PWM(n) and Emi_PAM(n) signals to the sub-pixel circuit 110 is completed and the application of the sweep voltage according to the Sweep(n) signal is completed, the corresponding emission period is ended.

At this time, as shown in reference number 6 of FIG. 7C , the voltage of the sweep signal changes linearly when the light emission period ends (specifically, when the application of the low voltage through the Emi_PWM(n) signal is completed) It can be seen that the previous voltage is restored.

As described above, since the voltage change of the sweep signal is coupled to the node A through the capacitor C1, when the voltage of the sweep signal is restored as described above, the voltage of the node A is also restored.

Accordingly, according to an embodiment of the present disclosure, the voltage of node A, which is linearly changed according to the sweep signal during the first emission period among the plurality of emission periods, is the value of the sweep signal before the second emission period, which is the next emission period, starts. It is restored according to voltage restoration.

Specifically, the voltage of node A becomes the voltage obtained by adding the PWM data voltage and the threshold voltage of the second driving transistor T6 during the data setting period, and changes linearly according to the change in the voltage of the sweep signal during the light emission period, When the period ends, the voltage is restored to the sum of the PWM data voltage and the threshold voltage of the second driving transistor T6 according to the voltage restoration of the sweep signal. Accordingly, the same light emission operation is possible in the next light emission section.

In addition, as described above, in order for the inorganic light emitting device 120 to emit light during the light emission period, the first switching transistor T17 must first be turned on. However, as described above, the second driving voltage is applied to the node C while one emission period of the plurality of emission periods is in progress, so that the first switching transistor T17 is turned off. Therefore, in order to proceed with the next light emission period, the voltage of the C node needs to be reset to a low voltage in order to turn on the first switching transistor T17 .

To this end, when the next light emission period starts, the driver 500 applies a low voltage again to the gate terminal of the transistor T8 through the SET(n) signal, and accordingly, the low voltage Vset voltage is applied to the C node. is applied so that the first switching transistor T17 is turned on again.

After the first switching transistor T17 is turned on through the SET(n) signal, the driver 500 applies a low voltage to the sub-pixel circuit 110 through the Emi_PWM(n) and Emi_PAM(n) signals, and Sweep( n) By applying a sweep voltage to the sub-pixel circuit 110 through a signal, the light-emitting operation of the inorganic light-emitting device 120 may be controlled in the next light-emitting period in the same manner as described above.

Meanwhile, referring to the timing diagrams of FIGS. 7C and 7D , it can be seen that there is a difference between the time when the low voltage is applied to the Emi_PWM(n) signal and the time when the low voltage is applied to the Emi_PAM(n) signal. This is to implement a black gradation.

Specifically, when the PWM data voltage corresponding to the black gray level is set at the node A, the first switching transistor T17 should be turned off as soon as the light emission period starts. That is, theoretically, when the low voltage is applied through the Emi_PWM(n) signal, the second driving voltage VDD_PWM is C through the on transistor T5, the second driving transistor T6, and the transistor T7. When applied to the node, the first switching transistor T17 must be immediately turned off. (When the first switching transistor T17 is immediately turned off, the driving current does not flow through the inorganic light emitting device 120 at all, and a black gradation is expressed. .)

However, in reality, it takes time for the second driving voltage VDD_PWM to be charged in the C node, so that the first switching transistor T17 is not immediately turned off. Specifically, after the second driving voltage VDD_PWM is applied to the C node to start charging the capacitor C3, the first switching is performed until a voltage capable of turning off the first switching transistor T17 is charged to the C node. The transistor T17 maintains an on state, and accordingly, a driving current is leaked from the first switching transistor T17 to the inorganic light emitting device 120 .

As a result, when the first switching transistor T17 and the inorganic light emitting device 120 are directly connected without the second switching transistor T18 , even if the PWM data voltage corresponding to the black gradation is set at the node A, the first switching transistor At T17, the leaked driving current flows through the inorganic light emitting device 120 for a predetermined period of time, so that an accurate black gradation cannot be realized.

To solve this problem, according to an embodiment of the present disclosure, the second switching transistor T18 may be disposed between the first switching transistor T17 and the inorganic light emitting device 120 . Also, the driving unit 500 may apply the Emi_PAM(n) signal so that the second switching transistor T18 is turned on after a predetermined time has elapsed from the time when the low voltage is applied to the Emi_PWM(n) signal. Here, the predetermined time may be a time equal to or longer than the time during which the voltage of the C node is charged from the Vset voltage to a voltage capable of turning off the first switching transistor T17.

In this case, even though the PWM data voltage corresponding to the black gray level is set at the node A, the leakage current generated because the first switching transistor T17 is not immediately turned off may be blocked by the second switching transistor T18 . Accordingly, an accurate black gradation may be realized.

Meanwhile, referring to FIG. 7B , it can be seen that when a low voltage is applied through the SP(n) signal line, the transistor T1 is turned on and the high voltage SW_VGH of the sweep signal is applied to the X node. Through such an operation, luminance non-uniformity and horizontal crosstalk that may be caused by the sweep rod may be minimized.

Specifically, FIGS. 8A and 8B are diagrams for explaining luminance non-uniformity and horizontal crosstalk that may occur due to a sweep rod.

As described above, in various embodiments of the present disclosure, the light emitting sections sequentially proceed in the order of the row lines of the display panel 100 . Accordingly, the emission signal cannot be applied through the global signal, and an emission driver circuit for providing an emission signal corresponding to each row line is required for each row line.

In particular, the sweep signal Sweep(n) for PWM driving of the display panel 100 is also sequentially provided to the display panel 100 in the order of the row lines through the emission driver circuits respectively corresponding to the row lines. ( Hereinafter, the emission driver circuit for providing the sweep signal Sweep(n) is referred to as a sweep driver circuit.)

In this case, a change in the voltage of the A node is coupled through the capacitor C1 while the PWM data voltage is set at the gate terminal of the second driving transistor T6, ie, the A node, and the voltage of the sweep(n) signal line changes will occur in

Thereafter, the change in the voltage generated in the sweep(n) signal line is restored, and accordingly, the voltage set at the node A changes conversely. In this case, the amount of change of the node A voltage varies depending on the sweep load as will be described later, which causes luminance non-uniformity and horizontal crosstalk.

Specifically, FIG. 8A illustrates a configuration in which a sweep driver circuit 505 corresponding to one row line is connected to one sub-pixel circuit 110 through a wiring. In this case, FIG. 8A illustrates a case in which the transistor T1 is not present in the sub-pixel circuit 110 of FIG. 7B .

As shown in FIG. 8A , the sweep signal Sweep(n) is transmitted to the sub-pixel circuit 110 through the sweep driver circuit 505 . At this time, a sweep wiring resistance, that is, an RC load, exists between the sweep driver circuit 505 and the sub-pixel circuit 110 , and the size of the RC load decreases as it approaches the sweep driver circuit 505 , and is The farther away it is, the bigger it gets.

FIG. 8B shows waveforms of various signals shown in FIG. 8A. Also, in FIG. 8B , far denotes a voltage change at the A node and the X node of the sub-pixel circuit 110 disposed relatively far from the sweep driver circuit 505 , and near denotes a change in voltage of the sweep driver circuit 505 relatively far away. The voltage changes of the A node and the X node of the sub-pixel circuit 110 disposed close to each other are shown.

When the low-level scan signal SP(n) is applied to the sub-pixel circuit 110 in the data setting period, the PWM data voltage applied from the data driver is the Vsig wiring, the transistor T3, the second driving transistor T6 and It is applied to the node A through the transistor T4. In this case, the PWM data voltage is a PWM data voltage corresponding to any one of R, G, and B sub-pixels selected by the demux circuit.

In this process, as shown in FIG. 8B, as the voltage of the A node changes, the change is coupled to the X node through the capacitor C1 to the X node voltage, that is, the voltage of the Sweep(n) signal line. change will occur

Thereafter, the voltage of the Sweep(n) signal line (the voltage of the X node) is restored to the original voltage level by the operation of the sweep driver circuit 505, and the voltage change at the X node that occurs in this process is the capacitor C1 ), and inversely brings about a change in the voltage of node A.

In particular, it can be seen that the change in the voltage of the A node increases as the X node is further away from the sweep driver circuit 505 due to the sweep load.

Therefore, even when the same PWM data voltage is applied, different voltages are set in the sub-pixel circuit 110 according to the sweep load, which causes luminance non-uniformity. In addition, the luminance non-uniformity problem according to the sweep load causes horizontal crosstalk when viewed from the overall viewpoint of the display panel 100 .

The above luminance non-uniformity and horizontal crosstalk problems are caused because the voltage of the X node changes together when the PWM data voltage is applied to the A node. This can be solved by not changing it.

According to an embodiment of the present disclosure, while the PWM data voltage is set to the A node, the high voltage SW_VGH of the sweep signal as shown in FIG. 8C may be applied to the X node. In this case, the high voltage SW_VGH of the sweep signal may be a global signal that is equally applied from the power IC to all sub-pixel circuits 110 of the display panel 100 .

More specifically, referring to FIG. 7B , the PWM circuit 112 has a transistor T1 having a source terminal connected to the SW_VGH signal line, a gate terminal connected to the SP(n) signal line, and a drain terminal connected to the X node. ) is included. In this case, the source terminal of the transistor T1 may be directly connected to a wiring to which the high voltage SW_VGH of the sweep signal from the power IC is applied.

Accordingly, while the low voltage is applied through the SP(n) signal line and the PWM data voltage is set to the A node, the high voltage SW_VGH of the sweep signal applied through the turned-on transistor T1 is forcibly applied to the X node. In this case, the voltage of the X node may be maintained as the high voltage SW_VGH of the sweep signal regardless of the voltage change of the A node.

Accordingly, luminance non-uniformity and horizontal crosstalk that may be caused by the sweep rod may be prevented or minimized.

Meanwhile, as another embodiment for solving the aforementioned problems of luminance non-uniformity and horizontal crosstalk, a method of connecting the low voltage (SW_VGL) input of the sweep signal to the X node may be considered. 9A and 9B are diagrams for explaining an embodiment of connecting a low voltage (SW_VGL) input of a sweep signal to an X node.

As shown in FIG. 9A , the low voltage SW_VGL of the sweep signal may be applied to the X node. In this case, the low voltage SW_VGL of the sweep signal may be a global signal that is equally applied from the power IC to all sub-pixel circuits 110 of the display panel 100 .

Specifically, the X node may be directly connected to the power IC through a wire to which the low voltage SW_VGL of the sweep signal is applied. Accordingly, even if the voltage of the A node is changed by the application of the PWM data voltage, the voltage of the X node may be maintained as the low voltage SW_VGL of the sweep signal without being affected by the coupling through the capacitor C1.

Meanwhile, as shown in FIG. 9A , the sweep signal Sweep(n) for PWM driving may be applied to the source terminal of the second driving transistor. In this case, the sweep signal Sweep(n) may be a voltage signal in the form of linearly increasing from a low voltage to a high voltage as shown in FIG. 9B .

As described above, the PWM circuit controls the on/off operation of the first switching transistor through the on/off operation of the second driving transistor, thereby controlling the time during which the driving current flows through the inorganic light emitting device 120, which is shown in FIG. The same applies to the embodiment of 9a.

Specifically, when the voltage at the source terminal of the second driving transistor increases according to the sweep signal Sweep(n) in a state where the PWM data voltage is set at node A, the voltage difference between the gate terminal and the source terminal of the second driving transistor is will decrease

When the reduced voltage difference between the gate terminal and the source terminal of the second driving transistor reaches the threshold voltage of the second driving transistor, the second driving transistor is turned on and the first switching transistor is turned off.

It can be seen that such a PWM driving mechanism is the same as the above-described embodiment (an embodiment in which a sweep signal is applied to the X node).

According to the embodiment described above, it can be seen that the above-described problems of luminance non-uniformity and horizontal crosstalk caused by the sweep rod can be solved. At this time, even if the sweep signal is applied to the source terminal of the second driving transistor, it can be seen that there is no problem in PWM driving of the display panel 100 .

10A is a detailed circuit diagram of the sub-pixel circuit 110 according to an embodiment of the present disclosure to which the embodiment described above with reference to FIGS. 9A and 9B is applied, and FIG. 10B is a display panel 100 including the sub-pixel circuit of FIG. 10A . It is a timing diagram of various signals for driving in one image frame period.

The embodiment shown in FIGS. 10A and 10B has a configuration and an operating principle similar to those described above with reference to FIGS. 7A to 7D , and thus overlapping descriptions will be omitted, and differences will be mainly described.

In the sub-pixel circuit 110 of FIG. 10A , the SW_VGL signal line is directly connected to the X node. Accordingly, unlike the sub-pixel circuit of FIG. 7B , the transistor T1 for applying the SW_VGH signal to the X node during the data setting period is not required. Referring to FIG. 10A , it can be seen that the transistor does not exist at a position corresponding to the transistor T1 of FIG. 7B . Accordingly, when the reference numbers of the transistors of FIGS. 10A and 7B are compared, it can be seen that the reference numbers for the transistors in the same position are indicated so that FIG. 10A precedes FIG. 7B by one.

Meanwhile, in the sub-pixel circuit 110 of FIG. 7B , when the low-level Emi_PWM(n) signal is applied during the emission period, the second driving voltage VDD_PWM is applied to the source of the second driving transistor T6 through the turned-on transistor T5. Although applied to the terminal and the sweep signal Sweep(n) is applied to the X node, in the sub-pixel circuit 110 of FIG. 10A , when the low-level Emi_PWM(n) signal is applied during the emission period, the sweep signal is transmitted through the turned-on transistor T4. It can be seen that Sweep(n) (specifically, a sweep voltage that linearly changes from a low voltage to a high voltage) is applied to the source terminal of the second driving transistor T5 .

At this time, the sweep signal Sweep(n) applied to the sub-pixel circuit 110 of FIG. 7B is linearly decreasing as shown in FIG. 7D, and the sweep signal Sweep(n) applied to the sub-pixel circuit 110 of FIG. 10A is n) is a linearly increasing form as shown in FIG. 10B , and it can be seen that there is a difference from each other.

The operation of the PWM circuit 112 according to the sweep signal in the embodiment of FIG. 10A will be described in detail as an example.

For example, the voltage of +13 [V] (specifically, the PWM data voltage (+14 [V]) + the threshold voltage (-1 [V]) of the second driving transistor T5) is A during the data setting period. In the state set in the node, when a sweep signal (eg, a voltage that increases linearly from +10 [V] to +15 [V]) is applied to the source terminal of the second driving transistor T5, the second driving The voltage difference between the gate terminal and the source terminal of the transistor T5 decreases from +3 [V] to -2 [V].

At this time, when the voltage difference between the gate terminal and the source terminal of the second driving transistor T5, which has decreased from +3 [V], reaches the threshold voltage of the second driving transistor T5 (-1 [V]), the second The driving transistor T5 is turned on, and +14 [V], which is the sweep voltage when the second driving transistor T5 is turned on, is applied to the first switching transistor T16 so that the first switching transistor T16 is turned off. .

It can be seen that the operation mechanism of the PWM circuit 112 of FIG. 10A is the same as the operation mechanism of the PWM circuit 112 described with reference to FIGS. 7A to 7D except that there is a difference only in the terminal to which the sweep signal is input.

Meanwhile, since the sub-pixel circuit 110 of FIGS. 10A and 10B and the remaining contents related to its driving overlap with those described in FIGS. 7A to 7D , a description thereof will be omitted.

Hereinafter, various embodiments of a display device to which an external compensation method is applied to a deviation in electrical characteristics of a driving transistor will be described with reference to FIGS. 11 to 31B . Contents that do not contradict the embodiments related to the external compensation scheme among the descriptions of the embodiments related to the internal compensation scheme described above may be directly applied to embodiments related to the external compensation scheme to be described later.

11 is a block diagram illustrating a configuration of a display device according to an embodiment of the present disclosure. 11 , the display apparatus 1000 includes a display panel 100 , a sensing unit 200 , a correction unit 300 , and a driving unit 500 .

The driving unit 500 drives the display panel 100 . Specifically, the driver 500 may drive the display panel 100 by providing various control signals, data signals, driving voltage signals, and the like to the display panel 100 .

As described above, according to an embodiment of the present disclosure, the display panel 100 may be driven in the order of row lines. To this end, the driver 500 may include a gate driver for driving the pixels on the pixel array in a row line unit.

In addition, the driver 500 may include a data driver for providing an image data voltage (specifically, a constant current source data voltage and a PWM data voltage) and a specific voltage to be described later to each pixel (or each sub-pixel) on the pixel array. there is.

In this case, the external compensation method is different from the above-described internal compensation method in that the constant current source data voltage is provided from the data driver rather than the power IC.

Meanwhile, the driver 500 may include a DeMUX circuit for selecting each of the plurality of sub-pixels 20 - 1 to 20 - 3 constituting the pixel 10 .

In addition, the driving unit 500 applies various DC voltages (eg, the first driving voltage VDD_PAM, the second driving voltage VDD_PWM, the ground voltage VSS, the Vset voltage, etc.) to the display panel 100 . A power IC (or a driving voltage providing circuit) for providing to each included sub-pixel circuit may be included.

Also, the driving unit 500 may include a clock signal providing circuit that provides various clock signals for driving the gate driver or data driver, and a sweep signal providing circuit (or sweeping voltage) for providing a sweep signal (or sweep voltage). driver) may be included.

Meanwhile, various embodiments related to the arrangement and connection of the various drivers or circuits of the driving unit 500 and the connection to the sub-pixel circuit formed in the TFT layer are the same as described above in the description of the driving unit 500 of FIG. 4 . , duplicate descriptions are omitted.

In particular, the driving unit 500 may drive the display panel 100 in a progressive driving manner. Since a detailed description of the progressive driving method is the same as that described above with reference to FIG. 5 , a redundant description thereof will be omitted.

In this case, in embodiments of the external compensation method, during the data setting period 61 , the driver 500 may set the image data voltages in the sub-pixel circuits of the display panel 100 in a row-line order.

To this end, the driving unit 500 applies an image data voltage (a constant current source data voltage and a PWM data voltage) during the data setting period 61 , and a control signal (hereinafter, a scan signal) for setting the applied image data voltage. For example, SP(n), SPWM(n), and SCCG(n), which will be described later) may be applied to the sub-pixel circuits of each row line in order of the row line.

Also, the driver 500 may drive the sub-pixel circuits so that the pixels of the pixel array emit light in a row-line order based on the sweep signal and the set image data voltage during the light-emitting periods 62-1 to 62-7. .

To this end, the driving unit 500 includes a control signal (hereinafter, referred to as an emission signal) for controlling the driving current providing operation during the plurality of light emitting sections 62-1 to 62-7. SET(n), which will be described later, Emi_PWM(n), Emi_PAM(n), and Sweep(n)) may be applied to the sub-pixel circuits of each row line in order of the row line.

Meanwhile, as will be described later, in embodiments of the external compensation method, the current flowing through the driving transistor should be sensed by the sensing unit 200 based on a specific voltage. To this end, the driver 500 transmits a control signal (hereinafter, referred to as a sense signal) for sensing the current flowing through the driving transistor. PWM_Sen(n), CCG_Sen(n), which will be described later, of at least one row line per image frame. It can be applied to sub-pixel circuits. More details on this will be described later.

The display panel 100 includes the pixel array as described above with reference to FIG. 2 , and may display an image corresponding to an applied image data voltage.

Each sub-pixel circuit included in the display panel 100 provides a driving current whose magnitude and driving time (or pulse width) are controlled based on the image data voltage applied to the corresponding inorganic light emitting device. can

The inorganic light emitting devices constituting the pixel array emit light according to a driving current provided from a corresponding sub-pixel circuit, and thus an image may be displayed on the display panel 100 .

Meanwhile, the external compensation method compensates for deviations in threshold voltage (Vth) and mobility (μ) of driving transistors between sub-pixel circuits by sensing a current flowing through the driving transistor and correcting the image data voltage based on the sensing result. way to do it

For this external compensation operation, the display apparatus 1000 of FIG. 11 further includes a sensing unit 200 and a correction unit 300 when compared to the display apparatus 1000 of FIG. 4 .

The sensing unit 200 is configured to sense a current flowing through a driving transistor included in the sub-pixel circuit and output sensing data corresponding to the sensed current.

When a current based on a specific voltage flows through the driving transistor, the sensing unit 200 may sense the current flowing through the driving transistor, convert it into sensing data, and output the converted sensing data to the correction unit 300 .

Here, the specific voltage is a voltage applied to the sub-pixel circuit separately from the image data voltage in order to sense the current flowing through the driving transistor, and as will be described later, a first for sensing the current flowing through the driving transistor of the constant current source circuit. The specific voltage and the second specific voltage for sensing the current flowing through the driving transistor of the PWM circuit may be included.

The correction unit 300 is configured to correct the image data voltage to be applied to the sub-pixel circuit based on the sensed data output from the sensing unit 200 .

The compensating unit 300 obtains a compensation value for correcting the image data based on the voltage-specific reference data and the sensing data output from the sensing unit 200, and corrects the image data based on the obtained compensation value. The data voltage can be corrected.

Here, the reference data for each voltage is data regarding a reference current value flowing through the driving transistor when a specific voltage is applied to the driving transistor, and may be theoretically or experimentally calculated in advance and stored in the form of a lookup table, but is limited thereto. not.

The reference data for each voltage may include first reference data corresponding to a first specific voltage and second reference data corresponding to a second specific voltage, as will be described later.

The reference data for each voltage may be pre-stored in various memories (not shown) inside or outside the correction unit 300, and the correction unit 300 loads reference data for each voltage from the memory (not shown) if necessary. Available.

A specific example in which the compensator 300 obtains a compensation value by using the reference data and sensed data for each voltage and corrects the image data voltage will be described later with reference to FIG. 12 .

The driver 500 (specifically, the data driver) applies the corrected image data voltage to the display panel 100 so that deviations in threshold voltage Vth and mobility μ of the driving transistors can be compensated. there is.

On the other hand, as described above in the description of the internal compensation scheme, a resistance component exists in the display panel 100 , and the driving voltage drop due to this is also present in the display panel 100 to which the external compensation scheme is applied.

In order to solve the driving voltage drop problem, in embodiments in which an external compensation method is applied to the electrical characteristic deviation of the driving transistor, the driving voltage used in the data setting period and the light emission period is different (ie, internal compensation of IR drop) , the image data voltage is corrected (ie, external compensation of IR drop). Details on this will be described later.

Hereinafter, the configuration of the display apparatus 1000 according to an embodiment of the present disclosure and an external compensation method (for a deviation in electrical characteristics of a driving transistor) will be described in detail with reference to FIG. 12 .

12 is a detailed block diagram of a display device according to an embodiment of the present disclosure. In the description of FIG. 12 , descriptions of contents overlapping those described above will be omitted.

12 , the display apparatus 1000 includes a display panel 100 , a sensing unit 200 , a correction unit 300 , a timing controller 400 (hereinafter, referred to as TCON), and a driving unit 500 .

The TCON 400 controls the overall operation of the display apparatus 1000 . In particular, the TCON 400 may sense driving the display device 1000 . Also, the TCON 400 may display driving the display device 1000 .

Here, sensing driving is driving updating a compensation value to compensate for deviations in threshold voltage (Vth) and mobility (μ) of driving transistors included in the display panel 100 , and driving display is an image data voltage to which the compensation value is reflected. Based on the driving, the image is displayed on the display panel 100 .

When display driving is performed, the TCON 400 provides image data for an input image to the driving unit 500 . In this case, the image data provided to the driving unit 500 may be image data corrected by the correction unit 300 .

The compensator 300 may correct the image data of the input image based on the compensation value. In this case, the compensation value may be acquired by the compensator 300 through sensing driving, which will be described later.

The compensator 300 may be implemented as a function module of the TCON 400 mounted on the TCON 400 as shown in FIG. 12 . However, the present invention is not limited thereto, and may be mounted on a separate processor different from the TCON 400, and may be implemented as a separate chip in an ASIC (Application Specific Integrated Circuit) or FPGA (Field-Programmable Gate Array) method. .

The driver 500 may generate an image data voltage based on image data provided from the TCON 400 , and may provide or apply the generated image data voltage to the display panel 100 . Accordingly, the display panel 100 may display an image based on the image data voltage provided from the driver 500 .

Meanwhile, when sensing driving is performed, the TCON 400 may provide specific voltage data for sensing a current flowing through a driving transistor included in the sub-pixel circuit 110 to the driving unit 500 .

The driving unit 500 generates a specific voltage corresponding to specific voltage data and provides it to the display panel 100 . Accordingly, the driving transistor included in the sub-pixel circuit 110 of the display panel 100 has a Current can flow.

The sensing unit 200 senses the current flowing through the driving transistor and outputs the sensed data to the correcting unit 300 , and the correcting unit 300 corrects the image data based on the sensed data output from the sensing unit 200 . It is possible to obtain or update a reward value for

Hereinafter, each configuration shown in FIG. 12 will be described in more detail.

The display panel 100 includes an inorganic light-emitting device 120 constituting a sub-pixel and a sub-pixel circuit 110 for providing a driving current to the inorganic light-emitting device 120 . 12 illustrates only one sub-pixel-related configuration included in the display panel 100 for convenience of explanation, the sub-pixel circuit 110 and the inorganic light emitting device 120 may be provided for each sub-pixel.

Since the description of the inorganic light emitting device 120 is the same as that described above with reference to FIG. 6 , a redundant description thereof will be omitted.

The sub-pixel circuit 110 provides a driving current to the inorganic light emitting device 120 when the display is driven. Specifically, the sub-pixel circuit 110 generates a driving current whose size and driving time are controlled based on the image data voltage (ie, the constant current source data voltage and the PWM data voltage) applied from the driving unit 500 to the inorganic light emitting device ( 20) can be provided.

That is, the sub-pixel circuit 110 may control the luminance of the light emitted from the inorganic light emitting device 120 by driving the inorganic light emitting device 20 by PAM (Pulse Amplified Modulation) and/or PWM (Pulse Width Modulation). .

To this end, the sub-pixel circuit 110 includes a constant current generator circuit 111 for providing a constant current having a constant magnitude to the inorganic light emitting device 120 based on the constant current source data voltage, and a PWM data voltage. A PWM circuit 112 for controlling the time when the constant current flows through the inorganic light emitting device 20 may be included based on the . Here, the constant current provided to the inorganic light emitting device 120 becomes the driving current.

Meanwhile, although not shown in the drawings, the constant current source circuit 111 and the PWM circuit 112 each include a driving transistor. Hereinafter, for convenience of description, a driving transistor included in the constant current source circuit 111 is referred to as a first driving transistor, and a driving transistor included in the PWM circuit 112 is referred to as a second driving transistor.

When sensing driving is performed, when a first specific voltage is applied to the constant current source circuit 111 , a first current corresponding to the first specific voltage flows in the first driving transistor, and a second specific voltage is applied to the PWM circuit 112 . When this is applied, a second current corresponding to the second specific voltage flows through the second driving transistor.

Accordingly, the sensing unit 200 senses the first and second currents, respectively, and outputs the first sensing data corresponding to the first current and the second sensing data corresponding to the second current to the correction unit 300 , respectively. can do. To this end, the sensing unit 200 may include a current detector and an analog to digital converter (ADC). In this case, the current detector may be implemented using an operational amplifier (OP-AMP) and a current integrator including a capacitor, but is not limited thereto.

The corrector 300 may correct the image data voltage applied to the sub-pixel circuit 110 based on the sensed data.

Specifically, the correction unit 300 identifies a first reference data value corresponding to a first specific voltage in the reference data for each voltage, and identifies the first reference data value and the first reference data value output from the sensing unit 200 . A first compensation value for correcting the constant current source data voltage may be calculated or obtained by comparing one sensed data value.

In addition, the compensator 300 checks the second reference data value corresponding to the second specific voltage in the sensing data for each voltage, and compares the checked reference data value with the second sensed data value output from the sensing unit 200 . Thus, a second compensation value for correcting the PWM data voltage may be calculated or obtained.

The first and second compensation values obtained in this way may be stored or updated in a memory (not shown) inside or outside the compensator 300 as described above, and then when the display is driven, image data It can be used for voltage correction.

Specifically, the compensator 300 corrects image data to be provided to the driver 500 (particularly, a data driver (not shown)) using the compensation value, thereby applying the image data voltage to the sub-pixel circuit 110 . can be corrected. Since the data driver (not shown) provides the image data voltage to the sub-pixel circuit 110 based on the input image data, the compensator 300 corrects the image data value to be applied to the sub-pixel circuit 110 . The image data voltage can be corrected.

That is, when the display driving is performed, the compensator 300 may correct the constant current source data value among the image data based on the first compensation value. Also, the compensator 300 may correct the PWM data value among the image data based on the second compensation value. Accordingly, the correction unit 300 may correct the constant current source data voltage and the PWM data voltage applied to the sub-pixel circuit 110 by providing the corrected constant current source data and the PWM data to the driver 500 , respectively.

Meanwhile, the driver 500 may include a gate driver that provides a scan signal and an emission signal to drive the pixels on the pixel array in a row line unit. In this case, in some cases, a gate driver providing a scan signal may be referred to as a scan driver, and a gate driver providing an emission signal may be referred to as an emission driver.

Also, the driver 500 includes a data driver for providing an image data voltage (ie, a constant current source data voltage, a PWM data voltage) and a specific voltage (ie, a first specific voltage and a second specific voltage) to the sub-pixel circuits. may include In this case, the data driver (not shown) may include a digital to analog converter (DAC) for converting image data and specific voltage data provided from the TCON 400 into an image data voltage and a specific voltage, respectively.

13A and 13B are diagrams illustrating implementation examples of the sensing unit 200 . 13A and 13B , the display panel 100 includes a plurality of pixels disposed in each area where a plurality of data lines DL and a plurality of scan lines SCL intersect in a matrix form.

In this case, each pixel may include three sub-pixels such as R, G, and B. Also, as described above, the display panel 100 may include the inorganic light emitting device 120 having a color corresponding to the sub-pixel and the sub-pixel circuit 110 provided for each inorganic light emitting device.

Here, the data line DL is a video data voltage (specifically, a constant current source data voltage and a PWM data voltage) or a specific voltage (specifically, a first specific voltage and a second specific voltage) applied from the data driver 510 . voltage) to each sub-pixel circuit 110 of the display panel 100 , and the scan line SCL is a scan signal or emission signal applied from the gate driver 520 , the display panel ( This is a wiring line for driving a pixel (or sub-pixel) in a row line unit by being applied to each sub-pixel circuit 110 of 100 .

Accordingly, the image data voltage or a specific voltage applied from the data driver 510 through the data line DL is the scan signal (eg, SPWM(n), SCCG(n), It may be applied to the sub-pixel circuits of the selected row line through SP(n)).

In this case, voltages (image data voltage and specific voltage) to be applied to each of the R, G, and B sub-pixels may be time division multiplexed and applied to each pixel of the display panel 100 . Meanwhile, the time division multiplexed voltages may be respectively applied to a corresponding sub-pixel circuit through a demux circuit (not shown).

According to an embodiment, unlike FIGS. 13A and 13B , separate data lines may be provided for each R, G, and B sub-pixel. In this case, voltages to be applied to each of the R, G, and B sub-pixels (image data) voltage and a specific voltage) may be simultaneously applied to a corresponding sub-pixel through a corresponding data line. In this case, a demux circuit (not shown) will not be needed.

This is the same for the sensing line SSL. That is, according to an embodiment of the present disclosure, the sensing line SSL may be provided for each column line of the pixel as shown in FIGS. 13A and 13B . In this case, a demux circuit (not shown) is required for the operation of the sensing unit 200 for each of the R, G, and B sub-pixels.

Also, unlike the example shown in FIGS. 13A and 13B , when the sensing line SSL is provided in units of column lines of sub-pixels, for the operation of the sensing unit 200 for each of the R, G, and B sub-pixels, A separate demux circuit (not shown) is not required. However, compared to the embodiment shown in FIGS. 13A and 13B , the unit configuration of the sensing unit 200 to be described later will be required three times more.

Meanwhile, in FIGS. 13A and 13B , only one scan line SCL is illustrated for one row line for convenience of illustration. However, the actual number of scan lines may vary according to a driving method or implementation example of the pixel circuit 110 included in the display panel 100 . For example, for each row line, the aforementioned scan signals SPWM(n), SCCG(n), SP(n) or emission signals SET(n), Emi_PWM(n), Emi_PAM(n), Sweep( Scan lines for providing n)) may each be provided.

Meanwhile, as described above, the first and second currents flowing through the first and second driving transistors based on a specific voltage may be transferred to the sensing unit 200 through the sensing line SSL. Accordingly, the sensing unit 200 senses the first and second currents, respectively, and outputs the first sensing data corresponding to the first current and the second sensing data corresponding to the second current to the correction unit 300 , respectively. can do.

At this time, according to an embodiment of the present disclosure, the sensing unit 200 may be implemented as an integrated circuit (IC) separate from the data driver 510 as shown in FIG. 13A , and as shown in FIG. 13B , Likewise, it may be implemented as a single IC together with the data driver 520 .

As described above, the correction unit 300 may correct the constant current source data voltage based on the first sensed data output from the sensing unit 200 and correct the PWM data voltage based on the second sensed data. .

Meanwhile, in FIGS. 13A and 13B , the example in which the first and second currents are transmitted to the sensing unit 200 through a sensing line SSL separate from the data line DL is exemplified. However, the embodiment is not limited thereto. For example, in an example in which the data driver 520 and the sensing unit 200 are implemented as one IC as shown in FIG. 13B , the first and second currents flow through the data line DL without the sensing line SSL. An example of being transmitted to the sensing unit 200 may also be possible.

Hereinafter, various embodiments of the present disclosure related to an external compensation method for a deviation in electrical characteristics of a driving transistor will be described in detail with reference to FIGS. 14A to 31B .

In this case, embodiments in which the driving voltages used in the data setting period and the light emission period are different (ie, the internal compensation method of the IR drop) will be described in relation to the IR drop problem described above with reference to FIGS. 14A to 23B , and FIG. 24A . Examples of correcting the image data voltage in relation to the aforementioned IR drop problem (ie, an external compensation method for IR drop) will be described with reference to FIGS. 31B .

14A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to an embodiment of the present disclosure. 14A shows a circuit related to one sub-pixel, that is, one inorganic light-emitting device 120 , a sub-pixel circuit 110 for driving the inorganic light-emitting device 120 , and a driving transistor included in the sub-pixel circuit 110 . The unit configuration of the sensing unit 200 for sensing the current flowing through T3 and T9 is specifically illustrated.

Referring to FIG. 14A , the sub-pixel circuit 110 includes a constant current source circuit 111 , a PWM circuit 112 , a driving voltage changer 113 , a first switching transistor T10 , a second switching transistor T11 , and a transistor. T12 , a transistor T13 , and a transistor T14 may be included.

The constant current source circuit 111 controls on/off according to the first driving transistor T9, the capacitor C2 connected between the source terminal and the gate terminal of the first driving transistor T9, and the scan signal SP(n). and a transistor T7 for applying the constant current source data voltage applied through the data signal line Vdata_ccg to the gate terminal of the first driving transistor T9 while it is turned on.

The driving voltage changing unit 113 may change the driving voltage applied to the first driving transistor T9 . Specifically, the driving voltage changing unit 113 applies the second driving voltage VDD_PWM to the source terminal of the first driving transistor T9 during the data setting period under the control of the driving unit 500 , and during the light emission period, the first driving voltage VDD_PWM is applied. The driving voltage VDD_PAM may be applied to the source terminal of the first driving transistor T9 .

To this end, the driving voltage changing unit 113 has a source terminal connected to a terminal to which the second driving voltage VDD_PWM is applied, a drain terminal connected to a source terminal of the first driving transistor T9, and a gate terminal connected to the first driving transistor T9. The transistor T6 to which the scan signal SP(n) is applied may be included. In addition, the driving voltage changing unit 113 has a source terminal connected to a terminal to which the first driving voltage VDD_PAM is applied, a drain terminal connected to a source terminal of the first driving transistor T9, and a gate terminal connected to the EMI. It may include a transistor T8 to which the signal Emi_PWM(n) is applied.

Meanwhile, the first driving voltage VDD_PAM and the second driving voltage VDD_PWM may be applied to the sub-pixel circuit 110 from a power IC (not shown) through separate wires. Therefore, they do not affect each other. In addition, the first driving voltage VDD_PAM and the second driving voltage VDD_PWM may have the same voltage, but are not limited thereto.

The PWM circuit 112 transmits a sweep signal that is a voltage signal sweeping between the second driving transistor T3 having a source terminal connected to the second driving voltage VDD_PWM terminal and two different voltages SW_VGH and SW_VGL to the second driving transistor A capacitor C1 for coupling to the gate terminal of T3, and a PWM data voltage controlled on/off according to the scan signal SP(n) and applied through the data signal line Vdata_pwm while turned on, the second driving transistor and a transistor T2 for application to the gate terminal of T3.

Meanwhile, the PWM circuit 112 includes a reset unit 13 . The reset unit 13 is configured to forcibly turn on the first switching transistor T10 before each light emission period starts.

In order for the driving current to flow to the inorganic light emitting device 120 , the first switching transistor T10 must be in an on state. However, as will be described later, when the light emission of the inorganic light emitting device 120 is finished within each light emitting period, the first switching transistor T10 is turned off, so the first switching transistor T10 is forcibly turned off before the next light emitting period starts need to turn on

Accordingly, according to an embodiment of the present disclosure, the first switching transistor T10 is turned on at the start time of each of the plurality of light emitting sections through the operation of the reset unit 13 to be described later, so that each light emitting section This will allow it to work normally.

Meanwhile, referring to FIG. 14A , the drain terminal of the second driving transistor T3 is connected to the gate terminal of the first switching transistor T10 through the transistor T4 turned on according to the emission signal Emi_PWM(n). you can see

Accordingly, the PWM circuit 112 controls the on/off operation of the first switching transistor T10 through the operation of the reset unit 13 and the on/off operation of the second driving transistor T3 , so that the light emission period It is possible to control the time during which the driving current flows through the inorganic light emitting device 120 in the inner body.

In addition, the PWM circuit 112 includes a transistor T1. When the transistor T1 is turned on according to the SP(n) signal, it can be seen that the high voltage SW_VGH of the sweep signal is applied to the X node. Through such an operation, luminance non-uniformity and horizontal crosstalk that may be caused by the sweep rod may be minimized. Details on this will be described later.

The second switching transistor T11 has a source terminal connected to a drain terminal of the first switching transistor T10 and a drain terminal connected to an anode terminal of the inorganic light emitting device 120 . The second switching transistor T11 may be turned on/off according to the control signal Emi_PAM(n) to electrically connect/disconnect the first switching transistor T10 and the inorganic light emitting device 120 . The on/off timing of the second switching transistor T11 is related to the implementation of the black gray level, and details thereof will be described later.

The transistor T12 is connected between the anode terminal and the cathode terminal of the inorganic light emitting device 120 . The transistor T12 may be used for different purposes before and after the inorganic light emitting device 120 is mounted on a TFT layer to be described later and electrically connected to the sub-pixel circuit 110 .

For example, before the inorganic light emitting device 120 is connected to the sub-pixel circuit 110 , the transistor T12 may be turned on according to the control signal TEST to check whether the sub-pixel circuit 110 is abnormal. .

In addition, after the inorganic light emitting device 120 is connected to the sub-pixel circuit 110 , the transistor T12 is configured to discharge the charge remaining in the inorganic light emitting device 110 as shown in FIG. 14B , the control signal TEST ) can be turned on.

The transistor T14 has a source terminal connected to a drain terminal of the first driving transistor T9 and a drain terminal connected to the sensing unit 200 . The transistor T14 is turned on according to the control signal CCG_Sen(n) while sensing driving is performed, and transmits the first current flowing through the first driving transistor T9 to the sensing unit 200 through the sensing line SSL. .

The transistor T13 has a source terminal connected to a drain terminal of the second driving transistor T3 and a drain terminal connected to the sensing unit 200 . The transistor T13 is turned on according to the control signal PWM_Sen(n) while sensing driving is performed, and transmits the second current flowing through the second driving transistor T3 to the sensing unit 200 through the sensing line SSL. .

A cathode terminal of the inorganic light emitting device 120 is connected to a ground voltage (VSS) terminal.

Meanwhile, according to FIG. 14A , the unit configuration of the sensing unit 200 includes a current integrator 210 and an analog to digital converter (ADC) 220 . The current integrator 210 may include an amplifier 211 , an integrating capacitor 212 , a first switch 213 , and a second switch 214 .

The amplifier 211 is connected to the sensing line SSL and receives the first and second currents flowing through the first and second driving transistors T9 and T3 of the sub-pixel circuit 110 inverted input terminal (-); It may include a non-inverting input terminal (+) and an output terminal (Vout) to which the reference voltage Vpre is input.

The integrating capacitor 212 may be connected between the inverting input terminal (−) and the output terminal Vout of the amplifier 211 , and the first switch 213 may be connected to both ends of the integrating capacitor 212 . Meanwhile, both ends of the second switch 214 are respectively connected to the output terminal Vout of the amplifier 211 and the input terminal of the ADC 220 , and may be switched according to the control signal Sam.

Meanwhile, the unit configuration of the sensing unit 200 illustrated in FIG. 14A may be provided for each sensing line SSL. Accordingly, for example, when a sensing line is provided for each column line of a pixel in the display panel 100 including 480 pixel column lines, the sensing unit 200 may include 480 unit components. As another example, when the sensing line is provided for each column line of the R, G, and B sub-pixels in the display panel 100 including 480 pixel column lines, the sensing unit 200 includes 1440 (=480*3) It may include a unit configuration.

14B is a driving timing diagram of the sub-pixel circuit 110 shown in FIG. 14A. Specifically, FIG. 14B shows various control signals, driving voltage signals, and data signals applied to the sub-pixel circuits 110 during one image frame period and blanking period.

Referring to FIG. 14B , the display panel 100 may be driven in the order of display driving and sensing driving.

During the display driving period, control signals SP, SET, Emi_PWM, Emi_PAM, and Sweep are applied to the display panel 100 as shown in FIG. 14B . For example, during the display driving period, the sub-pixel circuits 110 included in the n-th row line of the display panel 100 have control signals SP(n), SET(n), and Emi_PWM as shown in FIG. 14B . (n), Emi_PAM(n), and Sweep(n) may be applied.

As described above, the sub-pixel circuits included in each row line of the display panel 100 may be in the order of a data setting period and a plurality of light emission periods. In addition, sub-pixel circuits included in all row lines of the display panel 100 may be driven in the row line order.

Referring to FIG. 14B , when a single row line (eg, an n-th row line) is viewed as a reference, a scan signal SP(n) related to an image data voltage setting operation is applied, and then a driving current providing operation is performed. It can be seen that the related emission signals SET(n), Emi_PWM(n), Emi_PAM(n), and Sweep(n) are applied a plurality of times.

In addition, looking at the relationship between the row lines, it can be seen that the scan signal SP(n) for the n-th row line and the scan signal SP(n+1) for the n+1-th row line are sequentially applied in the row line order. can be checked Accordingly, the emission signals SET(n), Emi_PWM(n), Emi_PAM(n), Sweep(n)) for the n-th row line and the emission signals SET( It can be seen that n+1), Emi_PWM(n+1), Emi_PAM(n+1), and Sweep(n+1)) are also sequentially applied in the order of the row lines.

Hereinafter, with reference to the control signals SP(n), SET(n), Emi_PWM(n), EMi_PAM(n) and Sweep(n)) related to the n-th row line of FIG. 14B and the circuit of FIG. 14A, A detailed operation of the sub-pixel circuit 110 will be described.

First, in the data setting section, when the low-level scan signal SP(n) is applied to the sub-pixel circuit 110 , the transistor T2 of the PWM circuit 112 , the transistor T7 of the constant current source circuit 111 , The transistor T6 of the driving voltage changing unit 113 is turned on.

When the transistor T2 is turned on, the PWM data voltage PWM data applied from the second data driver (not shown) is transmitted through the data signal line Vdata_pwm to the gate terminal (hereinafter referred to as the A node) of the second driving transistor T3 . ) is approved.

Since the second driving voltage VDD_PWM is applied to the source terminal of the second driving transistor T3 , the difference between the PWM data voltage and the second driving voltage VDD_PWM is between the gate terminal and the source terminal of the second driving transistor T3 . The corresponding voltage is set.

In this case, the PWM data voltage may be higher than the second driving voltage VDD_PWM, assuming that the threshold voltage of the second driving transistor T3 is 0 [V]. Accordingly, in a state in which the PWM data voltage is set at the node A, the second driving transistor T3 maintains an off state. This is because it is turned off when a voltage exceeding the

Meanwhile, when the transistor T7 is turned on, the constant current source data voltage CCG data applied from the first data driver (not shown) passes through the data signal line Vdata_ccg to the gate terminal of the first driving transistor T9 (hereinafter referred to as hereinafter). , referred to as B node).

Since the transistor T6 of the driving voltage changing unit 113 is also turned on according to the scan signal SP(n), the second driving voltage VDD_PWM is applied to the source terminal of the first driving transistor T9 during the data setting period. Accordingly, a voltage corresponding to the difference between the constant current source data voltage and the second driving voltage VDD_PWM is set between the gate terminal and the source terminal of the first driving transistor T9 .

In this case, the constant current source data voltage may be lower than the second driving voltage VDD_PWM when it is assumed that the threshold voltage of the first driving transistor T9 is 0 [V]. Accordingly, while the constant current source data voltage is set at the node B, the first driving transistor T8 maintains an on state. (The PMOSFET is turned on when a voltage less than a threshold voltage is applied between the gate terminal and the source terminal, and the threshold voltage This is because it is turned off when a voltage exceeding the

Meanwhile, when the first emission period for the n-th row line starts, a low-level emission signal SET(n) is applied to the transistor T5 . Accordingly, the low voltage Vset is charged in the capacitor C3 through the turned-on transistor T5, and the low voltage is applied to the gate terminal (hereinafter, referred to as the C node) of the first switching transistor T10 to apply the first The switching transistor T10 is turned on.

Thereafter, during the first emission period, the emission signals Emi_PWM(n), Emi_PAM(n) and Sweep(n) are applied to the sub-pixel circuit 110 as shown in FIG. 14B .

Specifically, when the low-level emission signal Emi_PWM(n) is applied to the transistor T8 of the driving voltage changing unit 113 , the transistor T8 is turned on, and the One driving voltage VDD_PAM is applied.

At this time, even when the voltage applied to the source terminal of the first driving transistor T9 is changed from the second driving voltage VDD_PWM to the first driving voltage VDD_PAM, between the source terminal and the gate terminal of the first driving transistor T9 It can be seen that the voltage of is maintained as it is in the data setting period by the capacitor C2. Accordingly, the first driving transistor T9 still maintains an on state.

Meanwhile, when the low-level emission signal Emi_PAM(n) is applied to the second switching transistor T11 , the second switching transistor T11 is turned on.

As a result, the transistor T8 turned on according to the Emi_PWM(n) signal, the first driving transistor T9 maintaining the on state, the first switching transistor T10 turned on according to the SET(n) signal, and the Emi_PAM(n) signal The first driving voltage VDD_PAM is applied to the anode terminal of the inorganic light emitting device 120 through the second switching transistor T11 that is turned on according to , and a driving current flows through the inorganic light emitting device 120 .

At this time, the magnitude of the driving current is determined by the voltage difference between the gate terminal and the source terminal of the first driving transistor T9 , in particular, the magnitude of the constant current source data voltage set at the gate terminal of the first driving transistor T9 . do.

On the other hand, when the emission signal Sweep(n) (for example, a sweep voltage that decreases linearly as shown in FIG. 14B) is applied to the capacitor C1, the applied sweep voltage is coupled to the A node, Accordingly, the voltage at node A also decreases linearly.

Accordingly, when the difference between the voltage of node A and the second driving voltage VDD_PWM reaches the threshold voltage value of the second driving transistor T3 , the second driving transistor T3 is turned on, and the second driving transistor is turned on. The high level second driving voltage VDD_PWM is applied to the gate terminal of the first switching transistor T10 through T3. (At this time, of course, the transistor T4 is also turned on according to the low-level emission signal Emi_PWM(n).)

Accordingly, the first switching transistor T10 is turned off, the driving current no longer flows to the inorganic light emitting device 120 , and the inorganic light emitting device 120 stops emitting light. In this case, the time during which the driving current flows through the inorganic light emitting device 120 is determined by the voltage difference between the gate terminal and the source terminal of the second driving transistor T3 , in particular, the PWM set at the gate terminal of the second driving transistor T3 . It is determined by the size of the data voltage.

Meanwhile, the emission signals SET(n), Emi_PWM(n), Emi_PAM(n), and Sweep(n) are equally applied in the second and subsequent emission periods for the n-th row line, respectively. Accordingly, the inorganic light emitting devices 120 of the n-th row line also emit light in the second and subsequent light-emitting sections based on the image data voltage set in the data setting section, respectively.

On the other hand, even after the light emission of the inorganic light emitting device 120 is terminated, charges may remain in the inorganic light emitting device 120 (specifically, in the junction capacitance of the inorganic light emitting device 120 ). Due to this, a problem may be caused in that the inorganic light emitting device 20 emits light even after the light emitting period has ended, which may be particularly problematic when expressing a low gray level (eg, black).

Accordingly, according to an embodiment of the present disclosure, as shown in FIG. 14B , a low-level TEST signal may be applied to the sub-pixel circuit 110 after display driving and sensing driving are completed. In this case, the TEST signal may be a global signal that is simultaneously applied to all sub-pixel circuits 110 of the display panel 100 . Accordingly, the charge remaining in the inorganic light emitting device 120 through the turned-on transistor T12 is completely discharged to the ground voltage (VSS) terminal, and the above-described problem can be solved.

On the other hand, according to an embodiment, different from that shown in FIG. 14B , the low-level emission signal TEST(n) is applied after each emission period ends (that is, after the low-level emission signal Emi_PWM(n) is applied. ), an example of discharging the charge remaining in the inorganic light emitting device 120 to the ground voltage (VSS) terminal may be possible by immediately applying the same.

In the above, only the operation related to the n-th row line has been described, but the operation for the remaining row lines may also be fully understood through the above description.

Meanwhile, looking closely at the timing diagram of FIG. 14B , it can be seen that there is a difference between the emission signal Emi_PWM(n) and the emission signal Emi_PAM(n) at the low level. This is to implement a black gradation as described above.

Specifically, when the PWM data voltage corresponding to the black gray level is set at the node A, the first switching transistor T10 must be turned off as soon as the light emission period starts. That is, theoretically, when the emission signal Emi_PWM(n) becomes low, the second driving voltage VDD_PWM is applied to the node C through the on second driving transistor T3 and the on transistor T4, The first switching transistor T10 must be turned off immediately. (When the first switching transistor T10 is immediately turned off, the driving current does not flow through the inorganic light emitting device 120 at all, and a black gradation is expressed.)

However, in reality, it takes time until the second driving voltage VDD_PWM is charged in the C node, so that the first switching transistor T10 is not immediately turned off. Specifically, after the second driving voltage VDD_PWM is applied to the C node to start charging the capacitor C3, the transistor T10 is charged with a voltage capable of turning off the first switching transistor T10 until the C node is charged. ) maintains an on state, and accordingly, leakage of driving current occurs in the first switching transistor T10.

As a result, when the first switching transistor T10 and the inorganic light emitting device 120 are directly connected without the second switching transistor T11 , even if the PWM data voltage corresponding to the black gray level is set at the node A, the first switching transistor At T10 , the leaked driving current flows through the inorganic light emitting device 120 for a predetermined period of time, so that an accurate black gradation cannot be realized.

To solve this problem, according to an embodiment of the present disclosure, the second switching transistor T11 may be disposed between the first switching transistor T10 and the inorganic light emitting device 120 . Also, the driver 500 may apply the emission signal Emi_PAM(n) so that the second switching transistor T11 is turned on after a predetermined time has elapsed from the time when the emission signal Emi_PWM(n) becomes the low level. Here, the predetermined time may be a time equal to or longer than a time during which the voltage of node C is charged from the voltage Vset to a voltage capable of turning off the first switching transistor T10.

In this case, even though the PWM data voltage corresponding to the black gray level is set at the node A, the leakage current generated because the first switching transistor T10 is not immediately turned off may be blocked by the second switching transistor T11 . Accordingly, an accurate black gradation may be realized.

Meanwhile, referring to FIGS. 14A and 14B , the source terminal of the first driving transistor T9 of the constant current source circuit 111 is driven differently in the data setting period and the light emission period through the driving voltage changing unit 113 . You can see the voltage applied.

This is achieved between the gate terminal and the source terminal of the first driving transistor T9 by applying the second driving voltage VDD_PWM in which a voltage drop does not occur due to the driving current to the constant current source circuit 111 during the data setting period. This is to ensure that the correct voltage is set.

Specifically, as described above, since the resistance component is present in the display panel 100 , an IR drop occurs when a driving current flows, thereby causing a drop in the first driving voltage VDD_PAM. In addition, in various embodiments of the present disclosure, since the display panel 100 is driven in a progressive driving method, some row-line sub-pixel circuits operate in the light-emitting period while other row-line sub-pixel circuits operate in the data setting period will do

Accordingly, when the first driving voltage VDD_PAM is equally applied to the constant current source circuit 111 in the data setting period and the light emission period, the first driving voltage VDD_PAM applied to the constant current source circuits 111 of the low line operating in the data setting period The first driving voltage VDD_PAM is affected by a drop of the first driving voltage VDD_PAM due to the constant current source circuits 111 of the low line operating in the emission period. This prevents the correct constant current source data voltage from being set in the constant current source circuits 111 of the row line operating in the data setting period.

In addition, the resistance component actually present in the display panel 100 has a different value for each area of the display panel 100 . Accordingly, when the driving current flows, a difference occurs in the IR drop value for each region of the display panel 100 , that is, the drop level of the first driving voltage VDD_PAM, which also needs to be compensated for.

In order to solve the IR drop problem, according to an embodiment of the present disclosure, the driving unit 500 sets the second driving voltage VDD_PWM without a voltage drop according to the driving current during the data setting period to the constant current source circuit 111 . The driving voltage changing unit 113 may be controlled to be applied to the .

Accordingly, the constant current source data voltage is set in the constant current source circuit 111 based on the second driving voltage VDD_PWM during the data setting period.

Thereafter, the driving voltage applied to the constant current source circuit 111 is changed to the first driving voltage VDD_PAM in the light emission period, but the voltage between the gate terminal and the source terminal of the first driving transistor T9 set in the data setting period is changed to a capacitor Since it is maintained by (C2), an accurate constant current source data voltage can be set in the constant current source circuit 111 irrespective of whether or not the first driving voltage VDD_PAM has dropped or the degree of the drop.

Meanwhile, no driving current flows through the second driving transistor T2 of the PWM circuit 112 . Accordingly, the second driving voltage VDD_PWM during the data setting period and the light emission period does not have a voltage drop or is negligible even if it occurs, so the PWM circuit 112 has the same second driving voltage in the data setting period and the light emission period. Even if (VDD_PWM) is applied, there is no problem.

As described above, the method of including the driving voltage changing unit 113 in the sub-pixel circuit 110 and solving the above-described IR drop problem through the operation of the driving voltage changing unit 113 is called the IR drop internal compensation method. decide to do On the other hand, as will be described later with reference to FIGS. 24A to 31B , a method of solving the above-mentioned IR drop problem by correcting the image data voltage will be referred to as an external IR drop compensation method.

Meanwhile, according to an embodiment of the present disclosure, the same constant current source data voltage may be applied to all constant current source circuits 111 of the display panel 100 . Accordingly, the driving current (ie, constant current) of the same size is provided to the inorganic light emitting device 120 through the constant current source circuit 111, and accordingly, the problem of the wavelength change of the LED due to the change in the size of the driving current can be solved. can

Also, a PWM data voltage corresponding to a gray level value of each sub-pixel may be applied to each PWM circuit 112 of the display panel 100 . Accordingly, the gray level of each sub-pixel may be expressed by controlling the driving time of the driving current through the PWM circuit 112 .

Meanwhile, the same constant current source voltage may be applied to one display panel 100 , but different constant current source voltages may be applied to another display panel. Accordingly, when a plurality of display panels are connected to form one large display device, a brightness deviation or a color deviation between display panels that may occur may be compensated for by adjusting the constant current source voltage.

In the above, it has been described that the same constant current source data voltage is applied to the constant current source circuit 111 for convenience of explanation in terms of solving the problem of the wavelength change of the LED and expressing the grayscale of the image. However, as described above, in various embodiments of the present disclosure, since the constant current source data voltage is corrected to compensate for the threshold voltage and mobility deviation between the first driving transistors T9 , the constant current source circuit 111 is actually sensing The constant current source data voltage whose value is corrected through driving is applied. Accordingly, unlike the internal compensation method in which the constant current source data voltage is applied from the power IC, the external compensation method receives the constant current source data voltage from the data driver.

Referring back to FIG. 14B , the sensing driving section may include a sensing section (①) of the PWM circuit 112 and a sensing section (②) of the constant current source circuit 111 .

During the sensing period (①) of the PWM circuit 112 , the second current flowing through the second driving transistor T3 is transferred to the sensing unit 200 based on the second specific voltage.

During the sensing period (②) of the constant current source circuit 111 , the first current flowing through the first driving transistor T9 is transferred to the sensing unit 200 based on the first specific voltage.

Accordingly, the sensing unit 200 may output the first sensing data and the second sensing data, respectively, based on the first and second currents.

In this case, according to an embodiment of the present disclosure, the sensing driving may be performed within the blanking period 65 as shown in FIG. 14B . The blanking period 65 refers to a time period in which valid image data is not input to the display panel 100 . Taking a 120 Hz image as an example, the display driving period may occupy about 7.3 ms and the blanking period about 1 ms within one image frame time, but is not limited thereto.

Accordingly, the sensing unit 200 senses the current flowing through the driving transistors T9 and T3 based on a specific voltage applied within the blanking period 65 of one image frame, and outputs sensing data corresponding to the sensed current. can do.

However, the embodiment is not limited thereto. For example, the sensing driving may be performed during a boot-up period, a power-off period, or a screen-off period of the display apparatus 1000 . Here, the booting period refers to a period from when the system power is applied to before the screen is turned on, the power-off period refers to the period from when the screen is turned off to when the system power is released, and the screen-off period refers to the period from when the system power is released. may mean a period in which the screen is off although being authorized.

Hereinafter, an operation of the display apparatus 1000 in the sensing driving period will be described in more detail with reference to FIGS. 14A and 14B .

Specifically, a second specific voltage is applied from a second data driver (not shown) to the data signal line Vdata_pwm during the sensing period (①) of the PWM circuit 112 . The second specific voltage may be any predetermined voltage for turning on the second driving transistor T3 . At this time, the transistor T2 is turned on according to the scan signal SP(n), and a second specific voltage is input to the node A through the turned-on transistor T2.

In the sensing section (①) of the PWM circuit 112, the transistor T13 is turned on according to the control signal PWM_Sen(n), and a second current flowing through the second driving transistor T3 through the turned-on transistor T13 is transmitted to the sensing unit (200).

Meanwhile, during the PWM circuit 112 sensing period (①), the first switch 213 of the sensing unit 200 is turned on and off according to the control signal Spre. Hereinafter, a period in which the first switch 213 is turned on is referred to as a first initialization period and a period in which the first switch 213 is turned off in the sensing period (①) of the PWM circuit 112 is referred to as a first sensing period.

In the first initialization period, since the first switch 213 is in an on state, the reference voltage Vpre input to the non-inverting input terminal (+) of the amplifier 211 is maintained at the output terminal Vout of the amplifier 211 . .

Since the first switch 213 is turned off during the first sensing period, the amplifier 211 operates as a current integrator to integrate the second current. In this case, the voltage difference across the integrating capacitor 212 due to the second current flowing into the inverting input terminal (-) of the amplifier 211 in the first sensing period increases as the sensing time elapses, that is, as the amount of accumulated charge increases.

However, due to the characteristics of the virtual ground of the amplifier 211, the voltage of the inverting input terminal (-) in the first sensing period is maintained as the reference voltage Vpre regardless of the increase in the voltage difference of the integrating capacitor 212, The voltage of the output terminal Vout of the amplifier 211 is lowered in response to the voltage difference between both ends of the integrating capacitor 212 .

According to this principle, the second current flowing into the sensing unit 200 in the first sensing period is accumulated as an integral value Vpsen, which is a voltage value, through the integrating capacitor 212 . Since the falling slope of the voltage of the output terminal Vout of the amplifier 211 increases as the second current increases, the magnitude of the integral value Vpsen decreases as the second current increases.

The integral value Vpsen is input to the ADC 220 while the second switch 214 is maintained in the on state in the first sensing period, is converted into the second sensed data in the ADC 200, and then output to the compensator 300 will become

Meanwhile, during the sensing period (②) of the constant current source circuit 111 , a first specific voltage is applied from a first data driver (not shown) to the data signal line Vdata_ccg. The first specific voltage is a predetermined voltage for turning on the first driving transistor T9. At this time, the transistor T7 is turned on according to the scan signal SP(n), and a first specific voltage is input to the node B through the turned-on transistor T7.

In the constant current source circuit 111 sensing section (②), the transistor T14 is turned on according to the control signal CCG_Sen(n), and a first current flowing through the first driving transistor T9 through the turned-on transistor T14 is sensed. is transferred to the unit 200 .

Meanwhile, even during the constant current source circuit 111 sensing period (②), the first switch 213 of the sensing unit 200 is turned on and off according to the control signal Spre. Hereinafter, a period in which the first switch 213 is turned on in the sensing period (②) of the constant current source circuit 111 is referred to as a second initialization period, and a period in which the first switch 213 is turned off is referred to as a second sensing period.

In the second initialization period, since the first switch 213 is in an on state, the reference voltage Vpre input to the non-inverting input terminal (+) of the amplifier 211 is maintained at the output terminal Vout of the amplifier 211 . .

Since the first switch 213 is turned off in the second sensing period, the amplifier 211 operates as a current integrator to integrate the first current. At this time, in the second sensing period, the voltage difference between both ends of the integrating capacitor 212 due to the first current flowing into the inverting input terminal (-) of the amplifier 211 increases as the sensing time elapses, that is, as the amount of accumulated charge increases.

However, due to the characteristics of the virtual ground of the amplifier 211, the voltage of the inverting input terminal (-) in the second sensing period is maintained as the reference voltage Vpre regardless of the increase in the voltage difference of the integrating capacitor 212, The voltage of the output terminal Vout of the amplifier 211 is lowered in response to the voltage difference between both ends of the integrating capacitor 212 .

According to this principle, the first current flowing into the sensing unit 200 in the second sensing period is accumulated as an integral value Vcsen, which is a voltage value, through the integrating capacitor 212 . Since the falling slope of the voltage of the output terminal Vout of the amplifier 211 increases as the first current increases, the magnitude of the integral value Vcsen decreases as the first current increases.

The integral value Vcsen is input to the ADC 220 while the second switch 214 is maintained in the on state in the second sensing period, is converted into the first sensed data in the ADC 220, and then output to the compensator 300 will become

Accordingly, as described above, the compensator 300 performs first and second steps based on the reference data for each voltage stored in a memory (not shown) and the first and second sensing data output from the sensing unit 200 . Each of the compensation values may be obtained, and the obtained first and second compensation values may be stored or updated in a memory (not shown). Thereafter, when the display driving is performed, the compensator 300 may respectively correct the constant current source data voltage and the PWM data voltage to be applied to the sub-pixel circuit 110 based on the first and second compensation values.

Meanwhile, according to an embodiment of the present disclosure, the first specific voltage and the second specific voltage may be applied to sub-pixel circuits of one row line per one image frame. That is, according to an embodiment of the present disclosure, the above-described sensing driving may be performed for one row line per one image frame.

In this case, the above-described sensing driving may be sequentially performed in the order of the row lines of the display panel 100 . Accordingly, for example, when the display panel 100 is composed of 270 row lines, the sub-pixel circuits of the first row line are sensed after the first image frame is displayed, and the second image frame is displayed on the second row line. The included sub-pixel circuits may be sensing-driven. In this way, after the 270th image frame is displayed, the subpixel circuits of the 270th row are sensed and driven, so that the sensing driving of the subpixel circuits included in all the rowlines included in the display panel 100 is completed once. can

Alternatively, the above-described sensing driving may be performed in a random order of row lines. In this case, in the above example, all row lines of the display panel 100 may be sensed and driven in a random order while consecutive 270 image frames are displayed.

Meanwhile, according to another embodiment of the present disclosure, the first specific voltage and the second specific voltage may be applied to sub-pixel circuits of a plurality of row lines per one image frame. That is, the above-described sensing driving may be performed for a plurality of row lines per one image frame. Even in this case, the above-described sensing driving may be performed sequentially or in a random order in units of a plurality of row lines.

In the above, the sensing driving is carried out in the order of the PWM circuit 112 sensing section (①) and the constant current source circuit 111 sensing section (②) as an example, but it is not limited thereto, and according to the embodiment, the constant current source circuit Of course, it is also possible that the (111) sensing section (②) proceeds first, and the PWM circuit 112 sensing section (①) proceeds thereafter.

In addition, in the above description, the sensing driving is performed after the display driving as an example, but the present invention is not limited thereto. In some embodiments, the sensing driving may be performed first and the display driving may be performed thereafter.

Hereinafter, with respect to the transistor T1 of FIG. 14A , problems of luminance non-uniformity and horizontal crosstalk that may occur due to the sweep load will be described, and the high voltage SW_VGH of the sweep signal through the transistor T1 during the data setting period. It explains that this problem can be solved by applying to the X node.

15A and 15B are diagrams for explaining luminance non-uniformity and horizontal crosstalk that may occur due to a sweep load in a sub-pixel circuit to which an external compensation method for a deviation in electrical characteristics of a driving transistor is applied.

As described above, in various embodiments of the present disclosure, the light emitting sections sequentially proceed in the order of the row lines of the display panel 100 . Therefore, it is impossible to apply the emission signal to the display panel 110 at once through the global signal, and an emission driver circuit for providing the emission signal corresponding to each row line is required for each row line. .

In particular, the sweep signal Sweep(n) for PWM driving of the display panel 100 is also sequentially provided to the display panel 100 in the order of the row lines through the emission driver circuits respectively corresponding to the row lines. ( Hereinafter, the emission driver circuit for providing the sweep signal Sweep(n) is referred to as a sweep driver circuit.)

In this case, a change in the voltage of the A node is coupled through the capacitor C1 while the PWM data voltage is set at the gate terminal of the second driving transistor T3, ie, the A node, and the voltage of the sweep(n) signal line changes will occur in

Thereafter, the change in the voltage generated in the sweep(n) signal line is restored, and accordingly, the voltage set at the node A changes conversely. In this case, the amount of change of the node A voltage varies depending on the sweep load as will be described later, which causes luminance non-uniformity and horizontal crosstalk.

Specifically, FIG. 15A illustrates a configuration in which a sweep driver circuit 505 corresponding to one row line is connected to one sub-pixel circuit 110 through a wiring. In this case, FIG. 15A illustrates a case in which the transistor T1 is not present in the sub-pixel circuit 110 of FIG. 14A .

As shown in FIG. 15A , the sweep signal Sweep(n) is transmitted to the sub-pixel circuit 110 through the sweep driver circuit 505 . At this time, a sweep wiring resistance, that is, an RC load, exists between the sweep driver circuit 505 and the sub-pixel circuit 110 , and the size of the RC load decreases as it approaches the sweep driver circuit 505 , and is The farther away, the bigger it gets.

15B shows waveforms of various signals shown in FIG. 15A. In addition, in FIG. 15B , far denotes a voltage change at node A and node X of the sub-pixel circuit 110 disposed relatively far from the sweep driver circuit 505 , and near denotes a change in voltage at a node relatively far from the sweep driver circuit 505 . The voltage changes of the A node and the X node of the sub-pixel circuit 110 disposed close to each other are shown.

When the low-level scan signal SP(n) is applied to the sub-pixel circuit 110 in the data setting period, the PWM data voltage applied from the data driver is applied to the node A through the Vsig wiring and the transistor T2. In this case, the PWM data voltage is a PWM data voltage corresponding to any one of R, G, and B sub-pixels selected by the demux circuit.

In this process, as the voltage of the A node changes, as shown in FIG. 15B, the change is coupled to the X node through the capacitor C1 to the X node voltage, that is, the voltage of the Sweep(n) signal line. change will occur

Thereafter, the voltage of the Sweep(n) signal line (the voltage of the X node) is restored to the original voltage level by the operation of the sweep driver circuit 505, and the voltage change at the X node that occurs in this process is the capacitor C1 ), and inversely brings about a change in the voltage of node A.

In particular, it can be seen that the change in the voltage of the A node increases as the X node is further away from the sweep driver circuit 505 due to the sweep load.

Therefore, even when the same PWM data voltage is applied, different voltages are set in the sub-pixel circuit 110 according to the sweep load, which causes luminance non-uniformity. In addition, the luminance non-uniformity problem according to the sweep load causes horizontal crosstalk when viewed from the overall viewpoint of the display panel 100 .

The above luminance non-uniformity and horizontal crosstalk problems are caused because the voltage of the X node changes together when the PWM data voltage is applied to the A node. This can be solved by not changing it.

According to an embodiment of the present disclosure, while the PWM data voltage is set in the A node, the high voltage SW_VGH of the sweep signal as shown in FIG. 15C may be applied to the X node. In this case, the high voltage SW_VGH of the sweep signal may be a global signal that is equally applied to all sub-pixel circuits 110 of the display panel 100 from the power IC.

More specifically, referring to FIG. 14A , the PWM circuit 112 has a transistor T1 having a source terminal connected to the SW_VGH signal line, a gate terminal connected to the SP(n) signal line, and a drain terminal connected to the X node. ) is included. In this case, the source terminal of the transistor T1 may be directly connected to a wiring to which the high voltage SW_VGH of the sweep signal from the power IC is applied.

Accordingly, while the low voltage is applied through the SP(n) signal line and the PWM data voltage is set to the A node, the high voltage SW_VGH of the sweep signal applied through the turned-on transistor T1 is forcibly applied to the X node. In this case, the voltage of the X node may be maintained as the high voltage SW_VGH of the sweep signal regardless of the voltage change of the A node.

Accordingly, luminance non-uniformity and horizontal crosstalk that may be caused by the sweep rod may be prevented or minimized.

Hereinafter, various embodiments of the present disclosure will be described with reference to FIGS. 16A to 18B . At this time, since the embodiments shown in FIGS. 16A to 18B have similar configurations and operating principles to those described above with reference to FIGS. 14A to 15B , overlapping descriptions will be omitted and differences will be mainly described.

16A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to another embodiment of the present disclosure, and FIG. 16B is a driving timing diagram of the sub-pixel circuit 110 shown in FIG. 16A.

The sub-pixel circuit 110 shown in FIG. 16A receives separate control signals (PWM_Sen(n) and CCG_Sen(n) in FIG. 14A) to control on/off of the transistors T13 and T14. It is different from FIG. 14A only in that the scan signal SP(n) is not used and the rest is the same as the sub-pixel circuit 110 shown in FIG. 14A. The driving timing diagram shown in FIG. 14B is also the same as the driving timing diagram of FIG. 14B except that there are no control signals PWM_Sen(n) and CCG_Sen(n).

16A and 16B , as the low-level scan signal SP(n) is applied during the data setting period, not only the transistors T1, T2, T6, and T7 but also the transistors T13 and T14 are turned on. However, in this case, by turning off a switch (not shown) inside the amplifier 211 , it is possible to prevent current from flowing to the sensing unit 200 . Accordingly, the sensing driving operation is not performed during the data setting period, and only the data setting operation is performed.

Meanwhile, in the sensing driving period, a switch (not shown) inside the above-described amplifier 211 may be turned on. Accordingly, in the sensing driving period, the above-described first and second currents flow to the sensing unit 200 , and accordingly, the above-described sensing driving may be performed.

At this time, the second specific voltage is applied to the gate terminal of the second driving transistor T3 during the PWM circuit 112 sensing section (①), and the first specific voltage is applied to the second specific voltage during the constant current source circuit 111 sensing section (②). It is applied to the gate terminal of the first driving transistor T9, and a time for which the second specific voltage is applied and a time for which the first specific voltage is applied do not overlap with each other. Accordingly, it can be seen that the sensing driving operation described with reference to FIGS. 14A and 14B can be performed in the same manner even if the separate control signals PWM_Sen(n) and CCG_Sen(n) are not used.

In addition, the remaining contents related to display driving, sensing driving, and prevention of luminance non-uniformity and horizontal crosstalk caused by a sweep load of the sub-pixel circuit 110 can be fully understood through the foregoing in FIGS. 14A to 15C , A duplicate description will be omitted.

17A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to another embodiment of the present disclosure, and FIG. 17B is a driving timing diagram of the sub-pixel circuit 110 shown in FIG. 17A.

The sub-pixel circuit 110 illustrated in FIG. 17A is the same as the sub-pixel circuit 110 illustrated in FIG. 14A except that an image data voltage and a specific voltage are applied through one data signal line Vdata. Do.

In this case, the PWM data voltage and the constant current source data voltage from one data driver are time-divided and applied to the sub-pixel circuit 110 through the data signal line Vdata during the data setting period, and also the data signal during the sensing driving period. Through the line Vdata, the second specific voltage and the first specific voltage are time-divided from the one data driver to be applied to the sub-pixel circuit 110 .

Therefore, the PWM data voltage and the constant current source data voltage applied in time division during the data setting period are respectively applied to the A node and the B node, and the second specific voltage and the first specific voltage applied in time division during the sensing driving period are applied to the A node and the In order to respectively apply to the B node, two scan signals are required, and the scan signal SPWM(n) and the scan signal SCCG(n) in FIGS. 17A and 17B show these two scan signals.

17A and 17B , when the low-level scan signal SPWM(n) is applied to the sub-pixel circuit 110 in the data setting period, the PWM data voltage PWM data A applied to the node. Also, when the low-level scan signal SCCG(n) is applied to the sub-pixel circuit 110 , the constant current source data voltage CCG data is applied to the node B through the turned-on transistor T7 .

On the other hand, when the low-level scan signal SPWM(n) is applied to the sub-pixel circuit 110 during the sensing period (①) of the PWM circuit 112 during the sensing driving period, the second specific voltage is generated through the turned-on transistor T2. It is input to node A. Also, when the low-level scan signal SCCG(n) is applied to the sub-pixel circuit 110 , the first specific voltage is input to the node B through the turned-on transistor T7 .

Meanwhile, in FIG. 17B , the scan signal is applied in the order of SPWM(n) and SCCG(n) as an example, but the present invention is not limited thereto. Of course, the signal may be applied thereafter.

In addition, the remaining contents related to display driving, sensing driving, and prevention of luminance non-uniformity and horizontal crosstalk caused by a sweep load of the sub-pixel circuit 110 can be fully understood through the foregoing in FIGS. 14A to 15C , A duplicate description will be omitted.

18A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to another embodiment of the present disclosure, and FIG. 18B is a driving timing diagram of the sub-pixel circuit 110 shown in FIG. 18A.

The sub-pixel circuit 110 shown in FIG. 18A includes an image data voltage (PWM data voltage, constant current source data voltage) and a specific voltage (a second specific voltage, a first specific voltage) through one data signal line Vdata. It is similar to the sub-pixel circuit 110 of FIG. 17A in that it is applied.

Therefore, referring to FIGS. 18A and 18B , using two scan signals (or scan signal lines) such as SPWM(n) and SCCG(n), the image data voltage and the specific voltage are applied in the data setting period and the sensing driving period. It can be seen that each is applied to the sub-pixel circuit 110 .

On the other hand, the sub-pixel circuit 110 shown in FIG. 18A controls the on/off of the transistor T13 and the transistor T14 with separate control signals (PWM_Sen(n) and CCG_Sen of FIG. 14A or 17A ). (n)) is not used and a scan signal is used, which is similar to the embodiment of FIG. 16A .

In the case of the embodiment of FIG. 18A , since two scan signals such as SPWM(n) and SCCG(n) are used, the gate terminal of the transistor T13 is connected to the scan signal SPWM(n) and the transistor T14 as shown. ) is connected to the scan signal SCCG(n).

On the other hand, even in the examples of 18a and 18b, by turning off a switch (not shown) inside the amplifier 211 during the data setting section and turning on a switch (not shown) inside the amplifier 211 during the sensing driving section, sensing The fact that the current can flow to the sensing unit 200 only in the driving period is as described above with reference to FIGS. 16A and 16B .

In addition, the remaining contents related to display driving, sensing driving, and prevention of luminance non-uniformity and horizontal crosstalk caused by a sweep load of the sub-pixel circuit 110 can be fully understood through the foregoing in FIGS. 14A to 15C , A duplicate description will be omitted.

Meanwhile, as another embodiment for solving the problems of luminance non-uniformity and horizontal crosstalk described above with reference to FIGS. 15A and 15B , a method of connecting the low voltage (SW_VGL) input of the sweep signal to the X node may be considered.

19A and 19B are diagrams for explaining an embodiment of connecting a low voltage (SW_VGL) input of a sweep signal to an X node.

According to an embodiment of the present disclosure, as shown in FIG. 19A , the low voltage SW_VGL of the sweep signal may be applied to the X node. In this case, the low voltage SW_VGL of the sweep signal may be a global signal equally applied from the power IC to all sub-pixel circuits 110 of the display panel 100 .

Specifically, the X node may be directly connected to the power IC through a wire to which the low voltage SW_VGL of the sweep signal is applied. Accordingly, even if the voltage of the A node is changed by the application of the PWM data voltage, the voltage of the X node may be maintained as the low voltage SW_VGL of the sweep signal without being affected by the coupling through the capacitor C1.

Meanwhile, as shown in FIG. 19A , a sweep signal Sweep(n) for PWM driving may be applied to the source terminal of the second driving transistor. In this case, the sweep signal Sweep(n) may be a voltage signal in the form of linearly increasing from a low voltage to a high voltage as shown in FIG. 19B .

As described above, the PWM circuit controls the on/off operation of the first switching transistor through the on/off operation of the second driving transistor, thereby controlling the time during which the driving current flows through the inorganic light emitting device 120, which is shown in FIG. The same applies to the embodiment of 19a.

Specifically, when the voltage at the source terminal of the second driving transistor increases according to the sweep signal Sweep(n) in a state where the PWM data voltage is set at node A, the voltage difference between the gate terminal and the source terminal of the second driving transistor is will decrease

When the reduced voltage difference between the gate terminal and the source terminal of the second driving transistor reaches the threshold voltage of the second driving transistor, the second driving transistor is turned on and the first switching transistor is turned off.

It can be seen that this PWM driving mechanism is the same as the above-described embodiment (an embodiment in which the sweep signal Sweep(n) is applied to the X node).

According to the embodiment described above, it can be seen that the above-described problems of luminance non-uniformity and horizontal crosstalk caused by the sweep rod can be solved. Also, it can be seen that there is no problem in PWM driving of the display panel 100 even when the sweep signal is applied to the source terminal of the second driving transistor.

20A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to an embodiment of the present disclosure to which the embodiment described with reference to FIGS. 19A and 19B is applied, and FIG. 20B is the sub-pixel circuit 110 of FIG. 20A . It is a timing diagram of various signals for driving the display panel 100 including

The embodiment shown in FIGS. 20A and 20B is similar in configuration and operation principle to the embodiment described with reference to FIGS. 14A and 14B , and thus a redundant description will be omitted and differences will be mainly described.

In the sub-pixel circuit 110 of FIG. 20A , the SW_VGL signal line is directly connected to the X node. Accordingly, unlike the sub-pixel circuit 110 of FIG. 14A , the transistor T1 for applying the SW_VGH signal to the X node during the data setting period is not required.

Referring to FIG. 20A , it can be seen that the transistor does not exist at a position corresponding to the transistor T1 of FIG. 14A . Accordingly, when the reference numbers of the transistors of FIGS. 20A and 14A are compared, it can be seen that the reference numbers for the transistors in the same position are marked so that FIG. 20A precedes FIG. 14A by one.

On the other hand, in the sub-pixel circuit 110 of FIG. 14A , as shown in FIG. 14B , the sweep voltage that linearly decreases from the high voltage SW_VGH of the sweep signal to the low voltage of the sweep signal is applied to the X node in the emission period. is authorized

However, in the sub-pixel circuit 110 of FIG. 20A , as shown in FIG. 20B , the sweep voltage that linearly increases from the low voltage SW_VGL of the sweep signal to the high voltage of the sweep signal is the second driving in the light emission period. It can be seen that the voltage is applied to the source terminal of the transistor T2.

The operation of the PWM circuit 112 according to the sweep signal Sweep(n) in the embodiment of FIG. 20A will be described in detail as an example as follows.

For example, the voltage of +13 [V] (specifically, the PWM data voltage (+14 [V]) + the threshold voltage (-1 [V]) of the second driving transistor T2) is A during the data setting period. In the state set in the node, when a sweep signal (eg, a voltage that increases linearly from +10 [V] to +15 [V]) is applied to the source terminal of the second driving transistor T2, the second driving The voltage difference between the gate terminal and the source terminal of the transistor T2 decreases from +3 [V] to -2 [V].

At this time, when the voltage difference between the gate terminal and the source terminal of the second driving transistor T2, which has decreased from +3 [V], reaches the threshold voltage of the second driving transistor T2 (-1 [V]), the second The driving transistor T2 is turned on, and +14 [V], which is the sweep voltage when the second driving transistor T2 is turned on, is applied to the first switching transistor T9 so that the first switching transistor T9 is turned off. .

It can be seen that the operation mechanism of the PWM circuit 112 of FIG. 20A is the same as the operation mechanism of the PWM circuit 112 described in FIGS. 14A and 14B except that there is a difference only in the shape of the sweep signal and the terminal to which the sweep signal is input. can

The remaining details regarding the configuration and driving of the sub-pixel circuit 110 shown in FIGS. 20A and 20B can be fully understood through the descriptions described above with reference to FIGS. 14A and 14B , and thus a redundant description thereof will be omitted.

21A to 23B illustrate other embodiments of the present disclosure to which the embodiment described with reference to FIGS. 19A and 19B is applied. The embodiments shown in FIGS. 21A to 23B are similar in configuration and operation principle to those described with reference to FIGS. 20A and 20B , and thus a redundant description will be omitted.

21A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to another embodiment of the present disclosure, and FIG. 21B is a timing diagram of various signals for driving the sub-pixel circuit 110 of FIG. 21A am.

The sub-pixel circuit 110 shown in FIG. 21A receives separate control signals (PWM_Sen(n) and CCG_Sen(n) in FIG. 20A) to control on/off of the transistor T12 and the transistor T13. It is different from FIG. 20A only in that the scan signal SP(n) is not used and the rest is the same as the sub-pixel circuit 110 shown in FIG. 20A. The driving timing diagram shown in FIG. 20B is also the same as the driving timing diagram of FIG. 20B except that there are no control signals PWM_Sen(n) and CCG_Sen(n).

21A and 21B , as the low-level scan signal SP(n) is applied during the data setting period, not only the transistors T1, T5, and T6 but also the transistors T12 and T13 are turned on. However, in this case, by turning off a switch (not shown) inside the amplifier 211 , it is possible to prevent current from flowing to the sensing unit 200 . Accordingly, the sensing driving operation is not performed during the data setting period, and only the data setting operation is performed.

Meanwhile, a switch (not shown) inside the amplifier 211 may be turned on during the sensing driving period. Accordingly, in the sensing driving period, the above-described first and second currents flow to the sensing unit 200 , and accordingly, the above-described sensing driving may be performed.

At this time, the second specific voltage is applied to the gate terminal of the second driving transistor T2 during the PWM circuit 112 sensing period (①), and the first specific voltage is applied to the second specific voltage during the constant current source circuit 111 sensing period (②). It is applied to the gate terminal of the first driving transistor T8, and a time for which the second specific voltage is applied and a time for which the first specific voltage is applied do not overlap each other. Accordingly, the sensing driving may be performed without a problem even if the separate control signals PWM_Sen(n) and CCG_Sen(n) are not used.

In addition, the remaining contents related to the display driving and the sensing driving of the sub-pixel circuit 110 can be fully understood through the contents described above with reference to FIGS. 14A and 14B , and the luminance non-uniformity and horizontal crosstalk caused by the sweep load are prevented. Since the contents can be fully understood through the contents described above with reference to FIGS. 19A to 20B , a redundant description will be omitted below.

22A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to another embodiment of the present disclosure, and FIG. 22B is a driving timing diagram of the sub-pixel circuit 110 shown in FIG. 22A.

The sub-pixel circuit 110 illustrated in FIG. 22A is the same as the sub-pixel circuit 110 illustrated in FIG. 20A except that an image data voltage and a specific voltage are applied through one data signal line Vdata. Do. In this case, two scan signals are required as described above in the description of FIGS. 17A and 17B, and the scan signals SPWM(n) and SCCG(n) of FIGS. 22A and 22B represent these two scan signals, there is.

22A and 22B , when the low-level scan signal SPWM(n) is applied to the sub-pixel circuit 110 in the data setting period, the PWM data voltage PWM data is A through the turned-on transistor T1. applied to the node. Also, when the low-level scan signal SCCG(n) is applied to the sub-pixel circuit 110 , the constant current source data voltage CCG data is applied to the node B through the turned-on transistor T6 .

On the other hand, when the low-level scan signal SPWM(n) is applied to the sub-pixel circuit 110 during the sensing period (①) of the PWM circuit 112 during the sensing driving period, the second specific voltage is generated through the turned-on transistor T1. It is input to node A. Also, when the low-level scan signal SCCG(n) is applied to the sub-pixel circuit 110 , the first specific voltage is input to the node B through the turned-on transistor T6 .

Meanwhile, in FIG. 22B , the scan signal is applied in the order of SPWM(n) and SCCG(n) as an example, but the present invention is not limited thereto. Of course, the signal may be applied thereafter.

In addition, the remaining contents related to the display driving and the sensing driving of the sub-pixel circuit 110 can be fully understood through the contents described above with reference to FIGS. 14A and 14B , and the luminance non-uniformity and horizontal crosstalk caused by the sweep load are prevented. Since the contents can be fully understood through the contents described above with reference to FIGS. 19A to 20B , a redundant description will be omitted below.

23A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to another embodiment of the present disclosure, and FIG. 23B is a driving timing diagram of the sub-pixel circuit 110 shown in FIG. 23A.

The sub-pixel circuit 110 shown in FIG. 23A includes an image data voltage (PWM data voltage, constant current source data voltage) and a specific voltage (a second specific voltage, a first specific voltage) through one data signal line Vdata. It is similar to the sub-pixel circuit 110 of FIG. 22A in that it is applied.

Therefore, referring to FIGS. 23A and 23B , using two scan signals (or scan signal lines) such as SPWM(n) and SCCG(n), an image data voltage and a specific voltage are applied in a data setting period and a sensing driving period. It can be seen that each is applied to the sub-pixel circuit 110 .

On the other hand, the sub-pixel circuit 110 shown in FIG. 23A controls the on/off of the transistor T12 and the transistor T13 with separate control signals (PWM_Sen(n) and CCG_Sen(n) in FIG. 22A ). ) is not used and a scan signal is used, which is similar to the embodiment of FIG. 21A .

23A, since two scan signals such as SPWM(n) and SCCG(n) are used, the gate terminal of the transistor T12 is connected to the scan signal SPWM(n) as shown in the figure, and the transistor ( The gate terminal of T13) is connected to the scan signal SCCG(n).

On the other hand, even in the case of the embodiments of FIGS. 23A and 23B, by turning off a switch (not shown) inside the amplifier 211 during the data setting section, and turning on a switch (not shown) inside the amplifier 211 during the sensing driving section, It is as described above with reference to FIGS. 21A and 21B that a current can flow through the sensing unit 200 only in the sensing driving period.

In addition, the remaining contents related to the display driving and the sensing driving of the sub-pixel circuit 110 can be fully understood through the contents described above with reference to FIGS. 14A and 14B , and the luminance non-uniformity and horizontal crosstalk caused by the sweep load are prevented. Since the contents can be fully understood through the contents described above with reference to FIGS. 19A to 20B , a redundant description will be omitted below.

Hereinafter, various embodiments of the present disclosure to which the IR drop external compensation method is applied will be described with reference to FIGS. 24A to 31B .

At this time, in relation to the luminance non-uniformity and horizontal crosstalk problem caused by the sweep load, FIGS. 24A to 27B show that the high voltage SW_VGH of the sweep signal during the data setting period is applied to the X node to which the sweep signal is applied. Examples are shown.

Meanwhile, in FIGS. 28A to 31B , in relation to the luminance non-uniformity and horizontal crosstalk problem caused by the sweep load, the low voltage SW_VGL of the sweep signal is applied to the X node, and the sweep signal is applied to the source terminal of the second driving transistor. Examples to which the applied method is applied are shown.

On the other hand, among the above-mentioned contents, the contents that can be equally applied to the description of FIGS. 24A to 31B , even if there is a minor difference (for example, there is a difference only in reference numbers of transistors, etc.), the redundant description is omitted or, Briefly explain.

24A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to an embodiment of the present disclosure.

24A , the sub-pixel circuit 110 includes a constant current source circuit 111 , a PWM circuit 112 , a first switching transistor T8 , a second switching transistor T9 , a transistor T10 , and a transistor T11 . , including a transistor T12.

The constant current source circuit 111 controls on/off according to the first driving transistor T7, the capacitor C2 connected between the source terminal and the gate terminal of the first driving transistor T7, and the scan signal SP(n). and a transistor T6 for applying the constant current source data voltage applied through the data signal line Vdata_ccg to the gate terminal of the first driving transistor T7 while it is turned on.

The PWM circuit 112 transmits a sweep signal sweeping between two different voltages to the gate terminal of the second driving transistor T3, the source terminal of which is connected to the second driving voltage VDD_PWM, to the gate terminal of the second driving transistor T3. The capacitor C1 for coupling, and the PWM data voltage applied through the data signal line Vdata_pwm while on/off controlled according to the scan signal SP(n) are turned on to the gate terminal of the second driving transistor T3. A transistor T2 for applying is included.

In addition, the PWM circuit 112 includes a reset unit 13 . The reset unit 13 is configured to forcibly turn on the first switching transistor T8 before each light emission period starts. Since the contents of the reset unit 13 are the same as those described above with reference to FIG. 14A , a redundant description will be omitted.

Further, the PWM circuit 112 includes a transistor T1 having a source terminal connected to the SW_VGH signal line, a gate terminal connected to the SP(n) signal line, and a drain terminal connected to the X node. In this case, the source terminal of the transistor T1 may be directly connected to a wiring to which the high voltage SW_VGH of the sweep signal from the power IC is applied.

Accordingly, while the low voltage is applied through the SP(n) signal line and the PWM data voltage is set to the A node, the high voltage SW_VGH of the sweep signal applied through the turned-on transistor T1 is forcibly applied to the X node. In this case, the voltage of the X node may be maintained as the high voltage SW_VGH of the sweep signal regardless of the voltage change of the A node.

Accordingly, as described above, luminance non-uniformity and horizontal crosstalk that may occur due to the sweep rod can be prevented or minimized.

Meanwhile, referring to FIG. 24A , the drain terminal of the second driving transistor T3 is connected to the gate terminal of the first switching transistor T8 through the transistor T4 turned on according to the emission signal Emi_PWM(n). you can see

Accordingly, the PWM circuit 112 controls the on/off operation of the first switching transistor T8 through the operation of the reset unit 13 and the on/off operation of the second driving transistor T3 , so that the light emission period It is possible to control the time during which the driving current flows through the inorganic light emitting device 120 in the inner body.

The second switching transistor T9 has a source terminal connected to a drain terminal of the first switching transistor T8 and a drain terminal connected to an anode terminal of the inorganic light emitting device 120 . The second switching transistor T9 may be turned on/off according to the control signal Emi_PAM(n) to electrically connect/disconnect the first switching transistor T8 and the inorganic light emitting device 120 . The on/off timing of the second switching transistor T9 is related to the implementation of the black gradation.

The transistor T10 is connected between the anode terminal and the cathode terminal of the inorganic light emitting device 120 . The transistor T10 operates in the same manner as the transistor T12 of FIG. 14A , and since it performs the same function, a redundant description thereof will be omitted.

The transistor T12 has a source terminal connected to a drain terminal of the first driving transistor T7 and a drain terminal connected to the sensing unit 200 . The transistor T12 operates in the same manner as the transistor T14 of FIG. 14A , and since it performs the same function, a redundant description thereof will be omitted.

The transistor T11 has a source terminal connected to a drain terminal of the second driving transistor T3 and a drain terminal connected to the sensing unit 200 . The transistor T11 operates in the same manner as the transistor T13 of FIG. 14A , and since it performs the same function, a redundant description thereof will be omitted.

A cathode terminal of the inorganic light emitting device 120 is connected to a ground voltage (VSS) terminal.

Since the unit configuration of the sensing unit 200 is the same as that of the sensing unit 200 of FIG. 14A , a redundant description will be omitted.

24B is a driving timing diagram of the sub-pixel circuit 110 shown in FIG. 24A. Specifically, FIG. 24B shows various control signals, driving voltage signals, and data signals applied to the sub-pixel circuits 110 during one image frame period and blanking period.

Referring to FIG. 24B , the display panel 100 may be driven in the order of display driving and sensing driving.

During the display driving period, control signals SP, SET, Emi_PWM, Emi_PAM, and Sweep are applied to the display panel 100 as shown in FIG. 24B . For example, during the display driving period, the sub-pixel circuits 110 included in the n-th row line of the display panel 100 have control signals SP(n), SET(n), and Emi_PWM as shown in FIG. 24B . (n), Emi_PAM(n), and Sweep(n) may be applied.

The sub-pixel circuits included in each row line of the display panel 100 may be in the order of a data setting period and a plurality of light emission periods. In addition, sub-pixel circuits included in all row lines of the display panel 100 may be driven in the row line order.

Hereinafter, with reference to the control signals SP(n), SET(n), Emi_PWM(n), Emi_PAM(n) and Sweep(n)) related to the n-th row line of FIG. 24B and the circuit of FIG. 24A, A detailed operation of the sub-pixel circuit 110 will be described.

First, in the data setting period, when the low-level scan signal SP(n) is applied to the sub-pixel circuit 110 , the transistor T2 of the PWM circuit 112 and the transistor T6 of the constant current source circuit 111 are comes on

When the transistor T2 is turned on, the PWM data voltage PWM data applied from the second data driver (not shown) is transmitted through the data signal line Vdata_pwm to the gate terminal (hereinafter referred to as the A node) of the second driving transistor T3 . ) is approved.

In this case, the PWM data voltage may be higher than the second driving voltage VDD_PWM. Accordingly, in a state in which the PWM data voltage is set at node A, the second driving transistor T3 maintains an off state.

Meanwhile, when the transistor T6 is turned on, the constant current source data voltage CCG data applied from the first data driver (not shown) passes through the data signal line Vdata_ccg to the gate terminal of the first driving transistor T7 (hereinafter referred to as hereinafter). , referred to as B node).

The sub-pixel circuit 110 of FIG. 24A does not include the driving voltage changing unit 113 unlike the embodiments described above with reference to FIGS. 14A to 23B . Instead, it can be seen that the source terminal of the first driving transistor T7 is directly connected to the first driving voltage VDD_PAM terminal (or line). Accordingly, a voltage corresponding to the difference between the first driving voltage VDD_PAM and the constant current source data voltage is set between the source terminal and the gate terminal of the first driving transistor T7 .

In this case, the constant current source data voltage may be lower than the first driving voltage VDD_PAM. Accordingly, in a state in which the constant current source data voltage is set at node B, the first driving transistor T7 maintains an on state.

Meanwhile, when the first emission period for the n-th row line starts, a low-level emission signal SET(n) is applied to the transistor T5 . Accordingly, the low voltage Vset is charged in the capacitor C3 through the turned-on transistor T5, and the low voltage is applied to the gate terminal (hereinafter, referred to as the C node) of the first switching transistor T8, so that the first The switching transistor T8 is turned on.

Thereafter, during the first emission period, the emission signals Emi(n) and Sweep(n) are applied to the sub-pixel circuit 110 as shown in FIG. 24B .

Specifically, when the low-level emission signal Emi_PAM(n) is applied to the second switching transistor T9, the second switching transistor T9 is turned on.

Accordingly, through the first driving transistor T7 maintaining the on state, the first switching transistor T8 turned on according to the SET(n) signal, and the second switching transistor T9 turned on according to the Emi_PAM(n) signal, A driving current flows through the inorganic light emitting device 120 .

In this case, the magnitude of the driving current is determined by the voltage difference between the source terminal and the gate terminal of the first driving transistor T7 , in particular, the magnitude of the constant current source data voltage set at the gate terminal of the first driving transistor T7 . do.

On the other hand, when the emission signal Sweep(n) (for example, a sweep voltage that decreases linearly as shown in FIG. 24B) is applied to the capacitor C1, the applied sweep voltage is coupled to the A node, Accordingly, the voltage at node A also decreases linearly.

Accordingly, when the difference between the voltage of node A and the second driving voltage VDD_PWM reaches the threshold voltage value of the second driving transistor T3 , the second driving transistor T3 is turned on, and the second driving transistor is turned on. The high level second driving voltage VDD_PWM is applied to the gate terminal of the first switching transistor T8 through T3. (At this time, of course, the transistor T4 is also turned on according to the low-level emission signal Emi_PWM(n).)

Accordingly, the first switching transistor T8 is turned off, the driving current no longer flows to the inorganic light emitting device 120 , and the inorganic light emitting device 120 stops emitting light.

In this case, the time during which the driving current is provided to the inorganic light emitting device 120 is determined by the voltage difference between the source terminal and the gate terminal of the second driving transistor T3 , in particular, at the gate terminal of the second driving transistor T3 . It is determined by the magnitude of the PWM data voltage. (For example, the higher the PWM data voltage, the longer it takes for the difference between the voltage of node A and the second driving voltage VDD_PWM to reach the threshold voltage value of the second driving transistor T3 ).

Meanwhile, the emission signals SET(n), Emi_PWM(n), Emi_PAM(n), and Sweep(n) are equally applied in the second and subsequent emission periods for the n-th row line, respectively. Accordingly, the inorganic light emitting devices 120 of the n-th row line also emit light in the second and subsequent light-emitting sections based on the image data voltage set in the data setting section, respectively.

Meanwhile, according to FIG. 24B , it can be seen that the low-level TEST signal is subsequently applied to the sub-pixel circuit 110 after display driving and sensing driving are completed. Accordingly, as described above, the charge remaining in the inorganic light emitting device 120 can be completely discharged to the ground voltage VSS terminal through the turned-on transistor T10.

In the above, only the operation related to the n-th row line has been described, but the operation for the remaining row lines may also be fully understood through the above description.

Meanwhile, if you look closely at the timing diagram of FIG. 24B , it can be seen that there is a difference between the time when the emission signal Emi_PWM(n) becomes low level and the time when the emission signal Emi_PAM(n) becomes the low level. This is to implement a black gradation as described above with reference to FIG. 14B. In relation to this, there is a difference only in the reference numbers of the transistors, and the above-described contents of FIG. 14B may be applied as they are, and thus additional redundant descriptions will be omitted.

Meanwhile, referring to FIG. 24B , the sensing driving section may include a sensing section (①) of the PWM circuit 112 and a sensing section (②) of the constant current source circuit 111 .

At this time, according to an embodiment of the present disclosure, the sensing driving may be performed within the blanking period 65 as shown in FIG. 24B .

Accordingly, the sensing unit 200 senses a current flowing through the driving transistors T7 and T3 based on a specific voltage applied within the blanking period 65 of one image frame, and outputs sensing data corresponding to the sensed current. can do.

However, according to an embodiment, the sensing driving may be performed during a boot-up period, a power-off period, or a screen-off period of the display apparatus 1000 .

Specifically, during the sensing period (①) of the PWM circuit 112, the second specific voltage applied through the data signal line Vdata_pwm is input to the node A. In addition, in the sensing section (①) of the PWM circuit 112, the transistor T11 is turned on according to the control signal PWM_Sen(n), and a second current flowing through the second driving transistor T3 through the turned-on transistor T11 is It is transmitted to the sensing unit 200 . Accordingly, the sensing unit 200 may output the second sensing data corresponding to the second current to the correction unit 300 .

Meanwhile, during the sensing period (②) of the constant current source circuit 111 , the first specific voltage applied through the data signal line Vdata_ccg is input to the B node. In addition, in the sensing section (②) of the constant current source circuit 111 , the transistor T12 is turned on according to the control signal CCG_Sen(n), and a first current flowing through the first driving transistor T7 through the turned on transistor T12 is transmitted to the sensing unit 200 . Accordingly, the sensing unit 200 may output the first sensing data corresponding to the first current to the correction unit 300 .

The operation of the sensing unit 200 in the first initialization period and the first sensing period of the sensing period (①) of the PWM circuit 112, and the second initialization period and the second sensing of the sensing period (②) of the constant current source circuit 111 Since the detailed operation of the sensing unit 200 in the period is the same as described above with reference to FIG. 14B , a redundant description thereof will be omitted.

The compensator 300 obtains first and second compensation values, respectively, based on the first and second sensing data output from the sensing unit 200, and stores the obtained first and second compensation values in a memory (not shown). ) can be saved or updated. Thereafter, when the display driving is performed, the compensator 300 may respectively correct the constant current source data voltage and the PWM data voltage to be applied to the sub-pixel circuit 110 based on the first and second compensation values.

Meanwhile, the above-described sensing driving may be performed for one row line per one image frame or for a plurality of row lines per one image frame. In this case, the above-described sensing driving may be performed sequentially in the row line order or may proceed in a random order, as described above.

In addition, the above-described sensing driving, as shown, may proceed in the order of the PWM circuit 112 sensing section (①) and the constant current source circuit 111 sensing section (②), but is not limited thereto, and in the embodiment Accordingly, the constant current source circuit 111 sensing section (②) proceeds first, and the PWM circuit 112 sensing section (①) may proceed thereafter.

In addition, in the above description, it is exemplified that the sensing driving is performed after the display is driven, but according to an embodiment, the sensing driving may be performed first and the display driving may be performed thereafter.

Meanwhile, the sub-pixel circuit 110 of FIG. 24A does not separately include the driving voltage changing unit 113 , and the first driving voltage is applied to the source terminal of the first driving transistor T7 in both the data setting period and each light emission period. You can see that (VDD_PAM) is applied.

Accordingly, in the sub-pixel circuit 110 of FIG. 24A , the first driving voltage VDD_PAM applied to the sub-pixel circuits operating in the data setting period is the first driving voltage by the sub-pixel circuits operating in the light-emitting period. (VDD_PAM) is affected by the drop.

As described above, this interferes with setting an accurate constant current source data voltage in the constant current source circuits 111 belonging to the row line operating in the data setting period.

In order to solve the IR drop problem of the first driving voltage VDD_PAM, in the embodiments of FIGS. 24A to 31B , an external compensation method for IR drop (ie, a method for correcting the constant current source data voltage) may be used. there is.

That is, in the embodiment of FIGS. 14A to 23B , by controlling the driving voltage applied to the source terminal of the first driving transistor T9 or T8 through the driving voltage changing unit 113 , the IR of the first driving voltage VDD_PAM is If the drop problem is solved, in the embodiment of FIGS. 23A to 31B , the IR drop problem of the first driving voltage VDD_PAM is corrected by correcting the constant current source data voltage applied to the gate terminal of the first driving transistor T7 or T6. will solve

Specifically, according to an embodiment of the present disclosure, data (or information) regarding IR drop values for each region of the display panel 100 according to the magnitude of the driving current is stored in a storage unit (eg, a memory, etc.) can be

Here, the magnitude of the driving current refers to an average current value provided by the driving voltage providing unit (eg, a power IC) to the display panel 100 to display the image frame on the display panel 100 , and the image represented by the image frame The value may vary depending on

In addition, the driving current and IR drop values for each region may be sensed and calculated in advance in the manufacturing stage of the display apparatus 1000 and stored in a storage unit (not shown). Also, the driving current and IR drop values for each region may be sensed, calculated, and updated in advance before an image is displayed in the use stage of the display apparatus 1000 .

Accordingly, the compensator 300 is a constant current source to be applied to the display panel 100 based on the IR drop values for each region of the display panel 100 corresponding to the amount of driving current required to display the current image frame. data can be corrected.

Accordingly, the data driver (not shown) generates a constant current source data voltage based on the corrected constant current source data and applies it to the display panel 100 , so that the first An IR drop of the driving voltage VDD_PAM may be compensated.

In the above, the IR drop values for each region of the display panel 100 may be IR drop values for each row line of the display panel 100 , but are not limited thereto.

Hereinafter, various embodiments of the present disclosure will be described with reference to FIGS. 25A to 27B . At this time, since the embodiments shown in FIGS. 25A to 27B have similar configurations and operating principles to those described with reference to FIGS. 24A and 24B , overlapping descriptions will be omitted and differences will be mainly described.

25A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to another embodiment of the present disclosure, and FIG. 25B is a driving timing diagram of the sub-pixel circuit 110 illustrated in FIG. 25A .

The sub-pixel circuit 110 shown in FIG. 25A receives separate control signals (PWM_Sen(n) and CCG_Sen(n) in FIG. 24A) to control the on/off of the transistor T11 and the transistor T12. It is different from FIG. 24A only in that the scan signal SP(n) is not used and the rest is the same as the sub-pixel circuit 110 shown in FIG. 24A. The driving timing diagram shown in FIG. 25B is also the same as the driving timing diagram of FIG. 24B except that there are no control signals PWM_Sen(n) and CCG_Sen(n).

25A and 25B , as the low-level scan signal SP(n) is applied during the data setting period, not only the transistors T1, T2, and T6 but also the transistors T11 and T12 are turned on. However, in this case, by turning off a switch (not shown) inside the amplifier 211 , it is possible to prevent current from flowing to the sensing unit 200 . Accordingly, the sensing driving operation is not performed during the data setting period, and only the data setting operation is performed.

Meanwhile, in the sensing driving period, a switch (not shown) inside the above-described amplifier 211 may be turned on. Accordingly, in the sensing driving period, the above-described first and second currents flow to the sensing unit 200 , and accordingly, the above-described sensing driving may be performed.

At this time, the second specific voltage is applied to the gate terminal of the second driving transistor T3 during the PWM circuit 112 sensing section (①), and the first specific voltage is applied to the second specific voltage during the constant current source circuit 111 sensing section (②). It is applied to the gate terminal of the first driving transistor T7, and a time for which the second specific voltage is applied and a time for which the first specific voltage is applied do not overlap each other. Accordingly, it can be seen that the sensing driving operation described with reference to FIGS. 24A and 24B can be performed in the same manner even if the separate control signals PWM_Sen(n) and CCG_Sen(n) are not used.

In addition, the remaining contents related to the display driving of the sub-pixel circuit 110, the sensing driving, and the prevention of luminance non-uniformity and horizontal crosstalk caused by the sweep load can be fully understood through the foregoing in FIGS. 24A and 24B, A duplicate description will be omitted.

26A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to another embodiment of the present disclosure, and FIG. 26B is a driving timing diagram of the sub-pixel circuit 110 shown in FIG. 26A.

The sub-pixel circuit 110 illustrated in FIG. 26A is the same as the sub-pixel circuit 110 illustrated in FIG. 24A except that an image data voltage and a specific voltage are applied through one data signal line Vdata. Do.

In this case, the PWM data voltage and the constant current source data voltage from one data driver are time-divided and applied to the sub-pixel circuit 110 through the data signal line Vdata during the data setting period, and also the data signal during the sensing driving period. Through the line Vdata, the second specific voltage and the first specific voltage are time-divided from the one data driver to be applied to the sub-pixel circuit 110 .

Therefore, the PWM data voltage and the constant current source data voltage applied in time division during the data setting period are respectively applied to the A node and the B node, and the second specific voltage and the first specific voltage applied in time division during the sensing driving period are applied to the A node and the In order to respectively apply to the B node, two scan signals are required, and the scan signal SPWM(n) and the scan signal SCCG(n) in FIGS. 26A and 26B show these two scan signals.

26A and 26B , when the low-level scan signal SPWM(n) is applied to the sub-pixel circuit 110 in the data setting period, the PWM data voltage PWM data is set to A through the turned-on transistor T2. applied to the node. Also, when the low-level scan signal SCCG(n) is applied to the sub-pixel circuit 110 , the constant current source data voltage CCG data is applied to the node B through the turned-on transistor T6 .

On the other hand, when the low-level scan signal SPWM(n) is applied to the sub-pixel circuit 110 during the sensing period (①) of the PWM circuit 112 during the sensing driving period, the second specific voltage is generated through the turned-on transistor T2. It is input to node A. Also, when the low-level scan signal SCCG(n) is applied to the sub-pixel circuit 110 , the first specific voltage is input to the node B through the turned-on transistor T6 .

Meanwhile, in FIG. 26B , the scan signal is applied in the order of SPWM(n) and SCCG(n) as an example, but the present invention is not limited thereto. Of course, the signal may be applied thereafter.

In addition, the remaining contents related to the display driving of the sub-pixel circuit 110, the sensing driving, and the prevention of luminance non-uniformity and horizontal crosstalk caused by the sweep load can be fully understood through the foregoing in FIGS. 24A and 24B, A duplicate description will be omitted.

27A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to another embodiment of the present disclosure, and FIG. 27B is a driving timing diagram of the sub-pixel circuit 110 shown in FIG. 27A.

The sub-pixel circuit 110 illustrated in FIG. 27A includes an image data voltage (PWM data voltage, constant current source data voltage) and a specific voltage (a second specific voltage, a first specific voltage) through one data signal line Vdata. It is similar to the sub-pixel circuit 110 of FIG. 26A in that it is applied.

Therefore, referring to FIGS. 27A and 27B , using two scan signals (or scan signal lines) such as SPWM(n) and SCCG(n), an image data voltage and a specific voltage are applied in a data setting period and a sensing driving period. It can be seen that each is applied to the sub-pixel circuit 110 .

On the other hand, the sub-pixel circuit 110 shown in FIG. 27A controls the on/off of the transistor T11 and the transistor T12 with separate control signals (PWM_Sen(n) and CCG_Sen(n) in FIG. 26A ). ) is not used and a scan signal is used, which is similar to the embodiment of FIG. 25A .

In the embodiment of FIG. 27A , since two scan signals such as SPWM(n) and SCCG(n) are used, the gate terminal of the transistor T11 is connected to the scan signal SPWM(n) line as shown, and the transistor ( The gate terminal of T12) is connected to the scan signal SCCG(n) line.

On the other hand, even in the case of the embodiments 27a and 27b, by turning off a switch (not shown) inside the amplifier 211 during the data setting section and turning on a switch (not shown) inside the amplifier 211 during the sensing driving section, sensing It is as described above with reference to FIGS. 25A and 25B that a current can flow through the sensing unit 200 only in the driving period.

In addition, the remaining contents related to the display driving of the sub-pixel circuit 110, the sensing driving, and the prevention of luminance non-uniformity and horizontal crosstalk caused by the sweep load can be fully understood through the foregoing in FIGS. 24A and 24B, A duplicate description will be omitted.

Hereinafter, embodiments in which the low voltage SW_VGL of the sweep signal is applied to the X node and the sweep signal is applied to the source terminal of the second driving transistor will be described with reference to FIGS. 28A to 31B .

28A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to an embodiment of the present disclosure, and FIG. 28B is a driving timing diagram of the sub-pixel circuit 110 shown in FIG. 28A.

The embodiment shown in FIGS. 28A and 28B is similar in configuration and operation principle to the embodiment described with reference to FIGS. 24A and 24B , and thus redundant description will be omitted and differences will be mainly described.

In the sub-pixel circuit 110 of FIG. 28A , the SW_VGL signal line is directly connected to the X node. Accordingly, unlike the sub-pixel circuit 110 of FIG. 24A , the transistor T1 for applying the SW_VGH signal to the X node during the data setting period is not required.

Referring to FIG. 28A , it can be seen that the transistor does not exist at a position corresponding to the transistor T1 of FIG. 24A . Accordingly, when the reference numbers of the transistors of FIGS. 28A and 24A are compared, it can be seen that the reference numbers for the transistors in the same position are indicated such that FIG. 28A precedes FIG. 24A by one.

On the other hand, in the sub-pixel circuit 110 of FIG. 24A , as shown in FIG. 24B , the sweep voltage that linearly decreases from the high voltage SW_VGH of the sweep signal to the low voltage of the sweep signal is applied to the X node in the emission period. is authorized

However, in the sub-pixel circuit 110 of FIG. 28A , as shown in FIG. 28B , the sweep voltage that linearly increases from the low voltage SW_VGL of the sweep signal to the high voltage of the sweep signal is the second driving period in the emission period. It can be seen that the voltage is applied to the source terminal of the transistor T2.

The operation of the PWM circuit 112 according to the sweep signal Sweep(n) in the embodiment of FIG. 28A will be described in detail as an example.

For example, the voltage of +13 [V] (specifically, the PWM data voltage (+14 [V]) + the threshold voltage (-1 [V]) of the second driving transistor T2) is A during the data setting period. In the state set in the node, when a sweep signal (eg, a voltage that increases linearly from +10 [V] to +15 [V]) is applied to the source terminal of the second driving transistor T2, the second driving The voltage difference between the gate terminal and the source terminal of the transistor T2 decreases from +3 [V] to -2 [V].

At this time, when the voltage difference between the gate terminal and the source terminal of the second driving transistor T2, which has decreased from +3 [V], reaches the threshold voltage of the second driving transistor T2 (-1 [V]), the second The driving transistor T2 is turned on, and +14 [V], which is the sweep voltage when the second driving transistor T2 is turned on, is applied to the first switching transistor T7 so that the first transistor T7 is turned off.

It can be seen that the operation mechanism of the PWM circuit 112 of FIG. 28A is the same as the operation mechanism of the PWM circuit 112 described with reference to FIGS. 24A and 24B except that there is a difference only in the shape of the sweep signal and the terminal to which the sweep signal is input. can

The remaining contents regarding the configuration and driving of the sub-pixel circuit 110 shown in FIGS. 28A and 28B can be fully understood through the illustrated contents and the contents described above with reference to FIGS. 24A and 24B , and thus a redundant description thereof will be omitted.

29A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to another embodiment of the present disclosure, and FIG. 29B is a timing diagram of various signals for driving the sub-pixel circuit 110 of FIG. 29A am.

The sub-pixel circuit 110 shown in FIG. 29A receives separate control signals (PWM_Sen(n) and CCG_Sen(n) in FIG. 28A) to control on/off of the transistor T10 and the transistor T11. It is different from FIG. 28A only in that the scan signal SP(n) is not used and the rest is the same as the sub-pixel circuit 110 shown in FIG. 28A. The driving timing diagram shown in FIG. 29B is also the same as the driving timing diagram of FIG. 28B except that there are no control signals PWM_Sen(n) and CCG_Sen(n).

29A and 29B , as the low-level scan signal SP(n) is applied during the data setting period, not only the transistors T1 and T5 but also the transistors T10 and T11 are turned on. However, in this case, by turning off a switch (not shown) inside the amplifier 211 , it is possible to prevent current from flowing to the sensing unit 200 . Accordingly, the sensing driving operation is not performed during the data setting period, and only the data setting operation is performed.

Meanwhile, a switch (not shown) inside the amplifier 211 may be turned on during the sensing driving period. Accordingly, in the sensing driving period, the above-described first and second currents flow to the sensing unit 200 , and accordingly, the above-described sensing driving may be performed.

At this time, the second specific voltage is applied to the gate terminal of the second driving transistor T2 during the PWM circuit 112 sensing period (①), and the first specific voltage is applied to the second specific voltage during the constant current source circuit 111 sensing period (②). It is applied to the gate terminal of the first driving transistor T6, and a time for which the second specific voltage is applied and a time for which the first specific voltage is applied do not overlap each other. Accordingly, the sensing driving may be performed without a problem even if the separate control signals PWM_Sen(n) and CCG_Sen(n) are not used.

The remaining contents related to the configuration and driving of the sub-pixel circuit 110 shown in FIGS. 29A and 29B can be fully understood through the illustrated contents and the above-described contents, and thus a redundant description thereof will be omitted.

30A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to another embodiment of the present disclosure, and FIG. 30B is a driving timing diagram of the sub-pixel circuit 110 shown in FIG. 30A.

The sub-pixel circuit 110 shown in FIG. 30A is the same as the sub-pixel circuit 110 shown in FIG. 28A except that an image data voltage and a specific voltage are applied through one data signal line Vdata. Do. In this case, two scan signals are required as described above, and the scan signal SPWM(n) and the scan signal SCCG(n) in FIGS. 30A and 30B indicate these two scan signals.

30A and 30B , when the low-level scan signal SPWM(n) is applied to the sub-pixel circuit 110 in the data setting period, the PWM data voltage PWM data is A through the turned-on transistor T1. applied to the node. Also, when the low-level scan signal SCCG(n) is applied to the sub-pixel circuit 110 , the constant current source data voltage CCG data is applied to the node B through the turned-on transistor T5 .

On the other hand, when the low-level scan signal SPWM(n) is applied to the sub-pixel circuit 110 during the sensing period (①) of the PWM circuit 112 during the sensing driving period, the second specific voltage is generated through the turned-on transistor T1. It is input to node A. Also, when the low-level scan signal SCCG(n) is applied to the sub-pixel circuit 110 , the first specific voltage is input to the node B through the turned-on transistor T5 .

Meanwhile, in FIG. 30B , the scan signal is applied in the order of SPWM(n) and SCCG(n) as an example, but the present invention is not limited thereto. Of course, the signal may be applied thereafter.

The remaining contents related to the configuration and driving of the sub-pixel circuit 110 shown in FIGS. 30A and 30B can be fully understood through the illustrated contents and the above-described contents, and thus a redundant description thereof will be omitted.

31A is a detailed circuit diagram of the sub-pixel circuit 110 and the sensing unit 200 according to another embodiment of the present disclosure, and FIG. 31B is a driving timing diagram of the sub-pixel circuit 110 illustrated in FIG. 31A .

The sub-pixel circuit 110 shown in FIG. 31A includes an image data voltage (PWM data voltage, constant current source data voltage) and a specific voltage (a second specific voltage, a first specific voltage) through one data signal line Vdata. It is similar to the sub-pixel circuit 110 of FIG. 30A in that it is applied.

Therefore, referring to FIGS. 31A and 31B , using two scan signals (or scan signal lines) such as SPWM(n) and SCCG(n), an image data voltage and a specific voltage are applied in a data setting period and a sensing driving period. It can be seen that each is applied to the sub-pixel circuit 110 .

On the other hand, the sub-pixel circuit 110 shown in FIG. 31A controls the on/off of the transistor T10 and the transistor T11 with separate control signals (PWM_Sen(n) and CCG_Sen(n) in FIG. 30A ). ) is not used and a scan signal is used, which is similar to the embodiment of FIG. 29A .

31A, since two scan signals such as SPWM(n) and SCCG(n) are used, the gate terminal of the transistor T10 is connected to the scan signal SPWM(n) as shown, and the transistor ( The gate terminal of T11) is connected to the scan signal SCCG(n).

On the other hand, even in the case of the embodiment of FIGS. 31A and 31B, by turning off a switch (not shown) inside the amplifier 211 in the data setting section, and turning on a switch (not shown) inside the amplifier 211 in the sensing driving section, As described above, the current may flow to the sensing unit 200 only in the sensing driving period.

In addition, since the remaining contents related to the configuration and driving of the sub-pixel circuit 110 shown in FIGS. 30A and 30B can be fully understood through the illustrated contents and the above-described contents, a redundant description thereof will be omitted.

As described above, the embodiments to which the IR drop internal compensation method is applied simply compensate for the IR drop of the driving voltage during the operation of the sub-pixel circuit, and the embodiments to which the IR drop external compensation method is applied are relatively small. The number of transistors is used, and each has an advantage in that accurate IR drop compensation is possible.

In addition, in the above embodiments in which the PWM data voltage and the constant current source data voltage are respectively applied through separate wirings such as Vdata_pwm and Vdata_ccg, two types of data drivers are used to provide the constant current source data voltage and the PWM data voltage. Therefore, there is relatively no risk of overheating of the data driver. In addition, the configuration can be relatively simple in that the scan signal SP(n) can be provided using one type of scan driver. However, since two types of data drivers are used, the cost is relatively increased, and the design of the display panel may be relatively complicated in that two types of data signal lines are required.

Meanwhile, as described above, in the embodiments in which the PWM data voltage and the constant current source data voltage are respectively applied through one wiring such as Vdata, the cost is relatively reduced because one type of data driver is used, and one type of data signal line In that (Vdata) is sufficient, the design can be relatively simple.

However, since a relatively high PWM data voltage and a relatively low constant current source data voltage are alternately applied to the display panel 100 through one type of data driver, there is a risk of heat generation in the data driver, and the scan signal SPWM(n) The configuration may be relatively complicated in that two types of scan drivers are required to provide the scan signal SCCG(n).

32A is a cross-sectional view of the display panel 100 according to an embodiment of the present disclosure. In FIG. 32A , only one pixel included in the display panel 100 is illustrated for convenience of explanation.

Referring to FIG. 32A , the display panel 100 may include a glass substrate 80 , a TFT layer 70 , and inorganic light emitting devices R, G, and B 120 - 1 , 120 - 2 , and 120 - 3 . In this case, the aforementioned sub-pixel circuit 110 may be implemented as a TFT (Thin Film Transistor), and may be included in the TFT layer 70 on the glass substrate 80 .

Each of the inorganic light emitting devices R, G, and B 120-1, 120-2, and 120-3 is mounted on the TFT layer 70 so as to be electrically connected to the corresponding sub-pixel circuit 110 to form the aforementioned sub-pixels. configurable.

Although not shown in the drawings, the TFT layer 70 includes a sub-pixel circuit 110 for providing driving current to the inorganic light emitting devices 120-1, 120-2, and 120-3. 120-2 and 120-3), and each of the inorganic light emitting devices 120-1, 120-2, and 120-3 is on the TFT layer 70 so as to be electrically connected to the corresponding sub-pixel circuit 110, respectively. It may be mounted or disposed.

Meanwhile, in FIG. 32A , the inorganic light emitting devices R, G, and B 120-1, 120-2, and 120-3 are flip-chip type micro LEDs as an example. However, the present invention is not limited thereto, and the inorganic light emitting devices R, G, and B (120-1, 120-2, 120-3) may be a horizontal type or a vertical type micro LED according to an embodiment. may be

32B is a cross-sectional view of the display panel 100 according to another embodiment of the present disclosure.

Referring to FIG. 32B , the display panel 100 includes a TFT layer 70 formed on one surface of the glass substrate 80 and inorganic light emitting devices R, G, B (120-1, 120-) mounted on the TFT layer 70. 2, 120-3), the driving unit 500, the sensing unit 200, and the sub-pixel circuit 110 formed in the TFT layer 70 and the driving unit and/or the sensing unit 500, 200 are electrically connected It may include a connection wire 90 for

As described above, according to an embodiment of the present disclosure, at least some of the various drivers or circuits of the driving unit 500 are implemented in a separate chip form and disposed on the rear surface of the glass substrate 80 , and the connection wiring ( 90 may be connected to the sub-pixel circuits 110 formed in the TFT layer 70 . In addition, according to an embodiment of the present disclosure, the sensing unit 200 is also disposed on the rear surface of the glass substrate 80 , and includes sub-pixel circuits 110 and may be connected.

In this regard, referring to FIG. 32B , the sub-pixel circuits 110 included in the TFT layer 70 are a TFT panel (hereinafter, the TFT layer 70 and the glass substrate 80 are collectively referred to as a TFT panel). It can be seen that the driving unit 500 and/or the sensing unit 200 are electrically connected through the connecting wiring 90 formed on the edge (or side) of the . In this case, the connection line 90 may include at least a portion of the aforementioned scan line SCL, data line DL, and sensing line SSL.

In this way, the connection wiring 90 is formed in the edge region of the display panel 100 to connect the sub-pixel circuits 110 included in the TFT layer 70 and the driver 500 and/or the sensing unit 200 . The reason for this is that when a hole passing through the glass substrate 80 is formed to connect the sub-pixel circuits 110 and the driver 500 and/or the sensing unit 200, the TFT panels 70 and 80 This is because problems such as cracks in the glass substrate 80 may occur due to a temperature difference between the manufacturing process of ) and the process of filling the hole with a conductive material.

Meanwhile, as described above, according to another embodiment of the present disclosure, at least some of the various drivers and circuits of the driving unit 500 may include sub-pixel circuits formed in the TFT layer in the display panel 100 together with the TFT layer. may be formed and connected to sub-pixel circuits. Figure 32c shows such an embodiment.

32C is a plan view of the TFT layer 70 according to an embodiment of the present disclosure. Referring to FIG. 32C , the TFT layer 70 has a region occupied by one pixel 10 (in this region, sub-pixel circuits 110 corresponding to each of the R, G, and B sub-pixels included in the pixel 10) exists.), it can be seen that the remaining regions 11 exist.

As such, since the remaining regions 11 are present in the TFT layer 70 , some of the various drivers or circuits of the above-described driver 500 may be formed in the remaining regions 11 .

32C shows an example in which the aforementioned gate drivers are implemented in the remaining region 11 of the TFT layer 70 . As described above, the structure in which the gate driver is formed in the TFT layer 70 may be referred to as a GIP (Gate In Panel) structure, but the name is not limited thereto.

Meanwhile, FIG. 32C is only an example, and a circuit that may be included in the remaining region 11 of the TFT layer 70 is not limited to the gate driver. According to an embodiment, in the TFT layer 70 , a DeMUX circuit for selecting the R, G, and B sub-pixels, respectively, and an Electro Static Discharge (ESD) protection circuit for protecting the sub-pixel circuit 110 from static electricity , a sweep voltage providing circuit, etc. may be further included.

In the above, the case where the substrate on which the TFT layer 70 is formed is the glass substrate 80 has been exemplified, but the embodiment is not limited thereto. For example, the TFT layer 70 may be formed on a synthetic resin substrate. In this case, the sub-pixel circuits 100 of the TFT layer 70 and the driver 500 and/or the sensing unit 200 may be connected through a hole passing through the synthetic resin substrate.

Meanwhile, an example in which the sub-pixel circuit 110 is implemented in the TFT layer 70 has been described above. However, the embodiment is not limited thereto. That is, according to another embodiment of the present disclosure, when the sub-pixel circuit 110 is implemented, the TFT layer 70 is not used, and a sub-pixel or pixel-by-pixel pixel circuit chip is implemented in the form of a microchip. , it is also possible to mount it on a substrate. In this case, the position where the sub-pixel chip is mounted may be, for example, around the corresponding inorganic light emitting device 120 , but is not limited thereto.

In addition, in the various embodiments of the present disclosure described above, the TFT constituting the TFT layer (or TFT panel) is not limited to a specific structure or type, that is, the TFT cited in various examples of the present disclosure, LTPS (Low Temperature Poly Silicon) TFT, oxide TFT, silicon (poly silicon or a-silicon) TFT, organic TFT, graphene TFT, etc. can also be implemented, and P type (or N-type) MOSFET in Si wafer CMOS process You can just create and apply it.

According to various embodiments of the present disclosure as described above, it is possible to prevent the wavelength of the light emitted by the inorganic light emitting device from being changed according to the gray level. In addition, it is possible to easily compensate for unevenness that may appear in an image due to a difference in threshold voltage and mobility between driving transistors. In addition, color correction is facilitated. In addition, even when a large-area display panel is configured by combining module-type display panels or a single large-sized display panel is configured, it is possible to more easily compensate for spots and color correction. In addition, power consumption when driving the display panel can be reduced. In addition, it is possible to compensate for the influence of a drop of the driving voltage that is different for each position of the display panel on the data voltage setting process. In addition, it is possible to design a more optimized driving circuit, and it is possible to stably and efficiently drive the inorganic light emitting device. In addition, it is possible to improve the luminance non-uniformity and horizontal crosstalk problems caused by the sweep rod.

The above description is merely illustrative of the technical spirit of the present disclosure, and various modifications and variations will be possible without departing from the essential characteristics of the present disclosure by those of ordinary skill in the art to which the present disclosure pertains. In addition, the embodiments according to the present disclosure are for explanation rather than limiting the technical spirit of the present disclosure, and the scope of the technical spirit of the present disclosure is not limited by these embodiments. Accordingly, the protection scope of the present disclosure should be construed by the following claims, and all technical ideas within the scope equivalent thereto should be construed as being included in the scope of the present disclosure.

1000: display device 500: driving unit
100: display panel 110: sub-pixel circuit
120: inorganic light emitting element 111: constant current source circuit
112: PWM circuit

Claims (18)

In the display device,
a display panel comprising: a display panel including a pixel array in which pixels composed of a plurality of inorganic light emitting devices are disposed on a plurality of row lines, and a sub-pixel circuit provided for each of the plurality of inorganic light emitting devices and providing a driving current to the inorganic light emitting device; and
During the data setting period for each row line, an image data voltage is set in the sub-pixel circuits of the display panel in the row line order, and during the light emission period for each row line, a sweep signal that sweeps from the first voltage to the second voltage and the set a driving unit configured to drive the sub-pixel circuits such that the driving current is sequentially provided to the inorganic light emitting devices of the pixel array based on the image data voltage;
The sub-pixel circuit comprises:
a capacitor having one end to which the sweep signal is applied; and
A first driving transistor connected to the other end of the capacitor, receiving the sweep signal through the capacitor in the light emitting period, and controlling a time during which the driving current is provided to the inorganic light emitting device based on the sweep signal including;
The driving unit,
In the data setting period, the display device applies the first voltage to one end of the capacitor separately from the sweep signal. The method of claim 1,
The driving unit,
a sweep driver circuit provided for each row line and configured to apply the sweep signal to one end of the capacitor; and
and a power IC for providing the first voltage applied separately from the sweep signal to the display panel. 3. The method of claim 2,
The image data voltage is
including a constant current source data voltage and a pulse width modulation (PWM) data voltage,
The sub-pixel circuit comprises:
a constant current source circuit including a second driving transistor and providing a driving current having a magnitude based on the constant current source data voltage to the inorganic light emitting device; and
and a PWM circuit including the first driving transistor and controlling a time period during which the driving current is provided to the inorganic light emitting device based on the PWM data voltage. 4. The method of claim 3,
The constant current source circuit is
In the data setting period, a third voltage based on the constant current source data voltage and a threshold voltage of the second driving transistor is set at the gate terminal of the second driving transistor;
The PWM circuit is
In the data setting period, while the first voltage is applied to one end of the capacitor, a fourth voltage based on the PWM data voltage and a threshold voltage of the first driving transistor is set to the gate terminal of the first driving transistor display device. 5. The method of claim 4,
The constant current source circuit is
In the light emitting period, a driving current having a magnitude based on the third voltage is provided to the inorganic light emitting device,
The PWM circuit is
In the light emission period, the display device controls a time period during which the driving current is provided to the inorganic light emitting device based on a voltage of the gate terminal of the first driving transistor that is changed from the fourth voltage according to the sweep signal. The method of claim 1,
The sub-pixel circuits are
Each row line is driven in the order of the data setting section and the plurality of light emitting sections,
The driving unit,
In each of the plurality of light emitting sections, the display device drives the sub-pixel circuits of the row line so that a driving current corresponding to the set image data voltage is provided to the inorganic light emitting devices of the row line. 4. The method of claim 3,
Sensing the current flowing through the first driving transistor and the second driving transistor included in the sub-pixel circuit based on a specific voltage applied to the sub-pixel circuit, respectively, and outputting sensed data corresponding to the sensed current sensing unit; and
and a correction unit correcting the constant current source data voltage and the PWM data voltage applied to the sub-pixel circuit based on the sensed data. 8. The method of claim 7,
The driving unit,
In the data setting period, the image data voltage is set in the row line order of the sub-pixel circuits based on a first driving voltage, and in the light emission period, the driving is performed based on a second driving voltage and the first driving voltage A display device for driving the sub-pixel circuits such that a current is provided to the inorganic light emitting devices of the pixel array in a row-line order. 8. The method of claim 7,
a storage unit for storing data for compensating for a drop in driving voltage for each position of the display panel according to the driving current;
The correction unit,
The display device corrects the constant current source data voltage and the PWM data voltage applied to the sub-pixel circuit based on the sensed data and the stored data. In the display device,
a display panel comprising: a display panel including a pixel array in which pixels composed of a plurality of inorganic light emitting devices are disposed on a plurality of row lines, and a sub-pixel circuit provided for each of the plurality of inorganic light emitting devices and providing a driving current to the inorganic light emitting device; and
During the data setting period, image data voltages are set in the order of the row lines in the sub-pixel circuits of the display panel, and during the light emitting period, the sweep signal sweeps from the first voltage to the second voltage and based on the set image data voltage. a driving unit configured to drive the sub-pixel circuits such that the driving current is provided to the inorganic light emitting devices of the pixel array in a row-line order;
The sub-pixel circuit comprises:
capacitor; and
a first driving transistor connected to one end of the capacitor and configured to control a time for which the driving current is provided to the inorganic light emitting device based on the sweep signal applied to the light emitting section;
The driving unit,
A display device configured to apply the first voltage to the other terminal of the capacitor separately from the sweep signal. 11. The method of claim 10,
The driving unit,
a sweep driver circuit provided for each row line and configured to apply the sweep signal to the first driving transistor; and
and a power IC for providing the first voltage applied separately from the sweep signal to the display panel. 12. The method of claim 11,
The image data voltage is
including a constant current source data voltage and a pulse width modulation (PWM) data voltage,
The sub-pixel circuit comprises:
a constant current source circuit including a second driving transistor and providing a driving current having a magnitude based on the constant current source data voltage to the inorganic light emitting device; and
and a PWM circuit including the first driving transistor and controlling a time period during which the driving current is provided to the inorganic light emitting device based on the PWM data voltage. 13. The method of claim 12,
The constant current source circuit is
In the data setting period, a third voltage based on the constant current source data voltage and a threshold voltage of the second driving transistor is set at the gate terminal of the second driving transistor;
The PWM circuit is
In the data setting period, while the first voltage is applied to one end of the capacitor, a fourth voltage based on the PWM data voltage and a threshold voltage of the first driving transistor is set to the gate terminal of the first driving transistor display device. 14. The method of claim 13,
The constant current source circuit is
In the light emitting period, a driving current having a magnitude based on the third voltage is provided to the inorganic light emitting device,
The PWM circuit is
In the light emitting period, the display device controls a time during which the driving current is provided to the inorganic light emitting device based on a voltage difference between a source terminal and a gate terminal of the first driving transistor that is changed according to the sweep signal. 11. The method of claim 10,
The sub-pixel circuits are
Each row line is driven in the order of the data setting section and the plurality of light emitting sections,
The driving unit,
In each of the plurality of light emitting sections, the display device drives the sub-pixel circuits of the row line so that a driving current corresponding to the set image data voltage is provided to the inorganic light emitting devices of the row line. 13. The method of claim 12,
Sensing the current flowing through the first driving transistor and the second driving transistor included in the sub-pixel circuit based on a specific voltage applied to the sub-pixel circuit, respectively, and outputting sensed data corresponding to the sensed current sensing unit; and
and a correction unit correcting the constant current source data voltage and the PWM data voltage applied to the sub-pixel circuit based on the sensed data. 17. The method of claim 16,
The driving unit,
In the data setting period, the image data voltage is set in the row line order of the sub-pixel circuits based on a first driving voltage, and in the light emission period, the driving is performed based on a second driving voltage and the first driving voltage A display device for driving the sub-pixel circuits such that a current is provided to the inorganic light emitting devices of the pixel array in a row-line order. 11. The method of claim 10,
a storage unit for storing data for compensating for a drop in driving voltage for each position of the display panel according to the driving current;
The correction unit,
The display device corrects the constant current source data voltage and the PWM data voltage applied to the sub-pixel circuit based on the sensed data and the stored data.

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