KR101968615B1 - Apparatus and method for useing near field communication and wireless power transmission - Google Patents

Abstract

A method and apparatus for short range wireless communication and wireless power transmission are provided. When the resonance frequency for short range wireless communication and the resonance frequency for wireless power transmission are the same, the short range wireless communication receiver and the wireless power transmission receiver use the same resonator. Depending on the mode of operation of the device, the resonator is coupled to one of a near field wireless communication receiver and a wireless power transmission receiver. The operating mode of the device is determined by the magnitude of the input power reaching the resonator. When the resonance frequency for short-range wireless communication and the resonance frequency for wireless power transmission are different from each other, two resonators are used for short-range wireless communication and wireless power transmission, respectively.

Description

[0001] APPARATUS AND METHOD FOR USING NEAR FIELD COMMUNICATION AND WIRELESS POWER TRANSMISSION [0002]

The following embodiments are directed to methods and apparatus for using short range wireless communication and wireless power transmission.

A method and apparatus for providing short-range wireless communication and wireless power transmission are disclosed.

Wireless power refers to the energy delivered from a wireless power transmission device to a wireless power reception device through magnetic coupling. The wireless power receiving apparatus can charge the battery using the received energy. Accordingly, Wireless Power Transmission (WPT) and charging systems include a source device that wirelessly transmits power and a target device that wirelessly receives power. At this time, the source device may be referred to as a wireless power transmission device. The target device may also be referred to as a wireless power receiving device.

In particular, the resonant-mode wireless power transmission can provide a high degree of freedom in the position of the source device and the target device.

The source device has a source resonator, and the target device has a target resonator. A magnetic coupling or a resonant coupling may be formed between the source resonator and the target resonator. The source device and the target device may communicate to transmit and receive control and status information.

With the spread of smart phones and the like, new functions can be added to mobile devices to provide a variety of new services.

Near Field Communication (NFC) is an ultra short range wireless communication technology. By using NFC, devices within approximately 10cm can communicate with each other.

The NFC can provide a service, for example, an electronic approval system, in cooperation with an application of a smart phone. Therefore, especially high-end smart phones need to be equipped with NFC functions.

A structure of a mobile device having an NFC and a wireless power transmission function needs to be proposed.

One embodiment can provide an apparatus and method in which an NFC receiver and a WPT receiver use one resonator exclusively.

One embodiment may provide an apparatus and method for coupling a resonator to one of an NFC receiver and a WPT receiver depending on the magnitude of the input power.

One embodiment may provide an apparatus and method using an NFC resonator and a WPT resonator using resonant frequencies that are different from each other.

According to one aspect of the present invention, there is provided a power receiving apparatus comprising: a resonator for receiving power; a short range wireless communication receiver for performing wireless communication using the received power; And a mode selection unit for connecting the resonator with one of the short-range wireless communication receiver and the wireless power transmission receiver.

The device may be a mobile wireless communication terminal.

The resonator may have a resonant frequency of 13.56 Mhz, and the Q of the resonator may be greater than 100.

The power receiving apparatus may further include a loss matching circuit for providing a loss matching to the local wireless receiver in a low Q state.

The short-range wireless communication receiver may be connected to the resonator through the Ross matching circuit.

The mode selector may determine the operation mode of the apparatus and connect the resonator to one of the short-range wireless communication receiver and the wireless power transmission receiver.

Wherein the mode selector is capable of coupling the resonator to the short range wireless communication receiver when the input power is less than the maximum output power of the short range wireless communication and when the input is greater than the maximum output power, Lt; / RTI >

The apparatus may further include a first switch for connecting or disconnecting the resonator and the short-range wireless communication receiver, and a second switch for connecting or disconnecting the resonator and the wireless power transmission receiver.

The mode selector may connect the resonator to one of the short-range wireless communication receiver and the wireless power transmission receiver by controlling the first switch and the second switch.

The first switch may be a PMOS switch.

The second switch may be an NMOS switch.

The mode selector may control the first switch and the second switch by outputting a switch control signal to the first switch and the second switch.

According to the switch control signal, one of the first switch and the second switch may be turned ON and the other may be turned OFF.

The resonator may output the received power as input power of the mode selection unit.

Wherein the mode selection unit is capable of outputting a switch control signal for turning on the first switch and turning off the second switch when the input power is smaller than the maximum output power of the short range wireless communication, The first switch is turned off and the second switch is turned on to output a switch control signal.

The mode selection unit comprises: receiving an input power to the low drop for supplying the rectifier and the capacitor, V _ref for supplying V _pin - the via the output terminal if compared to the out and V _pin and V _ref and V _pin is greater than V _ref And a comparator that outputs a signal that _{couples a} short range wireless communication receiver with the resonator and outputs a signal that _couples the wireless power transmission receiver to the resonator through the output terminal when V _pin is less than V _ref .

The mode selection unit, the low drop-the first voltage divider and the converting the V _dd which is output from the out to the maximum output power criteria in terms of voltage, V _ref of the short-range wireless communication-out and of the comparator - connecting the terminals and a low drop And a second voltage divider that connects the capacitor and the + terminal of the comparator and converts the magnitude of the input power to a V _pin value.

The mode selection unit may further include a resistor connected to the output terminal of the comparator and the ground.

According to another aspect, there is provided a method comprising: receiving a resonator input power; coupling the resonator to one of a near field wireless communication receiver and a wireless power transmission receiver based on the magnitude of the input power; Operating in a short-range wireless communication mode when connected to the wireless power transmission receiver, and operating in a wireless power transmission reception mode when the resonator is connected to the wireless power transmission receiver.

&Quot; connecting the resonator to one of a near field wireless communication receiver and a wireless power transmission receiver based on the magnitude of the input power " comprises the steps of: comparing the magnitude of the input power and a predefined magnitude; Turning on the first switch and turning off the second switch when the input power is smaller than the predefined size, and turning on the first switch when the magnitude of the input power is larger than the predefined size, And turning off the power supply.

The first switch may connect the resonator and the short-range wireless communication receiver.

The second switch may couple the resonator and the wireless power transmission receiver.

According to another aspect of the present invention, there is provided a power receiving apparatus comprising: a short range wireless communication resonator for receiving a first power; a short range wireless communication receiver for performing wireless communication using the received first power; And a wireless power transmission receiver that uses a power transmission resonator and the received second power to supply a voltage for operation of the power reception device, wherein the resonant frequency of the short range wireless communication resonator and the resonant frequency of the wireless power transmission resonator Are different from each other.

The short-range wireless communication resonator may be disposed inside the wireless power transmission resonator.

According to another aspect, there is provided a method of wireless communication in which a short range wireless communication resonator receives a first power, a short range wireless communication receiver performs wireless communication using the received first power, And receiving a second power from the wireless power transmission receiver and supplying a voltage for operation of the power receiving device using the received second power, wherein the resonant frequency of the short- A method of operating a power receiving apparatus is provided, wherein the resonant frequencies are different from each other.

An apparatus and method are provided in which an NFC receiver and a WPT receiver exclusively use one resonator.

An apparatus and method are provided for coupling a resonator to one of an NFC receiver and a WPT receiver depending on the magnitude of the input power.

An apparatus and a method using an NFC resonator and a WPT resonator using different resonance frequencies are provided.

1 illustrates a wireless power transmission and charging system in accordance with one embodiment.
Figures 2-8 illustrate embodiments of resonators.
9 shows an equivalent circuit of the resonator shown in Fig.
10 is a block diagram of an NFC receiver (transceiver) according to one embodiment.
FIG. 11 shows a terminal having an NFC function according to an example.
12 is a block diagram of a WPT receiver 1200 having an inband communication function according to an example.
13 is a structural diagram of an apparatus having an NFC and a WPT according to an embodiment.
FIG. 14 illustrates a detailed configuration of a mode selection unit according to an example.
FIG. 15 shows the operation of the NFC mode according to an example.
16 shows the operation of the WPT mode according to an example.
17 is a flowchart of an operation method of an apparatus having an NFC and a WPT according to an embodiment.
18 is a structural view of an apparatus having an NFC and a WPT according to an embodiment.
19 is a structural diagram of an apparatus having an NFC and a WPT according to an embodiment.
20 is a graph showing resonance characteristics of an NFC resonator and a WPT resonator using different resonance frequencies according to an example.
21 is a flowchart of a method of operating a power receiving apparatus according to an embodiment.

Hereinafter, an embodiment of the present invention will be described in detail with reference to the accompanying drawings. However, the present invention is not limited to or limited by the embodiments. Like reference symbols in the drawings denote like elements.

1 illustrates a wireless power transmission and charging system in accordance with one embodiment.

Referring to FIG. 1, a wireless power transmission and charging system according to one embodiment includes a source device 110 and a target device 120.

The source device 110 includes an AC / DC converter 111, a resonance frequency generator 112, a modulator 113, a power converter 114, a control and communication unit 115 and a source resonator 116 .

The target device 120 includes a target resonator 121, a rectification section 122, a DC / DC converter 123, a switch section 124, a charging section 125 and a control and communication section 126.

The AC / DC converter 111 rectifies the AC voltage in the frequency band of several tens Hz to generate the DC voltage. The AC / DC converter 111 can output a DC voltage of a certain level or adjust the output level of the DC voltage according to the control of the control and communication unit 115. [

The resonance frequency generating unit 112 generates a switching pulse signal of several MHz to several tens MHz. At this time, the resonance frequency is the same as the frequency of the switching pulse signal. The switching pulse signal output from the resonance frequency generating unit 112 can be turned on / off via the modulating unit 113.

The modulation unit 113 generates a modulation signal under the control of the control and communication unit 115. [ The modulation unit 113 can generate a modulated signal for performing in-band communication through various methods. The modulation section 113 can generate a modulation signal by turning on / off the output signal of the resonance frequency generation section 112. [ Also, the modulator 113 can perform delta-sigma modulation to generate a modulated signal. The modulator 113 can generate a pulse width modulated signal having a constant envelope.

The power conversion section 114 can generate power by converting a DC voltage of a certain level into an AC voltage by a switching pulse signal of several MHz to several tens MHz. That is, the power conversion section 114 can generate "communication power" or "charging power" used in the target device by converting the DC voltage into the AC voltage using the resonance frequency. A detailed description of the " power for communication " and " power for charging " will be described later in the description of FIG.

The control and communication unit 115 can control the frequency of the switching pulse signal. The frequency of the switching pulse signal can be determined by the control and communication unit 115. The control and communication unit 115 can generate a modulation signal for transmission to the target device 120 by controlling the modulation unit 113. [ That is, the control and communication unit 115 can transmit various messages to the target device through in-band communication. Further, the control and communication unit 115 can detect the reflected wave and demodulate the signal received from the target device through the envelope of the reflected wave.

The source resonator 116 transfers the electromagnetic energy to the target resonator 121. That is, the source resonator 116 transfers the "communication power" or "charging power" to the target device 120 through the magnetic coupling with the target resonator 121.

The target resonator 121 receives electromagnetic energy from the source resonator 116. That is, the target resonator 121 receives " communication power " or " charging power " from the source device 110 through magnetic coupling with the source resonator 116. In addition, the target resonator 121 may receive various messages from the source device via in-band communication.

The rectifying unit 122 rectifies the AC voltage to generate a DC voltage. That is, the rectifying section 122 rectifies the received AC voltage to the target resonator 121.

The DC / DC converter 123 adjusts the level of the DC voltage output from the rectifying unit 122 to match the capacity of the charger 125. For example, the DC / DC converter 123 can adjust the level of the DC voltage output from the rectifying unit 122 to 3 to 10 Volts.

The switch unit 124 is turned on / off under the control of the control and communication unit 126. When the switch unit 124 is turned off, the control and communication unit 115 of the source device 110 detects the reflected wave. That is, when the switch portion 124 is turned off, the magnetic coupling between the source resonator 116 and the target resonator 121 can be removed.

The charging unit 125 may include a battery. The charging unit 125 can charge the battery using the DC voltage output from the DC / DC converter 123. [

The control and communication unit 126 may perform in-band communication for transmitting and receiving data using a resonant frequency. The control and communication unit 126 may detect a signal between the target resonator 121 and the rectifying unit 122 and demodulate the received signal or detect the output signal of the rectifying unit 122 to demodulate the received signal. That is, the control and communication unit 126 can demodulate the received message through the in-band communication. Further, the control and communication section can modulate the signal to be transmitted to the source device 110 by adjusting the impedance of the target resonator 121. [ The control and communication unit may also modulate a signal to be transmitted to the source device 110 through on / off of the switch unit 124. [ In a simple example, the control and communication unit 126 may increase the impedance of the target resonator 121 so that the reflected wave is detected in the control and communication unit 115 of the source device 110. Depending on whether or not the reflected wave is generated, the control and communication unit 115 of the source device 110 can detect the binary number " 0 " or " 1 ".

The control and communication unit 126 may transmit a response message to a message received from the source device to the source device using a short packet obtained by converting a byte-scale general type packet into a bit scale.

Figures 2-8 illustrate embodiments of resonators.

2 is a view illustrating a two-dimensional structure resonator according to one embodiment.

2, a two-dimensional resonator according to an embodiment of the present invention includes a transmission line including a first signal conductor portion 211, a second signal conductor portion 212, and a ground conductor portion 213, A capacitor 220, a matching unit 230, and conductors 241 and 242.

2, the capacitor 220 is inserted in series between the first signal conductor portion 211 and the second signal conductor portion 212 in the transmission line, so that the electric field is And is trapped in the capacitor 220. Generally, the transmission line includes at least one conductor at the top and at least one conductor at the bottom, where current flows through the conductor at the top and the conductor at the bottom is electrically grounded. In this specification, the conductor on the upper part of the transmission line is referred to as a first signal conductor part 211 and the second signal conductor part 212, and the conductor below the transmission line is referred to as a ground conductor part 213 .

As shown in FIG. 2, the resonator 200 according to an embodiment of the present invention has a two-dimensional structure. The transmission line includes a first signal conductor portion 211 and a second signal conductor portion 212 at the top and a ground conductor portion 213 at the bottom. The first signal conductor portion 211 and the second signal conductor portion 212 and the ground conductor portion 213 are disposed facing each other. The current flows through the first signal conductor portion 211 and the second signal conductor portion 212.

Also, as shown in FIG. 2, one end of the first signal conductor portion 211 is shorted to the conductor 242, and the other end is connected to the capacitor 220. One end of the second signal conductor portion 212 is grounded to the conductor 241 and the other end is connected to the capacitor 220. As a result, the first signal conductor portion 211, the second signal conductor portion 212 and the ground conductor portion 213, and the conductors 241 and 242 are connected to each other so that the resonator 200 has an electrically closed loop structure . Here, the 'loop structure' includes a circular structure, a polygonal structure such as a quadrangle, and the like, and having a loop structure means that it is electrically closed.

The capacitor 220 is inserted into the intermediate portion of the transmission line. More specifically, a capacitor 220 is inserted between the first signal conductor portion 211 and the second signal conductor portion 212. At this time, the capacitor 220 may have the form of a lumped element and a distributed element. In particular, a dispersed capacitor in the form of a dispersive element can comprise zigzag shaped conductor lines and a dielectric with a high dielectric constant existing between the conductor lines.

As the capacitor 220 is inserted into the transmission line, the resonator 200 may have a characteristic of metamaterial. Here, a metamaterial is a material having a special electrical property that can not be found in nature, and has an artificially designed structure. The electromagnetic properties of all materials present in nature have inherent permittivity or permeability, and most materials have a positive permittivity and a positive permeability. In most materials, the right-hand rule applies to electric fields, magnetic fields and pointing vectors, so these materials are called RHM (Right Handed Material). However, the meta-material is a material having a permittivity or permeability that does not exist in the natural world, and may be an epsilon negative material, an MNG (mu negative material), a DNG (double negative) material, index material, left-handed material, and the like.

At this time, when the capacitance of the capacitor 220 inserted as a lumped element is appropriately determined, the resonator 200 can have a metamaterial characteristic. In particular, by appropriately adjusting the capacitance of the capacitor 220, the resonator 200 can have a negative magnetic permeability, so that the resonator 200 according to an embodiment of the present invention can be referred to as an MNG resonator. As will be described below, the criterion for determining the capacitance of the capacitor 220 may vary. A criterion allowing the resonator 200 to have a characteristic of a metamaterial, a premise that the resonator 200 has a negative permeability at a target frequency, There may be a premise to have a resonant (Zeroth-Order Resonance) characteristic, and the capacitance of the capacitor 220 may be determined under the premise of at least one of the above-mentioned premises.

The MNG resonator 200 may have a zeroth-order resonance characteristic having a frequency when the propagation constant is 0 as a resonant frequency. Since the MNG resonator 200 may have a zero-th resonance characteristic, the resonance frequency may be independent of the physical size of the MNG resonator 200. In other words, as will be described below, it is sufficient to properly design the capacitor 220 in order to change the resonance frequency in the MNG resonator 200, so that the physical size of the MNG resonator 200 can be changed.

Also, since the electric field in the near field is concentrated in the capacitor 220 inserted in the transmission line, the magnetic field is dominant in the near field due to the capacitor 220. Since the MNG resonator 200 can have a high Q-factor by using the capacitor 220 of the lumped element, the efficiency of power transmission can be improved. For reference, the queue-factor represents the ratio of the reactance to the degree of resistance or ohmic loss in the wireless power transmission, the larger the queue-factor, the greater the efficiency of the wireless power transmission .

In addition, the MNG resonator 200 may include a matching unit 230 for impedance matching. At this time, the matching unit 230 appropriately tunes the intensity of the magnetic field of the MNG resonator 200, and the impedance of the MNG resonator 200 is determined by the matching unit 230. The current may flow into the MNG resonator 200 through the connector 240 or out of the MNG resonator 200. Here, the connector 240 may be connected to the ground conductor portion 213 or the matching unit 230. A physical connection may be formed between the connector 240 and the ground conductor 213 or the matching unit 230 and a physical connection between the connector 240 and the ground conductor 213 or the matching unit 230. [ Power may be delivered through the coupling without any connection.

More specifically, as shown in FIG. 2, the matching unit 230 may be located inside a loop formed by the loop structure of the resonator 200. The matching unit 230 can adjust the impedance of the resonator 200 by changing the physical shape. In particular, the matching device 230 may include a conductor 231 for impedance matching at a distance h from the ground conductor portion 213, and the impedance of the resonator 200 may be changed by adjusting the distance h have.

Although not shown in FIG. 2, if there is a controller capable of controlling the matching unit 230, the matching unit 230 may change the physical form of the matching unit 230 according to a control signal generated by the controller have. The distance h between the conductor 231 and the ground conductor portion 213 of the matching device 230 may be increased or decreased depending on the control signal so that the physical form of the matching device 230 is changed The impedance of the resonator 200 can be adjusted.

Matcher 230 may be implemented as a passive element, such as conductor portion 231, as shown in FIG. 2, and may be implemented as an active element, such as a diode, transistor, or the like, depending on the embodiment. When the active element is included in the matching unit 230, the active element can be driven according to a control signal generated by the controller, and the impedance of the resonator 200 can be adjusted according to the control signal. For example, the matching unit 230 may include a diode, which is a type of active element, and the impedance of the resonator 200 may be adjusted depending on whether the diode is in the 'on' state or the 'off' state .

Although not shown in FIG. 2, a magnetic core passing through the MNG resonator 200 may be further included. Such a magnetic core can perform a function of increasing a power transmission distance.

FIG. 3 is a view showing a three-dimensional structure resonator according to one embodiment.

3, a three-dimensional resonator 300 according to an embodiment of the present invention includes a first signal conductor portion 311, a second signal conductor portion 312, and a ground conductor portion 313 And a transmission line and a capacitor 320. Where the capacitor 320 is inserted in series between the first signal conductor portion 311 and the second signal conductor portion 312 in the transmission line and the electric field is confined in the capacitor 320.

Further, as shown in FIG. 9, the resonator 300 has a three-dimensional structure. The transmission line includes a first signal conductor portion 311 and a second signal conductor portion 312 at the top and a ground conductor portion 313 at the bottom. The first signal conductor portion 311 and the second signal conductor portion 312 and the ground conductor portion 313 are disposed facing each other. The current flows in the x direction through the first signal conductor portion 311 and the second signal conductor portion 312 and the magnetic field H (w) is generated in the -y direction due to this current. Of course, a magnetic field H (w) may occur in the + y direction, unlike that shown in FIG.

Also, as shown in FIG. 3, one end of the first signal conductor portion 311 is shorted to the conductor 342, and the other end is connected to the capacitor 320. One end of the second signal conductor portion 312 is grounded to the conductor 341 and the other end is connected to the capacitor 320. As a result, the first signal conductor portion 311, the second signal conductor portion 312 and the ground conductor portion 313, and the conductors 341 and 342 are connected to each other so that the resonator 300 has an electrically closed loop structure . Here, the 'loop structure' includes a circular structure, a polygonal structure such as a quadrangle, and the like, and having a loop structure means that it is electrically closed.

Also, as shown in FIG. 3, a capacitor 320 is inserted between the first signal conductor portion 311 and the second signal conductor portion 312. At this time, the capacitor 320 may have the form of a lumped element and a distributed element. In particular, a dispersed capacitor in the form of a dispersive element can comprise zigzag shaped conductor lines and a dielectric with a high dielectric constant existing between the conductor lines.

As shown in FIG. 3, as the capacitor 320 is inserted into the transmission line, the resonator 300 may have a metamaterial characteristic. When the capacitance of the capacitor 320 inserted as a lumped element is appropriately determined, the resonator 300 may have a metamaterial characteristic. In particular, by appropriately adjusting the capacitance of the capacitor 320, the resonator 300 can have a negative magnetic permeability in a specific frequency band, so that the resonator 300 according to an embodiment of the present invention can be referred to as an MNG resonator. As will be described below, the criterion for determining the capacitance of the capacitor 320 may vary. A criterion that allows the resonator 300 to have a characteristic of a metamaterial; a premise that the resonator 300 has a negative permeability at a target frequency; There may be a premise to have a resonance (Zeroth-Order Resonance) characteristic, and the capacitance of the capacitor 320 can be determined under the premise of at least one of the above-mentioned premises.

The MNG resonator 300 shown in FIG. 9 may have a zeroth-order resonance characteristic having a resonance frequency at a frequency when the propagation constant is zero. Since the MNG resonator 300 may have a zero resonance characteristic, the resonance frequency may be independent of the physical size of the MNG resonator 300. [ In order to change the resonance frequency in the MNG resonator 300, it is sufficient to appropriately design the capacitor 320, so that the physical size of the MNG resonator 300 may not be changed.

Referring to the MNG resonator 300 as shown in FIG. 9, since the electric field in the near field is concentrated on the capacitor 320 inserted in the transmission line 910, the capacitor 320 causes the near field The magnetic field becomes dominant. In particular, since the MNG resonator 300 having the zeroth-order resonance characteristic has properties similar to those of the magnetic dipole, the magnetic field is dominant in the near field, and is generated due to the insertion of the capacitor 320 Is also concentrated in the capacitor 320, the magnetic field becomes more dominant in the near field. The MNG resonator 300 can have a high Q-factor by using the capacitor 320 of the lumped element, thereby improving the efficiency of power transmission.

In addition, the MNG resonator 300 shown in FIG. 3 may include a matching unit 330 for impedance matching. At this time, the matching unit 330 appropriately tunes the intensity of the magnetic field of the MNG resonator 300, and the impedance of the MNG resonator 300 is determined by the matching unit 330. Then, the current flows into the MNG resonator 300 through the connector 340 or flows out of the MNG resonator 300. Here, the connector 340 may be connected to the ground conductor portion 313 or the matching unit 330.

9, the matching unit 330 may be located inside the loop formed by the loop structure of the resonator 300. In this case, The matching unit 330 can adjust the impedance of the resonator 300 by changing the physical shape. In particular, the matching device 330 may include a conductor portion 331 for impedance matching at a distance h from the ground conductor portion 313, and the impedance of the resonator 300 may be changed by adjusting the distance h .

9, if there is a controller capable of controlling the matching machine 330, the matching machine 330 can change the physical form of the matching machine 330 according to the control signal generated by the controller have. For example, depending on the control signal, the distance h between the conductor 331 and the ground conductor portion 330 of the matching device 330 may be increased or decreased such that the physical form of the matching device 330 changes The impedance of the resonator 300 can be adjusted. The distance h between the conductor 331 of the matching device 330 and the ground conductor portion 330 can be adjusted in various manners. That is, first, the matching unit 330 may include various conductors, and the distance h may be adjusted by adaptively activating any one of the conductors. Second, by adjusting the physical position of the conductor 331 up and down, the distance h can be adjusted. This distance h can be controlled according to the control signal of the controller, and the controller can generate the control signal considering various factors. The generation of the control signal by the controller will be described below.

Matcher 330 may be implemented as a passive element, such as conductor portion 331, as shown in FIG. 3, and may be implemented as an active element, such as a diode, transistor, or the like, depending on the embodiment. When the active element is included in the matching unit 330, the active element can be driven according to a control signal generated by the controller, and the impedance of the resonator 300 can be adjusted according to the control signal. For example, the matching unit 330 may include a diode that is a type of active device, and the impedance of the resonator 300 may be adjusted depending on whether the diode is in the 'on' state or the 'off' state .

Further, although not explicitly shown in FIG. 9, a magnetic core passing through the MNG resonator 300 may further be included. Such a magnetic core can perform a function of increasing a power transmission distance.

4 is a diagram illustrating an example of a resonator for a wireless power transmission designed in a bulky type.

Referring to FIG. 4, the first signal conductor portion 411 and the conductor 442 may be fabricated individually and then integrally formed instead of being connected to each other. Likewise, the second signal conductor portion 412 and the conductor 441 may also be fabricated as a single unit.

If the second signal conductor portion 412 and the conductor 441 are individually fabricated and then connected to each other, there may be a conductor loss due to the seam 450. In this case, according to the embodiment of the present invention, the second signal conductor portion 412 and the conductor 441 are connected to each other seamlessly, and the conductor 441 and the ground conductor portion 413 are also separated from each other Can be connected to each other seamlessly, and the conductor loss due to the joint can be reduced. As a result, the second signal conductor portion 412 and the ground conductor portion 413 can be fabricated as one integral piece without separate seams. Likewise, the first signal conductor portion 411 and the ground conductor portion 413 can be fabricated as a single unit without separate seams.

As shown in FIG. 4, the type that connects two or more partitions together as one integral type without separate seam is called a 'bulky type'.

5 is a view illustrating an example of a resonator for wireless power transmission designed as a hollow type.

5, the first signal conductor portion 511, the second signal conductor portion 512, the ground conductor portion 513, and the conductors 541 and 542 of the resonator for wireless power transmission designed as a hollow type Includes an empty space inside.

At a given resonant frequency, the effective current flows through all portions of each of the first signal conductor portion 511, the second signal conductor portion 512, the ground conductor portion 513, and the conductors 541 and 542 But can be modeled as flowing through only a portion of the portion. That is, at a given resonance frequency, the thickness of the first signal conductor portion 511, the second signal conductor portion 512, the ground conductor portion 513, and the conductors 541 and 542 is greater than the respective skin depth Thick ones can be inefficient. That is, it may cause the weight of the resonator 500 or the manufacturing cost of the resonator 500 to increase.

Therefore, according to the embodiment of the present invention, the skin depth of each of the first signal conductor portion 511, the second signal conductor portion 512, the ground conductor portion 513, and the conductors 541 and 542 at a given resonance frequency The thicknesses of the first signal conductor portion 511, the second signal conductor portion 512, the ground conductor portion 513, and the conductors 541 and 542 can be appropriately determined based on the thickness of the first signal conductor portion 511, the second signal conductor portion 512, If each of the first signal conductor portion 511, the second signal conductor portion 512, the ground conductor portion 513 and the conductors 541 and 542 has a thickness greater than the corresponding skin depth but has an appropriate thickness, And the fabrication cost of the resonator 500 can also be reduced.

를 통해서 결정될 수 있다. 여기서, f는 주파수,

는 투자율,

는 도체 상수를 나타낸다. 특히, 제1 신호 도체 부분(511), 제2 신호 도체 부분(512), 그라운드 도체 부분(513), 도체들(541, 542) 이 구리(copper)로서 5.8x10^7의 도전율(conductivity)을 갖는 경우에, 공진 주파수가 10kHz에 대해서는 skin depth가 약 0.6mm일 수 있으며, 공진 주파수가 100MHz에 대해서는 skin depth는 0.006mm일 수 있다.
For example, as shown in FIG. 5, the thickness of the second signal conductor portion 512 may be defined as dm,

Lt; / RTI > Where f is the frequency,

Is the investment rate,

Represents a conductor constant. Particularly, the first signal conductor portion 511, the second signal conductor portion 512, the ground conductor portion 513, and the conductors 541 and 542 have a conductivity of 5.8 x 10 ^ 7 as copper , The skin depth may be about 0.6 mm for the resonance frequency of 10 kHz and the skin depth may be 0.006 mm for the resonance frequency of 100 MHz.

6 is a view illustrating an example of a resonator for wireless power transmission to which a parallel-sheet is applied.

Referring to FIG. 6, a parallel-sheet may be applied to the surfaces of the first signal conductor portion 611 and the second signal conductor portion 612 included in the resonator for wireless power transmission to which the parallel-sheet is applied.

Since the first signal conductor portion 611 and the second signal conductor portion 612 are not perfect conductors, they may have resistance components, and ohmic losses may occur due to their resistance components . This resistance loss can reduce the Q factor and reduce the coupling efficiency.

According to an embodiment of the present invention, applying a parallel-sheet to the surface of each of the first signal conductor portion 611 and the second signal conductor portion 612 reduces resistance loss and increases the Q factor and coupling efficiency . Referring to portion 670 of FIG. 6, when a parallel-sheet is applied, each of the first signal conductor portion 611 and the second signal conductor portion 612 includes a plurality of conductor lines. These conductor lines are arranged in parallel and shorted at the ends of the first signal conductor portion 611 and the second signal conductor portion 612, respectively.

When parallel-sheet is applied to the surfaces of the first signal conductor portion 611 and the second signal conductor portion 612, the sum of the resistance components of the conductor lines is reduced since the conductor lines are arranged in parallel. Thus, the resistance loss can be reduced, and the Q factor and coupling efficiency can be increased.

7 is a diagram illustrating an example of a resonator for a wireless power transmission including a distributed capacitor.

Referring to FIG. 7, the capacitor 720 included in the resonator for the wireless power transmission may be a distributed capacitor. The capacitor as a lumped element may have a relatively high Equivalent Series Resistance (ESR). Although there are various proposals for reducing the ESR of the capacitor as the concentration device, the embodiment of the present invention can reduce the ESR by using the capacitor 720 as the dispersion element. For reference, loss due to ESR can reduce Q factor and coupling efficiency.

The capacitor 720 as a dispersion element may have a jig jig structure, as shown in Fig. That is, the capacitor 720 as a dispersion element can be realized by a conductor line and a dielectric of a zigzag structure.

In addition, as shown in FIG. 7, the embodiment of the present invention uses the capacitor 720 as the dispersing element, so that it is possible to reduce the loss due to the ESR, and to use the capacitors as a plurality of lumped elements in parallel The loss due to the ESR can be reduced. Because the resistance components of each of the capacitors as the lumped element are reduced through the parallel connection, the effective resistance of the capacitors as the lumped elements connected in parallel can also be reduced, and thus the loss due to the ESR can be reduced. For example, replacing the use of one 10 pF capacitor with the use of ten 1 pF capacitors can reduce losses due to ESR.

8 is a diagram showing examples of matching units used in a two-dimensional resonator and a three-dimensional resonator.

Fig. 8A shows a part of the two-dimensional resonator shown in Fig. 2 including the matching unit, and Fig. 8B shows a part of the three-dimensional resonator shown in Fig. 9 including the matching unit.

8A, the matching unit includes a conductor 231, a conductor 232 and a conductor 233, and the conductor 232 and the conductor 233 are electrically connected to the ground conductor portion 213 and the conductor 231). The impedance of the two-dimensional resonator is determined by the distance h between the conductor 231 and the ground conductor portion 213 and the distance h between the conductor 231 and the ground conductor portion 213 is controlled by the controller. The distance h between the conductor 231 and the ground conductor portion 213 can be adjusted in a variety of ways and can be adjusted by adjusting the distance h by adaptively activating any of the various conductors that may be the conductor 231 A method of adjusting the distance h by adjusting the physical position of the conductor 231 up and down, and the like.

8B, the matching unit includes a conductor 331, a conductor 332 and a conductor 333, and the conductor 332 and the conductor 333 are connected to the ground conductor portion 313 of the transmission line and the conductor 333, 331). The impedance of the three-dimensional resonator is determined according to the distance h between the conductor 331 and the ground conductor portion 313 and the distance h between the conductor 331 and the ground conductor portion 313 is controlled by the controller. The distance h between the conductor 331 and the ground conductor portion 313 can be adjusted in various ways in the matching device included in the three-dimensional resonator as well as the matching device included in the two-dimensional resonator. For example, the distance h may be adjusted by adaptively activating any of the conductors that may be the conductor 331, and the distance h may be adjusted by vertically adjusting the physical position of the conductor 331 Method, and the like.

Although not shown in FIG. 8, the matching unit may include an active element, and the method of adjusting the impedance of the resonator using the active element is similar to that described above. That is, by changing the path of the current flowing through the matching device using the active element, the impedance of the resonator can be adjusted.

9 is a diagram showing an equivalent circuit of the resonator for wireless power transmission shown in FIG.

The resonator for the wireless power transmission shown in Fig. 2 can be modeled as the equivalent circuit shown in Fig. In the equivalent circuit of Fig. 9, C _L represents a capacitor inserted in the form of a lumped element in the middle of the transmission line of Fig.

를 공진 주파수로 갖는다고 가정한다. 이 때, 공진 주파수

는 하기 수학식 1과 같이 표현될 수 있다. 여기서, MZR은 Mu Zero Resonator를 의미한다.At this time, the resonator for the radio power transmission shown in Fig. 2 has the zero-th resonance characteristic. That is, when the propagation constant is zero, the resonator for wireless power transmission

Is assumed to have a resonant frequency. At this time,

Can be expressed by the following equation (1). Here, MZR means Mu Zero Resonator.

는

에 의해 결정될 수 있고, 공진 주파수

와 공진기의 물리적인 사이즈는 서로 독립적일 수 있음을 알 수 있다. 따라서, 공진 주파수

와 공진기의 물리적인 사이즈가 서로 독립적이므로, 공진기의 물리적인 사이즈는 충분히 작아질 수 있다.
Referring to Equation 1, the resonance frequency of the resonator

The

And the resonance frequency < RTI ID = 0.0 >

And the physical size of the resonator can be independent of each other. Therefore,

And the physical size of the resonator are independent of each other, the physical size of the resonator can be sufficiently small.

10 is a block diagram of an NFC receiver (transceiver) according to an example.

Table 1 below shows an example of commercialized NFC standards.

18092 (NFC) Passive Active frequency
(Frequency) 13.56 MHz Modulation from R to T
(R to T Modulation) 100%, 8 ~ 30% Amplitude Shift Keying (ASK) modulation Coding from R to T
(R to T Coding) Modified Miller Data rate from T to R
(T to R Data Rate) 106 kbps, 212 kbps, 424 kbps Sub-carrier
(Sub-carrier) 847kHz Modulation from T to R
(T to R Modulation) OOK 100%, 8 ~ 30% ASK C coding from T to R
(T to R Coding) Manchester coding Deformed mirror

The NFC may have a reader (R) and a tag (T) system at the same time. The NFC can use a carrier frequency of 13.56 MHz.

Hereinafter, reader (R) mode operation and tag (T) mode operation will be described.

10, a first NFC receiver 1000 and a second NFC receiver 1090 are shown.

The first NFC receiver 1000 may be coupled to a first antenna and matching circuit (antenna & matching circuits) 1080.

The first NFC receiver 1000 may transmit the TX to the first antenna and the matching circuit 1080. The first NFC receiver 1000 may receive the RX from the first antenna and the matching circuit 1080.

The second NFC receiver 1090 may be coupled to a second antenna and matching circuit 1990.

And the second NFC receiver 1090 can transmit the TX to the second antenna and matching circuit 1095. [ The second NFC receiver 1090 may receive the RX from the second antenna and the matching circuit 1095.

Hereinafter, a case where the first NFC receiver 1090 operates in the reader mode will be described.

(I.e., the second NFC receiver 1090 or the second antenna and the matching circuit 1095) from the reader (i.e., the first NFC receiver 1000 or the first antenna and the matching circuit 1080) Power and TX data (data) can be transmitted simultaneously.

The reader can transmit power and TX data using an ASK modulator.

Then, the counterpart tag can recognize the reader by receiving power and TX data.

The other tag recognizing the reader can transmit the tag data to the reader by reflecting power using load modulation with a sub-carrier.

The reader can receive the signal carrying the tag data (i.e., the reflected power) and obtain the data of the tag by demodulating the received signal.

Hereinafter, a case where the first NFC receiver 1090 operates in the tag mode will be described.

In the tag mode, the counterpart reader (i.e., the second NFC receiver 1090 or the second antenna and matching circuit 1095) may transmit signals carrying power and TX data.

The tag (i.e., the first NFC receiver 1000 or the first antenna and matching circuit 1080) can receive signals carrying power and TX data, and by rectifying the received signals at a rectifier, a microcontroller unit (MCU) and a comparator can generate power to be used.

Also, the tag can recover the TX data of the other party's reader through an envelope detector, and can transmit the restored TX data to the MCU.

After recognizing the other party's reader, the MCU can transmit the tag data to the other party's leader by performing a load modulation by transmitting a signal containing the tag data for converting the load.

FIG. 11 shows a terminal having an NFC function according to an example.

NFC can use the frequency of 13.56MHz.

The NFC antenna 1120 may be embedded in the back case 1110 of the terminal 1100 and may cover the back surface of the terminal 1100. [

Therefore, in the case of a general mobile device, the space for additionally inserting the WPT resonator for WPT may be insufficient.

When a WPT resonator, for example, operating at 13.56 MHz, is inserted into the terminal 1100, the characteristics of each of the NFC antenna 1120 and the WPT resonator change due to strong coupling occurring between the NFC antenna 1120 and the WPT resonator . Therefore, a sufficient distance should be secured between the NFC antenna 1120 and the WPT resonator, and the NFC antenna 1120 and the WPT resonator should be arranged with a sufficient distance. However, in general, there is not enough room in the rear case 1110 of the terminal 1100 to place the NFC antenna 1120 and the WPT resonator at a sufficient distance.

12 is a block diagram of a WPT receiver having an inband communication function according to an example.

The WPT receiver 1200 is coupled to a high Q resonator and matching circuit 1290.

The WPT receiver 1200 may receive power (i.e., TX power) bearing TX data via a high Q resonator (i.e., a high Q resonator and matching circuit 1290).

The WPT receiver 1200 may rectify the received power through a rectifier. A power regulator (or a DC / DC converter) may receive the rectified power and supply the power required for operation of the WPT receiver 1200 (e.g., the voltage at which the MCU and comparator, etc. may operate). Most of the power can be used to charge the battery.

Some of the received TX power can be demodulated through the envelope detector and delivered to the MCU. The signal carrying the tag data can be sent via load modulation.

As described above with reference to Figs. 10 and 12, the structure of the tag operation mode of the NFC and the operation of the WPT that performs in-band communication are almost similar. The difference between the two is that the battery is only charged and the amount of power received. Therefore, NFC and WPT have a similar modulation / demodulation structure, so that a collision may occur between them and may not be used at the same time.

11, the WPT may also use a resonator (e.g., a high Q resonator and matching circuit 1290) embedded in the back case 1110 of the terminal 1100. [

The WPT resonator needs to use the space of the back case 1110 of the terminal 1100 as widely as possible in order to maintain high efficiency (i.e., high Q). The WPT resonator and the NFC antenna 1120 need to be disposed together with a sufficient distance therebetween so that coupling with the NFC antenna 1120 using the same resonance frequency does not occur. There may be insufficient space for the NFC antenna 1120 and the WPT resonator to be disposed together.

A WPT system having a resonance frequency of 13.56 MHz with the same resonance frequency as NFC can be used due to the problem of the inserting space of the resonator, in order for a device such as a mobile device to simultaneously have NFC function and WPT function.

Hereinafter, the terms " resonant frequency " and " operating frequency " may be used interchangeably and may be interchanged with each other.

&Quot; NFC " and " WPT system for in-band communication " use communication broadcasting using similar load modulation. Thus, if "NFC" and "WPT system with in-band communication" use a similar operating frequency (ie, carrier frequency), then "NFC" and "WPT system with in-band communication" can not be used simultaneously. &Quot; NFC " and " WPT system with in-band communication " can be selectively used by using the mode selection system and switches described below.

That is, when the resonance frequency of the WPT resonator and the resonance frequency of the NFC resonator are equal to each other, a high Q resonator for WPT can be commonly used as the NFC antenna 1120.

An apparatus and method for selectively using " NFC " and " WPT system for in-band communication " by using a mode selection system and switches will be described in detail below with reference to FIG. 13 to FIG.

On the other hand, in a device such as a mobile device, the resonance frequency of the WPT and the resonance frequency of the NFC may be different from each other. For example, the resonant frequency of the WPT may be 6.78 MHz. In this case, the device may have an independent WPT resonator, other than the NFC antenna 1120, for WPT. The independent resonator for the WPT may be a high Q WPT resonator. In the device, the WPT resonator may be preferentially disposed, and the NFC antenna 1120 may be disposed in the remaining space in the device after the WPT resonator is preferentially disposed. The space in which the NFC antenna 1120 is disposed may be internal or external to the WPT resonator.

An apparatus and method using an independent WPT resonator other than the NFC antenna 1120 will be described in detail below with reference to FIGS. 18 to 21. FIG.

13 is a structural diagram of an apparatus having an NFC and a WPT according to an embodiment.

Apparatus 1300 may be a device to which the WPT function using the same resonance frequency as the NFC resonance frequency is added to the NFC apparatus.

The apparatus 1300 includes a resonator 1310, a mode selector 1320 (or a mode selection system), a first switch 1330, a second switch 1340, a loss matching circuit 1350, an NFC receiver 1360, and a WPT receiver 1370.

Device 1300 may be a mobile device and may be a wireless communication terminal.

The resonator 1310 may be disposed in the case of the apparatus 1300. The case may be a back case of the device 1300. [

The resonator 1310 may receive power.

The NFC receiver 1360 can perform wireless communication using the received power.

The NFC receiver 1360 may be the first NFC receiver 1000 or the second NFC receiver 1090 described above.

The WPT receiver 1370 can charge the device 1300 using the received power. The WPT receiver 1370 can charge the battery in the device 1300 using the received power.

The WPT receiver 1370 may be the WPT receiver 1200 described above.

If the WPT receiver 1370 uses a low Q antenna used in NFC, the efficiency of the WPT receiver 1370 may be very low. Therefore, a high-efficiency high-Q resonator is required for wireless charging.

The WPT receiver 1370 may be a resonant WPT system using a resonant frequency of 13.56 MHz. That is, the resonator 1310 may be a high Q WPT resonator (or antenna) having a resonant frequency of 13.56 MHz. A high Q resonator may mean a resonator with Q greater than 100.

The WPT receiver 1370 needs to use a high Q resonator for the WPT for high efficiency radio power transmission and the high Q resonator is used as the antenna of the NFC receiver 1360 by the WPT receiver 1370 and the NFC receiver 1360 It can be used jointly.

The resonator 1310 may be shared and used between the NFC receiver 1360 and the WPT receiver 1370. That is, the high Q WPR resonator used by the WPT receiver 1370 may be shared as an antenna of the NFC.

The NFC may require a low Q resonator having a wide bandwidth because signals of subcarriers of frequencies away from 13.56 MHz to 847 kHz must be transmitted well.

In order to provide the above-described low Q resonator, a loss matching circuit 1350 can be used. The NFC receiver 1370 may be coupled to the resonator 1310 via a loss matching circuit 1350. The loss matching circuit 1350 can provide a loss matching by using a resistor. The loss matching circuit 1350 may be comprised of lumped elements, such as multi-stage capacitors and inductors, and may provide wideband matching.

The combination of the loss matching circuit 1350 and the resonator 1310 may be low Q. [ That is, the loss matching circuit 1350 may provide a loss matching that lowers the NFC receiver 1370. The NFC receiver 1370 may make the low Q state through the loss matching provided by the loss matching circuit 135. [

As described above, the WPT receiver 1370 and the NFC receiver 1360 can perform tag to reader communication using the same carrier frequency and load modulation. Therefore, if the WPT receiver 1370 and the NFC receiver 1360 are used at the same time, a collision may occur.

Thus, in apparatus 1300, the NFC operation by the NFC receiver 1360 and the WPT operation by the WPT receiver 1370 may not occur at the same time. Therefore, NFC operation and WPT operation need to be systematically separated.

The mode in which the NFC receiver 1360 of the device 1300 operates is referred to as the NFC mode. The mode in which the WPT receiver 1370 of the device 1300 operates is called the WPT mode. That is, the operating mode of the device 1300 may be an NFC mode or a WPT mode. When the apparatus 1300 is in the NFC mode, the NFC receiver 1360 may be a tag operation mode that operates as a reader operation mode or as a tag.

The mode selector 1320 may connect the resonator 1310 to one of the NFC receiver 1360 and the WPT receiver 1370. The mode selection unit 1320 can electrically or electronically connect the resonator 1310 to only one of the NFC receiver 1360 and the WPT receiver 1370.

That is, the resonator 1310 is connected to one of the NFC receiver 1360 and the WPT receiver 1370 by the mode selector 1320, and is separated from the other.

The mode selector 1320 determines whether the device 1300 is in the operation mode of the device 1300 (i.e., determines whether the device 1300 is in an operation mode), and outputs the resonator 1310 to the NFC receiver 1360 and the WPT receiver 1360 1370). ≪ / RTI >

The first switch 1330 may connect or disconnect the resonator 1310 and the NFC receiver 1360. The first switch 1330 may be coupled to the NFC receiver 1360 via a Ross matching circuit 1350. That is, the first switch 1330, the Ross matching circuit 1350, and the NFC receiver 1360 may be electrically or electronically connected.

The second switch 1340 may connect or disconnect the resonator 1310 and the WPT receiver 1370.

The mode selector 1320 may connect the resonator 1310 to one of the NFC receiver 1360 and the WPT receiver 1370 by controlling the first switch 1330 and the second switch 1340. [

The first switch 1330 and the second switch 1340 may selectively connect the resonator 1310 to one of the NFC receiver 1360 and the WPT receiver 1370. The first switch 1330 and the second switch 1340 may be referred to as a mode selection switch. The first switch 1330 and the second switch 1340 may be replaced by a single single pole double throw (SPDT) switch. The first switch 1330 and the second switch 1340 can prevent the large input power from being transmitted to the NFC receiver 1360 when the mode of the device 1300 is the WPT mode, have.

The mode selection unit 1320 can control the first switch 1330 and the second switch 1340 by outputting a switch control signal to the first switch 1330 and the second switch 1340. [ The switch control signal may be a switch input signal. _Vcon may represent a switch input signal.

The switch control signal may be an electrical or electronic signal. The switch control signal may be a 0V or 3.3V signal. The state where the switch control signal is 0V can be named as the initial state. Further, the state in which the switch control signal is 3.3 V can be named as a state in which a specific condition is satisfied.

The first switch 1330 may be a PMOS switch. The second switch 1340 may be an NMOS switch.

The first switch 1330 may cause the resonator 1310 to conduct to the NFC receiver 1360 in an initial state (e.g., when the switch control signal is 3.3V).

The second switch 1340 may cause the resonator 1310 to conduct to the WPT receiver 1370 in a state where certain conditions are met (e.g., when the switch control signal is 3.3V).

By the switch control signal, one of the first switch 1330 and the second switch 1340 is turned ON and the other is turned OFF. Therefore, the resonator 1310 is not conducted to the NFC receiver 1360 and the WPT receiver 1370 at the same time.

The mode selector 1320 can measure the level of power received by the resonator 1310 and can determine the switch control signal based on the level of the measured power.

The resonator 1310 may output the received power to the mode selection unit 1320. [ The power output from the resonator 1310 can be named as the input power. P _in can represent the input power.

The mode selection unit 1320 can determine the switch control signal based on the maximum output power of the NFC.

That is, when the input power input to the mode selection unit 1320 is smaller than the maximum output power of the NFC, the mode selection unit 1320 turns on the first switch and outputs a switch control signal (e.g., 0V The NFC receiver 1360 can be brought into conduction with the resonator 1310 by outputting the switch control signal of the NFC switch 1310. When the input power is larger than the maximum output power of the NFC, The WPT receiver 1370 can be made conductive with the resonator 1310 by outputting a control signal (e.g., a switch control signal of 3.3 V).

The maximum output power of the NFC may be 1W.

About 2 to 3 W of power is used to charge the mobile device. Thus, if the input power is greater than 1 W, the input power may be used by the WPT receiver 1370 to charge the battery.

When the NFC receiver 1360 is in the reader operation mode, power is not input through the resonator 1310. [ Therefore, since there is no input power P _in input to the mode selection unit 1320, a switch control signal of 0V, which is the same as the initial state, is outputted from the mode selection unit 1320, and the NFC mode is automatically .

The device 1300 may operate in the NFC mode in a basic state and may switch to the WPT mode if the incoming input power is large. That is, the device 1300 can basically operate in the reader mode or the tag mode of the NFC, and can be switched to the WPT mode only when the input power is inputted.

By the above switching, the apparatus 1300 can protect the NFC receiver 1360 and the like from large input power and can provide the NFC reader mode without any user intervention.

FIG. 14 illustrates a detailed configuration of a mode selection unit according to an example.

The mode selection unit 1320 includes a rectifier 1410, a capacitor 1420, a low dropout (LDO) 1430, a first voltage divider 1440, a second voltage divider 1450, A comparator 1460, and a fifth resistor 1470.

One end of the rectifier 1410 may receive input power.

The other end of the rectifier 1410 may be connected to the capacitor 1420.

One end of the capacitor 1420 may be connected to the rectifier 1410 and the LDO 1430.

The other end of the capacitor 1420 may be connected to ground.

That is, as with the structure of a power detector or a half-wave rectifier, the capacitor 1420 can be composed of a rectifier 1410 and a shunt.

The rectifier 1410 and the capacitor 1420 may constitute a power detector. The power detector can measure the level of the input power to determine if the input power is greater than or less than 1W. Here, 1 W may mean the maximum output power of the NFC. That is, 1 W in this example can be used to mean the maximum output power of the NFC.

LDO 1430 is provided with input power from a power detector and can supply power (V _dd ) and V _ref to a comparator. V _ref is the converted voltage based on 1W.

LOD 1430 can supply + 3.3V.

The second voltage divider 1450 can convert the magnitude of the input power into a proper V _pin value.

The second voltage divider 1450 may connect the positive terminal of the comparator 1460 and the capacitor 1420. In addition, the second voltage divider 1450 may be connected to the rectifier 1410 and may be connected to the LDO 1430.

The second voltage divider 1450 may include a third resistor 1452 and a fourth resistor 1454.

One end of the third resistor 1452 may be connected to the positive terminal of the comparator 1460 and the fourth resistor 1454.

The other end of the third resistor 1452 may be connected to the capacitor 1420. In addition, the other end of the third resistor 1452 may be connected to the rectifier 1410 and the LDO 1430.

One end of the fourth resistor 1454 may be connected to the positive terminal of the comparator 1460 and the third resistor 1452.

The other end of the fourth resistor 1454 may be connected to ground.

The first voltage divider 1440 can convert V _dd output from the LDO to V _ref , which is a 1W reference conversion voltage.

The first voltage divider 1440 can couple the negative terminal of the comparator 1460 and the LDO 1430.

The first voltage divider 1440 may include a first resistor 1442 and a second resistor 1444.

One end of the first resistor 1442 may be connected to the negative terminal of the comparator 1460 and the second resistor 1444.

The other end of the first resistor 1442 may be coupled to the LDO 1430.

One end of the second resistor 1444 may be connected to the negative terminal of the comparator 1460 and the first resistor 1442.

The other end of the second resistor 14454 may be connected to ground.

The comparator 1460 can output a switch control signal by comparing whether the input power is greater than or less than 1W.

The comparator 1460 compares the V _pin input through the + terminal with the V _ref input through the - terminal, and when the V _pin is greater than V _ref (i.e., when an input power greater than 1 W is received) And outputs a switch control signal of 3.3V that connects the resonator 1310 to the NFC receiver 1330 through the switch control signal. The comparator 1460 also receives a switch control signal 0V that couples the resonator 1310 to the WPT receiver 1370 via the output terminal when V _pin is less than V _ref (i.e., when less than 1W of input power is received) Can be output.

The comparator 1460 can output a switch control signal of 0V in the absence of power (i.e., in the absence of input power). That is, when the apparatus 1300 is in the NFC reader operation mode, the comparator 1460 can output a switch control signal of 0V.

The fifth resistor 1470 may serve as a ground ground for outputting a switch control signal of 0V when no input power is present (i.e., when the device 1300 is in the NFC reader operating mode).

The fifth resistor 1470 may have a resistance value of several kilo ohms (k [Omega]).

One end of the fifth resistor 1470 may be connected to an output terminal of the comparator 1460.

The other end of the fifth resistor 1470 may be connected to ground.

As described above, the mode selection unit 1320 can be simply analogously configured without using a digital component such as an additional MCU or the like.

FIG. 15 shows the operation of the NFC mode according to an example.

In the tag operation mode of the NFC (i.e., when the device 1300 is in the NFC tag operation mode), the magnitude of the input power incoming through the resonator 1310 is less than 1W. Therefore, the mode selection unit 1320 can output a switch control signal of 0V.

By the switch power signal of 0V, only the first switch 1330 can be conducted, and the second switch 1340 can be turned off.

Therefore, only the NFC receiver 1360 can be conducted to the resonator 1310 and the WPT receiver 1370 can be disconnected from the resonator 1310 by the switch power signal of 0V.

Here, 1 W may mean the maximum output power of the NFC.

In the reader operation mode of the NFC (i.e., when the device 1300 is in the NFC reader operation mode), there is no input power coming through the resonator 1310. Therefore, power is not supplied to the mode selection unit 1320. At this time, by the fifth resistor 1470 connected to the output terminal of the comparator 1460, the signal output by the comparator 1460 can maintain 0V. Therefore, only the NFC receiver 1360 can be conducted to the resonator 1310 and the WPT receiver 1370 can be disconnected from the resonator 1310 by the switch power signal of 0V.

16 shows the operation of the WPT mode according to an example.

When the device 1300 is in the WPT mode of operation, the magnitude of the input power coming through the resonator 1310 is greater than 1W. Therefore, the mode selection unit 1320 can output a switch control signal of 3.3V.

Only the second switch 1340 can be conducted and the first switch 1330 can be turned off by the switch power signal of 3.3 V. Therefore, by the switch power signal of 3.3 V, only the WPT receiver 1370 Resonator 1310 and the NFC receiver 1360 may be disconnected from the resonator 1310. [

17 is a flow chart of a method of operation of an apparatus according to an embodiment.

In step 1710, input power is received, e.g., by resonator 1310. [

In steps 1720-1740, the resonator 1310 is coupled to one of the NFC receiver 1360 and the WPT receiver 1370, e.g., by the mode selector 1320, based on the magnitude of the input power.

In step 1720, for example, the magnitude of the input power and the predefined magnitude are compared by the mode selector 1320. [

The predefined size may be the magnitude of the maximum output power of the NFC. Specifically, the predefined size may be 1W.

If the magnitude of the input power is less than the predefined magnitude, then step 1730 is performed.

If the magnitude of the input power is greater than the predefined magnitude, then step 1740 is performed.

In step 1730, the first switch 1330 is turned on and the second switch 1340 is turned off, for example, by the mode selection unit 1320.

In step 1740, for example, the mode selector 1320 turns off the first switch 1330 and turns on the second switch 1340. [

In step 1750, the device 1300 operates in an NFC mode.

At step 1760, the device 1300 operates in the WPT mode.

The technical contents according to the embodiment described above with reference to Figs. 1 to 16 can be applied to this embodiment as it is. Therefore, a more detailed description will be omitted below.

18 is a structural view of an apparatus having an NFC and a WPT according to an embodiment.

Apparatus 1800 may include a WPT resonator 1810 and an NFC resonator 1820.

The resonant frequency of the WPT used by the device 1800 may be different from the resonant frequency of the NFC. For example, the WPT resonator 1810 may be a high Q WPT resonator using a resonant frequency of 6.78 Mhz. The NFC resonator 1820 may be a low Q NFC resonator using a resonant frequency of 13.56 Mhz. The WPT resonator 1810 may use any Industrial, Scientific and Medical (ISM) band resonant frequency except for the resonant frequency of the NFC resonator 1820.

A WPT resonator 1810 requiring a high Q can be placed occupying a preferentially large space within the device 1800. [ After the WPT resonator 1810 is placed, an NFC resonator 1820 with a low Q in the empty space within the device 1800 can be placed. The void space may be above, below or inside the WPT resonator 1810. In Fig. 18, an NFC resonator 1820 is disposed inside the WPT resonator 1810.

19 is a structural diagram of an apparatus having an NFC and a WPT according to an embodiment.

Within the interior space of the device 1800, an NFC resonator 1820 is disposed above the WPT resonator 1810.

The apparatus 1800 may further include the NFC receiver 1360 and the WPT receiver 1370 described above with reference to FIG. The WPT resonator 1810 may be coupled to the WPT receiver 1370. The NFC resonator 1820 may be coupled to the NFC receiver 1360. The WPT receiver 1370 and the NFC receiver 1360 may be used independently of each other.

The NFC resonator 1820 and the WPT resonator 1810 may be respectively connected to the device 1810 and 1810 when the operating frequency of the NFC resonator 1820 and the operating frequency of the WPT resonator 1810 are different from each other as described above with reference to Figures 18 and 19. [ 1800), the NFC system and the WPT system can operate independently of each other. Here, the NFC system may include an NFC resonator 1820 and an NFC receiver 1360. The WPT system may include a WPT resonator 1810 and a WPT receiver 1370.

20 is a graph showing resonance characteristics of an NFC resonator and a WPT resonator using different resonance frequencies according to an example.

The x-axis of the graph represents frequency (MHz) and the y-axis represents S11 (dB). S11 may represent the S11 frequency response. 20, the resonance characteristics 2010 of the WPT resonator 1810 and the resonance characteristics 2020 of the NFC resonator 1820 are shown, respectively.

When two resonators cause resonance using an inductance (L) component and a lumped capacitance component of a coil of a resonator, respectively, two resonators, each using a different resonance frequency, Even if the two resonators are close to each other, coupling does not occur.

That is, even when two resonators using different resonance frequencies are arranged close to each other, almost no frequency change occurs in each of the two resonators. Therefore, the WPT resonator 1810 and the NFC resonator 1820 can exhibit resonance characteristics as shown in the graph of FIG. 20, respectively.

21 is a flowchart of a method of operating a power receiving apparatus according to an embodiment.

In step 2110, the NFC resonator 1820 may receive the first power.

In step 2120, the NFC receiver 1360 may perform wireless communication using the received first power.

In step 2130, the WPT resonator 1810 may receive the second power.

At step 2140, the WPT receiver 1370 may use the received second power to provide a voltage for operation of the device 1800. [

The resonant frequency of the NFC resonator 1820 and the resonant frequency of the WPT resonator 1810 may be different from each other. Inside the device 1800, an NFC resonator 1820 may be disposed inside the WPT resonator 1810.

The technical contents described above with reference to Figs. 1 to 20 can be applied as they are, so that a more detailed description will be omitted below. The input power may mean one or more of a first power and a second power.

The embodiments and examples described with reference to Figs. 1-21 can be used to add a WPT system to a device with NFC capability, and also to a WPT system that performs outband communication . That is to say, a WPT system that performs out-band communication can also use the WPT resonator 1310 by using the mode selection switch described above.

The method according to one embodiment may be implemented in the form of program instructions that may be executed through various computer means and recorded on a computer readable medium. The computer-readable medium may include program instructions, data files, data structures, and the like, alone or in combination. The program instructions recorded on the medium may be those specially designed and constructed for the present invention or may be available to those skilled in the art of computer software. Examples of computer-readable media include magnetic media such as hard disks, floppy disks and magnetic tape; optical media such as CD-ROMs and DVDs; magnetic media such as floppy disks; Magneto-optical media, and hardware devices specifically configured to store and execute program instructions such as ROM, RAM, flash memory, and the like. Examples of program instructions include machine language code such as those produced by a compiler, as well as high-level language code that can be executed by a computer using an interpreter or the like. The hardware devices described above may be configured to operate as one or more software modules to perform the operations of the present invention, and vice versa.

While the invention has been shown and described with reference to certain preferred embodiments thereof, it will be understood by those of ordinary skill in the art that various changes in form and details may be made therein without departing from the spirit and scope of the invention as defined by the appended claims. This is possible.

Therefore, the scope of the present invention should not be limited to the described embodiments, but should be determined by the equivalents of the claims, as well as the claims.

1300: Device
1310: Resonator
1320: Mode selection unit
1330: first switch
1340: second switch
1350: Ross matching circuit
1360: NFC receiver
1370: WPT receiver

Claims (18)

In the power receiving apparatus,
A resonator for receiving power;
A short range wireless communication receiver for performing wireless communication using the received power;
A wireless power transmission receiver that uses the received power to supply a voltage for operation of the power receiving device; And
A mode selection unit for connecting the resonator to one of the short-range wireless communication receiver and the wireless power transmission receiver,
And a power control unit. The method according to claim 1,
Wherein the resonator has a resonant frequency of 13.56 MHz and the Q of the resonator exceeds 100. < Desc / Clms Page number 17 > The method according to claim 1,
A loss matching circuit that provides a loss matching that reduces Q of the resonator;
Further comprising:
And the short range wireless communication receiver is connected to the resonator through the Ross matching circuit. The method according to claim 1,
Wherein the mode selection unit determines the operation mode of the apparatus and connects the resonator to one of the short-range wireless communication receiver and the wireless power transmission receiver. The method according to claim 1,
The resonator outputs the received power as an input power of the mode selection unit,
Wherein the mode selector connects the resonator to the short range wireless communication receiver when the input power is smaller than the maximum output power of the short range wireless communication and when the input power is greater than the maximum output power, The power receiving apparatus comprising: The method according to claim 1,
A first switch for connecting or disconnecting the resonator and the short-range wireless communication receiver; And
A second switch for connecting or disconnecting the resonator and the wireless power transmission receiver;
And the mode selector connects the resonator to one of the short-range wireless communication receiver and the wireless power transmission receiver by controlling the first switch and the second switch. The method according to claim 6,
Wherein the mode selector controls the first switch and the second switch by outputting a switch control signal to the first switch and the second switch such that the first switch and the second switch are connected to one Is ON and the other is OFF. 8. The method of claim 7,
The resonator outputs the received power as an input power of the mode selection unit,
Wherein the mode selection unit outputs the switch control signal for turning on the first switch and turning off the second switch when the input power is smaller than the maximum output power of the short- And outputs a switch control signal for turning off the first switch and turning on the second switch when the output power is greater than the output power. The method according to claim 1,
Wherein the mode selector comprises:
A rectifier and a capacitor for receiving input power to supply V _pin ;
A low dropout to supply V _ref ; And
Comparing V _pin and V _ref and outputting a signal to connect the short-range wireless communications receiver and the resonator when the V _pin is greater than V _ref via the output terminal, and when the V _pin is less than V _ref above through the output terminal A comparator for outputting a signal that couples the wireless power transmission receiver to the resonator;
And a power control unit. 10. The method of claim 9,
Wherein the mode selector comprises:
A first voltage divider for converting the _Vdd output from the low dropout and the negative terminal of the comparator to the maximum output power reference voltage _Vref of the short range wireless communication; And
And a second voltage divider for connecting the + terminal of the comparator and the capacitor and converting the magnitude of the input power to a V _pin value,
Further comprising: 10. The method of claim 9,
Wherein the mode selector comprises:
The output terminal of the comparator and the resistor connected to the ground
Further comprising: Receiving a resonator input power;
Coupling the resonator to one of a near field wireless communication receiver and a wireless power transmission receiver based on the magnitude of the input power;
Operating in a short-range wireless communication mode when the resonator is connected to the short-range wireless communication receiver; And
Operating in a wireless power transmission receive mode when the resonator is connected to the wireless power transmit receiver;
Wherein the power receiving apparatus comprises: 13. The method of claim 12,
&Quot; Connecting the resonator to one of the near field wireless communication receiver and the wireless power transmission receiver based on the magnitude of the input power "
Comparing the magnitude of the input power and a predefined magnitude;
Turning on the first switch and turning off the second switch when the magnitude of the input power is smaller than the predefined size; And
Turning on the first switch when the magnitude of the input power is greater than the predefined magnitude and turning off the second switch
Wherein the first switch couples the resonator and the short-range wireless communication receiver, and the second switch couples the resonator and the wireless power transmission receiver. A computer-readable recording medium containing a program for carrying out the method according to any one of claims 12 to 13. In the power receiving apparatus,
A short distance wireless communication resonator for receiving a first power;
A short range wireless communication receiver for performing wireless communication using the received first power;
A wireless power transmission resonator for receiving a second power; And
And a power controller for controlling the power of the wireless power transmission receiver to supply a voltage for operation of the power receiver using the received second power.
Lt; / RTI >
Wherein the resonance frequency of the short-range wireless communication resonator and the resonance frequency of the wireless power transmission resonator are different from each other. 16. The method of claim 15,
Wherein the short-range wireless communication resonator is disposed inside the wireless power transmission resonator. A short-range wireless communication resonator receiving a first power;
The short range wireless communication receiver performing wireless communication using the received first power;
The wireless power transmission resonator receiving a second power; And
The wireless power transmission receiver using the received second power to supply a voltage for operation of the power receiving device
Lt; / RTI >
Wherein the resonant frequency of the short-range wireless communication resonator and the resonant frequency of the wireless power transmission resonator are different from each other. 18. The method of claim 17,
Wherein the short-range wireless communication resonator is disposed inside the wireless power transmission resonator.

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