JPH10271032A - Radio equipment - Google Patents

Abstract

PROBLEM TO BE SOLVED: To miniaturize the radio equipment of a submillimeter wave/millimeter wave band and to reduce power consumption by transmitting a modulation wave corresponding to inputted data to an antenna and a frequency conversion means at the time of converting the frequency of the received modulation wave and transmitting a non-modulation wave to the frequency conversion means as a local signal at the time of reception. SOLUTION: A transmission/reception change-over switch for time division duplex(TDD), which connects the antenna 5 to a transmission side at the time of transmission and to a reception side at the time of reception is provided and communication is executed by a TDD system. An FSK modulator 1 is provided for the transmission side and a frequency converter 3 and an FSK demodulator 4 are provided for the reception side. When the frequency converter 3 converts the frequency of the received modulation wave, the FSK modulator 1 transmits the modulation wave corresponding to input data to the antenna 5 and adds it to the frequency converter 3 at the time of transmission. At the time of reception, the change-over switch 2 is changed over to the reception side by a TDD control signal and modulation by the FSK modulator 3 is stopped. Then, the non-modulation wave is transmitted to the frequency converter 3 as the local signal.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

2. Description of the Related Art In recent years, with the development of mobile communications, the use of microcells has been advanced, and miniaturization and low power consumption have been promoted not only for mobile terminals but also for short distances connecting these base stations and exchanges. There is a demand for a small wireless device that can be easily installed on a communication line.

In addition, since the above-mentioned wireless device is used to construct a large number of communication lines in a short distance, low power consumption and low power consumption are required.
Cost reduction is required. On the other hand, a time division duplex (TDD) system that allows effective use of frequency resources as a communication system, does not require demultiplexing of a transmission signal and a reception signal, and enables two-way communication with only one wave as a wireless device. Has come to be used a lot.

[0003] For this reason, there is a demand for providing a TDD wireless device satisfying the above requirements.

[0004]

2. Description of the Related Art FIG. 11 is an example of a configuration diagram of a conventional radio apparatus.
FIG. 12 is a timing chart showing a relationship between a time division duplex control signal (hereinafter abbreviated as a TDD control signal) and transmission / reception.

Hereinafter, FIGS. 11 and 12 will be described. In FIG. 11, 1 is an FSK modulator, 2 is a TDD transmission / reception switch (SW ₁ ), 3 is a frequency converter (CONV), 4 is an FSK demodulator (DEM), 5 is an antenna, 6 is a local oscillator (LO). ) And 7 are transmission amplifiers (T.AMP), and 8 is a low noise amplifier (LNA).

[0006] The FSK modulator 1 converts the input carrier of 10 GHz with, for example, 10 Mbps data to the FSK modulator.
Since the SK modulation is performed and transmitted to the transmission amplifier 7, the transmission amplifier amplifies the signal to a predetermined transmission output level (for example, +20 dBm) and transmits the amplified signal to the TDD transmission / reception switch 2.

Here, the TDD transmission / reception switch 2
As shown in FIG. 12, the switching operation is controlled by the state of the TDD control signal (CONT). For example, when the state of the TDD control signal is “1”, the antenna is connected to the output side of the transmission amplifier 7 because it is assigned to the transmission time.

[0008] Then, a transmission FSK signal of 10 GHz is output from the transmission amplifier via the antenna (see FIG. 12). On the other hand, when the state of the TDD control signal is “0” as shown in FIG. 12, the antenna 5 is connected to the input side of the low noise amplifier 8 because it is assigned to the reception time.

Thus, the received FSK signal input via the antenna is amplified by the low noise amplifier 8, and then mixed with the local signal (frequency is, for example, 9930 MHz) from the local oscillator 6 by the frequency converter 3. , 70 MHz, and is applied to the FSK demodulator 4.

As a result, the received FSK signal is demodulated by the FSK demodulator 4 and the reproduced data is taken out.

[0011]

In the configuration of the conventional radio apparatus, a local oscillator 6 is required to obtain a local oscillation signal used for frequency conversion of a received signal.

On the other hand, in radio communication including mobile communication, quasi-millimeter wave / millimeter wave bands have been developed and assigned in recent years due to a shortage of frequency resources. The FSK method, which can be realized with a simple configuration, is often used.

However, various devices such as transistors in the quasi-millimeter-wave band and the millimeter-wave band are not only expensive but also have high power consumption due to poor power efficiency, and have high precision due to the extremely short wavelength. Dimensions are required.

Further, when performing frequency conversion, the frequency stability of the local oscillation signal is determined by the allowable deviation at the intermediate frequency, so that relatively strict stability is required in the quasi-millimeter wave / millimeter wave band. .

For example, in the 70 MHz intermediate frequency band, 10
In order to obtain a KHz stability (1.4 × 10 ⁻⁴ ), 10
In the ultrahigh frequency band of GHz, a stability of 1 × 10 ⁻⁶ is required. In other words, a phase-locked oscillator (P
LO), the crystal oscillator used as the reference signal source is also 1
Since high stability of × 10 ^-6 is required, the crystal oscillator becomes expensive with temperature compensation or a thermostat.

Further, in order to configure a phase locked oscillator,
By frequency division, frequency conversion, or a combination of these,
It is necessary to reduce the frequency to a value that can be compared with the reference signal. In this case, at least 100
MHz or less. However, in order to synthesize the local oscillator, the frequency is reduced to a frequency determined by the output step width (for example, 1 MHz).

As described above, local oscillators (particularly, phase-locked oscillators and synthesizers) in the quasi-millimeter-wave / millimeter-wave band are very expensive, consume large power, and occupy a considerable part of the radio equipment. There have always been many problems in the configuration of wireless devices.

An object of the present invention is to provide a wireless device in a quasi-millimeter-wave / millimeter-wave band, for example, having a small size and low power consumption.

[0019]

FIG. 1 is a block diagram showing the principle of the first embodiment of the present invention. According to a first aspect of the present invention, a modulating means is provided on a transmitting side,
The receiving side is provided with frequency converting means and demodulating means, and when the frequency converting means converts the frequency of the received modulated wave, the modulating means transmits a modulated wave corresponding to the input data to the antenna and the frequency converting means at the time of transmission. I do.

However, at the time of reception, the modulation is stopped by the time division duplex control signal, and the unmodulated wave is sent to the frequency conversion means as a local oscillation signal. That is, as shown in FIG. 1, for example, a part of the output of the FSK modulator 1 is applied to the local oscillation input terminal of the frequency converter 3.

On the other hand, at the time of reception, TDD
Since the DD transmission / reception changeover switch 2 is switched to the reception side and the input data is not applied to the FSK modulator, the FSK modulator transmits an unmodulated wave.

Therefore, by using this unmodulated wave as a local oscillation signal for frequency conversion, a local oscillator in the receiving system is not required. According to a second aspect of the present invention, the modulating means is configured as a phase-synchronous synthesizer, and at the time of reception, when transmitting an unmodulated wave, the frequency of the transmitted unmodulated wave is shifted by an intermediate frequency on the receiving side, and the local oscillation signal is transmitted. And sent it out.

According to a third aspect of the present invention, one of the states taken by the inputted data is made to correspond to the transmission frequency f _0, and the polarity is alternately changed for the other states. And a code converter for converting the data into data having a plurality of states.

The modulation is performed by the output of the code converter. According to a fourth aspect of the present invention, when data in a state corresponding to the transmission frequency f ₀ is input at the time of reception, the input of subsequent data is stopped, and an unmodulated wave of the transmission frequency f ₀ is output from the local oscillation signal. To the frequency conversion means.

The frequency converting means takes out the difference frequency signal between the received signal and the local oscillation signal and sends it to the demodulation means. The demodulation means detects the difference frequency signal and reproduces the data.

According to a fifth aspect of the present invention, the modulating means constitutes a phase-locked frequency synthesizer. Then, at the time of transmission, the frequency division number of the frequency synthesizer is varied in accordance with the input data to extract the modulated wave.

According to a sixth aspect of the present invention, when the input data is multi-level data obtained by converting a plurality of series of data into multi-level data, the demodulation means separates the frequency-converted difference frequency component, and outputs a plurality of detectors. , And code conversion is performed to take out reproduced data.

According to a seventh aspect of the present invention, high-pass filter means is provided for suppressing a beat component which appears in the output of the frequency conversion means at the time of reception and is caused by the frequency difference between the partner station and the own station. According to an eighth aspect of the present invention, there is provided an automatic frequency control means for suppressing a beat component which appears in the output of the frequency conversion means at the time of reception and is caused by a frequency difference between the partner station and the own station.

According to a ninth aspect of the present invention, there is provided a changeover switch for switching between a phase locked loop control signal of the modulation means and an automatic frequency control signal of the automatic frequency control means. Then, at the time of reception, the changeover switch is switched to the automatic frequency control signal side, and a beat component appearing in the output of the frequency conversion means is added to the automatic frequency control means.

Thus, the automatic frequency control means generates an automatic frequency control signal corresponding to the applied beat component to control the oscillation frequency of the voltage controlled oscillator in the modulation means,
Beat components are suppressed.

According to a tenth aspect of the present invention, an automatic frequency control means, a control voltage holding means, a modulation means, and a frequency conversion means are provided in a slave station radio apparatus of a system in which a signal of a master station is guaranteed to be received at regular intervals. When receiving a signal from the master station, the automatic frequency control means controls the oscillation frequency of the voltage-controlled oscillator in the local station modulation means so as to match the transmission frequency of the master station, and sets the control voltage. The voltage is held by the control voltage holding means.

However, when transmitting from the own station to the master station, the control voltage held in the control voltage holding means and the input data are applied to the voltage controlled oscillator to generate a modulated wave.

That is, according to the present invention, by using the modulating means as the local signal source of the frequency converting means at the time of reception, a local oscillator in the receiving system is not required, and modulation and demodulation can be performed with a simple configuration. I made it.

[0034]

FIG. 2 is a block diagram of the second embodiment of the present invention, FIG. 3 is a block diagram of the third, fourth, and seventh embodiments of the present invention, and FIG. 4 is an operation of FIG. FIG. 5 is an operation explanatory diagram of FIG. 3 (part 2), and FIG. 6 is a configuration diagram of a fifth embodiment of the present invention.

FIG. 7 is an explanatory view of a sixth embodiment of the present invention.
(A) is a main part configuration diagram, (b) is transmitted multi-valued data,
(C) is a diagram showing an example of a difference frequency component after frequency conversion,
FIG. 8 is a block diagram of the eighth and ninth embodiments of the present invention, FIG. 9 is a block diagram of a tenth embodiment of the present invention (slave station), and FIG.
It is operation | movement explanatory drawing of FIG.

The same reference numerals indicate the same objects throughout the drawings. Also, the parts described in detail above will be described briefly, and the parts of the present invention will be described in detail. Hereinafter, FIGS. 2 to 10 will be described.

In FIG. 2, reference numeral 1 denotes an FSK modulator;
2 is a TDD transmission / reception switch (SW1), 3 is a frequency converter, 4 is an FSK demodulator, 5 is an antenna, 7 is a transmission amplifier, 8 is a low noise amplifier, 9 is a data switch (SW2), and 11 is Crystal oscillator, 12 is a phase comparator, 1
3 is a loop filter, 14 is a voltage controlled oscillator, 15 a variable frequency divider (DIV1), 16 is a channel information setter, 18
Is a fixed frequency divider (DIV2).

The FSK modulator 1 of this embodiment uses a phase-locked loop (hereinafter abbreviated as PLL) to stabilize the frequency, and uses a frequency synthesizer that can easily set a transmission channel, that is, a transmission frequency. Method is used.

A part of the output of the voltage controlled oscillator (hereinafter abbreviated as VCO) 14 which is the output of the FSK modulator 1 is divided by the variable frequency divider 15 up to the comparison frequency determined by the variable step width of the transmission frequency. The frequency-divided and frequency-divided signal is applied to the phase comparator 12.

Further, the phase comparator 12, so are also added signal of the comparison reference frequency f _r obtained by the output of the crystal oscillator 11 which is a reference frequency source divided by a fixed frequency divider 18, Here, a signal of a frequency difference between the signal of the comparison reference frequency and the signal of the comparison frequency (referred to as an error signal) is extracted and output.

This error signal is added to the VCO 14 via the loop filter 13 and the adder 17, so that the VCO 1
4 is controlled such that the output frequency f ₀ is the N × f _r.
Note that N is the frequency division number of the variable frequency divider 15. The loop filter 13 determines the response characteristics of the phase locked loop.

[0042] Here, To make a FSK modulation to VCO 14, the error signal by the adder 17, i.e., may be applied to the VCO in addition to data to the VCO control signal is bandwidth omega _n of the PLL modulation FSK It must be chosen sufficiently small compared to the frequency f _m (ie the data rate).

The channel information setting unit 16 adds the frequency division number N to the frequency divider 15 according to the communication channel frequency. Hereinafter, the operation of FIG. 2 will be described using a specific example.

Now, the output frequency of the FSK modulator 1 is set to 10 G
Assuming that Hz and the set step width are 1 MHz, the frequency division number N ₀ of the frequency divider 15 at this time is 10,000. Here, if the speed of the input data is 10 Mbps, the data switch 9 is turned on by the TDD control signal at the time of transmission, and the data is applied to the VCO 14 via the adder 17.

As a result, the output of the FSK modulator 1 becomes 10
A 10 GHz FSK modulated wave modulated at Mbps is sent to the transmission amplifier 7. Therefore, the transmission amplifier 7 amplifies the input FSK modulated wave to a required transmission power, and transmits it via the TDD transmission / reception switch 2 and the antenna 5 which are switched to the transmission side.

While the transmitting side is operating, the receiving side is in a non-operating state. On the other hand, at the time of reception, the transmission / reception switch 2 for TDD switches to the reception side and the data switch 9 is turned off, so that no data is input to the FSK modulator 1, the VCO 14 stops the modulation operation, and only the carrier is output. Is done.

Further, the channel information setting device 16
The local frequency of the frequency converter 3 is obtained by changing the frequency division number N of the frequency divider 15 from N ₀ to N _L by applying a TDD control signal for changing the output frequency of the frequency converter 14.

[0048] Here, the intermediate frequency is 70 MHz, the chosen to lower the frequency f ₁ of the local oscillation _{signal, f l = 10GHz-70MHz =} 9.93GHz , and the frequency division number N _L of the frequency divider 15 9 , 930 (at 10 GHz, a shift of 70 MHz is sufficiently possible in terms of fractional bandwidth).

As described above, at the time of reception, the FSK modulator 1 operates as a local signal source of the frequency converter 3, so that the FSK modulator 1
The demodulator 4 is connected to an antenna 5, a TDD transmission / reception switch 2, a low-noise amplifier 8, and a frequency
The received FSK modulated wave of z is input.

Thus, demodulation can be performed in the same manner as in the prior art. That is, during transmission, the FSK modulator 1 generates an FSK modulated wave, but during reception, sets the FSK modulator to the non-modulation mode and sets the oscillation frequency of the FSK modulator so that a local oscillation signal of a desired frequency can be obtained. Set.

As a result, the output of the FSK modulator is applied to the frequency converter 3 as a local oscillation signal, so that a received FSK modulated wave having an intermediate frequency is obtained from the frequency converter 3. In FIG. 3, reference numeral 100 denotes a code converter;
Is a high-pass filter, and 102 is a detector. In this embodiment, the output of the FSK modulator 1 can be used as a local oscillation signal at the time of reception without changing the frequency division number of the variable frequency divider 15 with the TDD control signal.

That is, the basic operations at the time of transmission and at the time of reception are the same as those in the first embodiment.
Is obtained by the manner corresponding to the transmission frequency f ₀ when the state of the data to be input at the time of transmission is "1" or "0".

For example, as in the bipolar system, "1" is represented by a pulse and "0" is represented without a pulse, and the polarity of the presence of a "1" pulse is alternately and sequentially changed to positive and negative.
The pulse is converted into three-state pulses of 0 and -1 (see FIGS. 4A and 4B).

Then, FSK modulation is performed with these three-state pulses. When the transmission frequency at this time is "1", f ₁ ,
When "0" is f _0, when -1 to as the f _-1. On the other hand, at the time of reception, the transmission frequency can be set to the center frequency f ₀ (for example, 10.0 GHz) by setting the state of data “0” by the TDD control signal.

Thus, the frequency converter 3 includes the antenna 5, the TDD transmission / reception switch 2, the low noise amplifier 8
And the three-state FSK modulation signal input through the
A local oscillation signal having a frequency f ₀ is applied from O14.

Therefore, the output side of the frequency converter 3 has three states.
State FSK signal and frequency f₀Difference signal from the
You. Here, the output of the frequency converter 3 has data "0".
Is f₀Therefore, only the DC component is “1” and
And "-I", the frequency is f₁And f_-1And frequency f ₀When
(F)₁−f₀) And (f)₀−f_-1)
Is obtained.

However, since the difference between the transmission frequency corresponding to f ₀ of the partner station and the oscillation frequency of the own station VCO is not actually 0, this difference appears as a beat component. Thus, as shown in FIG. 4C, a signal is obtained in which the frequency components (f ₁ −f ₀ ) and (f ₀ −f ₋₁ ) are superimposed on the beat component.

[0058] Therefore, after the state of FIG. 4-d by suppressing the beat component in the high-pass filter 101, f _1, f _-1
Detector (including, decoder) 10
After the detection in step 2, the ternary value is inversely converted into a binary value and decoded.
Retrieve the reproduction data indicated by -e.

FIG. 5 shows an example of a configuration method of the detector 102 of FIG. 3, and FIG.
FIG. 5B is a diagram of another main part configuration, and FIG.

FIG. 5A shows the presence / absence of a difference signal after frequency conversion and “1” and “0” of a demodulated signal as shown in FIGS. After associating and converting the presence / absence (frequency information) of the difference signal into amplitude information by the detection diode 102 ₁ or the like, the magnitude is compared with the threshold value of the comparator 102 ₂ , and the reproduction data is extracted using the comparison result It is what we did.

FIG. 5B shows a retriggerable monostable multivibrator after converting a difference signal component to a TTL level using a comparator 102 ₃ having a threshold of 0 V, for example, instead of the detection diode. data regenerator 102 ₄ having to detect the presence or absence of the difference signal is obtained by a manner to obtain reproduced data (see ~).

As described above, in this embodiment, it is not necessary to control the frequency shift of the FSK modulator, and it is possible to demodulate a signal with a very simple configuration. FIG. 6 shows the FSK modulation method, in which the input data is not added to the control signal of the VCO 14 as described above, but the data "1", the input data of the frequency division number of the frequency divider 15 constituting the FSK modulator 1 are input. By switching in response to “0”, FSK modulation is performed.

As means for stopping the FSK modulation at the time of reception, the frequency division number is set to one of "1" and "0" of the input data, thereby making the carrier unmodulated.

[0064] That is, when transmission is added input data to the channel information setting device 16 via the data switch 9, for example, the state of the input data is "0", the division number and N ₁ the signal of the frequency f ₁ by, the state of "1", the signal of the frequency f ₂ by the frequency division number and N _2, the manner for delivering respectively, frequency division number N ₁ in transmission data,
By switching the N ₂ FSK modulation signal is obtained.

At the time of reception, if the data switch 9 is fixed to, for example, “0” by the TDD control signal,
The output of VCO ₁₄ is fixed at frequency f1. Therefore,
Received signal in the frequency components of the difference from the frequency converter 3 frequency f ₁ and the reception frequency is obtained.

At this time, the transmitting side also sets “0” to the frequency f ₁ ,
Since “1” is associated with the frequency f ₂ , if the reception frequency is f ₁ , only the DC component is received and the reception frequency is f ₂
Frequency components of the difference between the frequencies f ₁ and f ₂ are output as long.

Here, the high-pass filter 101 in FIG.
The operation of the detector 102 is the same as that of the above-described second embodiment, and a description thereof will be omitted. FIG. 7 shows a method for multi-level data using a detection diode. The multi-level data transmitted as shown in FIG. 7 (b) and the frequency f ₀ after frequency conversion corresponding to the received multi-level data are used. Frequency component of the difference
(C)) is split by bandpass filters 102 ₅ and 102 ₆ corresponding to the respective difference frequency components as shown in FIG. 7A, and the presence or absence of the output signal is determined by diodes 102 ₇ and 102 2.
Detect at ₈

Then, in each signal state, the multi-value /
Transcoded binary conversion circuit 102 _9, in which the manner to obtain reproduced data. Here, in the case of the configuration shown in FIG. 2, FIG. 3, and FIG. 6, a beat signal due to the difference between the oscillation frequencies of the partner station VCO and the own station VCO appears on the output side of the frequency converter 3 during the reception operation.

Therefore, as shown in FIG. 8, the beat signal is used to control the operation of the VCO 14, which is also used as a local oscillator, to perform automatic frequency control (AFC).

In FIG. 8, reference numeral 200 denotes an integrating circuit;
Reference numeral denotes an AFC circuit, and reference numeral 202 denotes a changeover switch for switching between a control signal of a phase locked loop (PLL) of the FSK modulator and a control signal of the AFC.

Now, the AFC operation at the time of reception will be described with reference to FIG. In the frequency converter 3, the VCO 1
When the frequency of the received signal is converted by using the output of No. 4 as the local oscillation signal, as described above, for example, if the frequency at "0" completely matches the partner station and the own station, the DC component Only comes out.

However, since the frequency differs depending on the station,
The difference appears as a beat frequency. Therefore, the beat frequency component is smoothed by the integrating circuit 200 having the same function as the low-pass filter, and is applied to the VCO 14 via the AFC circuit 201 and the switch 202. The AFC circuit controls the VCO 14 so as to suppress the beat frequency component. Control the oscillation frequency of

FIG. 9 shows a case where one master station and a plurality of slave stations are
In a system that communicates by a communication method, periodic communication is always performed from a master station to a slave station, and periodic communication is performed at sufficiently short intervals as compared with the short-term frequency stability of the VCO 300 used for the FSK modulator. Applies to the system.

[0074] In other words, the child station when it receives a signal from the master station, turn on the switch SW _4, V by the AFC operation
The VCO control voltage is controlled so that the oscillation frequency of the CO 300 matches the transmission frequency of the master station. The control voltage at this time is held by the capacitor C.

Then, each slave station performs FSK modulation transmission to the master station at another predetermined time using the held control voltage. In other words, the slave station receives the signal of the master station at regular intervals and corrects and holds the control voltage, thereby eliminating the need for a phase locked loop and simplifying the configuration of the FSK modulator.

Here, reference numeral 300 in FIG. 9 denotes a VCO,
An FSK modulated wave is generated by adding transmission data to the O control voltage. An AFC circuit 301 is an AFC circuit 3
01 ₁ , switch SW ₄ , and capacitor C.
AFC control and holding of the control voltage of the VCO 300 are performed by the TDD control signal. 302 is an adder.

The switch SW ₄ is turned on when receiving the FSK modulated wave from the master station by the TDD control signal, and is turned off when transmitting the FSK wave to the master station. become.

The operation of FIG. 9 will be described below with reference to FIG. When the slave station receives the FSK modulated wave from the master station, the frequency converter 3 uses the output of the VCO 300 as a local oscillation signal to frequency-convert it into a difference signal between the received FSK wave and the local oscillation signal.

At this time, if there is a difference between the oscillation frequencies of the VCO 300 of the master station and the own station, the difference frequency appears as a beat component as described above. Add to ₁ .

Therefore, the AFC circuit 301 controls the VCO 300 so that the input beat component is reduced. In addition, at the time of the slave station reception, the switch 9 is operated by the TDD control signal.
Is in the "OFF" state, data input is blocked, and FSK modulation is not applied to the VCO 300.

[0081] Also, AFC circuits 301 _1, held in the capacitor C to the VCO control voltage during receiving via the switch SW ₄ in the ON state is provided on the output side are (stored) (Fig. 1
0a, b).

[0082] On the other hand, when slave station transmission, the TDD control signal, the switch SW ₄ in the output side of the AFC circuit 301 ₁
Is turned off, the AFC loop is opened, and the previously stored VCO control voltage is output from the capacitor C.

Then, the VCO 300 holds the held VCO control voltage and the data that has passed through the data switch 9 turned on by the adder 302, so that the oscillation frequency almost coincides with that of the master station at the beginning of transmission. Is obtained.

However, as the transmission time elapses, FIG.
Since the voltage stored in the capacitor gradually decreases as shown in FIG. 7, the transmission frequency from the slave station deviates from the initial value.

Then, while this frequency shift is within the allowable range, the slave station is again in the receiving state, as shown in FIG. 10A, so that the capacitor C is charged again and almost coincides with the master station. An FSK modulated wave having an oscillation frequency is obtained.

As described above, in the present embodiment, the frequency stability of the FSK modulated wave can be improved without using a phase locked loop, and the configuration of the transmission side of the slave station can be improved as compared with the above-described embodiment. It is very simple, and can be reduced in size, power consumption, and cost.

It is necessary for the master station to achieve high stability by using a phase locked loop or the like as in the above-described embodiment.

[0088]

According to the present invention, the modulator on the transmitting side is set in a non-modulated state at the time of reception, and is used as a local signal of the frequency converter.

As the simplest modulator, a frequency modulator is used as an embodiment. Frequency modulation can be easily performed by superimposing data on the control voltage of the VCO.
Further, the VCO is a component of the synthesizer, and by utilizing this, the configuration can be made simpler (it is easy to make the synthesizer a modulator).

Further, since frequency modulation can be realized by a VCO, not only microwaves but also quasi-millimeter waves and millimeter waves can be easily produced, so that direct modulation in these ultra-high frequency bands is also possible. Thus, a modulated wave in a high frequency band can be obtained without using the heterodyne method or the like.

That is, according to the present invention, by using the FSK modulator as the local oscillator of the frequency converter, the local oscillator on the receiving side is not required, and the FSK modulator has a simple configuration.
K modulation and demodulation can be performed.

As a result, the size and power consumption of the quasi-millimeter-wave / millimeter-wave band radio device can be reduced, and there is an effect that the provision of a low-cost device or a line is large.

[Brief description of the drawings]

FIG. 1 is a principle configuration diagram of the first invention.

FIG. 2 is a configuration diagram of a second embodiment of the present invention.

FIG. 3 is a configuration diagram of a third, a fourth, and a seventh embodiment of the present invention.

FIG. 4 is an operation explanatory view (part 1) of FIG. 3;

FIG. 5 is an operation explanatory view (part 2) of FIG. 3;

FIG. 6 is a configuration diagram of a fifth embodiment of the present invention.

FIGS. 7A and 7B are explanatory diagrams of a sixth embodiment of the present invention, wherein FIG. 7A is a configuration diagram of a main part, FIG. 7B is transmitted multi-value data, and FIG. 7C is an example of a difference frequency component after frequency conversion; FIG.

FIG. 8 is a configuration diagram of the eighth and ninth embodiments of the present invention.

FIG. 9 is a configuration diagram of a tenth embodiment of the present invention.

FIG. 10 is an operation explanatory diagram of FIG. 9;

FIG. 11 is an example of a configuration diagram of a conventional wireless device.

FIG. 12 is a timing chart showing the relationship between TDD control and transmission / reception.

[Explanation of symbols]

DESCRIPTION OF SYMBOLS 1 FSK modulator 2 TDD transmission / reception switch 3 Frequency converter 4 FSK demodulator 5 Antenna 6 Local oscillator 7 Transmission amplifier 8 Low noise amplifier 9 Data switch (SW ₂ ) 11 Crystal oscillator 12 Phase comparator 13 Loop filter 14 Voltage control Oscillator 15 Variable frequency divider (DIV1) 16 Channel information setting device 18 Fixed frequency divider (DIV2) 100 Code converter 101 High-pass filter 102 Detector 200 Integration circuit 201 AFC circuit 202 Switching switch

Claims (10)

[Claims] 1. A wireless device that includes a time division duplex transmission / reception switch for connecting an antenna to a transmission side during transmission and a reception side during reception, and performs communication in a time division duplex mode. The modulation means and the frequency conversion means and the demodulation means are provided on the receiving side. When the frequency conversion means converts the frequency of the reception modulation wave, the modulation means converts the modulation wave corresponding to the input data to the antenna at the time of transmission. A wireless device, wherein the wireless device is configured to transmit to a frequency conversion unit as a local oscillation signal when receiving the signal, but stop modulation by a time division duplex control signal upon reception. 2. The wireless device according to claim 1, wherein the modulating means is configured as a phase-locked synthesizer, and when transmitting a non-modulated wave, the frequency of the transmitted non-modulated wave is
A radio apparatus characterized in that it is configured to shift as an intermediate frequency on the receiving side and transmit as a local oscillation signal. 3. The radio apparatus according to claim 1, wherein one of states taken by the input data is made to correspond to the transmission frequency f _0, and the polarity is alternated for the other states. And a code converter for converting the data into data having a plurality of states by changing the data to a plurality of states, and performing modulation by an output of the code converter. 4. The wireless device according to claim 3, wherein the modulating means stops input of data when receiving data in a state corresponding to the transmission frequency f ₀ ,
An unmodulated wave having a transmission frequency f ₀ is sent to the frequency conversion means as a local oscillation signal, the frequency conversion means extracts a difference frequency signal between the received signal and the local oscillation signal, and sends it to the demodulation means. A wireless device having a configuration for detecting a difference frequency signal and reproducing data. 5. The radio apparatus according to claim 4, wherein the modulating means has a configuration of a phase-locked frequency synthesizer,
A wireless device, wherein at the time of transmission, a modulation frequency is taken out by varying the frequency division number of a frequency synthesizer according to input data. 6. The wireless device according to claim 3, wherein when the input data is multi-valued data obtained by converting a plurality of series of data into multi-valued data, the demodulation means separates the frequency-converted difference frequency component. ,
A wireless device characterized in that it is configured to detect with a plurality of detectors, perform code conversion, and extract reproduction data. 7. The radio apparatus according to claim 3, further comprising high-pass filter means for suppressing a beat component appearing in an output of the frequency conversion means at the time of reception and caused by a frequency difference between the partner station and the own station. A wireless device, comprising: 8. The radio apparatus according to claim 3, further comprising an automatic frequency control means for suppressing a beat component which appears in an output of the frequency conversion means at the time of reception and is caused by a frequency difference between the partner station and the own station. A wireless device characterized by the above-mentioned. 9. The wireless device according to claim 8, further comprising: a changeover switch for switching between a phase locked loop control signal of the modulating means and an automatic frequency control signal of the automatic frequency control means. Side, and adds a beat component appearing in the output of the frequency conversion means to the automatic frequency control means. The automatic frequency control means generates an automatic frequency control signal corresponding to the applied beat component, and A wireless device having a configuration in which an oscillation frequency of a voltage controlled oscillator is controlled to suppress a beat component. 10. A slave station radio apparatus of a system in which a signal of a master station is guaranteed to be able to be received at regular intervals, provided with an automatic frequency control means, a control voltage holding means, a modulation means and a frequency conversion means. The automatic frequency control means controls the oscillation frequency of the voltage controlled oscillator in the local station modulation means to be equal to the transmission frequency of the master station while receiving the control signal, and sends the control voltage to the control voltage holding means. When transmitting from the own station to the master station, the control voltage held in the control voltage holding means and the input data are applied to the voltage controlled oscillator to generate a modulated wave. The wireless device according to claim 1, wherein: