JPH02243077A - Picture display signal generator - Google Patents

Abstract

PURPOSE: To transmits such a signal that matches to a receiver having specific resolution by providing a signal source which generates signals indicting continuous line scanning distributed in a field direction and a means which alternately selects every other picture elements from adjacent pairs of scanning lines. CONSTITUTION: High-visibility luminance signals are impressed upon a 4.2-MHz low-pass filter 1106 and band width-limited signals are generated at the output terminal of the filter 1106. The principal advantage of this system is that the band width is affected in both the vertical and horizontal directions due to the zigzag scanning of one low-pass filter in ±45 deg. direction. During the effective period of each horizontal line, the band width-limited signals are impressed upon a chrominance burst inserting circuit shown as the block 1110 in the figure through a switch 1108 where chrominance signals are added to the luminance signals in a frequency alternating way. The synthesized chrominance-luminance signals are impressed upon another block 1112 where standard synthesized NTSC signals are formed by adding a synchronizing signal and a blanking signal to the chrominance-luminance signals. The NTSC signals are impressed upon a standard broadcasting device and transmitted to a standard receiver 1114 and a high-visibility receiver through a broadcasting antenna 1116.

Description

DETAILED DESCRIPTION OF THE INVENTION [Technical field to which the invention relates] The present invention relates to an image display signal generation device used in a television system, and an embodiment of the invention provides a The present invention is used in a television system with a resolution equal to or higher than that of 1, and the present invention will be described here for a case where the present invention is used in a demonstrative high-definition television system.

(Prior art) Standard NTSC television has 5 frames per frame.
25 scans are performed, and each frame has 262.
It is in the form of two fields with five lines each. Each scan line of each field is interlaced with each scan line of an adjacent field, and flicker at a field frequency of 60 Hz is reduced by visually integrating this interlace scan f:#i.

However, the vertical line structure is sometimes still visible, especially when viewing a large screen television screen from a relatively close distance. This problem is exacerbated in the case of very large wall screens formed by projection television display devices. Scan & IJ
The need for the viewer to be optically separated from the screen in order to integrate the image reduces the advantage of such large screens in providing the illusion of envelopment around the viewer.

The implementation column method uses a camera that generates two lines for each standard line (1050 lines per frame instead of 526 lines), and uses a camera that generates two lines for each standard line (1050 lines per frame instead of 526 lines), and relates the sum and difference of pixels on adjacent risk lines. By forming each separate signal and transmitting the sum signal as a dual-purpose signal together with the difference signal (which may be transmitted separately or obscured in the composite color signal), the NTSO (or PAL) type standard clear Visibility of vertical line structures is reduced in a manner similar to that of television. This method increases the vertical resolution by increasing the number of vertical lines, thereby allowing the super large screen to be viewed from a short distance without perceiving the vertical line structure. Using this method, the horizontal resolution set by the brightness bandwidth is approximately 330 TVs! /: As is the g-line, the vertical m degree and the rominance solution 1 degree are approximately 1 degree.
There will be 000 books. As vertical line structures become increasingly indistinguishable, horizontal resolution becomes the limiting factor in the distance between the viewer and the super-sized Iji surface.

A high-resolution television system has been proposed and produced, but in order to achieve an appropriate horizontal resolution, this system uses 20 M
A bandwidth as high as H2 is used. Until now, the high horizontal resolution of about 500 television lines was the usual N'r s c t
It was thought that such 1 still & could be transmitted to the receiver only by a transmission chatter V having a wide bandwidth (more than 6 MEIZi in the NTSO system). Therefore, proposals for this type of broadcasting focused on direct broadcasting (DSB) or cable distribution systems.

[Disclosure of the invention]

In such a way that the signal contains enough information to allow the receiver Sa to reproduce di@ with relatively improved vertical and horizontal resolution within the same bandwidth limit without significantly degrading the performance of the receiver Sa. It is possible to transmit a PV viewer signal in a composite format suitable for a receiver of a particular resolution.
Very desirable.

The present invention will now be described in detail with reference to the accompanying drawings.

The following explanation will be made regarding the NTSO method.

[Implementation sequence of the invention]

The uX1 diagram shows the risk of height to width having an aspect ratio of 3 to 4. This risk is scanned in a common manner by a series of water lines (not shown). Alternately bright and dark vertical lines are displayed on the raster, and these bright and dark lines are related to the number of cycles M of the signal to be processed. NTSC horizontal scanning time is 63
・It takes 6 microseconds, and the width of about 10 microseconds is used for water return and erasure, and the remaining about 53 microseconds is the time for effective line scanning. The alternating bright and dark lines formed on the raster in FIG. 1 require positive and negative signal swings of frequency determined by the number of lines of the subject to be broadcast on television and their physical relative spacing. television signal ti
If the bandwidth is implemented on each receiver, effectively about 4 ME (z), then the highest frequency signal that can pass through that channel V will take 74 μs to complete one full cycle (15 degrees). (one positive and negative swing of the signal) can pass.53
Approximately 220 complete cycles occur in μ seconds (the time of the effective portion of a horizontal line), so 220 black lines and 220 white lines can be generated in one horizontal line, and a total of 440 lines are generated in one complete water scan. Television lines are created. However, according to standard television practice, in order to determine the solution @e) when the Ill semi-resolution C'9 star is rectangular and the height and width are equal, the water motive solution I#! #t, k Need to be multiplied by 3/4. Therefore, the horizontal solution density is about 330 TVs9 with a bandwidth of 4 MHz.
In other words, there are about 80 televised lines per IMHz. Using this standard, the solution in the horizontal direction for a color signal component with a bandwidth of 1.a MHz is about 120 televised lines. Since it is much more sensitive to mvjX and change 1hi than to changes in
It is recognized that there are 330 books in Kan.

As shown in Figure 2 (each feed V contains more than 250 scan lines in the vertical direction), the horizontal resolution is limited to about 120 television lines by the bandwidth of the chrominance channel V as described above. On the other hand, the vertical color resolution is not determined by the Nayanne V band 1@, but by the number of horizontal lines sampled in the image in the vertical direction, so the color resolution in the 1 m vertical direction is much better than in the horizontal direction. The degree of sensitivity in the horizontal direction is inappropriate, and as mentioned above, the linear structure is visible on the nine-person screen, so the degree of smokeness in the vertical direction is also inappropriate.

Figure 3 shows the optical part of the high-resolution camera. In the figure, light from an object indicated by an arrow 301 passes through an optical system indicated by a block 302 and enters a color dividing prism 304. As is known in the art, the green light G is further focused through a pond optic 306 onto the photosensitive element or faceplate 12 of the videcon IO. The red component R of the light from the subject is separated by the prism 304 and sent to the optical system 3 component 9 by the sibi decon 31.
Similarly, the back light B is separated by a prism 304 and sent to a videcon 32 by an optical system 314.
is focused onto the photosensitive element 0. Vidacon 10.310
．． 320D is capable of resolution of more than 1000 lines in both the horizontal and vertical directions, and is of the type S (diode alpha gun immersion tube), etc., and is aligned as required for superimposition of the R and G%B rasters it generates. ing.

FIG. 4 shows a schematic diagram of a high-resolution one-quadrant videcon lO and its attached g circuit. The V-decoder Y10 has a face V-toe 12, behind which a photosensitive target element coupled to a target IC [14], and an electron beam (Fig. (not shown) is horizontally deflected to horizontally scan faceplate 12 to form horizontal scan line 20 . This scanning electron beam is deflected in the vertical direction by the magnetic field of the vertical winding #122 driven by the vertical deflection generator 24. Auxiliary deflection winding 26 is driven with a high frequency signal from a vibration signal generator 28. The high frequency signals generated from this generator 2 are also synchronized to the horizontal deflection generator 18 and the vertical deflection generator 24t - each generator of a synchronizing signal, a pinning signal and a subcarrier signal, shown schematically as a synchronizing block 30. Applied as a signal. The vibration signal generated by generator 28 is also associated with videcon 310, 320.

It is also applied to a synchronization signal generator corresponding to synchronization generator 30. The scanning of the face plate 12 by the electron beam on which the artist is focused generates a signal on the target metal 14, as is known, which signal indicates the 03ii moat.

The painter display signal from this target 14 is sent to the preamplifier 3.
2 and probe 34 are applied to ordinary signal processing circuits such as the black pair A/crimp circuit and gamma correction circuit.

g5 Figure a shows a TV screen raster, or a television screen, whose whole is represented by 500, and three scanning lines n-1, n%n+ arbitrarily selected from among the many scanning lines that make up the raster.
1 is shown. Each scan line consists of a number of pixels, the size of which is determined by the resolution of the television system. In the standard sharpness concealed NTSOy-v visual system, the number of pixels in each scan line is approximately 000. The first pixel of line fl-1 is 5
01, and the last pixel is 602. In the NTSC television system, n-1, n, and n+1 are sequentially scanned into one television frame, so that the scanning lines of the second feed V forming the television frame can be inserted between them. have sufficient spacing. In the sixth factor a, a region near an arbitrary pixel 504 on line n is shown enlarged to make it easier to understand.

The illustrated Il! It will be understood by those skilled in the art that +i'fg being square is merely an example. 6th
The figure shows a part of the lister pattern of the DIS high-resolution hand controller expanded as in the fifth factor a. Due to the high resolution of Sachicon, the pixels are small, so the space occupied by one pixel in a standard sharpness scan is replaced by four pixels.
510 to 616 are occupied. Pixels 510 and 612 can be considered to be part of the sub-raster line P, and pixels 514 and 616 can be considered to be pixels of the sub-raster line P-)-1. A DIS-type satin scan can deflect its beam to produce a raster with 1050 horizontal lines, each containing about 1400 pixels, which reduces the number of scan lines and each Each scan line has twice the number of pixels, and the sky +
14 resolution becomes 4f&. If you try to display the artist by transmitting a high-resolution signal extracted from a high-resolution camera attached to the conduit 5, Figure 00, and using all of your understanding abilities.

Also, if you try to transmit that image at a rate of 30 frames per second as in the standard NTSC system, the required bandwidth is N
This is four times the bandwidth required by the TSC method, that is, 4.2 MHz x 4 = 16.8 MHz. On top of this, the 6 sMHz luminance signal is 11 degrees K 4.2M
Standard alviHz NTS with only Hz allocated
It is clear that it is not possible to transmit via O channel V.

FIG. 6a shows a proposed viewing lister for a high-definition television screen system configured to be used in common with a standard-definition system. Subraster scanning @P, P+2゜P+4 F+
, a... correspond to the standard sharpness raster represented by the solid line corresponding to the odd numbered field and the broken line corresponding to the even numbered field.
An orthogonal pattern is formed with respect to the standard sharpness type sump M which occurs at an even integer multiple of 1/2 the horizontal line scan frequency. The pixels denoted by X also form a high definition television sump V which occurs on a high definition raster with twice the vertical resolution.

When the dynamic signal generator 2 energizes the auxiliary vertical deflection winding 26 at a frequency that is an odd multiple of 72 of the line scanning frequency and controls the amplitude of its vibration, the sub-risk @ P and P÷1 are searched in a zigzag manner as shown in FIG. 6b. Each successive scan of an results in 1050 @high definition pixels as shown in FIG. 6b. 1lljld
Explore one of two sets with different i elements.

The high definition television raster of FIG. 6b is scanned with scanning points that oscillate at an odd multiple of 172 of the horizontal line scan frequency M. This oscillatory scanning is shown by the zigzag diagonal lines 1, 2, 3, 4 representing the four feeds required to completely scan the high definition television v-lister. Time order scan @
The standing phase transfer of the vibrating butterfly ν on P, P+4%P+2°p+a is shown.

What is the frequency of this vibration?

1 oav x fh/2 = 8. S94229M
In E(Z, f is the line scanning frequency, and the integer 1061 is the frequency obtained when the obtained frequency is 2 of the resolution of the standard sharpness NTSC system.
The sub-image δ10.516,518.520.222 due to the vibration represented by a zigzag @X (with an arbitrary starting point) between
. . . are sequentially searched for sub-pixels. Subpixels 524 to 53 of the n+1th line after scanning the nth line
4 is searched in a zigzag path. 1/2 of line scanning frequency
For example, the subpixel alO, 516 of the nth line is
, 518 or the pattern of subpixels 528, 530, and 552 on the n+1th line immediately below it, so that a phase difference state may occur on the scanning lines formed in time order. I understand. a second interlaced monochrome buoy (2) is scanned at the end of the monochrome buoy;
# jumped between line n and n4-1! q subpixel 536~
648 will be explored soon. In the MX1 feed V (3) of the second frame, mn subpixels 610, 612, 51
4.612.614.616.618 is searched, and sub-111ij element (unnumbered) of line n+1 is searched. In the second fee y V (4) of the second frame, subpixels along line 4 are scanned. It can be seen that the second half of the subpixels searched during this second frame V-frame constitutes a completely different set of subpixels than the set searched in the gXl frame.

Sub-pixels of each line e.g. P and P+1 of line n and P+ of line q
Since interlacing of 2 and P+3 scans is performed by sequential vertical scanning, 525 camera scans! - The pattern will have to pass through two complete frames before exploring each sub-pixel. In this respect, the vibration signal has the same time compatibility as the color printing m transmission at an odd multiple of 172 of the line scanning frequency, and it takes 4 feeds to complete each cycle of repetition. Therefore, the output signal of the camera is a display of a high-definition image, but the high-definition-1 dormitory is generated at 15 Hz, which corresponds to two frames, instead of 30 Hz, which is for one frame. High definition painter is practically standard #J1 elephant frequency 1
/2, so the bandwidth required to transmit this painter is 16.8 ME (Z
It's not just 8.4MH2; The interlacing sub[i1i element repeats at a frequency of 15H2, so 1
A 2:1 reduction in bandwidth can be achieved with the 5H25 subpixel-to-subpixel flicker. Such small area flicker is not considered an eyesore, and this inter-subpixel flicker can be reduced or eliminated using the frame memory described above.

The high-definition camera of FIG. 4, which scans the risk of 525 #i including two interlaced fields of 262.51a at frequency 30E (Z) as described above, can be used in combination with a conventional standard-definition 525-line monitor. With a complete display, this dual-purpose capability is limited to 4.2 M bandwidth for standard definition monitors.
Obtained from Hz. Due to this bandwidth limitation, the monitor cannot resolve the sub-pixels caused by the zigzag sub-risks nor can it resolve the zigzag oscillations, but averages them out.

Since the scanning frequency is basically the standard 525#l scanning,
The image receiver 1 or monitor displays [quasi-image 1] even though the high-definition Ft information is buried in the signal. Standard sharpness of 525
#jjDisplay Device 15Hz7 II Lacquer This may result from the fact that the subpixels of each successive scan may be different and may be averaged differently for each displayed frame. This small area) II lacquer.

In particular, the oscillations are generally small and can be tolerated since the differences between adjacent sub-pixels that cause them occur only in tilts associated with high frequency changes or fine parts of the image. In Figure 1, No. 18 generated by the high definition camera 400 in Figure 44 is the signal source for the standard definition monitor 10, and the low frequency range is ft.
The device (I, PF) is limited to a bandwidth of 4.2 MH2 by the filter 12 to produce an image of standard definition, while at the same time the bandwidth is not so limited and the signal is properly It is symbolically shown that the configured multi-definition monitor 14 can produce a high-definition painter. FIG. 8 shows the general structure of high definition monitor 114 in simplified block diagram form.

In this figure, the high definition IJj signal is amplified by a broadband interpolated amplifier 810 and applied to each iE[ of the image tube 812. A sync signal separator 81 is coupled to the output terminal of the amplification aI 810, which separates vertical and horizontal sync signals from the composite signal and applies them to a vertical and horizontal deflection circuit indicated by block 816. The horizontal deflection signal is applied from the deflection circuit 816 to the horizontal deflection winding 818K associated with the picture tube 812, and the vertical direction signal is similarly applied to the vertical deflection winding 820. movie amplifier 8
A burst isolation 6822 is coupled to the output terminal of 10 to generate a burst-related subcarrier signal, which is connected to a rominance circuit (not shown) and a vibration signal generator 824 that generates a vibration signal of approximately 8.39 MHz. To 13J. The generated vibration signal is combined with the vertical-quotient signal and applied to the vertical 1iL deflection winding @820, and the 1iL deflection winding is applied to the display picture tube 812.
30 risk of having 525 zigzag lines with frame
Occurs at the E2i frequency. The bandwidth of the amplifier 810 is wide enough to prevent sub-pixel averaging, so that the sub-pixels are reproduced at appropriate points on the sub-scan lines of the scanning raster to achieve the Akane sharpness #.
Generates Jl elephant. A phase control circuit, shown at block 826, may also be coupled to control the phase of the vibration signal to provide the same effect as fine focusing adjustment.

FIG. 9 is similar to FIG. 8, but includes a 105/J line frame marking device 910 and an attached write address generator 912.
A high definition monitor is shown in simplified block diagram form, including a read address generator 914 and a read address generator 914 . This configuration is achieved by storing 1050 #l high definition frames corresponding to NTSC 4-feed V-domain high definition information [11111i
! Eliminate flicker. The information is burst separator 822
is stored at the frequency of the incoming signal by controlling the corrupting address generator 912 with the aid of a signal derived from the incoming signal. On the reading side, the local #IJJ occurrence 591st is the reading period If! lk, but this reading frequency can be made independent of the number of incoming signal stations M to obtain the benefits of progressive or non-interlaced scanning. Visible scan line e
Due to the above-mentioned reduction progressive scan, the high-definition signal of the configurations of FIGS. 4 to 9 has an effective frequency t extending to 8 MHz.
A high definition signal having a lt range is generated. c high visibility 1S at frequency 15f (not at Z (required when generated at soHz)) regardless of the effective drop from 16MHz, sMH
The signal band reduction width of z is 4.2 MH obtained by the 4-necessary definition method.
It is clear that such a signal will not match the WA-compliant NTSO broadcast signal, since it exceeds the m-bandwidth of Z.

Figure 10 shows a circuit configuration that allows a standard definition monitor to receive a luminance signal having an fs subband ds of 4.2 MHz while a high definition monitor receives a signal containing high definition information in Table 1. show. In this figure, a high definition camera "F 400" generates a baseband signal with an effective frequency bandwidth extending to 8.4 MHz, and this signal is passed through a 4.2 MHz low-pass filter fI 151010 to a standard definition monitor 110.
K is applied. In this way, the high frequency or high definition part of the information generated by the camera 400 is removed by the III wave generator 1010 before being applied to the sub-definition monitor.

This bandwidth limited signal is also applied to the first human power of the high definition monitor. A subtraction circuit 1014 subtracts the bandwidth-limited signal at the output of the a@wave D1010 from the full-bandwidth signal at the input of its l1M unit to produce a difference signal having a bandwidth of 8.4 MHz from 4.2M unit. This difference signal represents the high-definition part of the signal, and due to the combination of the filter 1010 and the subtraction circuit 1014, it is used as a high-frequency IIi wave filter.The difference signal is applied to the IIE2 of the high-definition monitor 1012. be done.

In the monitor 1012, an adder circuit 101B receives the bandwidth limit signal (I, BS) and the difference signal Δ, adds the two, reproduces a high definition signal, and applies it to the monitor 14, which outputs the high definition signal. generate.

In the circuit of FIG. 10, the high definition signal is divided into two elements. The 1jlE1 element is a bandwidth-limited signal that can be applied to the WA semi-definition monitor and the high-definition monitor via the normal 4.2 MHz brightness ≠ Janne V, representing the high-definition vertical water droplet. The video signal is sent to the high definition monitor via a second channel V, indicated by conductor 1016.

In the development of NTSO color television, the psychophysical properties of the human eye were considered, and the significant reduction in the bandwidth required to transmit a color television screen meant that the eye could no longer perceive fine details of color. obtained by using. Similarly, the psychophysical properties of the subject pond are used to reduce the bandwidth required to transmit the high definition signal by I#. A similar characteristic of the eye that tolerates low bandwidth for high definition television is the eye's inability to distinguish part a of a moving object.

In principle, therefore, television systems do not require large bandwidths whenever the subject is moving.

The circuit configurations of FIGS. 4-10 illustrate a means for generating a high definition image in which the high definition component includes portions of the vertical water column that are oriented in both directions.

FIG. 11a shows a signal processing low-transmission circuit 1100 that receives a high-definition change signal, a chrominance signal, and a synchronization signal and generates a dual-purpose signal in which the high-definition component of the stationary part of the imager is hidden within the blinking period. shows. In this figure, a high-definition signal generated by the zigzag running JEK described in FIGS. 4 to 6 is applied to the upper left input terminal 1101,
An associated synchronization signal is applied to input terminal 1102 and a modulated chrominance signal is applied to input terminal 1104. High definition 4
The variable signal is a 4.2M device (ZIga M fl device x1o6
is applied to generate a band 114m1lrtl signal at its output terminal. The main advantage of this method is that the low frequency range of 11
111f! is that the ±45@ direction of the zigzag scan affects the bandwidth in both directions of the vertical water droplet. During the validity period of each horizontal line, a bandwidth limiting signal is applied via switch 1108 to a chrominance burst insertion circuit, shown at block 111O, where the chrominance signal is added to the luminance signal in a frequency alternating manner. This composite chrominance luminance signal is applied to a pond block 1112 where a synchronization signal and a blinking signal are added to form a standard composite NTSO signal, which is applied to a standard broadcast 1111x4 and broadcast antenna 1116; The signal is sent to an Ill standard receiver and a special receiver that processes high-definition signals.

During the validity period of each horizontal line, the bandwidth limit signal is switched to switch 111.
8 K to Analog-to-digital converter (ADO) 1 unit 20
supplied to The switch 111B is interlocked with the switch 1108 and both are controlled by the switch control circuit 1122, and is in its upper position during the effective g of each scanning line.
The digital V signal at the output terminal of AD 01120, which is in its lower position during each additional scan line blanking portion and during the asynchronous portion of the vertical blinking period, is applied to a digital summing circuit 1124, where The digital V-band attenuation limit signal is modified by K by adding thereto the signal applied to the gg large input and applied to the input terminal of the 1050#% frame store 1126. The frame register 1126 receives a synchronization signal from the terminal 1102.
- Controlled by address generator 1128. glla
The ADO 1130 at the lower left of the figure has its input coupled to the input terminal 1101, receives a high-definition incoming signal, generates a digital signal representing it, and transfers this to the pixel comparison vIim circuit 113.
2.

A second component of comparator 1132 receives from memory 1126 a digital V signal representing the corresponding pixel from the previous high-definition frame.Comparator 1132 performs a pixel-by-pixel comparison for each address in the high-definition frame. , generates a digital V output signal representing the difference between each pixel value and the corresponding pixel value of the previous frame when the difference exceeds a set threshold. This difference signal is transmitted to the data buffer 11 via the input signal 4-1134.
36 and at the same time, the switch 38 applies the corresponding address to the address buffer 1140. Switch 11, 1138 is interlocked and motion detector 1146 is coupled to the sharpness limiting signal of the output of IIIM 1106.
Idj of the output of comparator 1132 in relation to the signal from
It is controlled by an AND gate 1142 according to the elementary difference. As described above, the definition limit signal of the previous frame stored in the memory 1126 is compared with the high definition signal of the 7 frames at that time every 1i1ii element, and if there is a difference between them, this is used together with the corresponding address of the data. stored in the buffer. It can be seen that the circuit described above is itself in the form of a motion detector in which the motion of a portion of the image between frames causes the output of comparator 1132 to detect motion in response to a low definition signal. Note only if the vessel shows no movement, tl! Because of this, the high group E! of the image causes the movement detected in the low group brightness g! Movement of the AIIt portion causes information storage in data buffer 1136. On the other hand, the total motion of the portion of the image that can be detected by the motion detector 1144 is 51
Prevent data storage in the filter 136.

In the wide flat part of both houses containing only a small part of the high frequency m part, the # of the bandwidth limited signal stored from the previous feed V
The J rock is the same L as the pixel of the high group 1311 variable signal to be compared.
Therefore, there is no output from comparator 1132. Therefore buffer 1136K stored data and buffer 1140K
The corresponding address to be stored is a still image, such as between two consecutive frames.

This occurs only for addresses where there is high frequency detail that exceeds the ability of the bandwidth reduction signal to resolve. The storage of data in the buffer 1136 and the corresponding address storage in the buffer 1136 occurs during the valid portion of each water column of each frame. During the blinking period, the switch 1101 is switched on, including during the vertical blinking period as required.
3.1118 is flipped to its opposite position by the switch control circuit 1122, and the buffers 1136 and 1140 supply data in parallel format to the parallel to serial converter 1124K;
Convert to serial format. This serial high-definition information is sent to transmitter 111 and antenna 1116, and is also supplied to corresponding data buffers 1148 and 1150 via serial-parallel conversion 51146 of high-definition update circuit 1119. At this time, the switch control circuit 1122 returns the switches 110B and 111+3 to the illustrated positions so that the band limit information is sent to the transmitter 1114 and the antenna 1116 again, and simultaneously applied to the input of the adder 1124 in digital M format. Because the incoming bandwidth limit signal steps pixel by pixel through the frame of incoming information, the address generator 1128 also performs a tl! The signal from the adder 1124 is stored through the corresponding address of the adder 1126. When the address generated by generator 1128 reaches the first address contained in buffer 1160, exclusive OR gate 1152 detects a match and closes input gate C (not shown). The data buffer 1148 and address buffer 1150 are energized by the clock bus and added to jE! The 42 inputs of xxz4 are supplied with a signal representing the difference between the pixel of the sharpness limit] signal and the high definition pixel of the previous frame. Adder 1124 sums these up and records them as part of the current frame.
i! B 1126 Generates a new pixel to be stored at the corresponding address. .

At the same time, a new address appears at the output of buffer '151150, which means that the last address is
This is the address of the sharpness reduction pixel that corresponds to the sharpness pixel. When that second address is reached, exclusive OR gate 1152 again closes switch 1154 and corrects the stored sharpness reduction signal value to make it correspond to the brightness equivalent signal. This process is repeated for the entire frame until, at the end of the frame, the pixels in memory 1126 accurately represent the static portion of the image with high definition.

First few frames of a still scene containing high-detail information of feces 1-
Medium VCMIH5xx36 may overflow. This overflow is detected by the overflow detector 11.
56 detects and generates a threshold pleasure groaning signal, which is sent to the comparator 1.
The suppression level of the difference that is considered to be significant when applied to 132 yft
increase. This reduces buffer overflow. The details of comparator 1132 and its threshold function are described below with reference to FIGS. 11b and 110.

#b Sometimes, starting from a blank feed V, the first frame of bandwidth limit information is stored in the storage 1126 at 4.2 MH
Provide an image corresponding to the z-bandwidth. In other words, terminal 11
01Tlc applied high definition signal contains a large amount of detail (although it provides standard definition -1 image).

During the second frame, buffer 51136.11401c is provided with difference information that is provided to high resolution update circuit 1119 during the next blinking period. Following the scene change, the information stored in memory 1126 during the <3 frames begins to be updated with high-resolution information such that as long as the scene remains still, the stored signal represents the l1lj image in all its details. If a display monitor can be coupled to the output of the frame store 1126, the detail information will be focused after the standard definition painter of the scene appears for the first two frames.

FIG. 11b shows a simplified digital V for understanding the comparator 1132.
Details of comparator 1158 are shown. 1160 (in the figure, an 8-bit or 8-person OR gate) receives the outputs of the 8 individual exclusive OR gates. (Each exclusive or game) 116
2 to 1166 have two input terminals. The first input terminal of 1162 is coupled to the most significant bit (MSB) of one of the 8-bit digital V words to be compared, and the input terminal of @2 is coupled to the other MSB of the digital V word to be compared. has been done. Each gate 1164-11
The 660 input terminal is coupled to the particular significant bit of the digital V word to be compared, and the 11615 input terminal is coupled to the least significant bit (LSB). Each exclusive-OR gate produces a high level output signal unless its two gates match. The output signal of the OR gate 1160 will be high since the output of at least one exclusive OR gate will be high V and V unless there is a match for the bits of the input word, and the output signal of the OR gate 1160 will be high (or gate only if all pairs are the same).
The output signal of 0 becomes low and becomes VV. Naturally, the number of exclusive-OR gates is equal to the number of bits of the words to be compared.

FIG. 110 shows digital V comparator 1132 in block form. As shown, the general shape is the same as comparator 1158, but each comparator 1132
3 bits (as many as the number of bits of the digital word to be compared) combined in the path to the exclusive OR gate
4 points! To! 151168-1112 and similarly arranged inverted three-state buffers 11'74-1 for the second word.
Contains 118. The output terminal of each three-state driver 4b is provided with a pull-up resistor coupled to a positive voltage source.

Each buffer can generate a high impedance state at its output terminal by passing a high or low level V input at its input terminal to its output terminal, or by energizing a control bus to a low V state. can. The control bus of driver 116 and 1114 is 1169, and driver 11'70, 11176
It is 11715, I, SB body charter 1172.11
18 is represented by 1113. In the high impedance mode, the output of each driver is pulled up to a high level by its associated pull-up resistor to form a binary 1. When the control bus is pulled down to low V, its attached driver pair becomes high impedance, and its output is pulled to high V, producing a pair of drivers a1; An exclusive-OR gate coupled to the output of a pair asserts a match between the two bits, so that the output of the exclusive-OR gate is low regardless of the actual state of the bit applied to its driver input. become. In this way, the control bus 1 for LSB
When 173 is pulled low to V, exclusive-or gate 1166 always finds a match on the LSB of the two words;
The change in Ij[ of that bit is ignored when making the comparison.

By controlling the number of bits that are forced into the artificial 1 state, the number and validity of the bits that are being compared can be changed and the threshold set can be moved accordingly. In FIG. 110, the MSB drive line combined bus line is pulled to high V by resistor 11-11 so that the MSB of the digital V word is always compared. The I pond control bus is controlled by a series of comparisons 61188-1192.

The 41 power of each ratio voltage generator is represented by 1196 points and is connected to one point on a resistive voltage divider connected in parallel with the pressure source.
The second manpower is both coupled to capacitor 11 and 4.

This capacitor 1186 is the charging resistor.
A transistor switch 1182 for discharge is coupled to the
The transistor switch 1182 is the data buffer overflow @d''a1158 in Figure 11a.
It is punched by 80.

Exclusive OR gate 11100-1110B, OR gate 11120-11128% AND gate array 11130
The first comprising ~11138 and 11140~1114B
The remainder of the circuit of FIG. 10 is configured to complete the subtraction circuit, thereby extracting the digital M-word (high definition signal) applied to drivers 1168-1172 from three-factor driver 1.
The negative V word (memory image signal) applied to numbers 11 to 1118 is subtracted and exclusive or game) 11100
An N-bit parallel output signal representing the difference is generated from .about.1110B.

In operation, an overflow of the buffer 1136 during a scene change causes an output signal from the dip detector 1156, which triggers the single-shot multi-voltage regulator 80 to discharge the capacitor 1184 at the pace of the switch transistor 1182. Apply a drive timing pass of sufficient duration. When capacitor 11B4 is absent, ratio 452 1188
~1192 responds to each control bus 1113~117.
5t&: Low voltage state, drive, 3-state driver MSB
All but one are placed in their high impedance state.

Due to the pull-up resistance of the driver output, all driver outputs other than MSB are in an artificial state, and the high definition signal and fatt
Ignored in comparison with sharpness limit signal. Therefore, the data buffer 11!1s6 stores only the maximum high-definition variation "H". When the capacitor 11B4 is charged, the first comparator 1192 that controls the %2M5Bill!If Generates a forming pressure and drives the driver 11 f0
゜1176 WE 2 M S of the word being compared
Through B, more details than just the MSB can be stored and finally transmitted. As time passes, the comparators 1188-119 until the LSB is included in the comparison.
The remainder of 0 sequentially lowers its busbar, pulling vVc down.

FIG. 12 is a simplified block diagram of a television receiver 1 which receives and displays a broadcast high-definition signal subjected to sign ratioing using the configuration shown in FIG. 11. In the figure, the upper left antenna 1210 receives multiple broadcast signals and
x, the tuner selects one broadcast channel lv from these signals and down-converts the desired signal t-filtered to an intermediate frequency (F).

This craft? The signal is applied to an amplifier 1212, where it is further amplified and applied to an image detector 12141c, where it is demodulated to generate a baseband video signal together with an intercarrier audio signal, as is known in the art.

The intercarrier audio signal is selected by intercarrier frequency amplifier 1216, filtered and amplified to produce audio [lI4
1218 to generate baseband audio No. 18. This baseband audio signal is applied to speaker 1222 via an amplifier and controller shown at block 1220. Further, the detected luminance signal output from the detector 1214 is applied to the automatic gain side (!Kl(AGO) delogimer 1224 to generate an AGO signal, which is applied to the tuner 1211 and the amplifier 61212 to generate an interposed signal and The baseband video output signal from the detector 1214 is also applied to a sync separator D1226, where various sync signals used throughout the receiver are separated. A burst gate 122B is coupled to the output of separator 1226.

A subcarrier H that can carry the burst signal in the form of AFPCv-de
(So) Passed through regenerator 1230. The frequency interleaved luminance and chrominance portions of the signal at the output of detector 1214 are separated by a chrominance separator 1232, which may include an A-type filter. The chrominance section receives the carrier signal from the reproduction 51230 and receives the chrominance cI.
The signal is applied to the L modulator 1234, and demodulates the color difference signals such as Q, Ql, etc. During this process, the Q signal is applied to matrix 1235K, where it is combined with the reconstructed high definition luminance signal Y to form the R, G, B signals.

The signals R, G, and B are sent to the video tube 1 via the video drive stage 1238.
240. Risk is scanned in the picture tube 1240 by a water deflection winding @1242 driven by a horizontal deflection circuit 1244PC. 9 Star Tare 1! The component is generated by a vertical deflection winding 1246 driven by a conventional vertical deflection circuit 124. Vibration during vertical deflection is introduced by a vibration signal button which is multiplied by a normal vertical IIIA tooth wave by a vibration generator 1250 which is synchronized with the aid of a subcarrier.

The separated luminance signal output from separator 1232 is sent to encoder 1.
The signal is applied to a high definition update circuit 1252, which is similar to the 1000 update circuit 1119. The update circuit 1252 is operated by a switch controller (not shown) for switching between the change signal enable signal and the blinking position.
-11154. In the active position, the separated luminance signal is applied to the ADCxz5a, where it is compressed, digitized and filtered and applied to the input of the digital adder 1258, and via the switch 1260 to its second input. It is summed with the applied high definition difference signal. The summed signal is stored in a 1060 line frame store 1262. The address at which the incoming signal is stored is set by address generator 1264 synchronized by the signal from separator 1226. The stored luminance signal is D A 0126
B periodically to generate a high definition analog luminance signal and apply it to matrix 1236.

During the blinking period, switch 1254 provides a Y signal containing high definition update information, along with the address to which this update information is added, to serial to parallel converter 1210 for conversion to parallel form and to data buffer 1212 and address buffer 1214. Apply. During the next active video period, switch 1254 is switched to the upper position and the sharpness control image signal is applied to digital adder 1258 while address generator 1
264 generates an address corresponding to the address of the video signal stored in the memory 1262. Exclusive OR Game) 12'76Fi The address appearing at the output of the address buffer 1214 at that time is compared with the address of the occurrence 51264 at that time, and when this matches -, the switch 1260
Close. This also energizes buffers 18 2 and 12-4 from each path C (not shown) to clock one pixel and one address of difference data through each buffer, respectively. Switch 1260 then opens until the address of the output of buffer 12'74 and the current address of generator 1264 match. Gate 12g 6 continues to provide the high definition update difference signal stored in data buffer 12'72 to summer 1268 at the proper address throughout the frame. Therefore, the signal stored in memory 1262 is the signal tl! of encoder 1100. 112a. As mentioned above, the encoder 1100 stores the standard sharpness signal for the first frame in the memory 1126 after the scene emerges from the blank risk, and gradually improves the resolution of the fine parts of the painter's still part +lJ degree. As a result, Uke 11!111
1200 provides a standard sharpness-f image following the blank risk when receiving high-definition detail, and also progressively improves the resolution of the high-definition portions of the scene. The subjective effect is that the static portions are brought into focus gradually but not so slowly that it is obtrusive to the average viewer. Risk areas containing motion do not have high definition details.

Embodiments of the pond of this invention will be obvious to those skilled in the art.

For example, one high-definition imager may be used to generate the high-definition sI& signal, and three separate high-definition videocons may be used to generate the low-definition color signal. Also 1
It is also possible to use MHz color signals by mixing the signals derived from the green-responsive DffSmcon, red-responsive and low-response one semi-definition videocon. Although the above embodiments have mainly been described with respect to the NTSO standard, this invention also applies to the PAL system and 81! ! Other standards such as the GIAM system may also be applied. The zigzag deflection may be generated by a separate winding and generator, or by applying an oscillatory frequency signal to the vertical deflection winding in the form of a nominal sawtooth signal. The scanning vibration of the camera can be generated synthetically by performing 1050 vibration-free scans in one frame, writing this into a frame memory, and reading it with an address generator that sequentially selects pixels from each adjacent line.

It is also possible to use an analog type function equivalent to the function explained for the digital V type. In particular, a charge-coupled device may be used for the frame memory rather than random access memory (RAM).

It is also possible to use progressive or interlaced scanning and to have the frequency at which the memory is interrogated be different from the writing frequency.

The functions described in the analog embodiment can also be performed digitally. In particular, a logic circuit that controls the three-state driver of FIG. 11 depending on the number of specific counts may be used for a counter that is triggered by the output of the overflow detector 1156 and counts the subcarrier θ size v.

In the above embodiment, only the tri resolution was improved.

The same method can also be used to improve the clarity of color difference signals.

However, in this embodiment, US FOC! for standard definition television! II standard is used, and in this FCCWArs 1
- A bandwidth of 5 MHz is possible, but in this case the bandwidth of the color difference signal engineer is aooKE (z K).

Fully utilizing standard sharpness (!Sm quasi) to improve color resolution reduces the need to relatively improve color resolution using this invention.

In the dual-purpose high-definition television system described above, the scanning spot of the camera PC (FIG. 4) is vibrated to double the high-definition resolution in both the vertical and horizontal directions.

The transmitted wider bandwidth signal is also used for standard definition TV receivers. The effect of the narrow bandwidth of this receiver is to average the signals of adjacent pixels both horizontally and vertically. In high-definition, wide-bandwidth television receivers, the scanning spot is synchronized to the vibrations introduced by the camera. This spot oscillates at a frequency of 72 or an odd multiple of the horizontal scanning frequency, so that a complete high-definition v''P star of pixels is formed over four consecutive feeds.

A disadvantage of spot oscillations at odd multiples of 1/2 the horizontal line frequency is that certain scanning graphics on the television display surface become visible to the viewer and can be distracting.

When the spot is vibrated at an odd multiple of 172 of the horizontal frequency, the phases of the vibrations on four consecutive scan lines of a given feed V differ by 180°. Therefore, the traversing structure displays visible high-definition modulation in the spaces between adjacent lines of the same field, giving the appearance of an array of superimposed black dots in one image. On the other hand, V-do's Sekil! J'f: The scan line with is over the black space of the previous feed V, so the array of black dots appears to move along a line of K 45° in either the vertical or horizontal direction or in any of the four directions.

This problem associated with such vibrations will be explained with reference to FIG. FIG. 13(a) is a schematic diagram of the scan line structure.

The vibration phase on the adjacent scanning line of a given buoy V is 18
Since they differ by 0°, the scan line structure appears as a visible high frequency modulation of the black spaces between each line, shown as black diamond shapes 20. This black figure appears diagonally across the screen and is eye-catching to the viewer.

If the starting frequency of the spot is selected to be an even multiple of /2 of the line frequency, a line pattern will appear on the screen. However, since not all of the pixels of the high-definition television camera are scanned, a complete resolution of the screen is insufficient.

The vibration pattern in Figure 14a vibrates at an even multiple of 72 of the horizontal line frequency, or 2nfH/2, and each 4 feet V.
On the line representing do-jun-wai, 2.3, 4 (the starting point on the line is arbitrary)
It forms an 11-band pattern.

This single buoy is schematically shown in FIG. 13(1)). The black part of this herringbone (tongue) is completely filled in with the next feed V, and there is no movement of the black dot array in Figure 13(a), but the complete high group gII The beam cannot scan all the pixels of the television.

FIG. 14b is a vibration I (tan) that erases the figure in FIG. 13(a) and scans all pixels of high definition (risk).

In Figure 141), the vibration frequency is an even multiple of the horizontal line frequency /, a, C, that is, znfH/2), so vibration! (P in field 1.)

P+l; P-)-4, p+a) and that of the frame (
Field 2 P+2%p+a; P+6. P+1)
are in phase. To provide high definition television risk dot interlacing and full scanning, the vibration phase is reversed from frame to frame, and such scanning results in a completely filled HE II bond pattern across two frames.

In Figure M14b, the high-definition camera 9 in Figure 4 (modified as in Figure 1 δ) detects the pixel at the vibration frequency ti'.
o, the sampling frequency of the pixel is "'
So or 1820 fHK. However, fH is the horizontal line scanning amount H, and the integer 1820 is selected so that the sampling frequency is eight times the color subcarrier frequency. The phase of the sampling button is inverted every frame l'), and the pixels 610 . 612.
Each pixel including 614, 616, 618, . . . is searched sequentially. #! In-phase scanning lines are sequentially formed by a zigzag path drawn with a risk of oscillation at an even multiple of 172 of the scanning frequency a[r. For example, the ■ mark #J element 610.612 on the nth line of the first buoy V in the first frame,
The pattern 614 is the ■ mark pixel 62 of the next n+1st line.
It is physically the same as 0,622,624. When the first feed V is finished, the second interlaced feed V (2) is scanned, and the pixels 626, 628, 630 of the line q that jumped between the ntI-th and n+1#-th lines are timely scanned. be explored.

mn during the first feed M field (3) of the next C second) frame
× mark pixel of th gravel 532.634, 636.638
... is searched, the x-printed pixel of the n+1st line (
(unnumbered) is explored. In the second field (4) of the second frame, the x of the nth 4-141st line of that frame is
The X-print pixel C (unnumbered) on line q at the position corresponding to pixel a1 is searched. X of Q2 explored during this second frame
The printing pixel size is completely different from 1050M high definition.
It can be seen that tWJ details are constructed. As mentioned above, according to the present invention, the risk of being scanned at an even multiple frequency can be solved. To make it sufficient, the phase of vibration No. 16 is reversed every 7 frames. If wk dynamic multiplier signal phase is not inverted, pixels 632, 634, 636% 638 of line n are 7v-m1
Pixels 610, 61ja, 6 instead of being searched every time.
14,616 will be explored every frame. By inverting the vibration signal phase every other frame.

Complete solution when using an even multiple of 172 of the line scan frequency @
You will get a degree of painter.

This phase inversion will be explained regarding the 15th factor. In order to invert the phase of vibration scanning, the camera shown in FIG. 4 is modified and a switch 2 is installed between the vibration signal generator 28 and the auxiliary deflection winding 1as16.
1 and an inverter 29 are inserted. The switch 21 operates at the frame frequency, that is, 1/2 of the vertical feed V frequency d, that is, rv/a, and the signal thus extracted from the generator a2B is auxiliary via the inverter, Q9, and the conductor 31 alternately. It is supplied to the deflection winding 26. Therefore, the phase of the vibration signal is inverted at the Hun-go frequency. As an example, the 15th
The vibration signal generator 28 in the figure is 14-3 MH2i (41
'sc) signal is generated.

In tlE13 to 16, the high-definition component is vertical water≠
1 shows a method for generating a high definition television signal that includes portions originating from both ends of the screen. Bandwidth limited channel A
For transmitting and receiving High Definition Television No. 16 over /, the description of FIGS. 1O to 12 may be referred to.

This description describes a transmitter that receives a high definition #XX flaw signal, a chrominance signal, and a synchronization signal and generates a dual-purpose signal for transmission over a bandwidth limit≠Janne V. The high-definition components of the still part of the painter are hidden within the vertical and horizontal blinking period 1lfl. Also described is a high definition television receiver suitable for receiving high definition signals transmitted in this manner.

Figure 16 shows a high-definition color television generation system in which water scanning is performed in a linear manner using a single linear storage device to vibrate, and a progressive scanning camera signal is digitally processed to provide a composite vibration scanning signal. FIG. 2 is a partial block diagram of the method. 17th
19 to 19 are used to explain the operation of the high definition method shown in FIG. 16. Figure 1'7a is a high-definition television camera 912
Part of the risk of 02 is shown, Sagra star row, 砿A
There are pixels A1 to A1820 in the row B, and pixels B1 to B1820 in the Sagra star row B (same as below C). The high-definition television camera 1202 operates at a frequency four times the horizontal line frequency of the standard-definition camera (ie, 4fH) and scans 1060 scanning lines per feed V field. The signals Y, E, and Q are mixed in the camera path 1204. These signals are clocked at a frequency equal to 1/1 of the hand scan frequency of camera 1202 to pass every second line two at a time. That is, feed Vdo 1, 3 and human tlc17b
In the continuous 4-feed V-domain in the figure, during odd-numbered feed V-feeds of the pond in the cape star, signals from M (1, 2), (5, 6), C9, 10) etc. are passed (alternating line pair game) ) 1206. In Figure 1'/b, the solid line is Ge) 120
6 shows the lines transmitted through.

The dashed line indicates the line where transmission is blocked.During the vertical scanning of feed V2 and the following even-numbered f . The signals R, G, B, and Q are scanned at high speed so that they only exist for 50 times, but have a bandwidth eight times that of the standard sharpness signal (NTSO). This 8-fold increase is based on the fact that the high-definition signal has four times the horizontal line frequency and twice the resolution If (high frequency content) of the standard definition signal. Therefore, to sample Y, H, and Q with a t14 number equivalent to four times the color printing carrier frequency (C, that is, 4 fsc).

Its sampling frequency is 32 times the color subcarrier frequency (
In other words, it should be 32 fsq).

Signal Y1, Q is analog/digital V converter CA/D
)121L 1214.1216 converts from analog to digital. Since the sampling frequency is 3nfsc, the analog delita V converter must also operate at this frequency. Therefore, K is 1212.12 for each block.
14. A high-speed analog-to-digital converter can be constructed by using a plurality of analog-to-digital converters for the IJ16 and mixing the data to Wh at a high data rate.

FIG. 18 is a timing diagram showing a signal sequence of the high definition method of tIE16. Timing diagrams 18a, 18
e.

181 accepts the output of the analog/digital means 51212, and connects the up line 2 to the gate 1206 through which the matte is passed alternately in two wooden groups.
Gaps in the book are generated in chronological order.

The sign ratio of the composite signal of the signal source by digital means is aided by sampling at an integer multiple of the color subcarrier frequency, for example 4fsc. Again in Figure 1'Fa, the vertical I/O direction shown in each sub-pixel corresponds to the wk motion of frequency 4fsc and the sf'soD high definition image. The phase correction of the sub-pixel of the high definition television set shown in Fig. 1'Fa is within the standard definition bandwidth (i.e. 4.2 ME (z
) must be allocated in such a way as to ensure compatibility with a primary electric clarity receiver that rejects waves.

To provide accurate phase alignment, the sampled signals r, y, and q are combined in a composite matrix 121 days to produce a signal Y+Q representing the sundae occurring at each +1 position of 0', 45° 90' 5315° of the color printing carrier fsq. ,,te+/-(work+Q,),Y÷work,te+,be1
(Knee Q, enter Y-Q, Y -/v'i (work + Q,),
Y-work, Y-1/v/2 (knee Q, ) is formed. 32
A composite output signal produced at a frequency of fso is selected by a selection switch 1220 switching at a frequency of 32 fsc, producing two outputs on conductors 1222 and 1224 that differ by 180 degrees of carrier phase. These signals are four times the standard visibility line frequency (i.e. 4fH)
Around a! Each line occurs in number and consists of samples taken from pairs of alternating lines with a time gap between two alternately drawn rocks. Switch 1226 operates at the standard sharpness horizontal line frequency (i.e., fH) to set the TV to high definition 1, which corresponds to every 311 lines of standard group 94 degree television! /Inverts the color subcarrier every Dan line number. For example, in FIG. 11a, the phase of the sump V is inverted between fiB,0 and F2O.

Samples are saved every other VC by gate 122, and odd samples V, Al, A3 . A5...Bl,
B3. B5...01,03, C5...Dl.

D3, D6... from one (odd number) output, I! Four samples A2, A4, A6...B2. B4. Baho・
・02,04. Oa...D2. D4%D6... are sent from the output of the other (g!% number). The signal passing through 1228 is fed by a switch xxrsoVcf#a which operates at a frequency equal to four times the horizontal frequency, or the camera's water hand scanning frequency. rV
/2) to perform illuminance inversion for every other frame necessary to obtain a complete solution.

The delay device 1251O output and the conductor Ia 1234 are switch/+1
236 (operating at 32 fsq), which causes the samples to be connected to the delay line 1231 and the conductor.
[1iii!
Mix I by vibration.

Game) 11128% switch 1a30.1235! ,
The operation of the delay device 1231 and the switch 1236 is
This will be explained with reference to FIG. 19. In FIG. 19, the AND gates 150j 1504 each have one input 1506, 1508 connected to an input conductor 1229, and the other input 1510, 1512 connected via a switch 1514 to a clock 1516 operating at a frequency of 32 f:Bc.
It is connected to the. Switch 1514 is clock 151
Antenna operating on frequency 17 of 6) 1501.
Timing diagram 18 when 1504 is opened alternately and #h is operated.
The samples V from the switch 1226 shown in a are taken out alternately to the outputs of the AND gates 1502 and 1504, and the odd samples V are taken from the output of the AND gate 1504 to the switch 12.
32, the VIk number Sv is applied from the output of AND gate 1502 to the other input of switch 1232. Therefore, in field 1 of frame 1 of any scanning order, switch 1232
That is, when the switch 1232 is tilted to the left), when an odd number sample V is supplied to the delay device 1231, an odd number #i, for example, A1. Odd number pixels such as A3 are switches 1230.12
32 to the delay line 1231, the y4 number line, for example B2.
Even number pixels such as 84 are in (-11230).

1232 to conductor 1234. Timing diagram 18k) shows the sun 19 column with delay 1231 facing conductor 1234, switch 1236 is shown in timing diagram 18
The sample V from the delay device 1231 and the conductor 1234 is arranged so that the even sample V is sandwiched between the odd sample V so as to correspond to 0.
It functions to mix.

The next field, the field of frame 1! In I, the line 0. Odd number sand V from G etc. is delay device 1
Even number samples V from @D, El, etc. are applied to ja31 by switching conductor 15134K (timing diagram 18f#
), SWIN+12S6 is Ip4 number S V or D
ja, B4...D18S! O, etc. are sandwiched between the odd samples V''t, ie, Ox, C3 .

For the next field, which is the first feed of 7V-2, the switch 1232 is turned to the right @VC, the even samples l are sent to the delay circuit 1231, and the odd samples V are sent to the conductor 1134.
K is now applied. Therefore, even samples V from lines AlE, etc. are switched to delay 51231, and odd samples V from @B, F, etc. are switched to conductor 1234 (timing diagram 1
8j). Switch 1236 is set to G]%V or A2. A4. A6 is the number sample V, that is, B1, B
3, B6...B 1819, each sump V is switched so as to produce an oscillating scanning effect as shown in the timing diagram 18k. Alternate samples from this mixed adjacent line are applied to a first-in-first-out buffer C (referred to as a VkF FO buffer) 1238. This buffer 123 is a delay line with space to store one scan line of data (i.e., 181 ao sample y).The data is fed into the buffer 1238 at a frequency of 32 fsc, and at a frequency of 174 of the input frequency, i.e., 8 fB(taken out at 3.

By changing the frequency when data is sent to and from the buffer 1238, the gap introduced by the gate 1206 that passes every other pair of scanning lines in every other field and the gap introduced by the delay device 1231 are removed. be done. Timing diagram 18d, 113fi% 181 is F engineering F
A slow sump V with no gaps is shown being delivered from the O1 & impulser 1238.

These sump pv (output of buffer 123) represent the composite vibration signal. The digital V signal from the buffer 123B is converted to analog in a delta V to analog converter 1242 and filtered to filter 1 with a sin x/x impulse V response.
242. The filtered signal can also be transmitted as an analog high-definition television composite vibration scanning signal in the manner described above with respect to FIGS. 101A-12, which has the advantage of being compatible with standard definition image reception.

In order to ensure that the quality of the correct answer accuracy display is not compromised by scanning structure products caused by spot vibration, the second
The line scan television monitor 1602 will be described with reference to FIG. The monitor in Figure 20 shows Ryotsu in full resolution for each display field with progressive scanning horizon risk 1606.
is given. In this method, each 1ij element transmitted by an excitation button forms a complete high-definition television frame C.
That is, the four NTSO frames (V-frames) are stored in the appropriate locations in the random access frame store 1604 in sequence until the displayed S@ is completed. Frame memory 1604 is 105
This is a 0-line memory device. This frame converter 1604 is attached with a built-in address generator 41608 and a read address generator 1610. This configuration is achieved by storing a 1050-line high-definition frame. Eliminate sub-pixel IJ sharpness. Information is stored at the proper ffLat at the frequency of the incoming signal by controlling the intrusion address generation 41608 with the aid of signals derived from the burst divider 1612 and the sync separator 1614. On the read side, a local sync generator 41616 determines the read speed and controls the deflection generator. Although this fje acquisition speed is in principle independent of the frequency of the incoming signal, it can exhibit the advantages of progressive scanning (i.e., not interlaced scanning).

The normal read sequence is synchronized with the imprinting speed by delayer 161B. If the delay is at least 3 FeeV
Framed tJio1604 is written and the 14th b
The first two lines in the diagram are now filled. Also, if the high definition frequency is transmitted separately from the luminance component, the highest quality of high definition television with a 3 m moat can be obtained, but NTSO receiving I#! To obtain full chrominance compatibility with the machine, the OK sub-sharp color signal must be encoded onto a 3.aa MHz subcarrier, implying composite transmission.

Framing [Line L instead of a vessel] Figure 21 shows the correct answer for using a vessel. Correct answer II for Figure 21
The IK receiver uses the NTSO method and is designed to scan at 3m and 5114H2 standard sharpness with water ≠ twice the frequency.

A high definition signal in vibration format is received at terminal 1102 . This received high-definition signal is a high-definition video 11
If1'104 is displayed linearly. As shown in Figure 1s21, the display surface is vertically at the frequency of standard clarity.

twice its standard visibility frequency or 2f' in the water direction
Scanned with H. The high definition signal at terminal 1702 is connected to analog-to-digital V converter 1106 and sync separator 1'108.
K: Supplied at the same time, synchronous separator lma08 is connected to terminal 1'1
02 to separate the vertical and horizontal synchronization numbers 48. Water synchronization signal is 2fH phase 1N constant V-de (p L L )
x'7xo! /c is supplied to generate a drive signal of 41[semi-clearness water, twice the number of waves, that is, 2fH. Vertical from the top of the separator 108 (including means for performing an oscillatory scan such that each line is in pairs and displayed between each pair so that the next pair of lines can be interleaved alternately). The drive signal is applied to the vertical deflection winding 12 associated with the tube 1'7t)4.

A double frequency horizontal drive signal is applied at 31.5 KE (z) to the horizontal deflection winding 1 fH, and each scanning line on the display surface of the picture tube 1 fH occurs for a time of 1/2 fH at 31.5 KHz.

The input signal is an odd numbered sample V from one high definition television signal line 3 mixed with an even numbered sample V from an adjacent high definition television signal line 14 in the form transmitted by the transmitter of FIG. be. F engineering FO loose (131'716~1)
22 is used to separate the alternating time-sequential samples V placed in one line of the oscillation signal into two lines of high definition line scanning. The two lines can be displayed in a high definition display surface IIc line scan format, such as the display surface of picture tube 1104.

For example, loose $51'716 ~ l'F22 is 9104? This is a 71/F engineering FO river buffer. One section of this series consists of the following four sections. Analog/digital V converter 1″706
is transmitting the sump V using the transmitter shown in FIG. 16! The heel switch l'/! samples the incoming signal at a high definition frequency, i.e. 8 fsc, which is the number 11. A4 is switched at 1/2 of the line frequency of the conductivity visibility, that is, fH/sa, and the incoming Mizuko #I is alternately buffered 1'/16.111 days and 1120.
1f122 respectively.

Switch F 26 is four times the subcarrier frequency, that is, 4f.
Switch with sc to buffer alternate time-sequential sampling V! 1vxa,
1'' 118 respectively. For example, in FIG. 11a, the first
When the th line is received, if the odd sample of line A is vn then A
l, A3. A3 etc. to the buffer 1116, even numbered samples 1v of line B, eg B2. B4, 86, etc. are selectively applied to the buffer 1118. Buffer 51'/16. When the buffer 18 goes negative, the signal of the odd sample V of the group A is read from the buffer 1 filter 16 in this column. When the buffer 1'16 is empty, a flame wrap or line B is read from the buffer 1'11B. While buffers 16.1 and 18 are being read, the signals of the next line are stored in buffers 1120.1yz2 via switches 171i14 and 1128, respectively. In this example, the second line of buoy Vd1 of frame 1 in Figure 1A includes odd samples from line E and even samples V from line F. Sweets≠1128 is Sweets+l
'F26 as well as 4 times the subcarrier frequency, i.e. 'S
#f1f at O, and the alternating time sequential sampling V is switched and applied to the buffers 1120.1 and 22, respectively.

On the reading side, the signal from the buffer 16.1118 is passed through a switch 1130 operating at the horizontal frequency fd and a switch 1132 operating at the frequency l/, that is, fH/2, to a digital output at 8 fBo. It is transmitted to analog converter 1 34 and converted to analog format for display on picture tube 1104. The analog signal from this digital V/Analog converter i51'l'js4 is processed by the video processing circuit 1'F36t', and is applied to the video tube 1'7'04 via the video tube driver 1138 to provide standard clarity. displayed at twice the horizontal frequency. Switch l'/40 operates similarly to switch 1'730 to alternately switch each line of the high definition signal to elements 1132%l'734. l'F36. l
'738 to the video tube 104 for display. Switch F 32#i is set out of phase with switch 1124 so that when a line is being written to one buffer pair, a signal can be continuously output from the other buffer pair. Teha, M E , F for field 1Vc
117) lines A and B of the frame are read while being written to
The signals are then read from buffers 1720.1?22, while buffers 1'Flf1. l'71B is entered by 6. FIG. 21 shows a line scanning display method for displaying high definition television signals transmitted by type Ila#J.

According to this system, each line aS device 4 with 910 samps V
High-definition display can be achieved with a stand or two line buffers with 1810 sump V. Please note that the system shown in Figure 21 requires a complete high-definition television (7 m) (4 buoys to display IR).

Various modifications will be apparent to those skilled in the art. It is possible to perform the functions described in digital terms in an analog manner, and vice versa, and both sequential scanning and interlaced scanning can be used.

111 IBA explanation of the drawings Figures 1 and 42 show the vertical △ and water ≠ lines on the raster, respectively, Figure 3 shows the optical part of the Cali camera, and Figure 4 shows the camera videocon and circuit. 5(a) and 61 and 6b are diagrams showing the details of the scanning pattern of the camera or high-resolution video tube in FIG. 4, and FIG. 8 and 9 are simplified block diagrams of a television monitor, and the HXO diagram is a simplified block diagram of a dual-purpose high-definition IK television system.

Figures 11a, 11b, and 110 are block diagrams of each part of the high-definition video encoder and broadcasting device, and Figure 12 shows the code ratio of the encoder of Figures 11a, 11b, and 110. Correct answer for broadcasted dual-purpose television signals [Block diagram of e-reception, FIG. 13(a).

(b) is a schematic diagram showing a scanning pattern generated by the method of the present invention; FIGS. 14a and 14b are diagrams showing details of the scanning pattern; and FIG. 815 is modified from the camera and circuit configuration of FIG. 4. A diagram showing the camera 9 and the circuit configuration,
FIG. 16 is a block diagram showing a high-definition signal encoder,
1a and 1b are diagrams showing details of a linear scanning high definition signal data, and FIG. 1B is a timing diagram used to explain the operation of the encoder of FIG. 16.

FIG. 19 shows 1! of the alternate sampling gate of FIG. 16. i
l! FIG. 21 is a simplified block diagram showing a progressive scan television monitor. FIG. 21 is a block diagram showing a high definition television filter using a line memory.

400.1202 meeting...first signal source, 1010.Q.
Second signal generation means, 1olla... Reproduction means, 1
014...Difference signal generation means %1018...g11 transmission/reproduction means, 1206.1220.1226, 123
0SL232. [31, 1ja36 - Pixel selection means.

Patent Applicant A/I/V-Nee Corpo v-vgn Representative Tetsu Shimizu and 2 others Figure 10 Figure 2 Figure 3 = 4 = # = Rumor = # = 滲P + 2 x--x-- x p÷3 Yu = ≠ = # = Yu = X = 4 Furnace = X = Rumor = = * = Rumor =
:X: = Erosion P+6%−−×−−%−−%−−%−−
＋−→←−)G−−−−−−X−−−−′X−−
X p6≠=sha=≠=4〉:X=hiro=×=mig==x
=<Hin≠20=≠X--)(--)e -X--X--X O6b Figure O80 Figure 13 Figure 11 CII Figure 14b Figure 17b Figure 17a Figure 8d M 112 J1384 A5 Bl
+0. ．． 1. ,．． 1. ,．． 1. ,．． 1. ,．． 118 & ao2 o D4 csm l,,,1. ,．． 1. ,．． 1. ,．． 1. ,.

18/ 8IA2113 ＾4IL5A5 Figure 18

Claims (2)

[Claims] (1) a signal source of a first signal representing successive line scans distributed over the field direction of the image on an image; An image display signal generation device comprising: means for selecting pixels; (2) An apparatus for reproducing an image from a signal in which signal samples representing an image along a scanning line are in an interpolated relationship with signal samples along other scanning lines adjacent to the scanning line, the apparatus comprising: a second storage means; a first switching means for switching to supply signal samples alternately to said first and second storage means; and a signal sample obtained from one of said two storage means; An image reproducing device comprising: second switching means for alternately passing sample outputs relating to a scanning line and sample outputs relating to adjacent scanning lines obtained from the other storage means.