JP2012218692A - Electric power steering device - Google Patents

Abstract

PROBLEM TO BE SOLVED: To provide an electric power steering device capable of effectively suppressing a motor current while suitably maintaining stability of motor control.SOLUTION: A second control part calculates a virtual rotational angle on control by executing torque feedback control based on torque deviation Δτ so that an actual steering torque may follow a target steering torque τ*. The second control part calculates γaxis current increase and decrease value η based on the torque deviation Δτ and calculates a γ axis current command value Iγ* by multiplying the γ axis current increase and decrease value η and further executes current feedback control in a rotating coordinate system following the rotational angle on control. The second control part (a current command value calculating part 61) is provided with a current command value limiting part 73 limiting the γ axis current command value Iγ* to be a current command upper limit value or below. The current command value limiting part 73 changes the current command upper limit value on the basis of the torque deviation Δτ.

Description

  The present invention relates to an electric power steering apparatus.

  2. Description of the Related Art Conventionally, some electric power steering devices (EPS) that apply assist force to a steering system using a motor as a drive source include a motor control device that can control a brushless motor without detecting the motor rotation angle. As an aspect of sensorless (resolverless) drive control that does not use such a rotation angle sensor (motor resolver), an addition angle corresponding to the motor rotation angle change amount for each calculation cycle is calculated, and the addition angles are integrated. A method of executing current feedback control in a rotating coordinate system according to the motor rotation angle on the control obtained by the above is proposed.

  For example, the motor control device described in Patent Document 1 calculates an addition angle corresponding to the motor rotation angle change amount for each calculation cycle based on the deviation between the target torque to be generated by the motor and the actual torque. . Further, the motor control device described in Patent Document 2 estimates the motor rotation angular velocity based on the motor current and the motor voltage. Then, the addition angle is calculated using the motor rotation angular velocity as a change component for each calculation cycle.

  In other words, even if the actual motor rotation angle (actual rotation angle) and the control motor rotation angle (control angle) do not exactly match, the brushless motor can be controlled as long as the deviation remains within a certain range. is there. Then, the difference between the actual rotation angle and the control angle is calculated by executing the current feedback control using the control angle obtained by calculating the addition angle by the method described in each of the above patent documents and integrating the addition angles. Can be kept within the range in which the motor can be controlled.

JP 2010-11709 A JP 2010-29031 A

  In the resolverless control using the virtual control angle as described above, as long as the stator can generate the magnetomotive force necessary to maintain the rotational position of the rotor, the control angle and the actual rotation angle are It is possible to keep the deviation in a range that can be stably controlled. That is, by generating a larger motor current, the stability of the motor control can be improved.

  However, by continuously energizing a motor with a large current, its energy efficiency decreases. And since the reliability of the motor may decrease due to the remarkable heat generation of the motor, the improvement has been left as a problem to be solved.

  The present invention has been made to solve the above-described problems, and an object of the present invention is to provide an electric power steering apparatus that can effectively suppress motor current while suitably maintaining stability of motor control. Is to provide.

  In order to solve the above problems, the invention according to claim 1 is directed to a steering force assisting device that applies an assist force to a steering system using a motor as a drive source, and a control unit that controls the operation of the steering force assisting device. And the control means includes a motor control signal output means for outputting a motor control signal, and a drive circuit for supplying three-phase drive power to the motor based on the motor control signal. The means calculates an addition angle corresponding to a motor rotation angle change amount for each calculation cycle by executing torque feedback control based on a torque deviation between the target steering torque and the actual steering torque, and integrates the addition angle. To calculate a motor rotation angle for control, calculate an increase / decrease value based on the torque deviation for each calculation cycle, and calculate the current command value by integrating the increase / decrease value. In the electric power steering apparatus that outputs the motor control signal by executing current feedback control in a rotating coordinate system according to the motor rotation angle on the control, the motor control signal output means sets the current command value to an upper limit value. The gist is to limit to the following and change the upper limit value based on the torque deviation.

  That is, in the motor control in which the rotation angle (control angle) on the control is calculated by executing the torque feedback control based on the torque deviation and the current feedback control is executed in the rotating coordinate system according to the control angle, The higher the followability of the steering torque, the more stable the motor control. In such a stable control state, the motor current required to maintain the stability of the motor control is also a small value. Therefore, according to the said structure, a motor current can be suppressed effectively, maintaining the stability of motor control suitably. As a result, the energy efficiency can be improved and the reliability of the motor can be improved by suppressing the heat generation of the motor.

  According to a second aspect of the present invention, when the torque deviation is in a range exceeding the stable region, the motor control signal output means sets the upper limit value to a higher value than when the torque deviation is in the stable region. The gist is to change.

  According to the above configuration, when the torque deviation is in a small region indicating that the control state is stable, that is, in the stable region, the upper limit value is set to a low value to suppress excessive motor current. To do. And when the torque deviation is in a range exceeding the stable region, that is, when indicating a decrease in the stability of the control state, by changing the upper limit value to a high value and allowing energization of a larger motor current, The stability of the motor control can be improved. As a result, it is possible to effectively suppress the motor current while suitably maintaining the stability of the motor control.

  ADVANTAGE OF THE INVENTION According to this invention, the electric power steering apparatus which can suppress a motor current effectively can be provided, maintaining the stability of motor control suitably.

The schematic block diagram of an electric power steering device (EPS). The block diagram which shows the electric constitution of EPS. The schematic block diagram of a 1st control part. The schematic block diagram of a 2nd control part. The block diagram which shows schematic structure of a disturbance observer. The flowchart which shows the process sequence of rotation angular velocity estimation. The flowchart which shows the process sequence of addition angle adjustment calculation. The schematic block diagram of the electric current command value calculating part by the side of a 2nd control part. Explanatory drawing which shows the relationship between a torque deviation and an electric current command upper limit. The schematic block diagram of an electric current upper limit determination part. The schematic block diagram of an electric current upper limit determination part.

DESCRIPTION OF EXEMPLARY EMBODIMENTS Hereinafter, an embodiment of the invention will be described with reference to the drawings.
As shown in FIG. 1, in the electric power steering apparatus (EPS) 1 of this embodiment, a steering shaft 3 to which a steering 2 is fixed is connected to a rack shaft 5 via a rack and pinion mechanism 4. The rotation of the steering shaft 3 accompanying the steering operation is converted into a reciprocating linear motion of the rack shaft 5 by the rack and pinion mechanism 4. The steering shaft 3 of this embodiment is formed by connecting a column shaft 3a, an intermediate shaft 3b, and a pinion shaft 3c. Then, the reciprocating linear motion of the rack shaft 5 accompanying the rotation of the steering shaft 3 is transmitted to a knuckle (not shown) via tie rods 6 connected to both ends of the rack shaft 5, whereby the steering angle of the steered wheels 7. That is, the traveling direction of the vehicle is changed.

  Further, the EPS 1 includes an EPS actuator 10 as a steering force assisting device that applies an assist force for assisting a steering operation to the steering system, and an ECU 11 as a control unit that controls the operation of the EPS actuator 10. .

  The EPS actuator 10 of the present embodiment is configured as a so-called column-type EPS actuator in which a motor 12 that is a drive source is drivingly connected to a column shaft 3 a via a speed reduction mechanism 13. In the present embodiment, the motor 12 employs a brushless motor that rotates based on three-phase (U, V, W) driving power. The EPS actuator 10 is configured to apply an assist force based on the motor torque to the steering system by decelerating the rotation of the motor 12 and transmitting it to the column shaft 3a.

  On the other hand, a torque sensor 14 is connected to the ECU 11, and the ECU 11 detects a steering torque τ transmitted to the steering shaft 3 based on an output signal of the torque sensor 14. Further, the vehicle speed V detected by the vehicle speed sensor 15 and the steering angle θs detected by the steering sensor (steering angle sensor) 16 are input to the ECU 11 of the present embodiment. The ECU 11 calculates a target assist force to be applied to the steering system based on each of these state quantities, and drives the motor 12 by supplying drive power to generate a corresponding motor torque. The operation of the EPS actuator 10 as a source, that is, the assist force applied to the steering system is controlled (power assist control).

Next, the electrical configuration of the EPS of this embodiment will be described.
FIG. 2 is a control block diagram of the EPS of this embodiment. As shown in the figure, the ECU 11 supplies three-phase drive power to the motor 12 based on the microcomputer 17 serving as motor control signal output means for outputting a motor control signal and the motor control signal output from the microcomputer 17. And a drive circuit 18.

  Each control block shown below is realized by a computer program executed by the microcomputer 17. The microcomputer 17 detects each state quantity at a predetermined sampling period, and generates a motor control signal by executing each arithmetic processing shown in the following control blocks at every predetermined period.

  Specifically, in the drive circuit 18 of the present embodiment, three switching arms corresponding to the respective phase motor coils 12u, 12v, 12w are arranged in parallel with a pair of switching elements connected in series as a basic unit (switching arm). A well-known PWM inverter connected to is used. That is, the motor control signal output from the microcomputer 17 defines the on / off state (duty of each phase switching arm) of each phase switching element constituting this drive circuit. The drive circuit 18 is activated by the input of the motor control signal and supplies three-phase drive power based on the applied power supply voltage V_pig to the motor.

  More specifically, the ECU 11 is provided with a current sensor 21 for detecting each phase current value Iu, Iv, Iw of the motor 12. Note that the current sensor 21 of the present embodiment has a well-known configuration in which a shunt resistor is connected to the low potential side (ground side) of each switching arm constituting the drive circuit 18. The microcomputer 17 of the present embodiment detects the phase current values Iu, Iv, and Iw flowing through the phase motor coils 12u, 12v, and 12w based on the output signal of the current sensor 21 (the voltage across the terminals of the shunt resistor). To do.

  Further, the microcomputer 17 of the present embodiment detects the rotation angle (electrical angle) θm of the motor 12 based on the output signal of the motor resolver 23. In the present embodiment, the motor resolver 23 has a two-phase sinusoidal signal (a sine signal S_sin and a cosine signal S_cos) whose amplitude changes according to the actual rotation angle (electrical angle) of the motor 12 as the sensor signal. A winding type resolver that outputs is used. The microcomputer 17 of the present embodiment executes a current feedback control based on the phase current values Iu, Iv, Iw and the rotation angle θm of the motor 12 to output a motor control signal to the drive circuit 18. Is generated.

  More specifically, in the present embodiment, the motor controller 24 of the microcomputer 17 provides the phase voltage command values Vu *, Vv *, Vw * to be applied to each phase of the motor 12 by executing current control in the rotating coordinate system. A first control unit 25 and a second control unit 26 that calculate (Vu **, Vv **, Vw **), and a PWM conversion unit 27 that converts the phase voltage command value into a motor control signal are provided. Yes. The microcomputer 17 according to the present embodiment is configured to output the motor control signal generated by the motor control unit 24 to the drive circuit 18.

  As shown in FIG. 3, the first control unit 25 includes a current command value calculation unit 31 that calculates a current command value corresponding to the target assist force based on the steering torque τ and the vehicle speed V detected as described above. ing. In addition, the first control unit 25 includes a d / q conversion unit 32, and the d / q conversion unit 32 is based on the rotation angle θm detected by the motor resolver 23, and each phase current value Iu, By mapping Iv and Iw on the d / q coordinate, the d-axis current value Id and the q-axis current value Iq are calculated. And the 1st control part 25 performs the current feedback control in the rotation coordinate system (d / q coordinate system) according to the real rotation angle ((theta) m) of this motor 12, The voltage which should be applied to each phase of the motor 12 The phase voltage command values Vu *, Vv *, and Vw * are calculated.

  That is, the current command value calculation unit 31 calculates the q-axis current command value Iq * as the current command value. Specifically, the current command value calculation unit 31 calculates a q-axis current command value Iq * that generates a larger assist force as the input steering torque τ is larger and the vehicle speed V is smaller. . The d-axis current command value Id * is fixed to “0” (Id * = 0). The d-axis current command value Id * and the q-axis current command value Iq *, together with the d-axis current value Id and the q-axis current value Iq output from the d / q conversion unit 32, the corresponding subtractors 33d and 33q. Is input.

  Next, the current deviations ΔId and ΔIq of the respective axes calculated by the subtracters 33d and 33q are input to the corresponding F / B control units (feedback control units) 34d and 34q, respectively. Each of the F / B control units 34d and 34q executes d / q by executing a feedback control calculation based on the input current deviations ΔId and ΔIq and a predetermined feedback gain (proportional: P, integral: I). A d-axis voltage command value Vd * and a q-axis voltage command value Vq *, which are voltage command values in the coordinate system, are calculated.

  Specifically, each of the F / B control units 34d and 34q sets a proportional component obtained by multiplying the input current deviations ΔId and ΔIq by a proportional gain, and an integral value of the current deviations ΔId and ΔIq, respectively. The integral component obtained by multiplying the integral gain is calculated. Then, the d-axis voltage command value Vd * and the q-axis voltage command value Vq * are generated by adding the proportional component and the integral component.

  Next, the d-axis voltage command value Vd * and the q-axis voltage command value Vq * are mapped onto three-phase (U, V, W) AC coordinates in the d / q inverse conversion unit 35. The first control unit 25 is configured to output the phase voltage command values Vu *, Vv *, Vw * obtained by the reverse conversion executed by the d / q reverse conversion unit 35 to the PWM conversion unit 27. ing.

  On the other hand, as shown in FIG. 4, the second control unit 26 includes an addition angle calculation unit 41 that calculates an addition angle θa (θa ′) corresponding to the motor rotation angle change amount for each calculation cycle, and the addition angle θa ( and a control angle calculation unit 42 for calculating a control angle θc as a virtual motor rotation angle for control by integrating θa ′) for each calculation cycle. And the 2nd control part 26 performs phase feedback command value Vu **, Vv **, Vw ** by performing electric current feedback control in the rotation coordinate system ((gamma) / (delta) coordinate system) according to the control angle (theta) c. It is configured to calculate.

  More specifically, the steering torque τ, the vehicle speed V, and the steering angle θs detected as described above are input to the addition angle calculation unit 41 of the present embodiment. The addition angle calculation unit 41 includes a target steering torque calculation unit 45 that calculates a target steering torque τ * corresponding to the target value of the steering torque τ based on the steering angle θs generated in the steering 2 and the vehicle speed V. The target steering torque τ * calculated by the target steering torque calculation unit 45 is input to the subtractor 46 together with the steering torque τ. The addition angle calculation unit 41 of the present embodiment calculates the addition angle θa based on the torque deviation Δτ obtained by subtracting the target steering torque τ * from the actual steering torque τ detected by the torque sensor 14. To do.

  That is, in EPS that applies assist force based on motor torque to the steering system, the target steering torque τ * is a parameter corresponding to the motor torque (target torque) to be generated by the motor 12, and the steering torque τ is the motor 12. This parameter corresponds to the actual torque. That is, the difference (torque deviation Δτ) between the target steering torque τ * and the actual steering torque τ is a state quantity indicating the excess or deficiency of the actual torque with respect to the target torque. Then, the addition angle calculation unit 41 of this embodiment calculates the addition angle θa by executing torque feedback control so that the actual steering torque τ follows the target steering torque τ *.

  Specifically, the torque deviation Δτ calculated by the subtractor 46 is input to the F / B control unit 47. Then, the F / B control unit 47 calculates a proportional component obtained by multiplying the torque deviation Δτ by a proportional gain, and an addition value of an integral component obtained by multiplying the integral value of the torque deviation Δτ by an integral gain. Calculation is performed as the first change component dθτ of the motor rotation angle in each calculation cycle.

  In the present embodiment, the second control unit 26 is provided with a rotation angular velocity estimation calculation unit 50 as motor rotation angular velocity estimation means for estimating the motor rotation angular velocity, and the addition angle calculation unit 41 includes The motor rotation angular velocity ωm_e estimated by the rotation angular velocity estimation calculation unit 50 is input as the second change component dθω of the motor rotation angle in each calculation cycle. Then, the addition angle calculation unit 41 of the present embodiment calculates the addition angle θa using the first change component dθτ based on the torque deviation Δτ and the second change component dθω based on the motor rotation angular velocity ωm_e.

  More specifically, the second controller 26 includes phase voltage command values Vu *, Vv *, Vw * (Vu **, Vv **, Vw *) used when the PWM converter 27 generates a motor control signal. An internal command value corresponding to *), that is, Duty is input. Moreover, ECU11 of this embodiment detects the power supply voltage V_pig applied to the drive circuit 18 with the voltage sensor 51 (refer FIG. 2). The second control unit 26 is provided with a phase voltage calculation unit 52 that calculates the phase voltage values Vu, Vv, and Vw of the motor 12 based on the detected power supply voltage V_pig and the duty.

  Further, these phase voltage values Vu, Vv, Vw and the phase current values Iu, Iv, Iw of the motor 12 detected by the current sensor 21 are fixed in two phases in the α / β converter 53, respectively. They are converted into an α-axis voltage value Vα and β-axis voltage value Vβ, an α-axis current value Iα, and a β-axis current value Iβ in the coordinate system (α / β coordinate system). Then, the rotational angular velocity estimation calculation unit 50 of the present embodiment is based on the motor voltage and motor current indicated by the α-axis voltage value Vα and β-axis voltage value Vβ, and the α-axis current value Iα and β-axis current value Iβ. Estimate the motor rotation angular velocity ωm_e.

  More specifically, the rotational angular velocity estimation calculation unit 50 of this embodiment includes a disturbance observer 54 that estimates an induced voltage generated in the motor 12 as a disturbance based on the motor model.

  That is, in the block diagram shown in FIG. 5, the motor 12 is represented by the motor model M1 that generates the motor current (Iα, Iβ) based on the motor voltage (Vα, Vβ) and the induced voltage (Eα, Eβ). . Accordingly, the induced voltage as described above is obtained by the reverse motor model M2 having the motor current (Iα, Iβ) as an input, and the subtractor 55 having the output of the reverse motor model M2 and the motor voltage (Vα, Vβ) as inputs. A disturbance observer 54 that outputs estimated values (Eα_e, Eβ_e) can be formed. For example, if the motor model M1 is “1 / (R + pL)”, the reverse motor model M2 is “R + pL” (where R: armature winding resistance, L: inductance, p: differential operator). Then, the rotational angular velocity estimation calculation unit 50 of the present embodiment estimates the motor rotational angular velocity ωm_e based on the induced voltage estimated values (Eα_e, Eβ_e) output from the disturbance observer 54.

That is, the induced voltages (Eα, Eβ) in the α / β coordinate system are expressed by the following equations (1) and (2), respectively. In each equation, “Ke” is an induced voltage constant, and “ωm” is a motor rotation angular velocity.
Eα = −Ke × ωm × sinθ (1)
Eβ = Ke × ωm × cosθ (2)
Further, the following equation (3) is obtained by solving these equations (1) and (2) with respect to the angle “θ”. In the formula, “arctan” is “arc tangent”.

θ = arctan (−Eα / Eβ) (3)
Therefore, the motor rotation angle (θm_e) can be estimated from the estimated voltage estimated values (Eα_e, Eβ_e) output from the disturbance observer 54. Then, the rotational angular velocity estimation calculation unit 50 of the present embodiment calculates the motor rotational angular velocity (estimated value) ωm_e by differentiating the estimated value (θm_e) of the motor rotational angle.

  Specifically, as shown in the flowchart in FIG. 6, when the rotational angular velocity estimation calculation unit 50 estimates the induced voltage of the motor 12 by the disturbance observer 54 (Eα_e, Eβ_e, step 101), first, the induced voltage estimation is performed. Filter processing is performed on the values (Eα_e, Eβ_e) (LPF: low-pass filter, step 102). Next, the rotational angular velocity estimation calculation unit 50 estimates the motor rotational angle (θm_e) from the induced voltage estimated values (Eα_e, Eβ_e) by using the above formula (3) (rotational angle estimation, step 103). . Then, the motor rotation angular velocity (estimated value) ωm_e is calculated by differentiating the motor rotation angle (θm_e) (estimation of rotation angle, step 104).

  The rotational angular velocity estimation calculation unit 50 of the present embodiment is configured to output the motor rotation angular velocity ωm_e to the addition angle calculation unit 41 as the second change component dθω of the motor rotation angle in each calculation cycle. (Step 105).

  As shown in FIG. 4, in the addition angle calculation unit 41 of the present embodiment, the first change component dθτ of the motor rotation angle based on the torque deviation Δτ calculated by the F / B control unit 47, and the rotation angular velocity estimation calculation unit The second change component dθω of the motor rotation angle based on the motor rotation angular velocity ωm_e calculated by 50 is input to the addition angle adjustment calculation unit 58. In this embodiment, the rotational angular velocity estimation calculation unit 50 calculates the sum of squares of the induced voltage estimation values (Eα_e, Eβ_e) output from the disturbance observer 54 (Esq_αβ = (Eα_e) ^ 2 + (Eβ_e) ^ 2, where “^ 2” indicates a square), and the induced voltage square sum Esq_αβ is output to the addition angle adjustment calculation unit 58. Then, the addition angle calculation unit 41 of the present embodiment changes the calculation mode of the addition angle θa based on the value of the induced voltage square sum Esq_αβ.

  More specifically, the addition angle adjustment calculation unit 58 of the present embodiment compares the input induced voltage square sum Esq_αβ with a predetermined threshold value (E0). When the induced voltage square sum Esq_αβ exceeds the threshold value (E0), the addition value of the first change component dθτ based on the torque deviation Δτ and the second change component dθω based on the motor rotation angular velocity ωm_e is defined as an addition angle θa. When the value is equal to or less than the threshold value (E0), the first change component dθτ based on the torque deviation Δτ is set as the addition angle θa.

  That is, the motor rotation angular velocity ωm_e having one calculation cycle as a basic unit has an equivalent meaning to the motor rotation angle change amount per one calculation cycle. The estimation of the induced voltage based on the motor current and the motor voltage using the disturbance observer 54 as described above ensures higher accuracy in the high-speed rotation region where the induced voltage increases.

  In consideration of this point, the addition angle adjustment calculation unit 58 of the present embodiment compares the estimated voltage square sum Esq_αβ and the threshold value (E0) with the estimated rotation speed ωm_e of the motor 12 based on the rotation state of the motor 12. It is determined whether or not it is in a high-speed rotation region where the estimation accuracy that can be used as the second change component dθω of the rotation angle is ensured. The second variation component dθω based on the motor rotation angular velocity ωm_e is used only when the required estimation accuracy is in a high-speed rotation region.

  Specifically, as shown in the flowchart of FIG. 7, the addition angle adjustment calculation unit 58 firstly includes a first change component dθτ based on the torque deviation Δτ and a second change component dθω based on the motor rotation angular velocity ωm_e, The induced voltage square sum Esq_αβ is acquired (step 201 to step 203).

  Next, the addition angle adjustment calculation unit 58 determines whether or not the induced voltage square sum Esq_αβ exceeds the threshold value E0 (step 204), and if it exceeds the threshold value E0 (step 204: YES), It is determined whether or not an excess flag indicating that the induced voltage square sum Esq_αβ is in a state exceeding the threshold value E0 is set (step 205). If the excess flag is not set (step 205: NO), the excess flag is set (step 206), and the value of the first change component dθτ acquired in step 201 is cleared (dθτ = 0, step 207).

  If the excess flag has already been set in step 205 (step 205: YES), the processing in step 206 and step 207 is not executed. If it is determined in step 204 that the induced voltage square sum Esq_αβ exceeds the threshold value E0 (step 204: YES), the first change component based on the torque deviation Δτ regardless of the excess flag. The addition angle θa is calculated by adding the second change component dθω based on dθτ and the motor rotational angular velocity ωm_e (step 208).

  On the other hand, when it is determined in step 204 that the induced voltage square sum Esq_αβ is equal to or less than the threshold value E0 (step 204: NO), the addition angle adjustment calculation unit 58 also determines whether or not the excess flag is set. (Step 209). If the excess flag is set (step 209: YES), the excess flag is reset (step 210). If the excess flag is not set (step 209: NO), the process of step 210 is not executed. Then, the first change component dθτ acquired in step 201 is calculated as the addition angle θa (step 211).

  The addition angle adjustment calculation unit 58 of the present embodiment is configured to output the addition angle θa calculated in step 208 or step 211 as described above (step 212).

  That is, the first change component dθτ based on the torque deviation Δτ is a value corresponding to the magnitude of the deviation between the actual rotation angle of the motor 12 and the virtual motor rotation angle in control. Therefore, the value is less affected by the motor rotation state than the second change component dθω based on the motor rotation angular velocity ωm_e. In consideration of this point, in the present embodiment, when the motor rotation state is in the low speed region as described above, the first change component dθτ is set as the addition angle θa. In the first calculation cycle (step 204: YES and step 205: NO) in which the addition angle θa is calculated using the second change component dθω based on the motor rotation angular velocity ωm_e, the first change component dθτ is cleared. This is because (Step 207) the first change component dθτ reflects the state of the previous calculation cycle in which the second change component dθω was not used. In the present embodiment, this makes it possible to calculate the addition angle with high accuracy regardless of the motor rotation state.

  As shown in FIG. 4, in the addition angle calculation unit 41, the addition angle θa output from the addition angle adjustment calculation unit 58 is input to the addition angle restriction unit 59. Then, the addition angle calculation unit 41 of the present embodiment outputs the addition angle θa ′ after the addition angle restriction processing is performed in the addition angle restriction unit 59 to the control angle calculation unit 42.

  On the other hand, the control angle calculation unit 42 holds the previous value of the control angle θc calculated in the previous calculation cycle in a storage area (not shown), and adds a new control by adding the addition angle θa to the previous value. The angle θc is calculated. Then, by updating the previous value stored in the storage area with the new control angle θc, the control angle θc is calculated by adding the addition angle θa for each calculation cycle. Yes.

  In the second control unit 26, the control angle θc as the virtual motor rotation angle for control calculated in this way is the two-phase fixed coordinate system (α / β coordinate) output by the α / β conversion unit 53. System) and α-axis current value Iα and β-axis current value Iβ. Then, the γ / δ conversion unit 60 maps the α-axis current value Iα and the β-axis current value Iβ onto the rotation coordinate system according to the control angle θc, that is, the orthogonal coordinate of the γ / δ coordinate system, thereby The γ-axis current value Iγ and the δ-axis current value Iδ are calculated as actual current values in the γ / δ coordinate system.

  In the present embodiment, in the γ / δ coordinate system as a virtual rotation coordinate for control, the deviation (load angle) between the control angle θc and the actual motor rotation angle (θm) is “0”. In this case, the “γ axis” coincides with the “d axis”.

  The second control unit 26 includes a current command value calculation unit 61 that calculates a γ-axis current command value Iγ * and a δ-axis current command value Iδ * as the current command value of the γ / δ coordinate system. Then, the current command value calculation unit 61 calculates the γ-axis current command value Iγ * and the δ-axis current command value Iδ * based on the torque deviation Δτ calculated by the addition angle calculation unit 41 and the target steering torque τ *. Calculate.

  The γ-axis current command value Iγ * calculated by the current command value calculation unit 61 is input to the corresponding subtracter 64a together with the γ-axis current value Iγ. Similarly, the δ-axis current command value Iδ * is also input to the corresponding subtracter 64b together with the δ-axis current value Iδ. In this embodiment, the δ-axis current command value Iδ * is fixed to “0” (Iδ * = 0). The current deviations ΔIγ and ΔIδ calculated by the subtracters 64a and 64b are input to the corresponding F / B control units 65a and 65b, respectively.

  Next, each F / B control unit 65a, 65b executes a feedback control calculation based on the current deviations ΔIγ, ΔIδ and a predetermined feedback gain (proportional: P, integral: I), thereby obtaining a γ / δ coordinate system. The γ-axis voltage command value Vγ * and the δ-axis voltage command value Vδ * which are the voltage command values are calculated. The feedback control calculation performed by each of the F / B controllers 65a and 65b is the same as that of the F / B controllers 34d and 34q on the first controller 25 side. Is omitted.

  Further, the γ-axis voltage command value Vγ * and the δ-axis voltage command value Vδ * are mapped onto the three-phase (U, V, W) AC coordinates in the two-phase / three-phase converter 66. The second control unit 26 is configured to output the phase voltage command values Vu **, Vv **, and Vw ** generated by the two-phase / three-phase conversion unit 66 to the PWM conversion unit 27. ing. For details of the principle of resolverless control executed by the second control unit 26 as described above, refer to, for example, the descriptions in Patent Document 1 and Patent Document 2 above.

  As shown in FIG. 2, the microcomputer 17 according to the present embodiment includes a rotation angle abnormality detection unit 68 that detects an abnormality in the rotation angle θm detected by the motor resolver 23. Specifically, the rotation angle abnormality detection unit 68 of this embodiment determines whether or not the sum of squares of the sine signal S_sin and the cosine signal S_cos output from the motor resolver 23 is within an appropriate range. Then, based on the determination result, an abnormality in the rotation angle θm is detected as the actual rotation angle of the motor 12. For details of such rotation angle abnormality detection, refer to, for example, the description of JP-A-2006-177750.

  Further, in the present embodiment, the result of abnormality detection by the rotation angle abnormality detection unit 68 is input to the motor control unit 24 as a rotation angle abnormality detection signal S_rsf. Then, when there is no abnormality in the rotation angle θm, the motor control unit 24 of the present embodiment performs a motor control signal based on the phase voltage command values Vu *, Vv *, Vw * calculated by the first control unit 25. When the rotation angle θm is abnormal, the motor control signal is output based on the phase voltage command values Vu **, Vv **, Vw ** calculated by the second control unit 26. Execute.

  That is, the second control unit 26 uses the control angle θc, which is a virtual motor rotation angle on control, without using the rotation angle θm detected by the motor resolver 23, which is the actual rotation angle of the motor 12. The phase voltage command values Vu **, Vv **, and Vw ** are calculated. Then, the ECU 11 of this embodiment generates a motor control signal based on the phase voltage command values Vu **, Vv **, and Vw ** calculated by the second control unit 26, thereby causing an abnormal rotation angle θm. Even after this is detected, the motor control can be continued stably.

(Current command value calculation)
Next, a mode of current command value calculation by the current command value calculation unit 61 of the present embodiment will be described.

  As shown in FIG. 8, the current command value calculation unit 61 of the present embodiment uses the γ-axis current command value Iγ in each calculation cycle based on the torque deviation Δτ between the target steering torque τ * and the actual steering torque τ. A γ-axis current increase / decrease value calculation unit 71 that calculates an increase / decrease value of γ (γ-axis current increase / decrease value η) and an integration control unit 72 that integrates the input γ-axis current increase / decrease value η for each calculation cycle are provided. .

  The integration control unit 72 of the present embodiment holds the control output in the previous calculation cycle, that is, the previous value of the γ-axis current command value Iγ * in a storage area (not shown). Then, the integration control unit 72 calculates a new γ-axis current command value Iγ * by adding the input γ-axis current increase / decrease value η to the previous value, and the new γ-axis current command value Iγ *. To update the previous value held in the storage area.

The current command value calculation unit 61 of the present embodiment is configured such that the control output of the integration control unit 72, that is, the integrated value of the γ-axis current increase / decrease value η is the γ-axis current command value Iγ *.
More specifically, the γ-axis current increase / decrease value computing unit 71 of this embodiment includes two maps (71a, 71b) in which the torque deviation Δτ and the γ-axis current increase / decrease value η are associated. Specifically, the first map 71a is formed corresponding to the case where the sign (direction) of the target steering torque τ * is “positive (τ *> 0)”, while the second map 71b is the target map The sign of the steering torque τ * is formed corresponding to “when it is negative (τ * <0)”. When the target steering torque τ * is “0”, the code immediately before is used. Then, the γ-axis current increase / decrease value calculation unit 71 switches the map to be referred to according to the sign of the input target steering torque τ *, and based on the torque deviation Δτ, the γ-axis current increase / decrease value η in each calculation cycle. Is calculated.

  That is, when the target steering torque τ * is “positive value”, the torque deviation Δτ is “positive value”, or when the sign of the target steering torque τ * is “negative value”, the torque deviation Δτ is “ The state of “negative value” indicates that the actual torque is “insufficient” with respect to the target torque that should be generated by the motor 12. On the other hand, when the target steering torque τ * is “positive value”, the torque deviation Δτ is “negative value”, or when the sign of the target steering torque τ * is “negative value”, the torque deviation Δτ is “ The state of “positive value” indicates that the actual torque is “excessive” with respect to the target torque that should be generated by the motor 12. Then, the γ-axis current increase / decrease value calculation unit 71 of the present embodiment calculates the γ-axis current increase / decrease value in each calculation cycle based on the excess or deficiency of the actual torque with respect to the target torque to be generated by the motor 12 indicated by the torque deviation Δτ. Calculate η.

  Specifically, in the first map 71a, the γ-axis current increase / decrease value η is greater than or equal to the predetermined value A1 having the “positive value” and the torque deviation Δτ is smaller than the predetermined value A2 having the same “positive value”. (A1 ≦ Δτ <A2) is set such that the larger the torque deviation Δτ is, the more positive the value is. Further, when the torque deviation Δτ is smaller than the predetermined value A1 and equal to or larger than the predetermined value A3 having the same “positive value” (A3 ≦ Δτ <A1), the torque deviation Δτ becomes larger as the value becomes smaller. It is set to be a “negative value” having an absolute value. When the torque deviation Δτ is equal to or greater than the predetermined value A2 (A2 ≦ Δτ), the γ-axis current increase / decrease value η is a constant “positive value (maximum increase value γ1)”, and the torque deviation Δτ is a predetermined value. When smaller than A3 (Δτ <A3), the γ-axis current increase / decrease value η is set to be a constant “negative value (maximum decrease value γ2)”.

  On the other hand, in the second map 71b, the γ-axis current increase / decrease value η is in a range where the torque deviation Δτ is equal to or less than the predetermined value A4 having the “negative value” and larger than the predetermined value A5 having the same “negative value”. (A5 <Δτ ≦ A4) is set so that the smaller the torque deviation Δτ, the “positive value” having a larger absolute value. When the torque deviation Δτ is greater than the predetermined value A4 and equal to or less than the predetermined value A6 having the same “negative value” (A4 <Δτ ≦ A6), the torque deviation Δτ is a large value (small absolute value). Is set to be a “negative value” having a larger absolute value. When the torque deviation Δτ is equal to or less than the predetermined value A5 (Δτ ≦ A5), the γ-axis current increase / decrease value η is a constant “positive value (maximum increase value γ1)”, and the torque deviation Δτ is a predetermined value. When larger than A6 (A6 <Δτ), the γ-axis current increase / decrease value η is set to be a constant “negative value (maximum decrease value γ2)”.

  The γ-axis current increase / decrease value calculation unit 71 of the present embodiment refers to these two maps (71a, 71b), and the actual torque is “excess” with respect to the target torque that should be generated by the motor 12 ( When τ *> 0, Δτ <0, or when τ * <0, Δτ> 0), the γ-axis current increase / decrease value η having a “negative value” that reduces the γ-axis current command value Iγ * is calculated. To do.

  Furthermore, in the present embodiment, a range in which the “shortage of actual torque” is allowed is set for the region indicating that the real torque is “insufficient” with respect to the target torque to be generated by the motor 12 (τ). *> 0, 0 ≦ Δτ <A1, or τ * <0, A4 <Δτ ≦ 0). Then, the γ-axis current increase / decrease value calculating unit 71 reduces the γ-axis current command value Iγ * so as to reduce the γ-axis current command value Iγ * even when “insufficient actual torque” indicated by the torque deviation Δτ is within the allowable range. Γ-axis current increase / decrease value η having “value” is calculated.

  Then, the γ-axis current increase / decrease value calculation unit 71 of the present embodiment, when “insufficient actual torque” indicated by the torque deviation Δτ exceeds the allowable range (Δτ ≧ A1 or τ * < At 0, Δτ ≦ A4) is configured to calculate a γ-axis current increase / decrease value η having a “positive value” that increases the γ-axis current command value Iγ *.

  Further, the current command value calculation unit 61 of the present embodiment is provided with a current command value limiting unit 73, and the γ-axis current command value Iγ * calculated by the integration control unit 72 is the current command value limitation. Input to the unit 73. Then, the current command value calculation unit 61 of the present embodiment outputs the γ-axis current command value Iγ ** after the limit process is performed in the current command value limit unit 73 to the subtractor 64a (FIG. 4). reference).

  Specifically, the current command value limiting unit 73 of the present embodiment limits the γ-axis current command value Iγ * to be equal to or less than the current command upper limit value Ilim. In other words, the γ-axis current command value Iγ * is corrected so as not to exceed the current command upper limit value Ilim (Ilim ≧ Iγ **). Further, in the present embodiment, the torque deviation Δτ is input to the current command value limiter 73. Then, the current command value limiter 73 changes the current command upper limit value Ilim based on the torque deviation Δτ.

  Specifically, as shown in FIG. 9, the current command value limiting unit 73 of the present embodiment, when the torque deviation Δτ (absolute value thereof) is equal to or less than a predetermined value T1 (| Δτ | ≦ T1) A predetermined value I1 is set as the current command upper limit value Ilim (Ilim = I1). Then, when the torque deviation Δτ exceeds the predetermined value T1, the current command value limiter 73 changes the current command upper limit value Ilim to a value higher than the predetermined value I1.

  Specifically, when the torque deviation Δτ (the absolute value thereof) is in a range greater than the predetermined value T1 and equal to or less than the predetermined value T2 (T1 <| Δτ | ≦ T2), The larger the torque deviation Δτ, the larger the current command upper limit value Ilim is set. When the torque deviation Δτ exceeds the predetermined value T2 (| Δτ | ≧ T2), the predetermined value I2 is set as the current command upper limit value Ilim (Ilim = I2).

  That is, the second control unit 26 according to the present embodiment calculates a virtual control angle θc in terms of control by executing torque feedback control based on the torque deviation Δτ as described above. In the motor control that executes current feedback control in the rotational coordinate system (γ / δ coordinate system) according to the control angle θc, as long as the stator can generate the magnetomotive force necessary to maintain the rotational position of the rotor, The deviation between the control angle θc and the actual motor rotation angle (θm) can be kept within a stable controllable range.

  In other words, in a stable control state where the actual steering torque τ follows the target steering torque τ *, paradoxically, the motor current exceeds the amount necessary to maintain the stability of the motor control. Indicates.

  Focusing on this point, the current command value limiting unit 73 of the present embodiment has a torque deviation Δτ (absolute value thereof) within a region (stable region) that is equal to or less than a predetermined value T1 indicating that the torque control is in a stable control state. In order to suppress the motor current, the current command upper limit value Ilim is set to a low value (predetermined value I0). When the torque deviation Δτ is in a range exceeding the above-described stable region (| Δτ |> T1), that is, when the stability of the control state is reduced, a larger motor current is allowed to be supplied. In order to increase the stability of the control, the current command upper limit value Ilim is changed to a higher value.

As described above, according to the present embodiment, the following effects can be obtained.
(1) The second control unit 26 calculates a virtual control angle θc for control by executing torque feedback control based on the torque deviation Δτ so that the actual steering torque τ follows the target steering torque τ *. To do. The second control unit 26 calculates a γ-axis current increase / decrease value η based on the torque deviation Δτ, and calculates the γ-axis current command value Iγ * by integrating the γ-axis current increase / decrease value η. Then, current feedback control is executed in a rotating coordinate system (γ / δ coordinate system) according to the control angle θc. Further, the second control unit 26 (current command value calculation unit 61) includes a current command value limiting unit 73 that limits the γ-axis current command value Iγ * to be equal to or less than the current command upper limit value Ilim. Then, the current command value limiter 73 changes the current command upper limit value Ilim based on the torque deviation Δτ.

  That is, in the motor control in which the control angle θc is calculated by executing the torque feedback control based on the torque deviation Δτ and the current feedback control is executed in the rotating coordinate system (γ / δ coordinate system) according to the control angle θc, the target steering torque The higher the followability of the actual steering torque τ with respect to τ *, the more stable the control state. In such a stable control state, the motor current necessary for maintaining the stability of the motor control is also a small value. Therefore, according to the said structure, a motor current can be suppressed effectively, maintaining the stability of motor control suitably. As a result, the energy efficiency can be improved and the reliability of the motor can be improved by suppressing the heat generation of the motor.

  (2) The current command value limiter 73 has a case where the torque deviation Δτ (the absolute value thereof) is in a range exceeding a region (stable region) that is equal to or less than a predetermined value T1 indicating that the torque control is in a stable control state (| Δτ |> T1), the current command upper limit value Ilim is changed to a value higher than when the torque deviation Δτ is within the stable region (Ilim = I1).

  According to the above configuration, the current command upper limit value Ilim is set to a low value (predetermined value I0) when the torque deviation Δτ indicating that the control state is stable, that is, in the stable region. Suppress excessive motor current. When the torque deviation Δτ is in a range exceeding the stable region, that is, when the stability of the control state is reduced, the current command upper limit value Ilim is changed to a high value to allow energization of a larger motor current. By doing so, the stability of motor control can be improved. As a result, it is possible to effectively suppress the motor current while suitably maintaining the stability of the motor control.

In addition, you may change the said embodiment as follows.
In the above embodiment, the present invention is embodied in a so-called column type electric power steering device (EPS) 1. However, the present invention is not limited to this, and the present invention may be applied to a so-called pinion type or rack assist type EPS.

In addition, the present invention may be applied to a motor control device used for purposes other than EPS as long as the deviation between the target torque to be generated by the motor and the actual torque can be detected.
In the above embodiment, the current command value limiting unit 73 directly changes the current command upper limit value Ilim based on the torque deviation Δτ. However, the present invention is not limited to this, and the current command upper limit value Ilim may be changed based on a combination with a plurality of state quantities by calculating a gain K that changes according to the torque deviation Δτ. .

  Specifically, for example, the current upper limit determination unit 74 shown in FIG. 10 includes a basic value map 74a in which the vehicle speed V, which is a state quantity other than the torque deviation Δτ, and the upper limit basic value Ilmb are associated with each other, and the torque deviation Δτ. And a gain map 74b in which the gain K is associated. In the basic value map 74a, the upper limit basic value Ilmb is set to be smaller as the vehicle speed V is higher. In the gain map 74b, similarly to the current command upper limit value Ilim in the above-described embodiment, the gain K is set to a larger value in a region where the torque deviation Δτ (its absolute value) is large (see FIG. 9). Then, the current upper limit determination unit 74 determines a value obtained by multiplying the upper limit basic value Ilmb and gain K calculated based on these two maps (74a, 74b) as the current command upper limit value Ilim.

  Even when the current command upper limit value Ilim calculated in this way is used, the same effect as in the above embodiment can be obtained. Incidentally, the basic value (upper limit basic value Ilmb) of the current command upper limit value Ilim multiplied by the gain K corresponding to the torque deviation Δτ (absolute value thereof) may be a fixed value.

  In the above embodiment, the current command upper limit value Ilim is continuously changed according to the torque deviation Δτ (absolute value) (see FIG. 9), but the current command upper limit value Ilim is discontinuously set. The structure to change may be sufficient.

  Specifically, for example, the current upper limit determination unit 75 shown in FIG. 11 has two maps (75a, 75b) in which the vehicle speed V, which is a state quantity other than the torque deviation Δτ, and the current command upper limit Ilim are associated with each other. It has. In the first map 75a, the current command upper limit value Ilim is set to be a constant value (predetermined value I3) regardless of the vehicle speed V. On the other hand, in the second map 75b, the current command upper limit value Ilim is set to be smaller as the vehicle speed V is higher, and the minimum value I4 is larger than the predetermined value I3 in the first map 75a. It is set to be a value. In this example, a region where the torque deviation Δτ (absolute value) is equal to or smaller than a predetermined value T3 is the stable region. Then, when the torque deviation Δτ (the absolute value thereof) is equal to or less than the predetermined value T3 (| Δτ | ≦ T3), the current upper limit value determination unit 75 refers to the first map 75a to refer to the current command upper limit value. Ilim is determined, and when the torque deviation Δτ exceeds the predetermined value T3 (| Δτ |> T3), the current command upper limit value Ilim is determined by referring to the second map 75b.

  Even in such a configuration, when the torque deviation Δτ is in the range exceeding the stable region (| Δτ |> T3), the torque deviation Δτ is in the stable region (| Δτ | By changing the current command upper limit value Ilim to a value higher than ≦ T3), the stability of the motor control can be improved.

  The state quantities other than the torque deviation Δτ are not necessarily limited to the vehicle speed V, and may be other state quantities. In addition to such a configuration using a plurality of maps, the current command upper limit value Ilim may be changed stepwise in accordance with the torque deviation Δτ (absolute value thereof).

  In the above embodiment, the addition angle calculation unit 41 calculates the addition angle θa by executing torque feedback control based on the torque deviation Δτ. The γ-axis current increase / decrease value calculation unit 71 calculates the γ-axis current increase / decrease value η based on the torque deviation Δτ. However, when the target steering torque τ * is fixed to “0” and controlled, it goes without saying that the configuration using the steering torque τ instead of the torque deviation Δτ is completely equivalent (Δτ = τ−τ *). ).

In the above embodiment, the steering angle θs is detected using the steering sensor 16, but a configuration in which the steering angle θs is estimated from the wheel speed difference may be employed.
Next, technical ideas that can be grasped from the above embodiments will be described together with effects.

  (A) a motor control signal output means for outputting a motor control signal; and a drive circuit for supplying three-phase drive power to the motor based on the motor control signal, wherein the motor control signal output means By executing torque feedback control based on the torque deviation of the actual torque with respect to the target torque to be generated, an addition angle corresponding to the amount of change in motor rotation angle for each calculation cycle is calculated, and the motor rotation on the control is calculated by integrating the addition angle A rotation coordinate system that calculates an angle, calculates an increase / decrease value based on the torque deviation for each calculation cycle, calculates a current command value by integrating the increase / decrease value, and follows the motor rotation angle on the control In the motor control device that outputs the motor control signal by executing current feedback control in the motor control signal output Stage, as well as limiting the current command value below the upper limit value, the motor control apparatus characterized by, for changing the upper limit value based on the torque deviation. According to the said structure, the motor control apparatus which can suppress a motor current effectively can be provided, maintaining the stability of motor control suitably.

(B) The motor control signal output means determines the upper limit value by multiplying a basic value of the upper limit value by a gain that changes according to the torque deviation.
(C) The motor control signal output means includes a plurality of maps in which state quantities other than the torque deviation are associated with the upper limit value, and the upper limit value is determined while switching the map to be referred to based on the torque deviation. It is characterized by determining.

  DESCRIPTION OF SYMBOLS 1 ... Electric power steering apparatus (EPS), 10 ... EPS actuator, 11 ... ECU, 12 ... Motor, 12u, 12v, 12w ... Motor coil, 14 ... Torque sensor, 15 ... Vehicle speed sensor, 16 ... Steering sensor, 17 ... Microcomputer , 18 ... Drive circuit, 21 ... Current sensor, 23 ... Motor resolver, 24 ... Motor controller, 25 ... First controller, 26 ... Second controller, 27 ... PWM converter, 41 ... Addition angle calculator, 42 ... control angle calculation unit, 45 ... target steering torque calculation unit, 46 ... subtractor, 47 ... F / B control unit, 50 ... rotational angular velocity estimation calculation unit, 52 ... phase voltage calculation unit, 53 ... α / β conversion unit, 54 ... Disturbance observer, 58 ... Addition angle adjustment calculation unit, 59 ... Addition angle restriction unit, 60 ... γ / δ conversion unit, 61 ... Current command value calculation unit, 65a, 65b ... F / B control unit, 66 ... Two-phase Three-phase conversion unit, 68 ... rotation angle abnormality detection unit, 71 ... γ-axis current increase / decrease value calculation unit, 71a ... first map, 71b ... second map, 72 ... integration control unit, 73 ... current command value limiting unit, 74 ... upper limit value determining unit, 74a ... basic value map, 74b ... gain map, 75 ... current upper limit determining unit, 75a ... first map, 75b ... second map, Iu, Iv, Iw ... phase current value, θm ... Rotation angle, Id ... d-axis current value, Iq ... q-axis current value, Id * ... d-axis current command value, Iq * ... q-axis current command value, ΔId, ΔIq ... current deviation, Vu *, Vv *, Vw * ... phase voltage command value, τ ... steering torque, τ * ... target steering torque, Δτ ... torque deviation, A1 to A6 ... predetermined values, T1, T2, T3 ... predetermined values, η ... γ-axis current increase / decrease value, dθτ ... 1 change component, Iα ... α-axis current value, Iβ ... β-axis current value, Vα ... α-axis voltage value, Vβ ... β-axis voltage value, Eα, Eβ ... induced voltage, α_e, Eβ_e: Estimated value of induced voltage, Esq_αβ: Sum of squares of induced voltage, E0: Threshold value, ωm_e: Motor rotation angular velocity, dθω: Second change component, θa, θa ′: Addition angle, θc: Control angle, Iγ: γ axis Current value, Iδ ... δ-axis current value, Iγ *, Iγ ** ... γ-axis current command value, Iδ * ... δ-axis current command value, ΔIγ, ΔIδ ... Current deviation, Vu **, Vv **, Vw ** ... Phase voltage command value, θs ... Steering angle, V ... Vehicle speed, Ilim ... Current command upper limit value, I1, I2, I3 ... Predetermined value, I4 ... Minimum value, Ilmb ... Upper limit basic value, K ... Gain, S_rsf ... Rotation angle Anomaly detection signal.

Claims (2)

A steering force assisting device for applying an assisting force to a steering system using a motor as a drive source; and a control means for controlling the operation of the steering force assisting device, wherein the control means outputs a motor control signal. Output means, and a drive circuit that supplies three-phase drive power to the motor based on the motor control signal, and the motor control signal output means generates a torque deviation between the target steering torque and the actual steering torque. Based on the execution of torque feedback control based on the calculation, an addition angle corresponding to the amount of change in the motor rotation angle for each calculation cycle is calculated, and the motor rotation angle on the control is calculated by integrating the addition angle, and for each calculation cycle, In the rotating coordinate system according to the motor rotation angle on the control while calculating the current command value by calculating the increase / decrease value based on the torque deviation and integrating the increase / decrease value By executing the flow feedback control, the electric power steering device for outputting the motor control signal,
The motor control signal output means limits the current command value to an upper limit value or less and changes the upper limit value based on the torque deviation.
An electric power steering device. The electric power steering apparatus according to claim 1, wherein
The motor control signal output means, when the torque deviation is in a range exceeding the stable region, changing the upper limit value to a higher value than when the torque deviation is in the stable region;
An electric power steering device.

Images