JP2002209387A - Drive device for current-control type element - Google Patents

Abstract

PROBLEM TO BE SOLVED: To supply a positive pulsive current and a negative pulsive current to the control terminal of a transistor for driving by time-sharing. SOLUTION: N-type MOS switches 13, 16, and 14, 15 are alternately turned on and off at a frequency of 300 kHz by the output of an oscillating circuit 11, and an AC voltage by a DC power supply source 12 is applied to a primary coil winding 71 of a pulse-type transformer 17. Diodes 18 and 19 are connected to the side of a secondary coil winding 72 in series with polarities being opposite to each other. N-type MOS switches 20 and 21 are connected to each diode. A control circuit 22 turns on the N-type MOS switch 21 and turns off the other for outputting a positive pulse current, and turns on the N-type MOS switch 20 and turns off the other for outputting a negative pulse current, thus outputting the positive pulse current that is rectified by a diode 18 and a negative pulse current that is rectified by the diode 18 from output terminals 24 and 25 by time-sharing.

Description

DETAILED DESCRIPTION OF THE INVENTION

[0001]

BACKGROUND OF THE INVENTION 1. Field of the Invention The present invention relates to a driving device for a current control type element.

[0002]

2. Description of the Related Art There is known a switching power supply circuit in which two outputs of a positive voltage and a negative voltage are taken out from one secondary winding provided in a main transformer. For example, Japanese Patent Application Laid-Open No. 7-337012 discloses that a positive voltage and a negative voltage are induced in a secondary winding of a transformer by changing a DC voltage applied to a primary winding wound on the transformer. Performs rectification and smoothing for positive voltage and negative voltage respectively 2
A power supply circuit in which two slave output circuits are connected in parallel is described. In such a power supply circuit, one of the slave output circuits outputs a positive voltage and the other slave output circuit outputs a negative voltage.

[0003]

If two slave output circuits are provided to output a positive voltage and a negative voltage respectively, there is room for improvement in miniaturization of the power supply circuit.

An object of the present invention is to provide a drive device for a current control element using a drive circuit in which the number of slave output circuits is reduced.

[0005]

The present invention will be described with reference to FIGS. 2, 5, 7, 9, and 11 showing one embodiment. (1) A current controlling element driving device according to the first aspect of the present invention includes a current controlling transistor for supplying a driving current to an inductive load connected to a driving terminal, and the current controlling transistor is inductive. Protecting means 23, 23A (270, 26, 72, 270A, 26A,
72A). And a pulse current generating means for supplying one of a positive pulse current and a negative pulse current to the control terminal of the current control transistor, and a direction in which the current control transistor drives the inductive load. A positive pulse current is continuously supplied to the control terminal during the ON period,
Control means 22, 22A (28, 28A) for controlling the pulse current generating means 10, 10A so as to supply a negative pulse-like current to the control terminal at the time when the current control type transistor reversely recovers from the state of being turned on in the reverse direction. 28A) achieves the above-described object. (2) According to a second aspect of the present invention, in the current control type element driving device according to the first aspect, the pulse current generating means includes a transformer 17 connected to both ends of the output of the DC voltage sources 12 and 12A.
AC generating means 11, 13 to 16, 11A, which alternately apply in both positive and negative directions from both ends of primary windings 71, 71A of 17A.
13A to 16A and secondary winding 7 of transformers 17 and 17A
Rectifiers 18 to 21 and 18A to 21A for rectifying the positive and negative voltages induced at 2,72A in a time sharing manner. (3) The invention according to claim 3 is the drive device for a current control type element according to claim 2, wherein the AC generating means includes a primary winding of the transformers 17 and 17A at both ends of the outputs of the DC voltage sources 12 and 12A. A first switch 13, 13A and a second switch 16, 16A connected so as to apply a positive voltage from both ends of 71, 71A, and primary windings of transformers 17, 17A are connected to both ends of the output of DC voltage sources 12, 12A. A third switch 1 connected so as to apply a voltage in the negative direction from both ends of the switches 71 and 71A.
4, 14A and the fourth switch 15, 15A, the longer of the time for connecting to apply in the positive direction and the time for connecting to apply in the negative direction, the longer of the other time and either the positive direction or the negative direction The first to fourth switches 13-16, 13A-
Switch control means 11 and 11A for opening and closing the 16A are provided. (4) According to a fourth aspect of the present invention, in the current controlling element driving device according to the second or third aspect, the rectifying means includes:
First connected in series so that the polarities are opposite to each other
Rectifiers 18, 18A (260, 260A) and second rectifiers 19, 19A (270, 270A), and first rectifiers 18, 18A (260, 260A) and second rectifiers 19, 19A ( 270, 270A) and a sixth switch 21, 26 (26, 26A) and a sixth switch 21, 21 (27, 27A) connected in parallel with the current-controlled transistor to drive the inductive load. Between the first rectifier element 18 and the first rectifier element 18A during the time when the current control type transistor reversely recovers from the state where it is turned on in the reverse direction.
(260, 260A) and second rectifying elements 19, 19A
(270, 270A) and second switch control means 22, 22A for controlling the opening and closing of the fifth switches 20, 20 (26, 26A) and the sixth switches 21, 21 (27, 27A) so as to switch the rectification direction. (28, 28A). (5) According to a fifth aspect of the present invention, in the current control type element driving device according to the second or third aspect, the rectifying means comprises:
The first rectifying element and the fifth switch connected in series and the second rectifying element and the sixth switch connected in series are opposite in polarity of the first rectifying element and the second rectifying element. Are connected in parallel so that the current control type transistor is turned on in the direction for driving the inductive load, and the current control type transistor reversely recovers from the state of being turned on in the reverse direction. A second switch control means for controlling the opening and closing of the fifth switch and the sixth switch so as to switch the rectifying direction by the rectifying element and the second rectifying element is provided. (6) The drive device for a current control type element according to the invention of claim 6 is located on the upper arm side with respect to the inductive load, supplies a drive current in the first direction, and is generated from the inductive load. A first current control type transistor for flowing a current due to a back electromotive force in a reverse direction, and a first current control type transistor connected in series with the first current control type transistor; A drive current is supplied in a different second direction, and a positive current is applied to a control terminal of the second current control transistor and a control terminal of the first current control transistor, in which a current caused by a back electromotive force generated from the inductive load flows in the reverse direction. A first pulse current generating means for supplying one of a pulsed current and a negative pulsed current; and a positive pulsed current during a period in which the first current control transistor is turned on to drive an inductive load. Electric Is continuously supplied to the control terminal of the first current control transistor, and when the first current control transistor reversely recovers from a state in which it is turned on in the reverse direction, a negative pulse-like current is supplied to the first current control transistor. The first pulse current generating means 10 is supplied to the control terminal of the control type transistor so as to supply it to the control terminal.
And a second pulse current generating means for supplying one of a positive pulse current and a negative pulse current to a control terminal of the second current control transistor. 10A, a positive pulsed current is continuously supplied to the control terminal of the second current control type transistor during a period in which the second current control type transistor is turned on to drive the inductive load, and the second current The second pulse current generating means 10A is controlled so that a negative pulse-like current is supplied to the control terminal of the second current control type transistor when the control type transistor reversely recovers from the ON state in the reverse direction. By providing the second control means 22A (28A), the above-described object is achieved. (7) The invention according to claim 7 is the current control type element driving device according to claim 6, wherein the first pulse current generating means 10 and the second pulse current generating means 10A are provided with a DC voltage source 12 , 12A Transformer 17, 17A at both ends
Generating means 11, 13-16, 11A, 13A for alternately applying in both positive and negative directions from both ends of primary windings 71, 71A.
To 16A and the secondary windings 72, 72 of the transformers 17, 17A.
Rectifying means 1 for rectifying positive and negative voltages induced in A in a time-sharing manner
8 to 21, and 18 to 21A, respectively. (8) The invention according to claim 8 is the current control element drive device according to claim 7, wherein the first control means 22
(28) and the second control means 22A (28A) switch the polarity of the pulsed current supplied to the control terminal of the other current control transistor depending on the on / off state of one current control transistor. Rectifying means 18-
21, 18 to 21A are controlled. (9) The current control type element driving device according to the ninth aspect of the present invention is located on the upper arm side with respect to the inductive load and supplies the driving current in the first direction, and is generated from the inductive load. A first current control type transistor for flowing a current due to a back electromotive force in a reverse direction, and a first current control type transistor connected in series with the first current control type transistor; A second current-controlled transistor that supplies a drive current in a different second direction and flows a current due to a back electromotive force generated from the inductive load in the reverse direction, and the first current-controlled transistor drives the inductive load The first pulse current generating means 10B for supplying a positive pulse-like current to the control terminal of the first current control type transistor during the period in which the transistor is turned on, and the second current control type transistor drives the inductive load. A second pulse current generating means for supplying a positive pulse current to the control terminal of the second current control type transistor during a period in which the first pulse current generating means is turned on. The current generating means 10A achieves the above-described object by being synchronized so as to supply pulse-like currents whose phases are inverted to each other to the first current control transistor and the second current control transistor, respectively. (10) According to a tenth aspect of the present invention, in the current control type element driving device according to the ninth aspect, the first pulse current generating means 10B turns on the first current control type transistor in the reverse direction. When a reverse recovery from the current state occurs, a negative pulse-like current is further supplied to the control terminal of the first current control type transistor, and the second pulse current generation means 10A outputs the second current control type transistor in the reverse direction. A negative pulse-like current is further supplied to the control terminal of the second current control type transistor at the point of reverse recovery from the ON state to the first pulse current generating means 10B and the second pulse current generating means 10A. Are the positive pulse current generated by the first pulse current generating means 10B and the second pulse current generating means 10B.
A, the phase of the negative pulse current generated by A matches the phase of the negative pulse current generated by the first pulse current generator 10B and the phase of the positive pulse current generated by the second pulse current generator 10A. Is supplied to the first current control transistor and the second current control transistor, respectively. (11) According to an eleventh aspect of the present invention, in the current control type element driving device according to the tenth aspect, the first pulse current generating means 10B includes an output of the first transformer 17B and an output of the DC voltage source 12. First AC generating means 11, 13 to 16 alternately applying both ends in both positive and negative directions from both ends of a primary winding 71 of a first transformer 17B, and positive and negative induced in a secondary winding 72B of the first transformer 17B. Rectifying means 18 to 21 for rectifying the voltage of the DC voltage source in a time-division manner. The second pulse current generating means 10A includes a second transformer 17A and a second transformer 17A connected to both ends of the output of the DC voltage source 12A. AC generators 11A, 13A to 16A alternately applied in both positive and negative directions from both ends of a primary winding 71A, and positive and negative voltages induced in a secondary winding 72A of a second transformer 17A are time-divisionally rectified. Second And a flow means 18A~21A,
The phase of the voltage induced in the secondary winding 72B of the first transformer 17B and the secondary winding 72A of the second transformer 17A
Is characterized in that the phase of the voltage induced in is inverted. (12) According to a twelfth aspect of the present invention, in the current controlling element driving device according to the eleventh aspect, the first transformer 17B and the second transformer 17A are one transformer 1
The transformer 17C includes a shared primary winding 71 and a first secondary winding 7 for inducing positive and negative voltages.
2B, and a second secondary winding 72A that induces a positive / negative voltage whose phase is inverted with respect to the positive / negative voltage induced by the first secondary winding 72B. (13) According to a thirteenth aspect of the present invention, in the current control type element driving device according to the ninth aspect, the driving current is supplied to the inductive load 40 on the upper arm side in the second direction. In addition, a third current control transistor 43 for flowing a current due to a back electromotive force generated from the inductive load 40 in the reverse direction, and the third current control transistor 43 are connected in series with each other. It is located on the lower arm side to supply the first direction driving current and
The fourth current control type transistor 44 for flowing a current due to the back electromotive force generated from 0 in the reverse direction, and the third current control type during the period when the third current control type transistor 43 is turned on to drive the inductive load 40. Pulse current generating means 58, 54, 47 for supplying a positive pulse current to the control terminal of the type transistor 43, and a period during which the fourth current control type transistor 44 is turned on to drive the inductive load 40 And a fourth pulse current generating means 58 for supplying a positive pulse current to the control terminal of the fourth current control transistor 44.
54, 48, the first to fourth pulse current generating means 57, 53, 45, 46,
58, 54, 47 and 48 are (1) the positive pulse currents generated by the first pulse current generating means 57, 53 and 45 and the positive pulse currents generated by the second pulse current generating means 57, 53 and 46. The phase is inverted, and (2) the phases of the positive pulse currents by the first pulse current generation means 57, 53, 45 and the positive pulse currents by the fourth pulse current generation means 58, 54, 48 match. (3) The phases of the positive pulse current by the third pulse current generating means 58, 54, 47 and the positive pulse current by the fourth pulse current generating means 58, 54, 48 are inverted, and (4) The first pulse current generated by the third pulse current generating means 58, 54, 47 and the second pulse current generated by the second pulse current generating means 57, 53, 46 have the same phase as the first pulse current. Current-controlled transistors- And supplying each of the current-controlled transistor.

In the section of the means for solving the above-mentioned problems, the present invention is associated with the drawings of the embodiments in order to explain the present invention in an easy-to-understand manner, but the present invention is not limited to the embodiments. is not.

[0007]

According to the present invention, the following effects can be obtained. (1) In the current controlling element driving device according to the first to fifth aspects of the present invention, a pulse current generating means for supplying a positive and negative pulse current to a control terminal of the current controlling transistor is provided, and the current controlling transistor is A positive pulse-like current is supplied to the control terminal during the period in which the inductive load is driven, and a negative pulse-like current is controlled when the current-controlled transistor reversely recovers from the state in which it is turned on in the reverse direction. It was supplied to the terminal. As a result, the pulse current generating means may supply either the positive pulse current or the negative pulse current among the generated positive and negative pulse currents to the control terminal in a time-sharing manner, and outputs the positive and negative pulse currents. Since the number of circuits can be reduced as compared with a case where circuits are separately provided, a small-sized and low-cost driving device can be obtained. (2) According to the second and seventh aspects of the invention, positive and negative voltages induced in the secondary winding of the transformer in accordance with the AC voltage applied to the primary winding of the transformer are rectified in a time-sharing manner. Therefore, the number of circuits on the secondary winding side of the transformer can be reduced. As a result, a compact and low-cost driving device can be obtained. (3) According to the third aspect of the present invention, of the positive and negative voltages applied to the primary winding of the transformer by the AC generating means, the longer application time is the shorter application time and the time during which neither positive or negative voltage is applied. To be shorter than the sum of As a result,
Since the alternating current flowing through the primary winding becomes 0 every cycle, a drive device that operates stably without the saturation of the transformer core can be obtained. (4) According to the invention described in claims 4 and 5, each of the first rectifier and the second rectifier connected in the opposite directions to each other generates the voltage induced in the secondary winding of the transformer in a time division manner. The fifth switch and the sixth switch were controlled to open and close so as to perform rectification. As a result, a circuit on the secondary winding side of the transformer can be configured with a small number of components, and a compact and low-cost drive device can be obtained. (5) In the current controlling element driving device according to the sixth to eighth aspects of the present invention, positive and negative pulse currents are supplied to the control terminals of the first and second current controlling transistors connected vertically. First and second pulse current generating means are provided, and the first and second current control transistors supply a positive pulse current to the first and second current control units during a period in which the first and second current control transistors are turned on to drive an inductive load. Negative currents are supplied to the control terminals of the first and second current control transistors, respectively, at the time when the first and second current control transistors reversely recover from the on state in the reverse direction. The voltage is supplied to each control terminal of the transistor. As a result, the first and second pulse current generating means can supply either the positive pulse current or the negative pulse current among the generated positive and negative pulse currents to the respective control terminals in a time-sharing manner. Since the number of circuits can be reduced as compared with a case where circuits for outputting positive and negative pulse currents are separately provided, a small-sized and low-cost driving device can be obtained. (6) According to the invention described in claim 8, one of the first and second current control transistors connected vertically is turned on / off of one of the first and second current control transistors.
The polarity of the pulsed current supplied to the control terminal of the other current control transistor is switched depending on the off state. Therefore, for example, when a charge is accumulated in the other current control type transistor when one current control type transistor is turned on, a negative pulse current is supplied to the control terminal of the other current control type transistor. , The stored charge is quickly extracted. As a result, the charge remaining in the other current control type transistor is reduced and the current control type transistor is turned off, so that a large current flowing through the first and second current control type transistors is prevented from flowing. Is done. (7) In the current controlling element driving device according to the ninth to thirteenth aspects, a positive pulse-shaped current is supplied to the control terminals of the first and second current controlling transistors connected vertically. First and second pulse current generating means are provided, and during a period in which the first and second current control transistors are turned on to drive the inductive load, respectively,
Pulsed currents synchronized so that their phases are inverted are supplied to the control terminals of the first and second current control transistors, respectively. As a result, a loss can be reduced as compared with the case of outputting a pulse current having the same phase, and a small-sized and low-cost driving device can be obtained.

[0008]

Embodiments of the present invention will be described below with reference to the drawings. -First Embodiment- FIG. 1 is a view for explaining a current control type element driving device according to a first embodiment of the present invention. In FIG. 1, T1
And T2 are current control type switching transistors (hereinafter simply referred to as driving transistors) for supplying a driving current to an inductive load L1 composed of a motor or the like, and drive circuits 10 and 10 connected to respective base terminals. Driven by 10A. The power supply voltage V1 is connected to the collector terminal of the driving transistor T1, and the emitter terminal of the driving transistor T2 is grounded. The emitter terminal of the driving transistor T1 and the driving transistor T
The inductive load L1 is connected between the second collector terminal and the second collector terminal.

Such a driving device for a current control type element for driving the inductive load L1 is used, for example, in a chopper circuit and an H-bridge circuit for controlling an induction motor. In these circuits, it is necessary to protect the driving transistors T1 and T2 from the back electromotive force generated by the inductive load L1.

For example, when the drive transistor T2 of the lower arm is turned on by the drive circuit 10A, a current flows in the direction indicated by A in the figure. Thereafter, when the driving transistor T2 is turned off by the driving circuit 10A, a back electromotive force is generated from the inductive load L1, and the potential at point P in the figure rises due to the back electromotive force. When the potential at the point P becomes higher than the potential of the base terminal of the driving transistor T1 of the upper arm, the collector-emitter of the driving transistor T1 is reverse-biased, and the driving transistor T1 turns on in the reverse direction. Circulates in the direction indicated by B in the figure.

While the driving transistor T1 is turned on in the reverse direction, the driving transistor T2 is again turned on by the driving circuit 1
When it is turned on by 0A, a current flows in point A again at point P. The driving transistor T1 enters a reverse recovery operation, and the electric charge accumulated in the driving transistor T1 stays as it is. As a result, while the driving transistor T1 is in the off state, a current flows in the direction from the collector to the emitter, that is, in the forward direction, and there is a possibility that a large through current Z passing through the driving transistor T1 and the driving transistor T2 flows. . The driving circuits 10 and 10A according to the present invention drive the driving transistors T1 and T2, respectively, and suppress a through current from flowing through the driving transistors T1 and T2.

FIG. 2 is a diagram showing the driving circuits 10 and 10A of FIG. 2, a driving circuit 10 includes an oscillation circuit 11, a DC voltage source 12, N-type MOS switches 13 to
16, transformer 17, diodes 18 and 19
, Switches 20, 21, and 23, a control circuit 22, and output terminals 24 and 25. A primary winding 71 and a secondary winding 72 are wound around the transformer 17. The reference numerals of the transformers, switches, and the like that constitute the lower arm drive circuit 10A denote the upper arm drive circuit 10A.
The same numbers as those used in the above are denoted by adding A.

The circuit on the primary winding 71 side of the transformer 17 has the voltage of the DC voltage source 12
, N-type MOS switches 13 and 16 are connected in series. Further, since the voltage of the DC voltage source 12 is applied to the primary winding 71 in a negative direction, an N-type MOS
Switches 14 and 15 are connected in series. The oscillation circuit 11 includes a set of N-type MOS switches 13 and 16,
A control signal is output so that one of the sets of N-type MOS switches 14 and 15 is turned on and the other set is turned off.

On the secondary winding 72 side of the transformer 17, diodes 18 and 19 are connected in series so that their polarities are opposite to each other. Diodes 18 and 1
9, N-type MOS switches 20 and 21 are connected in parallel, respectively. The control circuit 22 outputs a control signal to turn on one of the N-type MOS switches 20 and 21 and turn off the other. In FIG. 2, when a voltage is induced in the positive direction of the secondary winding 72 (upward toward the dots in the figure), the N-type MOS switch 21 is turned on and the N-type MOS switch 20 is turned off. When a voltage is induced in the negative direction of the secondary winding 72, the N-type MOS switch 20 is turned on and the N-type MOS switch 21 is turned off.

The operation timing of the drive circuit 10 will be described. FIG. 3 is a timing chart showing the operation timing of the drive circuit 10 of FIG. In FIG. 3, the current waveform flowing through the primary winding 71 is Ip, the control signal waveform applied to the gate terminals of the N-type MOS switches 13 and 16 is Sig13, and the control waveform applied to the gate terminals of the N-type MOS switches 14 and 15 is The signal waveform is Sig14. The control signals Sig13 and Sig14 have, for example, a frequency of 300
It is applied to the gate terminal of each switch continuously at kHz. In this case, one cycle is about 3.33 μsec, and if one cycle is 100%, the period of the timing t1 to t2 when the control signal SiG13 is set to the H level is 30%, and the control signal SiG1
The period between timings t2 and t3 when the control signal Sig14 becomes H level after 3 becomes L level is 5%, and the control signal SiG14
During the period from timing t3 to t4 when
%, And the period between timings t4 and t6 when the control signals Sig13 and Sig14 are both at the L level is 35%. Of these, the period from timing t2 to t3 is set to a value very close to 0, and the period from t4 to t6 is lengthened accordingly.

At time t1, the transmission circuit 11 on the primary winding 71 sets the control signal Sig13 to H level. At this time, the control signal Sig14 remains at the L level. Thereby, the N-type MOS switches 13 and 16
Are turned on, the N-type MOS switches 14 and 15 are turned off, and the exciting current starts to flow through the primary winding 71 from the dot side in FIG. At the timing t2, the transmission circuit 11 sets the control signal Sig13 to L level. At this time, the control signal Sig14 remains at the L level, whereby the N-type MOS switches 13 to 16 are turned off. At this time, the exciting current flowing through the primary winding 71 is an N-type MOS.
The current is circulated through a body diode (not shown) built in the switches 14 and 15.

At time t3, the transmission circuit 11 sets the control signal Sig14 to H level. At this time, the control signal Sig13 remains at the L level.
The type MOS switches 13 and 16 are turned off, and the N-type MOS switches 14 and 15 are turned on, so that the exciting current flowing downward from the dot side in FIG. At the timing t4, the transmission circuit 11
Sets the control signal Sig14 to L level. At this time, the control signal Sig13 remains at the L level.
The OS switches 13 to 16 are turned off. Where N-type M
The time during which the OS switches 13 and 16 are on is
The transmitting circuit 11 controls the N-type MOS switch 11 so that it becomes shorter than the sum of the time during which the N-type MOS switches 14 and 15 are turned on and the time during which all of the N-type MOS switches 13 to 16 are turned off.
The open / close control of the type MOS switches 13 to 16 is performed. As a result, the exciting current flowing through the primary winding 71 is circulated through the body diodes (not shown) incorporated in the N-type MOS switches 14 and 15, and becomes zero at the timing t5.

At time t6, the transmission circuit 11 sets the control signal Sig13 to the H level again. At this time, the control signal Sig14 remains at the L level, whereby the N-type MOS switches 13 and 16 are turned on, and the N-type M
The OS switches 14 and 15 are turned off, and the exciting current starts to flow through the primary winding 71 downward from the dot side in FIG. Thereafter, similarly, the operations at the timings t1 to t6 described above are repeatedly performed. Since the exciting current is temporarily set to 0 at the timing t5, the core of the transformer 17 does not saturate.

When the output terminal 24 outputs a positive voltage with respect to the potential of the output terminal 25, the control circuit 22 on the side of the secondary winding 72 outputs an L level, N-type MOS to the gate terminal of the N-type MOS switch 20. An H level control signal is output to the gate terminal of the switch 21 and a control signal for turning on the switch 23 is output. Thereby, the N-type MOS
The switch 20 is turned off, the N-type MOS switch 21 is turned on, the rectifying operation by the diode 18 is performed, and a positive voltage is output to the output terminal 24 via the switch 23. The output terminal 24 has the base terminal of the driving transistor T1 connected thereto.
When the emitter terminal of the driving transistor T1 is connected to the output terminal 25, respectively, the driving transistor T1
A drive current flows from the base terminal to the emitter terminal, and the drive transistor T1 is driven.

The current waveform Ip of FIG. 3 flowing through the primary winding 71 increases at the timing when the driving transistor T1 is driven, and becomes as shown by the current waveform IpL + of FIG. That is, the output terminals 24 and 25
Energy is transmitted from the primary winding 71 side of the transformer 17 to the secondary winding 72 side only when a load current is supplied therebetween.

During the period when the current of the primary winding 71 increases,
By the action of the transformer 17, a load current flows in a direction flowing out of the output terminal 24 on the dot side of the secondary winding 72. During the period in which the current of the primary winding 71 decreases, the potential on the dot side of the secondary winding 72 decreases with respect to the potential of the output terminal 25. Absent.

On the other hand, when the control circuit 22 causes the output terminal 24 to output a negative voltage with respect to the potential of the output terminal 25, the control terminal 22 sets the gate terminal of the N-type MOS switch 20 to H level,
An L-level control signal is output to the gate terminal of the N-type MOS switch 21 and a control signal for turning on the switch 23 is output. Thereby, the N-type MOS switch 2
0 is turned on, the N-type MOS switch 21 is turned off, the rectifying operation is performed by the diode 19, and a negative voltage is output to the output terminal 24 via the switch 23. Output terminal 2
4, the base terminal of the driving transistor T1 is connected to the output terminal 25, and the emitter terminal of the driving transistor T1 is connected to the output terminal 25. A current flows in a direction flowing into the output terminal 24 on the dot side of the line 72.
While the current of the primary winding 71 increases, the diode 1
9 prevents the load current from flowing out of the output terminal 24.

In the present embodiment, the electric charge stored in the driving transistor T1 is extracted by using a current flowing in the output terminal 24 on the dot side of the secondary winding 72. In other words, when there is reverse recovery electric charge at the time of reverse recovery staying in the driving transistor T1, by extracting the electric charge from the base terminal, the driving transistor T1 is in the off state and the collector → emitter direction.
That is, the time during which the current flows in the forward direction is reduced.

In the above description, the driving circuit 10 for driving the driving transistor T1 of the upper arm in FIG. 1 has been described. However, the driving circuit 10A for driving the driving transistor T2 of the lower arm performs the same operation. The control circuit 22 of the drive circuit 10 and the control circuit 2 of the drive circuit 10A
2A is synchronously controlled by a timing signal (not shown).

FIG. 4 is a timing chart showing the operation timing of the current control type element driving device of FIG. In FIG. 4, current waveform Ip corresponds to drive circuits 10 and 10
7A is a waveform of a current flowing through each of the primary windings 71 and 71A of FIG. The primary windings 71 and 71A have a frequency of about 3 regardless of the drive timing of the drive transistors T1 and T2.
A pulsed current of 00 kHz flows.

The control circuit 22A of the lower arm turns on the N-type MOS switch 21A and turns on the N-type MOS at the time t21 when the driving transistor T2 is turned on.
The switch 20A is turned off and the switch 23A is turned on.
As a result, a pulse-like current flows continuously from the base terminal of the driving transistor T2 to the emitter terminal. The driving transistor T2 is a capacitive load, and the lifetime of the electric charge in the driving transistor T2 is sufficiently longer than the period of the pulsed current. Turned on. In this case, the secondary winding 72 of the transformer 17A
It is not necessary to provide a smoothing capacitor on the side.

When the driving transistor T2 of the lower arm is turned on, a current flows in the direction A in FIG. At time t22 when the driving transistor T2 is turned off, the control circuit 22A determines that the N-type MOS switch 21A, the N-type MOS switch 20A, and the switch 23
Turn off all A. As a result, the pulse-like current is not supplied to the base terminal of the driving transistor T2, so that the driving transistor T2 is turned off. When the driving transistor T2 is turned off, a back electromotive force is generated from the inductive load L1, and the back electromotive force raises the potential at point P in FIG. Higher than the potential of the base terminal. At this time, the switch 23 of the upper arm disconnects the secondary winding 72 side from the base terminal (output terminal 24) of the driving transistor T1. A current flows from the (output terminal 25) to the base terminal (output terminal 24). As a result, the driving transistor T1 is turned on in the reverse direction, and the circulating current is reduced to B in FIG.
Flows in the direction.

The control circuit 22 of the upper arm turns off the N-type MOS switch 21, turns on the N-type MOS switch 20, and turns on the switch 23 at the timing t23 when the driving transistor T2 of the lower arm is turned on again. To The switch 23 connects the secondary winding 72 side to the base terminal (output terminal 24) of the driving transistor T1. Terminal 2
No current to 4) is passed. As a result, a pulse-like current flows from the base terminal of the driving transistor T1, and the electric charge accumulated in the driving transistor T1 is extracted. The pulse current for extracting charges is at least one pulse. The control circuit 22 sets the N-type MOS switch 21 and N
The type MOS switch 20 and the switch 23 are all turned off. Thus, no negative current is applied to the base terminal of the driving transistor T1.

On the other hand, the control circuit 22A of the lower arm switches the N-type MOS switch 2 at the timing t23.
1A is turned on, the N-type MOS switch 20A is turned off, and the switch 23A is turned on. When a pulsed current flows from the base terminal to the emitter terminal of the driving transistor T2, the driving transistor T2 is turned on again.
At point P, a current flows again in the direction A, and the driving transistor T1 of the upper arm starts a reverse recovery operation. At this time, since the electric charge in the driving transistor T1 of the upper arm is reduced as described above, the through current Z does not flow.

In the above description, an example is described in which the driving circuit 10A pulls off the charges remaining in the driving transistor T1 of the upper arm when the driving transistor T2 of the lower arm is turned on and off by the driving circuit 10A. As described above, the driving transistor T1 of the upper arm is connected to the driving circuit 1
When turning on and off at 0, the same applies to the case where the charge remaining in the driving transistor T2 of the lower arm is extracted by the driving circuit 10A.

The diodes 18 and 19 (18A and 19A) of the drive circuit 10 (10A) use Schottky diodes with small loss. By using a diode with a small voltage drop, the output voltage on the secondary winding 72 (72A) side of the transformer 17 (17A) can be reduced. As a result, the power consumption of the transformer can be reduced when designing the transformer 17 (17A).
0 (10A) can be obtained.

According to the first embodiment described above,
The following effects can be obtained. (1) The pulse type transformer 17 is connected to the drive circuit 10 (10A).
(17A), the operation at timing t1 to timing t6 is repeated at a frequency of 300 KHz,
At time 5, the exciting current of the primary winding 71 (71A) is temporarily reduced to 0.
I tried to. Therefore, the transformer 17 (17A)
The pulse-type power supply circuit can be operated stably without the core being saturated. (2) Since one cycle of the timings t1 to t6 is sufficiently shorter than the lifetime of the electric charge in the driving transistors T1 and T2, the driving transistors T1 and T2 can be turned on by a pulsed driving current. As a result, there is no need to provide a smoothing capacitor on the secondary side of the transformer 17 (17A), which has the effect of reducing the size of the circuit and reducing the cost. (3) Since the energy is transmitted to the secondary side of the transformer 17 (17A) only when the load current flows to the secondary winding 72 (72A) side, there is no need to continuously supply the current to the secondary side of the transformer. The circuit can be simplified by reducing the number of circuit components on the secondary side. (4) A diode 18 is provided on the secondary side of the transformer 17 (17A).
And 19 (18A and 19A) are connected in series so that the polarities are opposite to each other, and N-type MOS switches 20 and 21 (20A and 21A) are connected in parallel to the respective diodes. When outputting a positive pulse current from the drive circuit 10 (10A), the N-type MOS switch 21 (2
1A) is turned on and the other is turned off, and when outputting a negative pulse current, the N-type MOS switch 20 (20A) is turned on and the other is turned off. Therefore, when a positive pulse current is output, the current is rectified by the diode 18 (18A), and when a negative pulse current is output, the diode 19 (18A) is output.
(19A). As a result, currents in both positive and negative directions can be output from one slave output circuit in a time-sharing manner, which has the effect of reducing the size of the circuit and reducing the cost. (5) The driving circuit 10 outputs a negative pulse current when the driving transistor T1 of the upper arm shifts to the reverse recovery operation, and drives when the driving transistor T2 of the lower arm shifts to the reverse recovery operation. A negative pulse current is output from the circuit 10A. Therefore, the electric charges accumulated in the collector regions of the driving transistors T1 and T2 are quickly extracted from the respective base terminals by the negative current, so that the electric charges staying in the collector regions are eliminated, and the driving transistors T1 and T2 are turned off. State. As a result, the driving transistors T1 and T2
A large through current is prevented from flowing from the collector terminal of the transistor to the emitter terminal, eliminating unnecessary loss and preventing the drive transistor that is not performing reverse recovery operation from being destroyed by the through current. Is done.

The above-described N-type MOS switch 21A of FIG.
The opening / closing timing of the switch 23A is the same as the opening / closing timing of the switch 23A, but the opening / closing control of only the switch 23A as shown in FIG. 4 may be performed while the N-type MOS switch 21A remains on.

The opening / closing timing of the N-type MOS switch 20 in FIG. 4 is the same as the opening / closing timing of the switch 23, but only the switch 23 is controlled as shown in FIG. You may make it.

In the above description, the diodes 18 and 1
9 (18A and 19A) are connected in series so as to be opposite to each other, and an N-type MOS
Switches 20 and 21 (20A and 21A) were connected. Instead, diodes 18 and 19 (18A
And 19A) may be connected in parallel in opposite directions, and N-type MOS switches 20 and 21 (20A and 21A) may be connected in series with the respective diodes.

In the above description, the driving transistor T2 of the lower arm at the timing t22 in FIG.
Is turned off, and when the potential at point P in FIG. 1 becomes higher than the potential of the base terminal of the driving transistor T1 of the upper arm, the base from the emitter terminal (output terminal 25) of the driving transistor T1 via the switch 23 of the upper arm. Terminal
(Output terminal 24) to supply a current to the driving transistor T1.
Was turned on in the opposite direction. As a result, the circulating current flows in the direction B in FIG. Instead, at timing t2
During the period from 2 to t23, the N-type MOS switch 21 is turned on, and the emitter terminal (output terminal 25) of the driving transistor T1 → secondary winding 72 → diode 18 → N-type MOS switch 21 → base terminal (output terminal 24) )
The driving transistor T1 may be turned on in the reverse direction.

-Second Embodiment- A second embodiment will be described with reference to FIG. FIG.
FIG. 6 is a diagram illustrating a drive circuit according to a second embodiment of the present invention. In FIG. 5, the circuit on the primary side of the transformer 17 is the same as that of the first embodiment, and the description is omitted.

On the opposite side of the secondary winding 72 of the transformer 17 from the dots, the N-type MOS switches 26 and 2 are connected so that the connections of the drain terminal and the source terminal thereof are opposite to each other.
7 are connected in series. Control signals from the control circuit 28 are input to the gate terminals of the N-type MOS switches 26 and 27, respectively. The dot side of the secondary winding 72 is connected to the control circuit 28.

In FIG. 5, when a current in a positive direction (upward toward the dot side in FIG. 5) is output from the secondary winding 72, the N-type MOS switch 26 is turned on by the control circuit 28. The control circuit 28 further turns on the N-type MOS switch 27 when a positive potential is induced on the dot side of the secondary winding 72, and turns on when a negative potential is induced on the dot side of the secondary winding 72. Next, the N-type MOS switch 27 is turned off. As a result, a positive pulse current is output from the output terminal 24.

On the other hand, a negative direction from the secondary winding 72 (FIG. 5)
When a current is output from the dot side (downward from the dot side), the control circuit 28 turns on the N-type MOS switch 27.
The control circuit 28 further turns on the N-type MOS switch 26 when a negative potential is induced on the dot side of the secondary winding 72, and turns on when a positive potential is induced on the dot side of the secondary winding 72. Then, the N-type MOS switch 26 is turned off. As a result, a negative pulse current is output from the output terminal 24.

FIG. 6 is a timing chart showing the operation timing of the current control type element driving device according to the second embodiment. Note that the reference numerals of the transformers, switches, and the like that constitute the lower arm drive circuit are denoted by the same reference numerals as those used in the upper arm drive circuit, with A added. In FIG. 6, a current waveform Ip is a waveform of a current flowing through each of the primary windings 71 and 71A of the drive circuit. As in the first embodiment, the primary windings 71 and 71A are connected regardless of the drive timing of the drive transistors T1 and T2.
A pulse-shaped current having a frequency of about 300 kHz flows.

The control circuit 28A of the lower arm turns on the N-type MOS switch 26A at the timing t21 when the drive transistor T2 is turned on. The control circuit 28A further turns on the N-type MOS switch 27A when a positive potential is induced on the dot side of the secondary winding 72, and turns on the N-type MOS switch 27 when no positive potential is induced.
Turn A off. As a result, a pulsed current flows from the base terminal to the emitter terminal of the driving transistor T2, and the driving transistor T2 is turned on by the continuously applied pulsed current. Since the N-type MOS switch 27A is turned on at the timing of outputting a pulsed current in the positive direction, no forward drop loss occurs due to the built-in diode 270A. When a negative potential is induced on the dot side of the secondary winding 72A, the N-type MOS switch 2
Since 7A is turned off, no pulsating current flows due to the rectifying action of the built-in diode 270A.

At time t22 when the driving transistor T2 is turned off, the control circuit 28A turns off the N-type MOS switch 26A. Since no pulse current is supplied to the base terminal of the driving transistor T2, the driving transistor T2 is turned off. When the driving transistor T2 is turned off and the potential at the point P in FIG. 1 becomes higher than the potential of the base terminal of the driving transistor T1 in the upper arm, the N-type MOS switch 2 in the upper arm
6, the emitter terminal (output terminal 25) of the driving transistor T1 of the upper arm → the built-in diode 270 → the N-type MOS switch 26 → the secondary winding 7
2 → Current flows to the base terminal (output terminal 24), and the driving transistor T1 turns on in the reverse direction.

The control circuit 28 of the upper arm turns on the N-type MOS switch 27 at the timing t23 when the driving transistor T2 of the lower arm is turned on again. The control circuit 28 further controls the N-type MOS switch 26 when a negative potential is induced on the dot side of the secondary winding 72.
A is turned on, and if not induced, the N-type MOS switch 26A
Turn off. As a result, a pulse-like current flows from the base terminal of the driving transistor T1, and the electric charge accumulated in the driving transistor T1 is extracted. N-type M at the timing of outputting a pulsed current in the negative direction
Since the OS switch 26 is turned on, the built-in diode 2
No forward drop loss by 60 occurs. When a positive potential is induced on the dot side of the secondary winding 72, an N-type MO
Since the S switch 26 is turned off, the built-in diode 26
No pulsating current flows due to the rectification of zero.

The pulse current for extracting charges is at least one pulse. The control circuit 28 determines the timing t
At time t24 after 3.3 μsec (corresponding to one pulse) elapses from 23, the N-type MOS switch 27 is turned off. Thus, no negative current is applied to the base terminal of the driving transistor T1.

On the other hand, the control circuit 28A of the lower arm switches the N-type MOS switch 2 at the timing t23.
Turn on 6A. When a pulsed current flows from the base terminal to the emitter terminal of the driving transistor T2, the driving transistor T2 is turned on again. At point P, a current flows in the direction A again, and the driving transistor T1
Enters the reverse recovery operation. At this time, since the electric charge in the driving transistor T1 of the upper arm is reduced as described above, the through current Z does not flow.

In the above description, an example has been described in which the charge remaining in the drive transistor T1 of the upper arm is extracted when the drive transistor T2 of the lower arm is turned on and off. The same applies to the case where the charge remaining in the drive transistor T2 of the lower arm is extracted when the drive transistor T1 is turned on and off.

According to the second embodiment described above,
The following effects can be obtained. (1) The N-type MOS switch 26A is connected to the side of the secondary winding 72A of the transformer 17A of the driving circuit opposite to the dot so that the connection of the drain terminal and the connection of the source terminal are opposite to each other.
And 27A are connected in series. When a positive current is output from the secondary winding 72A of the transformer 17A, when the control circuit 28A turns on the N-type MOS switch 26A and a positive potential is induced on the dot side of the secondary winding 72A. When the N-type MOS switch 27A is turned on and a negative potential is induced on the dot side of the secondary winding 72A, the N-type MOS switch 27A is turned on.
The S switch 27A was turned off. As a result, the N-type M
Since the OS switch 27A is turned on, a forward drop loss due to the built-in diode 270 does not occur. Also,
When outputting a negative current from the secondary winding 72 of the transformer 17, the control circuit 28
Is turned on, and when a negative potential is induced on the dot side of the secondary winding 72, the N-type MOS switch 26 is turned on,
When a positive potential is induced on the dot side of the secondary winding 72, N
The type MOS switch 26 is turned off. As a result, the N-type MOS switch 26 is turned on at the timing of outputting a pulsed current in the negative direction, so that the built-in diode 260 does not cause a forward drop loss. (2) As in the first embodiment, the number of elements connected to the secondary winding 72A is two (the N-type MOS switch 26A ,
27A), it is possible to obtain a small-sized and low-cost drive device for the current control element.

The N-type MOS switch 27A shown in FIG.
Is turned on when a positive potential is induced on the dot side of the secondary winding 72A, but the timing t21 to t2 when the switch 26A is turned on.
2. Only during the period from t23 to t25, it may be turned on in accordance with the positive potential induced on the dot side of the secondary winding 72A.

The N-type MOS switch 26 shown in FIG. 6 is turned on when a negative potential is induced on the dot side of the secondary winding 72, but is turned on when the switch 27 is turned on. t23 to timing t
Only during the period of 24 may be turned on in accordance with the negative potential induced on the dot side of the secondary winding 72.

In the above description, the driving transistor T is connected to the primary windings 71, 71A of the transformers 17, 17A.
1, regardless of the drive timing of T2, the frequency is about 300
Although a pulse-like current of kHz is applied, the frequency may be 200 KHz or 500 KHz. This frequency is set according to the lifetime of carriers in the transistors T1 and T2 to be driven.

Third Embodiment FIG. 7 is a diagram illustrating a driving circuit according to a third embodiment of the present invention. 7, the same components as those in FIG. 2 according to the first embodiment are denoted by the same reference numerals as those in FIG. 2, and description thereof will be omitted. The drive circuit according to the third embodiment is different from the drive circuit according to the first embodiment in that the secondary winding 7 of the transformer 17B constituting the drive circuit 10B of the upper arm is different.
The difference is that the polarity of 2B is reversed.

The diode 18 is connected to the secondary winding 72B of the transformer 17B so that the polarities thereof are opposite to each other.
And 19 are connected in series. N-type MOS switches 20 and 21 are connected in parallel to the diodes 18 and 19, respectively. The control circuit 22 is an N-type M
A control signal is output so that one of the OS switches 20 and 21 is turned on and the other is turned off. In FIG.
When a voltage is induced in the positive direction of the secondary winding 72B (upward against the dots in the figure), the N-type MOS switch 21
Is turned on and the N-type MOS switch 20 is turned off. When a voltage is induced in the negative direction of the secondary winding 72B, the N-type MOS switch 20 is turned on and the N-type MOS switch 21 is turned off.

The operation timing of the drive circuit 10B of the upper arm will be described. The operation timing of the circuit on the primary winding 71 side is the same as the operation timing (FIG. 3) of the drive circuit 10 according to the first embodiment described above. However, since the polarity of the secondary winding 72B is reversed, the driving circuit 10B
When the waveform of the exciting current flowing through the primary winding 71 of the transformer 17B of the
Is applied with a negative pulse current. The driving circuit 10
B at the timing when the waveform of the exciting current flowing through the primary winding 71 of the transformer 17B becomes smaller.
1, a positive pulse current is applied.

When the control circuit 22 on the side of the secondary winding 72B arranged with the opposite polarity outputs a positive voltage from the output terminal 24 to the potential of the output terminal 25, the control circuit 22 connects the gate terminal of the N-type MOS switch 20 to the gate terminal. L level, N-type MOS switch 2
A control signal of H level is output to one gate terminal, and a control signal for turning on the switch 23 is output. As a result, the N-type MOS switch 20 is turned off,
When the switch 21 is turned on, a rectifying operation is performed by the diode 18, and a positive voltage is output to the output terminal 24 via the switch 23. When the base terminal of the driving transistor T1 is connected to the output terminal 24 and the emitter terminal of the driving transistor T1 is connected to the output terminal 25, the base of the driving transistor T1 is reduced during the period when the current of the primary winding 71 decreases. A drive current flows from the terminal to the emitter terminal, and the drive transistor T1 is driven. During the period in which the current of the primary winding 71 increases, no positive current is applied to the output terminal 24 by the rectifying action of the diode 19.

On the other hand, when the control circuit 22 causes the output terminal 24 to output a negative voltage with respect to the potential of the output terminal 25, the control circuit 22 sets the gate terminal of the N-type MOS switch 20 to H level,
An L-level control signal is output to the gate terminal of the N-type MOS switch 21 and a control signal for turning on the switch 23 is output. Thereby, the N-type MOS switch 2
0 is turned on, the N-type MOS switch 21 is turned off, the rectifying operation is performed by the diode 19, and a negative voltage is output to the output terminal 24 via the switch 23. Output terminal 2
4, the base terminal of the driving transistor T1 is connected to the output terminal 25, and the emitter terminal of the driving transistor T1 is connected to the output terminal 25. During the period in which the current of the primary winding 71 increases, the secondary winding is operated by the transformer 17B. Line 72B
A current flows in a direction flowing into the output terminal 24 on the opposite side of the dot. During the period in which the current of the primary winding 71 decreases, a positive current is not applied to the output terminal 24 by the rectifying action of the diode 19.

The drive circuit 10A for driving the lower arm drive transistor T2 operates in the same manner as in the first embodiment, and a description thereof will be omitted. Since the secondary winding 72B of the transformer 17B of the upper arm has the opposite polarity to the secondary winding 72A of the transformer 17A of the lower arm, the secondary winding 72B is output from the output terminal 24 when the driving transistor T1 is driven. The phase of the positive pulse current is inverted from the phase of the positive pulse current output from the output terminal 24A when the driving transistor T2 is driven. On the other hand, the phase of the positive pulse current output from the output terminal 24 when the driving transistor T1 is driven, and the phase of the positive pulse current from the base of the driving transistor T2 to the output terminal 24A when the electric charge is extracted from the base of the driving transistor T2. The phase of the flowing negative pulse current coincides. Similarly, the phase of the positive pulse current output from the output terminal 24A when the driving transistor T2 is driven and the output terminal 24 from the base of the driving transistor T2 when the electric charge is extracted from the base of the driving transistor T1. And the phase of the negative pulse current flowing into the memory cell. The control circuit 22 of the drive circuit 10B
And the control circuit 22A of the drive circuit 10A are synchronously controlled by a timing signal (not shown).

In the third embodiment, when there is a reverse recovery charge at the time of reverse recovery remaining in the driving transistor T1, the driving transistor T1 is driven at the same timing as the driving timing of the driving transistor T2. By extracting the electric charge from the base terminal of the transistor T1, the time required for the current to flow in the direction from the collector to the emitter, that is, in the forward direction while the driving transistor T1 is in the off state is shortened.

FIG. 8 shows a circuit diagram of FIG. 1 using the drive circuit of FIG.
5 is a timing chart showing operation timings when driving control of the current control type element driving device of FIG. 8, a current waveform IpB is a waveform of a current flowing through the primary winding 71 of the drive circuit 10B. The current waveform IpA is a waveform of a current flowing through the primary winding 71A of the drive circuit 10A. The primary windings 71 and 71A have a frequency of about 30 regardless of the drive timing of the drive transistors T1 and T2.
A pulsed current of 0 kHz flows.

The control circuit 22A of the lower arm turns on the N-type MOS switch 21A at the time t21 when the drive transistor T2 is turned on,
The switch 20A is turned off and the switch 23A is turned on.
As a result, a pulse-like current flows continuously from the base terminal of the driving transistor T2 to the emitter terminal. The driving transistor T2 is a capacitive load, and the lifetime of the electric charge in the driving transistor T2 is sufficiently longer than the period of the pulsed current. Turned on. In this case, the secondary winding 72 of the transformer 17A
It is not necessary to provide a smoothing capacitor on the A side.

When the driving transistor T2 of the lower arm is turned on, a current flows in the direction A in FIG. At time t22 when the driving transistor T2 is turned off, the control circuit 22A determines that the N-type MOS switch 21A, the N-type MOS switch 20A, and the switch 23
Turn off all A. As a result, a positive pulse current is not supplied to the base terminal of the driving transistor T2, and a negative pulse current for turning off is applied, so that the driving transistor T2 is turned off. When the driving transistor T2 is turned off, the inductive load L1
Generates a back electromotive force, and this back electromotive force causes P P in FIG.
The potential at the point increases, and the potential at the point P becomes higher than the potential of the base terminal of the driving transistor T1 of the upper arm. At this time, the switch 23 of the upper arm is connected to the secondary winding 72B side and the base terminal (output terminal 24) of the driving transistor T1.
Are disconnected, but a current flows from the emitter terminal (output terminal 25) of the driving transistor T1 to the base terminal (output terminal 24) via the switch 23. As a result, the driving transistor T1 is turned on in the reverse direction, and the circulating current is reduced as shown in FIG.
Flows in the B direction.

The control circuit 22B of the upper arm turns off the N-type MOS switch 21, turns on the N-type MOS switch 20, and turns on the switch 23 at the timing t23 when the lower-arm driving transistor T2 is turned on again. To The switch 23 connects the secondary winding 72 </ b> B side to the base terminal (output terminal 24) of the driving transistor T <b> 1, and from the emitter terminal (output terminal 25) of the driving transistor T <b> 1 Terminal 2
No current to 4) is passed. As a result, at the timing t25, a pulse-like current flows from the base terminal of the driving transistor T1, and the driving transistor T1
The electric charge stored in is extracted. The pulse current for extracting charges is at least one pulse. At time t24 after 3.3 μs (corresponding to one pulse) has elapsed from timing t23, the control circuit 22
The N-type MOS switch 21, the N-type MOS switch 20, and the switch 23 are all turned off. Thus, no negative current is applied to the base terminal of the driving transistor T1.

On the other hand, the control circuit 22A of the lower arm switches the N-type MOS switch 2 at the timing t23.
1A is turned on, the N-type MOS switch 20A is turned off, and the switch 23A is turned on. At timing t25, 1 is applied from the base terminal to the emitter terminal of the driving transistor T2.
The driving transistor T2 is turned on again when the first pulsed current flows. At point P, a current flows again in the direction A, and the driving transistor T1 of the upper arm starts a reverse recovery operation. At this time, the driving transistor T1
The turn-on of the driving transistor T2 starts at the same timing as the timing t25 when a negative pulse-like current is applied to the base terminal of the driving transistor T1. Does not flow.

In the above description, the case where the driving transistor T2 of the lower arm is turned on and off by the driving circuit 10A, and the charge accumulated in the driving transistor T1 of the upper arm is extracted by the driving circuit 10B will be described as an example. As described above, the same applies to the case where the driving circuit T1 of the upper arm is turned on and off by the driving circuit 10B, and the charge remaining in the driving transistor T2 of the lower arm is extracted by the driving circuit 10A.

According to the third embodiment described above,
The following operation and effect are obtained in addition to the operation and effect of the first and second embodiments. That is, in the control circuit 22 of the drive circuit 10B and the control circuit 22A of the drive circuit 10A, the polarity of the secondary winding 72B of the transformer 17B constituting the drive circuit 10B of the upper arm and the drive of the lower arm are controlled. Since the polarity of the secondary winding 72A of the transformer 17A constituting the circuit 10A is reversed, the generation timing of the negative pulse current waveform applied to the base terminal of the driving transistor T1 and the base terminal of the driving transistor T2 Can be matched with the generation timing of the positive pulse current waveform applied to. As a result, a negative pulse can be applied to the base terminal of the driving transistor T1 at the timing t25 of the first positive pulse that turns on the driving transistor T2.
The driving transistor T2 is turned on in a state where the accumulated charge is extracted from the inside of the transistor 1, and it is possible to prevent a through current from flowing. Since the switching loss is reduced by effectively suppressing the through current, the device can be downsized.

In the drive circuits of FIGS. 2 and 7 described above, the secondary winding 72 of the transformer 17 (17A) (17B)
The diodes 18 (18A) and 1 on the (72A) and (72B) sides
9 (19A) are N-type MOS switches 20 (20
A) and body diodes built into 21 (21A) may be used.

In the above description, the polarity of the secondary winding 72 of the transformer 17 of the drive circuit 10 of the upper arm is changed with respect to the drive circuit of FIG. The polarity of the secondary winding 72B of the transformer 17B of 10B and the secondary winding 72A of the transformer 17A of the drive circuit 10A of the lower arm were reversed. Instead of changing the polarity of the secondary winding of the transformer of the drive circuit of one arm, the phases of the pulse currents having a frequency of about 300 kHz applied to the primary windings of the transformers of both drive circuits may be reversed. For example, N-type MOS switches 13 to
Any method, such as changing the drive timing of the DC voltage source 16, changing the polarity of the DC voltage source 12, or changing the polarity of the primary winding 71, may be used.

Further, in order to change the polarity of the secondary winding of the transformer of the drive circuit of one arm, the drive circuit 10A of the lower arm is different from the drive circuit of FIG. 2 according to the first embodiment.
Of the secondary winding 72A of the transformer may be changed.

Further, as shown in FIG. 9, with the polarity of the secondary winding 72B for driving the upper arm and the secondary winding 72A for driving the lower arm reversed, the primary winding 71B is driven. May be configured to use a transformer 17 </ b> C that shares the same.
In this case, since the upper arm drive circuit and the lower arm drive circuit can always be synchronized, pulses of positive and negative polarities can be obtained exactly at the same timing. Further, the size of the circuit can be reduced as compared with the case where two transformers are used.

Fourth Embodiment FIG. 10 is a diagram showing an example in which a three-phase motor is driven by using three sets of the current control type element driving devices of FIG. In FIG. 10, motor 30 is driven by three-phase currents of a U-phase, a V-phase, and a W-phase. Current control transistors 33 and 34 are connected in series between the power supply terminal P and the power supply terminal N to supply current to the U phase. Further, current control type transistors 35 and 36 are connected in series between the power supply terminal P and the power supply terminal N to supply a current to the V phase. Further, a current control type transistor 3 is connected between the power supply terminal P and the power supply terminal N.
7, 38 are connected in series and supply current to the W phase.

The control terminal (base) of the current control type transistor 33 constituting the upper arm for supplying current to the U phase is
The drive circuit 31 is connected. As the drive circuit 31, for example, the drive circuit 10B described above is used. A drive circuit 32 is connected to a control terminal (base) of a current control transistor 34 constituting a lower arm for supplying a current to the U-phase. As the drive circuit 32, for example, the drive circuit 10A described above is used.

Similarly, a drive circuit (not shown) similar to the drive circuit 10B is connected to the control terminals of the current control type transistors 35 and 37 for the V phase and the W phase. Also, current control transistors 36 and 38
Are connected to drive terminals (not shown) similar to the drive circuit 10A.

As described above, according to the fourth embodiment, the drive control for the three-phase motor is performed by using three sets of the drive circuits according to the first to third embodiments. be able to.

Fifth Embodiment FIG. 11 is a diagram showing an example in which a motor drive device based on an H-bridge is configured using two sets of drive circuits shown in FIG. FIG.
, Current control transistors 41 and 42 are connected in series between a power supply terminal P and a power supply
A current is supplied to the terminal L of 0. Further, current control type transistors 43 and 44 are connected in series between the power supply terminal P and the power supply terminal N, and supply a current to the terminal R of the motor 40. Here, a circuit that supplies current to the terminal L is called a left leg, and a circuit that supplies current to the terminal R is called a right leg.

A switch circuit 45 is connected to the control terminal (base) of the current control transistor 41 constituting the upper arm of the left leg. The switch circuit 45 is a circuit including the control circuit 22, the N-type MOS switches 20 and 21, and the diodes 18 and 19 of the drive circuit 10B described above. The switch circuit 45 is connected to the secondary winding 49 of the transformer 53.

A switch circuit 46 is connected to the control terminal (base) of the current control transistor 42 constituting the lower arm of the left leg. The switch circuit 46 includes the control circuit 22A of the drive circuit 10A, the N-type MOS switches 20A and 21A, and the diodes 18A and 19A.
Circuit. The switch circuit 46 includes a transformer 53
Are connected to the secondary winding 50.

The transformer 53 is a transformer that shares the primary winding 55 with the polarity of the secondary winding 49 for driving the upper arm and the secondary winding 50 for driving the lower arm reversed. is there. A primary circuit 57 is connected to the primary winding 55 of the transformer 53. The primary circuit 57 includes the oscillation circuit 11, the DC voltage source 12, and the N-type MOS of the drive circuit 10B.
This is a circuit including switches 13 to 16.

A switch circuit 47 is connected to a control terminal (base) of the current control transistor 43 constituting the upper arm of the right leg. The switch circuit 47 is a circuit including the control circuit 22, the N-type MOS switches 20 and 21, and the diodes 18 and 19 of the drive circuit 10B described above. The switch circuit 47 is connected to the secondary winding 59 of the transformer 54.

A switch circuit 48 is connected to the control terminal (base) of the current control transistor 44 constituting the lower arm of the right leg. The switch circuit 48 includes the control circuit 22A of the drive circuit 10A, the N-type MOS switches 20A and 21A, and the diodes 18A and 19A.
Circuit. The switch circuit 48 includes a transformer 54
Are connected to the secondary winding 60.

The transformer 54 is a transformer that shares a primary winding 56 with the polarity of the secondary winding 59 for driving the upper arm and the secondary winding 60 for driving the lower arm reversed. is there. However, the polarity of the secondary winding 59 of the transformer 54 is configured to be opposite to the polarity of the secondary winding 49 of the transformer 53 described above. Further, the polarity of the secondary winding 60 of the transformer 54 is configured to be opposite to the polarity of the secondary winding 50 of the transformer 53 described above. The polarity of the primary winding 56 of the transformer 54 is the same as the polarity of the primary winding 55 of the transformer 53 described above. A primary side circuit 58 is connected to a primary winding 56 of the transformer 54. The primary circuit 58 includes the oscillation circuit 11, the DC voltage source 12, and the N-type MOS of the drive circuit 10B.
This is a circuit including switches 13 to 16.

The operation of the motor drive device using the H-bridge shown in FIG. 11 will be described. When the current control type transistors 41 and 44 are turned on in the forward direction and the current control type transistors 42 and 43 are off, a drive current in the direction indicated by A in FIG. Next, when the current control type transistors 41 and 44 are turned off and all the current control type transistors 41 to 44 are turned off, the motor 40
Cannot be stopped suddenly, the current control transistors 42 and 43 are turned on in the reverse direction, and a circulating current flows in the direction indicated by B in the figure.

When the current control type transistors 41 and 44 are turned on in such a state, the secondary winding 49 of the left leg and the secondary winding 60 of the right leg are configured to have the same polarity. The timings of the positive pulses applied to the current control transistors 41 and 44 are exactly the same in phase. Thereby, the current control type transistor 41
And 44 are turned on at the same timing.

If the timing of turning on the current control type transistors 41 and 44 is shifted, the current control type transistors 41 and 43 of the upper arm of both the left and right legs are transiently turned on, and the lower side of both the left and right legs are turned on. There is a possibility that the current control type transistors 42 and 44 of the arm may be turned off. In such a case, the terminal L and the terminal R of the motor 40 are short-circuited, the voltage between both terminals becomes 0, and the drive current is distorted, so that the drive of the motor 40 cannot be accurately controlled. .

Further, the secondary winding 49 of the upper arm and the secondary winding 50 of the lower arm constituting the left leg, and the secondary winding 59 of the upper arm and the secondary winding of the lower arm constituting the right leg. Since the windings 60 are configured to have opposite polarities, when the current control type transistors 41 and 44 are turned on, the current control type transistors 41 and 44 are turned on at the same timing as the application timing of the positive pulse for driving the current control type transistor 41. A negative pulse for extracting charge is applied to the transistor 42. Similarly, a negative pulse for extracting a charge is applied to the current control transistor 43 at the same timing as the application timing of the positive pulse for driving the current control transistor 44.

The upper arm secondary winding 49 (59)
And the secondary winding 50 (60) of the lower arm are reversed in polarity, so that the current control transistor 41 of the upper arm is
When the (43) is driven, the phase of the positive pulse current output from the switch circuit 45 (47) and when the current control transistor 42 (44) of the lower arm is driven, the switch circuit 46 (48) is driven. ) Is inverted from the phase of the positive pulse current output from (1).

As described above, according to the fifth embodiment, the following operation and effect can be obtained. (1) In a motor drive device using an H bridge, a current control transistor 4 constituting an upper arm of a left leg
1 and the current control transistor 44 constituting the lower arm of the right leg are driven at exactly the same drive timing. Further, the current control transistor 43 forming the upper arm of the right leg and the current control transistor 42 forming the lower arm of the left leg are driven at exactly the same drive timing. This prevents the current control type transistors of both the left and right legs from being simultaneously turned on at the same time transiently, so that the drive of the motor 40 can be accurately controlled with the drive current without distortion. (2) In both the left and right legs, the secondary winding of the upper arm and the secondary winding of the lower arm are configured to have opposite polarities, respectively. At the same timing as the application timing of the driving positive pulse current, a negative pulse current for extracting charges is applied to the other current control transistor of the upper and lower arms. As a result, as in the third embodiment, a through current between the upper and lower arms can be prevented.

The correspondence between each component in the claims and each component in the embodiment of the invention will be described. The emitter terminal is a drive terminal, the drive transistors T1 and T2 are current control transistors, The base terminal is the control terminal and the switch 23 (built-in diode 27
0, N-type MOS switch 26 and secondary winding 72) as protection means, drive circuit 10 as pulse current generating means, control circuit 22 (28) as control means, oscillation circuit 11 and N
The type MOS switches 13 to 16 serve as AC generation means, the diodes 18 and 19 and the N-type MOS switches 20 and 21 serve as rectification means, the N-type MOS switch 13 serves as a first switch, and the N-type MOS switch 16 serves as a second switch. N-type MOS switch 14 is the third switch, N-type MOS switch 15 is the fourth switch, oscillation circuit 11 is the switch control means, diode 18 (built-in diode 260).
Is the first rectifier, the diode 19 (built-in diode 270) is the second rectifier, and the N-type MOS switch 20 is
(N-type MOS switch 26) is the N-type M
The OS switch 21 (N-type MOS switch 27) serves as a sixth switch, the control circuit 22 (control circuit 28) serves as second switch control means, the drive transistor T1 serves as a first current control transistor, and the drive transistor T1 serves as a first current control transistor. The transistor T2 is a second current control type transistor, and the driving circuits 10 and 10B
Is the first pulse current generating means, and the driving circuit 10A is the second pulse current generating means.
The control circuit 22 (28) serves as the first control means, the control circuit 22A (28A) serves as the second control means, the transformer 17B serves as the first transformer,
A is the oscillation circuit 11 and the N-type MOS in the second transformer.
The switches 13 to 16 serve as first AC generation means, and the oscillation circuit 11A and the N-type MOS switches 13A to 16A serve as second AC generation means.
Diodes 18 and 19 and N-type M
The OS switches 20 and 21 serve as first rectifiers, and the diodes 18A and 19A and the N-type MOS switches 20A and 2
1A is a rectifier, the secondary winding 72B is a first secondary winding, the secondary winding 72A is a second secondary winding, the motor 40 is an inductive load, the primary circuit 57, the transformer 53 and a switch circuit 45 are connected to the first pulse current generating means as a primary circuit 57, a transformer 53, and a switch circuit 46.
However, the primary circuit 58, the transformer 54, and the switch circuit 47 are provided in the second pulse current generating means, and the primary circuit 58, the transformer 54, and the switch circuit 47 are provided in the third pulse current generating means. Pulse current generating means,
Each corresponds.

[Brief description of the drawings]

FIG. 1 is a diagram illustrating a current control type element driving device according to a first embodiment.

FIG. 2 is a diagram illustrating a driving circuit of FIG. 1;

FIG. 3 is a timing chart showing operation timings of the drive circuit of FIG. 2;

FIG. 4 is a timing chart illustrating operation timings of the current control type element driving device.

FIG. 5 is a diagram illustrating a drive circuit according to a second embodiment.

FIG. 6 is a timing chart showing operation timings of the current control type element driving device according to the second embodiment.

FIG. 7 is a diagram illustrating a drive circuit according to a third embodiment.

8 is a timing chart showing operation timing when driving control of the current control type element driving device using the driving circuit shown in FIG. 7;

FIG. 9 is a diagram illustrating a transformer that shares a primary winding with the polarity of the secondary winding for driving the upper arm and the secondary winding for driving the lower arm reversed.

FIG. 10 is a diagram showing an example in which a three-phase motor is driven by using three sets of current control type element driving devices.

FIG. 11 is a diagram illustrating an example in which a motor drive device using an H-bridge is configured using two sets of drive circuits.

[Explanation of symbols]

10, 10A, 10B ... drive circuit, 11, 11A ...
Oscillation circuit, 12, 12A DC voltage source, 13 to 16, 13
A-16A, 20,20A, 21,21A, 26,26A, 2
7,27A ... N-type MOS switch, 17,17A, 17B,
17C, 53, 54 ... pulse transformer, 18, 18A, 1
9, 19A ... diode, 22, 22A, 28, 28A ... control circuit, 23, 23A ... switch, 24, 24A, 25,
25A: output terminal, 30, 40: motor, 45 to 48 ...
Switch circuit, 55, 56, 71, 71A ... primary winding,
57, 58 ... primary side circuit, 49, 50, 59, 60, 72,
72A, 72B: secondary winding, 260, 260A, 270, 2
70A: Body diode, T1, T2, 33-38, 4
1 to 44: driving transistor, L1: inductive load,

 ────────────────────────────────────────────────── ─── Continuing on the front page (72) Inventor Hiroyuki Kaneko 2 Takaracho, Kanagawa-ku, Yokohama-shi, Kanagawa Prefecture F-term (reference) 5H007 CA02 CB02 CB04 CB05 CC07 CC32 DB07 EA02 5J055 AX27 AX44 AX64 BX16 CX20 DX13 EX04 EX29 EY07 EY12 EZ15 FX10 FX12 FX33 GX01

Claims (13)

[Claims] A current control transistor for supplying a drive current to an inductive load connected to a drive terminal, wherein the current control transistor is turned on in a direction opposite to a direction in which the inductive load is driven. A current control type element driving device comprising a protection means for supplying a current due to a back electromotive force generated from the inductive load to a control terminal of the current control type transistor, wherein a positive pulse is applied to the control terminal of the current control type transistor. A pulse current generating means for supplying one of a current and a negative pulse current; and the positive pulse current being continuously turned on during a period in which the current control transistor is turned on in a direction for driving the inductive load. The negative pulsed current is supplied to the control terminal, and the negative pulse-shaped current is suppressed at a point in time when the current control type transistor reversely recovers from the on state in the reverse direction. Current-controlled element driving apparatus, characterized in that it comprises a control means for controlling the pulse current generating means to supply to the terminal. 2. The current controlling element driving device according to claim 1, wherein said pulse current generating means alternately applies both ends of an output of a DC voltage source from both ends of a primary winding of a transformer in both positive and negative directions. A drive device for a current control element, comprising: a generation unit; and a rectification unit that rectifies positive and negative voltages induced in a secondary winding of the transformer in a time-division manner. 3. The current control type element driving device according to claim 2, wherein said AC generating means applies both ends of an output of said DC voltage source from both ends of a primary winding of said transformer in a positive direction. A first switch and a second switch to be connected; a third switch and a fourth switch to connect both ends of the output of the DC voltage source from both ends of the primary winding of the transformer in a negative direction; The longer one of the time for connecting to apply in the positive direction and the time for connecting to apply in the negative direction is shorter than the sum of the other time and the time of not connecting to any of the positive and negative directions. And a switch control means for controlling opening and closing of the first to fourth switches. 4. The current controlling element driving device according to claim 2, wherein the rectifying means includes a first rectifying element and a second rectifying element connected in series such that polarities thereof are opposite to each other. A rectifying element; a fifth switch and a sixth switch connected in parallel to the first rectifying element and the second rectifying element, respectively; and a direction in which the current control transistor drives the inductive load. The fifth rectifying device switches the rectifying direction by the first rectifying element and the second rectifying element during a period during which the current control transistor is turned on and when the current control type transistor reversely recovers from a state in which the transistor is turned on in the reverse direction. And a second switch control means for controlling the opening and closing of the sixth switch. 5. The current control type element driving device according to claim 2, wherein the rectifying means includes a first rectifying element and a fifth switch connected in series, and a rectifier connected in series with the fifth switch. The second rectifier and the sixth switch are connected in parallel so that the polarities of the first rectifier and the second rectifier are opposite, and the current control transistor drives the inductive load. The rectification direction of the first rectifying element and the rectifying direction of the second rectifying element is switched between a period in which the current control type transistor is turned on in a reverse direction and a point in time when the current control type transistor reversely recovers from the state in which the current control transistor is turned on. A drive device for a current control type element, comprising: second switch control means for controlling the opening and closing of the fifth switch and the sixth switch. 6. A first drive motor for supplying a drive current in a first direction to an inductive load on the upper arm side and for causing a current due to a back electromotive force generated from the inductive load to flow in a reverse direction.
A current-controlled transistor, which is connected in series with the first current-controlled transistor;
The first arm is located on the lower arm side with respect to the inductive load.
A second current-controlled transistor that supplies a drive current in a second direction different from the direction of the first current-controlled transistor and flows a current due to a back electromotive force generated from the inductive load in a reverse direction; First pulse current generating means for supplying one of a positive pulse current and a negative pulse current to a control terminal; and the first current control transistor is turned on so as to drive the inductive load. A point in time during which the positive pulsed current is continuously supplied to the control terminal of the first current control type transistor during a period, and the first current control type transistor reversely recovers from the ON state in the reverse direction A first control means for controlling the first pulse current generating means so as to supply the negative pulse current to a control terminal of the first current control type transistor; A second pulse current generating means for supplying one of a positive pulse current and a negative pulse current to a control terminal of the current control transistor, wherein the second current control transistor drives the inductive load A state in which the positive pulsed current is continuously supplied to the control terminal of the second current control type transistor during a period in which the second current control type transistor is turned on in the opposite direction, and the second current control type transistor is turned on in the reverse direction. And a second control means for controlling the second pulse current generation means so as to supply the negative pulse current to the control terminal of the second current control type transistor at the time of reverse recovery from Characteristic drive device for current control type element. 7. The current controlling element driving device according to claim 6, wherein said first pulse current generating means and said second pulse current generating means have primary and secondary ends of a transformer connected to both ends of a DC voltage source. A current control element comprising alternating current generating means for alternately applying positive and negative voltages from both ends of the wire, and rectifying means for rectifying positive and negative voltages induced in the secondary winding of the transformer in a time division manner. Drive. 8. The current control type element driving device according to claim 7, wherein the first control means and the second control means determine whether or not one of the current control type transistors is on / off. A drive device for a current control element, wherein each of the rectifiers is controlled so that the polarity of the pulse current supplied to the control terminal of the current control transistor is switched. 9. A method according to claim 1, wherein a driving current is supplied to the inductive load on the upper arm side in a first direction and a current caused by a back electromotive force generated from the inductive load flows in a reverse direction.
A current-controlled transistor, which is connected in series with the first current-controlled transistor;
The first arm is located on the lower arm side with respect to the inductive load.
A second current control transistor that supplies a drive current in a second direction different from the direction of the above, and flows a current due to a back electromotive force generated from the inductive load in a reverse direction; and the first current control transistor First pulse current generating means for supplying a positive pulse current to a control terminal of the first current control transistor during a period in which the inductive load is turned on, and the second current control transistor And a second pulse current generating means for supplying a positive pulse-like current to a control terminal of the second current control transistor during a period in which the first pulse is turned on to drive the inductive load. The current generating means and the second pulse current generating means transmit pulse-shaped currents whose phases are inverted with each other to the first current control transistor and the second current control transistor. Current control element drive device, characterized in that it is synchronized to supply respectively register. 10. The current control type element driving device according to claim 9, wherein the first pulse current generation means reverses the state in which the first current control type transistor is turned on in the reverse direction. At the time of recovery, a negative pulse-like current is further supplied to the control terminal of the first current control type transistor, and the second pulse current generating means turns on the second current control type transistor in the reverse direction. A negative pulse-like current is further supplied to the control terminal of the second current control type transistor at the time of reverse recovery from the state in which the first pulse current generation means and the second pulse current generation means The phases of the positive pulse-like current by the first pulse current generation means and the negative pulse-like current by the second pulse current generation means coincide with each other. A pulsed current in which the phases of the negative pulsed current and the positive pulsed current generated by the second pulsed current generating means match each other is supplied to the first current-controlled transistor and the second current-controlled transistor, respectively. A driving device for a current control type device, comprising: 11. The current control type element driving device according to claim 10, wherein said first pulse current generating means includes: a first transformer;
First AC generating means for alternately applying both ends of the output of the DC voltage source from both ends of the primary winding of the first transformer in both positive and negative directions, and positive and negative voltages induced in the secondary winding of the first transformer A first rectifier for rectifying the second pulse current in a time-division manner, wherein the second pulse current generator has a second transformer,
Second AC generating means for alternately applying both ends of the output of the DC voltage source from both ends of the primary winding of the second transformer in both positive and negative directions, and positive and negative voltages induced in the secondary winding of the second transformer And a second rectifier for rectifying the phase of the voltage in a time division manner. The phase of the voltage induced in the secondary winding of the first transformer and the phase of the voltage induced in the secondary winding of the second transformer Is a drive device for a current control type device, which is inverted. 12. The current control type element driving device according to claim 11, wherein the first transformer and the second transformer are constituted by one transformer, and the transformer includes a shared primary winding and a common primary winding. A first secondary winding for inducing positive and negative voltages, and a second secondary winding for inducing positive and negative voltages whose phases are inverted with respect to the positive and negative voltages induced by the first secondary winding. A driving device for a current control type element, comprising: 13. The drive device for a current control type device according to claim 9, wherein the second position is located on an upper arm side with respect to the inductive load.
A third current control transistor that supplies a drive current in the direction of, and flows a current due to a back electromotive force generated from the inductive load in a reverse direction, and is connected in series with the third current control transistor.
The first arm is located on the lower arm side with respect to the inductive load.
A fourth current-controlled transistor that supplies a direction drive current in the same direction and flows a current due to a back electromotive force generated from the inductive load in the reverse direction; and the third current-controlled transistor drives the inductive load. Third pulse current generating means for supplying a positive pulse current to a control terminal of the third current control transistor during a period in which the transistor is turned on in the direction; and the fourth current control transistor drives the inductive load. And a fourth pulse current generating means for supplying a positive pulse current to a control terminal of the fourth current control transistor during a period in which the first pulse current generating means is turned on. The pulse current generating means of (4) comprises: (1) the phase of the positive pulse current generated by the first pulse current generating means and the phase of the positive pulse current generated by the second pulse current generating means Rolling and, (2) the first
(3) the phase of the positive pulse current generated by the pulse current generating means coincides with the phase of the positive pulse current generated by the fourth pulse current generating means; The phase of the positive pulse current generated by the fourth pulse current generator is inverted, and (4) the positive pulse current generated by the third pulse current generator and the positive pulse generated by the second pulse current generator A current-control-type element driving device, wherein a pulse-like current having the same phase is supplied to each of the first to fourth current-control-type transistors.