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EP0113451B1 - Inverter with a load circuit comprising a series resonant circuit and a discharge lamp - Google Patents

Inverter with a load circuit comprising a series resonant circuit and a discharge lamp Download PDF

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Publication number
EP0113451B1
EP0113451B1 EP83112488A EP83112488A EP0113451B1 EP 0113451 B1 EP0113451 B1 EP 0113451B1 EP 83112488 A EP83112488 A EP 83112488A EP 83112488 A EP83112488 A EP 83112488A EP 0113451 B1 EP0113451 B1 EP 0113451B1
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EP
European Patent Office
Prior art keywords
inverter
voltage
capacitor
series resonant
resonant circuit
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Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
Expired
Application number
EP83112488A
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German (de)
French (fr)
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EP0113451A1 (en
Inventor
Peter Krummel
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Siemens AG
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Siemens AG
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Priority to AT83112488T priority Critical patent/ATE30290T1/en
Publication of EP0113451A1 publication Critical patent/EP0113451A1/en
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Publication of EP0113451B1 publication Critical patent/EP0113451B1/en
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    • H—ELECTRICITY
    • H05—ELECTRIC TECHNIQUES NOT OTHERWISE PROVIDED FOR
    • H05B—ELECTRIC HEATING; ELECTRIC LIGHT SOURCES NOT OTHERWISE PROVIDED FOR; CIRCUIT ARRANGEMENTS FOR ELECTRIC LIGHT SOURCES, IN GENERAL
    • H05B41/00—Circuit arrangements or apparatus for igniting or operating discharge lamps
    • H05B41/14—Circuit arrangements
    • H05B41/26—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC
    • H05B41/28—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters
    • H05B41/295—Circuit arrangements in which the lamp is fed by power derived from DC by means of a converter, e.g. by high-voltage DC using static converters with semiconductor devices and specially adapted for lamps with preheating electrodes, e.g. for fluorescent lamps
    • H05B41/298—Arrangements for protecting lamps or circuits against abnormal operating conditions
    • H05B41/2981—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions
    • H05B41/2985—Arrangements for protecting lamps or circuits against abnormal operating conditions for protecting the circuit against abnormal operating conditions against abnormal lamp operating conditions
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10—TECHNICAL SUBJECTS COVERED BY FORMER USPC
    • Y10S—TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y10S315/00—Electric lamp and discharge devices: systems
    • Y10S315/07—Starting and control circuits for gas discharge lamp using transistors

Definitions

  • the invention relates to an inverter with the features of the preamble of claim 1.
  • the object of the invention is therefore to avoid impermissible overvoltages.
  • the solution according to the invention is characterized in an inverter of the type mentioned at the outset by the features of the second part of the main claim.
  • each series resonance circuit has to be assigned such a parallel branch with voltage-dependent resistance.
  • the characteristic of a voltage-dependent resistor has a first range in which practically no current flows up to a certain limit voltage. This is followed by the current-carrying area in which the characteristic curve is to run as steeply as possible: the voltage-dependent resistor therefore blocks practically up to the limit voltage in both directions and has a practically very low resistance for voltages above it. With a corresponding adjustment of the limit voltage of the voltage-dependent resistor to the data of the inverter and its load circuit, it can be achieved that the voltage-dependent resistor works in the current-carrying area when the lamp is ignited.
  • the voltage-dependent resistor is also dimensioned such that it carries practically no current when the lamp has ignited: the series resonant circuit is then damped by the lamp or completely ineffective.
  • the voltage on the components of the load circuit is limited to the lower operating voltage of the lamp.
  • the inverter W is connected via terminals w1, w2 to a step-up converter H, which in turn is fed by an AC voltage network N and which supplies the inverter with a DC voltage. Between the terminals w1, w2 there is a very large storage capacitor C6 and the series connection of the two controllable switches in the form of transistor V1, V2.
  • the load circuit Parallel to the switching path of V1 is the load circuit, which consists of a series connection of a reversing capacitor C1, a discharge lamp E with the heatable electrodes e1, e2, an inductor L and the primary winding t1 of a saturation transformer T; the electrodes e1, e2 of the lamp E are connected in series via a capacitor C, this capacitor C and the inductor L determining the resonance frequency f o .
  • the two transistors V1, V2 are alternately turned on by a control set S, this control set containing secondary windings t2, t3 of the saturation transformer, from which the control voltages for the transistors are derived.
  • the operating frequency f B of the inverter is determined here by the dimensioning of the saturation transformer T in relation to the dimensioning of the inverter and its load circuit; it must always be above the resonance frequency of the load circuit, so that a currentless phase between the blocking of one transistor and the control of the other is ensured.
  • the voltage-dependent resistor R1 forms a parallel branch in series with a capacitor C4, which is connected in parallel with the series circuit comprising the inductor L, the saturation transformer T and the second transistor V2 of the inverter: C4 becomes C over conductive V2 and C1 charged from the storage capacitor C6 and reloaded in the same way when the V1 is conductive as soon as the limit voltage of R1 is exceeded.
  • the monitoring device for current-dependent disconnection of the inverter is connected to the capacitor C4: a thyristor V3 is used for disconnection, which is connected to DC voltage via the electrode e1 and to which a further secondary winding t4 of the saturation transformer T is connected in parallel via a diode D3.
  • the control path of this thyristor is connected via a switching diode D2 to an RC element R3, C5, which is connected in parallel with the aforementioned capacitor C4 via a resistor R2 and a diode D1.
  • thyristor V3 becomes conductive and short-circuits the winding t4, so that the transistors of the inverter no longer receive any control voltages.
  • the ignition capacitor C3, which is also parallel to V3, is short-circuited, the voltage of which initiates the start of the inverter via a switching diode D4. This state remains until the holding circuit of the thyristor is interrupted by replacing the lamp E.
  • the operating frequency can be shifted in the opposite direction up to the limit value f BG with the associated curve KRG.
  • the components must be dimensioned so that the highest operating frequency in question does not exceed this limit value, so that an operating point in the current-carrying region of the characteristic curve of the voltage-dependent resistor R1 is guaranteed.

Landscapes

  • Circuit Arrangements For Discharge Lamps (AREA)
  • Exchange Systems With Centralized Control (AREA)
  • Discharge-Lamp Control Circuits And Pulse- Feed Circuits (AREA)
  • Inverter Devices (AREA)
  • Telephonic Communication Services (AREA)
  • Casings For Electric Apparatus (AREA)
  • Materials For Medical Uses (AREA)

Abstract

In an inverter controlled with a firing unit connected to switches and defining an operating frequency, a resonant frequency of a series oscillating circuit of the inverter connected to one of the switches is placed below this operating frequency. Given this operating situation, a short of the d.c. voltage source is impossible. Given, for example, unfavorable component tolerances, however, the operating frequency can be moved close to the resonant frequency and cause impermissibly high voltages at the components. Such a voltage rise is limited according to the invention by means of a voltage-dependent resistor. It preferably lies in series with a capacitor and takes care of a voltage-dependent shift of the resonant frequency.

Description

Die Erfindung betrifft einen Wechselrichter mit den Merkmalen des Oberbegriffes von Anspruch 1.The invention relates to an inverter with the features of the preamble of claim 1.

Bei einem solchen, aus der DE-A-31 12 281 bekannten Wechselrichter ist darauf zu achten, daß die abwechselnd stromführenden Schalter niemals, auch nicht kurzzeitig, gleichzeitig Strom führen und dadurch die Gleichspannungsquelle kurzschließen; besonders wichtig ist die Einhaltung dieser Bedingung bei Verwendung von Halbleiterschaltern. Bei einem Wechselrichter der eingangs genannten Art wird daher die z. B. durch einen Sättigunqstransformator bestimmte Betriebsfrequenz des Wechselrichters bei Zündbetrieb über die Resonanzfrequenz des Reihenresonanzkreises gelegt: Der Wechselrichter ist dann induktiv belastet und der Strom durch einen Schalter wird zwangsläufig Null, bevor die Spannung durch Null geht und davon abhängig der andere Schalter durchgesteuert wird.In such an inverter, known from DE-A-31 12 281, care must be taken that the alternating current-carrying switches never, even not briefly, carry current at the same time and thereby short-circuit the DC voltage source; Compliance with this condition is particularly important when using semiconductor switches. In an inverter of the type mentioned, the z. B. determined by a saturation transformer operating frequency of the inverter in ignition mode above the resonance frequency of the series resonant circuit: the inverter is then loaded inductively and the current through a switch is inevitably zero before the voltage goes through zero and depending on that the other switch is turned on.

Verschiedene Ursachen, z. B. Ausfall einer von mehreren Lampen oder ungünstiges Zusammentreffen der Toleranzen von Bauelementen, können dazu führen, daß die Betriebsfrequenz des Wechselrichters dicht an die Resonanzfrequenz heranrückt, was - vor allem bei sehr verlustarmen Bauelementen des Reihenresonanzkreises - entsprechend hohe Spannungen zur folge hat, die nicht nur die Bauelemente des Wechselrichters sondern auch Menschen beim arbeiten an den Lampenfassungen gefährden können.Various causes, e.g. B. Failure of one of several lamps or unfavorable coincidence of the tolerances of components can lead to the operating frequency of the inverter coming close to the resonance frequency, which - especially with very low-loss components of the series resonant circuit - results in correspondingly high voltages that do not only the components of the inverter but also people when working on the lamp sockets.

Der Erfindung liegt daher die Aufgabe zugrunde, unzulässige Überspannungen zu vermeiden. Die erfindungsgemäße Lösung ist bei einem Wechselrichter der eingangs genannten Art gekennzeichnet durch die Merkmale des zweiten Teils des Hauptanspruchs.The object of the invention is therefore to avoid impermissible overvoltages. The solution according to the invention is characterized in an inverter of the type mentioned at the outset by the features of the second part of the main claim.

Speist der Wechselrichter mehrere Lampen mit zugeordneten Reihenresonanzkreisen im Parallelbetrieb, so ist jedem Reihenresonanzkreis ein derartiger Parallelzweig mit spannungsabhängigem Widerstand zuzuordnen.If the inverter feeds several lamps with assigned series resonance circuits in parallel operation, each series resonance circuit has to be assigned such a parallel branch with voltage-dependent resistance.

Die Kennlinie eines spannungsabhängigen Widerstandes weist einen ersten Bereich auf, in dem bis zu einer bestimmten Grenzspannung praktisch kein Strom fließt. Daran schließt sich der stromführende Bereich an, in dem die Kennlinie möglichst steil verlaufen soll: Der spannungsabhängige Widerstand sperrt also praktisch bis zu der Grenzspannung in beiden Richtung und hat für darüberliegende Spannungen einen praktisch sehr kleinen Widerstand. Bei entsprechender Abstimmung der Grenzspannung des spannungsabhängigen Widerstandes auf die Daten des Wechselrichters und seines Lastkreises läßt sich erreichen, daß der spannungsabhängige Widerstand bei Zündbetrieb der Lampe in dem stromführenden Bereich arbeitet.The characteristic of a voltage-dependent resistor has a first range in which practically no current flows up to a certain limit voltage. This is followed by the current-carrying area in which the characteristic curve is to run as steeply as possible: the voltage-dependent resistor therefore blocks practically up to the limit voltage in both directions and has a practically very low resistance for voltages above it. With a corresponding adjustment of the limit voltage of the voltage-dependent resistor to the data of the inverter and its load circuit, it can be achieved that the voltage-dependent resistor works in the current-carrying area when the lamp is ignited.

Der spannungsabhängige Widerstand ist ferner so bemessen, daß er praktisch keinen Strom führt, wenn die Lampe gezündet hat: Der Reihenresonanzkreis ist dann durch die Lampe bedämpft oder völlig unwirksam. Die Spannung an den Bauelementen des Lastkreises ist auf die niedrigere Brennspannung der Lampe begrenzt.The voltage-dependent resistor is also dimensioned such that it carries practically no current when the lamp has ignited: the series resonant circuit is then damped by the lamp or completely ineffective. The voltage on the components of the load circuit is limited to the lower operating voltage of the lamp.

Bei stromführenden spannungsabhängigem Widerstand - also bei Zündbetrieb - wird der mit ihm in Reihe geschaltete Kondensator wirksam und dadurch die Resonanzfrequenz des Reihenresonanzkreises verändert. Bei entsprechend steiler Kennlinie des spannungsabhängigen Widerstandes hat dann selbst eine Variation der Betriebsfrequenz des Wechselrichters in einem weiten Bereich nur eine sehr geringe Änderung der Zündspannung an der Lampe zur Folge. Dementsprechend kann man Bauelemente mit großer Toleranz zulassen, die außerdem nur eine entsprechend niedrige Spannungsfestigkeit zu haben brauchen.In the case of current-carrying, voltage-dependent resistance - that is to say during ignition operation - the capacitor connected in series with it becomes effective, thereby changing the resonance frequency of the series resonance circuit. With a correspondingly steep characteristic curve of the voltage-dependent resistance, even a variation in the operating frequency of the inverter over a wide range results in only a very slight change in the ignition voltage on the lamp. Accordingly, components with a large tolerance can be permitted, which also only need to have a correspondingly low dielectric strength.

Die Erfindung wird anhand eines Ausführungsbeispiels näher erläutert; es zeigen

  • FIG 1 die Schaltung eines Ausführungsbeispieles und
  • FIG 2 die Abhängigkeit zwischen Frequenz und Spannung an der Entladungslampe.
The invention is explained in more detail using an exemplary embodiment; show it
  • 1 shows the circuit of an embodiment and
  • 2 shows the dependence between frequency and voltage on the discharge lamp.

Der Wechselrichter W ist über Klemmen w1, w2 an einen Hochsetzsteller H angeschlossen, der seinerseits von einem Wechselspannungsnetz N gespeist wird und der dem Wechselrichter eine Gleichspannung liefert. Zwischen den Klemmen w1, w2 liegt ein sehr groß bemessener Speicherkondensator C6 und die Reihenschaltung der beiden steuerbaren Schalter in Form von TransistorertV1, V2. Parallel zur Schaltstrecke von V1 liegt der Lastkreis, der aus einer Reihenschaltung eines Umschwingkondensators C1, einer Entladungslampe E mit den heizbaren Elektroden e1, e2, einer Drossel L und der Primärwicklung t1 eines Sättigungstransformators T besteht; die Elektroden e1, e2 der Lampe E sind über einen Kondensator C in Reihe geschaltet, wobei dieser Kondenstor C und die Drossel L die Resonanzfrequenz fo bestimmen.The inverter W is connected via terminals w1, w2 to a step-up converter H, which in turn is fed by an AC voltage network N and which supplies the inverter with a DC voltage. Between the terminals w1, w2 there is a very large storage capacitor C6 and the series connection of the two controllable switches in the form of transistor V1, V2. Parallel to the switching path of V1 is the load circuit, which consists of a series connection of a reversing capacitor C1, a discharge lamp E with the heatable electrodes e1, e2, an inductor L and the primary winding t1 of a saturation transformer T; the electrodes e1, e2 of the lamp E are connected in series via a capacitor C, this capacitor C and the inductor L determining the resonance frequency f o .

Die beiden Transistoren V1, V2 werden durch einen Steuersatz S abwechselnd durchgesteuert, wobei dieser Steuersatz Sekundärwicklungen t2, t3 des Sättigungstransformators enthält, von denen die Steuerspannungen für die Transistoren abgeleitet werden. Die Betriebsfrequenz fB des Wechselrichters ist hier durch die Bemessung des Sättigungstransformators T im Verhältnis zur Bemessung des Wechselrichters und seines Lastkreises bestimmt; sie muß stets oberhalb der Resonanzfrequenz des Lastkreises liegen, damit eine stromlose Phase zwischen Sperren des einen Transistors und Aufsteuern des anderen gewährleistet ist.The two transistors V1, V2 are alternately turned on by a control set S, this control set containing secondary windings t2, t3 of the saturation transformer, from which the control voltages for the transistors are derived. The operating frequency f B of the inverter is determined here by the dimensioning of the saturation transformer T in relation to the dimensioning of the inverter and its load circuit; it must always be above the resonance frequency of the load circuit, so that a currentless phase between the blocking of one transistor and the control of the other is ensured.

Der spannungsabhängige Widerstand R1 bildet in Reihe mit einem Kondensator C4 einen Parallelzweig, der die Reihenschaltung aus Drossel L, Sättigungstransformator T und dem zweiten Transistor V2 des Wechselrichters parallel liegt: C4 wird so bei leitendem V2 über C und C1 aus dem Speicherkondensator C6 geladen und auf demselben Wege bei leitendem V1 umgeladen, sobald die Grenzspannung von R1 überschritten ist.The voltage-dependent resistor R1 forms a parallel branch in series with a capacitor C4, which is connected in parallel with the series circuit comprising the inductor L, the saturation transformer T and the second transistor V2 of the inverter: C4 becomes C over conductive V2 and C1 charged from the storage capacitor C6 and reloaded in the same way when the V1 is conductive as soon as the limit voltage of R1 is exceeded.

An den Kondensator C4 ist die Überwachungseinrichtung zur stromabhängigen Abschaltung des Wechselrichters angeschlossen: Zur Abschaltung dient ein Thyristor V3, der über die Elektrode e1 an Gleichspannung liegt und dem eine weitere Sekundärwicklung t4 des Sättigungstransformators T über eine Diode D3 parallel geschaltet ist. Die Steuerstrecke dieses Thyristors liegt über eine Schaltdiode D2 an einem RC-Glied R3, C5, das über einen Widerstand R2 und eine Diode D1 dem erwähnten Kondensator C4 parallel geschaltet ist. Erreicht somit die Spannung an C5 einen durch D2 bestimmten Grenzwert, dann wird Thyristor V3 leitend und schließt die Wicklung t4 kurz, so daß die Transistoren des Wechselrichters keine Steuerspannungen mehr erhalten. Zugleich wird auch der ebenfalls zu V3 parallel liegende Zündkondensator C3 kurzgeschlossen, dessen Spannung über eine Schaltdiode D4 den Start des Wechselrichters einleitet. Dieser Zustand bleibt bis zur Unterbrechung des Haltestromkreises des Thyristors durch auswechseln der Lampe E.The monitoring device for current-dependent disconnection of the inverter is connected to the capacitor C4: a thyristor V3 is used for disconnection, which is connected to DC voltage via the electrode e1 and to which a further secondary winding t4 of the saturation transformer T is connected in parallel via a diode D3. The control path of this thyristor is connected via a switching diode D2 to an RC element R3, C5, which is connected in parallel with the aforementioned capacitor C4 via a resistor R2 and a diode D1. If the voltage at C5 thus reaches a limit value determined by D2, thyristor V3 becomes conductive and short-circuits the winding t4, so that the transistors of the inverter no longer receive any control voltages. At the same time, the ignition capacitor C3, which is also parallel to V3, is short-circuited, the voltage of which initiates the start of the inverter via a switching diode D4. This state remains until the holding circuit of the thyristor is interrupted by replacing the lamp E.

Zur Erläuterung der Wirkung des spannungsabhängigen Widerstandes R, und des Kondensators C4 wird auf fIG 2 Bezug genommen: Dort ist auf der Ordinate die Spannung an der Entladungslampe UE aufgetragen, die zugleich die Spannung an dem Kondensator C des Reihenresonanzkreises ist. Auf der Abszisse ist die Frequenz f dargestellt.To explain the effect of the voltage-dependent resistor R and the capacitor C4, reference is made to fIG 2: there, the voltage on the discharge lamp U E is plotted on the ordinate, which is also the voltage on the capacitor C of the series resonant circuit. The frequency f is shown on the abscissa.

Mit KR1 ist zunächst der Spannungsverlauf an der Lampe bzw. an dem Kondensator C bei Zündbetrieb dargestellt, wenn alle Bauelemente die berechneten Werte haben: Der Wechselrichter arbeitet hierbei mit einer Betriebsfrequenz fe, zu der eine Lampenspannung UE1 gehört. Die Resonanzfrequenz sei f01 (bei verlustbehafteten Resonanzkreisen liegt die Resonanzfrequenz jedoch etwas rechts von dem eingezeichneten Wert und nicht im Maximum der Spannung am Kondensator). Diese Resonanzfrequenz ist nun aber infolge der Wirkung von R1 und C4 eine Funktion der Lampenspannung UE, und zwar in der Weise, wie dies die Kurve K2 in FIG 2 wiedergibt. Davon leitet sich die parallel nach rechts verschobene Kurve K1 ab, die die Abhängigkeit der Spannung UE von der Betriebsfrequenz fB zeigt:

  • Würde man z. B. statt der Betriebsfrequenz fS1 die niedrigere fB2 einstellen (die ohne die Erfindung eine entsprechend hohe Lampenspannung zur Folge hätte), so steigt die Lampenspannung entlang der Kurve K1 nur geringfügig auf den Wert UE2, weil sich gleichzeitig die Resonanzfrequenz entlang der Kurve K2 auf den Wert fo2 reduziert und damit Kurve KR2 maßgebend ist.
With KR1, the voltage curve at the lamp or at the capacitor C during ignition operation is initially shown when all components have the calculated values: The inverter operates here at an operating frequency fe, to which a lamp voltage U E1 belongs. The resonance frequency is f 01 (in the case of lossy resonance circuits, however, the resonance frequency is somewhat to the right of the value shown and not in the maximum of the voltage at the capacitor). However, due to the action of R1 and C4, this resonance frequency is now a function of the lamp voltage U E , in the manner in which the curve K2 in FIG. 2 shows. From this derives the curve K1, which is shifted parallel to the right and shows the dependence of the voltage U E on the operating frequency f B :
  • Would you z. B. Instead of the operating frequency f S1, set the lower f B2 (which would have resulted in a correspondingly high lamp voltage without the invention), the lamp voltage along the curve K1 increases only slightly to the value U E2 , because at the same time the resonance frequency along the curve K2 reduced to the value f o2 and therefore curve KR2 is decisive.

Eine Verschiebung der Betriebsfrequenz in umgekehrter Richtung ist bis zu dem Grenzwert fBG mit zugehöriger Kurve KRG zulässig. Die Bemessung der Bauelemente ist so vorzunehmen, daß die höchste in Betracht kommende Betriebsfrequenz diesen Grenzwert nicht übersteigt, damit ein Arbeitspunkt im stromführenden Bereich der Kennlinie des spannungsabhängigen Widerstandes R1 gewährleistet ist.The operating frequency can be shifted in the opposite direction up to the limit value f BG with the associated curve KRG. The components must be dimensioned so that the highest operating frequency in question does not exceed this limit value, so that an operating point in the current-carrying region of the characteristic curve of the voltage-dependent resistor R1 is guaranteed.

Nach dem Zünden der Lampe ist ihre Brennspannung UEB praktisch konstant. Im Normalbetrieb des Wechselrichters bei brennender Lampe ist somit der spannungsabhängige Widerstand R1 praktisch stromlos und verursacht keine Verluste.After the lamp has been ignited, its operating voltage U EB is practically constant. During normal operation of the inverter when the lamp is on, the voltage-dependent resistor R1 is therefore practically currentless and does not cause any losses.

Claims (5)

1. An inverter which serves to supply a discharge lamp (E) comprising heatable electrodes, each with two terminals,
- with a load circuit which includes a series resonant circuit (L, C), a coupling capacitor (C1) and the heatable electrodes (e1, e2) of the discharge lamp (E) in a series arrangement, where the capacitor (C) of the series resonant circuit connects one terminal of each of the two electrodes (e1, e2) to one another,
- with two alternatively conductive, controllable switches (V1, V2) of which one switch (V1) is parallel to the load circuit and the other switch (V2) is between the load circuit and a d.c. voltage source (H),
- with a control set (S) which alternately drives the switches (V1, V2) at an operating frequency (fB) which is above the resonance frequency (fo) of the series resonant circuit when the discharge lamp is not ignited,

characterised in that for the purpose of voltage limitation a voltage-dependent resistor (R1) is provided
- which forms in series with a capacitor (C4), a parallel arm to an arm which contains the choke (L) or the capacitor (C) of the series resonant circuit and thereby
- changes the resonance frequency (fo) of the series resonant circuit (L, C) when the voltage-dependent resistor (R1) is operating in its current-conducting range.
2. An inverter as claimed in Claim 1, characterised in that the parallel arm comprising the voltage-dependent resistor (R1) and the capacitor (C4) is connected parallel to the series arrangement of the choke (L) of the series resonant circuit and the second switch (V2) of the inverter.
3. An inverter as claimed in Claim 2, with a monitoring device which disconnects the inverter (W) in dependence upon the current, characterised in that the voltage connected to the capacitor (C4) controls the monitoring device.
4. An inverter as claimed in Claim 1, characterised by a design such that at the highest occurring operating frequency of the inverter the operating point of the voltage-dependent resistor (R2) always lies in the current-conducting range of the curve during the igniting operation of the discharge lamp, and lies in the currentless range of the curve only when the lamp has ignited.
5. An inverter as claimed in Claim 4, characterised in that the control set (S) contains a saturable transformer, from whose secondary windings (t2, t3) the control voltages for the switches (V1, V2) are derived, and whose primary winding (t1) lies in the load circuit.
EP83112488A 1982-12-15 1983-12-12 Inverter with a load circuit comprising a series resonant circuit and a discharge lamp Expired EP0113451B1 (en)

Priority Applications (1)

Application Number Priority Date Filing Date Title
AT83112488T ATE30290T1 (en) 1982-12-15 1983-12-12 INVERTER WITH A LOAD CIRCUIT INCLUDING A SERIES RESONANCE CIRCUIT AND A DISCHARGE LAMP.

Applications Claiming Priority (2)

Application Number Priority Date Filing Date Title
DE3246454 1982-12-15
DE19823246454 DE3246454A1 (en) 1982-12-15 1982-12-15 INVERTER WITH A LOAD CIRCUIT CONTAINING A SERIES RESONANCE CIRCUIT AND A DISCHARGE LAMP

Publications (2)

Publication Number Publication Date
EP0113451A1 EP0113451A1 (en) 1984-07-18
EP0113451B1 true EP0113451B1 (en) 1987-10-14

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Family Applications (1)

Application Number Title Priority Date Filing Date
EP83112488A Expired EP0113451B1 (en) 1982-12-15 1983-12-12 Inverter with a load circuit comprising a series resonant circuit and a discharge lamp

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US (1) US4547706A (en)
EP (1) EP0113451B1 (en)
JP (1) JPS59132597A (en)
AT (1) ATE30290T1 (en)
DE (2) DE3246454A1 (en)
DK (1) DK159038C (en)
FI (1) FI77135C (en)
NO (1) NO160960C (en)
SU (1) SU1351527A3 (en)
ZA (1) ZA839305B (en)

Cited By (7)

* Cited by examiner, † Cited by third party
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NL8403441A (en) * 1984-11-09 1986-06-02 Maars Holding Bv Ballast circuit for several fluorescent lamps - gives constant lighting despite fluctuations in natural light by detecting intensity and controlling LF-HF conversion accordingly
GB2180418A (en) * 1985-09-14 1987-03-25 Contrology Limited Fluorescent lamp supply circuit
US4798583A (en) * 1984-11-16 1989-01-17 Walter Beck Method and apparatus for aspirating secreted fluids from a wound
EP0610642A1 (en) * 1993-01-29 1994-08-17 MAGNETEK S.p.A. Inverter for the supply of discharge lamps with heated electrodes, with resonant circuit
US5801491A (en) * 1995-07-05 1998-09-01 Magnetek S.P.A. Supply circuit for discharge lamps with means for preheating the electrodes
US5825136A (en) * 1996-03-27 1998-10-20 Patent-Treuhand-Gesellschaft Fuer Elektrische Gluehlampen Mbh Circuit arrangement for operating electric lamps, and an operating method for electronic lamps
EP1071315A2 (en) * 1999-07-21 2001-01-24 General Electric Company Ballast shutdown circuit for a gas discharge lamp

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DE3441992A1 (en) * 1984-11-16 1986-05-22 Patent-Treuhand-Gesellschaft für elektrische Glühlampen mbH, 8000 München CIRCUIT ARRANGEMENT FOR IGNITING A LOW-PRESSURE DISCHARGE LAMP
US4734624A (en) * 1985-07-25 1988-03-29 Matsushita Electric Works, Ltd. Discharge lamp driving circuit
DE3611611A1 (en) * 1986-04-07 1987-10-08 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh CIRCUIT ARRANGEMENT FOR HIGH-FREQUENCY OPERATION OF A LOW-PRESSURE DISCHARGE LAMP
DE3711814C2 (en) * 1986-05-09 1998-04-09 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Electronic ballast for operating fluorescent lamps
DE3626209A1 (en) * 1986-08-02 1988-02-04 Telefunken Electronic Gmbh Ballast for at least one discharge lamp
US4885507A (en) * 1987-07-21 1989-12-05 Ham Byung I Electronic starter combined with the L-C ballast of a fluorescent lamp
EP0314077B1 (en) * 1987-10-27 1994-01-26 Matsushita Electric Works, Ltd. Discharge lamp driving circuit
US5130611A (en) * 1991-01-16 1992-07-14 Intent Patents A.G. Universal electronic ballast system
DE4210373A1 (en) * 1992-03-30 1993-10-07 Abb Patent Gmbh Electronic ballast
DE4210367A1 (en) * 1992-03-30 1993-10-07 Abb Patent Gmbh Electronic ballast
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DE4238409A1 (en) * 1992-11-13 1994-05-19 Patent Treuhand Ges Fuer Elektrische Gluehlampen Mbh Circuit arrangement for operating low-pressure discharge lamps
GB9304132D0 (en) * 1993-03-01 1993-04-14 Tunewell Transformers Ltd Improvements in or relating to an electrical arrangement
DE4318995C2 (en) * 1993-05-26 1998-10-15 Medium Tech Gmbh Regulated ballast with self-oscillating half-bridge circuit (electronic transformer)
DE4318996C2 (en) * 1993-05-26 1998-09-24 Medium Tech Gmbh Dimmable ballast
US5686799A (en) * 1994-03-25 1997-11-11 Pacific Scientific Company Ballast circuit for compact fluorescent lamp
US5691606A (en) * 1994-09-30 1997-11-25 Pacific Scientific Company Ballast circuit for fluorescent lamp
US6037722A (en) * 1994-09-30 2000-03-14 Pacific Scientific Dimmable ballast apparatus and method for controlling power delivered to a fluorescent lamp
US5821699A (en) * 1994-09-30 1998-10-13 Pacific Scientific Ballast circuit for fluorescent lamps
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US5925986A (en) * 1996-05-09 1999-07-20 Pacific Scientific Company Method and apparatus for controlling power delivered to a fluorescent lamp
US5866993A (en) * 1996-11-14 1999-02-02 Pacific Scientific Company Three-way dimming ballast circuit with passive power factor correction
US5798617A (en) * 1996-12-18 1998-08-25 Pacific Scientific Company Magnetic feedback ballast circuit for fluorescent lamp
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US6111368A (en) * 1997-09-26 2000-08-29 Lutron Electronics Co., Inc. System for preventing oscillations in a fluorescent lamp ballast
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Cited By (7)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
NL8403441A (en) * 1984-11-09 1986-06-02 Maars Holding Bv Ballast circuit for several fluorescent lamps - gives constant lighting despite fluctuations in natural light by detecting intensity and controlling LF-HF conversion accordingly
US4798583A (en) * 1984-11-16 1989-01-17 Walter Beck Method and apparatus for aspirating secreted fluids from a wound
GB2180418A (en) * 1985-09-14 1987-03-25 Contrology Limited Fluorescent lamp supply circuit
EP0610642A1 (en) * 1993-01-29 1994-08-17 MAGNETEK S.p.A. Inverter for the supply of discharge lamps with heated electrodes, with resonant circuit
US5801491A (en) * 1995-07-05 1998-09-01 Magnetek S.P.A. Supply circuit for discharge lamps with means for preheating the electrodes
US5825136A (en) * 1996-03-27 1998-10-20 Patent-Treuhand-Gesellschaft Fuer Elektrische Gluehlampen Mbh Circuit arrangement for operating electric lamps, and an operating method for electronic lamps
EP1071315A2 (en) * 1999-07-21 2001-01-24 General Electric Company Ballast shutdown circuit for a gas discharge lamp

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US4547706A (en) 1985-10-15
JPH0311516B2 (en) 1991-02-18
FI834184A0 (en) 1983-11-15
FI77135C (en) 1989-01-10
DE3374112D1 (en) 1987-11-19
DK159038B (en) 1990-08-20
NO160960B (en) 1989-03-06
NO834564L (en) 1984-06-18
NO160960C (en) 1989-06-14
DK577083D0 (en) 1983-12-14
FI77135B (en) 1988-09-30
ATE30290T1 (en) 1987-10-15
DK577083A (en) 1984-06-16
EP0113451A1 (en) 1984-07-18
SU1351527A3 (en) 1987-11-07
JPS59132597A (en) 1984-07-30
DE3246454A1 (en) 1984-06-20
DK159038C (en) 1991-01-28
FI834184A (en) 1984-06-16
ZA839305B (en) 1984-08-29

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