CN200956551Y - Quasi-resonant control circuit for power supply system - Google Patents
Quasi-resonant control circuit for power supply system Download PDFInfo
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- CN200956551Y CN200956551Y CN 200620135567 CN200620135567U CN200956551Y CN 200956551 Y CN200956551 Y CN 200956551Y CN 200620135567 CN200620135567 CN 200620135567 CN 200620135567 U CN200620135567 U CN 200620135567U CN 200956551 Y CN200956551 Y CN 200956551Y
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- 238000004804 winding Methods 0.000 claims abstract description 37
- 230000003287 optical effect Effects 0.000 claims description 6
- 230000001360 synchronised effect Effects 0.000 claims description 5
- 239000011469 building brick Substances 0.000 claims description 4
- 230000008447 perception Effects 0.000 claims description 3
- 230000008859 change Effects 0.000 claims description 2
- 230000010355 oscillation Effects 0.000 abstract 1
- 230000009471 action Effects 0.000 description 3
- 239000003990 capacitor Substances 0.000 description 3
- 230000002093 peripheral effect Effects 0.000 description 2
- 238000006073 displacement reaction Methods 0.000 description 1
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Abstract
The utility model provides a quasi-resonance control circuit is with control a power supply system, include: a flyback transformer having a primary winding, an auxiliary winding and a secondary winding; a power transistor connected to the primary winding; a first comparator connected to the auxiliary winding; an oscillating circuit connected to the first comparator; a second comparator connected to the oscillation circuit; a voltage feedback circuit having an optocoupler, the voltage feedback circuit being connected to the secondary circuit output; a current detecting resistor connected with the photoelectric coupler and the power transistor; a third comparator connected to the current detecting resistor; and a driving circuit connected to the second comparator, the third comparator and the power transistor. The utility model discloses utilize simple and easy electronic component to constitute control circuit, control power transistor begins to switch on when power transistor and transformer contact are zero voltage quasi-position, the switch switching loss when reducing power transistor and switching on.
Description
Technical field
The utility model be about a kind of quasi-resonance control circuit to control an electric power system, relate in particular to the conducting when the accurate position of no-voltage of a kind of power transistor and transformer contact, reduce the quasi-resonance control circuit of the electric power system of power transistor switch switch cost.
Background technology
The quasi-resonance flyback exchanges electric power system in generally being used in flyback exchange electric power system on the market, the switch switch cost and the electromagnetic interference noise that produce during with the reduction conducting.Fig. 1 is existing flyback quasi-resonance control circuit figure, the flyback circuit topography that is called RCC (Ring Choke Converter), please refer to Fig. 1, behind DC power supply B+ electric power starting, at first provide Weak current slowly to charge to make power transistor Q1 conducting, primary side current to begin to flow to the negative pole that flyback transformer T1, power transistor Q1 and electric current detect resistance R 10 to primary side DC power supply B+ through a resistance R 1.Power transistor Q1 is controlled by transistor Q3 by action, stops power transistor Q1 conducting when transistor Q3 base voltage reaches the about 0.7V of operation voltage.Transistor Q3 base stage operation voltage is to flow through resistance R 7, R8 and electric current by the optical coupler U1 in the Voltage Feedback control circuit in side to detect the current signal that resistance R 10 produces and the electric currents that flow through primary side power transistor Q1 and detect the generation that overlaps mutually of voltage on the resistance R 10.Then transistor Q3, transistor Q2 conducting when being higher than the about 0.7V of transistor Q3 base stage operation voltage, and make power transistor Q1 stop conducting.Otherwise transistor Q1 conduction period secondary side because winding die mutually with output rectifier diode D1 polarity, can't transmit energy to output V0 and temporarily with store energy in flyback transformer T1.Each winding polarity of flyback transformer T1 reverses at once behind the power transistor Q1 stop conducting, secondary side winding becomes forward with output rectifier diode D1 polarity transformation, and the energy that is stored among the flyback transformer T1 is released to output V0, and the charging current of required load of output V0 and output capacitance C3 is provided.Storage power among the flyback transformer T1 discharges when finishing, and secondary side winding flows to the current cut-off of output V0, and output capacitance C3 continues supply of current and keeps required load current for output V0.Flyback transformer T1 energy discharges the moment winding polarity of finishing and produces counter-rotating, and first side winding inductance and capacitor C 5 produce resonance and move and make voltage be sine wave to swing among this moment flyback transformer T1.When drain electrode (DRAIN) voltage of power transistor Q1 during near 0V, the grid of power transistor Q1 also simultaneously begins conducting by auxiliary winding supply of current through capacitor C 2, resistance R 2 when charging to high potential, just close power transistor Q1 up to control when the transistor Q3 base voltage of action arrives 0.7V.The shortcoming of this circuit is not have the frequency limitation loop when being operated in underloading, frequency produces free modulation higher switch switch cost and because of crossing the assembly reliability problem that high-frequency work produces, also is difficult to meet simultaneously the input power loss requirement of green mode standard to quite high operating frequency.
Fig. 2 is the movement oscillogram of the existing flyback quasi-resonance control circuit of Fig. 1, wherein, TON is the turn-on cycle oscillogram of power transistor Q1, Q1-IDS drains (DRAIN) to source electrode (SOURCE) current waveform figure for power transistor Q1, Q1-VDS drains (DRAIN) to source electrode (SOURCE) voltage oscillogram for power transistor Q1, voltage when VDS (ON) is power transistor Q1 conducting, T1-E1 then are that the oscillogram and the ID of the elementary winding voltage of flyback transformer T1 is the current waveform figure through diode D1.
Fig. 3 is another existing flyback quasi-resonance control circuit calcspar, because its circuit comparatively complexity can't draw its peripheral circuit is complete, but it is identical with the peripheral circuit of Fig. 4, the power transistor that following Fig. 3 explanation is carried be external switch module not in icon, its position corresponds to the power transistor Q2 ' of Fig. 4.As shown in Figure 3, this integrated circuit is the flyback quasi-resonance control circuit of improvement.It utilizes the Demag pin relatively to produce a conducting pulse signal as a comparator 1 among detecting input of assisting winding terminal voltage and the figure.This conducting pulse signal inputs to the S input of set-reset flip-floop 2, forces the Drv of control circuit output 3 to become high potential and makes the power transistor that is connected in after the control circuit output Drv be conducting state.This circuit then converts a voltage signal by the current signal of a side FB of the optical coupler in Voltage Feedback control circuit pin to through change-over circuit by control and detects signal CS with the electric current that flows through the primary side power transistor and compare, two signals utilize a comparator 5 relatively to produce the R reverse input end that the disabling pulse signal inputs to set-reset flip-floop 2, force control circuit output Drv to become electronegative potential and make power transistor be cut-off state.In addition, inside have one fixedly the blank time of 8us (blanking time) make control circuit 6 may command Drv conductings in first conducting pulse signal or conducting pulse signal backward.If first conducting pulse signal appears at after the blank time of 8us, then power transistor is controlled to conducting by first conducting pulse signal.Otherwise only the conducting pulse signal after the blank time of 8us can effectively allow the power transistor conducting.To be that frequency modulating is too high when preventing underloading produce higher switch switch cost to its purpose, because this blank time is fixing 8us value, so during underloading operating frequency the highest will be tuned to fs=1/8uS=125KHz just stop frequency rise, by second or the power transistor beginning conducting when producing of backward conducting pulse signal.The frequency of the operating frequency point of 125kHz still has very high switch switch cost producing by moment, removes the work of unsupported lower arrival output skip pattern and can just reduce this switch switch cost by moment because of component frequency reduces down.With reference to shown in Figure 3, required again for reaching this quasi-resonance control circuit action, the circuit complexity, number of parts is many, and cost costliness is its another shortcoming.
Therefore, how designing a quasi-resonance control circuit controlling an electric power system, and control circuit is simply reached reduce power transistor switch the loss when switching, will be that the utility model desires actively to inquire into part.
Summary of the invention
Main purpose of the present utility model is to provide a kind of quasi-resonance control circuit to control an electric power system, it is by the control circuit of being made up of simple and easy electronic building brick, make the conducting when the accurate position of no-voltage of power transistor and transformer contact, and then reach the purpose that reduces the power transistor switch switch cost.
The purpose of this utility model provides a kind of quasi-resonance control circuit to control an electric power system, comprise: a flyback transformer, it has an elementary winding, an auxiliary winding and a level winding, and this flyback transformer is in order to store and to change the energy of this electric power system of output; One power transistor, it connects this elementary winding; One first comparator, it connects should assist winding; One oscillating circuit, it connects this first comparator; One second comparator, it connects this oscillating circuit; One voltage feedback circuit, it has a photoelectrical coupler, and this voltage feedback circuit connects this secondary winding; One electric current detects resistance, and it connects this photoelectrical coupler and this power transistor; One the 3rd comparator, it connects this electric current and detects resistance; And one drive circuit, it connects this second comparator, the 3rd comparator and this power transistor; Wherein, when the voltage of this auxiliary winding during less than one first reference voltage of this first comparator, this first comparator produces a pulse signal, the sawtooth voltage signal that this pulse signal and this oscillating circuit produce overlaps and produces one first overlapping signal, the slope of this sawtooth voltage signal can be by a resistance value or a capacitance adjustment, maximum operating frequency value during with the setpoint frequency modulation, when the voltage of this first overlapping signal during greater than one second reference voltage of this second comparator, this second comparator produces a Continuity signal, this Continuity signal makes this power transistor conducting via this drive circuit, and makes this flyback transformer storage power; When the voltage of the circuit output end of this this secondary winding of voltage feedback circuit perception, this photoelectrical coupler produces a current signal, the electric current that this current signal and this electric current detect the resistance generation detects signal overlapping generation one second overlapping signal, when the voltage of this second overlapping signal during greater than one the 3rd reference voltage of the 3rd comparator, the 3rd comparator produces a pick-off signal, this pick-off signal ends this power transistor via this drive circuit, and makes the storage power output of this flyback transformer.
Whereby, utilize simple and easy electronic building brick to form control circuit, make the conducting when the accurate position of no-voltage of power transistor and transformer contact, and then reduce the power transistor switch switch cost.
Description of drawings
For further disclosing the purpose of this utility model, feature and effect, now by following specific embodiment, and cooperate attached figure that the utility model is described in detail, wherein:
Fig. 1 is existing flyback quasi-resonance control circuit figure.
Fig. 2 is the movement oscillogram of the flyback quasi-resonance control circuit of Fig. 1.
Fig. 3 is another existing flyback quasi-resonance control circuit calcspar.
Fig. 4 is the quasi-resonance control circuit figure of the electric power system of preferred embodiment of the present utility model.
Fig. 5 is the movement oscillogram of quasi-resonance control circuit of electric power system of the preferred embodiment of the present utility model of Fig. 4.
Fig. 6 is the quasi-resonance control circuit figure of the electric power system of another preferred embodiment of the present utility model.
The primary clustering symbol description is as follows among the figure:
R1, R2, R5, R6, R7, R8 resistance
Q1: power transistor
T1: flyback transformer
R7 ': electric current detects resistance
R10: electric current detects resistance
B+: DC power supply
Q2, Q3: transistor
Q2 ': power transistor
U1: optical coupler
D1: diode
V0: output
C2, C3, C5: electric capacity
1: comparator
The 2:SR trigger
3: output
5: comparator
6: control circuit
7,8,9: comparator
VCC: supply voltage
UVLO: under-voltage protecting circuit
DEM: detecting voltage pin
VERF1: first reference voltage
VERF2: second reference voltage
VERF3: the 3rd reference voltage
DRIVER CIRCUIT: drive circuit
FB: pressure feedback port
Embodiment
Fig. 4 is the quasi-resonance control circuit figure of the electric power system of preferred embodiment of the present utility model; as shown in the figure; this quasi-resonance control circuit is by the required voltage of supply voltage VCC pin supply control; this quasi-resonance control circuit comprises a under-voltage protecting circuit UVLO (UNDER VOLRAGE LOCKOUT); to guarantee charging to capacitor C 2 by starting resistance R1; supply voltage VCC just begins to have output when enough voltage is arranged, and prevents that circuit working from damaging assembly unusually.One detecting voltage pin DEM is responsible for detecting the wave trough position of assisting the winding terminal voltage waveform, and resistance R 8 can be adjusted detecting pin DEM voltage.Via first comparator 7, if the voltage of auxiliary winding then produces a pulse signal less than the first reference voltage VREF1 of first comparator, resistance R 8 makes the trough of pulse signal and auxiliary winding voltage waveform synchronous.The sawtooth voltage signal that this pulse signal and oscillator produce overlaps and produces one first overlapping signal, its again with the second reference voltage VREF2 of second comparator 8 relatively.If the voltage of first overlapping signal then produces a Continuity signal greater than the second reference voltage VREF2 of second comparator 8, the crest of Continuity signal and sawtooth voltage signal waveform is synchronous, and Continuity signal makes power transistor Q2 ' conducting through drive circuit (DRIVER CIRCUIT).Elementary winding, power transistor Q2 ', the electric current that DC power supply B+ provides electric current to flow through flyback transformer T1 detects resistance R 7 ' and gets back to the negative pole of primary side DC power supply B+ (primary side earth terminal), flyback transformer T1 storage power.When the voltage of the circuit output end V0 of this this secondary winding of voltage feedback circuit perception, the current signal of a side FB of the optical coupler U1 pin in the Voltage Feedback control circuit, detect resistance R 7 ' with electric current and detect signal overlapping generation one second overlapping signal through the electric current of resistance R 5, R6 generation, if the voltage of second overlapping signal through the 3rd comparator 9 relatively after greater than the 3rd reference voltage VREF3, then produce a pick-off signal and power transistor Q2 ' is ended, and make the storage power output of this flyback transformer to drive circuit.The sawtooth voltage signal that oscillator produces can see through resistance value or capacitance is freely adjusted the sawtooth voltage slope, control and whether produce Continuity signal when first pulse signal occurs, or delay and when pulse signal backward occurs, just produce Continuity signal, frequency modulating is too high and produce higher switch switch cost when preventing underloading.
Fig. 5 is the movement oscillogram of quasi-resonance control circuit of electric power system of the preferred embodiment of the present utility model of Fig. 4, please refer to Fig. 5, pulse signal (PULSE SIGNAL) is obtained by the wave trough position that detects auxiliary winding terminal voltage waveform (VDS/VAUX), and Continuity signal (ON SIGNAL) produces when first overlapping signal is higher than the second reference voltage VREF2.Pick-off signal (OFF SIGNAL) is then detected in side a current signal that produces and an electric current that flows through primary side power transistor Q2 ' by the optical coupler U1 in the Voltage Feedback control circuit and produces when signal overlaps with the 3rd reference voltage VREF3 relatively.Fig. 5 below shows that the underload conducting drops on second trough, and to drop on first trough different with top high capacity conducting.
Fig. 6 is the quasi-resonance control circuit figure of the electric power system of another preferred embodiment of the present utility model.It replaces the comparator among Fig. 4 respectively with transistor, first and third reference voltage then utilizes the about 0.7V of transistor base operation voltage to replace, second reference voltage then utilizes two or more electric resistance partial pressures to replace, and finishes the quasi-resonance control circuit of electric power system of the present utility model.
As mentioned above, the utility model utilizes simple and easy electronic building brick to form control circuit, makes the conducting when the accurate position of no-voltage of power transistor and transformer contact, and then reaches the purpose that reduces the power transistor switch switch cost; With regard to the utilizability on the industry, the product that utilizes the utility model to derive is when the demand that can fully satisfy existing market.
The utility model discloses with preferred embodiment hereinbefore, so has the knack of this operator and it should be understood that this embodiment only is used to describe the utility model, and should not be read as restriction protection range of the present utility model.It should be noted that the variation and the displacement of every and this embodiment equivalence all should be made as and be covered by in the category of the present utility model.Therefore, protection range of the present utility model is worked as with being as the criterion that appending claims was defined.
Claims (8)
1. the quasi-resonance control circuit of an electric power system is characterized in that, comprising:
One flyback transformer, it has an elementary winding, an auxiliary winding and a level winding, and this flyback transformer is in order to store and to change the energy of this electric power system of output;
One power transistor, it connects this elementary winding;
One first comparator, it connects should assist winding;
One oscillating circuit, it connects this first comparator;
One second comparator, it connects this oscillating circuit;
One voltage feedback circuit, it has an optical coupler, and this voltage feedback circuit connects this secondary circuit output;
One electric current detects resistance, and it connects this photoelectrical coupler and this power transistor;
One the 3rd comparator, it connects this electric current and detects resistance; And
One drive circuit, it connects this second comparator, the 3rd comparator and this power transistor;
Wherein, when the voltage of this auxiliary winding during less than one first reference voltage of this first comparator, this first comparator produces a pulse signal, the sawtooth voltage signal that this pulse signal and this oscillating circuit produce overlaps and produces one first overlapping signal, the slope of this sawtooth voltage signal can be by a resistance value or a capacitance adjustment, maximum operating frequency value during with the setpoint frequency modulation, when the voltage of this first overlapping signal during greater than one second reference voltage of this second comparator, this second comparator produces a Continuity signal, this Continuity signal makes this power transistor conducting via this drive circuit, and makes this flyback transformer storage power; When the voltage of the circuit output end of this this secondary winding of voltage feedback circuit perception, this photoelectrical coupler produces a current signal, the electric current that this current signal and this electric current detect the resistance generation detects signal overlapping generation one second overlapping signal, when the voltage of this second overlapping signal during greater than one the 3rd reference voltage of the 3rd comparator, the 3rd comparator produces a pick-off signal, this pick-off signal ends this power transistor via this drive circuit, and makes the storage power output of this flyback transformer.
2. the quasi-resonance control circuit of electric power system according to claim 1 is characterized in that, this pulse signal is synchronous with trough that should auxiliary winding voltage waveform.
3. the quasi-resonance control circuit of electric power system according to claim 1 is characterized in that the crest of this Continuity signal and this sawtooth voltage signal waveform is synchronous.
4. as the quasi-resonance control circuit of electric power system as described in the claim 2, it is characterized in that also comprising a resistance, it makes this pulse signal synchronous with trough that should auxiliary winding voltage waveform.
5. the quasi-resonance control circuit of electric power system according to claim 1 is characterized in that also comprising a under-voltage protecting circuit, and it prevents that the circuit start from damaging electronic building brick unusually.
6. the quasi-resonance control circuit of electric power system according to claim 1 is characterized in that this first comparator is made of at least one transistor.
7. the quasi-resonance control circuit of electric power system according to claim 1 is characterized in that this second comparator is made of at least one transistor.
8. the quasi-resonance control circuit of electric power system according to claim 1 is characterized in that the 3rd comparator is made of at least one transistor.
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 200620135567 CN200956551Y (en) | 2006-09-27 | 2006-09-27 | Quasi-resonant control circuit for power supply system |
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| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 200620135567 CN200956551Y (en) | 2006-09-27 | 2006-09-27 | Quasi-resonant control circuit for power supply system |
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| CN200956551Y true CN200956551Y (en) | 2007-10-03 |
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| CN 200620135567 Expired - Fee Related CN200956551Y (en) | 2006-09-27 | 2006-09-27 | Quasi-resonant control circuit for power supply system |
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Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101154113B (en) * | 2006-09-26 | 2010-05-12 | 尼克森微电子股份有限公司 | Quasi-resonance control circuit of power supply and control method thereof |
| CN101582639B (en) * | 2008-05-16 | 2011-06-15 | 群康科技(深圳)有限公司 | Switch power supply circuit |
| CN101453170B (en) * | 2008-12-19 | 2011-06-22 | 深圳创维－Rgb电子有限公司 | Electric power circuit with discrete components |
| CN103683867A (en) * | 2013-12-06 | 2014-03-26 | 深圳市华星光电技术有限公司 | Flyback switching power supply circuit and backlight source driving device with the same |
| CN103795232A (en) * | 2013-11-30 | 2014-05-14 | 许继电气股份有限公司 | Quasi resonant flyback power supply and high voltage starting circuit thereof |
-
2006
- 2006-09-27 CN CN 200620135567 patent/CN200956551Y/en not_active Expired - Fee Related
Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101154113B (en) * | 2006-09-26 | 2010-05-12 | 尼克森微电子股份有限公司 | Quasi-resonance control circuit of power supply and control method thereof |
| CN101582639B (en) * | 2008-05-16 | 2011-06-15 | 群康科技(深圳)有限公司 | Switch power supply circuit |
| CN101453170B (en) * | 2008-12-19 | 2011-06-22 | 深圳创维－Rgb电子有限公司 | Electric power circuit with discrete components |
| CN103795232A (en) * | 2013-11-30 | 2014-05-14 | 许继电气股份有限公司 | Quasi resonant flyback power supply and high voltage starting circuit thereof |
| CN103683867A (en) * | 2013-12-06 | 2014-03-26 | 深圳市华星光电技术有限公司 | Flyback switching power supply circuit and backlight source driving device with the same |
| CN103683867B (en) * | 2013-12-06 | 2016-03-30 | 深圳市华星光电技术有限公司 | Inverse-excitation type switch power-supply circuit and apply the backlight driving device of this circuit |
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Granted publication date: 20071003 Termination date: 20100927 |