CN1350406A - Bump interconnected decoding equalizer - Google Patents
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Abstract
A united decode equalizer in block shape includes block interlacer and multiplexer at transrnitting end of communication system, the feedforward filter at receiving end, demultiplexer and deinterlacer, noise predicting and counterbalancing module and the module of coefficient predicting and interpolation. The output of TCM code at transmitting end will be interlaced by interlacer and to be multiplexed with training series; the receiving signal will pass the multiplexer first and the exported training series part to be sent to module of coefficient training and interpolation for obtaining the module coefficient for feedforward filter, noise predicting and counterbalancing and the output of noise predicting and counterbalancing module to be sent to TCM decoder for decoding; the judging result will be fedback to noise predicting module. The present invention has realized the combination of equalizing and decoding tor raise the performance of intersymbol interferences as well as provided a new method of resisting channel time varying and intersymbol interference in single carrierwave wide band of radio communication.
Description
Technical field
The present invention is a kind of bump interconnected decoding equalizer, belongs to the broadband wireless communication technique field, is specially adapted to the mobile condition carrierband mobile communication system that places an order.
Background technology
One of feature of wireless mobile communications is exactly the multipath transmisstion of signal.In the system of single carrier, when the time delay of multipath transmisstion surpassed symbol period, the interference (ISI) between the meeting created symbol caused receiving terminal eye pattern closure, thereby the probability of the mistaken verdict of receiver is increased greatly.Another key character of wireless mobile communications is the time-varying characteristics of channel, i.e. the propagation delay of multipath and gain all changes with the variation of the environment of electromagnetic propagation in time, makes received signal decline.For correct judgement, receiver must be done adaptive adjustment according to channel variation.
According to former achievement in research, adaptive channel equalizer is a kind of conventional means of eliminating intersymbol interference.Divide according to structure, present equalizer has two kinds of linear equalization and decision feedback equalizations; According to the difference of algorithm that is adopted and weighing criteria, can be divided into zero forcing equalization, minimum variance equilibrium, least square equilibrium etc. again.Wherein the DFF (being called for short DFE) based on least-squares algorithm (Kalman's algorithm) or its derivative algorithm is considered to have stability and channel tracking performance preferably.
Traditional DFE structure comprises two parts: feedforward filter and feedback filter.In its feedback arrangement, the reference that local judgement is harassed as symbol in the follow-up receiving symbol is eliminated symbol and is harassed.But owing to the reasons such as noise of channel, the reliability of local judgement is lower.Stagger the time when this locality rules out, can have influence on the equilibrium of successive character inevitably, thereby make the mistake propagation.For addressing this problem, V.M.Eyuboglu is at " utilize the decision-feedback noise prediction and the linear distortion channel that interweaves in the detection of modulation signals " (IEEE Trans.Commu., vol.36, no.4, pp.401-409,1988) proposed noise prediction balancing technique (being called for short NPE) in, the decoding and the equilibrium of Trellis-coded modulation (TCM) combined, its principle is shown in the empty frame part among Fig. 1.Adopt the communication system of this noise prediction balancing technique to adopt Trellis-coded modulation (TCM), its equalizer comprises the processing that is arranged on two parts in transmitting terminal and the receiving terminal.Partly comprise multiple connection and two modules that interweave at this equalizer transmitting terminal, system is inserted into training sequence in the code stream of TCM coding by multiple connection, sends into interleaving block then and interweaves.This equalizer receiving terminal partly comprises modules such as feedforward filter, deinterleaver, time-delay, noise prediction and counteracting.By a kind of like this structure, can carry out the interference of noise counteracting with the judgement that has higher reliability after the channel decoding as feedback, thereby can reduce the propagation of error code.
But, when this noise prediction equalizer was applied to broadband connections, two problems can appear.One for offsetting the Doppler frequency shift of mobile channel, must adopt to have the algorithm of convergence property faster, such as the minimum power algorithm of recurrence.But in NPE, the coefficient of feedforward filter can only upgrade by the judgement of this locality, and the result of local judgement is insecure.Its two, be to adapt to broad-band channel, the exponent number of equalizer must be enough big, expands to offset multipath, like this, its computational complexity is certain to very high.
Summary of the invention
The present invention is the weak point that overcomes above-mentioned prior art, a kind of bump interconnected decoding equalizer is proposed, be characterized in to guarantee simultaneously channel tracking speed and lower computational complexity faster, thereby be specially adapted to the wide-band mobile communication system of single carrier.
A kind of bump interconnected decoding equalizer that the present invention proposes comprises the transmitting terminal balanced unit that is made of multiplexer and two modules of interleaver that is arranged in the communication system transmitting terminal and the receiving terminal balanced unit that is made of feedforward filter, deinterleaver, noise prediction and cancellation module, coefficient training and interpolating module; It is characterized in that, interleaver in the said transmitting terminal balanced unit is a block interleaver, this block interleaver input links to each other with the output of Trellis-coded modulation (the being called for short TCM) encoder of communication system front end, and the output of this block interleaver links to each other with the multiplexer input; The input of separating multiplexer in the said receiving terminal balanced unit links to each other with the matched filtering and the decimation blocks of communication system, output links to each other with interpolating module with feedforward filter, coefficient training respectively, said feedforward filter, coefficient training and interpolating module, piece deinterleaver and noise prediction and cancellation module are linked to be a loop mutually successively, the output in this loop links to each other with the TCM decoder of communication system, thereby has realized combined decoding and equilibrium.
Training of said coefficient and interpolating module comprise and utilize training sequence to carry out the coefficient training submodule of feedforward filter and noise prediction filter, and utilize and train the coefficient that obtains the filter coefficient between training sequence to be carried out the coefficient interpolation submodule of interpolation.Said coefficient training submodule utilizes least square method, adjusts filter coefficient, makes the accumulation power distortion of known training sequence and filtering output converge to minimum; Said coefficient interpolation submodule is to utilize non-linear multinomial interpolation algorithm, utilizes and trains the coefficient that obtains to all filter coefficients constantly in the interleaving block, to follow the tracks of the quick variation of channel.Characteristics of the present invention:
The noise prediction equalizer of the present invention and former same kind is compared, and all improves on equaliser structure and coefficient training algorithm.In the present invention, the insertion of training symbol block periodicity is through in the TCM coded identification sequence of block interleaving.At receiving terminal, adopt a kind of new non-linear multinomial interpolation algorithm to be used for being responsible for the renewal of coefficient.Like this, can guarantee channel tracking speed and lower computational complexity faster simultaneously.
The present invention can be applicable to ground system of digital television broadcast; Point is to the multimedia communications system of multiple spot; And other adopt the wide-band mobile communication system of single carrier system.
Description of drawings
Fig. 1 is the structure chart (being the structure of the noise prediction weighing apparatus of transmitting terminal and receiving terminal in the empty frame) of the communication system of existing noise prediction equalizer.
Fig. 2 is the structure chart (in the empty frame is the bump interconnected decoding equalizer structure of transmitting terminal and receiving terminal) of the wide-band mobile communication of the bump interconnected decoding equalizer of employing the present invention proposition.
Fig. 3 is block interleaver (deinterleaver) the structure embodiment schematic diagram among the present invention.
Fig. 4 is the feedforward filter structure embodiment schematic diagram among the present invention.
Fig. 5 is the noise prediction and the cancellation module embodiment schematic diagram of the equalizer among the present invention.
Fig. 6 is the training of the equalizer coefficients among the present invention and the embodiment flow graph of interpolating module.
Fig. 7 is the training of the coefficient among the present invention submodule embodiment schematic diagram.
Fig. 8 is the 8PSK1/2TCM code structure schematic diagram that is used for present embodiment.
Fig. 9 is the simulation result schematic diagram of the TCM decoded bit error rate-Doppler frequency shift of present embodiment.
Embodiment
The embodiment of a kind of bump interconnected decoding equalizer that the present invention proposes is described in detail as follows in conjunction with each accompanying drawing:
The general structure of the bump interconnected decoding equalizer of present embodiment as shown in Figure 2.As can be seen from the figure, whole equalizer can be divided into the processing of transmitting terminal and processing two parts of receiving terminal.The transmitting terminal processing module is given in the output of system front end TCM encoder.The transmitting terminal processing module can be divided into block interleaver and two parts of multiple connection.Different with Fig. 1 is, the multiple connection of the training sequence among the present invention is positioned at after the interleaver, can guarantee that so all information-bearing sequences are all cut apart by known array, thus the transfer function of the time varying channel on each time point of acquisition that can be more accurate.The multiple connection sequence is sent to the broadband mobile channel and transmits through shaping filter with after modulating.
The processing module of receiving terminal can be divided into by function separates multiple connection, feedforward filter, coefficient training and interpolation, modules such as piece deinterleaver and noise prediction counteracting.After processing such as matched filtering and sampling, training sequence is sent into de-interleaving block earlier and is carried out separating of training sequence and information-bearing sequence, separate the training sequence that obtains and send into coefficient training and interpolating module, and the information-bearing sequence is admitted to feedforward filter.The coefficient of feedforward filter has coefficient training and interpolating module to obtain and upgrades, and the antithesis function that de-interleaving block is carried out interleaving block is sent in its output.The output of deinterleaver is sent to noise prediction and cancellation module and is carried out rear feed filtering, and its output is decoded being sent to the TCM decoder.As the feedback fraction of system, the TCM decoded results will further deliver to noise prediction and cancellation module carries out noise prediction, and its coefficient is provided with interpolating module by the coefficient training.More than the embodiment detailed structure of each part and workflow details are as follows:
Block interleaver and multiple connection module
The structure of block interleaver and multiple connection module as shown in Figure 3.Empty frame inside is divided into block interleaver among the figure, and the implementation procedure of this block interleaver and multiple connection module is:
(1) signal reads in by column direction, and the length of every row is N.
(2) from top to bottom, write when full, signal is read when delegation's (length is K).
(3) after running through delegation's signal, inserting length is the training sequence of M, thereby is a frame with information-bearing sequence and training sequence multiple connection.
The line number design of block interleaver is greater than the decoding delay of TCM decoder, otherwise its rear feed filter can not obtain the reliable decision value of symbol before this when doing the intersymbol interference prediction.
Training sequence is generally pseudo random sequence.Training sequence length is greater than the length of intersymbol interference prediction.Otherwise symbol-interference can be crossed the symbol that training sequence has influence on back one row between the previous column symbol.In Fig. 3, the length of a frame is M+N.The size of interleaver is N * K.
Separate multiple connection and deinterleaver module
Separate multiple connection and the deinterleaver module execution function opposite respectively, as shown in Figure 3 with multiple connection and block interleaver.
At receiving terminal, after obtaining frame synchronization, can separate multiple connection through the sampled signal after the matched filtering.The length of each frame is M+N, and a preceding M symbol is a training sequence.
The process of deinterleaving with interweave opposite:
(1) signal reads in by line direction, and the length of every row is K.
(2) from left to right, the data of writing each full row (length is N) are read.
The feedforward filter module
The structure of feedforward filter module as shown in Figure 4.After separating the delayed device of information-bearing symbol after the multiple connection and postponing, respectively with coefficient training and the resulting multiplication of interpolating module, itself and be sent to the deinterleaver module as the output of filter.Its function can be expressed from the next:
C wherein
t'=[C
-K, t, C
-K+1, t, C
-1, t] be the t coefficient of filter constantly, Y
t=[v
t, v
T-1..., v
T-K+1] the expression input information carrying vector that sequence constituted, v
tBe t input constantly.
Noise prediction and cancellation module
Signal sampling symbol after process feedforward filtering and the deinterleaving disturbs between may still existing and meeting, and therefore need further eliminate by noise prediction and cancellation module.Intersymbol interference prediction is that the court verdict by the TCM decoder carries out, and its flow graph as shown in Figure 5.After the result of TCM decoder judgement postpones through a series of delayers, through coefficient training and the resulting coefficient weighting of interpolating module as noise prediction, deduct this prediction then from the result of deinterleaving, promptly get the result of noise cancellation, this result deciphers sending into the TCM decoder.The function of this module can be expressed from the next:
U in the following formula
t' be the t output of piece deinterleaver constantly, C
t"=[C
0, t, C
1, t, C
K-1, t] be the t coefficient of the noise prediction filter of filter constantly,
Be the vector of TCM judgement sequence formation,
Be the output behind the noise cancellation.
Coefficient training and interpolating module
This module is finished the training and the interpolation of the filter coefficient of feedforward filter and noise prediction and cancellation module, to follow the tracks of quick time-varying channel.This part can be divided into coefficient training submodule and coefficient interpolation submodule, and its processing procedure as shown in Figure 6.The training sequence after the multiple connection is separated in the utilization of coefficient training submodule, adopts least-squares algorithm to do the training of coefficient; Coefficient interpolation submodule carries out non-linear multinomial interpolation to each coefficient constantly between training sequence.
Before describing coefficient training submodule, define the coefficient and the incoming symbol of filter earlier:
Represent the coefficient of t moment feedforward filter and noise prediction filter.
Represent the input of t moment feedforward filter and noise prediction filter.
The embodiment of coefficient training submodule as shown in Figure 7, concrete steps are described below:
(1) before system starts working, forgetting factor w (0＜w＜1) is set, equalizer coefficients initial value C
0The matrix P of matrix of (complete zero or random number) and its correlation matrix
0(generally being made as unit matrix).
(2) for the i time computing, at first by the output of (1) formula calculation of filtered
Try to achieve output error by following formula then:
If ‖ is e
t‖≤ε then withdraws from iterative process.
(3) calculate kalman gain vector:
(4) inverse matrix of update signal correlation matrix
(5) upgrade filter coefficient
Coefficient interpolation submodule adopts following interpolation method to the filter coefficient between training sequence, is inserted the coefficient value that obtains this moment constantly by training sequence:
" t/N "=M wherein
0Be t piece constantly number, and N is the gap lengths between two training pieces in the symbol sebolic addressing.
Below provide the application example of bump interconnected decoding equalizer of the present invention in single-carrier wireless communication system.Table 1 has provided the design parameter of this system:
Table 1. system design parameters example
| System transmissions net load speed | 10Mbit/s |
| System's occupied bandwidth | 5.75MHZ |
| The system symbol transmission rate | 5M?Sample/s |
| Modulation system | 8PSK |
| Coded system | The 2/3TCM Trellis-coded modulation |
| The base band shaping filter rolloff-factor | 0.15 |
| Training sequence length | 127 |
| The block interleaver size | 4873×32 |
The realization block diagram of the 2/3TCM Trellis-coded modulation in the table 1 as shown in Figure 8; Training sequence employing length is 127 pseudo random sequence, and its primitive polynomial is
x
7+x
3+1?????????????????????????????????(8)
Fig. 9 has provided this system decoded bit error rate under different Doppler frequency shift conditions.The mobile condition lower channel B that selects GSM for use is as simulated channel.The non-linear multinomial interpolation of the employing that the present invention carried is got bump interconnected decoding equalizer (BDFE+MI, diamond indicia curve among the figure) and all the other equalizers of two kinds, promptly adopt the noise prediction equalizer (NPE+RLS of RLS algorithm, circular mark curve among the figure, V.M.Eyuboglu, " utilize the decision-feedback noise prediction and the linear distortion channel that interweaves in the detection of modulation signals ", IEEE Trans.Commu., vol.36, no.4, pp.401-409,1988) and adopt noise prediction equalizer ((NPE+BI, the square marks curve Hiiseyin Arslan among the figure of bilinear interpolation, R.Ramesh, Ayman Mostafa, the realization of the channel tracking receiver of interpolation algorithm " in the relevant M-ary PSK modulation based on ", IEEE Vehicular Technology Conference, vol.3, pp.2194-2199, May 16-20,1999.) under same emulation, contrast.As can be seen, the time channel condition that becomes under, particularly Doppler frequency shift is than higher the time, algorithm of the present invention obviously is superior to other two kinds of algorithms.Simultaneously, owing to adopted interpolation algorithm, the computational complexity when equalizer coefficients upgrades compares to and adopts the RLS algorithm to have substantial degradation fully.Therefore, the present invention is very helpful for the design of the communication control processor under the mobile condition of broadband.
Claims (2)
1, a kind of bump interconnected decoding equalizer comprises transmitting terminal balanced unit that is made of multiplexer and two modules of interleaver in the transmitting terminal that is arranged on communication system and the receiving terminal balanced unit that is made of feedforward filter, deinterleaver, noise prediction and cancellation module; It is characterized in that the interleaver in the said transmitting terminal balanced unit is a block interleaver, this block interleaver input links to each other with the output of communication system front end TCM encoder, and the output of this block interleaver links to each other with the multiplexer input; Said receiving terminal balanced unit also comprises separates multiplexer and coefficient training and interpolating module, said deinterleaver is the piece deinterleaver, the said input of separating multiplexer stops channel by communication and links to each other with said multiplexer output, this output of separating multiplexer links to each other with interpolating module with feedforward filter, coefficient training respectively, said feedforward filter, coefficient training and interpolating module, piece deinterleaver and noise prediction and cancellation module are linked to be a loop mutually successively, and the output in this loop is separated encoder with the TCM of communication system and linked to each other.
2, bump interconnected decoding equalizer as claimed in claim 1, it is characterized in that, training of said coefficient and interpolating module comprise and utilize training sequence to carry out the coefficient training submodule of feedforward filter and noise prediction filter, and utilize and train the coefficient that obtains the filter coefficient between training sequence to be carried out the coefficient interpolation submodule of interpolation.
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Cited By (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN100521524C (en) * | 2002-12-09 | 2009-07-29 | 飞思卡尔半导体公司 | Decision feed forward equalizer system and method |
| CN101404633B (en) * | 2008-11-20 | 2012-05-23 | 北京韦加航通科技有限责任公司 | Carrier wave tracing method for single carrier system based on block transmission |
| CN101414989B (en) * | 2008-12-02 | 2012-06-13 | 北京韦加航通科技有限责任公司 | Timing tracking method based on block transmission for single carrier system |
| CN101425848B (en) * | 2008-11-28 | 2012-12-26 | 北京韦加航通科技有限责任公司 | Timing estimation method in single carrier frequency domain equalization system |
| CN102891819A (en) * | 2011-07-21 | 2013-01-23 | 思亚诺移动芯片有限公司 | Training method for forward filter of receiver |
| CN103812806A (en) * | 2014-02-24 | 2014-05-21 | 北京大学 | Channel equalization method and system based on time domain channel estimation |
| CN105359443A (en) * | 2013-11-29 | 2016-02-24 | 华为技术有限公司 | Transmission and receiving method in a wireless communication system |
| CN114208065A (en) * | 2019-08-13 | 2022-03-18 | 华为技术有限公司 | Noise cancellation apparatus and method for receiver |
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2001
- 2001-12-14 CN CNB01144164XA patent/CN1156188C/en not_active Expired - Lifetime
Cited By (13)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN100521524C (en) * | 2002-12-09 | 2009-07-29 | 飞思卡尔半导体公司 | Decision feed forward equalizer system and method |
| CN101404633B (en) * | 2008-11-20 | 2012-05-23 | 北京韦加航通科技有限责任公司 | Carrier wave tracing method for single carrier system based on block transmission |
| CN101425848B (en) * | 2008-11-28 | 2012-12-26 | 北京韦加航通科技有限责任公司 | Timing estimation method in single carrier frequency domain equalization system |
| CN101414989B (en) * | 2008-12-02 | 2012-06-13 | 北京韦加航通科技有限责任公司 | Timing tracking method based on block transmission for single carrier system |
| CN102891819B (en) * | 2011-07-21 | 2015-06-24 | 思亚诺移动芯片有限公司 | Training method for forward filter of receiver |
| CN102891819A (en) * | 2011-07-21 | 2013-01-23 | 思亚诺移动芯片有限公司 | Training method for forward filter of receiver |
| CN105359443A (en) * | 2013-11-29 | 2016-02-24 | 华为技术有限公司 | Transmission and receiving method in a wireless communication system |
| US10250430B2 (en) | 2013-11-29 | 2019-04-02 | Huawei Technologies Co., Ltd. | Transmission and receiving method in a wireless communication system |
| CN105359443B (en) * | 2013-11-29 | 2019-08-20 | 华为技术有限公司 | Transmission method and method of reseptance in wireless communication system |
| CN103812806A (en) * | 2014-02-24 | 2014-05-21 | 北京大学 | Channel equalization method and system based on time domain channel estimation |
| WO2015123989A1 (en) * | 2014-02-24 | 2015-08-27 | 北京大学 | Channel equalization method and system based on time-domain channel estimation |
| CN114208065A (en) * | 2019-08-13 | 2022-03-18 | 华为技术有限公司 | Noise cancellation apparatus and method for receiver |
| CN114208065B (en) * | 2019-08-13 | 2023-09-08 | 华为技术有限公司 | Noise cancellation apparatus and method for receiver |
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