CN112887230B - Channel estimation method of space-time block coding MSK system under flat fading channel - Google Patents
Channel estimation method of space-time block coding MSK system under flat fading channel Download PDFInfo
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Abstract
The invention discloses a channel estimation method of a space-time block coding (MSK) system under a flat fading channel, which mainly solves the problems of inaccurate response estimation of the flat fading channel and higher complexity of a receiver in the conventional STBC-MSK system. The implementation scheme is as follows: 1) dividing an initial bit sequence generated by a transmitting end into a plurality of data blocks; 2) adding a phase continuous symbol at the tail of the data block to obtain a pre-modulation sequence; 3) decomposing the pre-modulation sequence into amplitude modulation pulse signals to obtain modulation signals; 4) carrying out STBC coding on the modulation signal, and adding a training sequence to obtain a transmitting signal; 5) transmitting signals to a receiving end through a flat fading channel; 6) and calculating the reliability variable of the training sequence at the receiving end, and estimating the channel response in sections. The invention improves the channel estimation precision and reduces the complexity, and can be used for signal transmission in the minimum frequency shift keying STBC-MSK system under the space-time block coding.
Description
Technical Field
The invention belongs to the technical field of communication, and particularly relates to a channel estimation method which can be used for signal transmission in a minimum frequency shift keying STBC-MSK system under space-time block coding.
Background
The minimum frequency shift keying (MSK) modulation mode is a modulation mode which is very advantageous under a nonlinear band-limited channel. The phase is continuous, phase jump can not occur during symbol switching, so that the side lobe of the power spectrum is attenuated quickly, the power spectrum is mainly concentrated in the main lobe, the interference of the side lobe on signals of adjacent frequency bands is small, and the utilization efficiency of the frequency band is high. Meanwhile, the phase carries transmission bit information, so that the system performance is insensitive to the attenuation of the signal amplitude.
M.P Fitz and X.Zhang put forward a space-time trellis coding (STTC) coding mode in 2003, which is applied to an MIMO-CPM system, and constructs a coding mode under the condition of Rayleigh flat fading channel, and in addition, the two people also put forward a calculation method for measuring the symmetric information rate of the MIMO system performance as the lower bound of the channel capacity, and a joint channel estimation algorithm and a data detection method aiming at soft output. Space-time trellis coding, however, introduces greater complexity to the system receiver.
Shenli introduces a predistortion circuit for processing aiming at the nonlinearity of a channel of the MIMO system, and researches a symbol timing synchronization method of the MIMO-CPM system. In forestry, chenghandong et al, further extend the OST-CPM coding method of g.y.wang to any number of antennas, and prove from the aspect of rank criterion that the OST-CPM system has complete diversity gain, and further research the non-coherent demodulation algorithm of the OST-CPM system, but these methods do not discuss the problem of CPM signal phase continuity during coding, and the phase discontinuity may affect the orthogonality of the transmitted signal on the transmitting antennas, so that the signal may be subject to self-interference during transmission, which affects the system receiving error performance.
G.y.wang et al propose an orthogonal-like construction method similar to Alamouti orthogonal space-time coding, which can use orthogonal space-time coding continuous phase modulation OST-CPM transmitted by two antennas to combat flat fading channels. But the construction method thereof increases the channel estimation complexity, and the STBC-MSK system can estimate the flat fading channel at the receiving end of the system and reduce the calculation complexity due to the characteristic of the coding block. The beam-Han-Sai researches the STBC-MSK coding structure and carries out channel estimation at the receiving end, but the channel estimation method adopts integral average, so that the channel response precision is low and the system error code performance is poor.
Disclosure of Invention
The invention aims to provide a channel estimation method of a space-time block coding MSK system under a flat fading channel aiming at the defects of the prior art so as to improve the channel response precision and the system error code performance.
The technical idea of the invention is as follows: the initial bit sequence is processed in a blocking mode at a sending end, a phase return-to-zero symbol is added, amplitude modulation pulse decomposition is carried out, STBC coding is carried out, and a training sequence credibility variable is introduced to a receiving end to carry out sectional estimation on channel response.
According to the above thought, the implementation steps of the invention include the following:
(1) randomly generating a data frame with length of L bits at a transmitting end of a space-time coding minimum frequency shift keying STBC-MSK systemDuration per bit of Ts;
(2) The data frame is partitioned into two transmitting antennas to obtain the data frame of each antennaHas a length ofDividing the data frame on each antenna into three sub-data blocksCalculating phase continuation symbols d from the three sub-data blocks respectivelyxAdding phase continuous symbols to the tail of each subdata block to obtain the 1 st antenna premodulation data block 2 nd antenna premodulation data block
(3) For the pre-modulated data block after adding phase continuous symbolsAndamplitude modulation pulse decomposition is carried out to obtain modulation signals s on two antennasm,1(t)、sm,2(t);
(4) Modulating signals s on two antennasm,1(t)、sm,2(t) the heads are each added with a length LcpTo obtain sm1(t)、sm2(t); and to sm1(t)、sm2(t) performing STBC coding to obtain a transmission signal s on the 1 st antenna1(t) and the transmitted signal s on the 2 nd antenna2(t);
(5) Transmitting signal s on the 1 st transmitting antenna1(t) adding a training sequence p before1(t), obtaining the transmitting signal s with training sequence on the 1 st transmitting antennap1(t) transmitting signal s on the 2 nd transmitting antenna2(t) adding a training sequence p before2(t), obtaining the transmitting signal s with training sequence on the 2 nd transmitting antennap2(t) wherein p1(t)、p2(t) all have a length of Lp;
(6) Transmitting signals s with training sequences on two transmitting antennasp1(t) and sp2(t) obtaining a receiving signal r (t) on a receiving antenna at a receiving end through a flat fading channel;
r(t)=h1sp1(t)+h2sp2(t)+n(t)
h1for the 1 st transmitting antenna to receiving antenna flat fading channel response, h2Is as followsFlat fading channel response of 2 transmitting antennas to receiving antennas;
(7) using training sequence of received signal r (t) on receiving antenna to make channel estimation:
(7a) dividing the training sequence p (t) on the received signal intoSegment interval with duration of 2TsCalculating the confidence level delta of the nth section of the training sequence p (t) on the received signali,n:
(7b) The reliability δ obtained from (7a)i,nTraining sequence p in (1) and (5)1(t)、p2And (t) calculating the average channel response estimated value from the ith transmitting antenna to the receiving antenna according to the received signal r (t) in (t) and (6)
Compared with the prior art, the invention has the following advantages:
firstly, the method comprises the following steps: because the invention introduces the pulse amplitude decomposition before the STBC coding of the signal, the complexity of the receiving end is reduced compared with the prior Viterbi demodulation while approaching the CPM signal as much as possible, the realization is simple, and the simulation result shows that the signal decomposed by the amplitude modulation pulse is completely consistent with the signal generated by the original MSK modulation, and the energy is not lost after the approach.
Secondly, the method comprises the following steps: the invention combines the STBC block coding requirement and the CPM signal characteristic to add the phase continuous symbol, maintains the MSK signal phase continuity, and simultaneously reduces the reduction of the frequency spectrum utilization rate caused by adding the phase continuous symbol to the maximum extent.
Thirdly, the method comprises the following steps: when the invention estimates the flat fading channel by using the training sequence, the channel estimation is more accurate because the training sequence credibility is introduced to take weighted average for the received training sequence segmental estimation, and the channel fading factor obtained by estimation is used for restoring the transmitted signal at the receiving end, so that the signal-to-noise ratio of the improved channel estimation is improved by 0.2dB compared with the signal-to-noise ratio when the bit error rate of the existing channel estimation reaches 10 e-6.
Drawings
FIG. 1 is a diagram of a MIMO-MSK system scenario for use with the present invention;
FIG. 2 is a flow chart of an implementation of the present invention;
FIG. 3 is a time comparison of the present invention with a prior art channel estimation;
FIG. 4 is a graph comparing an AM pulse decomposition modulated signal of the present invention with a conventional MSK modulated signal;
fig. 5 is a comparison of error performance curves of the channel estimation of the present invention and the existing channel estimation algorithm.
Detailed Description
Embodiments and effects of the present invention will be further described below with reference to the accompanying drawings.
Referring to fig. 1, an application scenario of this example is a MIMO-MSK system model, where the system includes a transmitting end and a receiving end, and a flat fading channel is used as a channel. Wherein:
the transmitting end sequentially adds phase continuous symbols, amplitude modulation pulse decomposition and STBC coding to a binary data bit sequence, adds a cyclic prefix and finally adds a training sequence to form a transmitting signal;
at a receiving end, performing channel estimation by using the received signal;
referring to fig. 2, the specific implementation steps of this example are as follows:
(1.1) constructing a randomly generated binary bit sequence data frame at a transmitting endDuration per bit of TsThe bit sequenceThe length L is 3994 bits,expressed as:
(1.2) data frame constructed by (1.1)Performing block processing with length of each block being Ld1997, cyclic prefix length LcpGet 400 data frame on the 1 st transmitting antennaData frame on 2 nd transmitting antennaThen will beEach divided into three sub-data blocks:
wherein, the 1 st sub-data block of the 1 st transmitting antenna is set as:in the formula diTo representThe ith bit in the bit, i is more than or equal to 1 and less than or equal to Lcp-1;
The 2 nd sub data block of the 1 st transmitting antenna is set as:in the formula djTo representMiddle j-th bit, Lcp≤j≤Ld-Lcp+1;
The 3 rd sub-data block of the 1 st transmitting antenna is set as:in the formula dkTo representMiddle k bit, Ld-Lcp+2≤k≤Ld;
The 1 st sub-data block of the 2 nd transmitting antenna is set as:in the formula dlTo representMiddle L bit, Ld+1≤l≤Ld+Lcp-1;
The 2 nd sub data block of the 2 nd transmitting antenna is set as:in the formula dmTo representM-th bit, Ld+Lcp≤m≤2Ld-Lcp+1;
The 3 rd sub-data block of the 2 nd transmitting antenna is set as:in the formula dnTo representMiddle nth bit 2Ld-Lcp+2≤n≤2Ld;
(1.3) calculating the phase continuation symbol dxPhase continuation symbol at tail of ith sub-data block on nth transmitting antenna
WhereinFor the L bit, L, of the ith sub-data block on the nth transmitting antennan,iThe length of the ith sub-data block on the nth transmitting antenna is obtained;
(1.4) addition of dxThe pre-modulated data sequence on the 1 st transmitting antennaAnd 2 pre-modulation data sequence on transmitting antennaThe following were used:
(1.5) carrying out pulse amplitude decomposition on the premodulation data added with the phase continuous symbols to obtain the 1 st antenna modulation signal sm,1(t) and 2 nd antenna modulation signal sm,2(t) are respectively represented as follows:
whereinDenotes the modulation index, Lo=Ld+ 3-2000 denotes the modulation signal length,to representThe upper i-th bit of the data,to representUpper ith bit, c0(t) is a shaping function, expressed as follows:
(1.6) the tail length of the modulation signal on the first transmitting antenna is LcpData of 400 is copied as cyclic prefix to the 1 st transmitting antenna modulation signalHeader portion for obtaining a modulated signal s to which a cyclic prefix is addedm1(t):
Modulating the 2 nd transmitting antenna with the tail length of LcpThe data is copied to the head of the modulation signal of the 2 nd transmitting antenna as a cyclic prefix to obtain a modulation signal s added with the cyclic prefixm2(t):
(1.7) adding the cyclic prefix to the 1 st transmitting antennam1(t) and modulated signal s with cyclic prefix added to 2 nd transmitting antennam2(t) space-time block coding to obtain the transmission signal s on the 1 st transmitting antenna1(t) and the transmission signal s on the 2 nd transmitting antenna2(t),s1(t)、s2(t) are respectively represented as follows:
s1(t)=[sm1(t) sm2(t)]
and 2, adding training sequences to the transmitting signals of the two transmitting antennas.
(2.1) the lengths produced are all LpDuration of Tp=LpTsThe 1 st transmitting antenna transmits a training sequence p of signals1(t) and training sequence p of the 2 nd transmitting antenna transmitting signal2(t), the training sequence in this example is:
[1,-1,1,-1,...,1,-1],Lp=100;
(2.2) transmitting the signal s at the 1 st transmitting antenna1(t) and 2 nd transmitting antenna transmitting signal s2Before (t), the training sequences generated in (2.1) are added respectively to obtain the 1 st transmitting antennaHas a transmitted signal s with a training sequencep1(t) and the transmitted signal s with training sequence on the 2 nd transmitting antennap2(t):
sp1(t)=[p1(t) s1(t)]
sp2(t)=[p2(t) s2(t)]。
Transmitting signal s with training sequence on the 1 st transmitting antennap1(t) flat fading channel response h to receive antenna via the 1 st transmit antenna1Reaches a receiving antenna to obtain a signal h after fading channel response1sp1(t);
Transmitting signal s with training sequence on 2 nd transmitting antennap2(t) flat fading channel response h to receive antenna via 2 nd transmit antenna2Reaches a receiving antenna to obtain a signal h after fading channel response2sp2(t);
The receiving antenna superposes the signals of the two transmitting antennas after the flat fading channel response to obtain a receiving signal r (t);
r(t)=h1sp1(t)+h2sp2(t)+n(t)
wherein n (t) is additive white Gaussian noise.
And 4, the receiving end obtains the received signal and estimates the channel.
In an emulated system, the experienced fading channel response h1、h2Unknown and not directly measurable, but the receiving signal after passing through the flat fading channel can be obtained on the receiving antenna of the receiving end, and the training sequence p (t) of the receiving signal and the training sequence p of the transmitting signal on the ith transmitting antenna can be utilizedi(t) estimating the fading channel response, which is achieved as follows:
(4.1) dividing the training sequence p (t) on the received signal intoSegment interval with duration of 2TsCalculating the reliability delta between the n-th segments of the training sequence p (t) on the received signali,n:
Wherein p isi(t) is the training sequence of the nth interval on the ith transmitting antenna, and p (t) is the training sequence of the nth interval on the receiving signal;
(4.2) calculating the estimated channel response of the ith transmitting antenna to the receiving antenna under the condition of neglecting the influence of noise
Wherein L ispFor the length of the transmit-end training sequence, pi(T) is the training sequence on the ith transmit antenna, r (T) is the received signal on the receive antenna, TsFor each duration of a bit of the data stream,is the conjugate of the training sequence on the ith transmit antenna.
The effects of the present invention can be further illustrated by the following simulations:
firstly, setting simulation system parameters
MATLAB R2020a simulation software is used, the MIMO-MSK system is a double-transmitting single-receiving system, and the length of original data of a transmitting end is 3994 bits; the training sequence length is 100 bits, the cyclic prefix length is 400 bits, and the duration of each bit is 2 x 10 e-7.
The multipath channel parameters apply flat fading to the signal using the comm.
Second, simulation content
As can be seen from fig. 3, the existing channel estimation running time exceeds the channel estimation algorithm of the present invention by 30% in the case of a signal-to-noise ratio of 5dB, and exceeds the estimation algorithm running time of the present invention by 40% in the case of 6dB, indicating that the estimation time of the present invention is short.
As can be seen from FIG. 5, the error code performance of the channel estimation of the invention is better than that of the existing channel estimation algorithm, when the signal-to-noise ratio is 10dB, the signal-to-noise ratio is improved by 0.2dB when the error code rate of the channel estimation of the invention reaches 10e-6 compared with the existing channel estimation, which shows that the channel response estimated by the invention is more accurate.
Claims (7)
1. A channel estimation method based on a space-time block coding (MSK) system under a flat fading channel is characterized by comprising the following steps:
(1) randomly generated data frame with length of L bits at transmitting end of space-time coding minimum frequency shift keying STBC-MSK systemDuration per bit of Ts;
(2) The data frame is partitioned into two transmitting antennas to obtain the data frame of each antennaHas a length ofDividing the data frame on each antenna into three sub-data blocksAnd calculating and adding phase continuation symbols at the tail of each sub-data blockObtaining the 1 st antenna premodulation data block2 nd antenna premodulation data blockWherein the phase continuation symbol added at the tail of each sub data blockIs determined by the following formula:
whereinFor the ith bit, L, of the jth sub-block on the ith transmit antennai,jThe length of the jth sub data block on the ith transmitting antenna is shown;
(3) for the pre-modulated data block after adding phase continuous symbolsAndamplitude modulation pulse decomposition is carried out to obtain modulation signals s on two antennasm,1(t)、sm,2(t); respectively, as follows:
whereinDenotes the modulation index, Lo=Ld+3 represents the length of the modulation signal,to representThe upper i' th bit of the data,to representUpper i' bit, c0(t) is a shaping function, expressed as follows:
(4) modulating signals s on two antennasm,1(t)、sm,2(t) the heads are each added with a length LcpTo obtain sm1(t)、sm2(t); and areTo sm1(t)、sm2(t) performing STBC coding to obtain a transmission signal s on the 1 st antenna1(t) and the transmitted signal s on the 2 nd antenna2(t);
(5) Transmitting signal s on the 1 st transmitting antenna1(t) adding a training sequence p before1(t), obtaining the transmitting signal s with training sequence on the 1 st transmitting antennap1(t) transmitting signal s on the 2 nd transmitting antenna2(t) adding a training sequence p before2(t), obtaining the transmitting signal s with training sequence on the 2 nd transmitting antennap2(t) wherein p1(t)、p2(t) all have a length of Lp;
(6) Transmitting signals s with training sequences on two transmitting antennasp1(t) and sp2(t) obtaining a receiving signal r (t) on a receiving antenna at a receiving end through a flat fading channel;
r(t)=h1sp1(t)+h2sp2(t)+n(t)
h1for the 1 st transmitting antenna to receiving antenna flat fading channel response, h2For the flat fading channel response from the 2 nd transmitting antenna to the receiving antenna, n (t) is additive white gaussian noise;
(7) using training sequence of received signal r (t) on receiving antenna to make channel estimation:
(7a) dividing the training sequence p (t) on the received signal intoSegment interval with duration of 2TsCalculating the confidence level delta of the nth section of the training sequence p (t) on the received signali,n:
Wherein p isi(t) represents the training sequence on the ith transmit antenna;
(7b) the reliability δ obtained from (7a)i,nTraining sequence p in (1) and (5)1(t)、p2And (t) calculating the average channel response estimated value from the ith transmitting antenna to the receiving antenna according to the received signal r (t) in (t) and (6)
3. The method of claim 1, wherein the length of each of the three sub-data blocks in (2) is L1=Lcp-1、L2=Ld-2Lcp+2、L3=Lcp-1, wherein LcpIs the cyclic prefix length.
4. The method of claim 1, wherein the length L is added in (4) at two modulation signal headerscpThe cyclic prefix of (c) is implemented as follows:
modulating the tail length of the signal by the 1 st transmitting antenna to be LcpThe data is copied to the head of the modulation signal of the 1 st transmitting antenna as a cyclic prefix to obtain a modulation signal s added with the cyclic prefixm1(t):
Modulating the 2 nd transmitting antenna with the tail length of LcpThe data is copied to the head of the modulation signal of the 2 nd transmitting antenna as a cyclic prefix to obtain a modulation signal s added with the cyclic prefixm2(t):
Wherein L iso=Ld+3 denotes the modulation signal length.
6. the method of claim 1, wherein in (5) two training sequences p of transmitted signals1(t)、p2(t) all internal structures are [1, -1,1, -1,.. multidot.1, -1]Length L ofpL is more than or equal to 50pAn even number less than or equal to 1000.
7. The method of claim 1, wherein the transmitted signal s with the training sequence on the 1 st antenna in (5)p1(t) and the transmitted signal s with training sequence on the 2 nd antennap2(t) are respectively represented as follows:
sp1(t)=[p1(t) s1(t)]
sp2(t)=[p2(t) s2(t)]
wherein s is1(t) is the transmitted signal on the 1 st antenna, s2(t) for signals transmitted on the 2 nd antenna, p1(t)For training sequences on the 1 st antenna, p2And (t) is a training sequence on the 2 nd antenna.
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