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CN112751479A - Mixed high-gain direct current converter - Google Patents

Mixed high-gain direct current converter Download PDF

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Publication number
CN112751479A
CN112751479A CN202110002699.5A CN202110002699A CN112751479A CN 112751479 A CN112751479 A CN 112751479A CN 202110002699 A CN202110002699 A CN 202110002699A CN 112751479 A CN112751479 A CN 112751479A
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Prior art keywords
unit
inductor
diode
switch
energy storage
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Inventor
李守翔
付昱
王向周
郑戍华
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Beijing Institute of Technology BIT
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Beijing Institute of Technology BIT
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Priority to CN202110002699.5A priority Critical patent/CN112751479A/en
Publication of CN112751479A publication Critical patent/CN112751479A/en
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    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of dc power input into dc power output
    • H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
    • H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
    • H02M3/06—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider
    • H02M3/07—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using resistors or capacitors, e.g. potential divider using capacitors charged and discharged alternately by semiconductor devices with control electrode, e.g. charge pumps

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Dc-Dc Converters (AREA)

Abstract

The invention relates to a hybrid high-gain direct current converter. According to the hybrid high-gain direct current converter, the first unidirectional conducting unit, the second unidirectional conducting unit, the first energy storage unit, the second energy storage unit, the third energy storage unit and the switch unit comprising the first switch subunit and the second switch subunit are adopted, so that current can be in a continuous state, a circuit is changed into a voltage-adjustable circuit, the voltage gain range is enlarged, and in addition, the specific circuit structure of the direct current converter designed by the invention can not cause the problem that the efficiency of the direct current converter is reduced.

Description

Mixed high-gain direct current converter
Technical Field
The invention relates to the technical field of electronic devices, in particular to a direct current converter.
Background
The conventional switched capacitor circuit has many defects, the first of which is the limited voltage range, namely the range of the regulated voltage and the range of the control output voltage; a second problem is the problem of hard-on switching, during which high dv/dt noise is easily generated, especially not suitable for high frequency applications. Furthermore, a third problem is that the efficiency of the SCC converter is greatly affected by the voltage gain and circuit configuration, and must be matched with appropriate topology and circuit parameters to achieve higher efficiency given the load range and requirements.
In view of the above problems in the prior art, the present invention is further improved by the patent document with publication number CN 110971124A.
Disclosure of Invention
The invention aims to provide a hybrid high-gain direct current converter, which can not only enable current to be in a continuous state, but also enable a circuit to be a voltage-adjustable circuit by utilizing the voltage pumping action of a switched capacitor and the turn ratio of the primary side and the secondary side of a coupling inductor, thereby enlarging the voltage gain range and avoiding the problem of efficiency reduction.
In order to achieve the purpose, the invention provides the following scheme:
a dc converter, comprising: the energy storage device comprises a positive input end, a negative input end, a positive output end, a negative output end, a first one-way conductive unit, a second one-way conductive unit, a switch unit, a first energy storage unit, a second energy storage unit and a third energy storage unit;
the switch unit comprises a first switch subunit and a second switch subunit;
the input end of the first unidirectional conducting unit, the negative output end and one end of the first switch subunit are all connected to the positive input end; the other end of the first switch subunit is connected with the negative input end; the second output end of the first unidirectional conductive unit is connected with the input end of the second unidirectional conductive unit; the second output end of the second unidirectional conductive unit is connected with the positive output end; the first output end of the second unidirectional conductive unit is connected with one end of the third energy storage unit; the other end of the third energy storage unit and one end of the first energy storage unit are both connected with the first output end of the first unidirectional conductive unit; the other end of the first energy storage unit is connected with one end of the second switch subunit; the other end of the second switch subunit is connected with the other end of the first switch subunit; one end of the second energy storage unit is connected with the positive input end; and the other end of the second energy storage unit is connected with a second output end of the second unidirectional conductive unit.
Preferably, the first switch subunit includes: a first inductor and a switching tube;
one end of the first inductor is connected with the input end of the first unidirectional conductive unit; the other end of the first inductor is connected with one end of the switching tube; the other end of the switch tube is connected with the negative input end; the other end of the second switch subunit is connected with a connecting line of the first inductor and the switch tube.
Preferably, the first switching unit includes: a switching tube and a first inductor;
one end of the switch tube is connected with the input end of the first unidirectional conductive unit; the other end of the switching tube is connected with one end of the first inductor; the other end of the first inductor is connected with the negative input end; the other end of the second switch subunit is connected with a connecting line of the switch tube and the first inductor.
Preferably, the second switching subunit includes: a second inductor;
one end of the second inductor is connected with the other end of the first energy storage unit; the other end of the second switch subunit is connected with a connecting line of the first inductor and the switch tube.
Preferably, the first unidirectional conductive unit includes a first diode and a second diode;
the input end of the first diode is connected with the positive input end; the output end of the first diode is respectively connected with the input end of the second diode and the first output end of the first unidirectional conductive unit; and the output end of the second diode is connected with the second output end of the first unidirectional conductive unit.
Preferably, the second unidirectional conductive unit includes a third diode and a fourth diode;
the input end of the third diode is connected with the second output end of the first unidirectional conductive unit; the output end of the third diode is connected with the first output end of the second unidirectional conductive unit; the input end of the fourth diode is connected with the first output end of the second unidirectional conductive unit; and the output end of the fourth diode is connected with the second output end of the second unidirectional conducting unit.
Preferably, the first energy storage unit, the second energy storage unit and the third energy storage unit each include a capacitor.
Preferably, the device further comprises a filtering unit;
one end of the filtering unit is connected with the positive output end; and the other end of the filtering unit is connected with the negative output end.
Preferably, the filtering unit includes a capacitor and a resistor;
the capacitor and the resistor are connected in parallel.
According to the specific embodiment provided by the invention, the invention discloses the following technical effects:
according to the hybrid high-gain direct current converter provided by the invention, the first unidirectional conductive unit, the second unidirectional conductive unit, the first energy storage unit, the second energy storage unit, the third energy storage unit and the switch unit comprising the first switch subunit and the second switch subunit are adopted, so that the current can be in a continuous state, the circuit is changed into a voltage-adjustable circuit, and the voltage gain range is enlarged.
Drawings
In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings needed to be used in the embodiments will be briefly described below, and it is obvious that the drawings in the following description are only some embodiments of the present invention, and it is obvious for those skilled in the art to obtain other drawings without inventive exercise.
FIG. 1 is a schematic diagram of a hybrid high-gain DC converter provided by the present invention;
fig. 2 is a schematic structural diagram of a dc converter when a first switch subunit provided by the embodiment of the present invention is in a first structure;
fig. 3 is a schematic diagram of an equivalent circuit of the dc converter in a time interval of [0, DTs ] when the first switch subunit of the embodiment of the present invention is in the first configuration;
fig. 4 is a schematic diagram of an equivalent circuit of the dc converter in the time interval [ DTs, Ts ] when the first switch subunit of the embodiment of the present invention is in the first configuration;
fig. 5 is a graph of simulation results of input voltages of the dc converter under conditions that D is 0.5 and n is 1 when the first switch subunit provided in the embodiment of the present invention is in the first configuration;
fig. 6 is a graph of simulation results of output voltages of the dc converter under conditions that D is 0.5 and n is 1 when the first switch subunit provided in the embodiment of the present invention is in the first configuration;
fig. 7 is a diagram illustrating simulation results of voltage gain of the dc converter under different duty ratios when the first switch subunit has the first structure according to an embodiment of the present invention;
fig. 8 is a schematic structural diagram of a dc converter when the first switch subunit is in the second configuration according to the embodiment of the present invention;
fig. 9 is a schematic structural diagram of a dc converter when a first switch subunit provided by the embodiment of the present invention is in a second structure;
fig. 10 is a schematic diagram of a dc converter with a coupled inductor primary side replacing a switching transistor in a conventional Dickson circuit according to an embodiment of the present invention;
fig. 11 is a schematic structural diagram of a dc converter in which a primary side of a coupling inductor is used to replace a switching tube in a conventional 3X fibonacci circuit according to an embodiment of the present invention;
fig. 12 is a schematic structural diagram of a dc converter when a switching tube in a conventional 3X series-parallel circuit is replaced by a primary side of a coupled inductor according to an embodiment of the present invention;
fig. 13 is a schematic structural diagram of a dc converter in which a switching tube of a conventional 4X voltage multiplier circuit is replaced by a primary side of a coupled inductor according to an embodiment of the present invention;
reference numerals:
the circuit comprises a positive input end 1, a negative input end 2, a positive output end 3, a negative output end 4, a first one-way conducting unit 5, a second one-way conducting unit 6, a switch unit 7, a first switch subunit 7-1, a second switch subunit 7-2, a first energy storage unit 8, a second energy storage unit 9, a third energy storage unit 10 and a filtering unit 11.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
The invention aims to provide a hybrid high-gain direct current converter, which can not only enable current to be in a continuous state, but also enable a circuit to be a voltage-adjustable circuit by utilizing the voltage pumping action of a switched capacitor and the turn ratio of the primary side and the secondary side of a coupling inductor, thereby enlarging the voltage gain range and avoiding the problem of efficiency reduction.
In order to make the aforementioned objects, features and advantages of the present invention comprehensible, embodiments accompanied with figures are described in further detail below.
Fig. 1 is a schematic diagram of a hybrid high-gain dc converter provided in the present invention, and as shown in fig. 1, a dc converter includes: the energy storage device comprises a positive input end 1, a negative input end 2, a positive output end 3, a negative output end 4, a first one-way conducting unit 5, a second one-way conducting unit 6, a switch unit 7, a first energy storage unit 8, a second energy storage unit 9 and a third energy storage unit 10.
The switching unit 7 comprises a first switching sub-unit 7-1 and a second switching sub-unit 7-2.
The input end and the negative output end 4 of the first unidirectional conducting unit 5 and one end of the first switch subunit 7-1 are all connected to the positive input end 1. The other end of the first switch subunit 7-1 is connected to the negative input terminal 2. A second output terminal of the first unidirectional conductive element 5 is connected to an input terminal of the second unidirectional conductive element 6. A second output of the second unidirectional conductive element 6 is connected to the positive output 3. A first output terminal of the second unidirectional conducting unit 6 is connected with one end of the third energy storage unit 10. The other end of the third energy storage unit 10 and one end of the first energy storage unit 8 are both connected with the first output end of the first unidirectional conductive unit 5. The other end of the first energy storage unit 8 is connected with one end of the second switch subunit 7-2. The other end of the second switch subunit 7-2 is connected to the other end of the first switch subunit 7-1. One end of the second energy storage unit 9 is connected with the positive input end 1. The other end of the second energy storage unit 9 is connected with a second output end of the second unidirectional conductive unit 6.
Wherein the first switch subunit 7-1 comprises: a first inductor L1 and a switch tube S2. The first switch subunit 7-1 has two different arrangement structures based on the first inductor L1 and the switch tube S2.
In the first structure, as shown in fig. 2, one end of the first inductor L1 is connected to the input end of the first unidirectional conductive element 5. The other end of the first inductor L1 is connected to one end of the switch tube S2. The other end of the switch tube S2 is connected to the negative input terminal 2. The other end of the second switch subunit 7-2 is connected to the connection between the first inductor L1 and the switch tube S2.
In the second structure, as shown in fig. 8, one end of the switching tube S2 is connected to the input end of the first unidirectional conductive element 5. The other end of the switch tube S2 is connected to one end of the first inductor L1. The other end of the first inductor L1 is connected to the negative input terminal 2. The other end of the second switch subunit 7-2 is connected to the connection between the switch tube S2 and the first inductor L1.
Based on the specific structure of the two different first switch subunits 7-1, the other units of the dc converter disclosed by the present invention are as follows:
the second switch subunit 7-2 includes: a second inductance L2. One end of the second inductor L2 is connected to the other end of the first energy storage unit 8. The other end of the second switch subunit 7-2 is connected to the connection between the first inductor L1 and the switch tube S2.
The first unidirectional conductive unit 5 includes a first diode D1 and a second diode D2. The input terminal of the first diode D1 is connected to the positive input terminal 1. An output terminal of the first diode D1 is connected to an input terminal of the second diode D2 and a first output terminal of the first unidirectional conductive unit 5, respectively. An output terminal of the second diode D2 is connected to a second output terminal of the first unidirectional conducting element 5.
The second unidirectional conductive unit 6 includes a third diode D3 and a fourth diode D4. An input terminal of the third diode D3 is connected to a second output terminal of the first unidirectional conducting element 5. An output terminal of the third diode D3 is connected to a first output terminal of the second unidirectional conducting element 6. An input terminal of the fourth diode D4 is connected to a first output terminal of the second unidirectional conducting element 6. An output terminal of the fourth diode D4 is connected to a second output terminal of the second unidirectional conducting element 6.
The first energy storage unit 8, the second energy storage unit 9 and the third energy storage unit 10 each include a capacitor. Wherein the first energy storage unit 8 comprises a first switched capacitor C1. The second energy storage unit 9 comprises a second switched capacitor C2; the third energy storage unit 10 comprises a third switched capacitor C3.
Preferably, the dc converter further comprises a filtering unit 11. One end of the filter unit 11 is connected to the positive output terminal 3. The other end of the filter unit 11 is connected to the negative output terminal 4.
The filter unit 11 includes a capacitor and a resistor. The capacitor and the resistor are connected in parallel.
In the conventional dc converter, the switching unit 7 includes two switching tubes, but the present invention provides a dc converter in which any one of the two switching tubes in the conventional dc converter is replaced by a coupled inductor (i.e., a first inductor), and a second switching subunit is added to provide a coupled inductor secondary side L2 (i.e., a second inductor L2) for the entire switching unit.
In the invention, the switch transistor S2, the first diode D1, the second diode D2, the third diode D3 and the fourth diode D4 may be mosfets or igbt transistors. When the circuit is arranged, the arrangement mode of ensuring the unidirectional flow of current is selected according to the working characteristics of the metal oxide semiconductor field effect transistor or the insulated gate bipolar transistor.
The dc converter in this embodiment of the present invention includes two states, and equivalent circuit diagrams in different time intervals are shown in fig. 3 and fig. 4, where D is a duty ratio of the switching tube S2, Ts is a period, and n is a ratio of secondary side turns to primary side turns of the coupling inductor. The specific working principle is as follows:
in [0, DTs]In a time interval, the switching tube S2 is controlled to be turned on, as shown in fig. 3, the first diode D1 and the third diode D3 are turned on, the second diode D2 and the fourth diode D4 are turned off, the power source Vin charges the first switching capacitor C1, the second switching capacitor C2 charges the third switching capacitor C3, and in an ideal situation and a CCM situation, voltages across the first inductor L1 have:
Figure BDA0002882179360000071
from the KVL equation:
Figure BDA0002882179360000072
in [ DTs, Ts ]]In a time interval, the switching tube S2 is controlled to be turned off, as shown in fig. 4, the second diode D2 and the fourth diode D4 are turned on, the first diode D1 and the third diode D3 are turned off, the first switching capacitor C1 charges the second switching capacitor C2, the power source Vin charges a load through the first switching capacitor C1 and the third switching capacitor C3, and under ideal conditions and CCM conditions, voltages at two ends of the first inductor L1 have: vL12＝VC1-VC2-VL22From the KVL equation: vin+VC2+VC3＝V0. Based on the volt-second balance principle of the two ends of the first inductor L1, DVL11+(1-D)V L120. Further, the voltage gain in the CCM case can be deduced as:
Figure BDA0002882179360000073
wherein V0To output a voltage, VinIs the input voltage of the power Vin.
As shown in fig. 5 and 6, the input voltage V is setin50V, duty cycle D0.5, formula derived from the above disclosure
Figure BDA0002882179360000074
Vo 450V, obtained from the simulated waveThe graph shows that the output voltage is approximately 450V, matching the theoretical calculation.
Fig. 7 shows that the error between the simulation result and the theoretical calculation is small and almost matches.
Analysis of the circuit in the second configuration of the first switch subunit reveals that, in the ideal case and CCM, when the switch S2 is turned on, there are:
VL11＝Vin。
when the switching tube S2 is turned off, there are:
VL12＝VC1-VC2-VL22。
also available from KCL and KVL:
VC2＝VC3。
Figure BDA0002882179360000075
Vin+VC2+VC3＝V0
the balance of the inductance volt-second is as follows:
DVL11+(1-D)VL12＝0。
further from the above formula:
Figure BDA0002882179360000081
as another embodiment of the present invention, as shown in fig. 8, the dc converter with the second structure of the first switch subunit as the core is provided.
One end of the switch tube S1 is connected with the input end of the first unidirectional conductive unit 5; the other end of the switch tube S1 is connected to one end of the primary side L1 of the coupled inductor; the other end of the primary side L1 of the coupled inductor is connected to the negative input terminal 2; one end of the secondary side L2 of the coupling inductor is connected with one end of the first energy storage unit 8; the other end of the secondary side L2 of the coupling inductor is connected to the connection line between the switching tube S1 and the primary side L1 of the coupling inductor.
D is the duty ratio of the switching tube S1, Ts is the period, and n is the ratio of the secondary side turns to the primary side turns of the coupling inductor. The specific working principle is as follows:
in [0, DTs]In a time interval, the switch tube S1 is controlled to be turned on, as shown in fig. 8, the second diode D2 and the fourth diode D4 are turned on, the first diode D1 and the third diode D3 are turned off, the first switch capacitor C1 charges the second switch capacitor C2, and the power supply V is connected to the power supply VinThe load is charged through the first switch capacitor C1 and the third switch capacitor C3, and under the ideal condition and the CCM condition, the voltage at two ends of the inductor L1 has VL11＝Vin. From the KVL equation:
VC1＝VC2-VL21、Vin+VC2+VC3＝V0。
in [ DTs, Ts ]]In the time interval, the switch tube S1 is controlled to be turned off, the first diode D1 and the third diode D3 are turned on, the second diode D2 and the fourth diode D4 are turned off, and the power supply V is controlled to be turned oninThe first switched capacitor C1 is charged, the second switched capacitor C2 is charged to the third switched capacitor C3, and in the ideal case and CCM, the voltage across the inductor L1 has:
VL12＝Vin-VC1-VL22from the KVL equation: vC2＝VC3. DV can be known according to the volt-second balance principle of the filter inductanceL11+(1-D)V L120. Further, the voltage gain in the case of CCM can be derived as
Figure BDA0002882179360000091
It was analytically found that in the ideal case and in the CCM case, when S1 is open, there are within [0, DTs ]:
VL11＝Vin。
VC1＝VC2-VL21。
Vin+VC2+VC3＝V0。
when S1 is turned off, within [ DTs, Ts ]:
VL12＝Vin-VC1-VL22。
also available from KCL and KVL:
VC2＝VC3
the voltage second balance of the filter inductor is as follows:
DVL11+(1-D)VL12＝0
further obtained from the above formulae:
Figure BDA0002882179360000092
when the position of the primary side of the coupling inductor is fixed, the secondary side winding has various insertion positions, and the directions of the same-name ends can be different.
As another embodiment of the present invention, the first switch subunit 7-1 in the dc converter provided by the present invention may include: a switch tube S2 and a coupling inductor primary side L1; the secondary winding position is shown in fig. 9. The specific structure of the dc exchanger in this embodiment is shown in fig. 9.
One end of the primary side L1 of the coupled inductor is connected to the input end of the first unidirectional conductive element 5; the other end of the primary side L1 of the coupling inductor is connected with one end of the switch tube S2; the other end of the switch tube S2 is connected with the negative input end 2; one end of the secondary side L2 of the coupling inductor is connected with the positive input end; the other end of the secondary side L2 of the coupled inductor is connected to the connection line between the primary side L1 of the coupled inductor and the first unidirectional conductive unit 5.
In [0, DTs]In a time interval, the switching tube S2 is controlled to be turned on, as shown in fig. 9, the first diode D1 and the third diode D3 are turned on, the second diode D2 and the fourth diode D4 are turned off, the power source Vin charges the first switching capacitor C1, the second switching capacitor C2 charges the third switching capacitor C3, and in an ideal situation and a CCM situation, n 2: n1 ═ n, the voltage across inductor L1 has: vL11＝Vin-VL21. From the KVL equation: vC2+VL21＝VC3、VC1＝VL11。
In [ DTs, Ts ]]In a time interval, the switch tube S2 is turned off, as shown in fig. 9, the second diode D2 and the fourth diode D4 are turned on, the first diode D1 and the third diode D3 are turned off, the first switch capacitor C1 charges the second switch capacitor C2, and the power supply V is connected to the power supply VinThe load is charged through the first switched capacitor C1 and the third switched capacitor C3, and under the ideal condition and the CCM condition, the voltage across the inductor L1 has: vL12＝VC1-VC2-VL22From the KVL equation: vin+VC2+VC3＝V0. DV is also known from the volt-second balance principle of two ends of the inductor L1L11+(1-D)V L120. Further, the voltage gain in the CCM case can be deduced as:
Figure BDA0002882179360000101
wherein V0Is the output voltage.
It was analytically found that in the ideal case and in the CCM case, when S1 is open, there are within [0, DTs ]:
VL11＝Vin-VL21
when S1 is turned off, within [ DTs, Ts ]:
VL12＝VC1--VC2--VL22
also available from KCL and KVL:
VC2+VL21＝VC3
VC1＝VL11
Vin+VC2+VC3＝V0
VL21＝nVL11
VL22＝nVL12
the voltage second balance of the filter inductor is as follows:
DVL11+(1-D)VL12＝0
further obtained from the above formulae:
Figure BDA0002882179360000102
according to the direct current converter, the switch tube is replaced by the coupling inductor, on one hand, the voltage pumping effect of the switch capacitor is utilized, on the other hand, the turn ratio of the primary side and the secondary side of the coupling inductor brings about further improvement of voltage gain, the defects that a traditional switch capacitor Ladder circuit is limited in voltage range and cannot regulate voltage are overcome, the circuit becomes a voltage-adjustable circuit, the voltage gain range is enlarged, and the circuit performance is greatly improved.
The following takes a conventional dc converter as an example to further extend the technical solution provided by the present invention and further explain the technical effects achieved.
First, a switching tube in a conventional Dickson circuit is replaced by a coupling inductor, and the secondary side position is as shown in fig. 10. The specific structure of the dc exchanger in this embodiment is shown in fig. 10.
Description of the drawings: in the following circuit, the voltage across the capacitor C1 is VC1The voltage across the capacitor C2 is VC2The voltage across the capacitor V3 is VC3，[0，DTs]Represents a model 1 circuit, [ DTs，Ts]Representing the Mode2 circuit, the voltage across the coupling inductor L1 (the first inductor L1) in the Mode1 circuit is VL11(ii) a The voltage across the coupling inductor L2 (the second inductor L2) is VL21The voltage across the coupling inductor L1 in the Mode2 circuit is VL12(ii) a The voltage across the coupling inductor L2 is VL22(ii) a The turn ratio of the secondary side L2 of the coupling inductor to the primary side L1 is n.
The circuit when the switch tube S1 is replaced by the coupled inductor primary side L1 is analyzed:
it is analytically known that in the ideal case and CCM situation, when the switching tube S2 is open, there are:
VL11＝Vin (1-1)
when the switching tube S2 is turned off, there are:
VL12＝Vin-VC2+VC1-VL22 (1-2)
also available from KCL and KVL:
VC2＝VC3-nVin (1-3)
VC1＝(n+1)Vin (1-4)
Vin-(n+1)VL12+VC3＝V0 (1-5)
the balance of the inductance volt-second is as follows:
DVL11+(1-D)VL12＝0 (1-6)
further obtainable from the formulae (1-1) to (1-6):
Figure BDA0002882179360000111
second, the switching tube in the 3X fibonacci circuit is replaced with a coupling inductor at the primary side, and the position of the coupling inductor at the secondary side is shown in the figure. The specific structure of the dc exchanger in this embodiment is shown in fig. 11.
Description of the drawings: in the following circuit, the voltage across the capacitor C1 is VC1The voltage across the capacitor C2 is VC2The voltage across the capacitor V3 is VC3，[0，DTs]Represents a model 1 circuit, [ DTs，Ts]The voltage across the coupling inductor L1 in the Mode1 circuit is V, which represents the Mode2 circuitL11(ii) a The voltage across the coupling inductor L2 is VL21The voltage across the coupling inductor L1 in the Mode2 circuit is VL12(ii) a The voltage across the coupling inductor L2 is VL22(ii) a The turn ratio of the secondary side to the primary side of the coupling inductor is n.
The circuit when the switching tube S1 was replaced by the primary side of the coupled inductor was analyzed:
it is analyzed that in the ideal case and CCM situation, when the switching tubes S2, S3 are on and S4 is off, there are:
VL11＝Vin (2-1)
when the switching tubes S2, S3 are turned off and S4 is turned on, there are:
VL12＝Vin+VC1-VC2 (2-2)
also available from KCL and KVL:
Vin+VL21+VC2＝V0 (2-3)
VC1＝(n+1)Vin (2-4)
the balance of the inductance volt-second is as follows:
DVL11+(1-D)VL12＝0 (2-5)
further obtainable from the formulae (2-1) to (2-5):
Figure BDA0002882179360000121
thirdly, the switching tube in the 3X series-parallel circuit is replaced by the coupling inductor at the primary side, and the position of the coupling inductor at the secondary side is shown in fig. 12. The specific structure of the dc exchanger in this embodiment is shown in fig. 12.
Description of the drawings: in the following circuit, the voltage across the capacitor C1 is VC1The voltage across the capacitor C2 is VC2，[0，DTs]Represents a model 1 circuit, [ DTs, Ts [ ]]The voltage across the coupling inductor L1 in the Mode1 circuit is V, which represents the Mode2 circuitL11(ii) a The voltage across the coupling inductor L2 is VL21Voltage V across coupling inductor L1 in Mode2 circuitL12(ii) a The voltage across the coupling inductor L2 is VL22(ii) a The turn ratio of the secondary side to the primary side of the coupling inductor is n.
The circuit when the switching tube S1 was replaced by the primary side of the coupled inductor was analyzed:
it was analytically found that in the ideal case and CCM situation, when S2, S4 are on and S3 are off, i.e. during [0, DTs ], the voltage across inductor L1 has:
VL11＝Vin (3-1)
when S2, S4 are turned off and S3 is turned on, i.e. during [ DTs, Ts ], the voltage across inductor L1 has:
VL12＝Vin-V0+VC1+VC2 (3-2)
and the KCL equation and the KVL equation can be used for obtaining:
VC1＝VC2＝(n+1)Vin (3-3)
the voltage volt-second balance between the two ends of the inductor L1 is as follows:
DVL11+(1-D)VL12＝0 (3-4)
the voltage gain in the case of CCM can be obtained from equations (3-1) to (3-4):
Figure BDA0002882179360000131
fourthly, the switching tube in the 4X voltage-multiplying circuit is replaced by the coupling inductor with the secondary side position as shown in fig. 13. The specific structure of the dc exchanger in this embodiment is shown in fig. 13.
Description of the drawings: in the following circuit, the voltage across the capacitor C1 is VC1The voltage across the capacitor C2 is VC2，[0，DTs]Represents a model 1 circuit, [ DTs, Ts [ ]]The voltage across the coupling inductor L1 in the Mode1 circuit is V, which represents the Mode2 circuitL11(ii) a The voltage across the coupling inductor L2 is VL21Voltage V across coupling inductor L1 in Mode2 circuitL12(ii) a The voltage across the coupling inductor L2 is VL22(ii) a The turn ratio of the secondary side to the primary side of the coupling inductor is n.
The circuit when the switching tube S1 was replaced by the primary side of the coupled inductor was analyzed:
it was analytically found that in the ideal case and CCM situation, when S2, S3 are on and S4 are off, i.e. during [0, DTs ], the voltage across inductor L1 has:
VL11＝Vin (4-1)
when S2, S3 are turned off and S4 is turned on, i.e. during [ DTs, Ts ], the voltage across inductor L1 has:
VL12＝Vin+VC1-VC2 (4-2)
and the KCL equation and the KVL equation can be used for obtaining:
Vin-VL12+VC1+VC3＝V0 (4-3)
VC2＝VC3 (4-4)
VC1＝(n+1)Vin (4-5)
the voltage volt-second balance between the two ends of the inductor L1 is as follows:
DVL11+(1-D)VL12＝0 (4-6)
the voltage gain in the case of CCM can be obtained from equations (4-1) to (4-5):
Figure BDA0002882179360000141
the embodiments in the present description are described in a progressive manner, each embodiment focuses on differences from other embodiments, and the same and similar parts among the embodiments are referred to each other.
The principles and embodiments of the present invention have been described herein using specific examples, which are provided only to help understand the method and the core concept of the present invention; meanwhile, for a person skilled in the art, according to the idea of the present invention, the specific embodiments and the application range may be changed. In view of the above, the present disclosure should not be construed as limiting the invention.

Claims (9)

1. A dc converter, comprising: the energy storage device comprises a positive input end, a negative input end, a positive output end, a negative output end, a first one-way conductive unit, a second one-way conductive unit, a switch unit, a first energy storage unit, a second energy storage unit and a third energy storage unit;
the switch unit comprises a first switch subunit and a second switch subunit;
the input end of the first unidirectional conducting unit, the negative output end and one end of the first switch subunit are all connected to the positive input end; the other end of the first switch subunit is connected with the negative input end; the second output end of the first unidirectional conductive unit is connected with the input end of the second unidirectional conductive unit; the second output end of the second unidirectional conductive unit is connected with the positive output end; the first output end of the second unidirectional conductive unit is connected with one end of the third energy storage unit; the other end of the third energy storage unit and one end of the first energy storage unit are both connected with the first output end of the first unidirectional conductive unit; the other end of the first energy storage unit is connected with one end of the second switch subunit; the other end of the second switch subunit is connected with the other end of the first switch subunit; one end of the second energy storage unit is connected with the positive input end; and the other end of the second energy storage unit is connected with a second output end of the second unidirectional conductive unit.
2. A dc converter according to claim 1, wherein the first switching sub-unit comprises: a first inductor and a switching tube;
one end of the first inductor is connected with the input end of the first unidirectional conductive unit; the other end of the first inductor is connected with one end of the switching tube; the other end of the switch tube is connected with the negative input end; the other end of the second switch subunit is connected with a connecting line of the first inductor and the switch tube.
3. A dc converter according to claim 1, wherein the first switching sub-unit comprises: a switching tube and a first inductor;
one end of the switch tube is connected with the input end of the first unidirectional conductive unit; the other end of the switching tube is connected with one end of the first inductor; the other end of the first inductor is connected with the negative input end; the other end of the second switch subunit is connected with a connecting line of the switch tube and the first inductor.
4. A dc converter according to claim 2 or 3, wherein the second switching sub-unit comprises: a second inductor;
one end of the second inductor is connected with the other end of the first energy storage unit; the other end of the second switch subunit is connected with a connecting line of the first inductor and the switch tube.
5. A dc converter according to claim 1, wherein the first unidirectional conducting unit comprises a first diode and a second diode;
the input end of the first diode is connected with the positive input end; the output end of the first diode is respectively connected with the input end of the second diode and the first output end of the first unidirectional conductive unit; and the output end of the second diode is connected with the second output end of the first unidirectional conductive unit.
6. A dc converter according to claim 1, wherein the second unidirectional conducting element comprises a third diode and a fourth diode;
the input end of the third diode is connected with the second output end of the first unidirectional conductive unit; the output end of the third diode is connected with the first output end of the second unidirectional conductive unit; the input end of the fourth diode is connected with the first output end of the second unidirectional conductive unit; and the output end of the fourth diode is connected with the second output end of the second unidirectional conducting unit.
7. A dc converter according to claim 1, wherein the first, second and third energy storage units each comprise a capacitor.
8. A dc converter according to claim 1, further comprising a filtering unit;
one end of the filtering unit is connected with the positive output end; and the other end of the filtering unit is connected with the negative output end.
9. A dc converter according to claim 8, wherein the filter unit comprises a capacitor and a resistor;
the capacitor and the resistor are connected in parallel.
CN202110002699.5A 2021-01-04 2021-01-04 Mixed high-gain direct current converter Pending CN112751479A (en)

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Cited By (1)

* Cited by examiner, † Cited by third party
Publication number Priority date Publication date Assignee Title
CN114944755A (en) * 2022-06-30 2022-08-26 北京理工大学 Wide-gain boost direct-current converter based on coupling inductor

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WO2015154563A1 (en) * 2014-08-13 2015-10-15 中兴通讯股份有限公司 Conversion circuit for direct-current switch power supply
CN108111014A (en) * 2017-11-30 2018-06-01 东南大学 Mixed symmetry active boost network transformation device
CN209120060U (en) * 2018-09-27 2019-07-16 许继电气股份有限公司 High-gain DC/DC converter and power-supply system based on coupling inductance
CN110971124A (en) * 2019-12-19 2020-04-07 北京理工大学 Direct current converter

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Publication number Priority date Publication date Assignee Title
WO2015154563A1 (en) * 2014-08-13 2015-10-15 中兴通讯股份有限公司 Conversion circuit for direct-current switch power supply
CN108111014A (en) * 2017-11-30 2018-06-01 东南大学 Mixed symmetry active boost network transformation device
CN209120060U (en) * 2018-09-27 2019-07-16 许继电气股份有限公司 High-gain DC/DC converter and power-supply system based on coupling inductance
CN110971124A (en) * 2019-12-19 2020-04-07 北京理工大学 Direct current converter

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* Cited by examiner, † Cited by third party
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