CN112583081A - Quick wireless charging circuit of battery - Google Patents
Quick wireless charging circuit of battery Download PDFInfo
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- CN112583081A CN112583081A CN202011530450.3A CN202011530450A CN112583081A CN 112583081 A CN112583081 A CN 112583081A CN 202011530450 A CN202011530450 A CN 202011530450A CN 112583081 A CN112583081 A CN 112583081A
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- 238000007600 charging Methods 0.000 title claims abstract description 70
- 238000012546 transfer Methods 0.000 claims abstract description 17
- 238000006243 chemical reaction Methods 0.000 claims abstract description 15
- 238000010280 constant potential charging Methods 0.000 claims abstract description 14
- 238000005070 sampling Methods 0.000 claims description 33
- 239000003990 capacitor Substances 0.000 claims description 25
- WHXSMMKQMYFTQS-UHFFFAOYSA-N Lithium Chemical compound [Li] WHXSMMKQMYFTQS-UHFFFAOYSA-N 0.000 claims description 20
- 229910052744 lithium Inorganic materials 0.000 claims description 20
- 238000000034 method Methods 0.000 claims description 17
- 229920000134 Metallised film Polymers 0.000 claims description 9
- 230000001105 regulatory effect Effects 0.000 claims description 9
- 230000008569 process Effects 0.000 claims description 7
- 239000000969 carrier Substances 0.000 claims description 6
- 238000001514 detection method Methods 0.000 claims description 3
- 230000000087 stabilizing effect Effects 0.000 claims description 3
- 238000012360 testing method Methods 0.000 claims description 3
- 230000008859 change Effects 0.000 description 7
- 238000004891 communication Methods 0.000 description 7
- 230000005540 biological transmission Effects 0.000 description 4
- 230000008901 benefit Effects 0.000 description 3
- 238000010586 diagram Methods 0.000 description 3
- 238000012986 modification Methods 0.000 description 3
- 230000004048 modification Effects 0.000 description 3
- 230000009471 action Effects 0.000 description 2
- 230000001276 controlling effect Effects 0.000 description 2
- 238000005516 engineering process Methods 0.000 description 2
- 230000006872 improvement Effects 0.000 description 2
- 230000003044 adaptive effect Effects 0.000 description 1
- 230000003321 amplification Effects 0.000 description 1
- 238000011217 control strategy Methods 0.000 description 1
- 230000007547 defect Effects 0.000 description 1
- 238000013461 design Methods 0.000 description 1
- 239000000428 dust Substances 0.000 description 1
- 230000005672 electromagnetic field Effects 0.000 description 1
- 238000003199 nucleic acid amplification method Methods 0.000 description 1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J7/00—Circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J7/007—Regulation of charging or discharging current or voltage
- H02J7/00712—Regulation of charging or discharging current or voltage the cycle being controlled or terminated in response to electric parameters
- H02J7/007182—Regulation of charging or discharging current or voltage the cycle being controlled or terminated in response to electric parameters in response to battery voltage
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J50/00—Circuit arrangements or systems for wireless supply or distribution of electric power
- H02J50/10—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling
- H02J50/12—Circuit arrangements or systems for wireless supply or distribution of electric power using inductive coupling of the resonant type
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
- H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02J—CIRCUIT ARRANGEMENTS OR SYSTEMS FOR SUPPLYING OR DISTRIBUTING ELECTRIC POWER; SYSTEMS FOR STORING ELECTRIC ENERGY
- H02J2207/00—Indexing scheme relating to details of circuit arrangements for charging or depolarising batteries or for supplying loads from batteries
- H02J2207/20—Charging or discharging characterised by the power electronics converter
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Computer Networks & Wireless Communication (AREA)
- Dc-Dc Converters (AREA)
- Charge And Discharge Circuits For Batteries Or The Like (AREA)
- Secondary Cells (AREA)
Abstract
The embodiment of the invention provides a rapid wireless charging circuit for a storage battery, which is characterized in that the rapid wireless charging circuit for the storage battery is applied to a magnetic resonance wireless energy transfer system and comprises a power conversion circuit and a control circuit, wherein the power conversion circuit is connected between a full-bridge rectification circuit of a receiving end circuit in the magnetic resonance wireless energy transfer system and a battery load and is used for adjusting output voltage and power to meet the charging requirement of the storage battery; the control circuit is used for realizing two stages of maximum efficiency charging and constant voltage charging of the storage battery.
Description
Technical Field
The invention belongs to the technical field of wireless power transmission power management, and relates to a power conversion circuit for rapidly and wirelessly charging a storage battery.
Background
Compared with a traditional wired power supply mode in a plug-in mode, the wireless energy transmission technology is more suitable for environments with dust and outer space, and the problems that a socket is easy to age, pollute and discharge instantly when being plugged in and out in wired plug-in charging are solved, so that the technology is more and more emphasized in the aerospace field.
The magnetic resonance wireless energy transfer system can completely physically isolate circuits at the transmitting end and the receiving end, can realize wireless power supply for external equipment and a detector, prolongs the service life of the external equipment and the detector, and does not need to frequently retransmit, thereby reducing the cost. However, since the transmitting end and the receiving end are physically isolated completely, the circuit information of the opposite end cannot be directly obtained at the two ends, so that a high-efficiency and high-power lithium battery is required to be charged, and higher requirements are provided for a circuit topology structure and a control strategy of the wireless energy transmission circuit topology structure.
The magnetic resonance wireless energy transfer system can generate an alternating electromagnetic field to transfer energy, and meanwhile, in an aerospace environment, communication control is not very reliable completely, so that a standby control scheme without communication needs to be researched, the magnetic resonance wireless energy transfer system can still normally work under the condition of communication failure, and the complexity of a communication circuit and control is reduced.
The traditional series resonant network has the advantages of being few in passive devices and simple in design, capable of achieving the input of a zero impedance angle and soft switching, meanwhile has a constant current output characteristic, and is a good choice for wireless charging of lithium batteries. However, the existing wireless charging system is controlled in a traditional constant-voltage constant-current mode, the efficiency is not high, and meanwhile, the complexity of a control circuit is improved due to the requirement of communication.
Disclosure of Invention
The invention aims to provide a quick wireless charging circuit for a storage battery, which is characterized in that the quick wireless charging circuit for the storage battery is applied to a magnetic resonance wireless energy transfer system and comprises a power conversion circuit and a control circuit, wherein the power conversion circuit is connected between a full-bridge rectification circuit of a receiving end circuit in the magnetic resonance wireless energy transfer system and a battery load and is used for adjusting output voltage and power so as to meet the charging requirement of the storage battery; the control circuit is used for realizing two stages of maximum efficiency charging and constant voltage charging of the storage battery.
Preferably, the power conversion circuit comprises a shunt regulator consisting of a switching tube Q1, a diode D1 and a voltage stabilizing filter capacitor C1, and a Buck circuit consisting of a switching tube Q2, a diode D2, a filter inductor L1 and a filter capacitor C2.
Preferably, the current output by the full-bridge rectifying circuit flows from the diode D1 to charge the capacitor C1, so that the output of the conventional S-S wireless energy transfer circuit is converted from a current source to a voltage source.
Preferably, by changing the duty ratio, the switching tube Q2 can be turned on and off continuously, current directly flows through the inductor when the switching tube Q2 is turned on, the capacitor and the battery are charged, the inductor L1 flows to the capacitor and the battery to discharge when the switching tube Q2 is turned off, and the diode D2 serves as a connector of a current loop; the duty cycles represent different ratios between the output voltage, i.e. the voltage Uc across the capacitor C2, and the input voltage, i.e. the voltage Uo across the capacitor C1.
Preferably, the control circuit comprises a voltage sampling module, a PI controller, an amplification circuit, a comparator, a subtractor, a triangular carrier generation circuit and a drive circuit; the control circuit controls the switching tubes Q1 and Q2 in the same way; the voltage sampling module is used for collecting a voltage Uc on the C1 and a voltage Uo on the C2; when the control circuit controls the switch tube Q1, the sampling value of the output voltage Uo and a given value Uref1 are connected to two ends of the PI controller, the PI output signal of the PI controller is connected to one end of the comparator, the other end of the PI controller is connected with the triangular carrier generating circuit, after the PI controller passes through the comparator, the output is high when the input of the positive end is higher than that of the negative end, otherwise, the output is zero, a square wave control signal with a certain duty ratio is formed, and the on-off state of the switch tube Q1 is changed through the driving circuit.
Preferably, the control circuit further comprises a maximum efficiency point tracking MPET linear fitting circuit, the maximum efficiency point tracking MPET linear fitting circuit obtains that the front end voltage of the Buck circuit has a linear relationship with the output voltage when the maximum efficiency is output by analyzing the relationship between the efficiency and the front end voltage of the Buck circuit and the output sampling voltage, and the maximum efficiency charging is realized by using the circuit as the given of the PI controller.
Preferably, the comparator comprises a comparator 1 and a comparator 2, the switching tube has two working states, and only one switching tube in each working state needs a soft switching control method when PWM wave control is needed; under the domain control, the triangular carriers of the comparator 1 and the comparator 2 are not necessarily consistent, and may be different carriers.
Preferably, the Buck circuit of the power variation circuit has two operation modes, including a maximum efficiency charging mode and a constant voltage charging mode; the maximum efficiency charging mode is that the switching tube Q1 is in a normally-off state, and the switching tube Q2 is in a modulation state; the constant-voltage charging mode is that the switching tube Q1 is in a modulation state, and the switching tube Q2 is in a normal open state.
Preferably, when the lithium battery does not reach the charging threshold voltage, the converter operates in the maximum efficiency charging mode, and the specific steps are as follows:
step 1: the input of a maximum efficiency tracking (MEPT) linear fitting circuit is a sampling value of output voltage, and the sampling ratio of the output voltage to the front end voltage is k; through actual tests, the front end voltage and the output voltage meet the linear relation under the state of the maximum efficiency working point; the output through the MEPT linear fitting circuit is used as the negative phase input Uref2 to the PI controller 2;
step 2: the negative phase input Uref1 of the PI controller 1 is equal to the threshold voltage of the lithium battery multiplied by the sampling ratio k, the positive phase input of the PI controller 1 is an output voltage sampling value, and when the voltage of the lithium battery does not reach the threshold voltage, the output of the PI controller 1 is zero;
and step 3: the negative phase input of the PI controller 2 is a given value obtained after the MPET algorithm is passed, the positive phase input of the PI controller 2 is a sampling value of the front end voltage, and the front end voltage of the Buck circuit is regulated through PI;
and 4, step 4: at the moment, the output of the PI controller 1 is zero, the PI controller 2 works normally, and the output is greater than zero, so that the output value of the large circuit is taken as the output of the PI controller 2; the output of the amplifying circuit is the positive input of the comparator 2 and is also the positive input of the subtracter; the negative phase input Vref of the subtracter needs to be larger than the maximum value of the triangular carrier 2, and the domains of the comparator 1 and the comparator 2 are completed;
and 5: the value range of the triangular wave 1 at the negative end of the comparator 1 is [ V1, V2], the value range of the triangular wave 2 at the negative end of the comparator 2 is [ V3, V4], the output value of the large circuit is larger than V1 and smaller than V2 through the self-adaptive adjustment of the PI controller, the comparator 2 outputs PWM waveform, and the PWM waveform is in a modulation state through a Buck driving circuit to adjust a switching tube Q2; since Vref is greater than V2, the output of comparator 1 is low, and the switch Q1 is adjusted to be in a normally-off state through the shoot driving circuit.
Preferably, when the lithium battery reaches the charging threshold voltage, the converter operates in a constant voltage charging mode, and the specific steps are as follows:
step 1: when the sampling value of the input and output voltage of the positive end of the PI controller 1 reaches the vicinity of the given value of the negative end, the output of the PI controller 1 starts to be increased continuously; when the output of the PI controller 1 is greater than the output of the PI controller 2, the large output is taken as the output of the PI controller 1, so that after passing through the comparator 2, the duty ratio of the Buck driving tube is continuously increased until the Buck tube is directly connected, and the Buck tube is in a flexible switching state;
step 2: the given Uref2 at the negative phase input of the PI controller 2 is larger than the voltage sampling value at the front end of the positive phase input, so the output of the PI controller 2 is zero; the positive and negative phase input of the PI controller 1 has a small error and is in a linear working area, and the PI output enters another range;
and step 3: taking the output of the PI controller 1 which is passed by the large circuit, wherein the output value is greater than (V3+ Vref) and less than (V4+ Vref) under the self-adaptive adjustment of the subtracter and the PI controller; when the negative phase input value Vref of the subtracter is subtracted from the output value, the input value of the positive phase input end of the comparator 1 is larger than V3 and smaller than V4, so that the comparator 1 outputs PWM waves, and the Shunt tube driving circuit controls the switching tube Q1 to be in a regulation state;
and 4, step 4: the large output value is greater than (V3+ Vref), since Vref is greater than V2, the output of the comparator 2 is at high level, and the switching tube Q2 is regulated to be in a normally-on state by the Buck tube driving circuit;
and 5: when the switch tube Q1 is switched on, the receiving end circuit is in a short-circuit state, and the battery load is powered by the capacitor C2; when the receiving end is short-circuited, the power of the transmitting end is sharply reduced, so that the power of the transmitting end is automatically adjusted along with the continuous increase of the duty ratio of the shunt pipe Q1, when the charging is finished, the power of the transmitting end is reduced to be extremely low, and the transmitting end can be automatically cut off through a detection circuit of the transmitting end, namely the whole charging process is completed.
The dual-mode charging control mode provided by the invention can automatically reduce power input along with the change of the charging state, and shunt the current to play a protection role, so that a large amount of power cannot be consumed on the shunt tube. The action of the shunt tube controls the output voltage, the duty ratio change of the shunt tube can change the input impedance, the power of the transmitting end can be gradually reduced along with the increase of the duty ratio, and finally when the power of the transmitting end is smaller than the lower power limit threshold, the transmitting end is powered off to finish the charging process.
The invention provides a high-efficiency wireless charging circuit without communication and a control mode, and realizes the dual-mode charging of a lithium battery by using a hardware circuit mode.
Drawings
FIG. 1 is a block diagram of a magnetic resonance wireless energy transfer system;
FIG. 2 is an improved power variation circuit in a block diagram of a magnetically resonant wireless energy transfer system;
fig. 3 is an improved control circuit in a block diagram of a magnetic resonance wireless energy transfer system.
Detailed Description
In order to make the aforementioned objects, features and advantages of the present invention comprehensible, embodiments accompanied with figures are described in further detail below.
In order to overcome the defect of low efficiency, a circuit topology is provided, namely a first-stage DC-DC converter is added at a receiving end to perform direct-current impedance matching on a battery. On the basis of the circuit topology, a corresponding control method and a corresponding control circuit are provided.
In order to meet the aim of quick charging of a storage battery, the invention provides a circuit topology which uses a traditional series resonant network, is added with a shunt pipe and is cascaded with a rear-stage Buck circuit, and has the capabilities of adapting to different battery loads and automatically adjusting primary side input power.
Based on the circuit topology, the invention provides a control method for realizing dual-mode charging of the lithium battery, and the Buck circuit and the shunt circuit are combined to flexibly switch two modes of maximum-efficiency charging and constant-voltage charging. And the purpose of protecting the battery load is realized by utilizing the shunt tubes, and the power-off operation after the charging is finished is realized by virtue of impedance change.
The invention provides a dual-mode control circuit and a method for maximum efficiency-constant voltage charging, which comprises the following steps: the method comprises the steps of detecting a front end voltage Uc and an output voltage Uo of the Buck converter, controlling the front end voltage of the Buck converter to finish impedance conversion when the output voltage is smaller than a threshold voltage of a battery, carrying out constant voltage regulation on the Buck converter when the output voltage is equal to the threshold voltage of the battery, continuously regulating the duty ratio of a switching tube of the Buck converter until the Buck converter is completely switched on, and enabling the shunt tube to act, so that a flexible conversion process is realized.
The dual-mode charging control mode provided by the invention can automatically reduce power input along with the change of the charging state, and shunt the current to play a protection role, so that a large amount of power cannot be consumed on the shunt tube. The action of the shunt tube controls the output voltage, the duty ratio change of the shunt tube can change the input impedance, the power of the transmitting end can be gradually reduced along with the increase of the duty ratio, and finally when the power of the transmitting end is smaller than the lower power limit threshold, the transmitting end is powered off to finish the charging process.
The invention provides a high-efficiency wireless charging circuit without communication and a control mode, and realizes the dual-mode charging of a lithium battery by using a hardware circuit mode.
In fig. 1, a magnetic resonance wireless energy transfer system in the prior art is mainly composed of a dc power supply, a high-frequency inverter, a primary side compensation network, a transmitting coil, a receiving coil, a secondary side compensation network, a rectifier, a power conversion circuit, and a battery load. The direct current power supply, the high-frequency inverter, the primary side compensation network and the transmitting coil belong to a transmitting end, and the receiving coil, the secondary side compensation network, the rectifier, the power conversion circuit and the battery load belong to a receiving end. When the lithium battery does not reach the charging threshold voltage, the maximum efficiency working point of series resonance is utilized to carry out impedance matching and then the lithium battery is charged with the maximum efficiency; and after the lithium battery reaches the charging threshold voltage, constant-voltage charging is carried out until the trickle charging state is reached, and the power supply is cut off to finish charging. The present invention is primarily an improvement of the power conversion circuit and control circuit of fig. 1.
As shown in fig. 2, the improved power conversion circuit includes a shunt regulator composed of a switching tube Q1, a diode D1, and a voltage stabilizing filter capacitor C1, and a Buck circuit composed of a switching tube Q2, a diode D2, a filter inductor L1, and a filter capacitor C2. The power converter is connected behind the rectifier, and the current of the rectified output flows from the diode D1 to charge the capacitor C1, so that the output of the traditional S-S type wireless energy transfer circuit can be converted into a voltage source from a current source. Under the control of a certain duty ratio, the switching tube Q2 can be switched on and off continuously, current directly flows through the inductor when the switching tube Q2 is switched on to charge the capacitor and the battery, the inductor L1 flows to discharge the capacitor and the battery after the switching tube Q2 is switched off, and the diode D2 serves as a connector of a current loop. Wherein diode D3 is an important protection against short-circuit discharge between the capacitor and the battery. The different duty cycles represent different ratios between the output voltage (the voltage Uc across the capacitor C2) and the input voltage (the voltage Uo across the capacitor C1) so that the battery can still be supplied with electrical energy as it increases voltage with changing state of charge.
The added shunt regulating circuit is an important improvement, aiming at the condition that the battery is not fully loaded in most of charging time, the problem that the battery needs trickle charging cannot be solved by only using a Buck circuit alone, the output characteristic of a common wireless energy transmission system is a constant current source, the battery cannot be fully charged without the shunt regulating function, and the battery is extremely easy to damage by using large current when the voltage threshold of the battery is reached.
As shown in fig. 3, the improved control circuit includes a voltage sampling module (a voltage Uc at C1 and a voltage Uo at C2), a PI controller, an amplifying circuit, a comparator, an adder, a triangular carrier generating circuit, and a driving circuit. The control circuit needs to control two switching tubes Q1, Q2, and one of them is taken as an example to illustrate the working process. The general control signal flow is as follows: the sampling value of the output voltage Uo and the given value Uref1 are connected to two ends of a PI controller, the PI output signal is connected to one end of a comparator, the other end of the PI output signal is connected with a triangular carrier, after the PI output signal passes through the comparator, the output is high when the input of the positive end is higher than that of the negative end, otherwise, the PI output signal is zero, a square wave control signal with a certain duty ratio is formed, and the on-off state of a switching tube can be changed through a driving circuit.
In addition, the maximum efficiency point tracking (MPET) linear fitting circuit analyzes the relationship between the efficiency and the Buck front end voltage and the output sampling voltage to obtain the linear relationship between the Buck front end voltage and the output voltage when the maximum efficiency is output, and the maximum efficiency charging can be realized by using the circuit as the given value of the PI controller.
The large circuit and the subtracter are core circuits for realizing the domain control, and the soft switching control method is used when the switching tube actually has two working states and only one switching tube needs PWM wave control in each working state. Under the domain control, the triangular carriers of the comparator 1 and the comparator 2 are not necessarily consistent, and can be different carriers, which is an important advantage.
Next, a method of controlling the circuit topology will be described.
In fig. 2, the Buck converter with the shunt function has two operation modes:
maximum efficiency charging mode: the switching tube Q1 is in a normally-off state, and the switching tube Q2 is in a modulation state;
constant voltage charging mode: the switch tube Q1 is in the modulating state, and the switch tube Q2 is in the normal on state.
Fig. 3 shows a control circuit and method based on a Buck converter with a Shunt function, which includes modules such as an output voltage sampling module, a front-end voltage sampling module, a maximum efficiency tracking (MPET) linear fitting circuit, a PI controller 1, a PI controller 2, a subtractor, a comparator 1, a comparator 2, a wave modulation circuit, a boost circuit, a Buck driving circuit, and a Shunt (Shunt) driving circuit.
When the lithium battery does not reach the charging threshold voltage, the converter works in the maximum efficiency charging mode, and the specific steps are as follows:
step 1: the input of the maximum efficiency tracking (MEPT) linear fitting circuit is a sampling value of output voltage, and the sampling ratio of the output voltage to the front end voltage is k. By utilizing the characteristic that the series resonant network has the maximum efficiency working point and being influenced by the efficiency of two-stage cascade of the Buck converter, the actual output still has the maximum efficiency output working point, but the actual output is deviated from the maximum efficiency working point of the series resonant network. Actual tests show that the front end voltage and the output voltage meet the linear relation under the maximum efficiency working point state. The output through the MEPT linear fitting circuit is input as the negative phase of the PI controller 2 Uref 2.
Step 2: the negative phase input Uref1 of the PI controller 1 is equal to the threshold voltage of the lithium battery multiplied by the sampling ratio k, the positive phase input of the PI controller 1 is an output voltage sampling value, and when the voltage of the lithium battery does not reach the threshold voltage, the output of the PI controller 1 is zero.
And step 3: the negative phase input of the PI controller 2 is a given value obtained after the MPET algorithm is carried out, the positive phase input of the PI controller 2 is a sampling value of the front end voltage, and the front end voltage of the Buck circuit is regulated through PI.
And 4, step 4: at this time, the output of the PI controller 1 is zero, the PI controller 2 operates normally, and the output is greater than zero, so that the output value of the large circuit is taken as the output of the PI controller 2. The output of the up circuit is the positive input of the comparator 2 and is also the positive input of the subtractor. The negative phase input Vref of the subtracter needs to be larger than the maximum value of the triangular carrier 2, and the domains of the comparator 1 and the comparator 2 are completed.
And 5: the value range of the triangular wave 1 at the negative end of the comparator 1 is [ V1, V2], the value range of the triangular wave 2 at the negative end of the comparator 2 is [ V3, V4], the output value of the large circuit is larger than V1 and smaller than V2 through the self-adaptive adjustment of the PI controller, the comparator 2 outputs PWM waveform, and the PWM waveform is in a modulation state through a Buck driving circuit to adjust a switching tube Q2; since Vref is greater than V2, the output of comparator 1 is low, and the switch Q1 is adjusted to be in a normally-off state through the shoot driving circuit.
When the lithium battery reaches the charging threshold voltage, the converter works in a constant-voltage charging mode, and the method specifically comprises the following steps:
step 1: when the sampling value of the positive terminal input/output voltage of the PI controller 1 reaches the vicinity of the negative terminal given value, the output of the PI controller 1 starts to rise continuously. When the output of the PI controller 1 is larger than the output of the PI controller 2, the large output is taken as the output of the PI controller 1, so that after passing through the comparator 2, the duty ratio of the Buck driving tube is continuously increased until the Buck tube is directly connected, and the Buck tube is in a flexible switching state.
Step 2: the negative input of the PI controller 2 gives Uref2 greater than the positive input front end voltage sample value, so the PI controller 2 output is zero. The positive and negative phase input of the PI controller 1 has a small error and is in a linear working area, and the PI output enters another range.
And step 3: the output of the PI controller 1 is taken as the output passed by the large circuit, and is subjected to adaptive adjustment by the subtracter and the PI controller at the moment, and the output value is greater than (V3+ Vref) and less than (V4+ Vref) at the moment. When the negative phase input value Vref of the subtractor is subtracted from the output value, the input value of the positive phase input terminal of the comparator 1 is greater than V3 and smaller than V4, so that the comparator 1 outputs a PWM wave, and the Shunt driving circuit controls the switching tube Q1 to be in a regulation state.
And 4, step 4: the large output value is greater than (V3+ Vref), the output of the comparator 2 is high because Vref is greater than V2, and the switching tube Q2 is regulated to be in a normally-on state by the Buck tube driving circuit.
And 5: when the switch tube Q1 is switched on, the receiving end circuit is in a short-circuit state, and the battery load is powered by the capacitor C2; when the receiving end is short-circuited, the power of the transmitting end is sharply reduced, so that the power of the transmitting end is automatically adjusted along with the continuous increase of the duty ratio of the shunt pipe Q1, when the charging is finished, the power of the transmitting end is reduced to be extremely low, and the transmitting end can be automatically cut off through a detection circuit of the transmitting end, namely the whole charging process is completed.
It will be apparent to those skilled in the art that various changes and modifications may be made in the invention without departing from the spirit and scope of the invention. Thus, if such modifications and variations of the present invention fall within the scope of the claims of the present invention and their equivalents, the present invention is also intended to include such modifications and variations.
Claims (10)
1. A quick wireless charging circuit for a storage battery is characterized in that the quick wireless charging circuit for the storage battery is applied to a magnetic resonance wireless energy transfer system and comprises a power conversion circuit and a control circuit, wherein the power conversion circuit is connected between a full-bridge rectification circuit of a receiving end circuit in the magnetic resonance wireless energy transfer system and a battery load and is used for adjusting output voltage and power to meet the charging requirement of the storage battery; the control circuit is used for realizing two stages of maximum efficiency charging and constant voltage charging of the storage battery.
2. The battery rapid wireless charging circuit according to claim 1, wherein the power conversion circuit comprises a Buck circuit consisting of a switching tube Q1, a diode D1, a shunt regulator consisting of a voltage stabilizing filter capacitor C1 and a switching tube Q2, a diode D2, a filter inductor L1 and a filter capacitor C2.
3. The fast wireless charging circuit for the storage battery as claimed in claim 2, wherein the current outputted from the full-bridge rectifying circuit flows from the diode D1 to charge the capacitor C1, so that the output of the conventional S-S type wireless energy transfer circuit is converted from a current source to a voltage source.
4. The fast wireless charging circuit of the storage battery as claimed in claim 3, wherein by changing the duty ratio, the switching tube Q2 can be turned on and off continuously, the current flows through the inductor directly when being turned on to charge the capacitor and the battery, the inductor L1 discharges the capacitor and the battery after being turned off, and the diode D2 serves as a connector of the current loop; the duty cycles represent different ratios between the output voltage, i.e. the voltage Uc across the capacitor C2, and the input voltage, i.e. the voltage Uo across the capacitor C1.
5. The fast wireless charging circuit for the storage battery according to claim 4, wherein the control circuit comprises a voltage sampling module, a PI controller, an amplifying circuit, a comparator, a subtracter, a triangular carrier generating circuit and a driving circuit; the control circuit controls the switching tubes Q1 and Q2 in the same way; the voltage sampling module is used for collecting a voltage Uc on the C1 and a voltage Uo on the C2; when the control circuit controls the switch tube Q1, the sampling value of the output voltage Uo and a given value Uref1 are connected to two ends of the PI controller, the PI output signal of the PI controller is connected to one end of the comparator, the other end of the PI controller is connected with the triangular carrier generating circuit, after the PI controller passes through the comparator, the output is high when the input of the positive end is higher than that of the negative end, otherwise, the output is zero, a square wave control signal with a certain duty ratio is formed, and the on-off state of the switch tube Q1 is changed through the driving circuit.
6. The circuit for rapidly wirelessly charging a secondary battery as claimed in claim 5, wherein the control circuit further comprises a maximum efficiency point tracking MPET linear fitting circuit, the maximum efficiency point tracking MPET linear fitting circuit obtains that the front end voltage of the Buck circuit has a linear relation with the output voltage when the maximum efficiency is output by analyzing the relation between the efficiency and the front end voltage of the Buck circuit and the output sampling voltage, and the maximum efficiency charging is realized by using the circuit as a given value of the PI controller.
7. The fast wireless charging circuit for the storage battery according to claim 6, wherein the comparator comprises a comparator 1 and a comparator 2, the switching tube has two working states, and each working state is a soft switching control method when only one switching tube needs PWM wave control; under the domain control, the triangular carriers of the comparator 1 and the comparator 2 are not necessarily consistent, and may be different carriers.
8. The battery fast wireless charging circuit according to claim 7, wherein the Buck circuit of the power varying circuit has two modes of operation, including a maximum efficiency charging mode and a constant voltage charging mode; the maximum efficiency charging mode is that the switching tube Q1 is in a normally-off state, and the switching tube Q2 is in a modulation state; the constant-voltage charging mode is that the switching tube Q1 is in a modulation state, and the switching tube Q2 is in a normal open state.
9. The fast wireless charging circuit for the storage battery according to claim 8, wherein when the lithium battery does not reach the charging threshold voltage, the converter operates in the maximum efficiency charging mode, and the specific steps are as follows:
step 1: the input of a maximum efficiency tracking (MEPT) linear fitting circuit is a sampling value of output voltage, and the sampling ratio of the output voltage to the front end voltage is k; through actual tests, the front end voltage and the output voltage meet the linear relation under the state of the maximum efficiency working point; the output through the MEPT linear fitting circuit is used as the negative phase input Uref2 to the PI controller 2;
step 2: the negative phase input Uref1 of the PI controller 1 is equal to the threshold voltage of the lithium battery multiplied by the sampling ratio k, the positive phase input of the PI controller 1 is an output voltage sampling value, and when the voltage of the lithium battery does not reach the threshold voltage, the output of the PI controller 1 is zero;
and step 3: the negative phase input of the PI controller 2 is a given value obtained after the MPET algorithm is passed, the positive phase input of the PI controller 2 is a sampling value of the front end voltage, and the front end voltage of the Buck circuit is regulated through PI;
and 4, step 4: at the moment, the output of the PI controller 1 is zero, the PI controller 2 works normally, and the output is greater than zero, so that the output value of the large circuit is taken as the output of the PI controller 2; the output of the amplifying circuit is the positive input of the comparator 2 and is also the positive input of the subtracter; the negative phase input Vref of the subtracter needs to be larger than the maximum value of the triangular carrier 2, and the domains of the comparator 1 and the comparator 2 are completed;
and 5: the value range of the triangular wave 1 at the negative end of the comparator 1 is [ V1, V2], the value range of the triangular wave 2 at the negative end of the comparator 2 is [ V3, V4], the output value of the large circuit is larger than V1 and smaller than V2 through the self-adaptive adjustment of the PI controller, the comparator 2 outputs PWM waveform, and the PWM waveform is in a modulation state through a Buck driving circuit to adjust a switching tube Q2; since Vref is greater than V2, the output of comparator 1 is low, and the switch Q1 is adjusted to be in a normally-off state through the shoot driving circuit.
10. The fast wireless charging circuit for secondary batteries according to claim 8, wherein the converter operates in a constant voltage charging mode when the lithium battery reaches a charging threshold voltage, comprising the steps of:
step 1: when the sampling value of the input and output voltage of the positive end of the PI controller 1 reaches the vicinity of the given value of the negative end, the output of the PI controller 1 starts to be increased continuously; when the output of the PI controller 1 is greater than the output of the PI controller 2, the large output is taken as the output of the PI controller 1, so that after passing through the comparator 2, the duty ratio of the Buck driving tube is continuously increased until the Buck tube is directly connected, and the Buck tube is in a flexible switching state;
step 2: the given Uref2 at the negative phase input of the PI controller 2 is larger than the voltage sampling value at the front end of the positive phase input, so the output of the PI controller 2 is zero; the positive and negative phase input of the PI controller 1 has a small error and is in a linear working area, and the PI output enters another range;
and step 3: taking the output of the PI controller 1 which is passed by the large circuit, wherein the output value is greater than (V3+ Vref) and less than (V4+ Vref) under the self-adaptive adjustment of the subtracter and the PI controller; when the negative phase input value Vref of the subtracter is subtracted from the output value, the input value of the positive phase input end of the comparator 1 is larger than V3 and smaller than V4, so that the comparator 1 outputs PWM waves, and the Shunt tube driving circuit controls the switching tube Q1 to be in a regulation state;
and 4, step 4: the large output value is greater than (V3+ Vref), since Vref is greater than V2, the output of the comparator 2 is at high level, and the switching tube Q2 is regulated to be in a normally-on state by the Buck tube driving circuit;
and 5: when the switch tube Q1 is switched on, the receiving end circuit is in a short-circuit state, and the battery load is powered by the capacitor C2; when the receiving end is short-circuited, the power of the transmitting end is sharply reduced, so that the power of the transmitting end is automatically adjusted along with the continuous increase of the duty ratio of the shunt pipe Q1, when the charging is finished, the power of the transmitting end is reduced to be extremely low, and the transmitting end can be automatically cut off through a detection circuit of the transmitting end, namely the whole charging process is completed.
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