CN111541373B - Control method of two-phase parallel synchronous rectification Boost converter based on forward coupling inductor - Google Patents
Control method of two-phase parallel synchronous rectification Boost converter based on forward coupling inductor Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/02—Conversion of dc power input into dc power output without intermediate conversion into ac
- H02M3/04—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters
- H02M3/10—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M3/145—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M3/155—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/156—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
- H02M3/158—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
- H02M3/1584—Conversion of dc power input into dc power output without intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load with a plurality of power processing stages connected in parallel
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/14—Arrangements for reducing ripples from dc input or output
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/38—Means for preventing simultaneous conduction of switches
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/0048—Circuits or arrangements for reducing losses
- H02M1/0054—Transistor switching losses
- H02M1/0058—Transistor switching losses by employing soft switching techniques, i.e. commutation of transistors when applied voltage is zero or when current flow is zero
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M1/00—Details of apparatus for conversion
- H02M1/38—Means for preventing simultaneous conduction of switches
- H02M1/385—Means for preventing simultaneous conduction of switches with means for correcting output voltage deviations introduced by the dead time
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention discloses a control method of a two-phase parallel synchronous rectification Boost converter based on a forward coupling inductor. The converter used by the invention only comprises the first power MOSFET, the second power MOSFET, the third power MOSFET, the fourth power MOSFET, the coupling inductor, the capacitor and the resistor, has a simple circuit structure and only has one magnetic element. Under the application of the PWM + phase-shift control method, the converter does not need any complex auxiliary circuit, can ensure the soft switching characteristic of a full switching tube, simultaneously reduces the inductive current ripple to the maximum extent, and realizes high-efficiency boost conversion. By adjusting the shift ratio, the converter can also work under the conditions of wide input voltage and wide load.
Description
Technical Field
The invention discloses a control method of a two-phase parallel synchronous rectification Boost converter based on a forward coupling inductor, and relates to the technical field of power electronics.
Background
A Boost converter circuit (Boost circuit) is the simplest Boost dc-dc converter circuit, and is widely used in the field of power electronics. However, since the soft switching cannot be realized when the switch works in the current continuous mode, large switching loss and high-frequency noise are caused, and the application of the switch in high-power occasions is limited.
In order to improve the power level of the Boost converter, the multiphase interleaved Boost converter is widely applied to high-power occasions due to the advantages of low input current ripple, low output voltage ripple and the like. However, the addition of magnetic elements and the operation in the hard switching state present challenges to high frequency and high power density. Therefore, the multiphase interleaving Boost converter based on the coupling inductor is produced at the same time, a plurality of magnetic elements can be integrated on one magnetic core by utilizing the magnetic integration technology, when the coupling inductor is coupled reversely, the inductive current ripple can be further inhibited, but soft switching is still not realized, and when the coupling inductor is coupled forwardly, the inductive current ripple can be greatly increased, the loss of each part can be increased, and the improvement of the efficiency is influenced.
Under the condition that an auxiliary circuit is not added, the traditional synchronous rectification Boost converter cannot realize the soft switching characteristic of a main switching tube, and all switching tubes need to work in a soft switching mode in order to further reduce the switching loss. In the two-phase interleaved parallel synchronous rectification Boost converter based on the forward coupling inductor, the inductor current reversal can be realized by means of mutual inductance, so that the soft switching characteristic of a full switching tube is realized, the switching loss of the switching tube can be obviously reduced, but the unnecessary power circulation is caused by the overlarge reverse current under the condition of light load, so that the current stress is larger, and the loss of other parts is increased.
Disclosure of Invention
The technical problem to be solved by the invention patent is as follows: in order to overcome the defects in the prior art, the control method of the two-phase parallel synchronous rectification Boost converter based on the forward coupling inductor is provided, and the soft switching characteristic of a full switching tube is realized and the inductor current ripple is reduced to the maximum extent by changing the modulation method, so that the conversion efficiency is improved, and the requirements of the high efficiency and the high power density of the converter are met.
The invention adopts the following technical scheme to solve the technical problems:
a control method of a two-phase parallel Boost converter based on a forward coupling inductor comprises a first power MOSFET, a second power MOSFET, a coupling inductor, a capacitor and a resistor, wherein the positive electrode of an input end is connected with the homonymous end of the first inductor of the coupling inductor and the homonymous end of the second inductor of the coupling inductor, the synonym end of the first inductor of the coupling inductor is connected with the drain electrode of the first power MOSFET and the source electrode of the second power MOSFET, the synonym end of the second inductor of the coupling inductor is connected with the drain electrode of the third power MOSFET and the source electrode of the fourth power MOSFET, the drain electrode of the second power MOSFET is connected with the drain electrode of the fourth power MOSFET, one end of the capacitor and one end of the resistor, and the negative electrode of the input end is connected with the source electrode of the first power MOSFET, the source electrode of the third power MOSFET, the other end of the capacitor and the other end of the resistor, and the control method comprises the following steps:
the upper and lower tubes of the two branch circuits are in complementary conduction, the duty ratios of the first power MOSFET and the third power MOSFET are represented by D, and the voltage is stably output through Pulse Width Modulation (PWM);
in the PWM control mode, a certain phase shift ratio exists between the driving signals of the main power MOSFETs of the two branches, and the phase shift ratio is used for representing the magnitude of a phase shift angle.
The phase shift ratio is adjusted according to the detected actual input voltage and the detected actual output power, so that the converter can realize the soft switching characteristic and simultaneously inhibit the inductive current ripple to the maximum extent.
The magnitude of the phase shift ratio is always smaller than D and smaller than 1-D.
The specific expression of the shift ratio is as follows:
to realize soft switching, the dead time of the driving signal is also required to satisfy:
compared with the prior art, the invention has the main technical characteristics that:
the two-phase parallel Boost converter circuit based on the forward coupling inductor has a simple structure, the phase shift ratio is dynamically adjusted by adopting the PWM + phase shift control method, and the coupling inductor current can obtain short-time reverse current, so that the soft switching characteristic of a full switch tube can be realized under the conditions of wide input voltage and wide load, the inductor current ripple is restrained to the maximum extent, the loss of each component of the converter is reduced, and the efficiency of the converter is improved.
Drawings
Fig. 1 is a two-phase parallel Boost converter circuit based on a forward-coupled inductor for use in the present invention, wherein: s1、S2、S3、S4Respectively a first MOSFET, a second MOSFET, a third MOSFET and a fourth MOSFET, L is the self-inductance in the coupling inductor, M is the mutual inductance in the coupling inductor, and the mutual inductance is
The homonymous terminal is shown as the figure CoIs a capacitor, RLIs a resistance.
Fig. 2 is an equivalent circuit diagram of a two-phase parallel Boost converter based on a forward coupling inductor after coupling inductor decoupling.
Fig. 3 is a three-dimensional relationship diagram of the inductive current ripple, the duty ratio and the phase shift ratio under the PWM + phase shift control.
Fig. 4 is a key waveform diagram of a two-phase parallel Boost converter based on a forward coupling inductor under PWM + phase shift control.
5-8 are equivalent circuit diagrams of different switching modes within one switching period of a two-phase parallel Boost converter based on forward coupling inductance under PWM + phase shift control when D is less than or equal to 0.5 and alpha is less than or equal to D.
FIG. 9 is S1And the starting process when the inductance current of the leading branch corresponding to the starting time is just zero.
FIG. 10 is a block diagram of the closed loop control of the system under PWM + phase shift control.
FIG. 11 is a closed loop simulation circuit diagram of one design example of the present invention.
Fig. 12 is a comparison of inductor current waveforms of fig. 11 under two-phase symmetric interleaving and phase shifting control at different input voltages.
Fig. 13 is a graph of the inductor current waveforms of the two branches of fig. 11 under full load, half load, and light load conditions.
Fig. 14 is a waveform of soft switching characteristics of the respective switching tubes of fig. 11 under nominal operating conditions.
Detailed Description
Reference will now be made in detail to embodiments of the present invention, examples of which are illustrated in the accompanying drawings, wherein like reference numerals refer to the same or similar elements or elements having the same or similar function throughout. The embodiments described below by referring to the drawings are exemplary only for explaining the present patent, and are not construed as limiting the present patent. All modifications made according to the spirit of the main technical scheme of the invention are covered in the protection scope of the invention.
The technical scheme of the invention is further explained in detail by combining the attached drawings:
a two-phase parallel synchronous rectification Boost converter based on a forward coupling inductor comprises first to fourth power MOSFETs, a coupling inductor, a capacitor and a resistor.
The positive electrode of the input end is connected with the homonymous end of a first inductor of the coupling inductor and the homonymous end of a second inductor of the coupling inductor, the synonym end of the first inductor of the coupling inductor is connected with the drain electrode of the first power MOSFET and the source electrode of the second power MOSFET, the synonym end of the second inductor of the coupling inductor is connected with the drain electrode of the third power MOSFET and the source electrode of the fourth power MOSFET, the drain electrode of the second power MOSFET is connected with the drain electrode of the fourth power MOSFET, one end of a capacitor and one end of a resistor, and the negative electrode of the input end is connected with the source electrode of the first power MOSFET, the source electrode of the third power MOSFET, the other end of the capacitor and the other end of the resistor.
FIG. 1 is a main circuit structure, FIG. 2 is an equivalent circuit after decoupling of a coupling inductor, because of two degrees of freedom of a duty ratio D and a phase shift angle alpha, a converter has multiple switch modes, and branch ripple current magnitude delta I under different modesL_maxThe expression of (a) is:
wherein L is the self-inductance of the coupling inductor, k is the coupling coefficient of the coupling inductor, fsTo the switching frequency, VoOutputting a voltage for the converter.
From the above equation, a three-dimensional relationship graph among the current ripple, the duty ratio and the phase shift ratio shown in fig. 3 can be drawn, and it can be concluded that the current ripple can be suppressed by reducing the phase shift ratio α under different duty ratio states, and the suppression effect is more obvious when the duty ratio D is about 0.5, so the phase shift ratio α is always smaller than D and smaller than 1-D.
The specific working principle of the invention is described by taking the case that the converter works at D less than or equal to 0.5 and alpha less than or equal to D as an example and combining the attached figures 4-8. As can be seen from fig. 2, the whole converter has 4 switching states in one switching cycle, respectively[t0～t1]、[t1～t2]、[t2～t3]、[t3～t4](see FIG. 2). The following contents are divided into two parts of switch mode concrete analysis and soft switch implementation condition concrete analysis.
The working conditions of the switching modes are specifically analyzed, and before analysis, all the devices are assumed to be ideal devices.
Switched mode 1[ t ]0～t1]
S1、S4Conduction, S2、S3Off, there are two circuits Vin→Lm→Llk2→S4→RL/Co，Vin→Lm→Llk1→S1Inductor current i2Linearly decreasing and then reversing, while the inductor current i1The linearity rises. When S is4After turn-off, the inductor current i2To S4Junction capacitance Cs4Charging to an output voltage VoThus S4For buffer turn-off, simultaneously for S3Junction capacitance Cs3Discharge to zero as S3Zero voltage turn-on creates conditions.
Switched mode 2[ t ]1～t2]
At t1Time of day, S3The zero voltage turns on. At this time S1、S3Conduction, S2、S4Off, there are two circuits Vin→Lm→Llk2→S1→RL/Co，Vin→Lm→Llk1→S3At this moment, the input side simultaneously transfers energy to the two branch inductors, namely inductor current i1Slowly rises to a maximum value Imax。
Switching mode 3[ t ]2～t3]
At t2Time of day, S1Off, inductor current i1To S1Junction capacitance Cs1Charging to an output voltage VoThus S1For buffer turn-off, simultaneously for S2Junction capacitance Cs2Discharge to zero, realize S2The zero voltage turns on. At this time S2、S3Conduction, S1、S4Off, there are two circuits Vin→Lm→Llk2→S3，Vin→Lm→Llk1→S2→RL/CoInductor current i1Linear decrease, inductor current i2Linearly increasing to a maximum value Imax。
Switch mode 4[ t ]3～t4]
S3After turn-off, inductor current i2To S3Junction capacitance Cs3Charging to the output voltage Vo, thus S3For buffer turn-off, simultaneously for S4Junction capacitance Cs4Discharge to zero, realize S4The zero voltage of (2) turns on. At this time S2、S4Conduction, S1、S3Off, there are two circuits Vin→Lm→Llk2→S4→RL/Co，Vin→Lm→Llk1→S2→RL/CoWhen the input side transmits energy to the output side through the two branches, the inductive current i1Slowly falls to the minimum value Imin。
The following detailed analysis of the soft switching implementation conditions can be equivalent to two aspects of reverse current limitation and dead time limitation.
Switch tube S2、S4As an auxiliary switch tube, the zero voltage switching-on can be realized relatively easily by means of forward current, and the switch tube S1、S3As the main switching tube realizes zero voltage switching-on by means of reverse current, the soft switching characteristic realization condition of the main switching tube is more rigorous.
It can also be seen from fig. 4 that the end of the switching mode 4 is the inductor current i1Rising rapidly, the part of the dead time current rise, S, not being negligible1Zero voltage conduction of (2) requires its turn-on time current i1Is equal to zero, thus S1Compared with S3，S1Zero voltage lead ofThe on condition is more severe, and is taken as a sufficient necessary condition for reverse current, namely:
Imin+k1βTs＝0
wherein IminMinimum value of inductor current, k1For switching mode 1 process i1The rate of change of rise, β, is the drive signal dead time.
Therefore, the requirements of the zero-voltage conduction condition downward shifting comparison can be met:
wherein, PoThe forward coupling inductor based two-phase parallel synchronous rectification Boost converter is used for representing the output power of the two-phase parallel synchronous rectification Boost converter based on the forward coupling inductor, and the phase shift ratio under different input voltage and output power conditions can be adjusted according to the formula so as to realize the minimum inductance current ripple on the premise of meeting the zero voltage conduction condition.
The reverse of the inductive current is only a necessary condition for realizing the soft switch, in addition, the junction capacitance of the main switch tube discharges to zero voltage at the conduction moment, which is another premise for realizing the zero voltage conduction of the main switch tube, and the dead time is required to be not too small, and the attached figure 9 is S1The method comprises the following steps that the starting process when the inductive current of a leading branch corresponding to the starting moment is just zero is carried out at the starting moment, and the shadow part is the total electric quantity which can be extracted through the inductive current in the dead time so as to meet the requirement of a main switching tube S1Zero voltage turns on, then needs to satisfy:
wherein C isossFor representing the output junction capacitances of the first through fourth power MOSFETs.
The invention aims at a two-phase parallel synchronous rectification Boost converter based on a forward coupling inductor, and draws a system closed-loop control block diagram G shown in figure 10c(s) is a compensator, VMFor modulating the amplitude of the triangular wave, Gvd(s) is a converterDuty cycle to output voltage transfer function, h(s) is the feedback link. The phase shift regulation is added on the basis of single-voltage closed-loop control, so that the technical characteristics of the invention are realized, and the performance of the converter is improved.
FIG. 11 is a closed loop simulation circuit diagram of one example of a design of the present invention. The performance indexes are that the input voltage range is 50-300V, the rated input voltage is 175V, the rated output voltage is 350V, the rated full-load power is 800W, and the switching frequency is 250 kHz. In the design, the structure provided by the invention is applied, the self inductance of the coupling inductor is 38.5 muH, the mutual inductance is 33.7 muH, and the capacitance value of the output capacitor is 20 muF.
Fig. 12 is a comparison graph of waveforms of inductive currents under two-phase symmetric interleaving and phase-shifting control under different input voltages obtained by simulation, and it can be known from simulation results that when two-phase coupled inductors are coupled in a forward direction, if fixed symmetric interleaving control is adopted, inductive current ripples are very large when the input voltage is large, although soft switching can be easily achieved, large reverse current can cause high-power energy backflow, so that efficiency improvement is affected, and this is an important reason why most scholars select reverse coupling without considering forward coupling. And under the phase shift regulation, the current ripple can be greatly reduced under different input voltage conditions, the ripple suppression effect is particularly obvious when the input voltage is 175V, and the result accords with the conclusion that the suppression effect is more obvious when the duty ratio D is about 0.5 analyzed above, so that the problem of large inductance current ripple during forward coupling is solved.
Fig. 13 shows the waveforms of the inductive currents of the two branches of the design example under the conditions of full load, half load and light load, and the simulation results show that the short-term reverse current can be obtained under different load conditions, so that the soft switching characteristic of the main switching tube is realized.
FIG. 14 shows the soft switching characteristic waveforms of the switching tubes under rated operating conditions, as can be seen from FIGS. 14(a) and (c), the leading branch main switching tube S1And lagging branch main switching tube S3The approximate ZVZC switching-on is realized, but the buffering switching-off effect is not obvious due to the fact that the current is large at the switching-off moment. From FIGS. 14(b) and (d), it can be seen that the leading branch auxiliary switch tube S2And a lagging branch auxiliary switching tubeS4In addition, the current at the turn-on moment is small, the buffer turn-off is obvious, and in addition, the switch tube S is provided with a switch tube S4While also achieving an approximate ZC turn-off.
From the above description, under the PWM + phase shift control method, the two-phase parallel synchronous rectification Boost converter based on the forward coupling inductor has the following advantages:
the circuit has simple structure, does not need to design additional auxiliary devices or circuits, does not need a complex control mode, can realize the soft switching characteristic of a full switching tube by only using one magnetic element, improves the efficiency of the converter, and is favorable for high-frequency high-power density design.
The phase shift ratio is dynamically adjusted, so that the converter can realize soft switching under the conditions of wide input voltage and wide load, the inductive current ripple is reduced to the maximum extent, and high-efficiency boost conversion is realized.
Claims (4)
1. A control method of a two-phase parallel synchronous rectification Boost converter based on a forward coupling inductor comprises a first power MOSFET, a second power MOSFET, a coupling inductor, a capacitor and a resistor, wherein the positive pole of an input end is connected with the dotted terminal of the first inductor of the coupling inductor and the dotted terminal of the second inductor of the coupling inductor, the synonym terminal of the first inductor of the coupling inductor is connected with the drain electrode of the first power MOSFET and the source electrode of the second power MOSFET, the synonym terminal of the second inductor of the coupling inductor is connected with the drain electrode of the third power MOSFET and the source electrode of the fourth power MOSFET, the drain electrode of the second power MOSFET is connected with the drain electrode of the fourth power MOSFET, one end of the capacitor and one end of the resistor, the negative pole of the input end is connected with the source electrode of the first power MOSFET, the source electrode of the third power MOSFET, the other end of the capacitor and the other end of the resistor, the control method comprises the following steps:
the upper and lower tubes of the two branch circuits are in complementary conduction, the duty ratios of the first power MOSFET and the third power MOSFET are represented by D, and the output voltage is stabilized through pulse width modulation;
under a PWM control mode, a certain phase shift ratio exists between driving signals of main power MOSFETs of two branches, and the phase shift ratio is used for representing the magnitude of a phase shift angle;
the expression of the phase shift ratio is as follows:
the alpha is used for representing the phase shift ratio of the two-phase parallel synchronous rectification Boost converter based on the forward coupling inductance, and the P isoIs used for representing the output power of the two-phase parallel synchronous rectification Boost converter based on the forward coupling inductor, and the V isoThe forward coupling inductor-based two-phase parallel synchronous rectification Boost converter is used for representing the output voltage of the forward coupling inductor-based two-phase parallel synchronous rectification Boost converter, the L is used for representing the self inductance of the coupling inductor, the k is used for representing the coupling coefficient of the coupling inductor, and the f is used for representing the self inductance of the coupling inductorsThe beta is used for representing the driving signal dead time of the two-phase parallel synchronous rectification Boost converter based on the forward coupling inductance.
2. The control method according to claim 1, wherein the phase shift ratio of the two-phase parallel synchronous rectification Boost converter based on the forward coupling inductor is adjusted according to the detected actual input voltage and actual output power, so that the converter can realize the soft switching characteristic and simultaneously suppress the inductor current ripple to the maximum extent without influencing the gain characteristic of the converter.
3. The control method of claim 2, wherein the phase shift ratio of the two-phase parallel synchronous rectification Boost converter based on the forward coupling inductor is always less than D and less than 1-D.
4. The control method according to claim 1, wherein the two-phase parallel synchronous rectification Boost converter based on the forward coupling inductor further requires that the dead time of the driving signal satisfies the following requirements for realizing the soft switching characteristic:
said C isossFor representing output junction capacitances of the first to fourth power MOSFETs, the IminFor representing a current minimum of the coupling inductance.
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| CN112886801B (en) * | 2021-01-11 | 2022-04-01 | 合肥科威尔电源系统股份有限公司 | Method and system for improving voltage and current overshoot during switching of PWM mode and phase-shift mode |
| CN113285598B (en) * | 2021-05-19 | 2022-11-25 | 哈尔滨工业大学 | Hybrid control structure and method for interleaved Boost converters |
| CN113783426A (en) * | 2021-08-20 | 2021-12-10 | 深圳市新思电能科技有限责任公司 | Synchronous coupling Boost circuit, Boost circuit and power supply device |
| CN113676045B (en) * | 2021-08-24 | 2024-01-26 | 北京理工大学 | Digital soft switch control method of staggered synchronous BUCK converter based on coupling inductance |
| CN115940637A (en) * | 2022-11-02 | 2023-04-07 | Oppo广东移动通信有限公司 | Power supply device, system, method, electronic device and readable storage medium |
| JP2024127083A (en) * | 2023-03-08 | 2024-09-20 | 株式会社デンソー | Control device for power conversion circuit and control program for power conversion circuit |
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