CN110943624A - Zero-voltage switch's resonant power supply converting circuit and converter - Google Patents
Zero-voltage switch's resonant power supply converting circuit and converter Download PDFInfo
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- CN110943624A CN110943624A CN201911309642.9A CN201911309642A CN110943624A CN 110943624 A CN110943624 A CN 110943624A CN 201911309642 A CN201911309642 A CN 201911309642A CN 110943624 A CN110943624 A CN 110943624A
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/33507—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters
- H02M3/33523—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of the output voltage or current, e.g. flyback converters with galvanic isolation between input and output of both the power stage and the feedback loop
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/4815—Resonant converters
- H02M7/4818—Resonant converters with means for adaptation of resonance frequency, e.g. by modification of capacitance or inductance of resonance circuits
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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Abstract
The invention relates to the technical field of power supply resonance, and particularly discloses a resonant power supply conversion circuit and a converter of a zero-voltage switch. The invention ensures that the switching tube of the power converter can realize zero-voltage switching within a wide input voltage range, the switching loss is low, and the efficiency of the power converter is high; the power converter can adapt to the wide range change and adjustment of the input voltage and the output voltage; the power converter is only provided with one power switch device, and the power switch device can adopt a driving mode with the ground as a reference point, so that the circuit structure is simplified; the isolation transformer of the power converter does not participate in resonance, the adaptability of the power converter to load change is improved, zero-voltage switching can be realized in the full-load range of the power converter, and the efficiency is improved.
Description
Technical Field
The invention relates to the technical field of power supply resonance, in particular to a resonant power supply conversion circuit and a resonant power supply conversion converter of a zero-voltage switch.
Background
At present, the main point of research on power conversion technology is high efficiency and high power density, so that the power converter is miniaturized, meets the energy efficiency requirement, and is convenient to match with various electrical equipment.
In a low-power converter, a switching tube is generally operated in a zero-voltage switching-on state by adopting topology circuits such as an active clamp flyback topology and the like, but the active clamp flyback topology can only realize zero-voltage switching-on, the switching tube has large switching-off current, and switching-off loss exists during high-frequency operation, so that the feasibility of further improving the working frequency on the basis of the active clamp flyback topology is not high, the working frequency of a power converter product mature in the industry can generally reach about 300KHz, and the energy efficiency can hardly meet the requirement if the frequency is further improved. In addition, the driving of the clamp switching tube in the active clamp topology circuit needs to shift the level of the clamp driving signal of the controller to match, the driving energy is provided by a bootstrap circuit, the circuit is complex, and the frequency cannot be too high.
In a power converter with medium and high power, an LLC resonant conversion topology circuit or a phase-shifted full-bridge conversion topology circuit is generally adopted, and when a conventional LLC resonant converter outputs light load, the turn-off current of a switching tube is still very large, so that the light load efficiency is not high; moreover, to ensure the high efficiency of the LLC resonant converter, the resonant inductance cannot be too large, which results in a small regulation range of the LLC resonant converter, and is not suitable for use in power converters with large regulation of input and output voltages. The conventional phase-shifted full-bridge conversion technology is a zero-voltage constant-frequency quasi-resonance technology, the zero-voltage switching condition of a switching tube is realized, namely the energy of a resonant inductor must be larger than the energy of all capacitors participating in resonance, and the energy storage of the resonant inductor is not large enough under light load, so that a lag bridge arm cannot easily meet the condition of zero-voltage switching, the light load efficiency is low, although the increase of the resonant inductor can be improved, the resonant inductor cannot be too large, the loss of the duty ratio can be caused by too large inductor, the primary current is large, the conduction loss is increased, and the efficiency is reduced; in addition, no matter the LLC resonant conversion topology circuit or the phase-shifted full-bridge conversion topology circuit, at least more than 2 switching devices are needed, and the driving of the switching tube of the upper bridge arm needs bootstrap driving or driving by adopting a driving optocoupler, so that the circuit is complex, the reliability is low and the cost is high; in addition, the isolation transformer in the LLC resonant conversion topology circuit and the phase-shifted full-bridge conversion topology circuit participates in resonance, and a change in load on the secondary side of the transformer will affect the resonance, possibly resulting in a deterioration of the zero-voltage switching condition of the switching tube and a deterioration of efficiency.
As shown in fig. 5, a resonant circuit of an isolation-type resonant power converter with zero-voltage switching is composed of a capacitor Cb, a capacitor Cc, an inductor Lb, and a transformer primary winding N1, a voltage wave at two ends of the transformer primary winding N1 is a wave which is close to a sine wave and symmetrical in positive and negative directions near a peak value and clamped by an output voltage at a middle part, and the transformer primary winding N1 participates in resonance, when a load deviates from an optimal load point, it may cause the drain voltage of the switching tube Qa not to resonate to zero to increase the turn-on loss, and therefore, the topological structure determines that the optimal switching duty ratio is about 50 percent, if the deviation is too much, zero-voltage zero-current switching can not be realized, meanwhile, the adjustment range of the input voltage and the output voltage is very small when the duty ratio cannot be changed in a large range, so that the method is not suitable for being applied to a power converter for adjusting the input voltage and the output voltage in a large range, and is only suitable for being applied to a power converter for fixing the input voltage and the output voltage.
In summary, the above conversion topology circuits of several power converters have disadvantages, and therefore, another circuit must be invented to overcome the above disadvantages.
Disclosure of Invention
The invention provides a resonant power conversion circuit and converter of a zero-voltage switch, and solves the technical problems that a conversion topological circuit of an existing power converter cannot simultaneously meet the requirements of zero-voltage switching, large-range voltage regulation, less power switching devices and large-range load change adaptation.
In order to solve the technical problems, the invention provides a resonant power conversion circuit of a zero-voltage switch, which comprises an input power positive end VIN +, an input power ground end VIN-, a resonant circuit 1, a resonant controller 2, an energy coupling and level shifting circuit 3, a zero-voltage detection circuit 4, an isolation transformer 5, a rectifying circuit 6, a PFC circuit 7, a filter circuit 8, an output positive end VO +, an output negative end VO-and an output voltage feedback signal FB;
the resonant circuit 1 comprises an input end 9, a switch control end 10, a ground end 11, a switch end voltage detection end 12 and an output end 13; the resonance controller 2 comprises a control signal input end 19, a zero voltage signal input end 20, a first signal ground end 21 and a switch driving output end 22; the zero voltage detection circuit 4 comprises a second signal ground terminal 16, a zero voltage detection input terminal 17 and a zero voltage signal output terminal 18; the isolation transformer 5 comprises a primary winding end 14, a primary winding other end 15 and a secondary winding; the rectification circuit 6 comprises a rectification input end, a rectification output positive end 24 and a rectification output negative end 23;
wherein, the input terminal 9 is electrically connected to the positive input power supply terminal VIN +, the switch control terminal 10 is electrically connected to the switch driving output terminal 22, the switch terminal voltage detecting terminal 12 is electrically connected to the zero voltage detecting input terminal 17, the ground terminal 11 and the second signal ground terminal 16, the first signal ground terminal 21, and the other end 15 of the primary winding are commonly electrically connected to the power ground terminal VIN-, the control signal input terminal 19 is electrically connected to the output voltage feedback signal FB, the zero voltage signal input terminal 20 is electrically connected to the zero voltage signal output terminal 18, the energy coupling and level shifting circuit 3 is connected in series between the output terminal 13 and one end 14 of the primary winding, the secondary winding is electrically connected to the rectifying input terminal, and the rectifying output positive terminal 24 is electrically connected to one end of the PFC circuit 7, the rectification output negative terminal 23 and one end of the filter circuit 8 are electrically connected with the output negative terminal VO-, and the other end of the PFC circuit 7 and the other end of the filter circuit 8 are electrically connected with the output positive terminal VO +.
The resonant circuit 1 is used for receiving a control signal of the resonant controller 2, and converting direct current input to the positive end VIN + of the power supply into voltage waves which are oscillated in an up-and-down constant amplitude manner according to a sine rule by taking a VIN + positive voltage point as an axis through resonance;
the resonance controller 2 is configured to receive the voltage of the output voltage feedback signal FB to adjust the switching frequency, receive a voltage signal from the zero voltage detection circuit 4 when the switching resonance reaches zero, and generate a driving signal when the voltage at the two ends of the switching tube Q1 is zero to control the resonance and the resonance operating frequency of the resonance circuit 1, so as to achieve the stabilization of the zero voltage switching and the output voltage;
the energy coupling and level shifting circuit 3 is used for injecting energy coupling of voltage waves which are output by an output end 13 of the resonant circuit 1 and oscillate up and down with equal amplitude according to a sine rule by taking a VIN + positive voltage point as an axis into the isolation transformer 5, and moving an axis point in an oscillation level to a ground level for inputting a power ground end VIN-;
the zero voltage detection circuit 4 is used for detecting the point of zero resonance of the voltage across the switching tube Q1 so as to realize zero voltage switching-on of the switching tube Q1, and is also used for eliminating the detected time delay of zero point of the voltage resonance across the switching tube Q1;
the isolation transformer 5 is used for energy isolation conversion of the primary and secondary sides and matching of voltage and impedance between the primary and secondary sides;
the rectifying circuit 6 is used for rectifying alternating current of secondary windings NS1 and NS2 of the isolation transformer 5 into continuous half-wave pulsating direct current;
the PFC circuit 7 is used for increasing the conduction angle of a rectifier tube in the rectifier circuit 6, improving the power factor, reducing the peak current of a primary winding and a secondary winding of the isolation transformer 5, and simultaneously enabling the voltage wave of the primary winding and the secondary winding to be close to a sine wave and to be clipped by the output voltage without clipping;
the filter circuit 8 is used for filtering the continuous half-wave pulsating direct current output by the rectifying circuit 6 into smooth direct current.
In the first embodiment, the resonant circuit 1 is provided with a switching tube Q1, a choke inductor L1, a resonant inductor L2, a first resonant capacitor C1, and a second resonant capacitor C2;
one end of the choke inductor L1 is the input end 9, and the other end is connected to one end of the resonant inductor L2; the other end of the resonant inductor L2 is the output end 13;
a control end (P1) of the switching tube Q1 is the switching control end 10, a switching signal input end (P2) is connected to the other end of the choke inductor L1, and a switching signal output end (P3) is the ground end 11;
the first resonant capacitor C1 is connected between the switching signal input terminal (P2) and the switching signal output terminal (P3), and the second resonant capacitor C2 is connected between the other end of the resonant inductor L2 and the switching signal output terminal (P3).
In the second embodiment, the energy coupling and level shifting circuit 3 is provided with a third capacitor C3.
In the third embodiment, the zero voltage detection circuit 4 is provided with at least a first resistor R1 and a second resistor R2;
one end of the second resistor R2 is used as the second signal ground terminal 16, the other end is connected to one end of the first resistor R1, and the other end of the first resistor R1 is used as the zero voltage detection input terminal 17; the common connection end of the first resistor R1 and the second resistor R2 is used as the zero-voltage signal output end 18.
In the fourth embodiment, the zero voltage detection circuit 4 is provided with a third resistor R3 and a fourth capacitor C4 in addition to the first resistor R1 and the second resistor R2, and is sequentially connected in series between the zero voltage detection input terminal 17 and the zero voltage signal output terminal 18.
In a fifth embodiment, the isolation transformer 5 is provided with a primary winding NP, a first secondary winding NS1, and the first secondary winding NS1 is used as the secondary winding.
In a sixth embodiment, the isolation transformer 5 is provided with a second secondary winding NS2 in addition to the first secondary winding NS1, and the second secondary winding NS2 and the first secondary winding NS1 together serve as the secondary winding.
In a seventh embodiment, in addition to the sixth embodiment, the rectifier circuit 6 is provided with a first rectifier tube D1 and a second rectifier tube D2; the first rectifier tube D1 is reversely connected between the dotted terminal of the second secondary winding NS2 and the output negative terminal VO-, the second rectifier tube D2 is reversely connected between the dotted terminal of the first secondary winding NS1 and the output negative terminal VO-, and the dotted terminal of the first secondary winding NS1 is also connected with the dotted terminal of the second secondary winding NS 2. In other embodiments, the rectifier circuit 6 may also be provided with a rectifier bridge to form bridge rectification.
In the eighth embodiment, the PFC circuit 7 is provided with a third inductor L3.
In the ninth embodiment, the filter circuit 8 is provided with a fifth capacitor C5.
The tenth embodiment combines the specific circuit designs of the above 9 embodiments. That is, the resonant circuit 1 is provided with a switching tube Q1, a choke inductor L1, a resonant inductor L2, a first resonant capacitor C1, and a second resonant capacitor C2, the energy coupling and level shift circuit 3 is provided with a third capacitor C3, the zero voltage detection circuit 4 is provided with a first resistor R1, a second resistor R2, a third resistor R3, and a fourth capacitor C4, the isolation transformer 5 is provided with a primary winding NP, a first secondary winding NS1, and a second secondary winding NS2, the rectifier circuit 6 is provided with a first rectifier tube D1 and a second rectifier tube D2, the PFC circuit 7 is provided with a third inductor L3, and the filter circuit 8 is provided with a fifth capacitor C5, and the electrical connection relationship of these components is consistent with the above embodiments.
In the eleventh embodiment, the resonance controller 2 is provided with at least a voltage controlled oscillator, a monostable pulse generator, a zero-crossing comparator, a logic circuit, and a driver.
The invention also provides a zero-voltage switching resonant power converter which comprises the resonant power conversion circuit in any one of the above embodiments.
The resonant power supply conversion circuit and converter of the zero-voltage switch provided by the invention have the following beneficial effects:
1. the switching tube of the power converter can realize zero-voltage switching within a wide input voltage range, the switching loss is low, the efficiency of the power converter is high, the switching frequency can be further improved, and the size of the power converter is reduced;
2. the power converter can adapt to the wide range change and adjustment of the input voltage and the output voltage;
3. the power converter is only provided with one power switch device, and the power switch device can adopt a driving mode taking the ground as a reference point, so that the circuit structure is simplified, the reliability of the power converter is improved, and the cost of the power converter is reduced;
4. the isolation transformer of the power converter does not participate in resonance, the adaptability of the power converter to load change is improved, zero-voltage switching can be realized in the full-load range of the power converter, and the efficiency is improved.
Drawings
Fig. 1 is a block diagram of a resonant power conversion circuit of a zero voltage switch according to an embodiment of the present invention;
FIG. 2 is a detailed circuit diagram corresponding to FIG. 1 according to an embodiment of the present invention;
FIG. 3 is a waveform diagram of the operation of FIG. 2 provided by an embodiment of the present invention;
FIG. 4 is a block diagram of the resonant controller of FIG. 2 according to an embodiment of the present invention;
fig. 5 is a topology circuit diagram of a conventional isolated resonant converter.
In FIGS. 1 to 2:
the power supply positive terminal VIN +, the power supply ground terminal VIN-, outputs a voltage feedback signal FB, outputs a positive terminal VO +, and outputs a negative terminal VO-;
the resonant circuit 1 (a switching tube Q1, a choke inductor L1, a resonant inductor L2, a first resonant capacitor C1 and a second resonant capacitor C2), an input end 9, an output end 13, a switch control end 10, a switch end voltage detection end 12 and a ground end 11;
the resonance controller 2 controls a signal input end 19, a zero voltage signal input end 20, a first signal ground end 21 and a switch driving output end 22;
the energy coupling and level shifting circuit 3 (third capacitor C3);
the zero voltage detection circuit 4 (a first resistor R1, a second resistor R2, a third resistor R3 and a fourth capacitor C4), the second signal ground terminal 16, the zero voltage detection input terminal 17 and the zero voltage signal output terminal 18;
an isolation transformer 5 (a primary winding NP, a first secondary winding NS1, a second secondary winding NS2), a primary winding one end 14, a primary winding other end 15;
a rectifying circuit 6 (a first rectifying tube D1, a second rectifying tube D2), a rectifying output positive terminal 24, and a rectifying output negative terminal 23;
the PFC circuit 7 (third inductor L3);
the filter circuit 8 (fifth capacitor C5).
In fig. 3:
the waveform shown in the first column a/V is the operating voltage waveform at the point a of the control terminal Q1 in the specific circuit diagram of the embodiment of the present invention shown in fig. 2;
the waveform shown in the second column B/V is the operating voltage waveform at the point B of the high potential terminal of the switching tube Q1 in the specific circuit diagram of the embodiment of the present invention shown in fig. 2;
the waveform shown in the third column C/a is the operating current waveform at point C of the current flowing through the switching tube Q1 in the specific circuit diagram of the embodiment of the present invention shown in fig. 2;
the waveform shown in the fourth column D/V is the operating voltage waveform at the point D in the specific circuit diagram of the embodiment of the present invention shown in fig. 2, i.e. at two ends of the second resonant capacitor C2;
the waveform shown in the fifth column E/V is the operating voltage waveform at point E in the specific circuit diagram of the embodiment of the invention shown in fig. 2, i.e. across the primary winding of the isolation transformer 5.
Detailed Description
The embodiments of the present invention will be described in detail with reference to the accompanying drawings, which are given for illustrative purposes only and are not to be construed as limiting the invention, and the embodiments and the dimensions of the components and the drawings are merely preferred embodiments, which are provided for reference and illustrative purposes only and do not limit the scope of the invention, since many changes may be made therein without departing from the spirit and scope thereof.
The module of the resonant power conversion circuit of the zero-voltage switch provided by the embodiment of the invention is shown in fig. 1, and comprises an input power positive terminal VIN +, an input power ground terminal VIN-, a resonant circuit 1, a resonant controller 2, an energy coupling and level shifting circuit 3, a zero-voltage detection circuit 4, an isolation transformer 5, a rectification circuit 6, a PFC circuit 7, a filter circuit 8, an output positive terminal VO +, an output negative terminal VO-, and an output voltage feedback signal FB;
the resonant circuit 1 comprises an input end 9, a switch control end 10, a ground end 11, a switch end voltage detection end 12 and an output end 13; the resonance controller 2 comprises a control signal input end 19, a zero voltage signal input end 20, a first signal ground end 21 and a switch driving output end 22; the zero voltage detection circuit 4 comprises a second signal ground terminal 16, a zero voltage detection input terminal 17 and a zero voltage signal output terminal 18; the isolation transformer 5 comprises a primary winding end 14, a primary winding other end 15 and a secondary winding; the rectification circuit 6 comprises a rectification input end, a rectification output positive end 24 and a rectification output negative end 23;
wherein, the input terminal 9 is electrically connected to the positive input power supply terminal VIN +, the switch control terminal 10 is electrically connected to the switch driving output terminal 22, the switch terminal voltage detecting terminal 12 is electrically connected to the zero voltage detecting input terminal 17, the ground terminal 11 and the second signal ground terminal 16, the first signal ground terminal 21, and the other end 15 of the primary winding are commonly electrically connected to the power ground terminal VIN-, the control signal input terminal 19 is electrically connected to the output voltage feedback signal FB, the zero voltage signal input terminal 20 is electrically connected to the zero voltage signal output terminal 18, the energy coupling and level shifting circuit 3 is connected in series between the output terminal 13 and one end 14 of the primary winding, the secondary winding is electrically connected to the rectifying input terminal, and the rectifying output positive terminal 24 is electrically connected to one end of the PFC circuit 7, the rectification output negative terminal 23 and one end of the filter circuit 8 are electrically connected with the output negative terminal VO-, and the other end of the PFC circuit 7 and the other end of the filter circuit 8 are electrically connected with the output positive terminal VO +.
The resonant circuit 1 is used for receiving a control signal of the resonant controller 2, and converting direct current input to the positive end VIN + of the power supply into voltage waves which are oscillated in an up-and-down constant amplitude manner according to a sine rule by taking a VIN + positive voltage point as an axis through resonance;
the resonance controller 2 is configured to receive the voltage of the output voltage feedback signal FB to adjust the switching frequency, receive a voltage signal from the zero voltage detection circuit 4 when the switching resonance reaches zero, and generate a driving signal when the voltage at the two ends of the switching tube Q1 is zero to control the resonance and the resonance operating frequency of the resonance circuit 1, so as to achieve the stabilization of the zero voltage switching and the output voltage;
the energy coupling and level shifting circuit 3 is used for injecting energy coupling of voltage waves which are output by an output end 13 of the resonant circuit 1 and oscillate up and down with equal amplitude according to a sine rule by taking a VIN + positive voltage point as an axis into the isolation transformer 5, and moving an axis point in an oscillation level to a ground level for inputting a power ground end VIN-;
the zero voltage detection circuit 4 is used for detecting the point of zero resonance of the voltage across the switching tube Q1 so as to realize zero voltage switching-on of the switching tube Q1, and is also used for eliminating the detected time delay of zero point of the voltage resonance across the switching tube Q1;
the isolation transformer 5 is used for energy isolation conversion of the primary and secondary sides and matching of voltage and impedance between the primary and secondary sides;
the rectifying circuit 6 is used for rectifying alternating current of secondary windings NS1 and NS2 of the isolation transformer 5 into continuous half-wave pulsating direct current;
the PFC circuit 7 is used for increasing the conduction angle of a rectifier tube in the rectifier circuit 6, improving the power factor, reducing the peak current of a primary winding and a secondary winding of the isolation transformer 5, and simultaneously enabling the voltage wave of the primary winding and the secondary winding to be close to a sine wave and to be clipped by the output voltage without clipping;
the filter circuit 8 is used for filtering the continuous half-wave pulsating direct current output by the rectifying circuit 6 into smooth direct current.
As shown in fig. 2, the present example will explain a tenth embodiment in more detail. In this embodiment, the resonant circuit 1 is provided with a switching tube Q1, a choke inductor L1, a resonant inductor L2, a first resonant capacitor C1, and a second resonant capacitor C2, one end of the choke inductor L1 is the input end 9, and the other end is connected to one end of the resonant inductor L2; the other end of the resonant inductor L2 is the output end 13; a control end (P1) of the switching tube Q1 is the switching control end 10, a switching signal input end (P2) is connected to the other end of the choke inductor L1, and a switching signal output end (P3) is the ground end 11; the first resonant capacitor C1 is connected between the switching signal input terminal (P2) and the switching signal output terminal (P3), and the second resonant capacitor C2 is connected between the other end of the resonant inductor L2 and the switching signal output terminal (P3). In this embodiment, the switching transistor Q1 is a MOS transistor, and the control terminal (P1), the switching signal input terminal (P2), and the switching signal output terminal (P3) of the switching transistor Q1 are a gate, a drain, and a source of the MOS transistor, respectively. In other embodiments, the switching tube Q1 may be a triode, or may be other switching elements.
The energy coupling and level shifting circuit 3 is provided with a third capacitor C3.
The zero voltage detection circuit 4 is provided with a first resistor R1, a second resistor R2, a third resistor R3 and a fourth capacitor C4, one end of the second resistor R2 is used as the second signal ground terminal 16, the other end of the second resistor R2 is connected to one end of the first resistor R1, and the other end of the first resistor R1 is used as the zero voltage detection input terminal 17; the common connection end of the first resistor R1 and the second resistor R2 is used as the zero voltage signal output end 18, and the third resistor R3 and the fourth capacitor C4 are sequentially connected in series between the zero voltage detection input end 17 and the zero voltage signal output end 18.
The isolation transformer 5 is provided with a primary winding NP, a first secondary winding NS1, and a second secondary winding NS2, and the second secondary winding NS2 and the first secondary winding NS1 together serve as the secondary winding.
The rectifying circuit 6 is provided with a first rectifying tube D1 and a second rectifying tube D2, the first rectifying tube D1 is reversely connected between the dotted terminal of the second secondary winding NS2 and the output negative terminal VO-, the second rectifying tube D2 is reversely connected between the dotted terminal of the first secondary winding NS1 and the output negative terminal VO-, and the dotted terminal of the first secondary winding NS1 is also connected with the dotted terminal of the second secondary winding NS 2.
The PFC circuit 7 is provided with a third inductor L3, and the filter circuit 8 is provided with a fifth capacitor C5.
The resonance controller 2 is at least provided with a voltage controlled oscillator, a monostable pulse generator, a zero-crossing comparator, a logic circuit and a driver, as shown in fig. 4. Because the resonant controller 2 is a mature technology, the present embodiment does not describe a specific circuit structure thereof, and based on the "to-be-completed" of the present embodiment, the resonant controller 2 is configured to receive the voltage of the output voltage feedback signal FB to adjust the switching frequency, and receive the voltage signal of the zero voltage detection circuit 4 when the switching resonance reaches zero to generate the driving signal of the switching tube Q1 when the voltage at the two ends is zero to control the resonance and the resonance operating frequency of the resonant circuit 1, so as to implement the functions of zero voltage switching and stabilizing the output voltage, "which is not difficult to implement.
The embodiment of the invention provides a resonant power conversion circuit and a converter of a zero-voltage switch, referring to fig. 2 and 3, the working principle is as follows:
the choke inductor L1 in the resonant circuit 1 functions as a choke while suppressing the influence of the high frequency current on the input power, and when the switching tube Q1 in the resonant circuit 1 is in a conducting state under the control of the resonant controller 2, the operating voltage waveform at the control terminal a point of the switching tube Q1 is as shown in the first column a/V in fig. 3. Since the resonant inductor L2 and the resonant capacitor C2 in the resonant circuit 1, and the capacitor C3 and the isolation transformer 5 of the energy coupling and level shifting circuit have stored energy before the switch Q1 is turned on, the capacitor C3 and the primary winding NP of the isolation transformer 5 of the energy coupling and level shifting circuit can be equivalent to a capacitor having a capacity much larger than that of the resonant capacitors C1 and C2, which are connected in series to form a relatively high impedance, the series circuit of the capacitor C3 and the primary winding NP of the isolation transformer 5 is weak capacitive, the equivalent capacitor after the capacitor is connected in parallel with the resonant capacitor C2 is set as a resonant capacitor CY, the current flowing through the choke inductor L1 plus the current flowing through the resonant inductor L2 and the resonant capacitor CY all flows through the switch tube Q1, the point C in fig. 2 is that the current flowing through the switch tube Q1 is as shown in the third column C/a in fig. 3, the current gradually rises from negative to positive, and at the same time, because the output capacitors of the resonant capacitor C1 and the switch tube Q1 are connected, when the current drops relatively small, because the voltage of the resonant capacitor CX cannot change suddenly, the voltage on the resonant capacitor CX rises slowly from zero according to a sine rule, and the working voltage waveform of a high-potential end B point of the switching tube Q1, namely the working voltage waveform of two ends of the resonant capacitor CX is as the waveform shown in a second column B/V in fig. 3, so that the voltages of the two ends of the switching tube Q1 are approximate to zero and are zero voltage switch, and the turn-off loss is greatly reduced;
during the turn-off period of the switching tube Q1, the resonance capacitor CX resonance inductor L2 and the resonance capacitor CY form a closed resonance loop to continue to resonate according to a sine rule, meanwhile, the choke inductor L1 supplements energy to the resonance loop, when the voltage of the resonance capacitor CX resonates to zero, the current flowing through the output capacitor of the switching tube Q1 is negative, the parasitic diode in the switching tube Q1 is in a conducting state, at the moment, the zero voltage detection circuit 4 detects the zero crossing point and inputs the zero crossing point into the resonance controller 2, then the resonance controller 2 outputs a high level to enable the switching tube Q1 to be switched on, and the switching tube Q1 realizes zero voltage switching on and reduces the switching loss.
The time for the resonant capacitance CX to resonate from zero to the highest voltage to zero is π SQRT (L2 CX// CY). Because the resonant capacitor CX resonant inductor L2 and the resonant capacitor CY form a closed resonant circuit, both ends of the resonant capacitor C2 are approximately sine waves, and the waveform of the test point D of the voltage waveform of both ends of the resonant capacitor C2 is shown as the waveform in the fourth column D/V in fig. 3. The period of the approximate sine wave is approximately pi × SQRT (L2 × CX// CY) + Ton, assuming that the on time of the switching tube Q1 is Ton. The approximate sine wave is a voltage wave oscillating vertically in a constant amplitude mode with a VIN + positive voltage point as an axis, the level of the central axis is shifted to a VIN-ground potential point through C3, energy is coupled to a primary winding NP of an isolation transformer 5, the waveform of a test point E point of the voltage waveform at two ends of the primary winding NP of the isolation transformer 5 is shown as the waveform shown in a fifth column E/V in figure 3, the isolated and converted approximate sine wave alternating current voltage output by secondary windings NS1 and NS2 of the isolation transformer 5 is rectified into continuous half-wave pulsating direct current through a full-wave rectifying circuit formed by a rectifying tube D1 and a rectifying tube D2 of a rectifying circuit 6, and the continuous half-wave pulsating direct current voltage is filtered through an inductor L3 of a PFC circuit 7 and a capacitor C5 of a filtering circuit 8 to. When the output direct-current voltage is higher than the set value, the difference value of the output direct-current voltage and the set value is amplified and then is input to an output voltage feedback signal FB through isolation, the resonance controller 2 receives the feedback signal and processes the feedback signal, so that the output high-level time of the resonance controller 2 is shortened, the on-time Ton of the switch tube Q1 is shortened, the off-time of the switch tube Q1 is approximate to pi multiplied by SQRT (L2 multiplied by CX// CY) and is basically unchanged, therefore, the switching period of the switch tube Q1 is shortened, namely the switching frequency is increased, and the voltage at two ends of the resonance capacitor C2 is reduced, the voltage at two ends of a primary winding of the isolation transformer 5 is also reduced, and the output voltage is also reduced as a closed resonance loop formed by the resonance capacitor C1 resonance inductor L2 and the resonance capacitor C2 is inductive; when the output dc voltage is lower than the set value, the on-time Ton of the switching tube Q1 is longer, the switching period of the switching tube Q1 is longer, that is, the switching frequency is lower, the voltage across the resonant capacitor C2 is increased, the output voltage is also increased, and the output voltage is stabilized near the set value.
On the whole, the resonant power conversion circuit and converter of the zero-voltage switch provided by the embodiment of the invention have the following beneficial effects:
1. the switching tube of the power converter can realize zero-voltage switching within a wide input voltage range, the switching loss is low, the efficiency of the power converter is high, the switching frequency can be further improved, and the size of the power converter is reduced;
2. the power converter can adapt to the wide range change and adjustment of the input voltage and the output voltage;
3. the power converter is only provided with one power switch device, and the power switch device can adopt a driving mode taking the ground as a reference point, so that the circuit structure is simplified, the reliability of the power converter is improved, and the cost of the power converter is reduced;
4. the isolation transformer of the power converter does not participate in resonance, the adaptability of the power converter to load change is improved, zero-voltage switching can be realized in the full-load range of the power converter, and the efficiency is improved.
The above embodiments are preferred embodiments of the present invention, but the present invention is not limited to the above embodiments, and any other changes, modifications, substitutions, combinations, and simplifications which do not depart from the spirit and principle of the present invention should be construed as equivalents thereof, and all such changes, modifications, substitutions, combinations, and simplifications are intended to be included in the scope of the present invention.
Claims (10)
1. A resonant power conversion circuit of a zero-voltage switch is characterized by comprising an input power positive terminal (VIN +), an input power ground terminal (VIN-), a resonant circuit (1), a resonant controller (2), an energy coupling and level shifting circuit (3), a zero-voltage detection circuit (4), an isolation transformer (5), a rectifying circuit (6), a PFC circuit (7), a filter circuit (8), an output positive terminal (VO +), an output negative terminal (VO-) and an output voltage feedback signal (FB);
the resonance circuit (1) comprises an input end (9), a switch control end (10), a ground end (11), a switch end voltage detection end (12) and an output end (13); the resonance controller (2) comprises a control signal input end (19), a zero voltage signal input end (20), a first signal ground end (21) and a switch driving output end (22); the zero voltage detection circuit (4) comprises a second signal ground terminal (16), a zero voltage detection input terminal (17) and a zero voltage signal output terminal (18); the isolation transformer (5) comprises a primary winding end (14), a primary winding other end (15) and a secondary winding; the rectification circuit (6) comprises a rectification input end, a rectification output positive end (24) and a rectification output negative end (23);
wherein the input terminal (9) is electrically connected to the positive input power terminal (VIN +), the switch control terminal (10) is electrically connected to the switch driving output terminal (22), the switch terminal voltage detection terminal (12) is electrically connected to the zero voltage detection input terminal (17), the ground terminal (11) and the second signal ground terminal (16), the first signal ground terminal (21), and the other end (15) of the primary winding are commonly electrically connected to the power ground terminal (VIN-), the control signal input terminal (19) is electrically connected to the output voltage feedback signal (FB), the zero voltage signal input terminal (20) is electrically connected to the zero voltage signal output terminal (18), the energy coupling and level shift circuit (3) is connected in series between the output terminal (13) and one end (14) of the primary winding, and the secondary winding is electrically connected to the rectification input terminal, the rectification output positive end (24) is electrically connected with one end of the PFC circuit (7), the rectification output negative end (23) and one end of the filter circuit (8) are electrically connected with the output negative end (VO-), and the other end of the PFC circuit (7) and the other end of the filter circuit (8) are electrically connected with the output positive end (VO +).
2. A zero-voltage switched resonant power conversion circuit as recited in claim 1, wherein: the resonant circuit (1) is provided with a switching tube (Q1), a choke inductor (L1), a resonant inductor (L2), a first resonant capacitor (C1) and a second resonant capacitor (C2);
one end of the choke inductor (L1) is the input end (9), and the other end of the choke inductor is connected with one end of the resonance inductor (L2); the other end of the resonant inductor (L2) is the output end (13);
the control end (P1) of the switch tube (Q1) is the switch control end (10), the switch signal input end (P2) is connected with the other end of the choke inductor (L1), and the switch signal output end (P3) is the ground end (11);
the first resonant capacitor (C1) is connected between the switching signal input terminal (P2) and the switching signal output terminal (P3), and the second resonant capacitor (C2) is connected between the other end of the resonant inductor (L2) and the switching signal output terminal (P3).
3. A zero-voltage switched resonant power conversion circuit as recited in claim 1, wherein: the energy coupling and level shifting circuit (3) is provided with a third capacitance (C3).
4. A zero-voltage switched resonant power conversion circuit as recited in claim 1, wherein: the zero voltage detection circuit (4) is at least provided with a first resistor (R1) and a second resistor (R2);
one end of the second resistor (R2) is used as the second signal ground terminal (16), the other end of the second resistor (R2) is connected with one end of the first resistor (R1), and the other end of the first resistor (R1) is used as the zero voltage detection input terminal (17); the common connection end of the first resistor (R1) and the second resistor (R2) is used as the zero-voltage signal output end (18).
5. The zero-voltage-switching resonant power conversion circuit of claim 4, wherein: the zero voltage detection circuit (4) is also provided with a third resistor (R3) and a fourth capacitor (C4) which are sequentially connected in series between the zero voltage detection input end (17) and the zero voltage signal output end (18).
6. A zero-voltage switched resonant power conversion circuit as recited in claim 1, wherein: the isolation transformer (5) is provided with a primary winding NP, a first secondary winding (NS1), the first secondary winding (NS1) being the secondary winding.
7. A zero-voltage-switched resonant power conversion circuit as recited in claim 6, wherein: the isolation transformer (5) is further provided with a second secondary winding (NS2), the second secondary winding (NS2) and the first secondary winding (NS1) jointly serve as the secondary winding.
8. A zero-voltage-switched resonant power conversion circuit as recited in claim 7, wherein: the rectifying circuit (6) is provided with a first rectifying tube (D1) and a second rectifying tube (D2); the first rectifier tube (D1) is reversely connected between the homonymous terminal of the second secondary winding (NS2) and the output negative terminal (VO-), the second rectifier tube (D2) is reversely connected between the heteronymous terminal of the first secondary winding (NS1) and the output negative terminal (VO-), and the homonymous terminal of the first secondary winding (NS1) is also connected with the heteronymous terminal of the second secondary winding (NS 2).
9. A zero-voltage switched resonant power conversion circuit as recited in claim 1, wherein: the PFC circuit (7) is provided with a third inductor (L3); the filter circuit (8) is provided with a fifth capacitor (C5).
10. A zero-voltage switching resonant power converter, characterized by: comprising a resonant power converter circuit according to any of claims 1 to 9.
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Cited By (1)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN114079385A (en) * | 2021-11-23 | 2022-02-22 | 吕真 | Power supply circuit based on synchronous driving LLC resonant circuit series-parallel conversion |
Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20100067259A1 (en) * | 2008-09-17 | 2010-03-18 | Delta Electronics, Inc. | Forward-flyback converter with active-clamp circuit |
| CN103312171A (en) * | 2013-06-15 | 2013-09-18 | 浙江大学 | Isolated soft switching two-diode forward resonant DC / DC (direct-current/direct-current) circuit |
| CN103887976A (en) * | 2014-03-25 | 2014-06-25 | 浙江大学 | Current source input type resonance soft switching DC/DC converter |
| CN107086789A (en) * | 2017-04-27 | 2017-08-22 | 天宝电子（惠州）有限公司 | A kind of switching power converters of secondary control quasi-resonance |
| CN211266770U (en) * | 2019-12-18 | 2020-08-14 | 天宝电子（惠州）有限公司 | Zero-voltage switch's resonant power supply converting circuit and converter |
-
2019
- 2019-12-18 CN CN201911309642.9A patent/CN110943624B/en active Active
Patent Citations (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US20100067259A1 (en) * | 2008-09-17 | 2010-03-18 | Delta Electronics, Inc. | Forward-flyback converter with active-clamp circuit |
| CN103312171A (en) * | 2013-06-15 | 2013-09-18 | 浙江大学 | Isolated soft switching two-diode forward resonant DC / DC (direct-current/direct-current) circuit |
| CN103887976A (en) * | 2014-03-25 | 2014-06-25 | 浙江大学 | Current source input type resonance soft switching DC/DC converter |
| CN107086789A (en) * | 2017-04-27 | 2017-08-22 | 天宝电子（惠州）有限公司 | A kind of switching power converters of secondary control quasi-resonance |
| CN211266770U (en) * | 2019-12-18 | 2020-08-14 | 天宝电子（惠州）有限公司 | Zero-voltage switch's resonant power supply converting circuit and converter |
Cited By (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN114079385A (en) * | 2021-11-23 | 2022-02-22 | 吕真 | Power supply circuit based on synchronous driving LLC resonant circuit series-parallel conversion |
| CN114079385B (en) * | 2021-11-23 | 2023-07-28 | 吕真 | LLC resonant circuit series-parallel conversion power supply circuit based on synchronous drive |
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