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CN117060707B - Single-stage single-phase bridgeless Zeta type PFC converter - Google Patents

Single-stage single-phase bridgeless Zeta type PFC converter Download PDF

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Publication number
CN117060707B
CN117060707B CN202311056912.6A CN202311056912A CN117060707B CN 117060707 B CN117060707 B CN 117060707B CN 202311056912 A CN202311056912 A CN 202311056912A CN 117060707 B CN117060707 B CN 117060707B
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inductor
inductance
filter capacitor
bidirectional switch
input
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CN117060707A (en
Inventor
李浩昱
丁明远
叶一舟
王鹏飞
刘智雄
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Harbin Institute of Technology
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Harbin Institute of Technology
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Classifications

    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/42—Circuits or arrangements for compensating for or adjusting power factor in converters or inverters
    • H02M1/4208—Arrangements for improving power factor of AC input
    • H02M1/4225—Arrangements for improving power factor of AC input using a non-isolated boost converter
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/08—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters
    • H02M1/088—Circuits specially adapted for the generation of control voltages for semiconductor devices incorporated in static converters for the simultaneous control of series or parallel connected semiconductor devices
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M1/00—Details of apparatus for conversion
    • H02M1/38—Means for preventing simultaneous conduction of switches
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M3/00—Conversion of DC power input into DC power output
    • H02M3/02—Conversion of DC power input into DC power output without intermediate conversion into AC
    • H02M3/04—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters
    • H02M3/10—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M3/145—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M3/155—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • H02M3/156—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators
    • H02M3/158—Conversion of DC power input into DC power output without intermediate conversion into AC by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only with automatic control of output voltage or current, e.g. switching regulators including plural semiconductor devices as final control devices for a single load
    • H—ELECTRICITY
    • H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
    • H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
    • H02M7/00—Conversion of AC power input into DC power output; Conversion of DC power input into AC power output
    • H02M7/02—Conversion of AC power input into DC power output without possibility of reversal
    • H02M7/04—Conversion of AC power input into DC power output without possibility of reversal by static converters
    • H02M7/12—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
    • H02M7/21—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
    • H02M7/217—Conversion of AC power input into DC power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
    • Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
    • Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
    • Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
    • Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
    • Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes

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  • Engineering & Computer Science (AREA)
  • Power Engineering (AREA)
  • Rectifiers (AREA)

Abstract

The single-phase bridgeless Zeta type PFC converter solves the problems of low efficiency and low power density of the traditional Zeta type PFC converter, and belongs to the topology field of single-phase bridgeless PFC converters. The invention comprises an input filter inductance L f, an input filter capacitance C f, an energy storage capacitance C, an inductance L 1, an inductance L 2, an NMOS switch tube S 5, an NMOS switch tube S 6, an output filter capacitance C dc1, an output filter capacitance C dc2, a bidirectional switch No. 1 and a bidirectional switch No. 2; when the direction of the output current is unchanged, an uncontrolled diode can be used for replacing a switching tube at the output side; the invention can design the inductance of the two inductors to be the same smaller value, the volume of the converter is obviously reduced, the power density is effectively improved, and the inductance of the output side inductor is larger than that of the input side inductor, but compared with the input filter inductor with larger PFC converter, the inductance of the output side inductor is still smaller.

Description

Single-stage single-phase bridgeless Zeta type PFC converter
Technical Field
The invention relates to a single-stage single-phase bridgeless Zeta type PFC converter, and belongs to the topology field of single-stage single-phase bridgeless PFC converters.
Background
Compared with other DC/DC circuits, the Zeta circuit has the advantages of buck-boost conversion, better dynamic response, capability of limiting surge current and preventing overload, and the Zeta PFC converter derived from the buck-boost conversion has the characteristic of automatically realizing power factor correction in a discontinuous operation mode (DCM), so that the Zeta PFC converter is applied to application occasions such as electric automobile (EVs) battery chargers and LED drivers which need to have the capability of preventing overcurrent or short circuit.
The related topologies of the Zeta type PFC converter are fewer, and only two types of typical rectifying bridges and double Zeta unit bridge-free types exist at present. The typical rectifier bridge type Zeta type PFC converter always has two conducting diodes at the AC input end, and the system efficiency is seriously reduced under the condition of low voltage and high current; the double-Zeta unit bridge-free Zeta type PFC converter uses two independent Zeta circuits to respectively process the positive half period and the negative half period of alternating input voltage, the circuit structure is more complicated, the number of used components is more, and the system power density is lower.
Disclosure of Invention
Aiming at the problems of low efficiency and low power density of the traditional Zeta type PFC converter, the invention provides a single-stage single-phase bridgeless Zeta type PFC converter.
The invention discloses a single-stage single-phase bridgeless Zeta type PFC converter, which comprises an input filter inductor L f, an input filter capacitor C f, an energy storage capacitor C, an inductor L 1, an inductor L 2, an NMOS switching tube S 5, an NMOS switching tube S 6, an output filter capacitor C dc1, an output filter capacitor C dc2, a No. 1 bidirectional switch and a No. 2 bidirectional switch;
The positive electrode of the input power supply is connected with one end of an input filter inductor L f, the other end of the input filter inductor L f is simultaneously connected with one end of a No. 1 bidirectional switch and one end of an input filter capacitor C f, the other end of the No. 1 bidirectional switch is simultaneously connected with one end of an inductor L 1 and one end of an energy storage capacitor C, the other end of the energy storage capacitor C, one end of a No. 2 bidirectional switch and one end of an inductor L 2 are simultaneously connected, and the other end of the inductor L 2 is simultaneously connected with the source electrode of an NMOS switch tube S 5 and the drain electrode of an NMOS switch tube S 6;
The negative electrode of the input power supply, the other end of the input filter capacitor C f, the other end of the inductor L 1, the other end of the No. 2 bidirectional switch, the negative electrode of the output filter capacitor C dc1 and the positive electrode of the output filter capacitor C dc2 are simultaneously connected;
The drain of the NMOS switching tube S 5 is connected to the positive electrode of the output filter capacitor C dc1, and the source of the NMOS switching tube S 6 is connected to the negative electrode of the output filter capacitor C dc2.
Preferably, the inductance values of the inductance L 1 and the inductance L 2 are equal, and are both L:
Where P o is the output power, V ac_rms is the ac voltage effective value, d is the duty cycle, and T S represents the switching period of the bi-directional switch.
Preferably, the maximum value d max of the duty cycle d is:
Where V dc represents the load voltage.
The invention also provides a single-stage single-phase bridgeless Zeta type PFC converter, which comprises an input filter inductor L f, an input filter capacitor C f, an energy storage capacitor C, an inductor L 1, an inductor L 2, a diode D 1, a diode D 2, an output filter capacitor C dc1, an output filter capacitor C dc2, a No. 1 bidirectional switch and a No. 2 bidirectional switch;
The positive electrode of the input power supply is connected with one end of an input filter inductor L f, the other end of the input filter inductor L f is simultaneously connected with one end of a No. 1 bidirectional switch and one end of an input filter capacitor C f, the other end of the No. 1 bidirectional switch is simultaneously connected with one end of an inductor L 1 and one end of an energy storage capacitor C, the other end of the energy storage capacitor C, one end of a No. 2 bidirectional switch and one end of an inductor L 2 are simultaneously connected, and the other end of the inductor L 2 is simultaneously connected with the anode of a diode D 1 and the cathode of a diode D 2;
The negative electrode of the input power supply, the other end of the input filter capacitor C f, the other end of the inductor L 1, the other end of the No. 2 bidirectional switch, the negative electrode of the output filter capacitor C dc1 and the positive electrode of the output filter capacitor C dc2 are simultaneously connected;
The cathode of the diode D 1 is connected to the anode of the output filter capacitor C dc1, and the anode of the diode D 2 is connected to the cathode of the output filter capacitor C dc2.
Preferably, the value of inductance L 2 is:
Where P o is the output power, V ac_rms is the ac voltage effective value, d is the duty cycle, and T S represents the switching period of the bi-directional switch.
Preferably, the parallel inductance value L 12 of the inductance L 1 and the inductance L 2 is:
the value of inductance L 1 is determined from the value of inductance L 2 and the parallel inductance value L 12.
Preferably, the value of inductance L 1 is:
Preferably, the maximum value d max of the duty cycle d is:
Where V dc represents the load voltage.
The rectifier bridge structure is completely removed, and only one group of circuit elements of the Zeta circuit is used, so that the rectifier bridge structure is simple in circuit structure and control. The converter also has the following advantages: when the output current direction is unchanged, an uncontrolled diode can be used for replacing a fully-controlled switching tube at the output side, and the control link is further simplified; the circuit can flexibly design the inductance of the two inductors according to different continuous requirements on high power density or output current direction, when the high power density is used as the requirement, the inductance of the two inductors of the PFC converter can be designed to be the same smaller value, the converter volume is obviously reduced, the power density is effectively improved, when the output current direction is required to be kept unchanged within positive and negative half cycles of alternating current input voltage, the inductance of the output side inductor is larger than the input side inductor, but compared with the larger input filter inductors of other PFC converters, the inductance of the output side inductor is still smaller.
Drawings
Fig. 1 is a circuit diagram of a single-stage single-phase bridgeless Zeta-type PFC converter using a switching tube at an output side;
Fig. 2 is a circuit diagram of a single-stage single-phase bridgeless Zeta-type PFC converter using a diode at the output side;
fig. 3 is a waveform diagram of the driving signal V GS1～VGS6, the inductor L 1、L2 current i L1、iL2, and the switching tube S 1、S3 current i S1、iS3 in one switching cycle of the positive half cycle of the ac voltage;
FIG. 4 is a diagram of three modes of the circuit in one switching cycle of the positive half cycle of the AC voltage, wherein FIG. 4 (a) is mode I, FIG. 4 (b) is mode II, and FIG. 4 (c) is mode III;
fig. 5 is a waveform diagram of the driving signal V GS1～VGS6, the inductor L 1、L2 current i L1、iL2, and the switching tube S 2、S4 current i S2、iS4 in one switching cycle of the negative half cycle of the ac voltage;
FIG. 6 is a diagram of three modes of the circuit in one switching cycle of the negative half cycle of the AC voltage, wherein FIG. 6 (a) is mode IV, FIG. 6 (b) is mode V, and FIG. 6 (c) is mode VI;
Fig. 7 is a waveform diagram of the driving signal V GS1～VGS6 in one switching cycle of the positive half cycle of the ac voltage, the current i L1、iL2 of the inductor L 1、L2 and the current i S1、iS3 of the switching tube S 1、S3 when the diode is used at the output side;
FIG. 8 is a diagram showing three modes of the circuit in one switching cycle of the positive half cycle of the AC voltage when the diode is used on the output side, wherein FIG. 8 (a) shows mode I, FIG. 8 (b) shows mode II, and FIG. 8 (c) shows mode III;
FIG. 9 is a waveform diagram of the driving signal V GS1～VGS6, the inductor L 1、L2 current i L1、iL2 and the switching tube S 2、S4 current i S2、iS4 in one switching cycle of the negative half cycle of the AC voltage when the diode is used at the output side;
FIG. 10 is a diagram showing three modes of the circuit in one switching cycle of the negative half cycle of the AC voltage in the case of using the diode on the output side, wherein FIG. 10 (a) shows mode IV, FIG. 10 (b) shows mode V, and FIG. 10 (c) shows mode VI;
Fig. 11 is a waveform diagram of input voltage and current at 100V/50Hz ac input and 100V/500W output, wherein fig. 11 (a) is a waveform diagram of input voltage and current at inductance L 1＝27μH、L2 =24 μh, and fig. 11 (b) is a waveform diagram of input voltage and current at inductance L 1＝13.34μH、L2 =200 μh;
Fig. 12 is a current waveform diagram of an inductor L 2 at an ac input of 100V/50Hz and an output of 100V/500W, wherein fig. 12 (a) is a current waveform diagram of an inductor L 2 at an inductor L 1＝27μH、L2 =24 μh, and fig. 12 (b) is a current waveform diagram of an inductor L 2 at an inductor L 1＝13.34μH、L2 =200 μh.
Detailed Description
The following description of the embodiments of the present invention will be made clearly and completely with reference to the accompanying drawings, in which it is apparent that the embodiments described are only some embodiments of the present invention, but not all embodiments. All other embodiments, which can be made by those skilled in the art based on the embodiments of the invention without making any inventive effort, are intended to be within the scope of the invention.
It should be noted that, without conflict, the embodiments of the present invention and features of the embodiments may be combined with each other.
The invention is further described below with reference to the drawings and specific examples, which are not intended to be limiting.
According to different requirements on high power density or continuous output current direction, the output side of the proposed Zeta type bridgeless PFC converter is divided into a full-control switching tube and an uncontrolled diode.
Before analyzing the circuit operating principle, the following assumptions are made: (1) the circuit operates in Discontinuous Conduction Mode (DCM);
(2) Neglecting the influence of parasitic parameters, conduction voltage drop and line parameters of the used components;
(3) The capacitance of the output filter capacitor C dc1、Cdc2 is equal and large enough, and the capacitance partial pressure is equal, namely v Cdc1＝vCdc2＝Vdc/2;
(4) The switching frequency f S is far higher than the power frequency, and the input voltage and the energy storage capacitor voltage in the switching period T S are all regarded as constant values.
Example 1: the Zeta-type bridgeless PFC converter with the fully-controlled switching tube at the output side is shown in fig. 1, and comprises an input filtering link (input filtering inductance L f, input filtering capacitance C f), inductance L 1、L2, energy storage capacitance C, two output filtering capacitances C dc1、Cdc2, two bidirectional switches (two groups of anti-series switching tubes: a first group S 1、S2 and a second group S 3、S4) and fully-controlled switching tubes (NMOS switching tubes S 5 and S 6). Wherein the bi-directional switch is capable of bi-directional current flow. The inductance of the inductance L 1 is equal to the inductance L 2, i.e., L 1＝L2 =l.
As shown in fig. 1, the positive pole of the input power supply is connected with one end of an input filter inductor L f, the other end of the input filter inductor L f is simultaneously connected with one end of a No. 1 bidirectional switch and one end of an input filter capacitor C f, the other end of the No. 1 bidirectional switch is simultaneously connected with one end of an inductor L 1 and one end of an energy storage capacitor C, the other end of the energy storage capacitor C, one end of a No. 2 bidirectional switch and one end of an inductor L 2 are simultaneously connected, and the other end of the inductor L 2 is simultaneously connected with the source electrode of an NMOS switch tube S 5 and the drain electrode of an NMOS switch tube S 6; the negative electrode of the input power supply, the other end of the input filter capacitor C f, the other end of the inductor L 1, the other end of the No. 2 bidirectional switch, the negative electrode of the output filter capacitor C dc1 and the positive electrode of the output filter capacitor C dc2 are simultaneously connected; the drain of the NMOS switching tube S 5 is connected to the positive electrode of the output filter capacitor C dc1, and the source of the NMOS switching tube S 6 is connected to the negative electrode of the output filter capacitor C dc2.
In the positive half cycle and the negative half cycle of the alternating-current input voltage, the Zeta type bridgeless PFC converter has six different working modes according to the switching conditions of two bidirectional switches. The main current waveform of the circuit in one switching period of the positive half cycle of the input voltage is shown in fig. 3, and the corresponding circuit mode diagram is shown in fig. 4; the main current waveform of the circuit in one switching cycle of the negative half cycle of the input voltage is shown in fig. 5, and the corresponding circuit mode diagram is shown in fig. 6.
Modality I: the switching tubes S 1 and S 2 of the bidirectional switch of the stage 1 are on, the switching tubes S 3 and S 4 of the bidirectional switch of the stage 2 are off, and the working condition of the circuit is shown in fig. 4 (a). The current of the inductors L 1 and L 2 increases linearly, and the current rising rule of the inductors L 1 and L 2 is identical because the inductance of the inductors L 1 and L 2 is equal and the voltages at the two ends are equal.
Modality II: the switching tubes S 1 and S 2 of the bidirectional switch of the stage 1 are turned off, the switching tubes S 3 and S 4 of the bidirectional switch of the stage 2 are turned on, and the working condition of the circuit is shown in fig. 4 (b). The alternating current power supply freewheels through a filter loop, the inductors L 1 and L 2 discharge to the energy storage capacitor C and the load respectively through the switching tubes S 3 and S 4 of the bidirectional switch, and the currents of the inductors L 1 and L 2 start to linearly decrease from the peak value i L_max. Since the inductances of the inductances L 1 and L 2 are equal and the voltages at the two ends are still equal, the current drop rules of the inductances L 1 and L 2 are exactly the same.
Modality III: the switching tubes S 1 and S 2 of the bidirectional switch of the stage 1 are turned off, the switching tubes S 3 and S 4 of the bidirectional switch of the stage 2 are turned off, and the working condition of the circuit is shown in fig. 4 (c). The alternating current power supply continuously flows through the filtering loop, and the change rule of the inductance L 1 and the change rule of the inductance L 2 are identical, so that the current of the two inductances in the stage is continuously 0, and the load is supplied by the two output filtering capacitors.
Modality IV: the switching tubes S 1 and S 2 of the bidirectional switch of the stage1 are on, the switching tubes S 3 and S 4 of the bidirectional switch of the stage2 are off, and the working condition of the circuit is shown in fig. 6 (a). The current of the inductors L 1 and L 2 increases linearly, and the current rising rule of the inductors L 1 and L 2 is identical because the inductance of the inductors L 1 and L 2 is equal and the voltages at the two ends are equal.
Modality V: the switching tubes S 1 and S 2 of the bidirectional switch of the stage 1 are turned off, the switching tubes S 3 and S 4 of the bidirectional switch of the stage 2 are turned on, and the working condition of the circuit is shown in fig. 6 (b). The alternating current power supply freewheels through a filter loop, the inductors L 1 and L 2 discharge to the energy storage capacitor C and the load respectively through the bidirectional switching tubes S 3 and S 4, and the currents of the inductors L 1 and L 2 start to linearly decrease from the peak value-i L_max. Since the inductances of the inductances L 1 and L 2 are equal and the voltages at the two ends are still equal, the current drop rules of the inductances L 1 and L 2 are exactly the same.
Mode VI: the switching tubes S 1 and S 2 of the bidirectional switch of the stage 1 are turned off, the switching tubes S 3 and S 4 of the bidirectional switch of the stage 2 are turned off, and the working condition of the circuit is shown in fig. 6 (c). The alternating current power supply continuously flows through the filtering loop, and the change rule of the inductance L 1 and the change rule of the inductance L 2 are identical, so that the current of the two inductances in the stage is continuously 0, and the load is supplied by the two output filtering capacitors.
The volt-second equilibrium equation for the switching period is written for the voltage across the inductors L 1 and L 2, which can be obtained:
Where d is the duty cycle, Δ 1 is the time duty cycle of mode II/V, and V C is the voltage across the storage capacitor. The above simplification can be obtained:
the voltage across the energy storage capacitor is 1/2 of the output voltage, and the voltage gain depends on the ratio of the mode I/IV to the mode II/V time duty cycle. As can be seen from the foregoing principle analysis, the mode I/IV phase inductors L 1 and L 2 are charged, and the mode II/V phase inductors L 1 and L 2 are discharged, so that the input side current reaches the peak value I S_max at the turn-off time of the switching transistors S 1 and S 2 of the bidirectional switch No. 1, which can be expressed as:
The expression of the ac input current at power frequency is deduced from this:
According to the alternating-current side current expression of the Zeta type PFC converter, under the condition that inductance parameters, switching period and duty ratio are fixed, the shape of the input current of the converter is consistent with the input voltage, and the control of the input current can be realized by adjusting the duty ratio. In addition, the inductance parameter L can be designed according to the above formula in combination with the output power, and the design formula is as follows:
Where P o is the output power and V ac_rms is the effective value of the AC voltage.
The maximum value of the duty cycle d, L is determined by the maximum duty cycle d max in the inductance design formula. The maximum duty cycle is typically limited by DCM conditions, which can be expressed as:
d+Δ1＜1
combining the converter voltage gain expression with the DCM constraint, the expression of the maximum duty cycle d max is obtained:
Under the condition of defining the circuit voltage index, the maximum duty ratio d max is calculated first, and then the inductance design formula is utilized to design L. Ideally, the inductance values of the inductors L 1 and L 2 are the same, but the inductance values of the two inductors are slightly different in consideration of factors such as actual processing, the fact that the magnetic materials cannot be completely the same, and the like. The difference of the inductance quantity only affects the current change slope, the current falling speeds of the two inductance currents are different in the mode II/V discharging period, the current change of the inductance with smaller inductance is quicker, and when the current becomes equal to the current of the inductance with larger inductance, the current enters into the follow current stage of the mode III/VI to carry out follow current, and at the moment, the inductance current is not 0. When the inductance value of the inductor L 2 is smaller than L 1, the current of the inductor L 2 is reversed, so that the output side switching tube S 5/S6 is required to provide a bi-directional path, and the output side switching tube cannot be replaced by a diode. The circuit still has three stages of charging, discharging and freewheeling, the voltage gain expression is unchanged, and the input current expression is as follows:
where L 12 is the parallel inductance of the inductances L 1 and L 2, which can be expressed as:
The difference in inductance will have an effect on the input current compared to the previous input current expression, whereas the duty cycle d is obtained by the output voltage outer loop, and the effect of the difference in inductance can be solved by closed loop regulation.
Example 2: the Zeta-type bridgeless PFC converter using an uncontrolled diode at the output side, as shown in fig. 2, includes an input filter element (input filter inductor L f, input filter capacitor C f), inductor L 1、L2, storage capacitor C, two output filter capacitors C dc1、Cdc2, two bi-directional switches (two sets of anti-series switching tubes: first set S 1、S2, second set S 3、S4) and an uncontrolled diode D 1、D2. Wherein two bi-directional switches are capable of bi-directional current flow. The inductance of inductance L 1 is smaller than inductance L 2, i.e., L 1<L2. The positive pole of the input power supply is connected with one end of an input filter inductance L f, the other end of the input filter inductance L f is simultaneously connected with one end of a No. 1 bidirectional switch and one end of an input filter capacitance C f, and the other end of the No. 1 bidirectional switch is connected with one end of an inductance L 1, One end of the energy storage capacitor C is connected at the same time, the other end of the energy storage capacitor C, one end of the No. 2 bidirectional switch and one end of the inductor L 2 are connected at the same time, and the other end of the inductor L 2 is connected with the anode of the diode D 1 and the cathode of the diode D 2 at the same time; The negative electrode of the input power supply, the other end of the input filter capacitor C f, the other end of the inductor L 1, the other end of the No. 2 bidirectional switch, the negative electrode of the output filter capacitor C dc1 and the positive electrode of the output filter capacitor C dc2 are simultaneously connected; The cathode of the diode D 1 is connected to the anode of the output filter capacitor C dc1, and the anode of the diode D 2 is connected to the cathode of the output filter capacitor C dc2.
In the circuit, the current direction of the inductor L 2 is kept unchanged in positive and negative half cycles of the alternating input voltage, so that an uncontrolled unidirectional diode is adopted at the output side, and the control link is simplified. According to the switching conditions of the two groups of bidirectional switching tubes, six different working modes are shared by the Zeta type bridgeless PFC converter. The main current waveform of the circuit in one switching period of the positive half cycle of the input voltage is shown in fig. 7, and the corresponding circuit mode diagram is shown in fig. 8; the main current waveform of the circuit in one switching cycle of the negative half cycle of the input voltage is shown in fig. 9, and the corresponding circuit mode diagram is shown in fig. 10.
Modality I: the switching tubes S 1 and S 2 of the bidirectional switch of the stage 1 are on, the switching tubes S 3 and S 4 of the bidirectional switch of the stage 2 are off, and the working condition of the circuit is shown in fig. 8 (a). The inductors L 1 and L 2 charge linearly in the forward direction, which increases the current linearly, since the rising speed of the L 1<L2,L1 current is greater than L 2.
Modality II: the switching tubes S 1 and S 2 of the bidirectional switch of the stage 1 are turned off, the switching tubes S 3 and S 4 of the bidirectional switch of the stage 2 are turned on, and the working condition of the circuit is shown in fig. 8 (b). The alternating current power supply freewheels through a filter circuit, the inductors L 1 and L 2 discharge to the energy storage capacitor C and the load respectively through the switching tubes S 3 and S 4 of the No. 2 bidirectional switch, the current of the inductor L 1 starts to linearly decrease from the peak value i L1_max, and the current of the inductor L 2 starts to linearly decrease from the peak value i L2_max. Since the falling rate of the L 1<L2,L1 current is greater than the falling rate of the L 2.L1 current to 0, the reverse direction starts until the current is equal to the current of L 2.
Modality III: the switching tubes S 1 and S 2 of the bidirectional switch of the stage 1 are turned off, the switching tubes S 3 and S 4 of the bidirectional switch of the stage 2 are turned off, and the working condition of the circuit is shown in fig. 8 (c). The alternating current power supply continuously freewheels through the filter circuit, the current of the inductor L 1 and the current of the inductor L 2 are equal and freewheels, and the load is powered by the two output filter capacitors.
Modality IV: the switching tubes S 1 and S 2 of the bidirectional switch of the stage 1 are on, the switching tubes S 3 and S 4 of the bidirectional switch of the stage 2 are off, and the working condition of the circuit is shown in fig. 10 (a). The inductors L 1 and L 2 are charged linearly in opposite directions, and the current increases linearly, since the rising speed of the current of L 1<L2,L1 is greater than that of L 2.
Modality V: the switching tubes S 1 and S 2 of the bidirectional switch of the stage 1 are turned off, the switching tubes S 3 and S 4 of the bidirectional switch of the stage 2 are turned on, and the working condition of the circuit is shown in fig. 10 (b). The alternating current power supply freewheels through a filter circuit, the inductors L 1 and L 2 discharge to the energy storage capacitor C and the load respectively through the switching tubes S 3 and S 4 of the No. 2 bidirectional switch, the current of the inductor L 1 starts to linearly decrease from the peak value-i L1_max, and the current of the inductor L 2 starts to linearly decrease from the peak value-i L2_max. Since the falling rate of the L 1<L2,L1 current is greater than the falling rate of the L 2.L1 current to 0, the reverse direction starts until the current is equal to the current of L 2.
Mode VI: the switching tubes S 1 and S 2 of the bidirectional switch of the stage 1 are turned off, the switching tubes S 3 and S 4 of the bidirectional switch of the stage 2 are turned off, and the working condition of the circuit is shown in fig. 10 (c). The alternating current power supply continuously freewheels through the filter circuit, the current of the inductor L 1 and the current of the inductor L 2 are equal and freewheels, and the load is powered by the two output filter capacitors.
The volt-second equilibrium equation for the switching period is written for the voltage across the inductors L 1 and L 2, which can be obtained:
Where d is the duty cycle, Δ 1 is the time duty cycle of mode II/V, and V C is the voltage across the storage capacitor. The above simplification can be obtained:
the voltage across the energy storage capacitor is 1/2 of the output voltage, and the voltage gain depends on the ratio of the mode I/IV to the mode II/V time duty cycle. As can be seen from the foregoing principle analysis, the mode I/IV phase inductors L 1 and L 2 are charged, and the mode II/V phase inductors L 1 and L 2 are discharged, so that the input side current reaches the peak value I S_max at the turn-off time of the switching transistors S 1 and S 2 of the bidirectional switch No. 1, which can be expressed as:
where L 12 is the parallel inductance of the inductances L 1 and L 2, which can be expressed as:
The expression of the ac input current at power frequency is deduced from this:
According to the alternating-current side current expression of the Zeta type PFC converter, under the condition that inductance parameters, switching period and duty ratio are fixed, the shape of the input current of the converter is consistent with the input voltage, and the control of the input current can be realized by adjusting the duty ratio. In addition, the parallel inductance parameter L 12 can be designed according to the above formula in combination with the output power, and the design formula is as follows:
Where P o is the output power and V ac_rms is the effective value of the AC voltage.
The maximum value of the duty ratio d, L 12 is determined by the maximum duty ratio d max in the design formula of the parallel inductor. The maximum duty cycle is typically limited by DCM conditions, which can be expressed as:
d+Δ1＜1
combining the converter voltage gain expression with the DCM constraint, the expression of the maximum duty cycle d max is obtained:
Therefore, under the condition of defining the circuit voltage index, the maximum duty ratio d max is calculated first, and on the basis, the parallel inductance parameter L 12 is designed by utilizing an inductance design formula.
The current of the inductor L 2 in the converter has continuity, the inductance value with the inductance value larger than L 1,L2 can be designed according to the peak-peak value delta i L2 of the current change of L 2 in the switching period, and the design requirements are as follows:
The design formula of the inductance L 2 is thus obtained:
Combining the parallel inductance L 12, the inductance L 2 and the parallel inductance formula to obtain a design formula of the inductance L 1:
The inductance parameters in examples 1 and 2 were designed using the power frequency input effective value of 100V/50Hz and the output of 100V/500W as an example.
The switching frequency was designed to be 50kHz. Based on the input-output voltage indicator, a maximum duty cycle is calculated:
The duty cycle d=0.25 is taken.
The inductance parameters L 1 and L 2 in example 1 were designed:
substituting the duty ratio and other index parameters into the design formula of the inductance L can obtain:
inductance L 1＝L2 =25μh is thus obtained. It can be seen that the inductance of the two inductors of the converter is smaller, the converter volume is significantly reduced, and the requirement of high power density is fulfilled.
The inductance parameters L 1 and L 2 in example 2 were designed:
Substituting the duty ratio and other index parameters into the design formula of the parallel inductor L 12 can obtain:
Meanwhile, the inductance L 2 is substituted into a design formula of the inductance L 2, so that the following steps are obtained:
According to the obtained parallel inductance L 12 and inductance L 2, substituting the inductance L 1 into a design formula to obtain:
It can be seen that the inductance of the larger inductor of the converter is 200 muh at this time, which is still small compared to the input filter inductance of the mH level of the other PFC converters.
Based on the two sets of inductance parameters, as shown in fig. 11, the input-side power factor correction of the proposed circuit considers that the inductance will be slightly different in practice, the simulation values of the inductance parameters L 1 and L 2 in embodiment 1 are L 1＝27μH、L2 =24μh, and the simulation values of the inductance parameters L 1 and L 2 in embodiment 2 are equal to the design values, i.e. L 1＝13.34μH、L2 =200μh. As can be seen from simulation results, the input current of the circuit under the two groups of inductance parameters is sinusoidal wave with the same phase as the alternating voltage, and the power factor correction effect is good. In addition, as shown in fig. 12, the current waveforms of the inductor L 2 under the two groups of inductance parameters are shown, and the observation of the simulation waveforms shows that the current of the inductor L 2 under the smaller inductance parameter in embodiment 1 is in an intermittent state, while the current of the inductor L 2 under the larger inductance parameter in embodiment 2 is in a continuous state, so that the continuity of the output current direction can be verified to be controlled through flexible design of the inductance.
Although the invention herein has been described with reference to particular embodiments, it is to be understood that these embodiments are merely illustrative of the principles and applications of the present invention. It is therefore to be understood that numerous modifications may be made to the illustrative embodiments and that other arrangements may be devised without departing from the spirit and scope of the present invention as defined by the appended claims. It should be understood that the different dependent claims and the features described herein may be combined in ways other than as described in the original claims. It is also to be understood that features described in connection with separate embodiments may be used in other described embodiments.

Claims (7)

1. The single-stage single-phase bridgeless Zeta type PFC converter is characterized by comprising an input filter inductor L f, an input filter capacitor C f, an energy storage capacitor C, an inductor L 1, an inductor L 2, an NMOS switching tube S 5, an NMOS switching tube S 6, an output filter capacitor C dc1, an output filter capacitor C dc2, a No. 1 bidirectional switch and a No. 2 bidirectional switch;
The positive electrode of the input power supply is connected with one end of an input filter inductor L f, the other end of the input filter inductor L f is simultaneously connected with one end of a No. 1 bidirectional switch and one end of an input filter capacitor C f, the other end of the No. 1 bidirectional switch is simultaneously connected with one end of an inductor L 1 and one end of an energy storage capacitor C, the other end of the energy storage capacitor C, one end of a No. 2 bidirectional switch and one end of an inductor L 2 are simultaneously connected, and the other end of the inductor L 2 is simultaneously connected with the source electrode of an NMOS switch tube S 5 and the drain electrode of an NMOS switch tube S 6;
The negative electrode of the input power supply, the other end of the input filter capacitor C f, the other end of the inductor L 1, the other end of the No. 2 bidirectional switch, the negative electrode of the output filter capacitor C dc1 and the positive electrode of the output filter capacitor C dc2 are simultaneously connected;
The drain electrode of the NMOS switch tube S 5 is connected with the positive electrode of the output filter capacitor C dc1, and the source electrode of the NMOS switch tube S 6 is connected with the negative electrode of the output filter capacitor C dc2;
the inductance values of the inductance L 1 and the inductance L 2 are equal, and are L:
Where P o is the output power, V ac_rms is the ac voltage effective value, d is the duty cycle, and T S represents the switching period of the bi-directional switch.
2. The single-stage single-phase bridgeless Zeta-type PFC converter according to claim 1, wherein the maximum value d max of the duty cycle d is:
Where V dc represents the load voltage.
3. The single-stage single-phase bridgeless Zeta type PFC converter is characterized by comprising an input filter inductor L f, an input filter capacitor C f, an energy storage capacitor C, an inductor L 1, an inductor L 2, a diode D 1, a diode D 2, an output filter capacitor C dc1, an output filter capacitor C dc2, a No. 1 bidirectional switch and a No. 2 bidirectional switch;
The positive electrode of the input power supply is connected with one end of an input filter inductor L f, the other end of the input filter inductor L f is simultaneously connected with one end of a No. 1 bidirectional switch and one end of an input filter capacitor C f, the other end of the No. 1 bidirectional switch is simultaneously connected with one end of an inductor L 1 and one end of an energy storage capacitor C, the other end of the energy storage capacitor C, one end of a No. 2 bidirectional switch and one end of an inductor L 2 are simultaneously connected, and the other end of the inductor L 2 is simultaneously connected with the anode of a diode D 1 and the cathode of a diode D 2;
The negative electrode of the input power supply, the other end of the input filter capacitor C f, the other end of the inductor L 1, the other end of the No. 2 bidirectional switch, the negative electrode of the output filter capacitor C dc1 and the positive electrode of the output filter capacitor C dc2 are simultaneously connected;
The cathode of the diode D 1 is connected with the anode of the output filter capacitor C dc1, and the anode of the diode D 2 is connected with the cathode of the output filter capacitor C dc2;
The value of inductance L 2 is:
Where P o is the output power, V ac_rms is the ac voltage effective value, d is the duty cycle, T S represents the switching cycle of the bi-directional switch, and the value of the inductor L 1 is smaller than the value of the inductor L 2.
4. A single-stage single-phase bridgeless Zeta-type PFC converter according to claim 3, wherein the parallel inductance value L 12 of the inductance L 1 and the inductance L 2 is:
the value of inductance L 1 is determined from the value of inductance L 2 and the parallel inductance value L 12.
5. A single-stage single-phase bridgeless Zeta-type PFC converter according to claim 4, wherein said inductance L 1 has a value of:
6. A single-stage single-phase bridgeless Zeta-type PFC converter according to claim 3, 4 or 5, wherein the maximum value d max of the duty cycle d is:
Where V dc represents the load voltage.
7. A single-stage single-phase bridgeless Zeta-type PFC converter according to claim 1 or claim 3, wherein the circuit is operable in an intermittent conduction mode.
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