CN116155130B - PWM output voltage deviation compensation method, device and medium under low carrier ratio - Google Patents
PWM output voltage deviation compensation method, device and medium under low carrier ratio Download PDFInfo
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- CN116155130B CN116155130B CN202310424591.4A CN202310424591A CN116155130B CN 116155130 B CN116155130 B CN 116155130B CN 202310424591 A CN202310424591 A CN 202310424591A CN 116155130 B CN116155130 B CN 116155130B
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/53—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/537—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters
- H02M7/539—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency
- H02M7/5395—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only, e.g. single switched pulse inverters with automatic control of output wave form or frequency by pulse-width modulation
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/42—Conversion of dc power input into ac power output without possibility of reversal
- H02M7/44—Conversion of dc power input into ac power output without possibility of reversal by static converters
- H02M7/48—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/501—Conversion of dc power input into ac power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode sinusoidal output voltages being obtained by the combination of several pulse-voltages having different amplitude and width
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Abstract
The application provides a PWM output voltage deviation compensation method, device and medium under low carrier ratio, and belongs to the technical field of electronics. The method comprises the following steps: transforming the desired output voltage into a target voltage vector in a synchronous rotation coordinate system; according to the angular frequency of the expected target output voltage and the PWM control period, adjusting the amplitude and the phase of the target voltage vector to obtain an intermediate voltage vector; reversely transforming the intermediate voltage vector to obtain a compensated output voltage; and controlling PWM output of the power electronic device according to the compensated output voltage. By the provided PWM output voltage deviation compensation scheme under the low carrier ratio, fundamental wave voltage deviation caused by digital-to-analog discretization in the PWM modulation technology is eliminated, and control and display accuracy is improved.
Description
Technical Field
The application relates to the technical field of electronics, in particular to a PWM output voltage deviation compensation method, device and medium under low carrier ratio.
Background
Many power electronics, such as frequency converters, inverters, etc., typically need to output an ac voltage. Digitally controlled devices are not capable of outputting a continuously adjustable analog output voltage, but rather approximate the desired output voltage by pulse width modulation techniques (Pulse width modulation, PWM). PWM technology is essentially a digital-to-analog conversion technology. The frequency of the ac voltage desired to be output is referred to as a fundamental frequency, and the frequency of PWM control is referred to as a carrier frequency. The ratio of the switching frequency to the fundamental frequency is called the carrier ratio.
The existing actual equipment mostly adopts a closed-loop control system, and even if the actual output voltage is inconsistent with the expected output voltage, the system can work normally through the adjusting function of the closed-loop system. So for most applications where the carrier is high, no compensation is made for this deviation. However, for special applications such as high-frequency converters, the output fundamental frequency is often as high as hundreds to kilohertz, and the switching frequency is limited by hardware, so that the carrier ratio is very low, and the voltage deviation caused by digital-to-analog conversion becomes large. At this time, if such deviation is not compensated, control performance is deteriorated, and calculation and display of voltage, power, and the like are affected.
Disclosure of Invention
In order to solve the technical problems, the application provides a PWM output voltage deviation compensation method, device and medium under a low carrier ratio.
In a first aspect, the present application provides a PWM output voltage deviation compensation method under a low carrier ratio, the method including:
transforming the desired output voltage into a target voltage vector in a synchronous rotation coordinate system;
according to the angular frequency of the expected output voltage and the PWM control period, amplitude and phase adjustment are carried out on the target voltage vector, so that an intermediate voltage vector is obtained, the average value of the phase angle of the intermediate voltage vector in one PWM control period is equal to the phase angle of the target voltage vector, the average value of the projection component of the intermediate voltage vector tangential to the target voltage vector in one PWM control period is the amplitude of the target voltage vector, and the average value of the projection component of the intermediate voltage vector normal to the target voltage vector in one PWM control period is 0;
inversely transforming the intermediate voltage vector to obtain a compensated output voltage;
and controlling PWM output of the power electronic device according to the compensated output voltage.
In an embodiment, the adjusting the amplitude and the phase of the target voltage vector according to the angular frequency of the desired output voltage and the PWM control period to obtain an intermediate voltage vector includes:
respectively determining an amplitude increasing multiple and a phase angle increasing amount according to the angular frequency of the expected output voltage and the PWM control period;
and adjusting the amplitude of the target voltage vector according to the amplitude increase multiple, and adjusting the phase angle of the target voltage vector according to the phase angle increase quantity to obtain the intermediate voltage vector.
In one embodiment, determining the magnitude increase factor according to the angular frequency of the desired output voltage and the PWM control period, respectively, includes:
determining the amplitude increase multiple according to the following formula;
where k represents the magnitude increase factor, Δθ=ω×ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period.
In one embodiment, determining the phase angle increase according to the angular frequency of the desired output voltage and the PWM control period, respectively, includes:
determining the phase angle increase according to the following formula;
where s represents the phase angle increase amount, Δθ=ω×ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period.
In a second aspect, the present application provides a PWM output voltage deviation compensation apparatus for low carrier ratio, the apparatus comprising:
the first transformation module is used for transforming the expected output voltage into a target voltage vector under a synchronous rotation coordinate system;
the adjusting module is used for adjusting the amplitude and the phase of the target voltage vector according to the angular frequency and the PWM control period of the expected output voltage to obtain an intermediate voltage vector, wherein the average value of the phase angle of the intermediate voltage vector in one PWM control period is equal to the phase angle of the target voltage vector, the average value of the projection component of the intermediate voltage vector tangential to the target voltage vector in one PWM control period is the amplitude of the target voltage vector, and the average value of the projection component of the intermediate voltage vector normal to the target voltage vector in one PWM control period is 0;
the second conversion module is used for reversely converting the intermediate voltage vector to obtain a compensated output voltage;
and the control module is used for controlling PWM output of the power electronic device according to the compensated output voltage.
In an embodiment, the adjusting module is further configured to determine an amplitude increase multiple and a phase angle increase amount according to the angular frequency of the desired output voltage and the PWM control period, respectively;
and adjusting the amplitude of the target voltage vector according to the amplitude increase multiple, and adjusting the phase angle of the target voltage vector according to the phase angle increase quantity to obtain the intermediate voltage vector.
In an embodiment, the adjusting module is further configured to determine the magnitude increase multiple according to the following formula;
where k represents the magnitude increase factor, Δθ=ω×ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period.
In an embodiment, the adjustment module is further configured to determine the phase angle increase according to the following formula;
where s represents the phase angle increase amount, Δθ=ω×ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period.
In a third aspect, the present application provides a power electronic device comprising a memory and a processor, the memory for storing a computer program which, when run by the processor, performs the PWM output voltage deviation compensation method provided in the first aspect at a low carrier ratio.
In a fourth aspect, the present application provides a computer readable storage medium storing a computer program which when run on a processor performs the PWM output voltage deviation compensation method of the first aspect.
According to the PWM output voltage deviation compensation method, device and medium under the low carrier ratio, the expected output voltage is converted into the target voltage vector under the synchronous rotation coordinate system, the amplitude and phase angle of the target voltage vector are adjusted to obtain the intermediate voltage vector, the intermediate voltage vector is obtained through reverse conversion, the compensated output voltage is obtained through reverse conversion, PWM output is controlled according to the compensated output voltage, fundamental wave voltage deviation caused by digital-to-analog discretization in the PWM modulation technology is eliminated, control and display accuracy is improved, and the method and device are significant for application occasions with low carrier ratio.
Drawings
In order to more clearly illustrate the technical solutions of the present application, the drawings that are required for the embodiments will be briefly described, it being understood that the following drawings only illustrate some embodiments of the present application and therefore should not be considered as limiting the scope of protection of the present application. Like elements are numbered alike in the various figures.
FIG. 1 shows a schematic diagram of a PWM equivalent output voltage provided herein ignoring PWM harmonics;
FIG. 2 shows a schematic diagram of the voltage output bias provided herein;
FIG. 3 shows a schematic diagram of a target voltage vector and an output voltage vector in a stationary coordinate system provided herein;
FIG. 4 is a schematic diagram of a target voltage vector and an output voltage vector in a synchronous rotating coordinate system provided herein;
FIG. 5 is a flow chart of the PWM output voltage deviation compensation method at low carrier ratio provided by the present application;
FIG. 6 is a schematic diagram of the target voltage vector and the compensated output voltage vector in the synchronous rotating coordinate system provided by the present application;
fig. 7 shows a schematic structural diagram of the power electronic device provided by the application.
Icon: the PWM output voltage deviation compensation device under 700-low carrier ratio comprises a first conversion module, a 702-adjustment module, a 703-second conversion module and a 704-control module.
Detailed Description
The following description of the embodiments of the present application will be made clearly and fully with reference to the accompanying drawings, in which it is evident that the embodiments described are only some, but not all, of the embodiments of the present application.
The components of the present application, as generally described and illustrated in the figures herein, may be arranged and designed in a wide variety of different configurations. Thus, the following detailed description of the embodiments of the present application, as provided in the accompanying drawings, is not intended to limit the scope of the application, as claimed, but is merely representative of selected embodiments of the application. All other embodiments, which can be made by those skilled in the art based on the embodiments of the present application without making any inventive effort, are intended to be within the scope of the present application.
In the following, the terms "comprises", "comprising", "having" and their cognate terms may be used in various embodiments of the present application are intended only to refer to a particular feature, number, step, operation, element, component, or combination of the foregoing, and should not be interpreted as first excluding the existence of or increasing the likelihood of one or more other features, numbers, steps, operations, elements, components, or combinations of the foregoing.
Furthermore, the terms "first," "second," "third," and the like are used merely to distinguish between descriptions and should not be construed as indicating or implying relative importance.
Unless otherwise defined, all terms (including technical and scientific terms) used herein have the same meaning as commonly understood by one of ordinary skill in the art to which various embodiments of this application belong. The terms (such as those defined in commonly used dictionaries) will be interpreted as having a meaning that is identical to the meaning of the context in the relevant art and will not be interpreted in an idealized or overly formal sense unless expressly so defined herein in connection with the various embodiments.
In the prior art, there is a deviation between the actual output voltage produced by PWM technology and the desired voltage. One is that due to the harmonic voltage deviation introduced by the PWM modulation technique itself, PWM is based on the principle of "volt-second product" equality, rather than absolute equality, so that harmonic components related to multiples of the switching frequency, called PWM harmonics, are added to the output. The other is digital-analog conversion, which mainly affects the amplitude and phase of the fundamental wave due to voltage deviation introduced by discretization. Since harmonics can be attenuated by subsequent filter circuits, fundamental voltage deviation introduced by digital-to-analog conversion is a major concern.
Referring to fig. 1, if the harmonics introduced by the PWM technique itself are ignored, the PWM equivalent output voltage is a step wave of constant amplitude over one switching period. Referring to fig. 2, even though the PWM harmonics are ignored, there is still a deviation between the equivalent stepped output voltage and the desired sinusoidal output voltage, which is due to the voltage deviation introduced by the digital-to-analog conversion. When the carrier ratio is high, the number of steps in one sinusoidal cycle is relatively large, the voltage deviation is small, and when the carrier ratio is low, the deviation becomes large. The actual equipment adopts a closed-loop control system, and even if the actual output voltage is inconsistent with the expected output voltage, the system can work normally through the regulation function of the closed-loop system. So for most applications where the carrier is high, no compensation is made for this deviation. However, for special applications such as high-frequency converters, the output fundamental frequency is often as high as hundreds to kilohertz, and the switching frequency is limited by hardware, so that the carrier ratio is very low, and the voltage deviation caused by digital-to-analog conversion becomes large. At this time, if such deviation is not compensated, control performance is deteriorated, and calculation and display of voltage, power, and the like are affected.
Example 1
The application provides a PWM output voltage deviation compensation method under a low carrier ratio, which is based on a synchronous rotation coordinate system, and is used for respectively compensating phase angles and amplitude values of output voltages, so that PWM output is controlled according to the compensated output voltages, fundamental wave voltage deviation caused by digital-to-analog discretization in a PWM modulation technology is eliminated, and control and display precision is improved. Is significant for low carrier ratio applications.
Referring again to fig. 2, fig. 2 shows a deviation indication of the actual output voltage and the desired voltage, but based on fig. 2, the compensation method thereof is not easily analyzed. As shown in fig. 3, the desired output voltage and the actual PWM output voltage are placed in a static voltage space vector diagram, where the desired output voltage may be a desired sinusoidal output voltage. In one PWM control period, the desired sinusoidal output voltage corresponding vector is referred to as the target voltage vector, which is a vector that rotates at a uniform speed along the sector, starting at vector OA and ending at vector OB. The angle of rotation in one PWM control period is Δθ=ω·ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period. The vector corresponding to the PWM actual output voltage is referred to as the output voltage vector, which is a fixed vector OA, coinciding with the starting rotational position of the target voltage vector.
In fig. 3, the target voltage vector is projected as an alpha-axis voltage on the alpha-axis, and it can be seen that its magnitude varies from OE to OF over a control period; the beta-axis voltage also varies from OM to ON during a PWM control period. The PWM output voltage vector is fixed, with the projected voltage on the α axis fixed at OE and the projected voltage on the β axis fixed at OM. Obviously, there is a deviation between the output voltage vector and the target voltage vector.
Further, the voltage vector diagram in the stationary coordinate system shown in fig. 3 is transformed to a synchronous rotation coordinate system. The synchronous rotation coordinate system is a coordinate system of the same rotation speed and the same steering rotation as the voltage vector. As shown in fig. 4, in the synchronous rotation coordinate system, the target voltage vector rotated in the original stationary coordinate system becomes a fixed vector; the fixed output voltage vector in the original stationary coordinate system becomes a vector that rotates in the opposite direction at the angular velocity ω. The output voltage vector is rotated in a PWM control cycle from position OA where the target voltage vector is located back to position OB by the same angle Δθ.
In order to make the actual output voltage vector equivalent to the target voltage vector, the PWM output voltage deviation compensation method at a low carrier ratio shown in fig. 5 is employed, and includes steps S501 to S504, which will be described below.
S501, converting the desired output voltage into a target voltage vector in the synchronous rotation coordinate system.
In this embodiment, the target voltage vector in the synchronous rotation coordinate system takes the form of a polar coordinate. The three-phase system can firstly perform CLARK conversion, convert the three-phase voltage into two-phase voltage, and then convert the two-phase voltage into a synchronous rotation coordinate system through PARK. For a single-phase system, orthogonal two-phase voltages can be constructed by delaying the single-phase voltage by 90 °, and then transformed to a synchronous rotation coordinate system by PARK variation.
S502, according to the angular frequency of the expected output voltage and the PWM control period, adjusting the amplitude and the phase of the target voltage vector to obtain an intermediate voltage vector, wherein the average value of the phase angle of the intermediate voltage vector in one PWM control period is equal to the phase angle of the target voltage vector, and the average value of the projection component of the intermediate voltage vector tangential to the target voltage vector in one PWM control period is the amplitude of the target voltage vector.
In an embodiment, in S502, according to the angular frequency and the PWM control period of the desired output voltage, the amplitude and the phase of the target voltage vector are adjusted to obtain an intermediate voltage vector, which includes:
respectively determining an amplitude increasing multiple and a phase angle increasing amount according to the angular frequency of the expected output voltage and the PWM control period;
and adjusting the amplitude of the target voltage vector according to the amplitude increase multiple, and adjusting the phase angle of the target voltage vector according to the phase angle increase quantity to obtain the intermediate voltage vector.
In one embodiment, determining the magnitude increase factor according to the angular frequency of the desired output voltage and the PWM control period, respectively, includes:
determining the amplitude increase multiple according to the following formula;
where k represents the magnitude increase factor, Δθ=ω×ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period.
In one embodiment, determining the phase angle increase according to the angular frequency of the desired output voltage and the PWM control period, respectively, includes:
determining the phase angle increase according to the following formula;
where s represents the phase angle increase amount, Δθ=ω×ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period.
The principles of amplitude adjustment and phase adjustment are described below. Referring to fig. 6, compensating for the phase of the output voltage vector increases the initial phase of the output voltage vector by Δθ/2, the output voltage vector rotates from OC to OD at a constant speed ω. It can be seen that the phase angle of the compensated output voltage is equal to the phase angle of the target voltage vector in one cycle average value.
The magnitude of the output voltage vector is compensated such that the magnitude of the compensated output voltage increases to k. For equivalent target voltage vectors, the projected component of the output voltage vector along the tangential direction of the target voltage vector should be equal to the magnitude of the target voltage vector in one control period, for example, if the magnitude of the target voltage vector is 1, the projected component of the output voltage vector along the direction of the target voltage vector should be equal to 1 in one control period. Meanwhile, the projected component of the output voltage vector along the normal direction of the target voltage vector is 0 in average value in one PWM control period.
Wherein, the average value of the projection component of the output voltage vector tangential to the target voltage vector in a control period should be equal to 1, and the projection component can be expressed by the following formula:
where α is the phase difference of the phase compensated output voltage with respect to the target voltage vector.
The integral expansion of the above equation yields the following equation:
the average value of the projected component of the output voltage vector along the normal direction of the target voltage vector should be equal to 0 in one period.
Can verify
The constant holds.
It should be noted that the output voltage vector is dynamically rotated, so that the output voltage vector is equivalent to the target voltage vector, while the target voltage vector is stationary, so that it is only possible to make an equivalent in an average sense. The output voltage vector is decomposed along the tangential direction and the normal direction of the target voltage vector. The average value of the tangential component along the output voltage vector in one control period should be equal to the target voltage vector in size, and the average value of the normal component along the output voltage vector should be equal to 0, so that the output voltage vector in one control period can be considered to be equivalent to the target voltage vector. Alpha in the formula is the angular difference of the output vector (the vector rotated from OC to OD in fig. 6) with respect to the target voltage vector (i.e., the centerline of the fan-shaped COD in fig. 6) that compensates for the phase angle.
After the compensation, the average value of the amplitude and the phase angle of the output voltage vector in one period is not different from the target voltage vector. The amplitude and phase of the output voltage thus coincide with the target voltage vector.
And S503, inversely transforming the intermediate voltage vector to obtain a compensated output voltage.
In this embodiment, the intermediate voltage vector is first transformed from a polar form to a two-phase form. Then, the voltage vector of the rotating coordinate system is converted into the voltage vector of the static coordinate system by the inverse PARK conversion. The three-phase system is further converted by the inverse CLARK, and the compensated three-phase output voltage can be obtained. For a single-phase system, the compensated output voltage can be obtained by directly taking one coordinate component in the static coordinate system.
S504, controlling PWM output of the power electronic device according to the compensated output voltage.
In this way, the expected output voltage is converted into the target voltage vector under the synchronous rotation coordinate system, the amplitude and phase angle of the target voltage vector are adjusted to obtain the intermediate voltage vector, the intermediate voltage vector is reversely converted to obtain the compensated output voltage, the PWM output is controlled according to the compensated output voltage, the fundamental wave voltage deviation caused by digital-to-analog discretization in the PWM modulation technology is eliminated, the control and display precision is improved, and the method has great significance for the application occasion with low carrier ratio.
Example 2
In addition, the application provides a PWM output voltage deviation compensation device under a low carrier ratio.
As shown in fig. 7, the PWM output voltage deviation compensation apparatus 700 for low carrier ratio includes:
a first transformation module 701 for transforming a desired output voltage into a target voltage vector in a synchronous rotation coordinate system;
the adjusting module 702 is configured to adjust the amplitude and the phase of the target voltage vector according to the angular frequency and the PWM control period of the desired output voltage, so as to obtain an intermediate voltage vector, where the average value of the phase angle of the intermediate voltage vector in one PWM control period is equal to the phase angle of the target voltage vector, the average value of the projection components of the intermediate voltage vector tangential to the target voltage vector in one PWM control period is the amplitude of the target voltage vector, and the average value of the projection components of the intermediate voltage vector normal to the target voltage vector in one PWM control period is 0;
a second conversion module 703, configured to inversely convert the intermediate voltage vector to obtain a compensated output voltage;
and the control module 704 is used for controlling PWM output of the power electronic device according to the compensated output voltage.
In an embodiment, the adjusting module 702 is further configured to determine an amplitude increase multiple and a phase angle increase amount according to the angular frequency of the desired output voltage and the PWM control period, respectively;
and adjusting the amplitude of the target voltage vector according to the amplitude increase multiple, and adjusting the phase angle of the target voltage vector according to the phase angle increase quantity to obtain the intermediate voltage vector.
In an embodiment, the adjustment module 702 is further configured to determine the magnitude increase multiple according to the following formula;
where k represents the magnitude increase factor, Δθ=ω×ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period.
In one embodiment, the adjustment module 702 is further configured to determine the phase angle increase according to the following formula;
where s represents the phase angle increase amount, Δθ=ω×ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period.
The PWM output voltage deviation compensation device 700 under low carrier ratio provided in this embodiment can implement the PWM output voltage deviation compensation method under low carrier ratio provided in embodiment 1, and in order to avoid repetition, the description is omitted here.
According to the PWM output voltage deviation compensation device under the low carrier ratio, the expected output voltage is converted into the target voltage vector under the synchronous rotation coordinate system, the amplitude and the phase angle of the target voltage vector are adjusted to obtain the intermediate voltage vector, the intermediate voltage vector is obtained through reverse conversion, the compensated output voltage is obtained through reverse conversion, PWM output is controlled according to the compensated output voltage, fundamental wave voltage deviation caused by digital-to-analog discretization in the PWM modulation technology is eliminated, control and display precision is improved, and the PWM output voltage deviation compensation device is significant to application occasions with the low carrier ratio.
Example 3
Further, the present application provides a power electronic device comprising a memory and a processor, the memory storing a computer program which, when run on the processor, performs the PWM output voltage deviation compensation method provided by embodiment 1 at low carrier ratios.
The power electronic device provided in this embodiment can implement the PWM output voltage deviation compensation method provided in embodiment 1 under the low carrier ratio, and in order to avoid repetition, a description thereof will be omitted.
Example 4
The present application also provides a computer-readable storage medium having stored thereon a computer program which, when executed by a processor, implements the PWM output voltage deviation compensation method under the low carrier ratio provided in embodiment 1.
In the present embodiment, the computer readable storage medium may be a Read-Only Memory (ROM), a random access Memory (Random Access Memory, RAM), a magnetic disk, an optical disk, or the like.
The computer readable storage medium provided in this embodiment can implement the PWM output voltage deviation compensation method provided in embodiment 1 under the low carrier ratio, and in order to avoid repetition, the description is omitted here.
It should be noted that, in this document, the terms "comprises," "comprising," or any other variation thereof, are intended to cover a non-exclusive inclusion, such that a process, method, article, or terminal that comprises a list of elements does not include only those elements but may include other elements not expressly listed or inherent to such process, method, article, or terminal. Without further limitation, an element defined by the phrase "comprising one … …" does not exclude the presence of other like elements in a process, method, article or terminal comprising the element.
From the above description of the embodiments, it will be clear to those skilled in the art that the above-described embodiment method may be implemented by means of software plus a necessary general hardware platform, but of course may also be implemented by means of hardware, but in many cases the former is a preferred embodiment. Based on such understanding, the technical solution of the present application may be embodied essentially or in a part contributing to the prior art in the form of a software product stored in a storage medium (such as ROM/RAM, magnetic disk, optical disk), including several instructions for causing a terminal (which may be a mobile phone, a computer, a server, an air conditioner, or a network device, etc.) to perform the method described in the embodiments of the present application.
The embodiments of the present application have been described above with reference to the accompanying drawings, but the present application is not limited to the above-described embodiments, which are merely illustrative and not restrictive, and many forms may be made by those of ordinary skill in the art without departing from the spirit of the present application and the scope of the claims, which are also within the protection of the present application.
Claims (10)
1. A method for compensating for PWM output voltage deviation at low carrier ratio, the method comprising:
transforming the desired output voltage into a target voltage vector in a synchronous rotation coordinate system;
according to the angular frequency of the expected output voltage and the PWM control period, amplitude and phase adjustment are carried out on the target voltage vector, so that an intermediate voltage vector is obtained, the average value of the phase angle of the intermediate voltage vector in one PWM control period is equal to the phase angle of the target voltage vector, the average value of the projection component of the intermediate voltage vector tangential to the target voltage vector in one PWM control period is the amplitude of the target voltage vector, and the average value of the projection component of the intermediate voltage vector normal to the target voltage vector in one PWM control period is 0;
inversely transforming the intermediate voltage vector to obtain a compensated output voltage;
and controlling PWM output of the power electronic device according to the compensated output voltage.
2. The method of claim 1, wherein said performing amplitude and phase adjustments on said target voltage vector based on said angular frequency of said desired output voltage and PWM control period to obtain an intermediate voltage vector comprises:
respectively determining an amplitude increasing multiple and a phase angle increasing amount according to the angular frequency of the expected output voltage and the PWM control period;
and adjusting the amplitude of the target voltage vector according to the amplitude increase multiple, and adjusting the phase angle of the target voltage vector according to the phase angle increase quantity to obtain the intermediate voltage vector.
3. The method of claim 2, wherein determining the magnitude increase factor from the angular frequency of the desired output voltage and the PWM control period, respectively, comprises:
determining the amplitude increase multiple according to the following formula;
where k represents the magnitude increase factor, Δθ=ω×ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period.
4. The method of claim 2, wherein determining the phase angle increase from the angular frequency of the desired output voltage and the PWM control period, respectively, comprises:
determining the phase angle increase according to the following formula;
where s represents the phase angle increase amount, Δθ=ω×ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period.
5. A PWM output voltage deviation compensation apparatus for a low carrier ratio, the apparatus comprising:
the first transformation module is used for transforming the expected output voltage into a target voltage vector under a synchronous rotation coordinate system;
the adjusting module is used for adjusting the amplitude and the phase of the target voltage vector according to the angular frequency and the PWM control period of the expected output voltage to obtain an intermediate voltage vector, wherein the average value of the phase angle of the intermediate voltage vector in one PWM control period is equal to the phase angle of the target voltage vector, the average value of the projection component of the intermediate voltage vector tangential to the target voltage vector in one PWM control period is the amplitude of the target voltage vector, and the average value of the projection component of the intermediate voltage vector normal to the target voltage vector in one PWM control period is 0;
the second conversion module is used for reversely converting the intermediate voltage vector to obtain a compensated output voltage;
and the control module is used for controlling PWM output of the power electronic device according to the compensated output voltage.
6. The apparatus of claim 5, wherein the adjustment module is further configured to determine a magnitude increase factor and a phase angle increase amount, respectively, based on the angular frequency of the desired output voltage and a PWM control period;
and adjusting the amplitude of the target voltage vector according to the amplitude increase multiple, and adjusting the phase angle of the target voltage vector according to the phase angle increase quantity to obtain the intermediate voltage vector.
7. The apparatus of claim 6, wherein the adjustment module is further configured to determine the magnitude increase factor according to the following equation;
where k represents the magnitude increase factor, Δθ=ω×ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period.
8. The apparatus of claim 6, wherein the adjustment module is further configured to determine the phase angle increase according to the following formula;
where s represents the phase angle increase amount, Δθ=ω×ts, ω is the angular frequency of the desired output voltage, and Ts is the PWM control period.
9. A power electronic device comprising a memory and a processor, the memory for storing a computer program that, when executed by the processor, performs the PWM output voltage deviation compensation method of any one of claims 1 to 4 at a low carrier ratio.
10. A computer readable storage medium, characterized in that it stores a computer program which, when run on a processor, performs the PWM output voltage deviation compensation method at a low carrier ratio according to any one of claims 1 to 4.
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Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101399498A (en) * | 2007-09-26 | 2009-04-01 | 华为技术有限公司 | DC conversion power source device and method for improving DC conversion power source device |
| CN102624276A (en) * | 2012-04-25 | 2012-08-01 | 杭州电子科技大学 | Novel dead-zone effect compensation method of AC servo inverter |
| WO2015115223A1 (en) * | 2014-01-31 | 2015-08-06 | 株式会社明電舎 | Inverter control method and voltage-type inverter |
| CN110752632A (en) * | 2018-07-24 | 2020-02-04 | 株洲中车时代电气股份有限公司 | Device for realizing train fireless loopback by adopting bidirectional charger and control method thereof |
| CN110932584A (en) * | 2019-12-05 | 2020-03-27 | 深圳市汇川技术股份有限公司 | Inverter nonlinear compensation method, system, device and storage medium |
| CN113422533A (en) * | 2021-06-30 | 2021-09-21 | 浙江大学 | Vector angle proportional-integral control method |
| CN113691155A (en) * | 2021-07-09 | 2021-11-23 | 重庆雅讯科技有限公司 | Single-phase inverter control method and system based on PI and repetitive control and inverter |
| JP2022091189A (en) * | 2020-12-09 | 2022-06-21 | 株式会社明電舎 | Power conversion device and method for controlling the same |
-
2023
- 2023-04-20 CN CN202310424591.4A patent/CN116155130B/en active Active
Patent Citations (8)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN101399498A (en) * | 2007-09-26 | 2009-04-01 | 华为技术有限公司 | DC conversion power source device and method for improving DC conversion power source device |
| CN102624276A (en) * | 2012-04-25 | 2012-08-01 | 杭州电子科技大学 | Novel dead-zone effect compensation method of AC servo inverter |
| WO2015115223A1 (en) * | 2014-01-31 | 2015-08-06 | 株式会社明電舎 | Inverter control method and voltage-type inverter |
| CN110752632A (en) * | 2018-07-24 | 2020-02-04 | 株洲中车时代电气股份有限公司 | Device for realizing train fireless loopback by adopting bidirectional charger and control method thereof |
| CN110932584A (en) * | 2019-12-05 | 2020-03-27 | 深圳市汇川技术股份有限公司 | Inverter nonlinear compensation method, system, device and storage medium |
| JP2022091189A (en) * | 2020-12-09 | 2022-06-21 | 株式会社明電舎 | Power conversion device and method for controlling the same |
| CN113422533A (en) * | 2021-06-30 | 2021-09-21 | 浙江大学 | Vector angle proportional-integral control method |
| CN113691155A (en) * | 2021-07-09 | 2021-11-23 | 重庆雅讯科技有限公司 | Single-phase inverter control method and system based on PI and repetitive control and inverter |
Non-Patent Citations (2)
| Title |
|---|
| 不平衡工况矩阵变换器前馈补偿闭环控制;杨佳丽;杨俊华;杨亮;吴捷;;计算机仿真(第10期);300-304 * |
| 基于瞬时无功的三相4象限整流器相位补偿控制;李伟;唐蕾;马志文;;电气传动(第09期);25-28 * |
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