CN114759811B - Converter and vienna rectifier - Google Patents
Converter and vienna rectifier Download PDFInfo
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- CN114759811B CN114759811B CN202210670265.7A CN202210670265A CN114759811B CN 114759811 B CN114759811 B CN 114759811B CN 202210670265 A CN202210670265 A CN 202210670265A CN 114759811 B CN114759811 B CN 114759811B
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- 238000000034 method Methods 0.000 claims abstract description 17
- 238000006243 chemical reaction Methods 0.000 claims description 107
- 238000004146 energy storage Methods 0.000 claims description 103
- 238000001914 filtration Methods 0.000 claims description 30
- 239000003990 capacitor Substances 0.000 claims description 21
- 230000007935 neutral effect Effects 0.000 claims description 14
- 238000005070 sampling Methods 0.000 claims description 2
- 230000008859 change Effects 0.000 abstract description 6
- 238000010586 diagram Methods 0.000 description 36
- 238000011217 control strategy Methods 0.000 description 16
- 238000004088 simulation Methods 0.000 description 13
- 238000012937 correction Methods 0.000 description 9
- 230000008569 process Effects 0.000 description 7
- 238000012546 transfer Methods 0.000 description 7
- 230000005669 field effect Effects 0.000 description 5
- 230000001939 inductive effect Effects 0.000 description 4
- 102100034033 Alpha-adducin Human genes 0.000 description 3
- 101000799076 Homo sapiens Alpha-adducin Proteins 0.000 description 3
- 101000629598 Rattus norvegicus Sterol regulatory element-binding protein 1 Proteins 0.000 description 3
- 230000000295 complement effect Effects 0.000 description 3
- 102100034004 Gamma-adducin Human genes 0.000 description 2
- 101000799011 Homo sapiens Gamma-adducin Proteins 0.000 description 2
- 230000007423 decrease Effects 0.000 description 2
- 238000012545 processing Methods 0.000 description 2
- 230000004044 response Effects 0.000 description 2
- 238000012706 support-vector machine Methods 0.000 description 2
- 230000007704 transition Effects 0.000 description 2
- 102100024348 Beta-adducin Human genes 0.000 description 1
- 101000689619 Homo sapiens Beta-adducin Proteins 0.000 description 1
- 101100381996 Saccharomyces cerevisiae (strain ATCC 204508 / S288c) BRO1 gene Proteins 0.000 description 1
- 101710176296 Switch 2 Proteins 0.000 description 1
- 230000002238 attenuated effect Effects 0.000 description 1
- 230000008878 coupling Effects 0.000 description 1
- 238000010168 coupling process Methods 0.000 description 1
- 238000005859 coupling reaction Methods 0.000 description 1
- 238000013461 design Methods 0.000 description 1
- 230000000694 effects Effects 0.000 description 1
- 239000000463 material Substances 0.000 description 1
- 238000012986 modification Methods 0.000 description 1
- 230000004048 modification Effects 0.000 description 1
- 238000006467 substitution reaction Methods 0.000 description 1
- 230000009466 transformation Effects 0.000 description 1
- 238000010200 validation analysis Methods 0.000 description 1
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M7/00—Conversion of ac power input into dc power output; Conversion of dc power input into ac power output
- H02M7/02—Conversion of ac power input into dc power output without possibility of reversal
- H02M7/04—Conversion of ac power input into dc power output without possibility of reversal by static converters
- H02M7/12—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode
- H02M7/21—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal
- H02M7/217—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M7/219—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration
- H02M7/2195—Conversion of ac power input into dc power output without possibility of reversal by static converters using discharge tubes with control electrode or semiconductor devices with control electrode using devices of a triode or transistor type requiring continuous application of a control signal using semiconductor devices only in a bridge configuration the switches being synchronously commutated at the same frequency of the AC input voltage
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02E—REDUCTION OF GREENHOUSE GAS [GHG] EMISSIONS, RELATED TO ENERGY GENERATION, TRANSMISSION OR DISTRIBUTION
- Y02E40/00—Technologies for an efficient electrical power generation, transmission or distribution
- Y02E40/40—Arrangements for reducing harmonics
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Abstract
The converter and the vienna rectifier only need to sample input current and output values of a voltage ring to realize control of the rectifier, do not need to sample input voltage, and also do not need to use a phase-locked loop and a coordinate system change method to realize control of the high-power factor rectifier, so that the phase and frequency of the input current can track the voltage phase of an alternating-current side power grid, and the in-phase work of the input current and the input voltage of the converter and the vienna rectifier is realized.
Description
Technical Field
The invention relates to the technical field of converters, in particular to a converter and a vienna rectifier.
Background
The Vienna rectifier is a pulse width modulation rectifier that receives three-phase ac power. As shown in fig. 1, before the conventional control strategy of the Vienna rectifier, it is necessary to sample the input voltage and current at the ac side, obtain the phase angle of the power grid at the ac side with a phase-locked loop, and then calculate and convert the phase angle to the dq coordinate system with a large number of trigonometric functions for control. And then respectively controlling id and iq by using a dq decoupling control method, and controlling the power level by using other PWM (pulse-width modulation) strategies such as an SVM (support vector machine) and the like after reversing the control quantity of dq to abc three phases.
However, the whole controller of the Vienna rectifier needs trigonometric function and coordinate system transformation, and the most critical is the design of a phase-locked loop, when a three-phase power grid is unbalanced, the common SRF-SPLL can not work sufficiently basically, and 2-order harmonic waves exist on output dq to influence the control effect of current. If the higher harmonics and the unbalance degree of the power grid are increased, the DDSRF-SPLL is needed to be used for positive and negative sequence decoupling control, the algorithm complexity of the control strategy is increased again, and the phase-locked loop can completely overcome the response speed of the power grid when the frequency changes, so that the traditional vienna control strategy is not applicable in severe power grid environments, when the higher harmonics and the frequency change, or in generator application and other scenes.
Disclosure of Invention
The technical problem mainly solved by the invention is to provide a converter and a vienna rectifier, so that the phase and the frequency of input current can track the phase and the frequency of voltage of an alternating-current side power grid, and the in-phase operation of the input current and the input voltage of the converter and the vienna rectifier is realized.
According to a first aspect, there is provided in an embodiment a transducer comprising: the energy storage and energy conversion module, the switch module, the follow current module, the filtering module and the controller; the switch module comprises a first end, a second end and a control end;
the energy storage and conversion module is used for converting direct current input by the direct current input end of the converter into magnetic energy for storage when the switch module is switched on; when the switch module is turned off, the stored magnetic energy is converted into an electric signal and is output to the output end of the converter through the follow current module;
the switch module is used for responding to a first control signal output by the controller to be switched off or switched on;
the follow current module is used for transmitting the converted electric signal output by the energy storage and conversion module to the output end of the converter;
the filtering module is used for filtering the electric signal output by the output end of the converter;
the controller is used for acquiring the current value of the electric signal output by the energy storage and conversion module and the output value of the voltage ring of the converter; determining a control quantity based on the current value of the electric signal output by the energy storage and conversion module and the voltage loop output value; and generating and outputting the control signal to a control end of the switch module based on the relation between the control quantity and a preset PWM carrier wave.
According to a second aspect, an embodiment provides a vienna rectifier for converting an input three-phase alternating current into a first direct current and a second direct current having the same voltage, the three-phase alternating current including an a-phase alternating current, a B-phase alternating current point, and a C-phase alternating current, wherein the vienna rectifier includes: a switch module and a controller;
the switch module comprises a first switch, a second switch and a third switch; the first end of the first switch is connected with the input end of the A-phase alternating current, and the second end of the first switch is connected with the neutral line of the vienna rectifier; the first end of the second switch is connected with the input end of the phase-B alternating current, and the second end of the second switch is connected with the neutral line of the vienna rectifier; the first end of the third switch is connected with the input end of the C-phase alternating current, and the second end of the third switch is connected with the neutral line of the vienna rectifier;
the switching module is used for alternately switching on and off through the first switch, the second switch and the third switch under the control of a first control signal, a second control signal and a third control signal output by the controller, so that the vienna rectifier outputs a first direct current and a second direct current; the first control signal is used for controlling the first switch to be turned on or off, the second control signal is used for controlling the second switch to be turned on or off, and the third control signal is used for controlling the third switch to be turned on or off;
the controller is used for acquiring a current value of the A-phase alternating current, a current value of the B-phase alternating current, a current value of the C-phase alternating current and an output value of a voltage ring of the vienna rectifier; determining a first control quantity, a second control quantity and a third control quantity based on the current value of the A-phase alternating current, the current value of the B-phase alternating current, the current value of the C-phase alternating current and the output value of the voltage loop of the vienna rectifier; and generating and outputting the first control signal, the second control signal and the third control signal based on the relation between the first control quantity, the second control quantity and the third control quantity and a preset PWM carrier wave.
According to a third aspect, an embodiment provides a vienna rectifier capable of realizing midpoint balance, for converting an input three-phase alternating current into a first direct current and a second direct current, the three-phase alternating current including an a-phase alternating current, a B-phase intersection point and a C-phase alternating current, the vienna rectifier comprising: a switch module and a controller;
the switch module comprises a first switch, a second switch and a third switch; the first end of the first switch is connected with the input end of the A-phase alternating current, and the second end of the first switch is connected with the neutral line of the vienna rectifier; the first end of the second switch is connected with the input end of the B-phase alternating current, and the second end of the second switch is connected with the neutral line of the vienna rectifier; the first end of the third switch is connected with the input end of the C-phase alternating current, and the second end of the third switch is connected with the neutral line of the vienna rectifier;
the switching module is used for alternately switching on and off through the first switch, the second switch and the third switch under the control of a first control signal, a second control signal and a third control signal output by the controller, so that the vienna rectifier outputs a first direct current and a second direct current; the first control signal is used for controlling the first switch to be turned on or off, the second control signal is used for controlling the second switch to be turned on or off, and the third control signal is used for controlling the third switch to be turned on or off;
the controller is used for acquiring a current value of the A-phase alternating current, a current value of the B-phase alternating current, a current value of the C-phase alternating current, an output value of a voltage ring of the vienna rectifier and an output value of a voltage equalizing ring of a direct-current side output voltage of the vienna rectifier; determining a first control quantity, a second control quantity and a third control quantity based on the current value of the A-phase alternating current, the current value of the B-phase alternating current and the current value of the C-phase alternating current, the output value of a voltage ring of the vienna rectifier and the output value of a voltage equalizing ring of the direct-current side output voltage of the vienna rectifier; and generating and outputting the first control signal, the second control signal and the third control signal based on the relationship between the first control quantity, the second control quantity and the third control quantity and a preset PWM carrier wave.
In an embodiment, the determining a first control quantity, a second control quantity and a third control quantity based on a current value of the a-phase alternating current, a current value of the B-phase alternating current and a current value of the C-phase alternating current, an output value of a voltage loop of the vienna rectifier and an output value of a voltage equalizing loop of a dc-side output voltage of the vienna rectifier includes:
taking the ratio of the sum of the current value of the A-phase alternating current and the output value of the equalizing ring to the output value of the voltage ring as a first control quantity;
taking the ratio of the sum of the current value of the phase-B alternating current and the output value of the equalizing ring to the output value of the voltage ring as a second control quantity;
taking the ratio of the sum of the current value of the C-phase alternating current and the output value of the equalizing ring to the output value of the voltage ring as a third control quantity;
wherein the first control quantity, the second control quantity and the third control quantity all satisfy more than 0 and less than 1.
In an embodiment, the generating and outputting the first control signal, the second control signal, and the third control signal based on the relationship between the first control quantity, the second control quantity, and the third control quantity and a preset PWM carrier includes:
multiplying the first control quantity by a preset switching cycle time to obtain a first core control quantity;
in each period of the preset PWM carrier, taking a time period when the preset PWM carrier is greater than or equal to the first core control quantity as a turn-off time period of the first switch, and taking a time period when the preset PWM carrier is less than the first core control quantity as a turn-on time period of the first switch;
generating and outputting first control signals of each period to a control end of the first switch based on the turn-off time period and the turn-on time period of the first switch;
generating a first control signal for controlling the first switch to be switched off in the switching-off time period of the first switch, and generating a first control signal for controlling the first switch to be switched on in the switching-on time period of the first switch;
multiplying the second control quantity by the preset switching cycle time to obtain a second core control quantity;
in each period of the preset PWM carrier, taking a time period when the preset PWM carrier is greater than or equal to the second core control quantity as a turn-off time period of the second switch, and taking a time period when the preset PWM carrier is less than the second core control quantity as a turn-on time period of the second switch;
generating and outputting a second control signal of each period to a control end of the second switch based on the turn-off time period and the turn-on time period of the second switch;
generating a second control signal for controlling the second switch to be switched off in the switching-off time period of the second switch, and generating a second control signal for controlling the second switch to be switched on in the switching-on time period of the second switch;
the generating and outputting the third control signal to the control end of the third switch based on the relationship between the third control quantity and a preset PWM carrier includes:
multiplying the third control quantity by the preset switching cycle time to obtain a third core control quantity;
in each period of the preset PWM carrier, taking a time period when the preset PWM carrier is greater than or equal to the third core control amount as a turn-off time period of the third switch, and taking a time period when the preset PWM carrier is less than the third core control amount as a turn-on time period of the third switch;
generating and outputting a third control signal of each period to a control end of the third switch based on the turn-off time period and the turn-on time period of the third switch;
wherein a third control signal for controlling the third switch to be turned off is generated in an off period of the third switch, and a third control signal for controlling the third switch to be turned on is generated in an on period of the third switch.
According to a fourth aspect, an embodiment provides a three-phase two-level rectifier for converting an input three-phase alternating current into a direct current, the three-phase alternating current including an a-phase alternating current, a B-phase alternating current, and a C-phase alternating current, including: a switch module and a controller;
the switch module comprises a first lower bridge switch, a second lower bridge switch and a third lower bridge switch; the first lower bridge switch is used for receiving the A-phase alternating current, the second lower bridge switch is used for receiving the B-phase alternating current, and the third lower bridge switch is used for receiving the C-phase alternating current;
the switch module is used for converting the three-phase alternating current into direct current under the control of a first control signal, a second control signal and a third control signal output by the controller; the first control signal is used for controlling the first lower bridge switch to be turned on or off, the second control signal is used for controlling the second lower bridge switch to be turned on or off, and the third control signal is used for controlling the third lower bridge switch to be turned on or off;
the controller is used for acquiring the current value of the A-phase alternating current, the current value of the B-phase alternating current, the current value of the C-phase alternating current and the output value of a voltage ring of the rectifier; determining a first control quantity, a second control quantity and a third control quantity based on the current value of the A-phase alternating current, the current value of the B-phase alternating current, the current value of the C-phase alternating current and the output value of the voltage ring of the rectifier; and generating and outputting the first control signal, the second control signal and the third control signal based on the relationship between the first control quantity, the second control quantity and the third control quantity and a preset PWM carrier wave.
In an embodiment, the determining a first control amount, a second control amount, and a third control amount based on a current value of the a-phase alternating current, a current value of the B-phase alternating current, a current value of the C-phase alternating current, and an output value of a voltage loop of the rectifier includes:
taking the ratio of the current value of the A-phase alternating current to the output value of the voltage loop as a first control quantity;
taking the ratio of the current value of the B-phase alternating current to the output value of the voltage loop as a second control quantity;
taking the ratio of the current value of the C-phase alternating current to the output value of the voltage loop as a third control quantity;
wherein the first control quantity, the second control quantity and the third control quantity all satisfy more than 0 and less than 1.
In an embodiment, the generating and outputting the first control signal, the second control signal, and the third control signal based on the relationship between the first control quantity, the second control quantity, and the third control quantity and a preset PWM carrier includes:
multiplying the first control quantity by a preset switching cycle time to obtain a first core control quantity;
in each period of the preset PWM carrier, taking a time period when the preset PWM carrier is greater than or equal to the first core control quantity as a turn-off time period of the first lower bridge switch, and taking a time period when the preset PWM carrier is less than the first core control quantity as a turn-on time period of the first lower bridge switch;
generating and outputting a first control signal of each period to a control end of the first lower bridge switch based on the turn-off time period and the turn-on time period of the first lower bridge switch;
generating a first control signal for controlling the first lower bridge switch to be turned off in an off time period of the first lower bridge switch, and generating a first control signal for controlling the first lower bridge switch to be turned on in an on time period of the first lower bridge switch;
multiplying the second control quantity by the preset switching cycle time to obtain a second core control quantity;
in each period of the preset PWM carrier, taking a time period when the preset PWM carrier is greater than or equal to the second core control quantity as a turn-off time period of the second lower bridge switch, and taking a time period when the preset PWM carrier is less than the second core control quantity as a turn-on time period of the second lower bridge switch;
generating and outputting a second control signal of each period to a control end of the second lower bridge switch based on the turn-off time period and the turn-on time period of the second lower bridge switch;
generating a second control signal for controlling the second lower bridge switch to be turned off in the turn-off time period of the second lower bridge switch, and generating a second control signal for controlling the second lower bridge switch to be turned on in the turn-on time period of the second lower bridge switch;
the generating and outputting the third control signal to the control end of the third lower bridge switch based on the relationship between the third control quantity and a preset PWM carrier includes:
multiplying the third control quantity by the preset switching cycle time to obtain a third core control quantity;
in each period of the preset PWM carrier, taking a time period when the preset PWM carrier is greater than or equal to the third core control quantity as a turn-off time period of the third lower bridge switch, and taking a time period when the preset PWM carrier is less than the third core control quantity as a turn-on time period of the third lower bridge switch;
generating and outputting a third control signal of each period to a control end of the third lower bridge switch based on the turn-off time period and the turn-on time period of the third lower bridge switch;
and generating a third control signal for controlling the third lower bridge switch to be turned off in the turn-off time period of the third lower bridge switch, and generating a third control signal for controlling the third lower bridge switch to be turned on in the turn-on time period of the third lower bridge switch.
According to a fifth aspect, an embodiment provides a single-phase bridgeless power factor correction converter, comprising: a switch module and a controller;
the switch module includes: the bridge comprises a first bridge arm unit, a second bridge arm unit and a third bridge arm unit; the first bridge arm unit, the second bridge arm unit and the third bridge arm unit are respectively connected with an alternating current power grid and used for converting alternating current output by the alternating current power grid into direct current;
the controller is used for acquiring a current value of the alternating current and an output value of a voltage ring of the converter; determining a control quantity based on the current value of the alternating current and an output value of a voltage loop of the converter; generating and outputting the first control signal and the second control signal based on the relation between the control quantity and a first preset PWM carrier wave and a second preset PWM carrier wave respectively;
the first control signal is used for controlling the first bridge arm unit to be switched on or switched off, and the second control signal is used for controlling the second bridge arm unit to be switched on or switched off.
According to a sixth aspect, an embodiment provides a control method of a single-phase bridgeless power factor correction converter, applied to the converter according to the above embodiment, wherein the control method includes:
acquiring a current value of the alternating current and an output value of a voltage ring of the converter;
determining a control quantity based on the current value of the alternating current and an output value of a voltage loop of the converter;
generating and outputting the first control signal and the second control signal based on the relation between the control quantity and a first preset PWM carrier wave and a second preset PWM carrier wave respectively;
the first control signal is used for controlling the first bridge arm unit to be switched on or switched off, and the second control signal is used for controlling the second bridge arm unit to be switched on or switched off.
According to the converter and the vienna rectifier of the embodiment, the control of the rectifier is realized by only sampling the input current and the output value of the voltage loop, the input voltage is not required to be sampled, and the control of the high-power-factor rectifier is realized by using a phase-locked loop and a coordinate system change method, so that the phase and the frequency of the input current can track the voltage phase of an alternating-current-side power grid, and the in-phase work of the input current and the input voltage of the converter and the vienna rectifier is realized.
Drawings
Fig. 1 is a schematic diagram of a control strategy of a conventional vienna rectifier;
FIG. 2 is a schematic diagram of a converter according to an embodiment;
FIG. 3 is a circuit schematic of a Boost converter of an embodiment;
fig. 4 is a schematic diagram of the switching period of the current iL and the first switch;
FIG. 5 is a schematic diagram of a switching cycle of the first switching module;
FIG. 6 is a schematic diagram of an embodiment of a vienna rectifier;
FIG. 7 is a circuit schematic of a vienna rectifier according to one embodiment;
FIG. 8 is a control block diagram of a controller of a vienna rectifier of an embodiment;
FIG. 9 is a schematic diagram of a simulation of a vienna rectifier;
FIG. 10 is another simulation of a vienna rectifier;
FIG. 11 is a schematic diagram of yet another simulation of a vienna rectifier;
FIG. 12 is a control block diagram of a controller of a vienna rectifier capable of neutral point balancing according to one embodiment;
fig. 13 is a control block diagram of the controller obtaining the output value Diff of the grading ring and the output value Vloop of the voltage ring;
fig. 14 is a schematic simulation diagram of a vienna rectifier capable of achieving midpoint balancing according to this embodiment;
fig. 15 is another simulation schematic diagram of the vienna rectifier capable of achieving midpoint balance according to the embodiment;
FIG. 16 is a schematic diagram of a three-phase two-level rectifier according to an embodiment;
FIG. 17 is a circuit schematic of a three-phase two-level rectifier of an embodiment;
FIG. 18 is a control block diagram of a controller of a three-phase two-level rectifier of an embodiment;
FIG. 19 is a schematic diagram of a simulation of a three-phase two-level rectifier;
FIG. 20 is another simulation of a three-phase two-level rectifier;
FIG. 21 is a schematic diagram of yet another simulation of a three-phase two-level rectifier;
FIG. 22 is a schematic diagram of an exemplary single-phase bridgeless PFC converter;
FIG. 23 is a circuit schematic of a single-phase bridgeless PFC converter according to an embodiment;
FIG. 24 is a control block diagram of a controller of a single-phase bridgeless PFC converter according to an embodiment;
FIG. 25 is a block diagram illustrating the generation of the first transition control signal AC _ L and the second transition control signal AC _ N according to one embodiment;
FIG. 26 is a flow chart of a control method for a single-phase bridgeless PFC converter;
fig. 27 is a simulation diagram of a single-phase bridgeless pfc converter.
Detailed Description
The present invention will be described in further detail with reference to the following detailed description and accompanying drawings. Wherein like elements in different embodiments are numbered with like associated elements. In the following description, numerous specific details are set forth in order to provide a better understanding of the present application. However, those skilled in the art will readily recognize that some of the features may be omitted or replaced with other elements, materials, methods in different instances. In some instances, certain operations related to the present application have not been shown or described in detail in order to avoid obscuring the core of the present application from excessive description, and it is not necessary for those skilled in the art to describe these operations in detail, so that they may be fully understood from the description in the specification and the general knowledge in the art.
Furthermore, the features, operations, or characteristics described in the specification may be combined in any suitable manner to form various embodiments. Also, the various steps or actions in the description of the methods may be transposed or transposed in order, as will be apparent to a person skilled in the art. Thus, the various sequences in the specification and drawings are for the purpose of describing certain embodiments only and are not intended to imply a required sequence unless otherwise indicated where such sequence must be followed.
The numbering of the components as such, e.g., "first", "second", etc., is used herein only to distinguish the objects as described, and does not have any sequential or technical meaning. The term "connected" and "coupled" when used in this application, unless otherwise indicated, includes both direct and indirect connections (couplings).
The first embodiment is as follows:
referring to fig. 2, fig. 2 is a schematic diagram of a converter according to an embodiment, and a circuit structure of the converter 10 provided in the embodiment is a common Boost converter, which includes: a first energy storage and conversion module 11, a first switching module 12, a first freewheel module 13, a first filtering module 14 and a first controller 15. The first switch module 12 includes a first terminal, a second terminal, and a control terminal; the input end of the first energy storage and energy conversion module 11 is connected with the direct current input end V1_ dc, the output end of the first energy storage and energy conversion module 11 is connected with the first end of the first switch module 12 and the input end of the first follow current module 13, the second end of the first switch module 12 is connected with the ground, the output end of the first follow current module 13 is connected with the output end (output load) of the converter 10, and the first filtering module 14 is connected in parallel with the output end (output load) of the converter 10; the control terminal of the first switch module 12 is connected to a first controller 15.
The first energy storage and conversion module 11 is used for converting the direct current input by the direct current input end V1_ dc into magnetic energy for storage when the first switch module 12 is turned on; when the first switching module 12 is turned off, the stored magnetic energy is converted into an electrical signal and output to the output terminal of the converter 10 through the first freewheeling module 13.
The first switch module 12 is configured to be turned off or turned on in response to a control signal output by the first controller 15.
The first flywheel module 13 is configured to transmit the converted electrical signal output by the first energy storage and conversion module 11 to the output terminal of the converter 10.
The first filtering module 14 is configured to filter the electrical signal output by the output terminal of the converter 10.
It should be noted that the converter shown in fig. 2 is an existing Boost converter, and the circuit structure of the converter may be the circuit structure of an existing Boost converter, for example: as shown in fig. 3, the first energy storage and conversion module 11 includes: an inductor L11 and a resistor R11; one end of the inductor L11 is connected to the input end of the first energy storage and conversion module 11, the other end of the inductor L11 is connected to one end of the resistor R11, and the other end of the resistor R11 is connected to the output end of the first energy storage and conversion module 11. The first switch module 12 includes a transistor Q11, the transistor Q11 includes a first pole, a second pole, and a control pole, the first pole of the transistor Q11 is connected to the first terminal of the first switch module 12, the second pole of the transistor Q11 is connected to the second terminal of the first switch module 12, and the control pole of the transistor Q11 is connected to the control terminal of the first switch module 12. The first freewheel module 13 includes a diode D11, an anode of the diode D11 is connected to the input of the first freewheel module 13, and a cathode of the diode D11 is connected to the output of the first freewheel module 13. The first filtering module 14 comprises: a capacitor C11 and a resistor R12; one end of the capacitor C11 is connected to the input end of the first filter module 14, the other end of the capacitor C11 is connected to one end of the resistor R12, and the other end of the resistor R11 is connected to the output end of the first filter module 14. Further, the inverter 10 includes: the low-pass filter module on the input side comprises a resistor R13 and a capacitor C12, one end of the resistor R13 is connected with the positive pole of the direct-current input end V1_ dc, the other end of the resistor R13 is connected with one pole of the capacitor C12, and the other pole of the capacitor C12 is connected with the negative pole of the direct-current input end V1_ dc. An output load Rload1 is connected in parallel across the output of the converter 10.
The first controller 15 generates and outputs a control signal of the PWM wave to the control terminal of the first switch module 12, and controls the on-time or off-time of the first switch module 12, so that the input current and the input voltage of the converter 10 can work in the same phase, thereby implementing the high power factor function of the converter 10.
The first controller 15 obtains the current value of the electric signal output by the first energy storage and conversion module 11 and the output value of the voltage loop of the converter 10; determining a control quantity based on the current value and the voltage loop output value of the electric signal output by the first energy storage and conversion module 11; based on the relationship between the control quantity and the preset PWM carrier, a control signal is generated and output to the control terminal of the first switching module 12. The current value of the electrical signal output by the first energy storage and energy conversion module 11 is the current value of the electrical signal flowing through the inductor L11 in fig. 3, and the output value of the voltage loop of the converter 10 is the error value between the output voltage of the converter 10 and the set voltage thereof. Therefore, the control strategy of the converter provided by the embodiment does not need to sample the input voltage and the phase angle of the alternating-current side power grid, does not need a current inner ring, and greatly simplifies the control of the converter.
In an embodiment, the determining the control amount based on the current value and the voltage loop output value of the electrical signal output by the first energy storage and conversion module 11 includes:
the first stored energy isThe energy conversion module 11 outputs the ratio of the current value iL of the electrical signal and the voltage loop output value Vloop as the control quantity Doff. Namely, it is
。
The control amount Doff is actually a duty ratio of the off time of the first switching module 12 to the switching period thereof, and is described in detail below by taking the Boost converter shown in fig. 3 as an example.
As shown in fig. 4, fig. 4 is a schematic diagram of the switching period of the transistor Q11 and the current iL in the inductor L11 in fig. 3. The formula of the duty ratio can be obtained as follows:
the relationship between input and output can be deduced as
Wherein
， 
. Wherein,
is the output voltage of the converter 10 and,
is the input voltage of the converter 10 and,
for the on-time of the transistor Q11,
for the off time of the transistor Q11,
is the switching period of transistor Q11.
After the current iL of the inductor L11 passes through the low-pass filter module on the input side, the result is that the input current Iin is substantially equal to:
. The input impedance of the Boost converter is then:
it can be seen that the input impedance Zin is related to the output voltage Vout, the inductor current iL, and the duty ratio Doff corresponding to the off time of the transistor Q11, and in actual operation, since the output voltage Vout is a fixed value, the input impedance analysis can be considered to be related to Doff and iL.
As shown in fig. 5, fig. 5 is a schematic diagram of the switching cycle of the first switching module 12, and the control of the converter is realized by directly controlling the time of Toff in the switching cycle on the PWM modulation strategy, where Toff is obtained by Vc × Tsw sent out by the control loop, that is, the control loop is a closed loop
Vc is a control amount of the off time Toff. From the input impedance point of view:
the denominator iL is the current of the inductor L11, wherein
When the output of the voltage loop is not considered,
，
is the inductance of the inductor L11. Therefore, an imaginary variable of the impedance of the inductor L11 is inevitably introduced, and therefore, in order to make the input impedance of the converter constant, the influence of iL on the input impedance must be eliminated. By establishing the following relation between the control quantity Vc of Toff and iLWherein Vloop is the output value of the voltage loop for controlling the output voltage to be stable
。
The input impedance is then:
。
it can be seen that: when the Doff is designed to be iL/Vloop, the wave is sent by the PWM strategy, the Doff control quantity is compared with the PWM carrier wave, the time that the Doff control quantity is smaller than the PWM carrier wave is taken as the Toff, and the time that the Doff control quantity is larger than the PWM carrier wave is taken as the Ton. The input impedance of the BOOST converter has been converted to
The voltage loop is no longer related to the current on the inductor L11 or the inductor L11, the Vout output voltage is constant in steady-state operation, is a quantity with a slow change speed, and can be close to a fixed value, and the voltage loop output Vloop is also a quantity with a slow change speed in steady-state operation, and can be considered as a direct current quantity to be analyzed, so that the input impedance of the Boost converter at the moment is constant, and is a resistive characteristic.
Under the condition of acquiring the control quantity, generating and outputting a control signal to the control end of the first switch module 12 based on the relationship between the control quantity and the preset PWM carrier, including:
multiplying the control quantity by the preset switching cycle time to obtain a core control quantity;
in each period of the preset PWM carrier, a time period in which the preset PWM carrier is greater than or equal to the core control amount is taken as an off time period of the first switch module 12, and a time period in which the preset PWM carrier is less than the core control amount is taken as an on time period of the first switch module 12;
based on the turn-off time period and the turn-on time period of the first switch module 12, generating and outputting a control signal of each period to a control end of the first switch module 12;
the control signal for controlling the first switch module 12 to turn off is generated in the off period of the first switch module 12, and the control signal for controlling the first switch module 12 to turn on is generated in the on period of the first switch module 12.
In summary, when the control quantity is
In the meantime, the input impedance of the converter 10 is a resistive characteristic, that is, the input current and the input voltage work in the same phase, so that the control of high power factor is realized.
Example two:
the three-phase three-level vienna rectifier can be equivalently regarded as three single-phase three-level Boost converters to work in parallel, so the control strategy of the controller of the vienna rectifier can be the control strategy of the controller of the converter in the first embodiment.
For a vienna rectifier, the control of a high power factor rectifier is to be realized, and the main purpose of the control is to track the phase and frequency of an input current and the voltage phase of a power grid at an alternating current input end, so that the input impedance of the rectifier is equal to a resistance, and the in-phase operation of the input current and the input voltage is realized. Therefore, if the input impedance of the rectifier can be made to be resistive, rather than inductive or capacitive, the input current can automatically follow the phase and frequency of the grid voltage. From impedance analysis, both inductive impedance and capacitive impedance exist imaginary numbers, and only resistive impedance is real number, so that the imaginary number component in the transfer function of the input impedance of the rectifier can be eliminated in control, and the characteristic that the input impedance presents resistance can be achieved.
Referring to fig. 6 and 7, fig. 6 is a schematic structural diagram of a vienna rectifier 20 according to an embodiment, and fig. 7 is a schematic circuit diagram of the vienna rectifier according to the embodiment, where the vienna rectifier 20 provided in this embodiment is used for converting an input three-phase alternating current into a first direct current and a second direct current having the same voltage value. The vienna rectifier 20 includes: a second energy storage and conversion module 21, a second switching module 22, a second freewheel module 23, a second filtering module 24 and a second controller 25. The second energy storage and conversion module 21 includes a first energy storage and conversion unit 211, a second energy storage and conversion unit 212, and a third energy storage and conversion unit 213, where the first energy storage and conversion unit 211 is configured to receive a-phase alternating current in three-phase alternating current output from the first alternating current input terminal V1_ ac, the second energy storage and conversion unit 212 is configured to receive a B-phase alternating current in three-phase alternating current output from the second alternating current input terminal V2_ ac, and the third energy storage and conversion unit 213 is configured to receive a C-phase alternating current in three-phase alternating current output from the third alternating current input terminal V3_ ac. The second switching module 22 includes a first switch 221, a second switch 222, and a third switch 223, the first switch 221 is connected to the first energy storage and energy conversion unit 211, the second switch 222 is connected to the second energy storage and energy conversion unit 212, and the third switch 223 is connected to the third energy storage and energy conversion unit 213. The second freewheel module 23 includes a first freewheel unit 231, a second freewheel unit 232, and a third freewheel unit 233, the first freewheel unit 231 is connected with the first energy storage and energy conversion unit 211, the second freewheel unit 232 is connected with the second energy storage and energy conversion unit 212, and the third freewheel unit 233 is connected with the third energy storage and energy conversion unit 213. The second filtering module 24 includes a first filtering unit 241 and a second filtering unit 242, the first filtering unit 241 is connected in parallel to the first output terminal of the vienna rectifier 20, the second filtering unit 242 is connected in parallel to the second output terminal of the vienna rectifier 20, and a neutral line is connected between the first output terminal and the second output terminal of the vienna rectifier 20.
The first energy storage and conversion unit 211 is configured to convert the a-phase alternating current input from the first alternating current input terminal V1_ ac into magnetic energy for storage when the first switch 221 is turned on; when the first switch 221 is turned off, the stored magnetic energy is converted into an electrical signal and is output to the first output terminal or the second output terminal of the vienna rectifier 20 through the first freewheeling unit 231.
The second energy storage and conversion unit 212 is configured to convert the B-phase alternating current input from the second alternating current input terminal V2_ ac into magnetic energy for storage when the second switch 222 is turned on; when the second switch 222 is turned off, the stored magnetic energy is converted into an electrical signal and is output to the first output terminal or the second output terminal of the vienna rectifier 20 through the second freewheeling unit 232.
The third energy storage and conversion unit 213 is configured to convert the C-phase alternating current input from the third alternating current input terminal V3_ ac into magnetic energy for storage when the third switch 223 is turned on; when the third switch 223 is turned off, the stored magnetic energy is converted into an electrical signal and is output to the first output terminal or the second output terminal of the vienna rectifier 20 through the third freewheeling unit 233.
The first switch 221, the second switch 222 and the third switch 223 respectively comprise a first end, a second end and a control end, the first end of the first switch 221 is connected with the output end of the first energy storage and energy conversion unit 211, the first end of the second switch 222 is connected with the output end of the second energy storage and energy conversion unit 212, and the first end of the third switch 223 is connected with the output end of the third energy storage and energy conversion unit 213; second terminals of the first switch 221, the second switch 222 and the third switch 223 are all connected to the neutral line of the vienna rectifier 20; the control terminals of the first switch 221, the second switch 222 and the third switch 223 are all connected to the second controller 25.
As shown in fig. 7, the first energy storage and conversion unit 211 includes an inductor L21 and a resistor R21, one end of the inductor L21 is connected to the input end of the first energy storage and conversion unit 211, the other end of the inductor L21 is connected to one end of the resistor R21, and the other end of the resistor R21 is connected to the output end of the first energy storage and conversion unit 211. The second energy storage and conversion unit 212 includes an inductor L22 and a resistor R22, and the third energy storage and conversion unit 213 includes an inductor L23 and a resistor R23, wherein the circuit structures of the second energy storage and conversion unit 212 and the third energy storage and conversion unit 213 are the same as those of the first energy storage and conversion unit 211, and are not described herein again.
It should be noted that the output ends of the first energy storage and energy conversion unit 211, the second energy storage and energy conversion unit 212, and the third energy storage and energy conversion unit 213 are respectively connected to a first current sampler a21, a second current sampler a22, a third current sampler a23, and a low pass filter LPF 2. The first current sampler A21 is used for acquiring a current signal of an A-phase alternating current; the second current sampler A22 is used for acquiring a current signal of the B alternating current; the third current sampler A23 is used for acquiring a current signal of the C-phase alternating current; the low pass filter LPF2 is configured to filter the current signal of the a-phase alternating current, the current signal of the B-phase alternating current, and the current signal of the C-phase alternating current, and output a current value of the a-phase alternating current, an alternating value of the B-phase alternating current, and an alternating value of the C-phase alternating current to the second controller 25.
The first switch 221 includes: transistor Q21 and transistor Q22; transistor Q21 includes a first pole, a second pole, and a control pole, and transistor Q22 includes a first pole, a second pole, and a control pole; a first electrode of the transistor Q21 is connected to the first terminal of the first switch 221, a second electrode of the transistor Q21 is connected to the second electrode of the transistor Q22, and a first electrode of the transistor Q22 is connected to the second terminal of the first switch 221; the control electrodes of the transistor Q21 and the transistor Q22 are both connected to the control terminal of the first switch 221.
The second switch 222 includes: a transistor Q23 and a fourth transistor Q24; the transistor Q23 comprises a first pole, a second pole and a control pole, and the fourth transistor Q24 comprises a first pole, a second pole and a control pole; a first pole of the transistor Q23 is connected to the first terminal of the second switch 222, a second pole of the transistor Q23 is connected to the second pole of the fourth transistor Q24, and a first pole of the fourth transistor Q24 is connected to the second terminal of the second switch; the control electrodes of the transistor Q23 and the fourth transistor Q24 are both connected to the control terminal of the second switch 222.
The third switch 223 includes: a fifth transistor Q25 and a sixth transistor Q26; the fifth transistor Q25 includes a first pole, a second pole and a control pole, and the sixth transistor Q26 includes a first pole, a second pole and a control pole; a first pole of the fifth transistor Q25 is connected to the first terminal of the third switch 223, a second pole of the fifth transistor Q25 is connected to the second pole of the sixth transistor Q26, and a first pole of the fifth transistor Q25 is connected to the second terminal of the third switch 223; the gates of the fifth transistor Q25 and the sixth transistor Q26 are both connected to the control terminal of the third switch 223.
The first freewheeling unit 231 includes a diode D21 and a diode D22, an anode of the diode D21 and a cathode of the diode D22 are connected to the output terminal of the first energy storage and conversion unit 211, a cathode of the diode D21 is connected to the first output terminal Vm1 of the vienna rectifier 20, and an anode of the diode D22 is connected to the second output terminal Vm2 of the vienna rectifier 20. The second freewheeling unit 232 includes a diode D23 and a diode D24, and the third freewheeling unit 233 includes a diode D25 and a diode D26, wherein the circuit structures of the second freewheeling unit 232, the third freewheeling unit 233 and the first freewheeling unit 231 are the same, and are not repeated here.
The first filtering unit 241 includes: the rectifier comprises a capacitor C21 and a resistor R22, wherein one end of the capacitor C21 is connected with a first output end Vm1 of the vienna rectifier 20, the other end of the capacitor C21 is connected with one end of a resistor R22, and the other end of the resistor R22 is connected with the neutral line of the vienna rectifier 20. The second filtering unit 242 includes: the rectifier comprises a capacitor C22 and a resistor R23, wherein one end of the capacitor C22 is connected with a second output end Vm2 of the vienna rectifier 20, the other end of the capacitor C22 is connected with one end of a resistor R23, and the other end of the resistor R23 is connected with the neutral line of the vienna rectifier 20.
In the present application, the transistor is a three-terminal transistor, and three terminals of the transistor are a control electrode, a first electrode, and a second electrode. The transistor may be a bipolar transistor, a field effect transistor, or the like. For example, when the transistor is a bipolar transistor, the control electrode of the transistor refers to a base electrode of the bipolar transistor, the first electrode may be a collector or an emitter of the bipolar transistor, and the corresponding second electrode may be an emitter or a collector of the bipolar transistor; when the transistor is a field effect transistor, the control electrode refers to a gate electrode of the field effect transistor, the first electrode may be a drain electrode or a source electrode of the field effect transistor, and the corresponding second electrode may be a source electrode or a drain electrode of the field effect transistor.
The second controller 25 is configured to obtain a current value of the a-phase alternating current, a current value of the B-phase alternating current, a current value of the C-phase alternating current, and an output value of the voltage loop of the vienna rectifier 20; determining a first control quantity, a second control quantity and a third control quantity based on the current value of the A-phase alternating current, the current value of the B-phase alternating current, the current value of the C-phase alternating current and the output value of the voltage loop of the vienna rectifier 20; and generating and outputting a first control signal, a second control signal and a third control signal based on the relation between the first control quantity, the second control quantity and the third control quantity and the preset PWM carrier wave.
The first control amount, the second control amount and the third control amount of the vienna rectifier 20 will be described in detail below, and since the first control amount, the second control amount and the third control amount are calculated in a similar manner, the first control amount is taken as an example in the present embodiment and described in detail.
The ratio of the current value of the A-phase alternating current to the output value of the voltage loop is used as a first control quantity, namely the first control quantity
，
Is the current signal of the a-phase alternating current on the inductor L11,
vloop is the output value of the voltage loop of the vienna rectifier 20 for the transfer function of the low pass filter LPF 2.
In some embodiments, the first control amount may be too large or too small, which may cause the maximum or minimum duty ratio of the PWM output to damage the transistor, so the present embodiment performs the clipping process on the first control amount, and in this embodiment, the first control amount is greater than 0 and less than 1, and preferably greater than or equal to 0.05 and less than or equal to 0.995. The second control amount and the third control amount also require the same clipping process, and are not described here again.
In one embodiment, generating and outputting the first control signal based on the relationship between the first control quantity and the preset PWM carrier includes:
and multiplying the first control quantity by the preset switching cycle time to obtain a first core control quantity. In each period of the preset PWM carrier, taking a time period in which the preset PWM carrier is greater than or equal to the first core control amount as an off time period of the first switch 221, and taking a time period in which the preset PWM carrier is less than the first core control amount as an on time period of the first switch 221; based on the off-period and the on-period of the first switch 221, first control signals of each cycle are generated and output to the control terminal of the first switch 221. Here, the first control signal for controlling the first switch 221 to be turned off is generated during the off period of the first switch, and the first control signal for controlling the first switch 221 to be turned on is generated during the on period of the first switch 221.
The generation manner of the second control signal and the third control signal is the same as that of the first control signal, and is not described in detail here.
In this embodiment, the control strategy of the second controller 25 can be implemented by using a digital circuit or an analog circuit, the present invention is not limited to an implementation manner, please refer to fig. 8, fig. 8 is a control block diagram of the second controller 25 of the vienna rectifier 20 according to an embodiment, the embodiment also takes the first control signal as an example for description, and the second controller 25 includes: an absolute value taking device Abs1, a divider 1, a limiter Satusion 1, a scaler TBPRD1, a PWM carrier generator PWM _ ramp and a comparator relative Operator 1; an input terminal of an absolute value device Abs1, an input terminal of an absolute value device Abs1 receives, an output terminal of an absolute value device Abs1 is connected to a first input terminal of a divider 1, a second input terminal of the divider 1 inputs Vloop, an output terminal of the divider 1 is connected to an input terminal of a limiter Saturation1, an output terminal of the limiter Saturation1 is connected to an input terminal of a scaler TBPRD1, an output terminal of the scaler TBPRD1 is connected to a first input terminal of a comparator relative Operator1, a second input terminal of a comparator relative Operator1 is connected to an output terminal of a PWM carrier generator PWM _ ramp, and an output terminal of the comparator relative Operator1 outputs a first control signal PWM _ a.
The above is a block diagram of generation control of the first control signal, and the second control signal and the third control signal are the same as the first control signal, and the second controller 25 further includes: absolute value taker Abs2, divider Divide2, limiter Saturation2, scaler TBPRD2, comparator related Operator2, absolute value taker Abs3, divider Divide3, limiter Saturation3, scaler TBPRD3, comparator related Operator3, where absolute value taker Abs2 receives
The absolute value taking device Abs3 receives
The output terminal of the comparator relative Operator2 outputs the first control signal PWM _ B, the output terminal of the comparator relative Operator3 outputs the first control signal PWM _ C, and the connection mode of the above devices is the same as that of the device generating the first control signal, which is not repeated herein.
Referring to fig. 9, fig. 9 is a simulation diagram of the vienna rectifier 20, where A, B, C in CH1 are three-phase input voltage signals, DoffA, DoffB, and DoffC in CH2 are first control quantity, second control quantity, and third control quantity output by the second controller 25, PWM _ ramp is a preset PWM carrier, and PWM _ A, PWM _ B, PWM _ C in CH3 is control signals of the first switch, the second switch, and the third switch.
Referring to fig. 10, at the time shown in fig. 10, phase a is a positive direction, phase B is immediately about to cross zero, phase C is in a negative direction region, and exactly corresponds to phase a with the largest Doff and the next phase B with the smallest Doff, the PWM driving signal output is logic with PWM carrier greater than Doff, and then the first switch, the second switch, and the third switch are controlled respectively, so as to implement the control strategy of the Vienna rectifier.
Referring to fig. 11, in fig. 11, CH1 is a voltage signal (a is phase a, B is phase B, and C is phase C) of an input three-phase ac power, CH2 is a current signal of the three-phase input ac power, CH3 is a dc-side output voltage signal Vout, and CH4 is a voltage signal between the arms.
The direct current side controller can use a proportional integral PI controller, outputs a Vloop signal, and controls the input impedance of the system together with the iL. It is known that when the dc side load power increases, the output voltage decreases, so the PI controller increases the output of Vloop, and decreases the input impedance of the system according to the control formula Vout/Vloop, and increases the input current and power, thereby achieving power balance.
Example three:
in the second embodiment, as shown in fig. 7, the vienna rectifier provided in this embodiment is configured to convert three-phase ac power input from the ac side thereof into a first dc power and a second dc power having the same voltage value, and output the first dc power and the second dc power through the dc side, where the dc side includes a first output terminal Vm1 for outputting the first dc power and a second output terminal Vm2 for outputting the second dc power, a load resistor Rload21 is connected in parallel to the first output terminal Vm1, and a load resistor Rload22 is connected in parallel to the second output terminal; theoretically, the load resistors Rload21 and Rload22 have the same resistance, but in practical cases, when the load resistors Rload21 and Rload22 are not equal, the voltages of the first dc power and the second dc power are unbalanced.
On the basis of the second embodiment, the high-power-factor rectification is realized, and the input impedance is compensated through the output value of the voltage-equalizing ring on the direct-current side of the vienna rectifier, so that the input current and the power are influenced, and the output voltage balance on the direct-current side is realized.
The detailed description of the energy storage and conversion module, the switching module, the freewheeling module, and the filtering module of the Vienna rectifier is given in the second embodiment, and will not be repeated here.
On the basis of the controller provided in the second embodiment, the second controller 25 provided in this embodiment is further configured to obtain a current value of the a-phase alternating current, a current value of the B-phase alternating current, a current value of the C-phase alternating current, an output value of a voltage loop of the vienna rectifier, and an output value of a voltage equalizer of a dc-side output voltage of the vienna rectifier; determining a first control quantity, a second control quantity and a third control quantity based on the current value of the A-phase alternating current, the current value of the B-phase alternating current, the current value of the C-phase alternating current, the output value of a voltage ring of the vienna rectifier 20 and the equalizing ring output value of the direct-current side output voltage of the vienna rectifier; and generating and outputting a first control signal, a second control signal and a third control signal based on the relation between the first control quantity, the second control quantity and the third control quantity and the preset PWM carrier wave.
The first control quantity, the second control quantity and the third control quantity of the vienna rectifier are explained in detail below, and since the first control quantity, the second control quantity and the third control quantity are calculated in a similar manner, the first control quantity is taken as an example for detailed explanation in the embodiment.
Taking the ratio of the sum of the current value of the A-phase alternating current and the output value of the equalizing ring to the output value of the voltage ring as a first control quantity, namely the first control quantity
，
Is the current signal of the a-phase alternating current on the inductor L11,
diff is the equalizer output of the dc side output voltage of the vienna rectifier 20, and Vloop is the output of the voltage loop of the vienna rectifier 20, which is the transfer function of the low pass filter LPF 2.
In some embodiments, the first control amount may be too large or too small, which may cause the maximum or minimum duty ratio of the PWM output to damage the transistor, so the present embodiment performs the clipping process on the first control amount, and in this embodiment, the first control amount is greater than 0 and less than 1, and preferably greater than or equal to 0.05 and less than or equal to 0.995. The second control amount and the third control amount also require the same clipping process, and are not described here again.
In one embodiment, generating and outputting the first control signal based on the relationship between the first control quantity and the preset PWM carrier includes:
and multiplying the first control quantity by the preset switching cycle time to obtain a first core control quantity. In each period of the preset PWM carrier, a time period in which the preset PWM carrier is greater than or equal to the first core control amount is used as an off time period of the first switch 221, and a time period in which the preset PWM carrier is less than the first core control amount is used as an on time period of the first switch 221; based on the off-period and the on-period of the first switch 221, first control signals of each cycle are generated and output to the control terminal of the first switch 221. Wherein, the first control signal for controlling the first switch 221 to be turned off is generated in the off period of the first switch, and the first control signal for controlling the first switch 221 to be turned on is generated in the on period of the first switch 221.
The generation manner of the second control signal and the third control signal is the same as that of the first control signal, and is not described in detail here.
In this embodiment, the control strategy of the controller can be implemented by using a digital circuit or an analog circuit, the present invention is not limited to an implementation manner, please refer to fig. 12, fig. 12 is a control block diagram of the controller of the vienna rectifier according to an embodiment, the embodiment also takes the first control signal as an example for description, and the second controller 25 includes: an adder ADD1, an absolute value taker Abs1, a divider Divide1, a limiter validation 1, a scaler TBPRD1, a PWM carrier generator PWM _ ramp, and a comparator relative Operator 1; adder ADD1 input
And Diff, the output end of the adder ADD1 is connected with the input end of an absolute value taker Abs1, the output end of the absolute value taker Abs1 is connected with the first input end of a divider 1, the second input end of the divider 1 is input Vloop, the output end of the divider 1 is connected with the input end of a limiter Saturation1, the output end of the limiter Saturation1 is connected with the input end of a comparator TBPRD1, the output end of the comparator TBPRD1 is connected with the first input end of a comparator relative Operator1, and the second input end of a comparator relative Operator1 is connected with the output end of a PWM carrier generator PWM _ ramp.
The above is a block diagram of the generation control of the first control signal, and the second control signal and the third control signal are the same as the first control signal, and the second controller 25 further includes: adder ADD2, absolute value taker Abs2, divider Divide2, slicer Saturation2, scaler TBPRD2, comparator relative Operator2, and adder ADD3, absolute value taker Abs3, divider Divide3, slicer Saturation3, ratioAn example TBPRD3 and a comparator relative Operator3, wherein the input of the adder ADD2
And Diff, adder ADD3 inputs
And Diff, the output end of the comparator relative Operator2 outputs PWM _ B, and the output end of the comparator relative Operator3 outputs PWM _ C, which are not described in detail herein.
In this embodiment, as shown in (a) of fig. 13, a grading ring output value Diff of a dc-side output voltage of the vienna rectifier is an output value of a difference between a voltage Vmo1 output by the first output terminal Vm1 and a voltage Vmo2 output by the second output terminal Vm2 in fig. 7 after passing through the zeroth-order keeper ZOH1 and the PI controller 1; as shown in fig. 13 (b), the output value Vloop of the voltage loop of the vienna rectifier is an output value obtained by passing the difference between the output value obtained by passing the sum of the voltage Vmo1 output from the first output terminal Vm1 and the voltage Vmo2 output from the second output terminal Vm2 through the zero-order keeper ZOH2 and the set voltage Vo _ set through the PI controller 2.
Referring to fig. 14, fig. 14 is a simulation diagram of another embodiment of the vienna rectifier, wherein A, B, C in CH1 are three-phase input voltage signals, DiffA, DiffB, DiffC in CH2 are first control quantity, second control quantity, and third control quantity output by the second controller 25, PWM _ ramp is a preset PWM carrier, and PWM _ A, PWM _ B, PWM _ C in CH3 is control signals of the first switch, the second switch, and the third switch.
Referring to fig. 15, fig. 15 shows an operation condition of the vienna rectifier 20 switched from load balancing to a midpoint voltage balancing strategy in which a positive dc bus load is weakened and a negative dc bus load is unchanged. In CH1, Vmo1 represents the positive dc bus voltage, and Vmo2 represents the negative dc bus voltage. In CH2, iLa is the phase A input current signal, Diff is the equalizer ring output value, 0 is output when the load is balanced, and the output is adjusted to-4.2A when the load is unbalanced. In CH3, which is the output of iLa + Diff, it can be seen that the positive peaks are attenuated and the negative peaks are increased, thereby affecting the input impedance at different AC phases. CH4 is the Doff of phase A.
Example four:
the three-phase two-level rectifier can be equivalently regarded as three single-phase three-level Boost converters to work in parallel, so the control strategy for the controller of the three-phase two-level rectifier can be the control strategy for the controller of the converter in the first embodiment.
For a three-phase two-level rectifier, the control of a high power factor rectifier is to be realized, and the main purpose of the realization is to track the voltage phase of a power grid at an alternating current input end on the phase and frequency of input current, so that the input impedance of the rectifier is equal to a resistance, and the in-phase operation of the input current and the input voltage is realized. Therefore, if the input impedance of the rectifier can be made to present resistance, but not inductance or capacitance, the input current can automatically follow the phase and frequency of the network voltage. From impedance analysis, both inductive impedance and capacitive impedance exist imaginary numbers, and only resistive impedance is real number, so that the imaginary number component in the transfer function of the input impedance of the rectifier can be eliminated in control, and the characteristic that the input impedance presents resistance can be achieved.
Referring to fig. 16 and 17, a three-phase two-level rectifier according to an embodiment of the present invention is used for converting an input three-phase ac power into a dc power. The three-phase two-level rectifier 30 provided in the present embodiment includes: a third energy storage and conversion module 31, a third switching module 32, a third filtering module 33 and a third controller 34.
The third energy storage and conversion module 31 comprises a first energy storage and conversion unit 311, a second energy storage and conversion unit 312 and a third energy storage and conversion unit 313, wherein the first energy storage and conversion unit 311 is used for receiving a-phase alternating current in three-phase alternating current output by the first alternating current input end V1_ ac, the second energy storage and conversion unit 312 is used for receiving B-phase alternating current in three-phase alternating current output by the second alternating current input end V2_ ac, and the third energy storage and conversion unit 313 is used for receiving C-phase alternating current in three-phase alternating current output by the third alternating current input end V3_ ac.
In an embodiment, the first energy storage and conversion unit 311 includes an inductor L31 and a resistor R31, one end of the inductor L31 is connected to the input end of the first energy storage and conversion unit 311, the other end of the inductor L31 is connected to one end of the resistor R31, and the other end of the resistor R31 is connected to the output end of the first energy storage and conversion unit 311. The second energy storage and energy conversion unit 312 includes an inductor L32 and a resistor R32, and the third energy storage and energy conversion unit 313 includes an inductor L33 and a resistor R33, wherein the circuit structures of the second energy storage and energy conversion unit 312 and the third energy storage and energy conversion unit 313 are the same as the first energy storage and energy conversion unit 311, and are not described in detail herein.
It should be noted that the output ends of the first energy storage and energy conversion unit 311, the second energy storage and energy conversion unit 312, and the third energy storage and energy conversion unit 313 are respectively connected with a first current sampler a31, a second current sampler a32, a third current sampler a33, and a low pass filter LPF 3. The first current sampler A31 is used for acquiring a current signal of an A-phase alternating current; the second current sampler A32 is used for acquiring a current signal of the B-phase alternating current; the third current sampler A33 is used for acquiring a current signal of the C-phase alternating current; the low pass filter LPF3 is configured to filter the current signal of the a-phase alternating current, the current signal of the B-phase alternating current, and the current signal of the C-phase alternating current, and output a current value of the a-phase alternating current, an alternating value of the B-phase alternating current, and an alternating value of the C-phase alternating current to the third controller 34.
The third switch module 32 includes a first upper bridge switch 321, a first lower bridge switch 322, a second upper bridge switch 323, a second lower bridge switch 324, a third upper bridge switch 325, and a third lower bridge switch 326. The first upper bridge switch 321 comprises a first end, a second end and a control end, the first lower bridge switch 322 comprises a first end, a second end and a control end, the first end of the first upper bridge switch 321 is connected with the anode of the output end of the rectifier, the second end of the first upper bridge switch 321 is connected with the first end of the first lower bridge switch 322, and the second end of the first lower bridge switch 322 is connected with the cathode of the output end of the rectifier; the second terminal of the first upper bridge switch 321 and the first terminal of the first lower bridge switch 322 are connected to receive a-phase alternating current; the second upper bridge switch 323 comprises a first end, a second end and a control end, the second lower bridge switch 324 comprises a first end, a second end and a control end, the first end of the second upper bridge switch 323 is connected with the anode of the output end of the rectifier, the second end of the second upper bridge switch 323 is connected with the first end of the second lower bridge switch 324, and the second end of the second lower bridge switch 324 is connected with the cathode of the output end of the rectifier; a second terminal of the second upper bridge switch 323 and a first terminal of the second lower bridge switch 324 are connected to receive a B-phase alternating current; the third upper bridge switch 325 comprises a first end, a second end and a control end, the third lower bridge switch 326 comprises a first end, a second end and a control end, the first end of the third upper bridge switch 325 is connected with the anode of the output end of the rectifier, the second end of the third upper bridge switch 325 is connected with the first end of the third lower bridge switch 326, and the second end of the third lower bridge switch 326 is connected with the cathode of the output end of the rectifier; the second terminal of the third upper bridge switch 325 and the first terminal of the third lower bridge switch 326 are connected to receive C-phase alternating current.
In an embodiment, the first upper bridge switch 321, the first lower bridge switch 322, the second upper bridge switch 323, the second lower bridge switch 324, the third upper bridge switch 325 and the third lower bridge switch 326 are all transistors, the first upper bridge switch 321 is a transistor Q31, a first pole of the transistor Q31 is connected to a first end of the first upper bridge switch 321, a second pole of the transistor Q31 is connected to a second end of the first upper bridge switch 321, and a control pole of the transistor Q31 is connected to a control end of the first upper bridge switch 321; the first lower bridge switch 322 is a transistor Q32, a first pole of the transistor Q32 is connected to a first end of the first lower bridge switch 322, a second pole of the transistor Q32 is connected to a second end of the first lower bridge switch 322, and a control pole of the transistor Q32 is connected to a control end of the first lower bridge switch 322; the second upper bridge switch 323 is a transistor Q33, a first pole of the transistor Q33 is connected to a first end of the second upper bridge switch 323, a second pole of the transistor Q33 is connected to a second end of the second upper bridge switch 323, and a control pole of the transistor Q33 is connected to a control end of the second upper bridge switch 323; the second lower bridge switch 324 is a transistor Q34, a first pole of the transistor Q34 is connected to a first end of the second lower bridge switch 324, a second pole of the transistor Q34 is connected to a second end of the second lower bridge switch 324, and a control pole of the transistor Q34 is connected to a control end of the second lower bridge switch 324; the third upper bridge switch 325 is a transistor Q35, a first pole of the transistor Q35 is connected to a first end of the third upper bridge switch 325, a second pole of the transistor Q35 is connected to a second end of the third upper bridge switch 325, and a control pole of the transistor Q35 is connected to a control end of the third upper bridge switch 325; the third lower bridge switch 326 is a transistor Q36, a first terminal of a transistor Q36 is connected to a first terminal of the third lower bridge switch 326, a second terminal of a transistor Q36 is connected to a second terminal of the third lower bridge switch 326, and a control terminal of a transistor Q36 is connected to a control terminal of the third lower bridge switch 326.
The third filtering module 33 is connected in parallel to the output end of the three-phase two-level rectifier 30, and is configured to perform filtering processing on a signal output by the output end of the three-phase two-level rectifier 30.
The third filtering module 33 includes a capacitor C31 and a resistor R34; one end of the capacitor C31 is connected to the positive electrode of the output terminal of the three-phase two-level rectifier 30, the other end of the capacitor C31 is connected to one end of the resistor R34, and the other end of the resistor R34 is connected to the negative electrode of the output terminal of the three-phase two-level rectifier 30.
The third controller 34 is configured to obtain a current value of the a-phase alternating current, a current value of the B-phase alternating current, a current value of the C-phase alternating current, and an output value of the voltage loop of the three-phase two-level rectifier 30; determining a first control quantity, a second control quantity and a third control quantity based on the current value of the A-phase alternating current, the current value of the B-phase alternating current, the current value of the C-phase alternating current and the output value of the voltage loop of the three-phase two-level rectifier 30; and generating and outputting a first control signal, a second control signal and a third control signal based on the relation between the first control quantity, the second control quantity and the third control quantity and the preset PWM carrier wave.
The first control amount, the second control amount and the third control amount of the rectifier are explained in detail below, and since the first control amount, the second control amount and the third control amount are calculated in a similar manner, the first control amount is taken as an example in the present embodiment and explained in detail.
The ratio of the current value of the A-phase alternating current to the output value of the voltage loop is used as a first control quantity, namely the first control quantity
，
Is the current signal of the a-phase alternating current on the inductor L31,
vloop is the output value of the voltage loop of the rectifier, which is the transfer function of the low pass filter LPF 3.
In some embodiments, the first control amount may be too large or too small, which may cause the maximum or minimum duty ratio of the PWM output to damage the transistor, so the present embodiment performs the clipping process on the first control amount, and in this embodiment, the first control amount is greater than 0 and less than 1, and preferably greater than or equal to 0.05 and less than or equal to 0.995. The second control amount and the third control amount also require the same clipping process, and are not described here again.
In one embodiment, generating and outputting the first control signal based on the relationship between the first control quantity and the preset PWM carrier includes:
and multiplying the first control quantity by the preset switching cycle time to obtain a first core control quantity. In each period of the preset PWM carrier, a time period in which the preset PWM carrier is greater than or equal to the first core control amount is taken as an off time period of the first lower bridge switch 322, and a time period in which the preset PWM carrier is less than the first core control amount is taken as an on time period of the first lower bridge switch 322; based on the turn-off time period and the turn-on time period of the first lower bridge switch 322, first control signals of each cycle are generated and output to the control terminal of the first lower bridge switch 322. The first control signal for controlling the first lower bridge switch 322 to be turned off is generated during the turn-off period of the first lower bridge switch 322, and the first control signal for controlling the first lower bridge switch 322 to be turned on is generated during the turn-on period of the first lower bridge switch 322.
The generation manner of the second control signal and the third control signal is the same as that of the first control signal, and is not described in detail here.
In this embodiment, the control strategy of the third controller 34 can be implemented by digital circuit or analog circuit, and the present invention is implemented by using a digital circuit or an analog circuitPlease refer to fig. 18, wherein fig. 18 is a control block diagram of the third controller 34 of the three-phase two-level rectifier 30 according to an embodiment, the embodiment also takes the first control signal as an example for description, and the third controller 34 includes: a divider 1, a limiter Satution 1, a scaler TBPRD1, a comparator relative Operator1 and a PWM carrier generator PWM _ ramp; the divider Divide1 comprises a first input terminal for receiving the current value of the a-phase alternating current
The second input end is used for receiving the voltage loop output value Vloop; the output end of the divider 1 is connected with the input end of the limiter Saturration 1; the output end of the limiter Saturation1 is connected with the input end of the scaler TBPRD 1; the output end of the scaler TBPRD1 is connected with the first input end of a comparator relative Operator 1; a second input terminal of the comparator relative Operator1 is connected to an output terminal of the PWM carrier generator PWM _ ramp, and an output terminal of the comparator relative Operator1 outputs the first control signal PWM _ a.
The above is a block diagram for generating and controlling the first control signal, the second control signal and the third control signal are similar to the first control signal, the third controller 34 further includes a divider 2, a limiter Saturation2, a comparator Operator2, a divider 3, a limiter Saturation3, and a comparator Operator3, wherein the divider 2 is used for receiving a current value of the B-phase alternating current
The divider Divide3 is used for receiving the current value of the C-phase alternating current
And the voltage loop output value Vloop, the output terminal of the comparator relative Operator2 outputs PWM _ B, and the output terminal of the comparator relative Operator3 outputs PWM _ C, which are not described in detail herein.
In this embodiment, the third controller 34 is further configured to output a fourth control signal, a fifth control signal and a sixth control signal, where the fourth control signal and the first control signal are complementary signals, the fifth control signal and the second control signal are complementary signals, and the sixth control signal and the third control signal are complementary signals; the fourth control signal is used to control the first upper bridge switch 321 to be turned on or off, the fifth control signal is used to control the second upper bridge switch 323 to be turned on or off, and the sixth control signal is used to control the third upper bridge switch 325 to be turned on or off.
In one embodiment, the first control module further comprises: an inverter; the inverter is configured to invert the first control signal to obtain and output a fourth control signal to the control terminal of the first upper bridge switch 321. Similarly, the second control signal is inverted by an inverter to obtain a fifth control signal, and the third control signal is inverted by an inverter to obtain a sixth control signal.
Referring to fig. 19, fig. 19 is a simulation diagram of the three-phase two-level rectifier 30, in which A, B, C in CH1 are three-phase input voltage signals, DoffA, DoffB, and DoffC in CH2 are first control quantity, second control quantity, and third control quantity output by the third controller 34, PWM _ ramp is a preset PWM carrier, and PWM _ A, PWM _ B, PWM _ C in CH3 is a first control signal, a second control signal, and a third control signal.
Referring to fig. 20, at the time shown in fig. 20, phase a is positive, phase B will cross zero immediately, phase C is in a negative region, which corresponds to phase a having the largest Doff and phase B having the next smallest Doff, and the driving signal output of PWM is logic with PWM carrier greater than Doff, and then the first lower bridge switch, the second lower bridge switch, and the third lower bridge switch are controlled respectively to implement the control strategy of the three-phase two-level rectifier 30.
Referring to fig. 21, in fig. 21, CH1 is a voltage signal (a is phase a, B is phase B, and C is phase C) of an input three-phase alternating current, CH2 is a current signal of the three-phase input alternating current, CH3 is a direct current side output voltage signal Vout, and CH4 is a voltage signal between the arms.
Example five:
the single-phase bridgeless pfc converter can be equivalently regarded as a BOOST converter operating in the switching direction in the L/N phase, and therefore the control strategy for the controller of the single-phase bridgeless pfc converter can be the same as that provided in the first embodiment.
For a single-phase bridgeless power factor correction converter, the control of high power factor is realized, and the main purpose of the realization is to track the phase and frequency of input current with the voltage phase of a power grid at an alternating current input end, namely to enable the input impedance of the converter to be equal to resistance, so as to realize the in-phase operation of the input current and the input voltage. Therefore, if the input impedance of the converter can be made to present resistance instead of inductance or capacitance, the input current can automatically follow the phase and frequency of the network voltage. From impedance analysis, both inductive impedance and capacitive impedance exist imaginary numbers, and only resistive impedance is real number, so that the imaginary number component in the transfer function of the input impedance of the converter can be eliminated in control, and the characteristic that the input impedance presents resistance can be achieved.
Referring to fig. 22 and 23, a single-phase bridgeless pfc converter 40 according to an embodiment of the present invention includes: a fourth energy storage and conversion module 41, a fourth switching module 42, a fourth filtering module 43 and a fourth controller 44.
The fourth energy storage and conversion module 41 includes a first energy storage and conversion unit 411 and a second energy storage and conversion unit 412; the first energy storage and conversion unit 411 and the second energy storage and conversion unit 412 are both used for receiving alternating current output by the alternating current power grid V _ ac.
In an embodiment, the first energy storage and conversion unit 411 includes an inductor L41 and a resistor R41, one end of the inductor L41 is connected to the input end of the first energy storage and conversion unit 411, the other end of the inductor L41 is connected to one end of the resistor R41, and the other end of the resistor R41 is connected to the output end of the first energy storage and conversion unit 411. The second energy storage and conversion unit 412 includes an inductor L42 and a resistor R42, wherein the circuit structure of the second energy storage and conversion unit 412 is the same as that of the first energy storage and conversion unit 411, and therefore detailed description thereof is omitted.
It should be noted that the output ends of the first energy storage and conversion unit 411 and the second energy storage and conversion unit 412 are respectively connected to the first current sampler a41, the second current sampler a42, and the low pass filter. The first current sampler A41 and the second current sampler A42 are used for acquiring current signals of alternating current; the low pass filter is configured to filter the current signal of the alternating current and output the current value of the alternating current to the fourth controller 44.
The fourth switching module 42 includes: the bridge arm comprises a first bridge arm unit, a second bridge arm unit and a third bridge arm unit; the first bridge arm unit, the second bridge arm unit and the third bridge arm unit are respectively connected with an alternating current power grid and used for converting alternating current output by the alternating current power grid into direct current. The first bridge arm unit comprises a first upper bridge switch Q41 and a first lower bridge switch Q42, the first upper bridge switch Q41 and the first lower bridge switch Q42 are both transistors, the first end of the first upper bridge switch Q41 is connected with the output end Vo _ sen of the single-phase bridgeless power factor correction converter 40, the second end of the first upper bridge switch Q41 is connected with the first end of the first lower bridge switch Q42, the second end of the first lower bridge switch Q42 is connected with the ground, the second end of the first upper bridge switch Q41 and the first end of the first lower bridge switch Q42 intersect at a point, and the point is connected with the output end of the first energy storage and energy conversion unit 411; the control terminals of the first upper bridge switch Q41 and the first lower bridge switch Q42 are both connected to the output terminal of the fourth controller 44. The second bridge arm unit comprises a second upper bridge switch Q43 and a second lower bridge switch Q44, both the second upper bridge switch Q43 and the second lower bridge switch Q44 are transistors, the first end of the second upper bridge switch Q43 is connected to the output Vo _ sen of the single-phase bridgeless power factor correction converter 40, the second end of the second upper bridge switch Q43 is connected to the first end of the second lower bridge switch Q44, the second end of the second lower bridge switch Q44 is connected to ground, the second end of the second upper bridge switch Q43 and the first end of the second lower bridge switch Q44 intersect at a point, and the point is connected to the output end of the second energy storage and energy conversion unit 412; the control terminals of the second upper bridge switch Q43 and the second lower bridge switch Q44 are both connected to the output terminal of the fourth controller 44. The third bridge arm unit comprises a third upper bridge switch Q45 and a third lower bridge switch Q46, the third upper bridge switch Q45 and the third lower bridge switch Q46 are both transistors, the first end of the third upper bridge switch Q45 is connected with the output end Vo _ sen of the single-phase bridgeless power factor correction converter 40, the second end of the third upper bridge switch Q45 is connected with the first end of the third lower bridge switch Q46, the second end of the third lower bridge switch Q46 is connected with the ground, and the second end of the third upper bridge switch Q45 and the first end of the third lower bridge switch Q45 intersect at a point which is connected with an alternating current power grid and is used for directly receiving alternating current; the control terminals of the third upper bridge switch Q45 and the third lower bridge switch Q46 are both connected to the ac power grid, and are turned on or off according to the phase change of the ac power grid.
The fourth filtering module 43 is connected in parallel to the output terminal of the single-phase bridgeless pfc converter 40, and is configured to perform filtering processing on a signal output by the output terminal of the single-phase bridgeless pfc converter 40.
The fourth filtering module 43 includes a capacitor C41 and a resistor R44; one end of the capacitor C41 is connected to the positive electrode of the output terminal of the three-phase two-level rectifier 30, the other end of the capacitor C41 is connected to one end of the resistor R44, and the other end of the resistor R44 is connected to the negative electrode of the output terminal of the single-phase bridgeless power factor correction converter 40.
The fourth controller 44 is used for obtaining the current value of the alternating current and the output value of the voltage loop of the single-phase bridgeless power factor correction converter 40; determining a control quantity based on the current value of the alternating current and the output value of the voltage loop of the single-phase bridgeless power factor correction converter 40; and generating and outputting a first control signal and a second control signal based on the relation between the control quantity and the first preset PWM carrier wave and the second preset PWM carrier wave respectively.
The ratio of the current value of the alternating current to the output value of the voltage loop is used as a control quantity, i.e. a control quantity
，
Is a current signal for the alternating current,
for the transfer function of the low pass filter, Vloop is the output value of the voltage loop.
In some embodiments, the control amount may be too large or too small, which may cause the maximum or minimum duty ratio of the PWM output to damage the transistor, so the present embodiment performs the clipping process on the control amount, and in this embodiment, the control amount is a value greater than 0 and less than 1, and preferably a value greater than or equal to 0.05 and less than or equal to 0.995.
In one embodiment, generating and outputting the first control signal and the second control signal based on the relationship between the control quantity and the first preset PWM carrier and the second preset PWM carrier respectively comprises:
and multiplying the control quantity by the preset switching period time to obtain the core control quantity. In each period of the first preset PWM carrier, a time period in which the first preset PWM carrier is greater than or equal to the first core control amount is taken as an off time period of the first upper bridge switch Q41 or the first lower bridge switch Q42, and a time period in which the first preset PWM carrier is less than the first core control amount is taken as an on time period of the first upper bridge switch Q41 or the first lower bridge switch Q42; generating a first control signal for each cycle based on an off-period and an on-period of the first upper bridge switch Q41 or the first lower bridge switch Q42; when the voltage value of the voltage signal on the live wire of the alternating-current power grid is greater than or equal to the voltage value of the voltage signal on the zero wire of the alternating-current power grid, outputting a first control signal to the control end of the first lower bridge switch Q42, and outputting a low-level constant signal to the control end of the first upper bridge switch Q41 to turn off the first upper bridge switch Q41, wherein the first lower bridge switch Q42 is controlled by the first control signal to be turned on or off, and the first upper bridge switch Q41 is in a completely turned-off state; when the voltage value of the voltage signal on the live wire of the alternating current power grid is smaller than the voltage value of the voltage signal on the zero wire of the alternating current power grid, the first control signal is output to the control end of the first upper bridge switch Q41, a low-level constant signal is output to the control end of the first lower bridge switch Q42 to turn off the first lower bridge switch Q42, at the moment, the first upper bridge switch Q41 is controlled by the first control signal to be switched on or switched off, and the first lower bridge switch Q42 is in a completely switched-off state.
In each period of the second preset PWM carrier, a time period in which the second preset PWM carrier is greater than or equal to the core control amount is taken as an off time period of the second upper bridge switch Q43 or the second lower bridge switch Q44, and a time period in which the second preset PWM carrier is less than the core control amount is taken as an on time period of the second upper bridge switch Q43 or the second lower bridge switch Q44; generating a second control signal for each cycle based on the turn-off period and the turn-on period of the second upper bridge switch Q43 or the second lower bridge switch Q44; when the voltage value of the voltage signal on the live wire of the alternating-current power grid is greater than or equal to the voltage value of the voltage signal on the zero wire of the alternating-current power grid, outputting a second control signal to the control end of the second lower bridge switch Q44, and outputting a low-level constant signal to the control end of the second upper bridge switch Q43; when the voltage value of the voltage signal on the live wire of the alternating current power grid is smaller than that of the voltage signal on the zero wire of the alternating current power grid, the second control signal is output to the control end of the second upper bridge switch Q43, and a low-level constant signal is output to the control end of the second lower bridge switch Q44.
In this embodiment, the control strategy of the fourth controller 44 can be implemented by using a digital circuit or an analog circuit, the present invention is not limited to an implementation manner, please refer to fig. 24, fig. 24 is a control block diagram of the fourth controller 44 of the single-phase bridgeless pfc converter 40 according to an embodiment, the embodiment also takes the first control signal as an example for description, and the fourth controller 44 includes: a divider 1, a limiter Saturation1, a scaler TBPRD1, a comparator Relational Operator1, a first PWM carrier generator PWM _ ramp a, a first converter Switch1 and a second converter Switch 2; the divider Divide1 comprises a first input terminal for receiving a current value of the alternating current
The second input end is used for receiving the voltage loop output value Vloop; the output end of the divider 1 is connected with the input end of a slicer Saturation 1; the output end of the limiter Saturation1 is connected with the input end of the scaler TBPRD 1; the output end of the scaler TBPRD1 is connected with the first input end of a comparator relative Operator 1; the second input terminal of the comparator relative Operator1 is connected with the first PWM carrier generator PWM _ ramPAThe output end of the comparator relative Operator1 outputs a first control signal PWM _ A; the first converter Switch1 includes a first input terminal connected to the output terminal of the comparator relative Operator1, a second input terminal for receiving a low-level Constant signal Constant, a control terminal for receiving the first conversion control signal AC _ L, and an output terminal for outputting the first control signal PWM _ a or the low-level Constant signal to the control terminal of the first lower bridge Switch Q42; the second Switch2 includes a first input terminal connected to the output terminal of the comparator relative Operator1, a second input terminal for receiving a low-level Constant signal Constant, a control terminal for receiving the second Switch control signal AC _ N, and an output terminal for outputting the first control signal PWM _ a or the low-level Constant signal Constant to the control terminal of the first upper bridge Switch Q41.
The fourth controller 44 further includes: the divider Divide2, the limiter Saturation2, the scaler TBPRD2, the comparator Relational Operator2, the second PWM carrier generator PWM _ ramp B, the third converter Switch3 and the fourth converter Switch4, the principle of generating the second control signal PWM _ B is the same as that of the first control signal PWM _ a, and details are not repeated here.
As shown in fig. 25, the voltage signal Vac _ sen of the AC power output by the AC power grid outputs a first conversion control signal AC _ L and a second conversion control signal AC _ N respectively after passing through the Constant comparator to Constant and the inverter logic Operator.
Referring to fig. 26, the single-phase bridgeless pfc converter 40 provided in the above embodiment further provides a control method of the single-phase bridgeless pfc converter, including the following steps:
step 1001: the current value of the alternating current and the output value of the voltage loop of the converter are obtained.
Step 1002: the control amount is determined based on a current value of the alternating current and an output value of a voltage loop of the inverter.
Step 1003: generating and outputting a first control signal and a second control signal based on the relation between the control quantity and a first preset PWM carrier wave and a second preset PWM carrier wave respectively; the first control signal is used for controlling the connection or disconnection of the first bridge arm unit, and the second control signal is used for controlling the connection or disconnection of the second bridge arm unit.
Referring to fig. 27, fig. 27 is a simulation diagram of the single-phase bridgeless pfc converter 40, where CH1 is ac power on an ac power grid, CH2 is output dc power, CH3 is a first preset PWM carrier and a second preset PWM carrier, CH4 is a first control signal and a second control signal, and CH5 is bridge arm voltage of the first bridge arm unit and bridge arm voltage of the second bridge arm unit.
The present invention has been described in terms of specific examples, which are provided to aid understanding of the invention and are not intended to be limiting. For a person skilled in the art to which the invention pertains, several simple deductions, modifications or substitutions may be made according to the idea of the invention.
Claims (7)
1. A transducer, comprising: the energy storage and energy conversion module, the switch module, the follow current module, the filtering module and the controller; the switch module comprises a first end, a second end and a control end;
the energy storage and conversion module is used for converting direct current input by the direct current input end of the converter into magnetic energy for storage when the switch module is switched on; when the switch module is turned off, the stored magnetic energy is converted into an electric signal and is output to the output end of the converter through the follow current module;
the switch module is used for responding to a control signal output by the controller to be switched off or switched on;
the follow current module is used for transmitting the converted electric signal output by the energy storage and conversion module to the output end of the converter;
the filtering module is used for filtering the electric signal output by the output end of the converter;
the controller is used for acquiring the current value of the electric signal output by the energy storage and conversion module and the output value of the voltage ring of the converter; determining a control quantity based on the current value of the electric signal output by the energy storage and conversion module and the voltage loop output value; generating and outputting the control signal to a control end of the switch module based on the relation between the control quantity and a preset PWM carrier wave;
the generating and outputting the control signal to the control end of the switch module based on the relationship between the control quantity and the preset PWM carrier includes:
multiplying the control quantity by the preset switching cycle time to obtain a core control quantity;
in each period of the preset PWM carrier, taking the time period when the preset PWM carrier is greater than or equal to the core control quantity as the turn-off time period of the switch module, and taking the time period when the preset PWM carrier is less than the core control quantity as the turn-on time period of the switch module;
generating and outputting control signals of each period to a control end of the switch module based on the turn-off time period and the turn-on time period of the switch module;
the control method comprises the steps of generating a control signal for controlling the switch module to be switched off in the switch-off time period of the switch module, and generating a control signal for controlling the switch module to be switched on in the switch-on time period of the switch module.
2. The converter of claim 1, wherein the determining a control quantity based on the current value of the electrical signal output by the energy storage and conversion module and the voltage loop output value comprises:
and taking the ratio of the current value of the electric signal output by the energy storage and energy conversion module to the output value of the voltage loop as a control quantity.
3. The converter according to claim 1 or2, wherein the energy storage and conversion module comprises: an inductor L11 and a resistor R11; one end of the inductor L11 is connected with the input end of the energy storage and energy conversion module, the other end of the inductor L11 is connected with one end of the resistor R11, and the other end of the resistor R11 is connected with the output end of the energy storage and energy conversion unit;
or the switch module comprises a transistor Q11, the transistor Q11 comprises a first pole, a second pole and a control pole, the first pole of the transistor Q11 is connected with the first end of the switch module, the second pole of the transistor Q11 is connected with the second end of the switch module, and the control pole of the transistor Q11 is connected with the control end of the switch module;
alternatively, the freewheel module includes a diode D11; the anode of the diode D11 is connected with the input end of the freewheel module, and the cathode of the diode D11 is connected with the output end of the freewheel module;
alternatively, the filtering module includes: a capacitor C11 and a resistor R12; one end of the capacitor C11 is connected to the input end of the filter module, the other end of the capacitor C11 is connected to one end of the resistor R12, and the other end of the resistor R12 is connected to the output end of the filter module.
4. A vienna rectifier for converting an input three-phase alternating current power into a first direct current power and a second direct current power having the same voltage, the three-phase alternating current power including an a-phase alternating current power, a B-phase alternating current power, and a C-phase alternating current power, the vienna rectifier comprising: a switch module and a controller;
the switch module comprises a first switch, a second switch and a third switch; the first end of the first switch is connected with the input end of the A-phase alternating current, and the second end of the first switch is connected with the neutral line of the vienna rectifier; the first end of the second switch is connected with the input end of the B-phase alternating current, and the second end of the second switch is connected with the neutral line of the vienna rectifier; the first end of the third switch is connected with the input end of the C-phase alternating current, and the second end of the third switch is connected with the neutral line of the vienna rectifier;
the switching module is used for alternately switching on and off through the first switch, the second switch and the third switch under the control of a first control signal, a second control signal and a third control signal output by the controller, so that the vienna rectifier outputs a first direct current and a second direct current; the first control signal is used for controlling the first switch to be turned on or off, the second control signal is used for controlling the second switch to be turned on or off, and the third control signal is used for controlling the third switch to be turned on or off;
the controller is used for acquiring a current value of the A-phase alternating current, a current value of the B-phase alternating current, a current value of the C-phase alternating current and an output value of a voltage ring of the vienna rectifier; determining a first control quantity based on the current value of the A-phase alternating current and the output value of the voltage ring of the vienna rectifier, determining a second control quantity based on the current value of the B-phase alternating current and the output value of the voltage ring of the vienna rectifier, and determining a third control quantity based on the current value of the C-phase alternating current and the output value of the voltage ring of the vienna rectifier; generating and outputting the first control signal based on a relation between the first control quantity and a preset PWM carrier, generating and outputting the second control signal based on a relation between the second control quantity and a preset PWM carrier, and generating and outputting the third control signal based on a relation between the third control quantity and a preset PWM carrier;
the generating and outputting the first control signal based on the relationship between the first control quantity and a preset PWM carrier, the generating and outputting the second control signal based on the relationship between the second control quantity and the preset PWM carrier, and the generating and outputting the third control signal based on the relationship between the third control quantity and the preset PWM carrier include:
multiplying the first control quantity by a preset switching cycle time to obtain a first core control quantity;
in each period of the preset PWM carrier, taking a time period when the preset PWM carrier is greater than or equal to the first core control quantity as a turn-off time period of the first switch, and taking a time period when the preset PWM carrier is less than the first core control quantity as a turn-on time period of the first switch;
generating and outputting first control signals of each period to a control end of the first switch based on the turn-off time period and the turn-on time period of the first switch;
generating a first control signal for controlling the first switch to be switched off in the switching-off time period of the first switch, and generating a first control signal for controlling the first switch to be switched on in the switching-on time period of the first switch;
multiplying the second control quantity by the preset switching cycle time to obtain a second core control quantity;
in each period of the preset PWM carrier, taking a time period when the preset PWM carrier is greater than or equal to the second core control quantity as a turn-off time period of the second switch, and taking a time period when the preset PWM carrier is less than the second core control quantity as a turn-on time period of the second switch;
generating and outputting a second control signal of each period to a control end of the second switch based on the turn-off time period and the turn-on time period of the second switch;
generating a second control signal for controlling the second switch to be switched off in the switching-off time period of the second switch, and generating a second control signal for controlling the second switch to be switched on in the switching-on time period of the second switch;
the generating and outputting the third control signal to the control end of the third switch based on the relationship between the third control quantity and a preset PWM carrier includes:
multiplying the third control quantity by the preset switching cycle time to obtain a third core control quantity;
in each period of the preset PWM carrier, taking a time period when the preset PWM carrier is greater than or equal to the third core control amount as a turn-off time period of the third switch, and taking a time period when the preset PWM carrier is less than the third core control amount as a turn-on time period of the third switch;
generating and outputting a third control signal of each period to a control end of the third switch based on the turn-off time period and the turn-on time period of the third switch;
wherein a third control signal for controlling the third switch to be turned off is generated in an off period of the third switch, and a third control signal for controlling the third switch to be turned on is generated in an on period of the third switch.
5. The vienna rectifier of claim 4, wherein determining a first control amount based on the current value of the A-phase alternating current and the output value of the voltage loop of the vienna rectifier, determining a second control amount based on the current value of the B-phase alternating current and the output value of the voltage loop of the vienna rectifier, and determining a third control amount based on the current value of the C-phase alternating current and the output value of the voltage loop of the vienna rectifier comprises:
taking the ratio of the current value of the A-phase alternating current to the output value of the voltage loop as a first control quantity;
taking the ratio of the current value of the B-phase alternating current to the output value of the voltage loop as a second control quantity;
taking the ratio of the current value of the C-phase alternating current to the voltage loop output value as a third control quantity;
wherein the first control quantity, the second control quantity and the third control quantity all satisfy more than 0 and less than 1.
6. The vienna rectifier of claim 4 or 5, further comprising: the device comprises an energy storage and conversion module, a follow current module and a filtering module;
the energy storage and energy conversion module comprises a first energy storage and energy conversion unit, a second energy storage and energy conversion unit and a third energy storage and energy conversion unit; the freewheel module includes: the device comprises a first follow current unit, a second follow current unit and a third follow current unit;
the first energy storage and energy conversion unit is used for converting A-phase alternating current into magnetic energy for storage when the first switch is switched on; when the first switch is turned off, the stored magnetic energy is converted into an electric signal and is output to a first output end or a second output end of the vienna rectifier through the first freewheeling unit;
the second energy storage and conversion unit is used for converting the B-phase alternating current into magnetic energy for storage when the second switch is switched on; when the second switch is turned off, the stored magnetic energy is converted into an electric signal and is output to the first output end or the second output end of the vienna rectifier through the second freewheeling unit;
the third energy storage and conversion unit is used for converting the C-phase alternating current into magnetic energy for storage when the third switch is switched on; when the third switch is turned off, the stored magnetic energy is converted into an electric signal and is output to the first output end or the second output end of the vienna rectifier through the third freewheeling unit.
7. A vienna rectifier as claimed in claim 4 or 5, further comprising: the current sampling device comprises a first current sampler, a second current sampler, a third current sampler and a low-pass filter;
the first current sampler is used for acquiring a current signal of the A-phase alternating current;
the second current sampler is used for acquiring a current signal of the B-phase alternating current;
the third current sampler is used for acquiring a current signal of the C-phase alternating current;
the low-pass filter is used for filtering the current signal of the A-phase alternating current, the current signal of the B-phase alternating current and the current signal of the C-phase alternating current and then outputting the current value of the A-phase alternating current, the alternating current value of the B-phase alternating current and the alternating current value of the C-phase alternating current to the controller.
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| Application Number | Priority Date | Filing Date | Title |
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| CN202211009960.5A CN117277841A (en) | 2022-06-15 | 2022-06-15 | Three-phase two-level rectifier |
| CN202210670265.7A CN114759811B (en) | 2022-06-15 | 2022-06-15 | Converter and vienna rectifier |
| CN202211009976.6A CN117277842A (en) | 2022-06-15 | 2022-06-15 | Vienna rectifier capable of achieving midpoint balance |
| CN202211009942.7A CN117277840A (en) | 2022-06-15 | 2022-06-15 | Single-phase bridgeless power factor correction converter and control method thereof |
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| CN202210670265.7A CN114759811B (en) | 2022-06-15 | 2022-06-15 | Converter and vienna rectifier |
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| CN202211009976.6A Division CN117277842A (en) | 2022-06-15 | 2022-06-15 | Vienna rectifier capable of achieving midpoint balance |
| CN202211009942.7A Division CN117277840A (en) | 2022-06-15 | 2022-06-15 | Single-phase bridgeless power factor correction converter and control method thereof |
| CN202211009960.5A Division CN117277841A (en) | 2022-06-15 | 2022-06-15 | Three-phase two-level rectifier |
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| CN202211009960.5A Pending CN117277841A (en) | 2022-06-15 | 2022-06-15 | Three-phase two-level rectifier |
| CN202210670265.7A Active CN114759811B (en) | 2022-06-15 | 2022-06-15 | Converter and vienna rectifier |
| CN202211009942.7A Pending CN117277840A (en) | 2022-06-15 | 2022-06-15 | Single-phase bridgeless power factor correction converter and control method thereof |
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| Publication number | Priority date | Publication date | Assignee | Title |
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| CN103595239A (en) * | 2012-08-15 | 2014-02-19 | 珠海格力电器股份有限公司 | Power factor correction circuit and control method thereof |
| CN106059281A (en) * | 2016-07-01 | 2016-10-26 | 安徽亮亮电子科技有限公司 | Power factor correction circuit for large-power LED |
| CN107395090A (en) * | 2017-06-22 | 2017-11-24 | 东南大学 | A kind of high-power High Power Factor drive control device for single-phase linear Stirling motor |
| CN110199463A (en) * | 2016-11-10 | 2019-09-03 | 雷诺股份公司 | Method for controlling the three-phase rectifier of charging equipment vehicle-mounted on electronic or hybrid vehicle |
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| CN104079182B (en) * | 2014-06-18 | 2017-11-21 | 华为技术有限公司 | Inverter system |
| US11258352B2 (en) * | 2019-05-10 | 2022-02-22 | Dell Products L.P. | Systems and methods for fast response and low total harmonic distortion power factor correction |
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| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103595239A (en) * | 2012-08-15 | 2014-02-19 | 珠海格力电器股份有限公司 | Power factor correction circuit and control method thereof |
| CN106059281A (en) * | 2016-07-01 | 2016-10-26 | 安徽亮亮电子科技有限公司 | Power factor correction circuit for large-power LED |
| CN110199463A (en) * | 2016-11-10 | 2019-09-03 | 雷诺股份公司 | Method for controlling the three-phase rectifier of charging equipment vehicle-mounted on electronic or hybrid vehicle |
| CN107395090A (en) * | 2017-06-22 | 2017-11-24 | 东南大学 | A kind of high-power High Power Factor drive control device for single-phase linear Stirling motor |
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| CN117277840A (en) | 2023-12-22 |
| CN117277842A (en) | 2023-12-22 |
| CN117277841A (en) | 2023-12-22 |
| CN114759811A (en) | 2022-07-15 |
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