CN102005955A - Dead zone compensation method based on DSP (Digital Signal Processor) controller - Google Patents
Dead zone compensation method based on DSP (Digital Signal Processor) controller Download PDFInfo
- Publication number
- CN102005955A CN102005955A CN 201010566483 CN201010566483A CN102005955A CN 102005955 A CN102005955 A CN 102005955A CN 201010566483 CN201010566483 CN 201010566483 CN 201010566483 A CN201010566483 A CN 201010566483A CN 102005955 A CN102005955 A CN 102005955A
- Authority
- CN
- China
- Prior art keywords
- current
- dsp
- phase current
- cmpr
- underflow
- Prior art date
- Legal status (The legal status is an assumption and is not a legal conclusion. Google has not performed a legal analysis and makes no representation as to the accuracy of the status listed.)
- Granted
Links
Images
Landscapes
- Inverter Devices (AREA)
Abstract
The invention provides a dead zone compensation method based on a DSP (Digital Signal Processor) controller, comprising the following steps of: firstly configuring a DSP chip to ensure that the comparison value calculated in period interrupt takes an effect after a timer returns to zero, and the comparison value calculated in underflow interrupt takes the effect after the timer reaches a period value; then judging the direction of phase current and calculating the opening point t1 and the closing point t2 of an ideal driving waveform; and finally shifting a comparison register according to the direction of the phase current. The dead zone compensation method realizes full digitization by using a control chip DSP 2812 of the current main-current motor and has more obvious effect than the prior dead zone compensation method.
Description
Technical field
The present invention relates to the power device field.
Background technology
The action of power device has certain turning on and off the time, and two brachium pontis take place to lead directly in order to avoid up and down, adopt the time delay technology, are called the control dead area time.Switching frequency is high more, the dead time effect of the PWM that Dead Time caused (pulse width modulation) inverter is remarkable more: promptly export fundamental voltage amplitude and reduce, harmonic content increases, the output current distortion is serious more, and inverter switching frequency is high more, and dead time effect is remarkable more: promptly export fundamental voltage amplitude and reduce, the harmonic voltage amplitude increases, the output current distortion, the output torque pulsation easily causes motor oscillates in the application scenario of translator.At this problem a lot of different compensation methodes have been proposed, a kind of is to use the control method of space vector that error vector voltage is compensated, it regards error voltage as another voltage vector, and it and given voltage vector is synthesized, in order to the influence of compensation dead band generation, but the control more complicated; Another kind is the mechanism that produces in conjunction with the dead band, and the moment point that turns on and off of switching tube is compensated.At present, dsp controller has been widely used in the inverter control, the programmable dead band control that it carries can be inserted the dead band easily in pwm signal, this paper has proposed a kind of more effective dead area compensation strategy in conjunction with current main-stream motor control chip TSM320F2812 and according to the dead band genesis mechanism, and has verified the validity of this method by asynchronous motor speed-regulating system.
Summary of the invention
Technical problem to be solved by this invention is: a kind of dead-zone compensation method based on dsp controller is provided, and it is equal to ideal and turns on and off moment point according to the principle of the dead time effect moment point that turns on and off to the switching tube that works.This method is more convenient.
The technical solution adopted in the present invention is: a kind of dead-zone compensation method based on dsp controller comprises: at first dsp chip is configured, make the comparison value that calculates in the cycle interruption after timer returns zero, work, and the comparison value that interrupts calculating in underflow after reaching periodic quantity, timer work; Judge the direction of phase current then, and calculate a t that opens of desirable drive waveforms
1With pass breakpoint t
2Carry out shifting processing according to the direction of phase current to comparing register at last.
Advantage of the present invention: realize that with current main-stream motor control chip DSP2812 total digitalization realizes, more obvious than current dead-zone compensation method effect.
Description of drawings
Fig. 1 is a three-phase inverter bridge circuit.
Fig. 2 is the inversion waveform behind the adding dead band.
Fig. 3 is the actual drive waveforms (electric current is greater than 0) that turns on and off behind the dead area compensation.
Fig. 4 is the dead area compensation flow chart.
Fig. 5 is the contrast of conventional method and new method.
Embodiment
The present invention is the mechanism that produces in conjunction with the dead band, and the moment point that turns on and off of switching tube is compensated.
The dead band mechanism of production: as shown in Figure 1, in the bridge type inverse system, two switching tubes under the perfect condition on the same brachium pontis are operated in complementary state, consider the time-delay that turns on and off of device itself, general turn off delay time t
OffGreater than opening time-delay t
On,, need between the PWM drive signal, to add enough Dead Times in order to prevent two bridge arm direct pass up and down.In dsp system, when counter and comparand register coupling, level overturns, if do not consider the time-delay that turns on and off of dead band and device, its ideal waveform is shown in Fig. 2 a, if consider both factors, insert in the drive signal of then last two IGBT (insulated gate bipolar transistor) behind the waveform of dead band up and down shown in the following Fig. 2 b of drive waveforms of two brachium pontis, high level is represented open-minded among the figure, owing to turn on and off time-delay, after adding Dead Time, power device to turn on and off moment point obviously different with perfect condition.
Can be got by Fig. 2, the size of comparator registers has determined the width of effective drive waveforms, but when comparison value very little or very big because the introducing in dead band may make the output significant level lose.
With three-phase inverter bridge circuit a is example mutually, and as shown in Figure 1, T1～T6 is IGBT, and D1～D6 is a fly-wheel diode.If the electric current of flow direction motor winding is a positive direction, the sense of current that flows to inverter is a negative direction.Work as i
a＞0 o'clock, two kinds of operating states are arranged, a kind of is normal operating conditions, on to manage T1 open-minded, following pipe T4 turn-offs, electric current flows through the T1 flow direction motor; And when T1 turn-offs, this moment electric current by under manage antiparallel sustained diode 2 and finish afterflow, the holding current flow direction motor.Work as i
a, two kinds of operating states are equally also arranged at＜0 o'clock: normal T1 turn-offs, and T4 is open-minded, and electric current flows through T4 and forms passage, and when T4 turn-offed, by 1 afterflow of last pipe inverse parallel sustained diode, holding current formed path.
So, work as i according to the dead time effect analysis
a＞0 o'clock, have only last brachium pontis pipe T1 to work, and work as i
a, have only following brachium pontis pipe T4 to work at＜0 o'clock.The target of this paper compensation is how to make the moment point that turns on and off of the switching tube that works be equal to ideal and turn on and off moment point.Must must separate configuration open constantly and turn-off moment point in the ascent stage and the decline stage of triangular carrier like this.In the hardware configuration system of DSP2812, current ripple count mode is set for increasing/subtract counting continuously according to SVPWM seven segmentation waveforms, the fully loaded transportation condition of comparand register is that the value of current counter is 0 or heavy duty when equaling the value of cycle stockpile device, and current ripple timer cycle interrupts and the underflow interruption is all effective.The comparison value that calculates in cycle interruption like this can work after timer returns 0, and the comparison value that interrupts calculating in underflow can work after timer reaches periodic quantity.
The change (is example mutually with a) of compensation rear drive waveform is discussed below in two kinds of situation:
Work as current i
a＞0 o'clock, the T4 pulse can be ignored, if guarantee T1 after overcompensation actual turn on and off a little consistent with turning on and off of desirable drive waveforms.In Fig. 2, the T1 pipe is opened the open some t of moment point than desirable drive waveforms
1Delayed t
d+ t
OnTime, because it reacts on the cycle interruption of a carrier cycle, can be with comparand register CMPR reach, that is:
In cycle interruption, have: CMPR=t
1-T
d-T
On
In like manner in interrupting, underflow has: CMPR=t
2+ T
Off
Consider that then dead band and device turn on and off the time-delay drive waveforms as shown in Figure 3.
Work as i
a＜0 o'clock, T1 not conducting all the time, so the T1 pulse can ignore, as long as guarantee that the T4 pulse duration after overcompensation is consistent with T4 ideal pulse width, promptly has:
In cycle interruption, have: CMPR=t
1-T
Off
In like manner in interrupting, underflow has: CMPR=t
2+ T
On+ T
d
Then interrupt respectively that configuration turns on and off a little, make the moment point that turns on and off be equal to ideal and turn on and off moment point the switching tube that works by cycle interruption and underflow.
By top argumentation as can be known, this dead-zone compensation method depends on the sense of current, in the motor driven systems of SVPWM control, on phase place, differ a power-factor angle by space voltage vector and space current vector, then be easy to obtain the space angle of space current vector, can obtain the direction of every phase phase current under the current space vector of voltage by the relation of coordinate transform, this method can effectively be eliminated the influence of real-time current detection drift.Its realization flow is illustrated in fig. 4 shown below, and in the test, comparison point must be done amplitude limiting processing.
The compensation method of current routine be in an effective impulse compensation because the influence of Dead Time and device time-delay, as shown in Figure 2, promptly a PWM cycle internal loss T=T
d+ T
On-T
Off, promptly by judging that current polarity makes the comparison point reach or the hysteresis of effective switching tube
But this method makes PWM ripple hysteresis ideal waveform.
Embodiment:
Present embodiment IGBT module adopts FS150R12KT3, and motor is 22KW, given dead band T
d=3 μ s, the typical case turns on and off to delay time and is T in the time of 25 ℃
On=0.26 μ s, T
Off=0.42 μ s, carrier frequency f
c=2k, test is at 30H
zCompared behind the conventional dead area compensation shown in the no-load current waveform and harmonic analysis figure below 5, had figure as can be known, adopted its voltage distortion rate of this test method THD=2.4%, its effect is apparent.
Claims (5)
1. dead-zone compensation method based on dsp controller, it is characterized in that comprising: at first dsp chip is configured, make the comparison value that calculates in the cycle interruption after timer returns zero, work, and the comparison value that interrupts calculating in underflow after reaching periodic quantity, timer work; Judge the direction of phase current then, and calculate a t that opens of desirable drive waveforms
1With pass breakpoint t
2Carry out shifting processing according to the direction of phase current to comparing register at last.
2. method according to claim 1 is characterized in that: described dsp chip adopts TMS320F2812.
3. method according to claim 1, it is characterized in that the method that dsp chip is configured is comprised: current ripple count mode is set for increasing/subtract counting continuously according to SVPWM seven segmentation waveforms, the fully loaded transportation condition of comparand register is that the value of current counter is 0 or heavy duty when equaling the value of cycle stockpile device, and current ripple timer cycle interrupts and the underflow interruption is all effective.
4. method according to claim 1, the method that it is characterized in that judging the direction of phase current comprises: the power-factor angle that differs on phase place according to space voltage vector and space current vector, obtain the space angle of space current vector, obtain the direction of every phase phase current under the current space vector of voltage then by the relation of coordinate transform.
5. method according to claim 1 is characterized in that the method for the comparison register being carried out shifting processing comprises:
As phase current i
a＞0 o'clock,
In cycle interruption, have: CMPR=t
1-T
d-T
On,
In interrupting, underflow has: CMPR=t
2+ T
Off
As phase current i
a＜0 o'clock,
In cycle interruption, have: CMPR=t
1-T
Off,
In interrupting, underflow has: CMPR=t
2+ T
On+ T
d
Wherein CMPR is a comparand register, T
dBe Dead Time, T
OnFor opening time-delay, T
OffBe turn off delay time.
Priority Applications (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 201010566483 CN102005955B (en) | 2010-11-30 | 2010-11-30 | Dead zone compensation method based on DSP (Digital Signal Processor) controller |
Applications Claiming Priority (1)
| Application Number | Priority Date | Filing Date | Title |
|---|---|---|---|
| CN 201010566483 CN102005955B (en) | 2010-11-30 | 2010-11-30 | Dead zone compensation method based on DSP (Digital Signal Processor) controller |
Publications (2)
| Publication Number | Publication Date |
|---|---|
| CN102005955A true CN102005955A (en) | 2011-04-06 |
| CN102005955B CN102005955B (en) | 2013-02-27 |
Family
ID=43813086
Family Applications (1)
| Application Number | Title | Priority Date | Filing Date |
|---|---|---|---|
| CN 201010566483 Expired - Fee Related CN102005955B (en) | 2010-11-30 | 2010-11-30 | Dead zone compensation method based on DSP (Digital Signal Processor) controller |
Country Status (1)
| Country | Link |
|---|---|
| CN (1) | CN102005955B (en) |
Cited By (5)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103019774A (en) * | 2012-11-27 | 2013-04-03 | 中国航空工业集团公司第六三一研究所 | Dynamic overloading method for DSP (Digital Signal Processor) |
| CN104811079A (en) * | 2015-05-05 | 2015-07-29 | 上海新时达电气股份有限公司 | Dead-time compensation method and system of open-loop driver |
| CN110912393A (en) * | 2019-11-29 | 2020-03-24 | 中国南方电网有限责任公司超高压输电公司 | Dead zone accurate control method for modular multilevel topology power module |
| CN112769335A (en) * | 2021-02-26 | 2021-05-07 | 许继电源有限公司 | Output current control method and system for multiphase interleaving parallel DC-DC converter |
| CN112904771A (en) * | 2021-01-19 | 2021-06-04 | 厦门欧万精密科技有限公司 | DSP hardware sampling delay compensation method and device based on PWM synchronization mechanism |
Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5706187A (en) * | 1994-10-21 | 1998-01-06 | Nec Corporation | Switching power source circuitry having a current bypass circuit |
| CN1355596A (en) * | 2001-12-14 | 2002-06-26 | 清华大学 | Dead area compensation method for PWM-type frequency-conversion power supply |
-
2010
- 2010-11-30 CN CN 201010566483 patent/CN102005955B/en not_active Expired - Fee Related
Patent Citations (2)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US5706187A (en) * | 1994-10-21 | 1998-01-06 | Nec Corporation | Switching power source circuitry having a current bypass circuit |
| CN1355596A (en) * | 2001-12-14 | 2002-06-26 | 清华大学 | Dead area compensation method for PWM-type frequency-conversion power supply |
Cited By (6)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN103019774A (en) * | 2012-11-27 | 2013-04-03 | 中国航空工业集团公司第六三一研究所 | Dynamic overloading method for DSP (Digital Signal Processor) |
| CN104811079A (en) * | 2015-05-05 | 2015-07-29 | 上海新时达电气股份有限公司 | Dead-time compensation method and system of open-loop driver |
| CN110912393A (en) * | 2019-11-29 | 2020-03-24 | 中国南方电网有限责任公司超高压输电公司 | Dead zone accurate control method for modular multilevel topology power module |
| CN112904771A (en) * | 2021-01-19 | 2021-06-04 | 厦门欧万精密科技有限公司 | DSP hardware sampling delay compensation method and device based on PWM synchronization mechanism |
| CN112769335A (en) * | 2021-02-26 | 2021-05-07 | 许继电源有限公司 | Output current control method and system for multiphase interleaving parallel DC-DC converter |
| CN112769335B (en) * | 2021-02-26 | 2022-08-19 | 许继电源有限公司 | Output current control method and system for multiphase interleaved parallel DC-DC converter |
Also Published As
| Publication number | Publication date |
|---|---|
| CN102005955B (en) | 2013-02-27 |
Similar Documents
| Publication | Publication Date | Title |
|---|---|---|
| CN102005955B (en) | Dead zone compensation method based on DSP (Digital Signal Processor) controller | |
| CN102624276A (en) | Novel dead-zone effect compensation method of AC servo inverter | |
| CN105576993B (en) | A kind of frequency converter dead-time compensation method and compensation system | |
| WO2014156003A1 (en) | Inverter device | |
| CN109698612A (en) | A kind of resonant gate drive circuit suitable for frequency applications | |
| CN201956925U (en) | Inverter circuit for single-phase grid-connected inverter | |
| CN103684031A (en) | Current hysteresis control digital implementation system for PWM rectifier | |
| CN105450068A (en) | IGBT narrow pulse suppression method for three-level converter | |
| CN102611288B (en) | Three-level driving method of gallium nitride power transistor | |
| CN110460019A (en) | A kind of control method and device of bridge converter short-circuit protection | |
| CN102890183B (en) | Method and device for automatic voltage correction of zero crossing detection circuit | |
| Chen et al. | A dead-time compensation method for voltage source inverters | |
| CN104852621A (en) | Switch driving method eliminating dead zone influence of neutral-point-clamped three-level topology switch | |
| CN102570873A (en) | Dead zone compensation method used in voltage space vector pulse width modulation technology | |
| CN102522912B (en) | Bipolar SPWM (Sinusoidal Pulse Width Modulation) type adaptive dead-zone compensation method | |
| CN104092238B (en) | Control method based on the asymmetric deviation of inverter current that modulating wave directly processes | |
| CN103607105B (en) | A kind of dead time compensation control method and system | |
| CN101789739A (en) | Method for controlling phase shifting stagger angle of doubly salient motor | |
| CN102035425B (en) | Method for controlling inverter circuit of single-phase grid-connected inverter | |
| CN105375808B (en) | A kind of optimal Five-phase inverter space vector modulation systems of switching loss and method | |
| CN101383563B (en) | SPWM controller based on FPGA | |
| CN111756287A (en) | Dead zone compensation method suitable for permanent magnet motor control based on current prediction | |
| CN103607160A (en) | Current chopping controller and achievement method | |
| CN108540026B (en) | Silicon carbide/gallium nitride MOSFET-based permanent magnet synchronous motor drive control real-time voltage regulating circuit | |
| CN102684581A (en) | Control method of driving duty ratio of permanent magnet motor |
Legal Events
| Date | Code | Title | Description |
|---|---|---|---|
| C06 | Publication | ||
| PB01 | Publication | ||
| C10 | Entry into substantive examination | ||
| SE01 | Entry into force of request for substantive examination | ||
| C14 | Grant of patent or utility model | ||
| GR01 | Patent grant | ||
| CF01 | Termination of patent right due to non-payment of annual fee |
Granted publication date: 20130227 Termination date: 20211130 |
|
| CF01 | Termination of patent right due to non-payment of annual fee |