CN109842577B - Channel quality determination method under high dynamic situation - Google Patents
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Abstract
The invention relates to a channel quality measuring method under a high dynamic situation, which comprises the following steps: acquiring current frame data, wherein the current frame data comprises pilot frequency subcarriers, data auxiliary subcarriers and data subcarriers; decoding the pilot frequency sub-carrier and carrying out first channel estimation to obtain a first estimation value; carrying out decoding reconstruction and second channel estimation on the data auxiliary subcarriers to obtain a second estimation value; obtaining a third estimated value according to the first estimated value and the second estimated value; obtaining the effective signal-to-noise ratio of the current frame according to the first estimation value, the second estimation value and the third estimation value; and carrying out modulation coding mode selection on the next frame data according to the effective signal-to-noise ratio of the current frame. The channel quality measuring method provided by the invention reduces the influence of the high dynamic property of the mobile ad hoc network on the channel estimation in the prior art, and improves the throughput performance and reliability of the communication system.
Description
Technical Field
The invention belongs to the field of wireless communication, and particularly relates to a channel estimation method under a high dynamic situation.
Background
The performance of a wireless communication system is greatly affected by the radio channel. In the field of mobile ad hoc networks, due to factors such as the movement of nodes and the reflection of the surrounding environment, the propagation path between a transmitter and a receiver is very complex, and thus frequency selective fading and fast fading can occur in the signal during transmission. In coherent detection of an OFDM (Orthogonal frequency division Multiplexing) system, a channel needs to be estimated, and the accuracy of channel estimation directly affects the performance of the whole system. In order to accurately recover a transmission signal at a receiving end, people adopt various measures to resist the influence of multipath effect on a transmission signal, and the realization of a channel estimation technology needs to know information of a wireless channel, namely Channel State Information (CSI), such as channel order, doppler shift, multipath delay or impulse response of the channel. Therefore, channel parameter estimation is a key technology for implementing a wireless communication system. Whether detailed channel information can be obtained or not is an important index for measuring the performance of a wireless communication system, so that a transmitting signal can be correctly demodulated at a receiving end. Therefore, the research on the channel parameter estimation algorithm is a significant work.
Channel State Information (CSI) is typically obtained by using pilot training symbols, which are known to both the transmitter and the receiver for channel estimation and decoding by channel compensation at the receiver. In a mobile ad hoc network applying the OFDM technology, channel estimation has a close relationship with the structure of a physical layer frame and the insertion of a pilot scheme. Channel estimation based on training symbols can generally provide better performance. The known training sequence is sent, initial channel estimation is carried out at a receiving end, and when useful information data is sent, a judgment updating is carried out by utilizing the initial channel estimation result, so that the real-time channel estimation is completed. Channel estimation based on pilot symbols can obtain the channel estimation result of the pilot position by inserting known pilot symbols into the transmitted useful data, and then the channel estimation result of the useful data position is obtained by interpolation by using the channel estimation result of the pilot position, thus completing the channel estimation.
However, because the high dynamics of the mobile ad hoc network seriously affects channel estimation, too many pilot subcarriers are inserted in the frequency domain or too many pilot symbols are inserted in the time domain for channel estimation, so that the throughput performance of the communication system is greatly lost, and in one packet, a small number of pilot subcarriers and pilot symbols cannot provide accurate channel estimation, and the system reliability is low.
Disclosure of Invention
In order to solve the above problems in the prior art, the present invention provides a method for measuring channel quality under high dynamic conditions. The technical problem to be solved by the invention is realized by the following technical scheme:
a method for measuring channel quality under a high dynamic scene comprises the following steps:
acquiring current frame data, wherein the current frame data comprises pilot frequency subcarriers, data auxiliary subcarriers and data subcarriers;
decoding the pilot frequency sub-carrier and carrying out first channel estimation to obtain a first estimation value;
carrying out decoding reconstruction and second channel estimation on the data auxiliary subcarriers to obtain a second estimation value;
obtaining a third estimated value according to the first estimated value and the second estimated value;
obtaining the effective signal-to-noise ratio of the current frame according to the first estimation value, the second estimation value and the third estimation value;
and carrying out modulation coding mode selection on the next frame data according to the effective signal-to-noise ratio of the current frame.
In one embodiment of the present invention, the frequency spacing between two adjacent data-assisted sub-carrier frequencies in the current frame data is smaller than the coherence bandwidth.
In an embodiment of the present invention, the number of data-assisted subcarriers in the current frame data is:
wherein, taumaxFor maximum multipath delay spread of the channel, NpilotIs the number of pilot subcarriers, NdataIs the number of data subcarriers.
In an embodiment of the present invention, decoding the pilot subcarriers and performing a first channel estimation to obtain a first estimation value includes:
decoding the pilot frequency sub-carrier, if the pilot frequency sub-carrier is judged not to be decoded correctly, judging that the sending of the current frame data fails, and re-receiving the current frame data; and if the pilot frequency subcarrier is judged to be decoded correctly, performing first channel estimation on the decoded pilot frequency subcarrier to obtain a first estimation value.
In one embodiment of the present invention, the first estimated value is:
wherein, Y [ k ]]For the received signal of the k pilot sub-carrier, X k]Is the transmitted signal of the k pilot sub-carrier.
Is the channel estimation value of the k pilot sub-carrier.
In one embodiment of the present invention, decoding reconstruction and second channel estimation are performed on the data-aided subcarriers to obtain a second estimation value; the method comprises the following steps:
decoding the data auxiliary subcarrier, recoding and modulating the obtained data, and reconstructing the data of a transmitting party;
and performing second channel estimation on the reconstructed data of the sender to obtain a second estimation value.
In one embodiment of the present invention, the second estimated value is:
wherein: y isdata_pro[k]For the received signal of the k-th auxiliary data sub-carrier, Xdata_pro[k]For the reconstructed transmission signal after decoding of the kth auxiliary data subcarrier signal,
is the channel estimate for the kth secondary data subcarrier.
In an embodiment of the present invention, obtaining the effective snr of the current frame according to the first estimation value, the second estimation value, and the third estimation value includes:
respectively obtaining a first effective signal-to-noise ratio, a second effective signal-to-noise ratio and a third effective signal-to-noise ratio according to the first estimation value, the second estimation value and the third estimation value;
and obtaining the effective signal-to-noise ratio of the current frame according to the first effective signal-to-noise ratio, the second effective signal-to-noise ratio and the third effective signal-to-noise ratio.
In an embodiment of the present invention, the effective snr of the current frame is:
SNReff＝λ1*SNReff_pilot+λ2*SNReff_data_pro+λ3*SNReff_data
wherein the SNReff_pilotFor the first effective signal-to-noise ratio, SNReff_data_proFor the second effective signal-to-noise ratio, SNReff_dataFor a third effective signal-to-noise ratio, λ1，λ2，λ3Respectively representing corresponding partial effective signal-to-noise ratiosAnd satisfy
Compared with the prior art, the invention has the beneficial effects that:
the invention provides a channel quality determination method under a high dynamic situation, which is based on the design of a physical layer frame structure of a mobile ad hoc network of an 802.11p standard, and assists channel estimation and updating of a channel estimation value through data symbols carried by a low-bit-rate Turbo code, so that channel compensation is more accurately performed in a decoding stage, and the channel state quality determination method under the scheme is provided, a basis is provided for the selection of a modulation coding mode of next frame data, the influence of high dynamics of the mobile ad hoc network on channel estimation in the prior art is reduced, and the throughput performance and reliability of a communication system are improved.
Drawings
Fig. 1 is a structural design diagram of a mobile ad hoc network physical layer frame according to an embodiment of the present invention;
FIG. 2 is a schematic diagram of a data-aided sub-carrier frequency domain interpolation scheme according to an embodiment of the present invention;
FIG. 3 is a schematic diagram of a data auxiliary symbol time domain insertion method according to an embodiment of the present invention;
fig. 4 is a schematic diagram of a time-frequency domain insertion method for data-aided sub-carriers (symbols) according to an embodiment of the present invention;
fig. 5 is a schematic flow chart of a channel quality measurement method under a high dynamic scenario according to an embodiment of the present invention.
Detailed Description
The present invention will be described in further detail with reference to specific examples, but the embodiments of the present invention are not limited thereto.
Example one
In the invention, the Channel State Information (CSI) is expressed by a signal-to-noise ratio (SNR) and is used for evaluating the channel quality of an adaptive modulation and coding system in the mobile ad hoc network.
The invention is realized based on the 802.11P standard. 802.11 is a standard for wireless network communications defined by IEEE (Institute of Electrical and Electronics Engineers) The Institute of Electrical and Electronics Engineers). 802.11p (also known as WAVE, Wireless Access in the Vehicular Environment) is a communication protocol extended by IEEE 802.11 standard, and is mainly used for Wireless communication of Vehicular electronics.
In this embodiment, a frame structure of a physical layer of the mobile ad hoc network is designed based on an 802.11p standard, the physical layer uses an Orthogonal Frequency Division Multiplexing (OFDM) technology, and a constellation mapping scheme includes BPSK, QPSK, and 16 QAM. The channel coding uses Turbo code, the code rate is selected from 1/2, 1/3 and 2/3, and the frame structure is shown in fig. 1. Wherein, the Training Symbol is a Training Symbol, the signaling Symbol is a marked modulation coding mode, and the OFDM Symbol is a carried data Symbol.
In the present embodiment, the value of the data symbol is 183. The detailed information of each symbol is explained below. The Training Symbol 1 is 10 repeated short Training sequences, each short sequence is 1.6us in duration, the total duration is 16us, the Training Symbol 2 is two long Training sequences plus a protection prefix, the duration is 16us, the subcarrier spacing of OFDM is 156.25kHz, the durations of Signals and OFDM Symbol i (i ═ 1,2,3,4 … 183) are both 8us in duration, including 6.4us of data and 1.6us of cyclic prefix, so the duration of the entire physical frame is 1.5 ms.
One OFDM symbol includes 53 subcarriers, numbered 1 to 53, in the frequency domain, of which 4 are pilot subcarriers, numbered 6, 20, 34, 48, 27 are dc subcarriers, and the rest are data subcarriers. For frequency selective fading channels and fast fading channels, channel estimation under this frame structure relies solely on the channel estimation results of the training symbols for channel compensation of the entire frame, which is obviously unreliable. To deal with this problem, low rate Turbo codes (e.g., code rate 1/3), low order modulation (e.g., BPSK) protected data subcarriers (or OFDM data symbols) are periodically inserted in the frequency domain (or time domain), and for convenience of description, these data subcarriers (symbols) are referred to herein as data auxiliary subcarriers (data auxiliary symbols). The channel estimation value is updated through the data auxiliary subcarriers (symbols), so that the channel change can be better tracked under the conditions of fast fading and frequency selective fading, thereby being beneficial to correct demodulation of data, and simultaneously being basically in line with the physical layer protocol of 802.11.
There are three ways of inserting data-aided subcarriers (symbols): frequency domain interpolation, time domain interpolation, and time-frequency domain interpolation, respectively. The three insertion methods will be described below with reference to the structure of the physical layer frame designed in fig. 1.
The frequency domain insertion means that in addition to the original pilot frequency sub-carrier, the auxiliary data sub-carrier is periodically inserted into each following OFDM symbol at a certain frequency interval, including the pilot frequency sub-carrier of all data symbols in the frame, and the inserted frequency interval
The number of data-aided subcarriers is:
wherein, taumaxFor maximum delay spread, NpilotIs the number of pilot subcarriers, NdataFor the number of data subcarriers, the spacing between two adjacent data-assisted subcarriers is less than the coherence bandwidth, and the spacing includes the spacing between the pilot subcarrier and the data-assisted subcarrier. As shown in fig. 2, part a is the original pilot subcarrier, part B is the data subcarrier protected by the low-bit-rate and low-order modulation, i.e., the data auxiliary subcarrier, and the rest is the data subcarrier. The frequency interval between A and B is the frequency interval Sf。
The time domain insertion means that in addition to the original training symbols, a plurality of OFDM symbols are inserted periodically in the frame at intervals of data auxiliary symbols, and the insertion time interval is
I.e. the time interval of part D in fig. 3, where fDopplerIs the maximum doppler shift. Such asAs shown in fig. 3, T1 and T2, i.e., C, indicate training symbols, D indicates data auxiliary symbols, and the rest is data symbols.
The time-frequency domain insertion combines the above two insertion methods, similar to the insertion method of the trellis pilot, except that not the pilot, but the data auxiliary symbols and subcarriers are inserted. The conditions to be satisfied in the frequency domain and the time domain are
As shown in fig. 4, the horizontal axis is a time axis, the vertical axis is a frequency axis, part E represents a pilot subcarrier, part F represents an auxiliary data signal, the rest is a data symbol, and the first and second columns from the left are training symbols.
In this embodiment, a first insertion mode is selected, see the frequency-domain insertion mode in fig. 2, where the pilot subcarriers are labeled a and the data-aided subcarriers are labeled B, and these subcarriers are used for carrying information and aiding channel estimation and tracking.
Periodically inserting 1/3Turbo codes with low code rate and BPSK protected data auxiliary subcarriers in a frequency domain, thereby ensuring that channel estimation is updated in time and information of the data auxiliary subcarriers is correctly demodulated;
and then carrying out 2/3 code rate Turbo coding on other data subcarriers of the whole packet, and carrying out data mapping on 16QAM or even 64QAM so as to improve the throughput of the system.
In this embodiment, the number of pilot subcarriers NpilotIs 4, the number of data subcarriers NdataIs 48. The number of data-aided subcarriers is:
the data auxiliary sub-carrier adopts 1/3 code rate and BPSK mapping mode, the data sub-carrier adopts 16QAM mapping mode, no channel coding exists, and the percentage ratio of the throughput performance of the channel loss is
But is howeverIt may be possible to trade off reliable channel estimation and frame error rate (typically 0.1) to meet reliability requirements.
The following data streams are interleaved, IFFT (inverse fast fourier transform), CP (cyclic prefix) processed (only baseband processing of the channel is involved for clarity of presentation of the invention), finally noisy, and subject to fast fading and frequency selective fading.
An embodiment of the present invention provides a method for measuring channel quality under a high dynamic scenario, which is mainly implemented according to the following steps:
s1: acquiring current frame data, wherein the current frame data comprises pilot frequency subcarriers, data auxiliary subcarriers and data subcarriers;
after the time-frequency synchronization is carried out on the receiving party, CP (code division protocol) removal, FFT (fast Fourier transform) and de-interleaving are carried out on the obtained information, and the data of the current frame channel are obtained. When the receiving side obtains data information, channel estimation is generally performed using Least Squares (LS), Minimum Mean Square Error (MMSE) algorithm. DFT (discrete fourier transform) based channel estimation techniques can improve the performance of LS or MMSE channel estimation. In the present embodiment, the LS estimation algorithm is taken as an example for detailed description.
S2: decoding the pilot frequency sub-carrier and carrying out first channel estimation to obtain a first estimation value;
after pilot frequency subcarrier information is obtained, Turbo decoding is carried out on the pilot frequency subcarrier information to obtain a decoded signal Yl[k]，Yl[k]Denotes a signal on the kth subcarrier of the ith OFDM (1, 2) symbol.
Judging whether the pilot frequency subcarrier decoding is correct or not, if the pilot frequency subcarrier cannot be decoded correctly, judging that the frame data transmission fails, discarding the acquired data, and requiring a sender to retransmit the current frame data so as to obtain accurate information and improve the subsequent calculation precision; if the pilot frequency sub-carrier is decoded correctly, the first channel estimation is carried out on the decoded pilot frequency sub-carrier to obtain a first estimation value, namely an estimation value of a pilot frequency sub-carrier channel.
Let the pilot sub-carrier channel estimate be
The cost function is:
where H denotes a matrix transpose.
To minimize the cost function, the above cost function is related to
Is 0, i.e.:
wherein denotes a complex conjugate.
Can obtain
Namely to obtain
Wherein
Which represents the LS channel estimate value, is,-1representing the inversion, a first estimated value is obtained as:
wherein, Y [ k ]]For the received signal of the k pilot sub-carrier, X k]Is the transmitted signal of the k pilot sub-carrier.
The channel estimation value of the k pilot sub-carrier is
Elements of a channel estimation matrix.
S3: carrying out decoding reconstruction and second channel estimation on the data auxiliary subcarriers to obtain a second estimation value;
and similarly, decoding the data auxiliary subcarrier by using an LS algorithm, recoding and modulating the obtained data, and reconstructing the data of the transmitting party. The reconstructed data is unknown to the receiving side, but the probability of being correctly demodulated is very high because the data auxiliary sub-carrier has the protection of a Turbo code with a low code rate and a low-order modulation mode, so the reconstructed data is considered to be correct. And carrying out second channel estimation on the data obtained by reconstruction to obtain a second estimation value, namely the estimation value of the data auxiliary subcarrier channel, thereby realizing the tracking of the fast time-varying and frequency selective channel. The second estimate is:
wherein, Ydata_pro[k]For the received signal of the kth data auxiliary subcarrier, Xdata_pro[k]For the transmitted data reconstructed after the decoding of the kth data-aided sub-carrier signal, i.e. the correctly decoded mapped complex signal,
is the channel estimate for the kth secondary data subcarrier.
S4: obtaining a third estimated value according to the first estimated value and the second estimated value;
since the insertion interval of the data auxiliary sub-carrier in the frequency domain is smaller than the coherence bandwidth of the channel, the channel estimation value of other data sub-carriers is directly obtained through interpolation. The first channel estimation value and the second channel estimation value are subjected to LS (least squares, this example) spline interpolation by DFT technology to obtain the estimation value of the data subcarrier channel
I.e. the third estimate.
S5: and obtaining the effective signal-to-noise ratio of the current frame according to the first estimation value, the second estimation value and the third estimation value.
Carrying out equalization on each estimated value to construct a reference signal so as to obtain the signal-to-noise ratio of each subcarrier; and mapping the signal-to-noise ratio (SNR) of each subcarrier by using an exponential effective signal-to-noise ratio mapping (EESM) algorithm to obtain the effective SNR of the current frame. In this embodiment, the snr calculation method uses a constellation diagram-based method, that is:
Calculating SNR of the pilot subcarriers by using the first estimated value, and mapping the SNR on the pilot subcarriers by an EESM algorithm to obtain a first effective SNR (signal to noise ratio)eff_pilot；
Calculating SNR of the data auxiliary sub-carrier by using the second estimated value, and mapping the SNR on the data auxiliary sub-carrier by an EESM algorithm to obtain a second effective SNR (signal to noise ratio)eff_data_pro；
Calculating SNR of the data subcarriers by using the third estimated value, and mapping SNR on other data subcarriers by using an EESM algorithm to obtain a third effective SNR (signal to noise ratio)eff_data；
Weighting by the above obtained 3 effective snr to obtain the channel quality measurement for describing the frame, where the effective snr for measuring the channel quality in the current frame duration is:
SNReff＝λ1*SNReff_pilot+λ2*SNReff_data_pro+λ3*SNReff_data
wherein λ1，λ2，λ3Respectively, representing the weights of the corresponding partial effective snrs.
Obviously, the reliability of the channel estimation based on the pilot subcarriers is greater than that of the channel estimation based on the auxiliary data subcarriers, which is greater than that of the interpolated other data subcarriers, so the following condition must be satisfied.
S6: and carrying out modulation coding mode selection on the next frame data according to the effective signal-to-noise ratio of the current frame.
SNR of the current frame is measuredeffThe method is applied to a mobile ad hoc network adaptive modulation coding system, and the modulation coding mode selection suitable for the sub-carrier of the next frame data is carried out, so that the channel data of the next frame is subjected to channel estimation, and the throughput of the system is further improved on the premise of meeting the frame error rate of the system.
The invention provides a channel quality determination method under a high dynamic situation, which is based on the design of a physical layer frame structure of a mobile ad hoc network of an 802.11p standard, and assists channel estimation and updating of a channel estimation value through data symbols carried by a low-bit-rate Turbo code, so that channel compensation is more accurately performed in a decoding stage, and the channel state quality determination method under the scheme is provided, a basis is provided for the selection of a modulation coding mode of next frame data, the influence of high dynamics of the mobile ad hoc network on channel estimation in the prior art is reduced, and the throughput performance and reliability of a communication system are improved.
The foregoing is a more detailed description of the invention in connection with specific preferred embodiments and it is not intended that the invention be limited to these specific details. For those skilled in the art to which the invention pertains, several simple deductions or substitutions can be made without departing from the spirit of the invention, and all shall be considered as belonging to the protection scope of the invention.
Claims (9)
1. A method for measuring channel quality under a high dynamic scene is characterized by comprising the following steps:
acquiring current frame data, wherein the current frame data comprises pilot frequency subcarriers, data auxiliary subcarriers and data subcarriers; the data auxiliary subcarrier is a data subcarrier of low-price modulation coding inserted in the data frequency domain of the current frame;
decoding the pilot frequency sub-carrier and carrying out first channel estimation to obtain a first estimation value;
carrying out decoding reconstruction and second channel estimation on the data auxiliary subcarriers to obtain a second estimation value;
obtaining a third estimated value according to the first estimated value and the second estimated value;
obtaining the effective signal-to-noise ratio of the current frame according to the first estimation value, the second estimation value and the third estimation value;
and carrying out modulation coding mode selection on the next frame data according to the effective signal-to-noise ratio of the current frame.
2. The method of claim 1, wherein a distance between two adjacent data-assisted sub-carrier frequencies in the current frame data is smaller than a coherence bandwidth.
3. The method according to claim 1, wherein the number of data-aided subcarriers in the current frame data is:
wherein, taumaxFor maximum multipath delay spread of the channel, NpilotIs the number of pilot subcarriers, NdataIs the number of data subcarriers.
4. The method of claim 1, wherein the decoding the pilot subcarriers and performing the first channel estimation to obtain the first estimated value comprises:
decoding the pilot frequency sub-carrier, if the pilot frequency sub-carrier is judged not to be decoded correctly, judging that the sending of the current frame data fails, and re-receiving the current frame data; and if the pilot frequency subcarrier is judged to be decoded correctly, performing first channel estimation on the decoded pilot frequency subcarrier to obtain a first estimation value.
5. The method of claim 1, wherein the first estimation value is:
wherein, Y [ k ]]For the received signal of the k pilot sub-carrier, X k]For the transmitted signal of the k-th pilot subcarrier,
is the channel estimation value of the k pilot sub-carrier.
6. The method of claim 1, wherein the performing decoding reconstruction and second channel estimation on the data-aided subcarriers to obtain a second estimated value comprises:
decoding the data auxiliary subcarrier, recoding and modulating the obtained data, and reconstructing the data of a transmitting party;
and performing second channel estimation on the reconstructed data of the sender to obtain a second estimation value.
7. The method of claim 1, wherein the second estimation value is:
wherein: y isdata_pro[k]For the received signal of the k-th auxiliary data sub-carrier, Xdata_pro[k]For the reconstructed transmission signal after decoding of the kth auxiliary data subcarrier signal,
is the channel estimate for the kth secondary data subcarrier.
8. The method of claim 1, wherein obtaining the effective snr of the current frame according to the first estimate, the second estimate, and the third estimate comprises:
respectively obtaining a first effective signal-to-noise ratio, a second effective signal-to-noise ratio and a third effective signal-to-noise ratio according to the first estimation value, the second estimation value and the third estimation value;
and obtaining the effective signal-to-noise ratio of the current frame according to the first effective signal-to-noise ratio, the second effective signal-to-noise ratio and the third effective signal-to-noise ratio.
9. The method of claim 8, wherein the effective snr of the current frame is:
SNReff＝λ1*SNReff_pilot+λ2*SNReff_data_pro+λ3*SNReff_data
wherein the SNReff_pilotFor the first effective signal-to-noise ratio, SNReff_data_proFor the second effective signal-to-noise ratio, SNReff_dataFor a third effective signal-to-noise ratio, λ1，λ2，λ3Respectively represent the weight of the corresponding partial effective signal-to-noise ratio, and satisfy
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Citations (3)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| WO2010087776A1 (en) * | 2009-02-02 | 2010-08-05 | Telefonaktiebolaget L M Ericsson (Publ) | Encoding and decoding methods for expurgated convolutional codes and convolutional turbo codes |
| CN102469050A (en) * | 2011-06-30 | 2012-05-23 | 重庆重邮信科通信技术有限公司 | Chanel estimating method in long-term evolution system based on specific reference signal of terminal |
| CN105519059A (en) * | 2013-07-17 | 2016-04-20 | 三星电子株式会社 | Method and apparatus for estimating channel in wireless communication system |
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| CN101494528B (en) * | 2009-02-27 | 2011-12-28 | 清华大学 | Training sequence design and channel estimation method of transmission diversity block transmission system |
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| CN102469050A (en) * | 2011-06-30 | 2012-05-23 | 重庆重邮信科通信技术有限公司 | Chanel estimating method in long-term evolution system based on specific reference signal of terminal |
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