CN109283497A - Bistatic FDA-MIMO distance by radar cheating interference recognition methods - Google Patents
Bistatic FDA-MIMO distance by radar cheating interference recognition methods Download PDFInfo
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Abstract
The invention belongs to Anti-jamming Technology for Radar fields, disclose bistatic FDA-MIMO distance by radar cheating interference recognition methods, it include: to utilize the frequency diversity array emitter signal, obtain the signal of each array element transmitting in the frequency diversity array, the transmitted waveform of any two array element is mutually orthogonal in frequency diversity array；Obtain the echo-signal of each received target of array element in M member uniform line-array；The target echo signal received to n array element hair m array element carries out matched filtering, the target echo signal r that the n array element hair m array element after obtaining matched filtering processing is receiveds,mn；Obtain the snapshot data vector x of target echo signals；Adaptive beamformer is carried out to the target echo signal, so that the decoy return generated to false target genera tor inhibits.
Description
Technical Field
The invention belongs to the technical field of radar anti-interference, And particularly relates to a bistatic FDA-MIMO (frequency diversity Array And Multiple Output frequency diversity Array combined with a multi-Input multi-Output system architecture) radar range deception interference identification method, which is mainly suitable for main lobe interference identification And suppression of range modulation in practical engineering application.
Background
Today, with the rapid advancement of electronic information, the interference faced by combat radars in a battlefield environment is increasingly complex. The FTG (False Target Generator) destroys the enemy's detection of the strategy of the own party by acquiring the waveform signal emitted by the enemy radar and then generating a huge number of virtual targets according to the acquired signal characteristics.
Most current approaches to combat jamming are to increase the variability of the probe signal, such as frequency agile radar. The possibility of interception by the FTG is reduced as much as possible, and the purpose of interference resistance is achieved. But today, as information technology is rapidly developed, the above technology has little effect in more complicated electronic countermeasure environments.
Disclosure of Invention
In view of the above problems, an object of the present invention is to provide a bistatic radar range spoofing type interference identification method, in which a frequency diversity array is used at a transmitting end, so that a transmission steering vector of the array is a function of a propagation distance and a transmission angle, the propagation distance and the transmission angle have a correlation, and a processing degree of freedom of the transmitting end is increased.
In order to achieve the purpose, the invention is realized by adopting the following technical scheme.
The technical idea of the invention is as follows: the method comprises the steps of obtaining a space frequency distance according to a transmitting space frequency by utilizing two-dimensional coupling of a frequency diversity array signal distance and an angle, obtaining a space triangulation distance by utilizing correlation between a bistatic MIMO radar transmitting and receiving angle and the space distance, and finally completing identification of distance deception interference by utilizing whether a delay distance, the space frequency distance and the triangulation distance are matched or not.
A bistatic FDA-MIMO radar range-spoofing interference identification method, the method comprising the steps of:
step 1, constructing a bistatic FDA-MIMO radar comprising a transmitting array and a receiving array, wherein the transmitting array is a uniform linear array of N array elements, the receiving array is a uniform linear array of M array elements, and the distance between the central point of the transmitting array and the central point of the receiving array is d; true and false targets exist in the detection range of the bistatic FDA-MIMO radar, and the false targets are range deception interferences;
step 2, determining the transmitting signal of each array element in the transmitting array, wherein the transmitting signals of any two array elements in the transmitting array are orthogonal to each other;
step 3, obtaining a receiving signal of each array element in the receiving array; performing matched filtering on a received signal of each array element in the receiving array so as to obtain a delay propagation distance of a true and false target existing in a detection range of the bistatic FDA-MIMO radar;
step 4, acquiring the emission angle of the true and false target relative to the normal of the emission array, the receiving angle of the true and false target relative to the normal of the receiving array, the emission guide vector of the emission array and the receiving guide vector of the receiving array;
step 5, determining the triangular propagation distance of the true and false targets according to the emission angle of the true and false targets relative to the normal of the emission array and the receiving angle of the true and false targets relative to the normal of the receiving array;
step 6, setting a first detection threshold, and determining a quasi-true target and a distance deception jamming in the true and false targets according to the delay propagation distance of the true and false targets and the triangular propagation distance of the true and false targets;
step 7, obtaining the equivalent transmitting space frequency of the transmitting signals of the transmitting array and the transmitting angle of the quasi-real target relative to the normal of the transmitting array according to the transmitting guide vector of the transmitting array, and determining the space propagation distance of the quasi-real target according to the equivalent transmitting space frequency of the transmitting space; and setting a second detection threshold, and determining a real target and distance deception jamming in the quasi-real target according to the second detection threshold.
The technical scheme of the invention has the characteristics and further improvements that:
(1) the step 2 specifically comprises the following substeps:
(2a) the transmitting array is a uniform linear array comprising N array elements, and the transmitting array element interval dtThe carrier frequency is half wavelength, and the carrier frequency of the transmitting signal of each array element is sequentially and linearly increased, then the carrier frequency f of the transmitting signal of the nth array element of the transmitting array isnComprises the following steps:
fn＝f0+(n-1)Δf n＝1，2，…，N
wherein f is0Is the reference frequency of the transmit array, Δ f is a fixed frequency increment;
(2b) transmitting signal s of nth array element of transmitting arrayn(t) is:
wherein,and transmitting a complex envelope of a signal for the nth array element in the transmitting array, wherein E represents the energy of the transmitted signal, T is a time variable, and T represents the pulse repetition period.
(2) The step 3 specifically comprises the following substeps:
(3a) the receiving array is a uniform linear array comprising M array elements, and the spacing d of the receiving array elementsrIs half wavelength and receives the received signal r of the m-th array element of the arrays，m(t) is expressed as:
where M is 1, 2, …, M, ξ denotes a complex coefficient of the received signal,representing the complex envelope, τ, of the signal transmitted by the nth array element of the transmit arrays(m, n) represents the delay generated by the nth array element of the transmitting array transmitting and the mth array element of the receiving array receiving signals;
(3b) performing matched filtering on signals received by each array element in a receiving array to obtain matched filtered signals, and determining the delay propagation distance of a true and false target according to a spectral peak which is greater than a set threshold value in the matched filtered signals, wherein the delay propagation distance of the ith true and false target is recorded as Rdelay，iI, I is the total number of true and false targets in the detection range of the bistatic FDA-MIMO radar.
(3) The step 4 specifically comprises the following substeps:
(4a) after matched filtering, receiving a signal r received by the mth array element of the arrays，m' (t) is
Wherein, ξsRepresenting the product of the scattering coefficient, the antenna gain and the pulse compression gain of the received signal, fnFor transmitting the carrier frequency of the signal of the nth array element of the array, the signal rs，m' (t) is decomposed to obtain the signal r which is transmitted by the nth array element of the transmitting array and received by the mth array element of the receiving array after matched filterings，mnExpressed as:
(4b) performing wave beam formation on all signals received by the same receiving array element after matched filtering to obtain the transmission angle theta of the ith true and false target relative to the normal of the transmission arrayt，iI, I is the total number of true and false targets in the detection range of the bistatic FDA-MIMO radar;
the same transmitting signal received by all receiving array elements is formed by wave beams to obtain the receiving angle theta of the ith true and false target relative to the normal of the receiving arrayr，iI, I is the total number of true and false targets in the detection range of the bistatic FDA-MIMO radar;
(4c) receiving snapshot data vector x of array received signalsExpressed as:
wherein,is kronecker product, a (theta)s，Rt，Rr)＝aθ(θs)⊙ar(Rt，Rr) A transmit steering vector for the transmit array, aθ(θs) For directing the vector at the emission angle, ar(Rt，Rr) For transmitting a range-oriented vector, b (θ)s) Is the receive steering vector of the receive array.
(4) The step 5 specifically comprises the following steps:
according to the emission angle theta of the ith true and false target relative to the normal of the emission arrayt，iAnd the receiving angle theta of the ith true and false target relative to the normal of the receiving arrayr，iDetermining the triangular propagation distance of the ith true and false target
I, I is the total number of true and false targets in the detection range of the bistatic FDA-MIMO radar, and d is the distance between the center point of the transmitting array and the center point of the receiving array.
(5) The step 6 specifically comprises the following steps:
determining a first detection threshold D when Rangle，i-Rdelay，iWhen | < D, the ith true and false target is judged as the quasi-true target, and when | Rangle，i-Rdelay，iAnd if the value is greater than D, judging that the ith true and false target is distance deception interference, wherein I is 1, 2.
(6) The step 7 specifically comprises the following steps:
(7a) transmitting signals according to equivalent transmit spatial frequencies of a transmit arrayCalculating the spatial propagation distance R of the jth quasi-real targetfreq，jJ is 1, 2,., J is the total number of quasi-real targets, J is less than or equal to I, thetat，jRepresenting the emission angle, λ, of the jth quasi-true target relative to the normal of the emitting array0Is the emission signal wavelength;
(7b) determining a second detection threshold D', when Rangle，j-Rfreq，jWhen | ≦ D', the jth quasi-real target is determined as the real target, and when | R ≦ D |, the quasi-real target is determined as the real targetangle-RfreqAnd when the value is greater than D', judging that the jth quasi-real target is distance deception jamming.
Compared with the prior art, the technology has the following advantages: (1) the transmitting end of the invention adopts the frequency diversity array, so that the transmitting guide vector of the array is a function of the propagation distance and the transmitting angle, the propagation distance and the angle have correlation, and the processing freedom degree of the transmitting end is increased; (2) the invention adopts bistatic FDA-MIMO system radar, the receiving end can equivalently form transmitting end wave beams after matched filtering, the transmitting angle and the receiving angle of the target are extracted, and the triangular propagation distance R is obtained by utilizing the triangular positioning theoryangleAnd matched filter peak distance Rdelay(delay propagation distance) identifying false targets generated by the stationary FTG; (3) the invention can estimate the transmission guide vector by the transmission angle information by using the frequency diversity arrayIncluding the true propagation distance Rfreq(spatial propagation distance), and the false target generated by the motion FTG can be further identified by combining the judgment result.
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In order to more clearly illustrate the embodiments of the present invention or the technical solutions in the prior art, the drawings used in the description of the embodiments or the prior art will be briefly described below, it is obvious that the drawings in the following description are only some embodiments of the present invention, and for those skilled in the art, other drawings can be obtained according to the drawings without creative efforts.
FIG. 1 is a schematic diagram of an array space structure according to an embodiment of the present invention;
FIG. 2 is a schematic flow chart of a bistatic FDA-MIMO radar range spoofing interference identification method according to an embodiment of the present invention;
FIG. 3 is a diagram illustrating a static decoy generator and a two-dimensional spatial distribution diagram of a decoy and a real target generated by the static decoy generator in a transmitting angle-receiving angle according to an embodiment of the present invention;
FIG. 4 is a diagram of a static false target generator and its difference distribution diagram between a false target and a real target in a three-dimensional space of emission angle-reception angle-distance and an ideal triangulation distance according to an embodiment of the present invention;
FIG. 5 is a diagram illustrating a difference distribution of the quasi-real target from an ideal position in a two-dimensional plane of the transmitting spatial frequency and the receiving spatial frequency according to an embodiment of the present invention;
fig. 6 is a distribution diagram of adaptive interference suppression weights in a two-dimensional plane of transmit spatial frequency-receive spatial frequency according to an embodiment of the present invention.
Detailed Description
The technical solutions in the embodiments of the present invention will be clearly and completely described below with reference to the drawings in the embodiments of the present invention, and it is obvious that the described embodiments are only a part of the embodiments of the present invention, and not all of the embodiments. All other embodiments, which can be derived by a person skilled in the art from the embodiments given herein without making any creative effort, shall fall within the protection scope of the present invention.
Fig. 1 is a schematic diagram of an array spatial structure according to the present invention, in the present invention, a bistatic radar is used to complete detection of a target, but a radar received signal may be obtained by reflection of a real target, and may also be a storage delay false target signal generated by a false target generator, and in the spatial model shown in fig. 1, the bistatic FDA-MIMO system-based radar distance spoofing type interference identification method according to the present invention is shown in fig. 2, and includes the following steps:
step 1, constructing a bistatic FDA-MIMO radar array spatial structure, wherein a transmitting array of the radar system is a uniform linear array of N array elements, a receiving array is a uniform linear array of M array elements, the distance between the center point of the transmitting array and the center point of the receiving array is d, and the carrier frequency reference frequency of a transmitting signal of the transmitting array is f0The frequency increment among the array elements of the transmitting array is delta f, and the specific steps are as follows:
1a) transmit array and transmit signal design
Constructing a uniform linear array containing N array elements with an array element spacing dtAt half a wavelength. The carrier frequency of each array element transmitting signal of the radar antenna array is sequentially increased linearly, and the carrier frequency f of the nth array element transmitting signal isnExpressed as:
fn＝f0+(n-1)Δf n＝1，2，…，N
wherein f is0For the reference frequency of the radar transmitting array, Δ f is a known frequency increment, satisfying f0> Δ f. Therefore, the transmission signal of the nth array element can be expressed as:
in the formula,for the transmit signal complex envelope, E represents the signal energy, T is a time variable, and T represents the pulse repetition period. The transmitting signals of different transmitting array elements meet the condition of mutual orthogonality:
1b) receive array and received signal representation
The receiving array is a uniform linear array containing M array elements, and the spacing between the array elements is half wavelength. Utilizing the M-element equidistant linear array to receive the echo signal of a target to obtain that the echo signal received by the mth array element of the receiving array is rs，m(t)，m＝1，2，…，M；
The method comprises the following specific steps:
for a real target, the transmitted signal is reflected by the real target and received by the receiving array element. For spoofing interference, the received transmitted signal is delayed by a decoy generator through storage, and digital modulation produces positive and negative range offsets. The spoofed interference and the real target are received by the receiving array simultaneously. The target (real target and false target interference are collectively referred to as target in this and the following description) signal received by the mth array element can be represented as:
where ξ represents the complex coefficient of the target, relating to radar transmission power, target transmission coefficient, etc.Representing signals transmitted by the nth array element in the transmit arrayComplex envelope of (tau)s(m, n) represents the delay caused by the signal transmitted by the nth array element of the transmitting array, reflected by a target, and received by the mth array element of the receiving array.
Wherein R istFor transmitting the distance of the array reference point to the target, RrTo receive the distance of the array reference point to the target, dtFor transmitting array element spacing, drFor receiving array element spacing, thetatIs the emission angle, i.e. the angle between the target and the normal of the emitting array, thetarIs the acceptance angle, i.e. the angle between the target and the normal of the receiving array, and c is the speed of light.
1c) Matched filtering of received signals
Carrying out matched filtering on signals received by each receiving array element to obtain signals which are transmitted by the nth array element of the transmitting array after matched filtering, and receiving signals received by the mth array element of the receiving array, namely rs，mn. The propagation distance R of the ith target can be obtained according to the peak delay of the matched filtering spectrumdelay，i，And setting a judgment threshold, judging that a target exists when the spectrum peak is larger than the threshold, and judging that the noise exists when the spectrum peak is smaller than the threshold. The propagation distance Rdelay，iThe distance from the target to the receiving array is the distance from the transmitting array to the target. According to the equivalent transmitting beam forming of the receiving end, the angle transmitting angle of the target relative to the normal of the transmitting array can be obtainedAccording to the receiving beam forming of the receiving end, the receiving angle of the target relative to the normal of the receiving array can be obtainedObtaining snapshot data vector x of target echos，xs＝[rs，11，rs，12，…，rs，1N，…，rs，mn，…，rs，MN]TWhere the superscript T represents the transpose of a matrix or vector.
The method comprises the following specific steps:
on the premise that the transmission signal is a narrowband signal, the following steps are provided:
wherein,after matched filtering, receiving a signal r received by the mth array element of the arrays，m' (t) is:
wherein, ξsRepresenting the scattering coefficient of the target, the product of the antenna gain and the pulse compression gain, fnAnd transmitting the carrier frequency of the signal for the nth array element of the transmitting array. To rs，m't' signal is decomposed to obtain the signal r received by the mth array element of the nth array element transmitting and receiving array after matched filterings，mnIt can be expressed as:
rs，mn＝ξsexp{-j2πfn(Rt+Rs)/c}exp{j2πfndtsinθt(n-1)/c}exp{j2πfndrsinθr(m-1)/c}
as can be seen from the above equation, the snapshot data vector x of the target echosCan be expressed as:
wherein,is kronecker product, a (theta)s，Rt，Rr)＝aθ(θs)⊙ar(Rt，Rr) For transmitting steering vectors, aθ(θs) For directing the vector at the emission angle, ar(Rt，Rr) The steering vectors are the transmission distances and can be expressed as:
aθ(θs)＝[1，exp(j2πd sinθt/λ0)，…，exp(j2πd sinθt(N-1)/λ0)]T
ar(Rt，Rr)＝[1，exp(-j2πΔf(Rt+Rr)/c)，…，exp(-j2πΔf(Rt+Rr)(N-1)/c)]Tb(θs) For receiving the steering vector, it can be expressed as
b(θs)＝[1，exp(j2πd sinθs/λ0)，…，exp(j2πd sinθs(N-1)/λ0)]T
At this time, the equivalent transmit spatial frequency M of the frequency diversity array transmit signal and the equivalent receive spatial frequency M of the receive signalRespectively as follows:
according to the formula, different from the traditional bistatic MIMO radar, the bistatic MIMO radar adopting the frequency diversity array transmits the steering vector with distance and angle two-dimensional dependence.
Step 2, distance deception jamming identification
The deceptive range decoy jamming principle is that a decoy generator captures radar emission waveforms, generates decoys with positive and negative range offsets through proper digital FM modulation timing, and then places them in a space at a certain range and angle.
Under the interference condition of a far-field static false target generator, obtaining a target emission angle through the step 1c)Receiving angleThe distance d between the transmitting array element and the receiving array element can be obtained by a trigonometric formulaangleExpressed as:
determining a discrimination threshold D, and determining an ideal triangular distance RangleWhether or not to reach 1c) the echo delay distance RdelayAnd (3) consistency:
for a moving decoy generator, a decoy generated by a part of the moving decoy generator may be recognized as a quasi-real target in the previous recognition, and further judgment is needed. Because the decoy generator only stores and delays the received signal and does not change the equivalent transmitting spatial frequency of the signal, decoys generated by the same decoy generator in the same time period have the same transmitting spatial frequency and are not related to the delay time. The equivalent transmit spatial frequency carries the false target generator true propagation distance. Equivalent transmitting spaceThe inter-frequency is related to the transmission angle and the signal propagation distance, so the transceiving angle is obtained by the step 1c)Andand transmitting spatial frequency by detecting echoBy the formulaCan yield Rfreq. On the basis of the judgment of the previous step, R is judged for the sample which is judged to be a quasi-real targetfreqAnd RangleWhether the two are consistent or not, determining a discrimination threshold D,
and after the true and false targets are judged, the false targets are suppressed through self-adaptive processing.
The effects of the present invention are further illustrated by the following simulation results.
Simulation experiment for static decoy generator
Simulation conditions
Two frequency diversity arrays with 12 array elements are arranged, the distance between the array elements is half wavelength, the reference frequency is 1GHz, the frequency increment is 15kHz, the distance from a transmitting array to a receiving array is 30km, a real target is arranged, the arrival angle of the real target is 30 degrees, the distance of the real target is 15km, the speed is 100m/s, the signal to noise ratio is 5dB, two false target generators are arranged, the arrival angles of the false target generators are 30 degrees to 30 degrees respectively, the distances between the false target generators and the frequency diversity arrays are 30km and 30km respectively, the speeds are random, and the dry-to-noise ratios are 25dB and 25dB respectively.
Emulated content
According to the receiving angle and the emitting angle of the target, the distribution of the real target and the false target in the emitting and receiving domain is calculated, as shown in fig. 3, it can be known that the distribution of all the false targets generated by the static false target generator in the emitting and receiving angular domain is consistent. The ideal signal propagation distance can be calculated according to the triangulation theory by the target transmitting angle and receiving angle and the distance between the transmitting array and the receiving array. The signal transmitting-receiving delay distance and the triangular ideal distance are consistent for the real target. For the false target signal generated by the storage delay of the static false target generator, the transmitting and receiving delay distance is changed, so that the ideal distance is inconsistent with the triangular ideal distance, and the identification of the true and false targets can be completed. The simulation result is shown in fig. 4, and the method can have a good recognition effect on the static false target generator.
Simulation experiment two-for-one motion false target generator
1) Simulation conditions
Two frequency diversity arrays with 12 array elements are arranged, the distance between the array elements is half wavelength, the reference frequency is 1GHz, the frequency increment is 15kHz, the distance between a transmitting array and a receiving array is 30km, a real target is arranged, the transmitting angle is 60, the arrival angle is 30, the distance is 15km, the speed is 100m/s, and the signal to noise ratio is 5dB, two false target generators are arranged, the transmitting angles are 60 and 60 respectively, the arrival angles are-30 and 30 respectively, the distances between the false target generators and the transmitting array during capturing transmitting signals are 21km and 50km respectively, the distances between the false target generators and the receiving array during generating echo signals are 10km and 25km respectively, the distances between the false target generators and the receiving array are random with the speed, and the interference to noise ratios are 25dB and 25dB respectively.
Emulated content
The decoys generated by transmitting the same intercepted signal are distributed equally in the transmitting and receiving spatial frequency plane due to the same decoy generator, and as shown in fig. 5, the decoy distribution generated by FTG1 and FTG2 is consistent with the position of the decoy generator. The frequency diversity array has two-dimensional distance and angle dependence, and the transmission space frequency contains the real propagation distance. By comparing the ideal triangular distance in the previous experiment with the real propagation distance, the false target generated by the motion false target generator can be distinguished, as shown in fig. 5.
As shown in fig. 6, there is beam forming at the position of the real target (corresponding to the brightest spot in fig. 5), and the false target generated by the 1 st false target generator and the false target generated by the 2 nd false target generator, so that the false targets generated by the same false target generator overlap regardless of how many false targets are generated by the False Target Generator (FTG), and thus, the deceptive jamming is suppressed due to the distance mismatch.
In conclusion, the simulation experiment verifies the correctness, the effectiveness and the reliability of the method.
Those of ordinary skill in the art will understand that: all or part of the steps for realizing the method embodiments can be completed by hardware related to program instructions, the program can be stored in a computer readable storage medium, and the program executes the steps comprising the method embodiments when executed; and the aforementioned storage medium includes: various media that can store program codes, such as ROM, RAM, magnetic or optical disks.
The above description is only for the specific embodiments of the present invention, but the scope of the present invention is not limited thereto, and any person skilled in the art can easily conceive of the changes or substitutions within the technical scope of the present invention, and all the changes or substitutions should be covered within the scope of the present invention. Therefore, the protection scope of the present invention shall be subject to the protection scope of the appended claims.
Claims (7)
1. A bistatic FDA-MIMO radar range-spoofing interference identification method, characterized in that the method comprises the following steps:
step 1, constructing a bistatic FDA-MIMO radar comprising a transmitting array and a receiving array, wherein the transmitting array is a uniform linear array of N array elements, the receiving array is a uniform linear array of M array elements, and the distance between the central point of the transmitting array and the central point of the receiving array is d; true and false targets exist in the detection range of the bistatic FDA-MIMO radar, and the false targets are range deception interferences;
step 2, determining the transmitting signal of each array element in the transmitting array, wherein the transmitting signals of any two array elements in the transmitting array are orthogonal to each other;
step 3, obtaining a receiving signal of each array element in the receiving array; performing matched filtering on a received signal of each array element in the receiving array so as to obtain a delay propagation distance of a true and false target existing in a detection range of the bistatic FDA-MIMO radar;
step 4, acquiring the emission angle of the true and false target relative to the normal of the emission array, the receiving angle of the true and false target relative to the normal of the receiving array, the emission guide vector of the emission array and the receiving guide vector of the receiving array;
step 5, determining the triangular propagation distance of the true and false targets according to the emission angle of the true and false targets relative to the normal of the emission array and the receiving angle of the true and false targets relative to the normal of the receiving array;
step 6, setting a first detection threshold, and determining a quasi-true target and a distance deception jamming in the true and false targets according to the delay propagation distance of the true and false targets and the triangular propagation distance of the true and false targets;
step 7, obtaining the equivalent transmitting space frequency of the transmitting signals of the transmitting array and the transmitting angle of the quasi-real target relative to the normal of the transmitting array according to the transmitting guide vector of the transmitting array, and determining the space propagation distance of the quasi-real target according to the equivalent transmitting space frequency of the transmitting space; and setting a second detection threshold, and determining a real target and distance deception jamming in the quasi-real target according to the second detection threshold.
2. The bistatic FDA-MIMO radar range spoofing interference identification method of claim 1, wherein step 2 specifically comprises the following substeps:
(2a) the transmitting array is a uniform linear array comprising N array elements, and the transmitting array element interval dtThe carrier frequency is half wavelength, and the carrier frequency of the transmitting signal of each array element is sequentially and linearly increased, then the carrier frequency f of the transmitting signal of the nth array element of the transmitting array isnComprises the following steps:
fn＝f0+(n-1)Δf n＝1，2，…，N
wherein f is0Is the reference frequency of the transmit array, Δ f is a fixed frequency increment;
(2b) transmitting signal s of nth array element of transmitting arrayn(t) is:
wherein,and transmitting a complex envelope of a signal for the nth array element in the transmitting array, wherein E represents the energy of the transmitted signal, T is a time variable, and T represents the pulse repetition period.
3. The bistatic FDA-MIMO radar range spoofing interference identification method of claim 1, wherein step 3 specifically comprises the following substeps:
(3a) the receiving array is a uniform linear array comprising M array elements, and the spacing d of the receiving array elementsrIs half wavelength and receives the received signal r of the m-th array element of the arrays，m(t) is expressed as:
where M is 1, 2, …, M, ξ denotes a complex coefficient of the received signal,representing the complex envelope, τ, of the signal transmitted by the nth array element of the transmit arrays(m, n) represents the delay generated by the nth array element of the transmitting array transmitting and the mth array element of the receiving array receiving signals;
(3b) performing matched filtering on signals received by each array element in a receiving array to obtain matched filtered signals, and then obtaining signals larger than a set threshold value in the matched filtered signalsDetermining the delay propagation distance of a true and false target by the spectral peak, wherein the delay propagation distance of the ith true and false target is recorded as Rdelay，iI, I is the total number of true and false targets in the detection range of the bistatic FDA-MIMO radar.
4. The bistatic FDA-MIMO radar range spoofing interference identification method of claim 1, wherein step 4 specifically comprises the following substeps:
(4a) after matched filtering, receiving a signal r received by the mth array element of the arrays，m' (t) is
Wherein, ξsRepresenting the product of the scattering coefficient, the antenna gain and the pulse compression gain of the received signal, fnFor transmitting the carrier frequency of the signal of the nth array element of the array, the signal rs，m' (t) is decomposed to obtain the signal r which is transmitted by the nth array element of the transmitting array and received by the mth array element of the receiving array after matched filterings，mnExpressed as:
(4b) performing wave beam formation on all signals received by the same receiving array element after matched filtering to obtain the transmission angle theta of the ith true and false target relative to the normal of the transmission arrayt，iI, I is the total number of true and false targets in the detection range of the bistatic FDA-MIMO radar;
the same transmitting signal received by all receiving array elements is formed by wave beams to obtain the receiving angle theta of the ith true and false target relative to the normal of the receiving arrayr，iI, I is the total number of true and false targets in the detection range of the bistatic FDA-MIMO radar;
(4c) receiving snapshot data vector x of array received signalsExpressed as:
wherein,is the product of kronecker, and is,a transmit steering vector for the transmit array, aθ(θs) For directing the vector at the emission angle, ar(Rt，Rr) For transmitting a range-oriented vector, b (θ)s) Is the receive steering vector of the receive array.
5. The bistatic FDA-MIMO radar range-spoofing interference identification method as claimed in claim 1, wherein step 5 specifically comprises:
according to the emission angle theta of the ith true and false target relative to the normal of the emission arrayt，iAnd the receiving angle theta of the ith true and false target relative to the normal of the receiving arrayr，iDetermining the triangular propagation distance R of the ith true and false targetangle，i：
I, I is the total number of true and false targets in the detection range of the bistatic FDA-MIMO radar, and d is the distance between the center point of the transmitting array and the center point of the receiving array.
6. The bistatic FDA-MIMO radar range spoofing interference identification method of claim 1, wherein step 6 specifically comprises:
determining a first detection threshold D when Rangle，i-Rdelay，iWhen | < D, the ith true and false target is judged as the quasi-true target, when | < D|Rangle，i-Rdelay，iAnd if the value is greater than D, judging that the ith true and false target is distance deception interference, wherein I is 1, 2.
7. The bistatic FDA-MIMO radar range spoofing interference identification method of claim 1, wherein step 7 specifically comprises:
(7a) transmitting signals according to equivalent transmit spatial frequencies of a transmit arrayCalculating the spatial propagation distance R of the jth quasi-real targetfreq，jJ is 1, 2,., J is the total number of quasi-real targets, J is less than or equal to I, thetat，jRepresenting the emission angle, λ, of the jth quasi-true target relative to the normal of the emitting array0Is the emission signal wavelength;
(7b) determining a second detection threshold D', when Rangle，j-Rfreq，jWhen | is less than or equal to D ', the jth quasi-real target is judged as a real target, and when | R is less than or equal to D', the | R is judged as a real targetangle-RfreqAnd when the value is greater than D', judging that the jth quasi-real target is distance deception jamming.
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