CN106656453A

CN106656453A - Synchronous device and method in narrowband wireless communication terminal

Info

Publication number: CN106656453A
Application number: CN201710064995.1A
Authority: CN
Inventors: 李文龙
Original assignee: SUZHOU WEITEBI INFORMATION TECHNOLOGY Co Ltd
Current assignee: Zhejiang Central Corp Of Technology And Technology Co ltd
Priority date: 2017-02-05
Filing date: 2017-02-05
Publication date: 2017-05-10
Anticipated expiration: 2037-02-05
Also published as: CN111106924B; CN106656453B; CN111106923A; CN111106892B; CN110932837A; CN110798304B; CN111106892A; CN110798304A; CN111342948B; CN111342948A; CN111106924A; CN111106923B; CN110932837B

Abstract

The invention discloses a synchronous detection device applied to a narrowband wireless communication system terminal. The device comprises a down-sampling module, a sliding autocorrelation module and a difference cross-correlation module. A received 1.92 MHz time-domain signal is subjected to down sampling to a 240 kHz signal through the down-sampling module in terms of OFDM symbol time periods and a fixed down-sampling pattern. Through the sliding autocorrelation module, sampling point data in a 10 ms wireless frame processing window is moved bit by bit as an initial position t, date of which the length is eleven OFDM symbol time periods is taken as a sliding window, and the eleven groups of sample points in the sliding window are correlatively accumulated at intervals of two groups. Through the difference cross-correlation module, an obtained primary synchronizing sequence is subjected to differencing to form two approximately equal parts and is correlatively accumulated with a main synchronizing sequence generated locally. According to the invention, by employing the synchronous detection device, main synchronizing signals are detected well in the narrowband-wireless-communication-system application scenario in which the signal-to-noise ratio is low and the frequency deviation is large, and the implementation complexity is low so that the low-cost requirement of the narrowband wireless communication terminal is met.

Description

Synchronization device and method in narrow-band wireless communication terminal

Technical Field

The invention relates to the field of mobile communication, in particular to a synchronizing device and a synchronizing method applied to a narrow-band cellular communication terminal in a future internet of things network.

Background

IoT (internet of things) has become an industry highlight in the recent communication market, and recent innovation results and application cases thereof are shown on many operators and equipment. The narrow-band wireless communication technology (NB-Iot) is the key of an operator in the market of the Internet of things. The narrow-band wireless communication system has the advantages of low power consumption, wide coverage, low cost, high capacity and the like, so that the narrow-band wireless communication system can be widely applied to various vertical industries, such as remote meter reading, asset tracking, intelligent parking, intelligent agriculture and the like. The first release of the 3GPP standard is expected to be released in 2016, and narrowband wireless communication is expected to stand out in multiple technological competitions in the LPWA market, becoming the best choice for leading operators.

The first version of narrowband wireless communication supports 3 operation modes (standby, in-band, guard-band), including:

■ Standalone: using the spectrum of an existing GERAN system to replace one or more GSM carriers

■ Guard-band: utilizing unused resource blocks within LTE carrier guard intervals

■ In-band: utilizing normal LTE intra-carrier resource blocks.

In network deployment of narrowband wireless communication, bandwidth resources available to a base station are wide, but for a specific narrowband wireless communication terminal device, the uplink and downlink bandwidths of the terminal device occupy only 180kHz (i.e. one PRB) at most, when the terminal device shares bandwidth deployment with the conventional LTE, a downlink synchronization pilot of a narrowband wireless communication system can only be transmitted on a specific PRB, and the specific PRB differs from a 100kHz grid point by a fixed 2.5kHz or 7.5kHz, which is called an anchor PRB.

The invention relates to a technical scheme of detecting a main synchronization sequence of a narrow-band wireless communication system. The characteristics of the primary synchronization pilot (NPSS) in the first 3gpp version of the narrowband wireless communication system include:

■ NPSS transmission period is one wireless frame length (10 ms)

■ NPSS uses the last 11 OFDM symbols of sub-frame 5 in each radio frame and occupies 11 sub-carrier transmissions on each symbol, from sub-carrier 0 to sub-carrier 10

■ NPSS adopts the same ZC sequence as a base sequence in each OFDM symbol, the ZC root sequence is u =5, the ZC sequence is generated in the frequency domain, and the ZC sequence has good correlation between the time domain and the frequency domain

■ NPSS employs a binary scrambling sequence of random patterns between different OFDM symbols.

In addition, as mentioned above, in the same network deployment mode as the conventional LTE, a 2.5/7.5kHz frequency offset exists between the anchor PRB where the downlink synchronization pilot frequency of the narrowband wireless communication system is located and the 100kHz frequency sweep grid, and the superposition of the two factors causes the initial frequency offset which may reach 25kHz or more at most when the narrowband wireless communication terminal device is initially synchronized.

Moreover, the narrowband wireless communication terminal device is often deployed in an extremely low network environment with a low signal-to-noise ratio, and how to detect the synchronization signal in a strong noise background is also a technical problem to be overcome.

The primary synchronization detection method in the conventional LTE system, for example, the invention of application No. 20101038021, a 3gpp LTE downlink initial primary synchronization detection method, or the invention of application No. 2013103796348, a fast downlink primary synchronization method for TD-LTE cell handover, and the invention of application No. 201010111963, a method and apparatus for detecting and generating a sequence of an LTE primary synchronization signal in an LTE system, all disclose methods for detecting (or determining) the existence of a synchronization signal by cross-correlating a received sequence with a locally generated sequence. For a narrowband wireless communication system, because the synchronization sequence is short and works in an environment with an extremely low signal-to-noise ratio and a large initial frequency offset, a synchronization sequence detection method applying frequency domain data cross-correlation used in a traditional LTE system cannot find a correlation peak at all.

Disclosure of Invention

In view of the above drawbacks and deficiencies in the prior art, an object of the present invention is to provide a synchronization apparatus and method for an internet of things narrowband cellular communication terminal, which can better detect a primary synchronization signal in an environment with a very low signal-to-noise ratio and a large frequency offset, and the implementation cost is low.

According to an aspect of the present invention, there is provided a synchronization apparatus for a narrowband cellular communication terminal, comprising the following modules, as shown in fig. 1.

And the M101 down-sampling module is used for down-sampling the time domain sampling signal with the sampling rate of 1.92MHz into a signal of 240 kHz.

The down-sampling module divides 1920 sampling points of every 1ms (one sub-frame length) into 14 OFDM symbol durations, the down-sampling patterns in the 1 st and 7 th OFDM symbol durations are {10,8,8,8,8,8,8,8,8,8,8, 8}, and the down-sampling patterns in other OFDM symbol lengths are {9,8,8,8,8,8,8,8,8,8,8,8,8,8,8,8 }.

M201 sliding auto-correlation module for preliminary determination of the existence and preliminary location of the primary synchronization sequence.

The sliding autocorrelation module further comprises a data buffer for buffering the down-sampled data of the last 11 OFDM time durations of the last 10ms radio frame, so that the total data length processed by the sliding autocorrelation module at one time is the sum of the current 10ms radio frame and the last 11 OFDM symbols of the last 10ms radio frame.

The sliding autocorrelation module moves sampling point data in a processing window bit by bit to serve as an initial position t, downsampled data with the duration of 11 OFDM symbols are taken out to serve as a sliding window, then the sampling points in the sliding window are divided into 11 groups, correlation accumulation is carried out after the sampling points between every two groups are multiplied by corresponding scrambling sequences, alpha filtering is carried out on a plurality of groups of sliding autocorrelation results of a plurality of 10ms wireless frame processing windows, and finally power normalization is carried out on the sliding autocorrelation results of all the sliding windows.

And if the sliding autocorrelation result of one sliding window is larger than the threshold value of the preset value, starting the differential cross-correlation module.

Further, the sliding autocorrelation module further comprises a decimal frequency offset estimation and calibration submodule, which performs decimal frequency offset estimation and calibration according to the phase value of the obtained sliding autocorrelation result, wherein the decimal frequency offset estimation is estimated according to the following formula,

wherein, arctan { A_tThe phase value of the result of the sliding autocorrelation is taken, 1.92MHz is the sampling rate of the initial time domain data, and 137 is the number of sampling points for one OFDM symbol duration.

And the M301 differential cross-correlation module is used for further determining whether the NPSS signal exists.

The data object processed by the differential cross-correlation module is a 187-point sampling sequence in a sliding window obtained from the sliding autocorrelation module, the 187-point sampling sequence is differentiated into two sections with approximately equal length, for example, the length of the first section is 97 points, the length of the second section is 98 points, or the length of the first section is 98 points, the length of the second section is 97 points, after conjugate multiplication and accumulation are respectively performed on the two sections of sequences and a locally generated NPSS time domain sequence, correlation and combination are performed on the two sections of results, and if the correlation and combination result is greater than a preset threshold value, existence of NPSS is confirmed.

Further, the correlation combining further includes power normalizing the combined result in each 10ms radio frame.

Preferably, the differential correlation module further includes a sub-module for performing integer-multiple frequency offset estimation and calibration on the received sequence, the sub-module enumerates all possible integer-multiple frequency offset values within the frequency offset range, tries to modulate the locally generated NPSS time domain sequence with each integer-multiple frequency offset value, performs differential correlation using the modulated local NPSS sequence, and finds out the maximum value of the differential cross-correlation result, where the corresponding integer-multiple frequency offset value is the estimated value. Then, the sum of the decimal frequency multiplication deviation estimation value and the integer frequency multiplication deviation estimation value is synthesized to be a total frequency deviation estimation value, and phase calibration is carried out according to the sampling time of the sampling point.

Preferably, the differential correlation module further includes a timing estimation sub-module, that is, the local NPSS time domain sequence with a high sampling rate is generated, then different initial sampling point offsets are tried and downsampled to generate the local NPSS time domain sequence, then the differential cross correlation is performed, and an initial offset value which enables the differential cross correlation value to be maximum is found out and is used as the estimated timing offset.

The device of the invention has the beneficial effects that: the scheme provided by the invention has better performance, and because the combined gain among a plurality of 10ms wireless frames can be obtained by sampling the scheme provided by the invention, the accuracy of synchronous access can be obtained by using longer synchronous time in specific engineering practice, so that the method is suitable for the low-delay sensitive and high-severe environment of narrow-band wireless communicationPerformance requirements of the lower access. Under a better configuration, the device disclosed by the invention also performs estimation and calibration of decimal frequency offset and integer frequency offset in the process of detecting the NPSS signal, so that the performance of resisting large frequency offset is further improved. Under a better configuration, the device disclosed by the invention can also carry out preliminary timing estimation, thereby creating better conditions for subsequent downlink data reception and improving the overall performance of a receiver. The device of the invention has been carried out multiple times of simulation experiments and evaluations, according to the convention of the 3gpp protocol and the simulation configuration agreed by the 3gpp, the device disclosed by the invention can obtain more than 95% of detection success rate, and can achieve timing synchronization at 4T under better configuration_sampWithin (wherein T)_sampCorresponding to a 1.92MHz sampling interval), the frequency synchronization error is in the 50Hz range.

According to another aspect of the present invention, there is provided a synchronization detection method for a narrowband cellular communication terminal, which includes the following several processes.

S101, a down-sampling process, namely down-sampling a time domain signal with a sampling rate of 1.92MHz into a signal with a sampling rate of 240kHz according to a fixed down-sampling pattern by taking an OFDM symbol as a unit length; the fixed downsampling pattern is as described in the apparatus section of the present invention.

S201, in the sliding self-correlation process, sampling point data in a 10ms wireless frame processing window length are moved bit by bit to serve as an initial position t, the length of 11 OFDM symbol durations serves as a sliding window, sampling points in the sliding window are divided into 11 groups, and correlation accumulation is carried out on the sampling points between the two groups at intervals.

Preferably, the sliding autocorrelation process further includes a sub-process of fractional frequency offset estimation and calibration according to the autocorrelation result.

And if the sliding autocorrelation obtained by the calculation of the sliding autocorrelation process is greater than a threshold value, starting a differential cross-correlation process.

S301, a differential cross-correlation process, in which the synchronization sequence in the sliding window obtained in the sliding auto-correlation process is differentiated into two parts with equal length, and is cross-correlated and accumulated with the locally generated synchronization sequence.

Preferably, the differential cross-correlation process further includes a sub-process of estimating and calibrating the integer multiple frequency offset.

Preferably, the differential cross-correlation process further comprises a timing estimation sub-process.

And if the cross-correlation result obtained in the differential cross-correlation process is larger than a threshold value, determining that the detected sequence is a main synchronization sequence.

Drawings

Fig. 1 is a schematic block diagram of a synchronization apparatus according to the present invention.

Fig. 2 is a schematic diagram of a down-sampling pattern.

Fig. 3 is a schematic diagram showing a comparison relationship between actual sub-frame sampling points and sampling patterns in practice, wherein the actual sub-frame sampling points are randomly extracted within a time length of 1 ms.

Fig. 4 is a diagram illustrating the physical mapping of NPSS sequences.

Fig. 5 is a diagram showing a comparison of the actual 10ms processing window with the actual radio frame location.

Fig. 6 is a schematic diagram of sliding autocorrelation.

Fig. 7 is a diagram illustrating attempts at different timing offsets in timing estimation.

Detailed Description

The embodiments of the present invention will be described below by specific examples, which are described herein for the purpose of illustration only and are not intended to be limiting. Other advantages and effects of the present invention will be readily apparent to those skilled in the art from the disclosure herein.

Referring to the drawings, the NPSS detection apparatus includes modules as shown in fig. 1, including a down-sampling module, a sliding auto-correlation module (AutoCorr), a coarse cross-correlation module, and a fine cross-correlation module.

M101 down-sampling module

The down-sampling module implements down-sampling from a sampling rate of 1.92MHz to 240K, inputting 1920= (137 × 14+2) samples for 1ms per sub-frame before down-sampling, outputting 238= (17 × 14) samples per sub-frame after down-sampling, and according to the following fixed down-sampling pattern:

the 1920 samples of each sub-frame are taken as 14 groups (14 OFDM symbols), the 1 st group of samples is 138, the 2 nd to 6 th groups of samples are 137, the 7 th group of samples is 138, and the 8 th to 14 th groups of samples are 137. The 1 st to 6 th groups are denoted as slot1 (slot 1), the 7 th to 14 th groups are denoted as slot2 (slot 2), the 1 st group of each slot is denoted as the first OFDM symbol, and the remaining groups are denoted as non-first OFDM symbols.

The first OFDM symbol (i.e., groups 1 and 7) of each slot is down-sampled with a pattern of {10,8,8,8,8,8,8,8,8,8 }; as shown in the upper half of fig. 2, 1 point is sampled every 10 points, 1 point is sampled every 8 points for the remaining sampling points, and so on.

The sampling pattern of the non-first OFDM symbol (i.e., groups 2-6, groups 8-14) is {9,8,8,8,8,8,8,8,8,8 }; as shown in the lower half of fig. 2, 1 point is sampled every 9 points, 1 point is sampled every 8 points for the remaining sampling points, and so on.

Thus, the number of down-sampled points of each OFDM symbol is 17, and the number of sampling points included in each 1ms duration is 238= (17 × 14).

FIG. 3 is a schematic diagram showing the comparison between the sampling point of the actual subframe and the sampling pattern in the practically randomly sampled 1ms time length, assuming that the starting position of the randomly sampled 1ms time window corresponds to the last OFDM symbol of the previous subframe, and the sampling pattern of the first group is {10,8,8,8,8,8,8,8,8,8,8,8,8,8,8,8,8}, so that the first 17 down-sampled data in the subframe corresponds to the 1 st point in the original CP section, the 2 nd, 10 th, … th, 122 nd point in the data section, and the down-sampling window corresponds to the first OFDM symbol of the subframe, and the sampling pattern is {9,8,8,8,8,8,8,8,8,8,8, 8}, so that the 17 data in the down-sampled subframe corresponds to the 3 rd point in the original CP section, the 1 st, 9 th, … th, 122 th and third down-sampling windows in the data segment correspond to the second OFDM symbol of the sub-frame, and the sampling pattern is still {9,8,8,8,8,8,8,8,8, 8}, so that the 17 down-sampled data in the sub-frame correspond to the 2 nd point in the original CP segment, the 1 st, 9 th, … th, 122 th point in the data segment, and so on.

Therefore, the fixed sampling pattern is adopted for down-sampling, the number of points after down-sampling in each OFDM symbol time length can be ensured to be the same, the error between sampling positions of an original OFDM symbol after down-sampling is ensured to be kept at the maximum 1 sampling point, and most OFDM sampling positions are free from error, so that the calculation amount of subsequent sliding autocorrelation is reduced, and the performance reduction caused by the down-sampling to the sliding autocorrelation is reduced to the maximum extent.

M201 sliding auto-correlation module

As shown in fig. 4, the primary synchronization code NB-PSS sequence of the narrowband wireless communication system is a short sequence in the frequency domain, occupies 11 REs in the frequency domain, occupies 11 consecutive OFDM symbols in the time domain, and is transmitted after being scrambled, as agreed in the protocol [36.211 ].

The number of sampling points of 1ms after down-sampling is 238, the primary processing object of the sliding autocorrelation module is the received time domain data in each wireless frame (10 ms) window time, the actual sliding autocorrelation module further comprises a data buffer for buffering the last 11 data of the OFDM symbols in the last wireless frame window, namely 11 sampling points, so that the actual primary processing object of the sliding autocorrelation module comprises 2380 sampling points +11 sampling points after down-sampling of one wireless frame, and the data of 2567 down-sampling points in total.

The beneficial effect of adding the data buffer in the sliding autocorrelation module is to prevent data missing detection, as shown in fig. 5, there may be a scenario where the starting position of the current 10ms processing window is just inside the frame of the real-sent NPSS subframe, and the data buffer with the added 11 OFDM symbol durations can ensure that at least one complete NPSS sequence is certainly stored in the increased sliding autocorrelation processing window.

As shown in fig. 6, the sample data in the processing window is shifted bit by bit as a start position t, and the sample is taken out from a duration window with a length of 11 OFDM symbols (i.e., 187 samples) as a sliding window.

The 187 samples within a sliding window are then divided into 11 groups of 17 samples, with the correlation accumulation being performed at intervals between two groups as shown in fig. 6, where the scrambling sequence for each OFDM symbol is also multiplied, as shown below,

in the above formula, the first and second carbon atoms are,、is the received sample point sequence, s, of the duration of the mth OFDM symbol from the tth sample point_m、s_m+1Is the scrambling code corresponding to these two OFDM symbol sequences, which represents the conjugate operation taken for each point in the sequence.

Preferably, the engineering practice also includes an alpha filtering operation of the autocorrelation result in a continuous wireless frame (10 ms) window

Thereby obtaining diversity combining gain and further improving the accuracy of detection.

Then, the power normalization is carried out on the sliding correlation result,

and judging whether the normalized sliding autocorrelation result is larger than a predefined threshold value, if so, determining that the wireless frame window contains NPSS (network provider service) and the approximate initial position is at the t-th sampling point, and transferring to a next coarse cross-correlation module, otherwise, transferring to the judgment of the next wireless frame window.

Preferably, the method further comprises the step of carrying out fractional frequency offset estimation and calibration on the down-sampled signal according to the sliding autocorrelation result.

As described above, since the initial sampling rate is 1.92MHz, the number of sampling points included in one OFDM symbol is 137, and thus the time length of one OFDM symbol is 137/1.92MHz, the phase rotation caused by the frequency offset over the time length of one OFDM symbol is:

where θ is the phase value of the autocorrelation result.

Therefore, the estimate of the frequency offset:

it should be noted that, when the phase rotation caused by the true frequency offset value on one OFDM symbol is smaller than pi, the estimation result in the above formula is the complete frequency offset value, but in general, as described in the background art, since the very large initial frequency offset of the narrowband wireless communication system will cause the phase rotation larger than pi, the estimation result in the above formula is only the fractional part of the frequency offset value, which is called the fractional frequency offset value.

Finally, according to the estimated decimal frequency offset value, the frequency offset calibration is carried out on the down-sampling sequence in the sliding window,

wherein λ is_iIs the sampling instant of the ith sample point.

M301Differential cross-correlation module

The differential cross-correlation module is started only when the sliding autocorrelation judges that NPSS exists, and is used for confirming the existence of the NPSS and estimating and calibrating integral multiple frequency offset, and preferably, timing deviation is eliminated.

First, a local sequence without frequency offset, denoted as d, is generated according to the protocol specification_i，d_iIs the same as the down-sampled received sequence and modulates d according to different integer frequency offsets_i。

In the background art, the maximum frequency deviation is + -25.5 KHz when a narrow-band wireless communication system encounters in cell search, and 5 possible integer frequency deviations exist in the range, respectivelyThe above-mentioned frequency offset values all fall within the maximum frequency offset range.

By way of enumeration, each integer frequency offset in the above assumptions is attempted to modulate the original native sequence.

Then, the modulated local sequence is correlated with the sampling sequence output by the sliding autocorrelation, the NPSS sequence within 11 OFDM symbol duration is divided into two segments with approximately equal length for differential correlation, i.e. the local sequence with the length of 187 points and the received sampling sequence are equally divided into two segments, the first segment is 94 points in length, the second segment is 93 points in length (or can be divided into the first segment 93 points and the second segment 94 points), and the two segments are correlated,

where denotes the conjugate operation.

In the conventional technical method in the art, most of the cross-correlation is obtained by performing correlation operation on a complete received sequence and a local sequence, but in the scheme of the invention, the complete synchronization sequence is split into two segments with approximately equal length, and then the two segments are respectively correlated with the local sequence. This is because NPSS can be mapped to different antenna ports for transmission in different radio frames as specified by the protocol, so that if the conventional means is sampled, NPSS local sequences and received sequences of one subframe length (187 points) are directly correlated, and cannot be combined among multiple radio frame windows to obtain combining gain; according to the scheme, two sections in the subframe are firstly differentiated and then correlated, the antenna port in one subframe is unchanged, and the differential correlation results among different wireless frames can still be combined, so that the problem of switching among the antenna ports among the wireless frames is avoided, and the combining gain is obtained.

The power normalization is carried out on the differential correlation results in the 10ms wireless frame, and the differential correlation results in a plurality of 10ms wireless frame windows are combined

Wherein,is normalized within the window of the last 10ms radio frameThe results of the conversion were obtained.

If the differential cross-correlation result is greater than the threshold value, finding a k value which maximizes the differential cross-correlation result,

the differential cross-correlation is considered to confirm that the NPSS signal has been successfully detected, and the corresponding frequency offset value is the integer frequency offset estimation result.

The total frequency deviation estimation result is the sum of decimal multiple and integral multiple frequency deviation estimation results。

The received NPSS sequence is frequency offset calibrated,

wherein λ is_iIs the sampling instant of the ith sample point.

In the preferred case of engineering, the differential cross-correlation module also includes processing of preliminary timing estimates. As described earlier, the initial local sequence d_iIs the same as the down-sampled received sequence (i.e., 240 kHz). If the process of preliminary timing estimation is needed, a local sequence with a high sampling rate is generated, and then a plurality of initial sample point offsets are tried and downsampled, for example, the sampling rate of the generated local sequence is 1.92MHz, as shown in fig. 7, the tried sample point offsets are j =0,1,2, …, 7 points, the downsampling rate is 8, and the corresponding downsampled sequence is recorded asThe down-sampled sequence is still 240kHz, then the differential cross-correlation is performed as described above, and the maximum differential cross-correlation result is found,

the corresponding sample point offset j is the initial timing estimator.

According to the simulation configuration (as shown in table 1) agreed by 3gpp, the device disclosed by the invention can obtain a detection success rate of more than 95%, and can achieve timing synchronization at 4T under better configuration_sampWithin (wherein T)_sampCorresponding to a 1.92MHz sampling interval), the frequency synchronization error is within 50Hz range

Table 1 performance simulation conditions

Claims

1. A synchronous detection device applied to a narrow-band wireless communication system terminal is characterized by comprising a down-sampling module, a sliding auto-correlation module and a differential cross-correlation module, wherein,

the down-sampling module down-samples the time domain signal of 1.92MHz sampling rate into a signal of 240kHz sampling rate according to a fixed down-sampling pattern by taking an OFDM symbol as a unit length;

the sliding autocorrelation module takes the bit-by-bit movement of sampling point data in a wireless frame processing window length of 10ms as an initial position t, takes the OFDM symbol duration with the length of 11 as a sliding window, divides the sampling points in the sliding window into 11 groups, and performs correlation accumulation at intervals of the sampling points between the two groups;

if the sliding autocorrelation obtained by the calculation of the sliding autocorrelation module is greater than a threshold value, starting the differential cross-correlation module;

the differential cross-correlation module differentiates the synchronous sequence in the sliding window obtained by the sliding self-correlation module into two parts with equal length, and performs cross-correlation accumulation with the locally generated synchronous sequence,

and if the differential cross-correlation result is larger than a threshold value, determining that the detected sequence is a main synchronization sequence.

2. The synchronization detection apparatus according to claim 1,

the down-sampling module divides sampling points of one subframe into 14 OFDM symbol lengths, the sampling patterns in the 1 st and 7 th OFDM symbol time lengths are {10,8,8,8,8,8,8,8,8, 8}, and the sampling patterns in the other OFDM symbol time lengths are {9,8,8,8,8,8,8,8,8,8,8,8,8,8,8,8,8 }.

3. The synchronization detection apparatus according to claim 1,

the sliding autocorrelation module further comprises a data buffer for buffering the down-sampled data of the last 11 OFDM symbol durations in the last 10ms wireless frame window, and the total processing data of the sliding autocorrelation module is a data sequence of one wireless frame and the last 11 OFDM symbols of the last wireless frame.

4. The synchronization detection apparatus according to claim 1,

before the sliding autocorrelation module performs correlation accumulation between two groups of data intervals of 11 groups of OFDM symbol duration in the sliding window, each group of data sequences needs to be multiplied by scrambling sequences;

the sliding autocorrelation module further needs to perform alpha filtering on a plurality of groups of sliding autocorrelation results of a plurality of 10ms wireless frame processing windows, and perform power normalization on the sliding autocorrelation results of each sliding window.

5. The synchronization detection apparatus according to claim 1,

the sliding autocorrelation module further comprises a sub-module for performing fractional frequency offset estimation and calibration according to the phase value of the sliding autocorrelation result, the fractional frequency offset estimation is calculated according to the following formula,

wherein, arctan { A_tThe result of sliding autocorrelation takes the phase value, 1.92MHz is the sampling rate of the initial time domain data, 137 is the number of samples of one OFDM symbol duration,

and the decimal frequency offset calibration processing is to carry out phase calibration according to the decimal frequency offset estimation value and the sampling time of each sampling point.

6. The synchronization detection apparatus according to claim 1,

and the differential cross-correlation module is used for carrying out power normalization on the differential correlation results and combining the differential correlation results in a plurality of 10ms wireless frame windows.

7. The synchronization detection apparatus according to claim 1,

the differential cross-correlation module further comprises an estimation and calibration sub-module for integer multiple frequency offset,

the integer frequency offset estimation comprises enumerating all possible integer frequency offset values in the maximum frequency offset range to modulate the local sequence, finding out the maximum value of the module value of the result of the differential cross-correlation under each frequency offset value, wherein the frequency offset value corresponding to the maximum module value is the integer frequency offset value,

and the integer frequency offset calibration submodule carries out phase compensation according to the integer frequency offset estimation value and the sampling time of each sampling point.

8. The synchronization detection apparatus according to claim 1,

the differential cross-correlation module further comprises a timing offset estimation sub-module,

the timing offset estimation submodule firstly generates a local sequence with high sampling rate, then enumerates a plurality of timing offsets, down-samples the local sequence to the sampling rate of 240kHz, respectively performs differential cross-correlation with the received data sequence, and takes the timing offset enumerated value corresponding to the maximum module value of the differential cross-correlation value as the estimated timing offset value.

9. A synchronous detection method applied to a narrow-band wireless communication system terminal is characterized by comprising the following processes

Step S101, a down-sampling process, namely down-sampling a time domain signal with a sampling rate of 1.92MHz into a signal with a sampling rate of 240kHz according to a fixed down-sampling pattern by taking an OFDM symbol as a unit length;

step S201, a sliding self-correlation process, namely moving sampling point data in a wireless frame processing window length of 10ms bit by bit to serve as an initial position t, taking an OFDM symbol duration with the length of 11 as a sliding window, dividing sampling points in the sliding window into 11 groups, and performing correlation accumulation at intervals of the sampling points between the two groups;

if the sliding autocorrelation obtained by the calculation of the sliding autocorrelation process is greater than a threshold value, starting a differential cross-correlation process;

step S301, a differential cross-correlation process, which is to differentiate the synchronization sequence in the sliding window obtained in the sliding auto-correlation process into two parts with equal length, and perform cross-correlation accumulation with the locally generated synchronization sequence,