CN106655793B - A kind of common resonant inductive type wide input range LLC resonant converter - Google Patents
A kind of common resonant inductive type wide input range LLC resonant converter Download PDFInfo
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- CN106655793B CN106655793B CN201710070060.4A CN201710070060A CN106655793B CN 106655793 B CN106655793 B CN 106655793B CN 201710070060 A CN201710070060 A CN 201710070060A CN 106655793 B CN106655793 B CN 106655793B
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- 230000033228 biological regulation Effects 0.000 abstract description 3
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- 238000006243 chemical reaction Methods 0.000 description 3
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- 230000005611 electricity Effects 0.000 description 3
- 239000000446 fuel Substances 0.000 description 3
- 238000010248 power generation Methods 0.000 description 2
- 239000004065 semiconductor Substances 0.000 description 2
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Classifications
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/338—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement
- H02M3/3381—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement using a single commutation path
-
- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02M—APPARATUS FOR CONVERSION BETWEEN AC AND AC, BETWEEN AC AND DC, OR BETWEEN DC AND DC, AND FOR USE WITH MAINS OR SIMILAR POWER SUPPLY SYSTEMS; CONVERSION OF DC OR AC INPUT POWER INTO SURGE OUTPUT POWER; CONTROL OR REGULATION THEREOF
- H02M3/00—Conversion of dc power input into dc power output
- H02M3/22—Conversion of dc power input into dc power output with intermediate conversion into ac
- H02M3/24—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters
- H02M3/28—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac
- H02M3/325—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal
- H02M3/335—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only
- H02M3/338—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement
- H02M3/3385—Conversion of dc power input into dc power output with intermediate conversion into ac by static converters using discharge tubes with control electrode or semiconductor devices with control electrode to produce the intermediate ac using devices of a triode or a transistor type requiring continuous application of a control signal using semiconductor devices only in a self-oscillating arrangement with automatic control of output voltage or current
-
- Y—GENERAL TAGGING OF NEW TECHNOLOGICAL DEVELOPMENTS; GENERAL TAGGING OF CROSS-SECTIONAL TECHNOLOGIES SPANNING OVER SEVERAL SECTIONS OF THE IPC; TECHNICAL SUBJECTS COVERED BY FORMER USPC CROSS-REFERENCE ART COLLECTIONS [XRACs] AND DIGESTS
- Y02—TECHNOLOGIES OR APPLICATIONS FOR MITIGATION OR ADAPTATION AGAINST CLIMATE CHANGE
- Y02B—CLIMATE CHANGE MITIGATION TECHNOLOGIES RELATED TO BUILDINGS, e.g. HOUSING, HOUSE APPLIANCES OR RELATED END-USER APPLICATIONS
- Y02B70/00—Technologies for an efficient end-user side electric power management and consumption
- Y02B70/10—Technologies improving the efficiency by using switched-mode power supplies [SMPS], i.e. efficient power electronics conversion e.g. power factor correction or reduction of losses in power supplies or efficient standby modes
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- Engineering & Computer Science (AREA)
- Power Engineering (AREA)
- Dc-Dc Converters (AREA)
Abstract
The invention discloses a kind of common resonant inductive type wide input range LLC resonant converters, belong to converters technical field.The converter is made of input source, primary side switch network, common resonant inductance, two resonant capacitances, two transformers, secondary side rectification circuit, output filter capacitor and output loading, and the input voltage range of converter is widened by the way of dynamic regulation topological structure.The present invention contains a distinctive operating mode, voltage gain is 0.75 times of conventional full bridge LLC resonant converter, the input voltage range of single operating mode can be obviously reduced in this, optimal cavity parameter, improve transformer utilization factor, device cost is reduced, the efficiency and power density of Lifting Transform device meet the needs of wide input range occasion high efficiency and high power density.
Description
Technical field
The present invention relates to a kind of common resonant inductive type wide input range LLC resonant converters, belong to Technics of Power Electronic Conversion
Device technical field especially belongs to isolated DC-direct current energy converter technique field.
Background technique
With getting worse for environmental pollution and energy shortage problem, renewable energy is increasingly valued by people.
Renewable energy power generation form mainly has photovoltaic power generation, wind-power electricity generation, water generating and fuel cell-powered etc., they all have
The wide feature of output voltage range.Therefore, in order to efficiently utilize renewable energy, energy waste is reduced, one kind is needed
The DC/DC converter that can be worked in wide input voltage range.
In recent years, traditional LLC controlled resonant converter because high-efficient, power density is high, it is at low cost due to be widely used.It
The Sofe Switch of all power semiconductors may be implemented, reduce electromagnetic interference, realize high frequency.Attached tradition shown in FIG. 1 is complete
Shown in the voltage gain expression formula such as formula (1) of bridge LLC resonant converter.It is in document the experimental results showed that, input voltage range
MrangeAt 1.5 times or so, the entire working range efficiency relative equilibrium of traditional LLC controlled resonant converter.Input voltage range is wider,
Magnetizing inductance (the L of converterm) it is smaller, caused by circulation it is bigger, the efficiency of entire working range is also lower.Therefore, traditional
LLC resonant converter is not appropriate for the wide occasion of input voltage range.
In formula, inductance ratio k=Lm/Lr, switching frequency (fs) one change value f of markn=2 π fs(LrCr)0.5, load (Ro) mark one
Change value Q=π2(Lr/Cr)0.5/(8n2Ro)。
In order to expand the input voltage range of traditional LLC controlled resonant converter, document " Z.Liang, R.Guo, G.Wang, A.
Huang.A new wide input range high efficiency photovoltaic inverter[C].IEEE
Energy Conversion Congr.and Expos., Atlanta, USA:IEEE, 2010:2937-2943 " are in attached drawing 1
On the basis of propose the mode of dynamic regulation topological structure.As the switching tube S of conventional full bridge LLC resonant converter in attached drawing 1P3Place
Yu Changguan, switching tube SP4In it is normally opened when, conventional half-bridge LLC resonant converter that converter will be equivalent in Fig. 2.Half-bridge LLC
Controlled resonant converter is because of resonant capacitance CrThere are DC offset voltage 0.5Uin, voltage gain only has the one of full-bridge LLC resonant converter
Half, as shown in formula (2).(high-gain operating mode and low gain Working mould are denoted as respectively herein using both operating modes
Formula) jointly control after, in Fig. 1 conventional full bridge LLC resonant converter expand after transducer gain it is as shown in Figure 3.By formula (1),
Formula (2) and attached drawing 3 are it is found that input voltage range M of the converter under single operating moderange>=2 times, it just can guarantee two kinds
The gain of operating mode is connected.Although total input voltage range of two operating modes reaches 4 times or more (2Mrange), but in list
A operating mode input voltage range will be in the case where at least 2 times, efficiency and unbalanced, table of the converter in entire working range
It is now unoutstanding.
In order to further enhance the efficiency of each operating point, document " Haibing Hu, Xiang Fang, Frank Chen,
Z.John Shen, Issa Batarseh.A Modified High-Efficiency LLC Converter With Two
Transformers for Wide Input-Voltage Range Applications[J].IEEE Trans.Power
Electron., Apr.2013,28 (4): 1946-1960 " proposes dual transformer type wide input range LLC as shown in Fig. 4
Controlled resonant converter.On the basis of original high-gain or low gain operating mode, pass through the second transformer (T2) incision with
No, there are four types of operating modes in total for dual transformer type LLC resonant converter.Every kind of operating mode input voltage range is at 1.5 times
Left and right, hence it is evident that improve the efficiency in entire working range.But wherein under two kinds of operating modes, transformer (T2) be short-circuited,
Energy is not transmitted, magnetic core utilization rate is reduced.In hardware composition, secondary side rectifying tube number is more, the more short-circuit transformations of primary side
Device (T2) two switching tube (SP5And SP6), corresponding driving circuit (such as isolation optocoupler driving) and supervisor (SP1、SP2、SP3With
SP4) driving circuit (such as charge pump half-bridge driven chip) is inconsistent, increase the complexity of hardware.
In the occasions such as fuel cell-powered, the input voltage range of converter is at 2~3 times.Above two scheme
Total input voltage range design value reaches 4 times, it appears and it is wide, and the device cost of converter can be brought to increase and efficiency sacrifice.
Summary of the invention
The purpose of the present invention is in view of the deficiencies of the prior art, provide a kind of common resonant for wide input voltage range occasion
Inductive type wide input range LLC resonant converter.
The purpose of the present invention is achieved through the following technical solutions:
A kind of common resonant inductive type wide input range LLC resonant converter is by input source (Uin), primary side switch net
Network (10), common resonant inductance (Lr), the first resonant capacitance (Cr1), the second resonant capacitance (Cr2), the first transformer (T1), second
Transformer (T2), secondary side rectification circuit (20), output filter capacitor (Co) and output loading (Ro) constitute, wherein the first transformer
(T1) primary side magnetizing inductance value be Lm1, the second transformer (T2) primary side magnetizing inductance value be Lm2；The primary side switch network
(10) input both ends respectively with input source (Uin) both ends be connected, the output end b and the first resonance of primary side switch network (10)
Capacitor (Cr1) one end be connected, the first resonant capacitance (Cr1) other end and the first transformer (T1) primary side winding different name end phase
Even, the first transformer (T1) primary side winding Same Name of Ends and the second transformer (T2) primary side winding Same Name of Ends, common resonant inductance
(Lr) one end be connected, common resonant inductance (Lr) the other end be connected with the output end a of primary side switch network (10), second become
Depressor (T2) primary side winding different name end and the second resonant capacitance (Cr2) one end be connected, the second resonant capacitance (Cr2) the other end
It is connected with the output end c of primary side switch network (10), the first transformer (T1) vice-side winding Same Name of Ends and secondary side rectification circuit
(20) input terminal d is connected, the input terminal e of secondary side rectification circuit (20) and the second transformer (T2) vice-side winding different name end phase
Even, the second transformer (T2) vice-side winding Same Name of Ends and the first transformer (T1) vice-side winding different name end be connected, secondary side is whole
The output both ends of current circuit (20) respectively with output filter capacitor (Co) both ends, output loading (Ro) both ends be connected.
Primary side switch network (10) the output positive pulse amplitude is Uin, negative pulse amplitude be-UinOr 0, positive negative pulse stuffing is wide
The square-wave voltage u that degree is 50%abAnd uac, and the phase of the two square-wave voltages is consistent.
The primary side switch network (10) is two bridge arm switching networks, it is by first switch tube (SP1), second switch
(SP2), third switching tube (SP3) and the 4th switching tube (SP4) constitute, first switch tube (SP1) drain electrode and third switching tube
(SP3) drain electrode, input source (Uin) anode be connected, first switch tube (SP1) source electrode and second switch (SP2) drain electrode,
Primary side switch network (10) output end a is connected, second switch (SP2) source electrode and the 4th switching tube (SP4) source electrode, input
Source (Uin) cathode, primary side switch network (10) output end c be connected, the 4th switching tube (SP4) drain electrode and third switching tube
(SP3) source electrode, primary side switch network (10) output end b be connected.
The primary side switch network (10) is three bridge arm switching networks, it is by first switch tube (SP1), second switch
(SP2), third switching tube (SP3), the 4th switching tube (SP4), the 5th switching tube (SP5) and the 6th switching tube (SP6) constitute, first
Switching tube (SP1) drain electrode and third switching tube (SP3) drain electrode, the 5th switching tube (SP5) drain electrode, input source (Uin) just
Extremely it is connected, first switch tube (SP1) source electrode and second switch (SP2) drain electrode, primary side switch network (10) output end a phase
Even, second switch (SP2) source electrode and the 4th switching tube (SP4) source electrode, the 6th switching tube (SP6) source electrode, input source
(Uin) cathode be connected, the 4th switching tube (SP4) drain electrode and third switching tube (SP3) source electrode, primary side switch network (10) it is defeated
Outlet b is connected, the 6th switching tube (SP6) drain electrode and the 5th switching tube (SP5) source electrode, primary side switch network (10) output end c
It is connected.
The secondary side rectification circuit (20) is full bridge rectifier, it is by the first rectifier diode (D1), second rectification two
Pole pipe (D2), third rectifier diode (D3) and the 4th rectifier diode (D4) constitute, the first rectifier diode (D1) anode and
The input terminal d of secondary side rectification circuit (20), the second rectifier diode (D2) cathode be connected, the second rectifier diode (D2) sun
Pole and the 4th rectifier diode (D4) anode, output filter capacitor (Co) cathode, output loading (Ro) cathode be connected, the
Four rectifier diode (D4) cathode and secondary side rectification circuit (20) input terminal e, third rectifier diode (D3) anode phase
Even, third rectifier diode (D3) cathode and the first rectifier diode (D1) cathode, output filter capacitor (Co) anode,
Output loading (Ro) anode be connected.
The secondary side rectification circuit (20) is a kind of voltage doubling rectifing circuit, it is by the first rectifier diode (D1), it is second whole
Flow diode (D2), the first voltage multiplying rectifier capacitor (Co1) and the second voltage multiplying rectifier capacitor (Co2) constitute, the first rectifier diode
(D1) anode and secondary side rectification circuit (20) input terminal d, the second rectifier diode (D2) cathode be connected, second rectification two
Pole pipe (D2) anode and the second voltage multiplying rectifier capacitor (Co2) cathode, output filter capacitor (Co) cathode, output loading (Ro)
Cathode be connected, the second voltage multiplying rectifier capacitor (Co2) anode and secondary side rectification circuit (20) input terminal e, the first voltage multiplying rectifier
Capacitor (Co1) cathode be connected, the first voltage multiplying rectifier capacitor (Co1) anode and the first rectifier diode (D1) cathode, output
Filter capacitor (Co) anode, output loading (Ro) anode be connected.
The secondary side rectification circuit (20) is another voltage doubling rectifing circuit, it is by the first rectifier diode (D1), second
Rectifier diode (D2), auxiliary voltage multiplying rectifier capacitor (Caux) constitute, assist voltage multiplying rectifier capacitor (Caux) cathode and secondary side it is whole
The input terminal d of current circuit (20) is connected, and assists voltage multiplying rectifier capacitor (Caux) anode and the first rectifier diode (D1) sun
Pole, the second rectifier diode (D2) cathode be connected, the first rectifier diode (D1) cathode and output filter capacitor (Co) just
Pole, output loading (Ro) anode be connected, the second rectifier diode (D2) anode and secondary side rectification circuit (20) input terminal e,
Output filter capacitor (Co) cathode, output loading (Ro) cathode be connected.
The essential distinction of technical solution of the present invention and existing technical solution is, traditional LLC resonant cavity is split into two
Branch, two branch common resonant inductance respectively contain a resonant capacitance and a transformer, and two transformer secondaries are connected,
Two transformers work at the same time always, when resonant capacitance DC offset voltage is 0, and in another branch in a wherein branch
Resonant capacitance DC offset voltage is 0.5UinWhen, there is specific operating mode of the invention in converter, as shown in formula (3)
Voltage gain, be 0.75 times of formula (1) conventional full bridge LLC converter, 1.5 times of formula (2) conventional half-bridge LLC converter, this
The input voltage range of single operating mode can be obviously reduced, optimal cavity parameter improves transformer utilization factor, reduces device
Part cost, the efficiency and power density of Lifting Transform device meet wide input voltage range occasion high efficiency and high power density
Demand.
The invention has the following beneficial effects:
(1) input voltage range under single operating mode is obviously reduced, and LLC resonator parameter is optimized, and is promoted whole
The efficiency of a working range；
(2) two transformers work at the same time always, and utilization rate improves, and reduce volume, hoisting power density；
(3) power semiconductor number is obviously reduced, and reduces cost, hoisting power density；
(4) driving circuit of primary side switch pipe is consistent, and reduces cost.
Detailed description of the invention
Attached drawing 1 is conventional full bridge LLC resonant converter schematic diagram；
Attached drawing 2 is conventional half-bridge LLC resonant converter schematic diagram；
Attached drawing 3 is after conventional full bridge LLC resonant converter is jointly controlled using two kinds of operating modes of high-gain and low gain
Voltage gain schematic diagram；
Attached drawing 4 is traditional dual transformer type wide input range LLC resonant converter schematic diagram；
Attached drawing 5 is a kind of common resonant inductive type wide input range LLC resonant converter schematic diagram of the invention；
Attached drawing 6 is that primary side switch network (10) of the present invention is used using two bridge arm switching networks, secondary side rectification circuit (20)
A kind of common resonant inductive type wide input range LLC resonant converter schematic diagram of full bridge rectifier；
Attached drawing 7 is that primary side switch network (10) of the present invention is used using two bridge arm switching networks, secondary side rectification circuit (20)
A kind of a kind of common resonant inductive type wide input range LLC resonant converter schematic diagram of voltage doubling rectifing circuit；
Attached drawing 8 is that primary side switch network (10) of the present invention is used using two bridge arm switching networks, secondary side rectification circuit (20)
A kind of another common resonant inductive type wide input range LLC resonant converter schematic diagram of voltage doubling rectifing circuit；
Attached drawing 9 is that primary side switch network (10) of the present invention is used using three bridge arm switching networks, secondary side rectification circuit (20)
A kind of common resonant inductive type wide input range LLC resonant converter schematic diagram of full bridge rectifier；
Attached drawing 10 is that primary side switch network (10) of the present invention is used using three bridge arm switching networks, secondary side rectification circuit (20)
A kind of a kind of common resonant inductive type wide input range LLC resonant converter schematic diagram of voltage doubling rectifing circuit；
Attached drawing 11 is that primary side switch network (10) of the present invention is used using three bridge arm switching networks, secondary side rectification circuit (20)
A kind of another common resonant inductive type wide input range LLC resonant converter schematic diagram of voltage doubling rectifing circuit；
Attached drawing 12 is the primary side switch pipe control strategy schematic diagram in low gain operating mode of converter shown in attached drawing 6；
Attached drawing 13 is the exemplary operation waveform diagram in middle gain operating mode of converter shown in attached drawing 6；
Attached drawing 14~16 is the t in attached drawing 13 of converter shown in attached drawing 60~t1、t1~t2、t2~t3Each mould in period
State equivalent circuit (current direction is labeled as positive direction in figure)；
Attached drawing 17 is Fundamental Wave Equivalent Circuit schematic diagram of the converter shown in attached drawing 6 in middle gain operating mode；
Attached drawing 18 be converter shown in attached drawing 6 use in two kinds of operating modes of gain and low gain jointly control after voltage
Gain schematic diagram；
Attached drawing 19 is the primary side switch pipe control strategy schematic diagram in high-gain operating mode of converter shown in attached drawing 9；
Attached drawing 20 is that converter shown in attached drawing 9 is jointly controlled using three kinds of high-gain, middle gain and low gain operating modes
Voltage gain schematic diagram afterwards；
Designation in the figures above: UinFor input source；10 be primary side switch network；A, b, c are primary side switch network
(10) three output ports；20 be secondary side rectification circuit；D, e is two input ports of secondary side rectification circuit (20)；LrFor
Common resonant inductance；CrFor resonant capacitance；Cr1For the first resonant capacitance；Cr2For the second resonant capacitance；T1For the first transformer；
T2For the second transformer；LmFor the primary side magnetizing inductance of transformer；Lm1For the first transformer (T1) primary side magnetizing inductance； Lm2
For the second transformer (T2) primary side magnetizing inductance；N: 1 is transformer turns ratio；n1: 1 or n1: be first transformer (T at 1: 11)
The former pair side turn ratio；n2: 1 or n2: be second transformer (T at 1: 12) the secondary side turn ratio of original；SP1、SP2、SP3、SP4、SP5And SP6Respectively
For primary side the first, second, third, fourth, the 5th and the 6th switching tube；D1、D2、D3、D4、D5、D6、 D7、D8Respectively first,
Two, the rectifier diode of third, the four, the five, the six, the 7th and the 8th；CoFor output filter capacitor；Co1And Co2It is first,
Voltage-doubler rectification capacitor；CauxTo assist voltage multiplying rectifier capacitor；RoFor output loading； UoFor output voltage；IoTo export electric current；M
For voltage gain；fnTo mark a Switching frequency；fnminFor the one change value of mark of lowermost switch frequency；fnmaxFor highest switching frequency
One change value of mark；iLr、iLr1、iLr2Respectively flow through Lr、Cr1、Cr2Electric current； im1、im2Respectively flow through Lm1、Lm2Electric current；
isFor the electric current for flowing through two transformer secondaries；uLr、uCr1、uCr2Respectively Lr、Cr1、Cr2The voltage at both ends；uGSP1、uGSP2、
uGSP3、uGSP4、uGSP5And uGSP6Respectively switching tube SP1、SP2、 SP3、SP4、SP5And SP6Driving voltage；uabFor primary side switch net
Network (10) two voltage between port a, b, uacFor the voltage between two ports a, c；UiacFor positive negative pulse stuffing amplitude ± Uin、
The fundametal compoment of the square-wave voltage of pulse width 50%；ILr、ILr1、ILr2、Im1、Im2、IsRespectively iLr、iLr1、iLr2、im1、im2、
isFundametal compoment；ULr、UCr1、UCr2Respectively uLr、uCr1、uCr2Fundametal compoment；t0、t1、t2、t3And t4For the time.
Specific embodiment
Technical solution of the present invention is described in detail in conjunction with attached drawing.
As shown in Fig. 5, a kind of common resonant inductive type wide input range LLC resonant converter is by input source
(Uin), primary side switch network (10), common resonant inductance (Lr), the first resonant capacitance (Cr1), the second resonant capacitance (Cr2),
One transformer (T1), the second transformer (T2), secondary side rectification circuit (20), output filter capacitor (Co) and output loading (Ro) structure
At wherein the first transformer (T1) primary side magnetizing inductance value be Lm1, the second transformer (T2) primary side magnetizing inductance value be Lm2；
The input both ends of the primary side switch network (10) respectively with input source (Uin) both ends be connected, primary side switch network (10) it is defeated
Outlet b and the first resonant capacitance (Cr1) one end be connected, the first resonant capacitance (Cr1) other end and the first transformer (T1) primary side
The different name end of winding is connected, the first transformer (T1) primary side winding Same Name of Ends and the second transformer (T2) primary side winding it is of the same name
End, common resonant inductance (Lr) one end be connected, common resonant inductance (Lr) the other end and primary side switch network (10) output
A is held to be connected, the second transformer (T2) primary side winding different name end and the second resonant capacitance (Cr2) one end be connected, the second resonance
Capacitor (Cr2) the other end be connected with the output end c of primary side switch network (10), the first transformer (T1) vice-side winding it is of the same name
End is connected with the input terminal d of secondary side rectification circuit (20), the input terminal e of secondary side rectification circuit (20) and the second transformer (T2)
Vice-side winding different name end is connected, the second transformer (T2) vice-side winding Same Name of Ends and the first transformer (T1) vice-side winding it is different
Name end be connected, the output both ends of secondary side rectification circuit (20) respectively with output filter capacitor (Co) both ends, output loading (Ro) two
End is connected.
In the present invention, primary side switch network (10) the output positive pulse amplitude is Uin, negative pulse amplitude be-UinOr
0, the square-wave voltage u that positive negative pulse stuffing width is 50%abAnd uac, and the phase of the two square-wave voltages is consistent.In order to realize
This purpose, the primary side switch network (10) can be two bridge arm switching networks or three bridge arm switching networks.
As shown in attached drawing 6, attached drawing 7 or attached drawing 8, the primary side switch network (10) is two bridge arm switching networks, it is by the
One switching tube (SP1), second switch (SP2), third switching tube (SP3) and the 4th switching tube (SP4) constitute, first switch tube
(SP1) drain electrode and third switching tube (SP3) drain electrode, input source (Uin) anode be connected, first switch tube (SP1) source electrode
With second switch (SP2) drain electrode, primary side switch network (10) output end a be connected, second switch (SP2) source electrode and
Four switching tube (SP4) source electrode, input source (Uin) cathode, primary side switch network (10) output end c be connected, the 4th switching tube
(SP4) drain electrode and third switching tube (SP3) source electrode, primary side switch network (10) output end b be connected.
As shown in attached drawing 9, attached drawing 10 or attached drawing 11, the primary side switch network (10) be three bridge arm switching networks, it by
First switch tube (SP1), second switch (SP2), third switching tube (SP3), the 4th switching tube (SP4), the 5th switching tube (SP5)
With the 6th switching tube (SP6) constitute, first switch tube (SP1) drain electrode and third switching tube (SP3) drain electrode, the 5th switching tube
(SP5) drain electrode, input source (Uin) anode be connected, first switch tube (SP1) source electrode and second switch (SP2) drain electrode,
Primary side switch network (10) output end a is connected, second switch (SP2) source electrode and the 4th switching tube (SP4) source electrode, the 6th
Switching tube (SP6) source electrode, input source (Uin) cathode be connected, the 4th switching tube (SP4) drain electrode and third switching tube (SP3)
Source electrode, primary side switch network (10) output end b are connected, the 6th switching tube (SP6) drain electrode and the 5th switching tube (SP5) source electrode,
Primary side switch network (10) output end c is connected.
As shown in attached drawing 6 or attached drawing 9, the secondary side rectification circuit (20) is full bridge rectifier, it is by the first rectification two
Pole pipe (D1), the second rectifier diode (D2), third rectifier diode (D3) and the 4th rectifier diode (D4) constitute, first is whole
Flow diode (D1) anode and secondary side rectification circuit (20) input terminal d, the second rectifier diode (D2) cathode be connected, the
Two rectifier diode (D2) anode and the 4th rectifier diode (D4) anode, output filter capacitor (Co) cathode, output it is negative
Carry (Ro) cathode be connected, the 4th rectifier diode (D4) cathode and secondary side rectification circuit (20) input terminal e, third rectification
Diode (D3) anode be connected, third rectifier diode (D3) cathode and the first rectifier diode (D1) cathode, output
Filter capacitor (Co) anode, output loading (Ro) anode be connected.
As shown in attached drawing 7 or attached drawing 10, the secondary side rectification circuit (20) is a kind of voltage doubling rectifing circuit, it is whole by first
Flow diode (D1), the second rectifier diode (D2), the first voltage multiplying rectifier capacitor (Co1) and the second voltage multiplying rectifier capacitor (Co2) structure
At the first rectifier diode (D1) anode and secondary side rectification circuit (20) input terminal d, the second rectifier diode (D2) yin
Extremely it is connected, the second rectifier diode (D2) anode and the second voltage multiplying rectifier capacitor (Co2) cathode, output filter capacitor (Co)
Cathode, output loading (Ro) cathode be connected, the second voltage multiplying rectifier capacitor (Co2) anode and secondary side rectification circuit (20)
Input terminal e, the first voltage multiplying rectifier capacitor (Co1) cathode be connected, the first voltage multiplying rectifier capacitor (Co1) anode and first rectification
Diode (D1) cathode, output filter capacitor (Co) anode, output loading (Ro) anode be connected.
As shown in attached drawing 8 or attached drawing 11, the secondary side rectification circuit (20) is another voltage doubling rectifing circuit, it is by first
Rectifier diode (D1), the second rectifier diode (D2), auxiliary voltage multiplying rectifier capacitor (Caux) constitute, assist voltage multiplying rectifier capacitor
(Caux) cathode be connected with the input terminal d of secondary side rectification circuit (20), assist voltage multiplying rectifier capacitor (Caux) anode and first
Rectifier diode (D1) anode, the second rectifier diode (D2) cathode be connected, the first rectifier diode (D1) cathode and defeated
Filter capacitor (C outo) anode, output loading (Ro) anode be connected, the second rectifier diode (D2) anode and the rectification of secondary side
Input terminal e, the output filter capacitor (C of circuit (20)o) cathode, output loading (Ro) cathode be connected.
The purpose of the present invention is the isolated DC of high efficiency and high power density is realized for wide input voltage range occasion
Transformation, in order to realize the purpose, the present invention widens the input voltage range of converter by the way of dynamic regulation topological structure.
Traditional LLC resonant cavity is split into two branches by the present invention, and two branch common resonant inductance respectively contain a resonant capacitance
With a transformer, the series connection of two transformer secondaries, two transformers are worked at the same time always, when resonant capacitance in a wherein branch
DC offset voltage is 0, and resonant capacitance DC offset voltage is 0.5U in another branchinWhen, there is this hair in converter
Bright specific operating mode, the voltage gain as shown in formula (3) is 0.75 times, formula of formula (1) conventional full bridge LLC converter
(2) 1.5 times of conventional half-bridge LLC converter, the input voltage range of single operating mode can be obviously reduced in this, optimize humorous
Vibration chamber parameter, improves transformer utilization factor, reduces device cost, and the efficiency and power density of Lifting Transform device meet wide input
The demand of voltage range occasion high efficiency and high power density.
Two bridge arm switching networks, secondary side rectification circuit (20) are used with attached primary side switch network (10) shown in fig. 6 below
For a kind of common resonant inductive type wide input range LLC resonant converter of full bridge rectifier, illustrate of the invention
Working principle.In attached drawing 6, Lm1=Lm2=2Lm, Cr1=Cr2=0.5Cr, n1=n2=2n.In the prior art, in order to meet function
Rate demand, converter resonant capacitance CrOften need multiple thin-film capacitors in parallel.Therefore, compared with converter in existing literature, attached drawing 6
In converter resonant capacitance volume not will increase.The converter uses frequency control, low gain operating mode and middle gain work
Primary side switch pipe control strategy under operation mode is respectively as shown in attached drawing 12 and attached drawing 13.
In the low gain operating mode of attached drawing 12, (the S of converter primary side third switching tube shown in attached drawing 6P3) driving uGSP3
It keeps often closing, the 4th switching tube (SP4) driving uGSP4It maintains a normally open, first switch tube (SP1) driving uGSP1And second switch
(SP2) driving uGSP2For the complementary conducting of duty ratio 50%.The square-wave voltage u of switching network (10) outputab、uacPositive pulse width
Value is all Uin, negative pulse amplitude be all that 0, positive negative pulse stuffing width is all 50%, the two phase is consistent.Under low gain operating mode,
The converter can be equivalent to the conventional half-bridge LLC converter in Fig. 2, shown in voltage gain such as formula (2), not remake herein in detail
Description.
Attached drawing 13 gives attached primary side switch network (10) shown in fig. 6 using two bridge arm switching networks, secondary side rectified current
Road (20) is using a kind of common resonant inductive type wide input range LLC resonant converter of full bridge rectifier in middle gain work
Exemplary operation waveform when operation mode.In attached drawing 13, the converter primary side first switch tube (SP1) driving uGSP1It is opened with the 4th
Close pipe (SP4) driving uGSP4It is consistent, second switch (SP2) driving uGSP2With third switching tube (SP3) driving uGSP3It keeps
Unanimously, uGSP1And uGSP2For the complementary conducting of duty ratio 50%.The square-wave voltage u of switching network (10) outputabPositive negative pulse stuffing width
Value is ± Uin, square-wave voltage uacPositive pulse amplitude is Uin, negative pulse amplitude be 0, uab、uacPositive negative pulse stuffing width is all
50%, the two phase is consistent.
t0Moment, primary side first switch tube (SP1) and the 4th switching tube (S of primary sideP4) simultaneously turn off, four switching tubes of primary side
(SP1、 SP2、SP3And SP4) all in off state, secondary current isIt is 0, four, secondary side rectifying tube (D1、D2、D3And D4) not
Conducting, the magnetizing inductance (L of the first transformerm1), the magnetizing inductance (L of the second transformerm2) and shared resonant inductance (Lr), first
Resonant capacitance (Cr1), the second resonant capacitance (Cr2) common resonance, in the process, primary side second switch (SP2) and third open
Close pipe (SP3) drain-source voltage is reduced to 0, it opens and gets ready for no-voltage, output filter capacitor (Co) to output loading (Ro)
Power supply, t0~t1Mode equivalent circuit in period is as shown in Fig. 14.
t1Moment, primary side second switch (SP2) and third switching tube (SP3) realize that no-voltage is open-minded, the first transformer
Magnetizing inductance (Lm1), the magnetizing inductance (L of the second transformerm2) exported (Uo) it is refracted to the voltage reversal clamp of primary side, im1、
im2Electric current linear decline, common resonant inductance (Lr), the first resonant capacitance (Cr1), the second resonant capacitance (Cr2) common resonance, it is defeated
Enter source (Uin) to resonant cavity and load provide energy, iLr1With im1Difference and secondary side refraction electric current is/n1It is equal, iLr2With im2
Difference and secondary side refraction electric current is/n2It is equal, secondary the second rectifier diode of side (D2) and third rectifier diode (D3) in stream
Overcurrent is, with output filter capacitor (Co) jointly to output loading (Ro) power supply, t1~t2Mode equivalent circuit in period
As shown in Fig. 15.
t2Moment, resonance current (i equal with excitation currentLr1=im1, iLr2=im2), the second rectifier diode (D2) and the
Three rectifier diode (D3) realize zero-current switching, the magnetizing inductance (L of the first transformerm1), the magnetizing inductance of the second transformer
(Lm2) and secondary side disengagement, with shared resonant inductance (Lr), the first resonant capacitance (Cr1), the second resonant capacitance (Cr2) common humorous
Vibration, input source (Uin) to resonant cavity storage energy, output filter capacitor (Co) to output loading (Ro) power supply, t2~t3Period
Interior mode equivalent circuit is as shown in Fig. 16.
t3Moment, primary side second switch (SP2) and third switching tube (SP3) simultaneously turn off, lower half of switch periods start,
The course of work is similar, is not repeated to describe.
In the whole work process of attached drawing 13, the first resonant capacitance (Cr1) DC offset voltage be 0, the second resonance electricity
Hold (Cr2) DC offset voltage be 0.5Uin.Attached drawing 17 is Fundamental Wave Equivalent Circuit of the converter under middle gain operating mode,
Converter voltage gain at this time is derived using fundamental Wave Analysis, as shown in formula (3).Voltage gain under middle gain operating mode
It is 0.75 times of formula (1) conventional full bridge LLC converter, 1.5 times of formula (2) conventional half-bridge LLC converter.Middle gain operating mode
It is operating mode specific to the present invention.
After being jointly controlled using two kinds of operating modes of low gain and middle gain, the voltage gain model of converter shown in attached drawing 6
It encloses to have obtained apparent extension, as shown in Fig. 18.By formula (2), formula (3) and attached drawing 18 it is found that the converter is individually working
Input voltage range M under moderangeAt >=1.5 times, it is ensured that operating mode low gain operating mode and middle gain work
The gain of mode is connected.Therefore, total input voltage range under two operating modes can achieve 2.25 times or more
(1.5Mrange).Compared with the converter in existing literature, total input voltage range of converter shown in attached drawing 6 is attached at 2.25 times
When close (2.5 times of input voltage ranges of such as certain fuel cell-powered occasions), because of the input voltage model under single operating mode
It encloses and obviously narrows, efficiency performance is preferable.
Three bridge arm switching networks, secondary side rectification circuit (20) are used with attached primary side switch network (10) shown in Fig. 9 below
For a kind of common resonant inductive type wide input range LLC resonant converter of full bridge rectifier, this is further illustrated
The working principle of invention.In attached drawing 9, Lm1=Lm2=2Lm, Cr1=Cr2=0.5Cr, n1=n2=2n.The converter uses frequency conversion
Control.Compared with the converter shown in the attached drawing 6, converter shown in attached drawing 9 is there are three types of operating mode, a kind of more high-gain Working moulds
Formula, primary side switch pipe control strategy are as shown in Fig. 19.In figure, the converter primary side first switch tube (SP1) driving uGSP1With
4th switching tube (SP4) driving uGSP4, the 6th switching tube (SP6) driving uGSP6It is consistent, second switch (SP2) driving uGSP2
With third switching tube (SP3) driving uGSP3, the 5th switching tube (SP5) driving uGSP5It is consistent, uGSP1And uGSP2For duty ratio 50%
Complementation conducting.The square-wave voltage u of switching network (10) outputab、uacPositive negative pulse stuffing amplitude be all ± Uin, positive negative pulse stuffing it is wide
Degree is all 50%, and the two phase is consistent.Under high-gain operating mode, which can be equivalent to the conventional full bridge in Fig. 1
LLC converter is no longer described in detail herein shown in voltage gain such as formula (1).
In middle gain operating mode, the 5th switching tube (S of the converter primary sideP5) driving uGSP5It keeps often closing, the 6th opens
Close pipe (SP6) driving uGSP6It maintains a normally open, first switch tube (SP1) driving uGSP1With the 4th switching tube (SP4) driving uGSP4Keep one
It causes, second switch (SP2) driving uGSP2With third switching tube (SP3) driving uGSP3It is consistent, uGSP1And uGSP2For duty ratio
50% complementary conducting.The square-wave voltage u of switching network (10) outputabPositive negative pulse stuffing amplitude is ± Uin, square-wave voltage uacJust
Pulse amplitude is Uin, negative pulse amplitude be 0, uab、uacPositive negative pulse stuffing width is all 50%, and the two phase is consistent.In middle gain work
Under operation mode, which can be equivalent to attached converter shown in fig. 6 and does not remake herein shown in voltage gain such as formula (3)
Detailed description.
In low gain operating mode, the converter primary side third switching tube (SP3) driving uGSP3With the 5th switching tube (SP5)
Drive uGSP5It keeps often closing, the 4th switching tube (SP4) driving uGSP4With the 6th switching tube (SP6) driving uGSP6It maintains a normally open, first
Switching tube (SP1) driving uGSP1With second switch (SP2) driving uGSP2For the complementary conducting of duty ratio 50%.Switching network (10) is defeated
Square-wave voltage u outab、uacPositive pulse amplitude be all Uin, negative pulse amplitude be all that 0, positive negative pulse stuffing width is all 50%,
The two phase is consistent.Under low gain operating mode, which can be equivalent to the conventional half-bridge LLC converter in Fig. 2, electricity
It presses shown in gain such as formula (2), is no longer described in detail herein.
After being jointly controlled using three kinds of operating modes, the voltage gain range of converter shown in attached drawing 9 has been obtained significantly
Extension, as shown in Fig. 20.By formula (1), formula (2), formula (3) and attached drawing 20 it is found that the converter is under single operating mode
Input voltage range Mrange>=1.5 times, it is ensured that the gain of low gain operating mode and middle gain operating mode is connected.Cause
This, the input voltage range under three operating modes can achieve 3 times or more (2Mrange).With the converter phase in existing literature
Than total input voltage range of attached converter shown in Fig. 9 is at 3 times, because the input voltage range under single operating mode is bright
Aobvious to narrow, efficiency performance is preferable.
According to the description of above-mentioned two embodiment it is found that compared with the converter in existing literature, power of the present invention is partly led
Body device count is less, and the driving circuit of primary side switch pipe is consistent, and reduces costs；Single Working mould can be obviously reduced
Input voltage range under formula, optimal cavity parameter, improves efficiency；Two transformers work at the same time always, improve device
Part utilization rate, reduces volume, improves power density, meets wide input voltage range occasion high efficiency and high power density
Demand.
Above content is only illustrations made for the present invention described in this specification.Technology belonging to the present invention
The technical staff in field can do various modifications or supplement or is substituted in a similar manner to described specific embodiment, only
It should belong to guarantor of the invention without departing from the content or beyond the scope defined by this claim of description of the invention
Protect range.
Claims (5)
1. a kind of common resonant inductive type wide input range LLC resonant converter, it is characterised in that:
A kind of common resonant inductive type wide input range LLC resonant converter is by input source (Uin), primary side switch network
(10), common resonant inductance (Lr), the first resonant capacitance (Cr1), the second resonant capacitance (Cr2), the first transformer (T1), second become
Depressor (T2), secondary side rectification circuit (20), output filter capacitor (Co) and output loading (Ro) constitute, wherein the first transformer
(T1) primary side magnetizing inductance value be Lm1, the second transformer (T2) primary side magnetizing inductance value be Lm2；The primary side switch network
(10) input both ends respectively with input source (Uin) both ends be connected, the output end b and the first resonance of primary side switch network (10)
Capacitor (Cr1) one end be connected, the first resonant capacitance (Cr1) other end and the first transformer (T1) primary side winding different name end phase
Even, the first transformer (T1) primary side winding Same Name of Ends and the second transformer (T2) primary side winding Same Name of Ends, common resonant inductance
(Lr) one end be connected, common resonant inductance (Lr) the other end be connected with the output end a of primary side switch network (10), second become
Depressor (T2) primary side winding different name end and the second resonant capacitance (Cr2) one end be connected, the second resonant capacitance (Cr2) the other end
It is connected with the output end c of primary side switch network (10), the first transformer (T1) vice-side winding Same Name of Ends and secondary side rectification circuit
(20) input terminal d is connected, the input terminal e of secondary side rectification circuit (20) and the second transformer (T2) vice-side winding different name end phase
Even, the second transformer (T2) vice-side winding Same Name of Ends and the first transformer (T1) vice-side winding different name end be connected, the rectification of secondary side
The output both ends of circuit (20) respectively with output filter capacitor (Co) both ends, output loading (Ro) both ends be connected；
Primary side switch network (10) the output positive pulse amplitude is Uin, negative pulse amplitude be-UinOr 0, positive negative pulse stuffing width is
50% square-wave voltage uabAnd uac, and the phase of the two square-wave voltages is consistent；
The primary side switch network (10) is two bridge arm switching networks, it is by first switch tube (SP1), second switch (SP2),
Three switching tube (SP3) and the 4th switching tube (SP4) constitute, first switch tube (SP1) drain electrode and third switching tube (SP3) drain electrode,
Input source (Uin) anode be connected, first switch tube (SP1) source electrode and second switch (SP2) drain electrode, primary side switch network
(10) output end a is connected, second switch (SP2) source electrode and the 4th switching tube (SP4) source electrode, input source (Uin) cathode,
Primary side switch network (10) output end c is connected, the 4th switching tube (SP4) drain electrode and third switching tube (SP3) source electrode, primary side
Switching network (10) output end b is connected.
2. a kind of common resonant inductive type wide input range LLC resonant converter according to claim 1, feature exist
In: the primary side switch network (10) is three bridge arm switching networks, it is by first switch tube (SP1), second switch (SP2),
Three switching tube (SP3), the 4th switching tube (SP4), the 5th switching tube (SP5) and the 6th switching tube (SP6) constitute, first switch tube
(SP1) drain electrode and third switching tube (SP3) drain electrode, the 5th switching tube (SP5) drain electrode, input source (Uin) anode be connected,
First switch tube (SP1) source electrode and second switch (SP2) drain electrode, primary side switch network (10) output end a be connected, second
Switching tube (SP2) source electrode and the 4th switching tube (SP4) source electrode, the 6th switching tube (SP6) source electrode, input source (Uin) cathode
It is connected, the 4th switching tube (SP4) drain electrode and third switching tube (SP3) source electrode, primary side switch network (10) output end b be connected,
6th switching tube (SP6) drain electrode and the 5th switching tube (SP5) source electrode, primary side switch network (10) output end c be connected.
3. a kind of common resonant inductive type wide input range LLC resonant converter according to claim 1, feature exist
In: the secondary side rectification circuit (20) is full bridge rectifier, it is by the first rectifier diode (D1), the second rectifier diode
(D2), third rectifier diode (D3) and the 4th rectifier diode (D4) constitute, the first rectifier diode (D1) anode and secondary side
The input terminal d of rectification circuit (20), the second rectifier diode (D2) cathode be connected, the second rectifier diode (D2) anode and
4th rectifier diode (D4) anode, output filter capacitor (Co) cathode, output loading (Ro) cathode be connected, the 4th is whole
Flow diode (D4) cathode and secondary side rectification circuit (20) input terminal e, third rectifier diode (D3) anode be connected, the
Three rectifier diode (D3) cathode and the first rectifier diode (D1) cathode, output filter capacitor (Co) anode, output it is negative
Carry (Ro) anode be connected.
4. a kind of common resonant inductive type wide input range LLC resonant converter according to claim 1, feature exist
In: the secondary side rectification circuit (20) is a kind of voltage doubling rectifing circuit, it is by the first rectifier diode (D1), second rectification two poles
Manage (D2), the first voltage multiplying rectifier capacitor (Co1) and the second voltage multiplying rectifier capacitor (Co2) constitute, the first rectifier diode (D1) sun
The input terminal d of pole and secondary side rectification circuit (20), the second rectifier diode (D2) cathode be connected, the second rectifier diode (D2)
Anode and the second voltage multiplying rectifier capacitor (Co2) cathode, output filter capacitor (Co) cathode, output loading (Ro) cathode
It is connected, the second voltage multiplying rectifier capacitor (Co2) anode and secondary side rectification circuit (20) input terminal e, the first voltage multiplying rectifier capacitor
(Co1) cathode be connected, the first voltage multiplying rectifier capacitor (Co1) anode and the first rectifier diode (D1) cathode, output filtering
Capacitor (Co) anode, output loading (Ro) anode be connected.
5. a kind of common resonant inductive type wide input range LLC resonant converter according to claim 1, feature exist
In: the secondary side rectification circuit (20) is another voltage doubling rectifing circuit, it is by the first rectifier diode (D1), second rectification two
Pole pipe (D2), auxiliary voltage multiplying rectifier capacitor (Caux) constitute, assist voltage multiplying rectifier capacitor (Caux) cathode and secondary side rectification circuit
(20) input terminal d is connected, and assists voltage multiplying rectifier capacitor (Caux) anode and the first rectifier diode (D1) anode, second
Rectifier diode (D2) cathode be connected, the first rectifier diode (D1) cathode and output filter capacitor (Co) anode, output
Load (Ro) anode be connected, the second rectifier diode (D2) anode and secondary side rectification circuit (20) input terminal e, output filter
Wave capacitor (Co) cathode, output loading (Ro) cathode be connected.
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| CN108566094B (en) * | 2017-12-25 | 2022-08-26 | 华为数字能源技术有限公司 | Resonant converter, and control method and system of resonant converter |
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| WO2019208318A1 (en) * | 2018-04-26 | 2019-10-31 | パナソニックＩｐマネジメント株式会社 | Power conversion device |
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| WO2022000217A1 (en) * | 2020-06-29 | 2022-01-06 | 华为数字能源技术有限公司 | Resonant converter, and voltage conversion method |
| CN112234835B (en) * | 2020-09-30 | 2022-01-18 | 燕山大学 | Variable structure combined LLC resonant converter |
| CN112636605B (en) * | 2020-12-23 | 2022-04-26 | 上海交通大学 | Direct current conversion circuit and mode switching control method thereof under wide voltage range |
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| CN113037095B (en) * | 2021-04-07 | 2022-06-14 | 湖北工业大学 | Hybrid DPS double full bridge LLC resonant converter with ultra-wide output range |
| CN113691141A (en) * | 2021-10-11 | 2021-11-23 | 重庆平创半导体研究院有限责任公司 | Topological structure of DC-DC converter |
| CN114825955A (en) * | 2022-04-08 | 2022-07-29 | 南京航空航天大学 | Integrated type co-resonant unit multiphase parallel resonant converter capable of automatically equalizing current |
| CN114759803B (en) * | 2022-06-15 | 2022-09-13 | 湖北工业大学 | Asymmetric multi-mode variable-bandwidth output LLC converter and design method |
| CN115833602B (en) * | 2022-11-18 | 2023-11-03 | 常熟理工学院 | Double-transformer type resonant converter and modulation method thereof |
| CN115912934B (en) * | 2022-11-29 | 2024-07-05 | 湖南昇辉新能源技术有限公司 | Topological structure of mixed parallel LLC resonant circuit and control method thereof |
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