CN105610476B - Divergence type numerical model analysis receives and dispatches the analog beam vector optimization method in communication system - Google Patents
Divergence type numerical model analysis receives and dispatches the analog beam vector optimization method in communication system Download PDFInfo
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Abstract
The invention discloses a kind of divergence type numerical model analysis to receive and dispatch the analog beam vector optimization method in communication system; in divergence type numerical model analysis receives and dispatches communication system; a kind of iterative algorithm of Optimized Simulated beam vector is proposed using interference alignment thought; by this iterative algorithm according to the beam vector of each subarray of the beam vector and transmitting terminal of the reciprocity property alternative optimization receiving terminal of channel each subarray, until the threshold value that the small Mr. Yu of variation of the interference of each subarray gives.The iterative algorithm has the advantages that fast convergence rate, calculation amount are small, complexity is low etc., may be implemented to interfere alignment between subarray, by being interfered between interfering alignment that can reduce subarray, and then improves the spectrum efficiency of system, improve system performance.
Description
Technical Field
The invention belongs to the technical field of wireless communication, and relates to an analog beam vector optimization method in a Millimeter wave (Millimeter wave) Multiple-Input Multiple-Output (MIMO) separated digital-analog hybrid transceiving communication system.
Background
With the continuous development of communication technology, the access amount of wireless communication equipment and the requirement of users on data rate are also continuously increased, and the combination of millimeter waves with high frequency bands and an MIMO system can realize the improvement of transmission rate and spectral efficiency. The millimeter wave MIMO communication system is receiving attention of global people, and a new round of technical competition in the global mobile communication field is raised. In order to realize rapid development of the mobile internet and improvement of service support capability, 5G introduces advanced wireless transmission technologies such as a multiple access technology, a multiple antenna technology, a code modulation technology, a new beam design technology and the like, and adopts wireless network technologies such as a flexible network architecture, a networking technology and the like, and meanwhile, a millimeter wave frequency band becomes a frequency band with development prospect in a new generation communication technology.
In the millimeter wave MIMO communication system, in order to improve the system transmission rate and realize high quality communication, the beamforming technology becomes a focus of attention. In a conventional MIMO communication system, digital beam forming technology is adopted in a baseband, however, as one antenna is connected to one Radio Frequency (RF) link, the required cost increases as the number of antennas increases. The cost can be greatly reduced by using the analog beam forming formed by cheap phase shifters in the analog domain, but because the performance is influenced by the limit conditions of the phase shifters, the better design of the analog beam forming has greater value.
Disclosure of Invention
The purpose of the invention is as follows: in the existing beamforming technology, most of them determine digital domain beamforming or analog domain beamforming based on transmission rate or received power. The invention aims to provide an analog beam vector optimization method in a separated digital-analog hybrid transceiving communication system, and provides an iterative algorithm for optimizing an analog beam vector by utilizing an interference alignment thought in the separated digital-analog hybrid transceiving communication system, wherein the iterative algorithm has the advantages of high convergence speed, small calculated amount, low complexity and the like.
The technical scheme is as follows: in order to achieve the purpose, the invention adopts the technical scheme that: the method utilizes the idea of interference alignment, based on an initial analog precoding matrix and an analog synthesis matrix, alternately optimizes a beam vector of each subarray at a receiving end and a beam vector of each subarray at a transmitting end according to the reciprocity characteristic of a channel until the change of the interference of each subarray is less than a given threshold value, and then obtains a final analog precoding matrix and an analog synthesis matrix.
In order to better understand the technical solution of the present invention, first, a precoding matrix and a combining matrix in the separate type digital-analog hybrid transceiving communication system related to the above method are introduced. In a separate type digital-analog hybrid transceiving communication system, a radio frequency link is connected with an antenna sub-array, and an antenna is connected with a phase shifter. The analog precoder is implemented by a phase shifter, that is to say an analog precoding matrix FRThe element needs to satisfy a constraint condition of constant amplitude, FRCan be expressed as follows:
wherein FRHas dimension of NxNRF，NRFIs the number of radio frequency links, N is the total number of transmit antennas, for the number of antennas on the ith transmit antenna sub-array,of the ith sub-arrayBeam steering vector of thetai,lDenotes the phase angle of the ith antenna of the ith sub-array, and T denotes the transposition. Similarly, the analog composite matrix is expressed in the same way as the analog precoding matrix at the transmitting end, and the analog composite matrix GRIs represented as follows:
wherein G isRIs MXNRFMatrix of NRFWhich represents the number of radio frequency links,the number of the total receiving antennas is,for the number of antennas on the kth receive sub-array,represents the k-th sub-array dimension ofThe beam steering vector of (a) is,representing the phase angle of the ith antenna of the kth sub-array.
The method specifically optimizes the beam vector of each sub-array of the receiving terminal, and comprises the following steps: for a given transmitting end RF pre-coding matrix, the minimum signal energy received by the kth sub-array of the receiving end to the ith sub-array of the transmitting end is taken as a target, i is not equal to k, and the phase vector iteration updating of the phase shifter is carried out on the kth sub-array of the receiving end by taking the amplitude of the beam control vector of the kth sub-array of the receiving end as a constant as a constraint condition.
In order to reduce the interference of the ith (i ≠ k) sub-array of the transmitting end to the kth sub-array of the receiving end, the interference signal received by the kth sub-array is minimized by optimizing the beam direction of the kth sub-array, i.e. the interference signal is minimized
Wherein Hk,iRepresenting the channel between the kth sub-array of the receiving end and the ith sub-array of the transmitting end with the dimension of H represents the conjugate transpose as the phase vector of the phase shifter for the kth sub-array at the receiving end. By observing (equation 3), the objective function can be converted to the following equation
WhereinIs a Hermitian semi-positive definite matrix, gk(l) Represents a column vector gkThe first element of (a) is,representation matrixThe (l, l) -th element,denotes gkAfter the first element is taken out, the dimension isThe column vector of (a) is,representation matrixThe column vector after the l element is removed,representation matrixThe matrix after the ith row and ith column is removed,the representation takes the real part. As can be seen from (equation 4), the phase angle of the l-th antenna element of the k-th sub-array is related to the third term in (equation 4) only. In addition, gkThe medium element is also subject to a constraint that the amplitude is constant, thus gkEach element in (1) needs to satisfy the optimum condition
Where angle represents the value of the angle.
RF precoding matrix F for a given transmitting endRMeanwhile, the specific method for updating the phase vector of the phase shifter for the sub-array of the receiving end and solving the phase vector of the phase shifter for the kth sub-array of the receiving end comprises the following steps:
step 1: initial gk，τ＝0，χτ＝0；
Step 2: updating the phase of each receiving antenna in turn:wherein,
step 3, mixing gkSubstitution formulaFind xτ+1；
And 4, step 4: if xτ+1-χτAnd if | ≦ ε, obtaining the phase vector of the phase shifter of the kth sub-array of the receiving end and stopping iteration, otherwise τ +1, and continuing the step 2.
Wherein, tau and chiτAnd epsilon represent the number of iterations, the objective function and the iteration termination threshold, respectively.
Similarly, the specific method for optimizing the beam vector of each sub-array of the transmitting terminal in the method of the present invention is as follows: for a given receiving end RF synthesis matrix, the minimum signal energy received by the ith sub-array of the transmitting end by the kth sub-array of the receiving end is taken as a target, k is not equal to i, and the iterative update of the phase vector of the phase shifter is carried out on the ith sub-array of the transmitting end by taking the amplitude of the beam control vector of the ith sub-array of the transmitting end as a constant.
According to the reciprocal characteristic of the channel, the beam direction optimization function of the ith sub-array of the transmitting end can be expressed by using interference alignment
Also, the above formula can be expressed as (formula 4) a similar expression
WhereinIs a Hermitian semi-positive definite matrix, fi(l) Representing a column vector fiThe first element of (a) is,representation matrixThe (l, l) -th element,denotes fiAfter the first element is taken out, the dimension isThe column vector of (a) is,representation matrixThe column vector after the l element is removed,representation matrixThe matrix after the ith row and ith column is removed. Is easy to know, fiThe optimal conditions to be satisfied by each element in the group are as follows:
given receiving end RF synthesis matrix GRMeanwhile, the phase vector of the phase shifter is updated for the sub-array of the transmitting terminal, and the specific method for solving the phase vector of the phase shifter of the ith sub-array of the transmitting terminal comprises the following steps:
step 1: initialization fi，τ＝0，
Step 2: updating the phase of each transmitting antenna in turn:
wherein,
and step 3: will f isiSubstitution formulaTo obtain
And 4, step 4: if it is notThe iteration is stopped, otherwise τ +1, and step 2 is continued. Wherein tau is,And epsilon represents the number of iterations, the objective function and the iteration termination threshold, respectively.
By alternately operating and updating the phase vectors of the phase shifters of the receiving end and the transmitting end until the change of the interference value of each sub-array is smaller than a given threshold value, the beam control vector of each sub-array can be obtained, and further, an analog precoding matrix and an analog synthesis matrix are obtained.
Has the advantages that: the invention provides a simulation beam vector optimization method in a separated digital-analog hybrid transceiving communication system, which is characterized in that an iterative algorithm for optimizing a simulation beam vector is provided by utilizing an interference alignment thought in the separated digital-analog hybrid transceiving communication system, and the beam vector of each sub-array of a receiving end and the beam vector of each sub-array of a transmitting end are alternately optimized according to the reciprocity characteristic of a channel by the iterative algorithm until the required performance is met. The iterative algorithm has the advantages of high convergence rate, small calculation amount, low complexity and the like, can realize the interference alignment between the subarrays, can reduce the interference between the subarrays through the interference alignment, further improves the frequency spectrum efficiency of the system and improves the system performance.
Drawings
Fig. 1 is a block diagram of a separate digital-analog hybrid transceiving communication system according to the present invention.
Fig. 2 is a flowchart of an algorithm for optimizing a simulated beam vector based on interference alignment according to the present invention.
Fig. 3 is a block diagram of a corresponding transceiver in the embodiment of the present invention.
Detailed Description
The present invention is further illustrated by the following examples, which are intended to be purely exemplary and are not intended to limit the scope of the invention, as various equivalent modifications of the invention will occur to those skilled in the art upon reading the present disclosure and fall within the scope of the appended claims.
As shown in fig. 1, in a separate digital-analog hybrid transceiving communication system, a radio frequency link is connected to a sub-array, and an antenna is connected to a phase shifter, in order to solve an analog precoding matrix and an analog combining matrix, a beam vector of each sub-array needs to be optimized, and a specific optimization flow chart is shown in fig. 2.
In the embodiment of the invention, a transmitting end is provided with 4 radio frequency links, one radio frequency link is connected with one sub-array, the number of antennas on each sub-array is 8, one antenna is connected with one phase shifter, a receiving end is provided with 4 radio frequency links, one radio frequency link is connected with one sub-array, each sub-array is provided with 8 antennas, one antenna is connected with one phase shifter, and a block diagram of the transceiver is shown in figure 3. The apparatus supporting different numbers of rf links and antennas per sub-array may be obtained by modifying the example in this embodiment.
In a separate type digital-analog hybrid transceiving communication system, a radio frequency link is connected with an antenna sub-array, and an antenna is connected with a phase shifter. The analog precoder is implemented by a phase shifter, that is to say an analog precoding matrix FRThe element needs to satisfy a constraint condition of constant amplitude, FRCan be expressed as follows:
wherein FRHas a dimension of 32 x 4, 4 being the number of radio frequency links at the transmitting end, 32 being the total number of transmit antennas, fiEach of i-1, 2, …, and 4 is [0.3536,0.3536, …,0.3536 ]]TAnd 8 × 1, T denotes transposition. Similarly, the analog composite matrix is expressed in the same way as the analog precoding matrix at the transmitting end, and the analog composite matrix GRIs represented as follows:
wherein G isRIs a 32 x 4 matrix, 4 denotes the number of RF links at the receiving end, 32 is the total number of receive antennas, and initially gkEach of k-1, 2, …, and 4 is also [0.3536,0.3536, …,0.3536 ]]T8 x 1 beam steering vector of (1).
In order to reduce the interference of the ith (i ≠ k) sub-array of the transmitting end to the kth sub-array of the receiving end, the interference signal received by the kth sub-array is minimized by optimizing the beam direction of the kth sub-array, i.e. the interference signal is minimized
Wherein Hk,iRepresenting the channel between the kth sub-array at the receiving end and the ith sub-array at the transmitting end, with dimensions of 8 x 8,h represents the conjugate transpose as the phase vector of the phase shifter for the kth sub-array at the receiving end. By observing (equation 11), the objective function can be converted to the following equation
WhereinIs a Hermitian semi-positive definite matrix, gk(l) Represents a column vector gkThe first element of (a) is,representation matrixThe (l, l) -th element,denotes gkAfter the first element is taken out, the dimension isThe column vector of (a) is,representation matrixThe column vector after the l element is removed,representation matrixThe matrix after the ith row and ith column is removed,the representation takes the real part. As can be seen from (equation 12), the phase angle of the l-th antenna element of the k-th sub-array is related to the third term in (equation 12) only. In addition, gkThe medium element is also subject to a constraint that the amplitude is constant, thus gkEach element in (1) needs to satisfy the optimum condition
Where angle represents the value of the angle.
RF precoding matrix F for a given transmitting endRMeanwhile, the specific method for updating the phase vector of the phase shifter for the sub-array of the receiving end and solving the phase vector of the phase shifter for the kth sub-array of the receiving end comprises the following steps:
step 1: initial gk，τ＝0，χτ＝0；
Step 2: updating the phase of each receiving antenna in turn:wherein, l is 1,2, …, 8;
step 3, mixing gkSubstitution formulaFind xτ+1；
And 4, step 4: if xτ+1-χτIf | ≦ epsilon, obtaining a phase vector of the phase shifter of the kth sub-array of the receiving end and stopping iteration, otherwise, if τ ═ τ +1, and continuing the step 2;
wherein, tau and chiτAnd epsilon represent the number of iterations, the objective function and the iteration termination threshold, respectively.
According to the reciprocal characteristic of the channel, the beam direction optimization function of the ith sub-array of the transmitting end can be expressed by using interference alignment
Also, the above formula can be expressed as a similar expression (formula 12)
WhereinIs a Hermitian semi-positive definite matrix, fi(l) Representing a column vector fiThe first element of (a) is,representation matrixThe (l, l) -th element,denotes fiAfter the first element is taken out, the dimension isThe column vector of (a) is,representation matrixThe column vector after the l element is removed,representation matrixRemoving the l row and l columnThe latter matrix. Is easy to know, fiThe optimal conditions to be satisfied by each element in the group are as follows:
given receiving end RF synthesis matrix GRMeanwhile, the phase vector of the phase shifter is updated for the sub-array of the transmitting terminal, and the specific method for solving the phase vector of the phase shifter of the ith sub-array of the transmitting terminal comprises the following steps:
step 1: initialization fi，τ＝0，
Step 2: updating the phase of each transmitting antenna in turn:wherein, l is 1,2, …, 8;
and step 3: will f isiSubstitution formulaTo obtain
And 4, step 4: if it is notStopping iteration, otherwise, keeping the step 2; wherein tau is,And epsilon represents the number of iterations, the objective function and the iteration termination threshold, respectively.
By alternately operating and updating the phase vectors of the phase shifters of the receiving end and the transmitting end until the change of the interference of each sub-array is smaller than a given threshold value, the beam control vector of each sub-array can be obtained, and further, the analog precoding matrix and the analog synthesis matrix can be obtained.
Claims (5)
1. The method is characterized in that the method optimizes a beam vector of each sub-array of a receiving end and a beam vector of each sub-array of a transmitting end on the basis of an initial analog pre-coding matrix and an initial analog synthesis matrix by taking minimum receiving interference as a target until the change of the interference of each sub-array is smaller than a given threshold value to obtain a final analog pre-coding matrix and a final analog synthesis matrix;
the optimized wave beam vector of each sub array of the receiving end is as follows: for a given transmitting end RF pre-coding matrix, aiming at the minimum signal energy received by the kth sub-array of the receiving end by the ith sub-array of the transmitting end, i is not equal to k, and carrying out iterative update of a phase vector of a phase shifter on the kth sub-array of the receiving end by taking the amplitude of a beam control vector of the kth sub-array of the receiving end as a constant; wherein the target is represented as:
wherein Hk,iIndicating the channel between the kth sub-array at the receiving end and the ith sub-array at the transmitting end, fiBeam steering vector, g, for the i-th sub-array of the transmitting endkBeam steering vector for kth sub-array of receiving end, NRFIs the number of the radio frequency links,h represents a conjugate transpose for a phase vector of a phase shifter of the kth sub-array of the receiving end;
optimizing the wave beam vector of each sub array of the transmitting terminal as follows: for a given receiving end RF synthesis matrix, aiming at the fact that the energy of a signal received by the ith sub-array of the transmitting end by the kth sub-array of the receiving end is the minimum, k is not equal to i, and the phase vector iteration updating of a phase shifter is carried out on the ith sub-array of the transmitting end by taking the amplitude of a beam control vector of the ith sub-array of the transmitting end as a constant; wherein the target is represented as:
wherein theta isiThe phase vector of the phase shifter of the ith sub-array at the transmitting end.
2. The method of claim 1, wherein g is the number of beams in the systemkThe calculation formula for each element in (a) is:
wherein M is the total receiving antenna number of the receiving end, angle represents the angle value,
representation matrixThe column vector after the l element is removed,representing the column vector after gk removes the l-th element.
3. The method as claimed in claim 2, wherein the step of iteratively solving and updating the phase vector of the phase shifter of the kth sub-array at the receiving end comprises:
step 1: initial iteration parameters, including gkThe iteration number τ is 0, and the objective function value χτ0 and an iteration end threshold epsilon;
step 2: according to the formulaAnd sequentially updating the phase of each receiving antenna of the kth sub-array at the receiving end, wherein, the number of antennas on the kth receiving subarray;
and step 3: g obtained in step 2kSubstitution formulaObtaining the target function value χτ+1；
And 4, step 4: if xτ+1-χτIf | ≦ ε, the phase vector of the phase shifter of the kth sub-array of the receiving end is obtained and iteration is stopped, otherwise τ +1, and step 2 is continued.
4. The method of claim 1, wherein f is the analog beam vector optimization method in the separate-type digital-analog hybrid transceiving communication systemiThe calculation formula of each element in (a) is as follows:
wherein N represents the total number of transmitting antennas at the transmitting end,representation matrixThe column vector after the removal of the l-th element, angle represents the angle value,denotes fiThe column vector after the l-th element is removed.
5. The method according to claim 4, wherein the step of iteratively solving and updating the phase vector of the phase shifter of the ith sub-array at the transmitting end comprises:
step 1: initial iteration parameters, including fiThe number of iterations τ is 0, the value of the objective functionAnd an iteration termination threshold epsilon;
step 2: according to the formulaAnd sequentially updating the phase of each transmitting antenna of the ith sub-array of the transmitting terminal, wherein, the number of antennas on the ith transmitting subarray is;
and step 3: f obtained in step 2iSubstitution formulaCalculating the value of the objective function
And 4, step 4: if it is notThe phase shifter phase vector for the ith sub-array of the transmitting end is obtained and the iteration is stopped, otherwise τ +1, and step 2 is continued.
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