CN104854529A - Maximum power point tracking controllers and associated systems and methods - Google Patents

Abstract

A maximum power point tracking controller includes an input port for electrically coupling to an electric power source, an output port for electrically coupling to a load, a control switching device, and a control subsystem. The control switching device is adapted to repeatedly switch between its conductive and non- conductive states to transfer power from the input port to the output port. The control subsystem is adapted to control switching of the control switching device to regulate a voltage across the input port, based at least in part on a signal representing current flowing out of the output port, to maximize a signal representing power out of the output port.

Description

MPPT maximum power point tracking controller and related system and method

Background technology

Photovoltaic cell produces the voltage changed with electric current, cell operating condition, battery physics, battery defect and battery illumination.As shown in Figure 1, output current is modeled as by a mathematical model for photovoltaic cell:

$I=I_L-I_0\left\{\exp \[\frac{q(V+{\mathrm{IR}}_S}{nkT}\]-1\right\}-\frac{V+{\mathrm{IR}}_S}{R_{SH}}$ Equation 1

Wherein

I _l=photogenerated current

R _s=resistance in series

R _sH=shunt resistance

I ₀=reverse saturation current

N=Diode Ideality Factor (for ideal diode, being 1)

Q=elementary charge

K=Boltzmann constant

T=absolute temperature

I=is at the output current at battery terminal place

V=is at the voltage at battery terminal place

For 25 DEG C, kT/q=0.0259 volt silicon.

Typical cell output voltage is low, and depends on the band gap of the material for the manufacture of battery.For silion cell, cell output voltage can be only half volt, its far below to charge in batteries or drive great majority other load needed for voltage.Due to these low-voltages, typically serial battery is joined together to form module or array, there is the output voltage more much higher than the output voltage produced by single battery.

Real world photovoltaic cell usually has one or more trickle defect.These battery defect can cause resistance in series Rs, shunt resistance R in module from battery to battery _sHwith photogenerated current I _lmismatch.In addition, for the reason comprised by the shade of tree projection, the ight soil covering the bird of the part of battery or module, dust, earth and other defect, battery illumination can be different from battery from battery in the system of photovoltaic cell, and may even in the module from different between battery from battery.These mismatches in illumination may understand cross-module movement by different with the different time of every day between sky from sky-shade in one day, and rainwater can wash away the dust or earth that cover battery.

According to equation 1, output voltage is maximum when zero output electric current, and output voltage V non-linear decline along with the output current I increased.Fig. 2 shows the impact of the electric current from the increase obtained from photovoltaic device when constant illumination.Along with electric current I increases under constant illumination, voltage V declines lentamente, but increases near photocurrent I along with electric current I _loutput current, output voltage V sharply declines.Similarly, the power of battery (product of electric current and voltage) increases with electric current I and increases, until the voltage V declined overcomes the impact of the electric current of increase, so the further increase of the electric current I obtained from battery causes power P to reduce fast.For given illumination, thus the array of each battery, module and battery and module has maximum power point, and described maximum power point represents the maximized voltage and current combination of output power made from device.The MPP of battery, module or array can change along with temperature and illumination, and therefore photogenerated current I _lchange.The MPP of battery, module or array also can be subject to the impact of aging and so on factor of such as shade and/or battery, module or array.

Proposed for photovoltaic cell maximum power point or near MPPT maximum power point tracking (MPPT) controller of the described photovoltaic cell of operation.These controllers typically determine MPP voltage and current for the photovoltaic device being connected to its input, and adjust its virtual impedance so that photovoltaic device is remained on MPP.But traditional MPPT controller usually has one or more shortcoming.Such as, some MPPT controller proposed under certain conditions can be relatively slow, thus be delayed MPP operation.

Summary of the invention

In an embodiment, a kind of MPPT maximum power point tracking controller, comprising: input port, and described input port is used for being electrically coupled to power supply; Output port, described output port is used for being electrically coupled to load; Gauge tap device; And control subsystem.Gauge tap device is suitable for repeatedly switching between its conducting state and nonconducting state, so that power is sent to output port from input port.Control subsystem is suitable at least in part based on representing that the signal of the electric current flowing out output port controls the switching of gauge tap device, to regulate the voltage across input port, maximizes to make the signal representing the power exported from output port.

In an embodiment, a kind of power-supply system, comprises power supply and MPPT maximum power point tracking controller.MPPT maximum power point tracking controller comprises: input port, and described input port is used for being electrically coupled to described power supply; Output port, described output port is used for being electrically coupled to load; Gauge tap device; And control subsystem.Gauge tap device is suitable for repeatedly switching between its conducting state and nonconducting state, so that power is sent to output port from power supply.Control subsystem is suitable at least in part based on representing that the signal of the electric current flowing out output port controls the switching of gauge tap device, to regulate the voltage across input port, maximizes to make the signal representing the power exported from output port.

In an embodiment, a kind of method for operational maximum power point tracking control unit, described MPPT maximum power point tracking controller comprises: input port, and described input port is used for being electrically coupled to power supply, and output port, described output port is used for being electrically coupled to load, said method comprising the steps of: (a) repeatedly switches described gauge tap device between the conducting state and nonconducting state of the gauge tap device of described MPPT maximum power point tracking controller, so that power is sent to output port from input port, and (b) is at least in part based on representing that the signal of the electric current flowing out output port controls the switching of gauge tap device, to regulate the value across the voltage of input port, maximize to make the signal representing the power exported from output port.

In an embodiment, a kind of method for using MPPT maximum power point tracking controller to transmit electric power between power supply and load, comprise at least in part based on representing that the signal flowing through the electric current of the energy storage inductor of MPPT maximum power point tracking controller controls the switching of the gauge tap device of MPPT maximum power point tracking controller, to regulate the voltage across power supply, make: (a) is more than or equal to the voltage across load across the voltage of power supply, and the signal that (b) makes expression be sent to the power of load maximizes.

In an embodiment, a kind of multiplier, comprises first input end mouth and the second input port, output port, the first field effect transistor, the second field effect transistor, the 3rd field effect transistor and control circuit.First field effect transistor and first input end mouth coupled in series electrical, the second field effect transistor and the second input port coupled in series electrical, and the 3rd field effect transistor and output port coupled in series electrical.Control circuit is suitable for each field effect transistor in control first field effect transistor, the second field effect transistor and the 3rd field effect transistor, and making the value of the electric current flowed in output port and (a) flow into the value of the electric current in first input end mouth and (b), to flow into the product of the amount of the electric current in the second input port proportional.

In an embodiment, a kind of electronic filter, comprises integrator subsystem and transconductance circuit.Integrator subsystem is suitable for operating in bipolarity territory, with the AC compounent in filtering input signal.Transconductance circuit is suitable for operating in unipolarity territory, to generate the output current signal proportional with the mean value of input current signal.

In an embodiment, a kind of method for carrying out filtering to input signal, is included in the AC compounent in filtering input signal in bipolarity territory, and in unipolarity territory, generates the DC component of input signal.

In an embodiment, a kind of signal panntographic system, comprises mutual conductance subsystem and steering logic.Mutual conductance subsystem is suitable for input voltage signal to be converted to output current signal, and mutual conductance subsystem comprises programmable resistance, and described programmable resistance is suitable for the gain setting mutual conductance subsystem.Steering logic is suitable for the resistance setting programmable resistance, to adjust the gain of mutual conductance subsystem, makes the value of output current signal at least equally large with first threshold.

In an embodiment, a kind of signal level shift unit for the Complementary input structure voltage signal in the first power domain being displaced to the complementary output voltage signal in second source territory, comprises transconductance stage and load circuit.Transconductance stage in the first power domain, and is suitable in response to Complementary input structure voltage signal and generates complementary current signal.Load circuit in second source territory, and is suitable in response to complementary current signal and generates complementary output voltage signal.Load circuit comprises the first inverter circuit and the second inverter circuit, is suitable in response to complementary current signal and generates complementary output voltage signal described in described first inverter circuit and described second inverter circuit.

In an embodiment, one is used for the system of the signal determining the power represented in MPPT maximum power point tracking (MPPT) controller, comprises voltage filter subsystem, current filter subsystem, voltage scaling subsystem, electric current convergent-divergent subsystem and multiplier.Voltage filter subsystem is suitable for by carrying out filtering to generate across the signal of the voltage of the output port of MPPT controller the signal that represents across the average voltage of described output port to representing.Current filter subsystem is suitable for the signal by carrying out filtering to generate representing the average current flowing out output port to the signal of the electric current representing outflow output port.Voltage scaling subsystem is suitable for by zooming in the first preset range across the signal of the average voltage of output port the scale signal generating and represent across the average voltage of output port by representing.Electric current convergent-divergent subsystem is suitable for by representing that the signal of the average current flowing out output port zooms in the second preset range the scale signal generating and represent the average current flowing out output port.Multiplier be suitable for according to represent across the average voltage of output port scale signal with represent that the product flowing out the scale signal of the average current of output port determines to represent the signal of power.

In an embodiment, one is used for the method for the signal determining the power represented in MPPT maximum power point tracking (MPPT) controller, comprise the following steps: (a) signal to the electric current representing the output port flowing out MPPT controller carries out filtering, to obtain the signal representing the average current flowing out output port; B () carries out filtering, to obtain the signal of the average voltage represented across output port to the signal represented across the voltage of output port; C () convergent-divergent represents the signal of the average current flowing out output port, to obtain the scale signal representing the average current flowing out output port; D () convergent-divergent represents the signal of the average voltage across output port, to obtain the scale signal of the average voltage represented across output port; And (e) will represent that the scale signal of the average current flowing out output port is multiplied by the scale signal represented across the average voltage of output port, to obtain the signal representing power.

Accompanying drawing explanation

Fig. 1 shows a model of photovoltaic cell.

Fig. 2 shows for the voltage of a photovoltaic cell and the power curve map with curent change.

Fig. 3 shows the power-supply system comprising MPPT controller according to embodiment.

Fig. 4 shows the block diagram of the control subsystem of Fig. 3 MPPT controller.

Fig. 5 shows the possible operator scheme of of the control subsystem of Fig. 3 MPPT controller.

Fig. 6 shows the example with the operation of the electric current convergent-divergent subsystem of minimum output valve constraint according to embodiment.

Fig. 7 shows the electronic filter according to embodiment.

Fig. 8 shows the signal convergent-divergent subsystem according to embodiment.

Fig. 9 shows the multiplier according to embodiment.

Figure 10 shows the possible embodiment of logic in the embodiment of Fig. 3 MPPT controller and drive circuit one, wherein, to control and continued flow switch device is implemented by N slot field-effect transistor.

Figure 11 shows the curve map for the node voltage of Fig. 3 MPPT controller and the relation of time.

Figure 12 shows the signal level shift unit according to embodiment.

Figure 13 shows the power-supply system comprising the Multi-instance of Fig. 3 MPPT controller according to embodiment.

Embodiment

Applicant has developed the new MPPT controller that can realize one or more advantage.Such as, some embodiment of controller can operate together with various load, and can restrain on MPP relatively rapidly.

Fig. 3 shows power-supply system 300, and power-supply system 300 comprises the MPPT controller 302 of electric coupling between power supply 304 and load 306.As described below, MPPT controller 302 is suitable for while power is sent to load 306 from power supply 304, the MPP place of power supply 304 or near operating power 304.

MPPT controller 302 comprises input port 308 and output port 314, and input port 308 comprises input terminal 310, input terminal 312, and output port 314 comprises lead-out terminal 316, lead-out terminal 318.The positive terminal 320 of power supply 304 is electrically coupled to input terminal 310, and the negative terminal 322 of power supply 304 is electrically coupled to input terminal 312, makes power supply 304 and input port 308 series coupled.Terminal 310, terminal 320 form the part of positive supply node or rail (Vddh), and terminal 312, terminal 322 form the part of reference power source node or rail (Vss).Such as, power supply 304 is photovoltaic devices, such as comprises the photovoltaic module of the photovoltaic cell of multiple interconnection, Single-junction photovoltaic cell or multi-junction photovoltaic battery.But system 300 is not limited to photovoltaic application.Such as, in some alternative embodiments, power supply 304 is one or more fuel cell or one or more accumulator.

System 300 comprises the one or more input capacitors 324 across input port 308 electric coupling alternatively.Capacitor 324 helps the ripple component providing controller 302 input current Iin, thus helps the value of the ripple current flowing through power supply 304 is minimized.Then effective power operation is facilitated by the low ripple current magnitude of power supply 304.In some embodiment that MPPT controller 302 carries out switching with relatively high frequency (such as with 500 kilo hertzs or larger) wherein, capacitor 324 is multilayer ceramic capacitors, to promote little capacitor sizes and long capacitor life-span.

MPPT controller 302 comprises the on-off circuit 326 across input port 308 electric coupling.On-off circuit 326 comprises the gauge tap device 328 of electric coupling between input terminal 310 and switching node Vx and the continued flow switch device 330 of electric coupling between switching node Vx and input terminal 312.Lead-out terminal 316 is electrically coupled to switching node Vx, and lead-out terminal 318 is electrically coupled to input terminal 312.In this document, switching device includes but not limited to bipolar junction transistor, field effect transistor (such as, the N raceway groove of such as LDMOS transistor (LDFET) or P-channel metal-oxide-semiconductor field effect transistor (MOSFET), junction field effect transistor, metal-semiconductor field effect transistor), insulated gate bipolar junction transistor, thyristor or silicon controlled rectifier.

Load 306 and output port 314 coupled in series electrical, to form part load 306 being electrically coupled to on-off circuit 326 of output circuit 332.Load 306 comprises such as phase inverter or battery charger.One or more output capacitor 334 across load 306 electric coupling, to absorb the ripple component of output current Iout.Although load wherein 306 comprises in the embodiment of sizable electric capacity, such as load wherein 306 is in the embodiment of the phase inverter with sizable input capacitance, omits capacitor 334 alternatively.In some embodiment that MPPT controller 302 carries out switching with relatively high frequency (such as with 500 kilo hertzs or larger) wherein, capacitor 334 is multilayer ceramic capacitors, to promote little capacitor sizes and long capacitor life-span.Output circuit 332 comprises energy storage inductor 336.In certain embodiments, energy storage inductor 336 comprises one or more discrete inductor, as shown in symbol in Fig. 3.But, in some other embodiments, eliminate discrete energy-storage reactor, and " parasitism " interconnection inductance relevant to the loop forming output circuit 332 serves as energy storage inductor 336.

MPPT controller 302 also comprises control subsystem 338.On-off circuit 326, energy storage inductor 336 and capacitor 334 form the step-down controller controlled by control subsystem 338 jointly.Control subsystem 338 is suitable for the switching of gauge tap circuit 326, makes step-down controller from input port 308 to output port 314 delivering power, thus from power supply 304 to load 306 delivering power.Specifically, control subsystem 338 makes gauge tap device 328 between its conducting state and nonconducting state, repeatedly switch (typically with the frequency of at least 100 kilo hertzs), so that power is sent to output port 314 from input port 308.Switching device 328 is called as " control " switching device, because input voltage vin and the ratio of the output voltage Vout across load 306 are the functions of the dutycycle of switching device 328.

Control subsystem 338 also controls the switching of continued flow switch device 330, it is made to perform afterflow function, or in other words, make continued flow switch device 330 when gauge tap device 328 is in its nonconducting state for the output current Iout of flowing between lead-out terminal 316, lead-out terminal 318 provides path.In some alternative embodiments, replace continued flow switch device 330 with the afterflow device substituted, such as its anode is electrically coupled to reference mode Vss and its cathodic electricity is coupled to the diode of switching node Vx.

MPPT controller 302 also comprises the electric current reconstructing device subsystem 340 being suitable for generating the signal Io representing the output current Iout flowing out output port 314.In certain embodiments, electric current reconstructing device subsystem 340 adopts the one or more U.S. Patent numbers 6,160 people such as Stratakos, 441 and 6,445, system and method disclosed in 244 generates signal Io, and each in described patent is by reference to being incorporated herein.But, when not departing from its scope, can otherwise implement electric current reconstructing device subsystem 340.

Control subsystem 338 also controls the switching of gauge tap device 328 at least in part based on signal Io, to regulate the input voltage vin across input port 308, maximize to make the signal representing the power exported from output port 314.In other words, control subsystem 338 adjusts the value of Vin, MPPT controller 302 is had at least substantially make the effective input impedance of the maximizes power exported from output port 314, as when look to input port 308 from power supply 304.The maximizes power exported from output port 314 is made to make the maximizes power of load 306, and the power obtained from power supply 304 is maximized substantially, because equal from the power of output port 314 output the power (have ignored the loss MPPT controller 302) entering input port 308.Therefore, represent that the signal of the power exported from output port 314 can represent the power entered input port 308 or the power exported from output port 314, because two values are identical (ignoring the loss in controller 302).It should be noted that, although the power entered in input port 308 is substantially the same with the power exported from output port 314, but except at gauge tap device 328 with except during absolutely duty cycle, input current Iin can be different with output current Iout.

In certain embodiments, represent that the signal of the power exported from output port 314 represents the real power exported from output port, or enter the real power in input port 308.But, in some other embodiments, represent that the signal of the power exported from output port 314 represents the relative power exported from output port, or enter the relative power of input port 308.In these embodiments, by making relative output port or input port maximizes power effectively make actual output port or input port maximizes power.

In certain embodiments, in common integrated circuit, implement some or all in MPPT controller 302, so consequently promote the little spurious impedance between small size, parts and fast signal delivery time.In these embodiments, integrated circuit is packaged together jointly with power supply 304 alternatively, to promote little system dimension and the minimum impedance between power supply 304 and controller 302.But MPPT controller 302 is not limited to integrated circuit embodiment, and can be formed by discrete parts partially or completely on the contrary.

Although on-off circuit 326, energy storage inductor 336 and capacitor 334 form step-down controller, also can think that these parts form the boost converter with negative " output " electric current.Specifically, owing to have adjusted input voltage vin, and input voltage vin is more than or equal to output voltage Vout, so can think that on-off circuit 326, energy storage inductor 336 and capacitor 334 form boost converter, load 306 is electrically coupled to the input end of boost converter, and power supply 304 is electrically coupled to the output terminal of boost converter.But the output current of boost converter is negative, because input current Iin flows into MPPT controller 302 from power supply 304.Thus, depend on the viewpoint of individual, can think that on-off circuit 326, energy storage inductor 336 and capacitor 334 form the step-down controller with the input voltage vin of adjustment, or there is the boost converter of negative " output " electric current I in.

Fig. 4 shows the block diagram of control subsystem 338.Control subsystem 338 comprises current filter subsystem 402, and current filter subsystem 402 is suitable for signal Io_avg that is refined from signal Io filtering ripple component and the average current of generation expression outflow output port 314.Electric current convergent-divergent subsystem 404 convergent-divergent Io_avg is to generate signal scaled_Io_avg, and it is the signal Io_avg zoomed in the first numerical range.Voltage filter subsystem 406 couples of output port voltage Vp carry out filtering to generate the signal Vp_avg of the mean value of the voltage Vp represented across output port 314, and output port voltage Vp is the waveform with roughly square-wave form.But, in some alternative embodiments, replace across output port 314, across load 306 sampled voltage Vp, thus make it possible to omit voltage filter subsystem 406.Voltage scaling subsystem 408 convergent-divergent Vp_avg, to generate scaled_Vp_avg, scaled_Vp_avg is the signal Vp_avg zoomed within the scope of second value.The second value scope of convergent-divergent subsystem 408 is typically identical with the first numerical range of panntographic system 404, to promote that scaled_Io_avg and scaled_Vp_avg is multiplied.Some possible examples of filter subsystem and convergent-divergent subsystem are discussed below relative to Fig. 7 and Fig. 8.

Control subsystem 338 also comprises the multiplier 410 being suitable for scaled_Io_avg and scaled_Vp_avg to be multiplied, to generate signal Po, Po represents the power exported from output port 314 and the power entering input port 308 and at least substantially with described both are proportional.The example of the possible embodiment of of multiplier 410 is discussed below relative to Fig. 9.MPPT control circuit 412 generates signal Vref order, and reference voltage generator 414 in response to signal Vref order generating reference voltage Vref.MPPT control circuit 412 and reference voltage generator 414 cooperate the value setting Vref, to make signal Po maximize, thus effectively make the power exported from output port 314 and the maximizes power entered input port 308.An example of this MPPT function is discussed below relative to Fig. 5.

Error amplifier 416 generates error voltage Verr, by PWM comparer 418 by error voltage Verr compared with ramp signal Vramp, to generate pwm control signal PWM.Logic and driver circuitry 420 generates signal 422, the signal 424 of the switching of gauge tap device 328, switching device 330 respectively according to signal PWM.

By error amplifier 416 generate error voltage Verr by:

Verr=-Kv* (Vin-Vref)+Ki*Io equation 2

Provide, wherein, Kv and Ki is zoom factor.These zoom factors are chosen as and make under the operating conditions of expection, and the amount Kv*Vin amount of being greater than Ki*Io, to keep stability.In addition, zoom factor Kv typically is large, because system bandwidth and Kv*I/Cin are roughly proportional, wherein, Cin is the total capacitance value of input capacitor 324, and I is the mean value of output current Iout.In certain embodiments, zoom factor Kv is chosen as and is inversely proportional to the expectation value of Vin, and Ki is chosen as is inversely proportional to the estimated average value of output current Iout.Zoom factor Kv and Ki can be constant, or such as due to operating conditions change can in these factors of dynamic conditioning one or both.

But in some alternative embodiments, error amplifier 416 has slightly different transport function, by:

Verr=-Kv* (Vin-Vref)+Ki*Iout_avg equation 3

Provide, wherein, Iout_avg is the mean value of electric current I out.In some embodiment of these embodiments, Iout_avg is the signal Io_avg from current filter subsystem 402.But in other embodiment of these embodiments, Iout_avg stems from other filter circuit, is such as similar to the circuit of current filter subsystem 402.

Verr is that the fact of the function of Vin facilitates rapid system response, thus contributes to setting up MPP operation fast.In addition, Verr is that the fact of the function of signal Io helps attenuation factor, thus contributes to that the ring during the working point Spline smoothing relevant to MPPT is minimized and even eliminate.And, MPPT based on input/output power (with only based on voltage or electric current contrary) the fact MPPT controller 302 may be made can to work together with the various loads of voltage source load with comprising current source load.

Depend on the embodiment of different sub-systems block, control subsystem 338 can be adjusted to the mixed signal that the signal making to process is voltage signal, current signal or voltage and current signal herein.Such as, depend on the embodiment of electric current reconstructing device subsystem 340, represent that the signal Io of the electric current flowing out output port 314 can be current signal or voltage signal.Again such as, depend on the configuration of multiplier 410, represent that the signal Po of the power exported from output port 314 can be curtage signal.And it is simulating signal and/or digital signal that control subsystem 338 can be adjusted to the signal making to process herein.

Fig. 5 shows a kind of method 500 for using control subsystem 338 to make the maximizes power sent out from output port 314.Method that method 500 can be considered to " disturbance observation ", wherein, periodically disturbance Vref, and observe the effect of disturbance, to determine which direction should adjust Vref value to increase signal Po to.

In step 502, convergent-divergent subsystem 404, convergent-divergent subsystem 408 are adjusted to and make signal scaled_Io_avg and scaled_Vp_avg respectively within the scope of its first numerical range and second value.This signal convergent-divergent contributes to when generating signal Po, the dynamic range of multiplier 410 being maximized.In step 504, MPPT control circuit 412 is sampled and is stored multiplier output signal Po, to serve as the reference point before Vref disturbance.In step 506, the value of Vref is changed the first step-length, with disturbance Vref by changing signal Vref order by MPPT control circuit 412.This Vref disturbance or be just, or be negative, depend on that last Vref disturbance causes the increase of Po still to reduce.Specifically, if last Vref disturbance causes the increase of Po, Vref just stepping in the same direction.On the other hand, when last Vref disturbance causes the reduction of Po, Vref just stepping in the opposite direction.In step 508, control circuit 412 is sampled Po again, and the Vref disturbance of determining step 506 increases Po still reduces Po.Method 500 repeats every now and then, thus cause control subsystem 338 the MPP place of power supply 304 or near operating power 304.

But should be realized, control subsystem 338 can be operated by the method except method 500.Such as, MPPT control circuit 412 can alternatively be suitable for by periodically adjusting signal Vref order, to make the inswept numerical range of Vref, calculate the signal Po at each the value place in these values, and determine which value of Vref causes the maximal value of signal Po to determine MPP condition of work.

Some embodiments of MPPT controller 302 can be used to the absolutely duty cycle operation supporting gauge tap device 328.In these embodiments, the disturbance observation of Fig. 5 be revised as make the dutycycle when gauge tap device 328 be absolutely time, (step 506) that the value of Vref always reduces.Increase due to the Vref at 100 duty cycle operation can not cause the condition of work of MPPT controller 302 to change, so be necessary to this amendment of method 500, because dutycycle increases with the Vref increased, and dutycycle can not increase above absolutely.

In some cases, even if when the maximum gain setting of electric current convergent-divergent subsystem 404, the value of signal Io also can be too small in the first numerical range for zooming to.The value of little scaled_Io_avg can make to determine that signal Po becomes difficult or impossible according to the product of scaled_Io_avg and scaled_Vp_avg then.Therefore, how little the value that electric current convergent-divergent subsystem 404 is suitable for alternatively regardless of Io_avg is, also makes the value of scaled_Io_avg not drop to below minimum threshold.In these embodiments, signal scaled_Io_avg can not change in response to the Vref disturbance in little output current Iout value, and makes the average voltage (instead of output power) across output port 314 maximize under these conditions.MPPT control circuit 412 is not advantageously needed to change pattern to support low Iout level or to introduce discontinuous in Iout transport function in this technology of little Iout value process MPP operation.

Fig. 6 shows an example of the operation of embodiment, wherein, does not allow signal scaled_Io_avg to drop to below threshold value.In this embodiment, electric current panntographic system 404 is suitable for signal scaled_Io_avg to remain in the first numerical range of being defined by upper threshold value 602 and lower threshold value 604, and no matter how little the value of signal Io_avg have.In input range 606, the value of signal Io_avg is so little, so that signal scaled_Io_avg is set as its minimum threshold corresponding with lower threshold value 604 by electric current panntographic system 404.Dotted line 608 represents if the minimum value of scaled_Io_avg is not constrained to lower threshold value 604, scaled_Io_avg by electric current convergent-divergent subsystem 404 can have what value.

In some other embodiments, electric current convergent-divergent subsystem 404 is suitable for increasing positive offset amount to scaled_Io_avg under little Io_avg value, makes scaled_Io_avg to drop to below minimum threshold.Such as, the input range 606 of Fig. 6 is again considered.In some embodiment substituted, electric current convergent-divergent subsystem 404 is suitable for, when Io_avg increases positive offset amount when inputting in numerical range 606 to scaled_Io_avg, making scaled_Io_avg can not drop to lower threshold value less than 604.In these embodiments, scaled_Io_avg keeps the shape identical with Io_avg.Thus, dotted portion 608 can keep diagonal line, but part 608 can be displaced in the numerical range that defined by upper threshold value 602, lower threshold value 604.

Control subsystem 338 also comprises extra Vref control circuit 426, Vref control circuit 426 alternatively in order to implement one or more additional features of controller 302.Although extra Vref control circuit 426 is symbolically depicted as discrete block, it is integrated in one or more pieces in other block of control subsystem 338 alternatively, is such as integrated in MPPT control circuit 412.

Extra Vref control circuit 426 is suitable for preventing Vin from dropping to below minimum value and/or rising to more than maximal value alternatively.Expect to limit minimum Vin value to support the proper handling of MPPT controller 302.On the other hand, expect that the maximal value limiting Vin is to prevent the infringement due to high voltage condition to power supply 304 and/or MPPT controller 302, and/or promote security.Therefore, in certain embodiments, if Vin can be caused to drop to below threshold value if Vin drops to below threshold value or reduces Vref, then extra Vref control circuit 426 is suitable for covering (override) MPPT control circuit 412, and prevent Vref from reducing further, or even increase Vref.Similarly, in certain embodiments, if Vref can be caused to rise to more than threshold value if Vin rises to more than threshold value or increases Vin, then extra Vref control circuit 426 is suitable for covering MPPT control circuit 412 and the further increase preventing Vref.

And, in certain embodiments, if the value of signal Io drops to below threshold value, extra Vref control circuit 426 is suitable for covering MPPT control circuit 412 and reducing Vref, thus prevents the possible insecure operation relevant to minimum output current Iout value.In a particular embodiment, set the threshold to can by electric current reconstructing device subsystem 340 differentiate just above minimum output current Iout value.Such as, consider that wherein electric current convergent-divergent subsystem 404 is adapted so that the value of scaled_Io_avg does not drop to the embodiment of below minimum threshold.As above, in this embodiment, when signal Io drops to below threshold value, the average voltage (instead of output power) across output port 314 is maximized.But this maximization of average output port 314 voltage can not make power supply 304 maximizes power; On the contrary, power supply 304 can be operated in high voltage, the low current point of its below MPP.But, reduce the dutycycle that Vref can increase gauge tap device 328, thus increase output current Iout value and power supply 304 is worked closer to its maximum power point.Reduce Vref and also likely can increase output current Iout value, normal MPPT can be recovered.Therefore, some embodiments comprise (1) circuit in order to prevent the value of scaled_Io_avg from dropping to below threshold value, and (2) are if the value in order to signal Io drops to the circuit that below threshold value just reduces Vref.

In certain embodiments, if control subsystem 338 is suitable for signal Io drop to below the threshold value of the possible negative output current of instruction, just operation-control switch device 328 is carried out with fixed duty cycle.Promote with inverse current work with fixed duty cycle operation-control switch device 328, wherein, Iout have replace on the occasion of negative value.Reverse current condition can be electrically coupled in the application of output port 314 at one or more additional power supply and occur, such as in the application of string (string) comprising photovoltaic device in parallel.Be contemplated that when signal Io indicates possible negative output current, control subsystem 338 can carry out operation-control switch device 328 with large fixed duty cycle (such as 95 percent or absolutely dutycycle).Typically the threshold value of negative output current possible for instruction can be set as lower than other lower output current threshold value, if such as Io as above drops to below threshold value just in order to reduce the threshold value of Vref.

In some cases, the size of Vref disturbance is reduced when can be desirably in high gauge tap device 328 dutycycle, to promote the MPPT of more robust, because the large Vref step-length when high duty ratio can cause less desirable operation.As by equation 2 and equation 4 visible, the change in duty cycle in response to given Vref step-length is not necessarily constant, because change in duty cycle can change according to Io and other factors.Change in duty cycle when little Io value is typically greater than the change in duty cycle when large Io value, and low Io value typically corresponds to big space rate operation.Thus, under high duty cycle operation, given Vref step-length usually causes relatively large dutycycle step-length.Big space rate step-length then can adversely affect MPPT and/or load 306 operates.

Therefore, in certain embodiments, extra Vref control circuit 426 cooperates with MPPT control circuit 41, and make compared to when low duty ratio, MPPT control circuit 412 changes the less step-length of Vref when high duty ratio.Specifically, when the order of the dutycycle in order to control gauge tap device 328 is lower than first threshold, circuit 412, circuit 426 make Vref change the first step-length during MPPT, and when the order of the dutycycle in order to control gauge tap device 328 is higher than Second Threshold, circuit 412, circuit 426 make Vref change the second step-length during MPPT.Second step-length is less than the first step-length, and first threshold is less than or equal to Second Threshold.Contemplate in many examples, first threshold can be less than Second Threshold, delayed with what realize between large Vref step-length operator scheme and little Vref step-length operator scheme.Such as, the order in order to the dutycycle controlling gauge tap device 328 stems from the signal 422 generated by logic and drive circuit 420.

Can also expect when MPP place or near work time reduce the size of Vref disturbance because in this case, Vref disturbance can temporarily cause power supply 304 to operate away from its MPP.Thus, in certain embodiments, extra Vref control circuit 426 cooperates with MPPT control circuit 412, and make compared to when power supply 304 is away from its MPP, when power supply 304 is close to its MPP, MPPT control circuit 412 changes the less step-length of Vref.Specifically, when the difference of the Po between continuous print Vref disturbance is lower than first threshold, circuit 412, circuit 426 make Vref change the first step-length during MPPT, when the difference of the Po between continuous print Vref disturbance is higher than Second Threshold, circuit 412, circuit 426 make Vref change the second step-length during MPPT.Second step is grown up in the first step-length, and first threshold is less than or equal to Second Threshold.Contemplate in many examples, first threshold can be less than Second Threshold, delayed with what realize between large Vref step-length operator scheme and little Vref step-length operator scheme.

Expect in numerous applications to reach MPP operation fast.Therefore, in certain embodiments, control subsystem 338 is suitable for when MPPT controller 302 works at the extreme point unlikely representing MPP operation (such as when starting) and changes Vref fast, thus promotes at the operational Fast Convergent of MPP.In these embodiments, MPPT control circuit 412 and extra Vref control circuit 426 cooperate, make compared to when gauge tap device 328 is in normal duty cycle condition, when being in extreme duty cycle condition in order to gauge tap device 328, MPPT control circuit 412 is with the Vref of speed change faster.Specifically, when the order of the dutycycle in order to control gauge tap device 328 is in the first numerical range, circuit 412 changes Vref with first rate, and when the order of the dutycycle in order to control gauge tap device 328 is within the scope of second value, circuit 412 changes Vref with the second speed.Second speed is greater than first rate, and the very big or minimum duty command of second value Range Representation, and the first numerical range represents normal duty cycle order.Such as, in one embodiment, the first numerical range represent the dutycycle of gauge tap device 328 zero and absolutely between order, and the dutycycle of second value Range Representation gauge tap device 328 be less than zero or be greater than percent 100 order.

Power supply 304 is in the embodiment of photovoltaic device wherein, roughly can estimate the MPP of described device before MPPT controller 302 starts to switch according to the open-circuit voltage of device.Specifically, the somewhere of the MPP of photovoltaic device typically between nine ten five ten to percent 8 percent of its open-circuit voltage occurs.Vref initial setting can be accelerated MPP operation to this scope of photovoltaic device open-circuit voltage.

Therefore, in certain embodiments, when MPPT controller 302 starts, extra Vref control circuit 426 is suitable for the initial value setting Vref at least in part based on the initial average voltage across input port 308.Such as, in certain embodiments, extra Vref control circuit 426 is suitable for the initial value of the setting Vref when starting, and makes gauge tap device 328 at first carry out work with the dutycycle of the mark (such as within nine ten five ten to percent 8 percent of its initial value) average voltage across input port 308 roughly being remained its initial value.MPPT control circuit adjusts Vref value subsequently to realize MPP operation, such as above relative to described in Fig. 5.

In certain embodiments, gauge tap device 328 and/or continued flow switch device 330 comprise one or more switching devices of the field effect transistor (FET) for dynamic conditioning size.The FET of this dynamic conditioning size comprises with the some independent controlled member of the composition FET form of electric coupling in parallel separately, and wherein, effectively the quantity of this composition FET of (active) can change, with the size of dynamic conditioning FET.The attribute of FET can be changed (that is, effectively it forms the quantity of FET) by changing its size.Such as, total FET channel resistance can be reduced by increasing FET size (that is, increasing the quantity of effective composition FET).But effective composition FET is more, grid capacitance and associated switching losses larger (assuming that each composition FET is by common driver drives).For each dutycycle, typically there is the minimized best FET size of summation of the loss making the loss relevant to resistance and be correlated with grid capacitance.

In some embodiments of the FET and electric current reconstructing device subsystem 340 that comprise one or more dynamic conditioning size, if the value of signal Io_avg drops to below threshold value, control subsystem 338 just reduces FET size, namely, reduce the quantity of effective composition FET, to change the gain of electric current reconstructing device subsystem 340.In these embodiments, the quantity of effective composition FET is depended in the gain of electric current reconstructing device subsystem 340 at least in part, and gain increases along with the quantity reduction of effective composition FET.Thus, reduce the value that FET size increases reconstructor gain and signal Io_avg, thus may reduce or even eliminate the difficulty relevant to the low value of signal Io_avg/Io_avg_scaled, such as above relative to the difficulty described in Fig. 6.Therefore, reducing FET size can make control subsystem 338 can perform MPPT to measure lower output current Io amount than the output current Io feasible when not reducing FET size.

Fig. 7 shows electronic filter 700.Each in electric current and voltage filter subsystem 402,406 comprises the example of such as wave filter 700.But, alternatively can implement filter subsystem 402 and/or filter subsystem 406 with different filter type.Such as, in some other embodiments, implement voltage filter subsystem 406 with R-C wave filter, to promote simplicity and low cost.And electronic filter 700 is not limited to in control subsystem 338.

Wave filter 700 can be used to the output current signal 702 generating the mean value representing input current signal 704.Even if when input current signal 704 is bipolar signals, such as when input current signal 704 has little direct current (DC) component with when exchanging greatly (AC) component, output current signal 702 is unipolar signal under the operating conditions of expection.In the linguistic context of presents, unipolar signal keeps plus or minus.In other words, unipolar signal is not changing between negative value.On the other hand, bipolar signal is changing between negative value.As known in the art, unipolar signal is processed usually more simply too much than process bipolar signal.Such as, pair transistor current mirror may be used for convergent-divergent unipolar signal, and needs significantly more complicated circuit to carry out convergent-divergent bipolar signal.Therefore, under the operating conditions of expection, output current signal 702 is that the fact of unipolar signal is advantageous particularly in some applications.

Wave filter 700 comprises integrator subsystem 706 and transconductance circuit, and transconductance circuit comprises the first trsanscondutance amplifier 708 and the second trsanscondutance amplifier 710.Integrator subsystem 706 comprises the integrator 712 with reversed input terminal and non-inverting input terminal, across the resistance device 714 of the input end electric coupling of integrator, and electric coupling constant pressure source 716 between the non-inverting input and reference mode 718 of integrator.The inverting input of integrator is electrically coupled to node 724.The AC component 720 of input current signal 704 is flowed in node 724 by resistance device 714, thus generates the AC signal across the input end of integrator 712.Integrator 712 carries out integration to this AC signal, and generates the integrator signal AVG of the mean value representing input current signal 704.

Second trsanscondutance amplifier 710 generates the current signal 722 flowed in node 724 in response to integrator signal AVG, make integrator subsystem 706 and the second trsanscondutance amplifier 710 jointly form closed-loop path low-pass filter.Current signal 722 represents the DC component of input current signal 704, makes DC current signal 722 and AC current signal 720 jointly form the input current signal 704 flowing out node 724.First trsanscondutance amplifier 708 is also subject to integrator signal AVG and controls, to generate output current signal 702, and output current signal 702 mirror image DC current signal 722 and thus proportional with the mean value of input current signal 704.

Therefore, integrator subsystem 706 is operated in bipolarity territory, to filter the AC component of bipolar or input current signal 704, and the first trsanscondutance amplifier 708 and the second trsanscondutance amplifier 710 are operated in unipolarity territory, to process the DC component of one pole or input current signal 704.This separating treatment of the bipolar and monopole component of input current signal 704 promotes the bipolar AC component that avoids in filtering input current signal 704 and keeps the accuracy of one pole DC component simultaneously.

Fig. 8 shows signal convergent-divergent subsystem 800.Each in electric current and voltage scaling subsystem 404,408 comprises the example of such as convergent-divergent subsystem 800.But convergent-divergent subsystem 404 and/or convergent-divergent subsystem 408 can alternatively comprise different zoom circuit.And signal convergent-divergent subsystem 800 is not limited to in control subsystem 338.

Subsystem 800 comprises amplifier 802, controls transistor 804, programmable resistance 806 and mirrored transistor 808,810.In the linguistic context of presents, the field effect transistor terminal being labeled as G, D and S corresponds respectively to grid, drain electrode and source terminal.Output terminal 812 drive control transistor 804 of amplifier 802, controls transistor 804 electric coupling between mirrored transistor 808 and programmable resistance 806.Mirrored transistor 808 electric coupling is at high side power supply node or rail 814 and control between transistor 804, and programmable resistance 806 electric coupling is between control transistor 804 and reference mode or rail 816.The inverting input of amplifier 802 is electrically coupled to node 818, and node 818 links control transistor 804 and programmable resistance 806, and the non-inverting input of amplifier 802 receives input voltage signal 820.

Amplifier 802 controls the operation of transistor 804, makes the current signal 822 flowing through transistor 804 and programmable resistance 806 cause the voltage across programmable resistance 806 to equal input voltage signal 820.Thus, amplifier 802 regulates the voltage across variohm 806 in response to input voltage signal 820.Transistor 810 image current signal 822, to generate the output current signal 824 proportional with current signal 822.The resistance value of programmable resistance 806 is set by steering logic 826.Thus, amplifier 802, control transistor 804, programmable resistance 806 and mirrored transistor 808,810 form mutual conductance subsystem, input voltage signal 820 is converted to output current signal 824 by described mutual conductance subsystem operable ground, wherein, steering logic 826 sets the resistance of programmable resistance 806 to control the gain of mutual conductance subsystem.

Along with gain margin increases, the quantity realizing the gain step size needed for change in gain expected in each step also increases.Thus, in certain embodiments, programmable resistance 806 and steering logic 826 are chosen as and make to make gain change the subduplicate coefficient of two at each gain step size, to be provided in trading off between large gain margin and the quantity of gain step size.

Subsystem 800 also comprises the extra mirrored transistor 826 of image current signal 822.Comparer 828 is by the current signal of mirror image compared with reference current signal 830, and if the current signal of mirror image is at least equally large with reference current signal, comparer 828 just exports GainOK signal.Once enable signal ENABLE effectively (assertion), programmable resistance 806 is set as its maximum resistance by steering logic 826, thus gain is set as minimum value.Steering logic 826 incrementally reduces the resistance of programmable resistance 806 subsequently in response to clock signal clk, thus gain is increased progressively, until effective from the GainOK signal of comparer 828.Thus, once signal ENABLE is effective, signal convergent-divergent subsystem 800 convergent-divergent output current signal 824, to have at least equally large with reference signal 830 value.Comprise the subsystem 800 as convergent-divergent subsystem example control subsystem 338 embodiment in, such as, once the step 502 of manner of execution 500 (Fig. 5), just make signal ENABLE effective.

Comprise the subsystem 800 as convergent-divergent subsystem example control subsystem 338 some embodiment in, before at convergent-divergent subsystem 404, convergent-divergent subsystem 408 again convergent-divergent, it exports, Vref disturbance may cause the large increase of scaled_Io_average and/or scaled_Vp_avg.This increase greatly of signal quantity can make multiplier 410 saturated, thus causes incorrect MPPT to operate.Therefore, subsystem 800 also comprises mirrored transistor 832, comparer 834 and reference current source 836 alternatively, to detect the large increase (it can cause unsuitable MPPT to operate) of output current signal 824 value.

Specifically, mirrored transistor 832 image current signal 822, and comparer 834 by the current signal of mirror image compared with reference current signal 836, reference current signal 836 is greater than reference current signal 830.In certain embodiments, reference current signal 836 is reference current signals 830 4 times, and represents under it, think the threshold value that output current signal 824 value is excessive.If the value of image current is at least equally large with reference current signal 836 value, comparer 834 exports GainHi signal.

Comprise the subsystem 800 as convergent-divergent subsystem example control subsystem 338 some embodiment in, MPPT control circuit 412, when the Po value before not comparing disturbance and after disturbance, increases Po value by supposition disturbance and effectively makes response to GainHi.As mentioned above, Po calculates can be inaccurate after the large-signal effectively indicated by GainHi increases, and compare GainHi effectively after the Po value MPPT that can lead to errors operate.

Some embodiment of signal convergent-divergent subsystem 800 can realize one or more advantages that classical signal convergent-divergent subsystem not necessarily can realize.Such as, the gain of subsystem 800 and the resistance of programmable resistance 806 are inversely proportional to, thus allow subsystem 800 to realize the gain of wide region by the resistance changing programmable resistance 806 simply.

Again such as, the configuration of subsystem 800 facilitates the fast and stable of gain after gain step size changes, and stabilization time keeps relative constancy with change in gain.Specifically, ignore second-order effects, control transistor 804 and serve as close to unity gain buffer, and no matter the resistance of programmable resistance 806 is how.Thus, the loop gain of amplifier 802 changes with resistor 806 and almost constant, causes the bandwidth sum of amplifier 802 also to keep relative irrelevant with resistor 806 resistance value stabilization time.Therefore, typically can selective amplifier 802, to provide enough stabilization time fast when change in gain need not be solved.

Fig. 9 shows multiplier 900.Multiplier 900 is such as used to implement the multiplier 410 of control subsystem 338.But multiplier 410 can alternatively be implemented by different way.And multiplier 900 is not limited to in control subsystem 338.

Multiplier 900 comprises first input end mouth 902, second input port 906 and output port 910.First input current signal 904 flows in first input end mouth 902, and the second input current signal 908 flows in the second input port 906, and output current signal 912 flows in output port 910.First field effect transistor 914 and first input end mouth 902 coupled in series electrical, the second field effect transistor 916 and the second input port 906 coupled in series electrical, and the 3rd field effect transistor 918 and output port 910 coupled in series electrical.As described below, multiplier 900 also comprises control circuit, described control circuit is suitable for controlling each in the first transistor, transistor seconds and third transistor, make transistor in its linear zone or three polar regions, and the value of output current signal 912 and (a) first value and (b) second product of value of input current signal 908 of input current signal 904 is proportional.

Control circuit comprises the 4th effect transistor 920, the 5th effect transistor 922 and the 6th field effect transistor 924, and amplifier 926, amplifier 928.The grid of the first transistor 914 and third transistor 918 is electrically coupled together at common node 932 place, and the grid of transistor seconds 916, the 4th transistor 920 and the 5th transistor 922 is electrically coupled together at different common node 940 places.4th transistor 920 and the 5th transistor 922 have separately x coupling cell transistor, wherein, x be greater than zero integer.Therefore, transistor 920, transistor 922 can have identical channel resistance when working under identical gate source voltage, because two transistors have the matching unit transistor of equal number.On the other hand, the first transistor 914, transistor seconds 916 and third transistor 918 have m*x coupling cell transistor, wherein, m be greater than one integer.Therefore, each in transistor 914, transistor 916 and transistor 918 can have the channel resistance equaling R/m, wherein, R is the channel resistance of transistor 920 or transistor 922, assuming that each in transistor 914, transistor 916, transistor 918, transistor 920 and transistor 922 works under common gate source voltage.

Amplifier 926 is suitable for controlling the grid of the first transistor 914, and its channel resistance R914 is determined by the voltage of reference mode 938 and the first input current signal 904.Specifically, amplifier 926 forces the voltage across the first transistor 914 equal with the voltage on node 934 to become identical with the voltage across the 4th transistor 920, makes:

R914=V938/I904 equation 4

Wherein, V938 is the voltage on node 938, and I904 is the value of the first input current signal 904.Each transistor 914,918 has identical channel resistance, because two transistors have m*x the cell transistor mated, and is driven by the common gate source voltage from amplifier 926.

Amplifier 928 controls the grid of the 6th transistor 924, makes the voltage across transistor seconds 916 identical with the voltage (it equals the voltage on node 930) across third transistor 918.Therefore, the value of output current signal 912 is provided by following:

I912=V942/R914=V942/ (V938/I904)=I904* (V942/V938) equation 5

Wherein, I912 is the value of output current signal 912, and V942 is the voltage on node 942.Provided by following at the voltage at reference mode 938 place:

V938=(Iref/m) * R920 equation 6

Wherein, R920 is the channel resistance of the 4th transistor 920.4th transistor 920 and the 5th transistor 922 form current mirror, described current mirror is configured such that the drain-source current flowing through the 5th transistor 922 has the value equaling Iref, and the drain-source current flowing through the 4th transistor 920 has the value equaling Iref/m.As described below, this is configured with and helps guarantee that transistor 914, transistor 916, transistor 918, transistor 920 such as proper handling is desirably operated in its three polar region.

The grid of transistor seconds 916 and the 4th transistor 920 is all coupled to node 940, and the channel resistance R916 of transistor seconds 916 is provided by following:

R916=R920/m equation 7

Therefore, can illustrate, the voltage on node 942 is provided by following:

V942=I908*R916=I908* (R920/m) equation 8

Wherein, I908 is the value of the second input current signal 908.Therefore provided by following at the voltage of node 942 and the ratio of the voltage at node 938:

V942/V938=I908* (R920/m)/[(Iref/m) * R920]=I908/Iref equation 9

Equation 9 is substituted into equation 5, obtains following:

I912=(I904*I908)/Iref equation 10

The value that equation 10 illustrates output current signal 912 and (a) first value and (b) second product of value of input current signal 908 of input current signal 904 is proportional.Equation 10 also illustrates that output current signal 912 and reference current signal Iref are inversely proportional to.

Multiplier 900 can realize one or more advantages that conventional multiplier not necessarily can realize.Such as, each current signal naturally of input signal 904, input signal 908 and output signal 912, contrary with voltage signal, this is easy to multiplier 900 to be connected with external circuit in some applications.Again such as, and need separate power supply or be reference with mid-rail current potential signal is contrary, some embodiment can by being that the single unipolar power source of reference and signal carry out work with ground.In addition, some embodiment of multiplier 900 does not need resistor, as shown in Figure 9.The circuit forming non-resistance device especially has superiority, because resistor can take sizable integrated circuit lead area in integrated circuit embodiment.

And the configuration of multiplier 900 is by assisting in ensuring that transistor 914, transistor 916, transistor 918, transistor 920 such as proper handling is desirably operated in its linear zone or three polar regions the reliable operation facilitated under the suboptimal conditions of such as temperature and/or manufacturing process flex point.Specifically, configuration multiplier 900 makes the drain-source current of the 4th transistor 920 doubly ensure that the 4th transistor 920 is operated in its three polar region than the little m of the drain-source current of the 5th transistor 922, and voltage on reference mode 938 is relatively low.Low-voltage on reference mode 938 also causes the first transistor 914 and third transistor 918 to be operated in its three polar region, because amplifier 926 forces the voltage across the first transistor 914 identical with the voltage on reference mode 938.Transistor seconds 916 can be operated in its three polar region then, as long as its drain-source current is less than m*Iref, because transistor is controlled by the 5th transistor 922 for this reason.Thus, the value of parameter m is larger, and transistor 914, transistor 916, transistor 918, transistor 920 more deeply (further) are operated in its three polar region.As long as m is greater than two also while the value of the first input current signal 904 and the second input current signal 908 is less than Iref, even if in temperature and/or manufacturing process flex point, transistor 914, transistor 916, transistor 918, transistor 920 also can be operated in its three polar region.

As mentioned above, logic and drive circuit 420 (Fig. 4) export two signals 422,424, gauge tap device 328, switching device 330.Each in signal 422, signal 424 typically in different power domain because control and continued flow switch device with different node for reference.

Such as, Figure 10 is the possible embodiment of logic in embodiment and drive circuit 420 one, and wherein, gauge tap device 328 is embodied as N slot field-effect transistor 1028, and continued flow switch device 330 is embodied as N slot field-effect transistor 1030.But it should be understood that MPPT controller 302 is not limited to Figure 10 embodiment.

Regulator 1002 generates " house keeper " power rail (Vcc) according to positive supply node Vddh.Vcc is with reference power source node Vss for reference, and Vcc or another rail of stemming from it are powered for the major part (such as PWM comparer 418) for the circuit in control subsystem 338.

Signal PWM is in Vcc/Vss power domain, because PWM comparer 418 is powered from Vcc power rail, it take Vss as reference.Signal PWM is converted to the gauge tap signal 1006 for controlling transistor 1028 by the steering logic 1004 of circuit 420, and for controlling the afterflow signal 1008 of transistor 1030.Two signals 1006,1008 are all in Vcc/Vss power domain.Drive circuit 1010 generates gate drive voltage signal Vgs1 in response to afterflow signal 1008.Gate drive voltage signal Vgs1 driving transistors 1030, or in other words, control the gate source voltage of transistor 1030 to control the switch to transistor 1030.The source electrode of transistor 1030 is electrically coupled to reference mode Vss.Therefore, gate drive voltage signal Vgs1 is also in Vcc/Vss power domain.

Replace reference mode Vss, control transistor 1028 with switching node Vx for reference." bootstrapping " Voltage rails (Vbst) that it is reference with switching node Vx that the bootstrapping parts of driver and boostrap circuit 1012 generate, allows circuit 1012 to be just be relative to the source electrode of transistor by the raster data model of transistor 1028.The energy-storage travelling wave tube of such as capacitor 1014 is used for for bootstrap voltage mode rail stored energy.Driver and boostrap circuit 1012 generate the gate drive signal Vgs2 in Vbst/Vx power domain, with driving transistors 1028.

Signal in Vcc/Vss territory can not directly be electrically coupled to Vbst/Vx territory, because two territories have different references.Specifically, the reference Vss in Vcc/Vss territory is substantially in constant voltage.On the other hand, Vbst/Vx territory is with switching node Vx for reference, and it has large voltage swing.Such as, Figure 11 shows the curve map of voltage on switching node Vx and the relation of time.Signal PWM also shown by dashed lines on described curve map.As observed, the voltage responsive of switching node Vx in signal PWM change and significantly change.

Therefore, logic and drive circuit 420 comprise level shifter 1016, and level shifter 1016 is in order to be shifted gauge tap information 1006 as the signal 1018 Vbst/Vx territory from Vcc/Vss territory.Thus, the steering logic 1004 in Vcc/Vss territory is connected with the driver in Vbst/Vx territory and boostrap circuit 1012 by level shifter 1016.Figure 12 shows signal level shift unit 1200, and it is the possible embodiment of of level shifter 1016.But, should be realized, otherwise can implement level shifter 1016.In addition, level shifter 1200 is not limited to in circuit 420.

Level shifter 1200 is received in complementary input signal INP, INN in Vcc/Vss power domain.Before signal INP, signal INN are coupled to the transconductance stage 1206 in Vcc/Vss power domain, phase inverter 1202 makes signal INP anti-phase, and phase inverter 1204 makes signal INN anti-phase.Transconductance stage 1206 is suitable in response to input signal INP, INN and generates complementary current signal 1208,1210.

The output terminal of phase inverter 1202 is electrically coupled to the grid of P-channel field-effect transistor (PEFT) transistor 1212 and N slot field-effect transistor 1214, and they are configured to control across the gate terminal of N slot field-effect transistor 1216 and the voltage of source terminal.The output terminal of phase inverter 1204 is electrically coupled to the grid of P-channel field-effect transistor (PEFT) transistor 1218 and N slot field-effect transistor 1220, and they are configured to control across the gate terminal of N slot field-effect transistor 1222 and the voltage of source terminal.When signal INP is in its high state, transistor 1212 is in its conducting state, and transistor 1214 is in its nonconducting state, the gate source voltage of transistor 1216 is substantially zero, and transistor 1216 is for its nonconducting state.On the other hand, when signal INP is in its low state, transistor 1212 is in its nonconducting state, and transistor 1214 is in its conducting state, make the gate source voltage of transistor 1216 be substantially equal to Vcc-Vss, and transistor 1216 is for its conducting state.Transistor 1218, transistor 1220 and transistor 1222 work in a similar fashion in response to signal INN.

Complementary current signal 1208,1210 is electrically coupled to the load circuit 1224 in Vbst/Vx power domain, and it is suitable in response to current signal 1208, current signal 1210 and generate complementary output voltage signal OUTP, OUTN.Load circuit 1224 comprises P-channel field-effect transistor (PEFT) transistor 1226, P-channel field-effect transistor (PEFT) transistor 1228.Transistor 1226 electric coupling between Vbst and transistor 1222, and is adapted to operate in its linear zone, thus the value of Limited Current signal 1208.Similarly, transistor 1228 electric coupling between Vbst and transistor 1216, and is adapted to operate in its linear zone, thus the value of Limited Current signal 1210.

The first inverter circuit 1230 and the second inverter circuit 1232 that it is reference that load circuit 1224 also comprises with Vbst/Vx power domain.First inverter circuit 1230 is suitable for carrying out generating output signal OUTP according to current signal 1208, and the second inverter circuit 1232 is suitable for according to current signal 1210 generating output signal OUTN.Phase inverter 1230 comprises P-channel field-effect transistor (PEFT) high-side transistor 1234 and N channelling effect low side transistors 1236.Transistor 1234 electric coupling is between the high siding track S2 and output node 1238 of phase inverter, and transistor 1236 electric coupling is between output node 1238 and Vx.The grid of transistor 1234, transistor 1236 is electrically coupled to the drain electrode of transistor 1222, transistor 1226, and the drain electrode of transistor 1222, transistor 1226 is connected to the high siding track S1 of inverter circuit 1232.Similarly, phase inverter 1232 comprises P-channel field-effect transistor (PEFT) high-side transistor 1240 and N channelling effect low side transistors 1242.Transistor 1240 electric coupling is between the high siding track S1 and output node 1244 of phase inverter, and transistor 1242 electric coupling is between output node 1244 and Vx.The grid of transistor 1240, transistor 1242 is electrically coupled to the drain electrode of transistor 1216, transistor 1228, and the drain electrode of transistor 1216, transistor 1228 is connected to the high siding track S2 of inverter circuit 1230.

The high siding track S2 of inverter circuit 1230 is electrically coupled to Vbst by P-channel field-effect transistor (PEFT) transistor 1246, and the high siding track S1 of inverter circuit 1232 is electrically coupled to Vbst by P-channel field-effect transistor (PEFT) transistor 1248.Grid due to transistor 1246 is electrically coupled to the drain electrode of transistor 1248 and the grid of transistor 1248 is electrically coupled to drain electrode, transistor 1246 and transistor 1248 cross-couplings of transistor 1246.The grid of transistor 1246 is electrically coupled to the high siding track S1 of inverter circuit 1232, and the grid of transistor 1248 is electrically coupled to the high siding track S2 of inverter circuit 1230.Cross-coupled transistor 1246,1248 achieves Regenerative feedback, thus facilitates high siding track S1, the quick switching of high siding track S2 and the corresponding fast operating of level shifter 1200.

In high-side transistor 1234, the meaning of high-side transistor 1240 than low side transistors 1236, low side transistors 1242 " stronger ", inverter circuit 1230 and inverter circuit 1232 are skewed.Specifically, when low side transistors 1236 is in its conducting state, high-side transistor 1234 can be used to five ten at least percent of the current potential be pulled upward to by output node 1238 on high siding track S2.Similarly, when low side transistors 1242 is in its conducting state, high-side transistor 1240 can be used to five ten at least percent of the current potential be pulled upward to by output node 1244 on high siding track S1.In some cases, need this deflection of inverter circuit 1230, inverter circuit 1232 to realize suitable operation.

Such as, situation when considering that wherein INP is effective.Transistor 1222 can be in its conducting state, and transistor 1216 can be in its nonconducting state, makes high siding track S1 pull down near Vss, and is pulled upward near Vbst by high siding track S2.Thus, high-side transistor 1234 can work in its conducting state, and low side transistors 1236 can work in its nonconducting state, makes output signal OUTP for high.On the other hand, high-side transistor 1240 can work in its nonconducting state, and low side transistors 1242 can work in its conducting state, makes output signal OUTN be low.But, if the current potential of switching node Vx drop to reference mode Vss current potential below (such as because the afterflow of continued flow switch device 330 operates), low side transistors 1236 just can not be made to end, because its gate source voltage just can be.Thus, even if by inverter circuit 1230 deflection for making when low side transistors 1236 is in its conducting state, high-side transistor 1234 also can pull-up output node 1238, and to allow when Vx is in negative potential relative to Vss, its output state is changed into height from low by inverter circuit 1230.For similar reason by inverter circuit 1232 deflection, that is, when Vx is in negative potential relative to Vss, allow phase inverter that its output state is changed into height from low.

Load circuit 1224 also comprises diode 1250, diode 1252.The anode of diode 1250 is electrically coupled to Vx, and the cathodic electricity of diode 1250 is coupled to high siding track S1.The anode of diode 1252 is electrically coupled to Vx, and the cathodic electricity of diode 1252 is coupled to high siding track S2.Diode 1250, diode 1252 clamp across any voltage swing of transistor 1226, transistor 1228, thus help these transistors of protection to avoid transient voltage skew.

In certain environments, transistor 1222, transistor 1226 also help the switching accelerating level shifter 1200.Such as, again consider that wherein signal INP is high and signal INN is low situation.As mentioned above, transistor 1222, transistor 1234 and transistor 1242 can be in its conducting state, and transistor 1216, transistor 1236 and transistor 1240 can be in its nonconducting state, make signal OUTP for high and signal OUTN is low.In some cases, Vx can be negative potential relative to Vss, causes Vbst to be negative potential relative to Vcc.Therefore, the drain electrode of transistor 1216 can be in the current potential lower than its grid, and cause when the drain-to-gate voltage of transistor 1216 exceedes threshold value Vth, transistor 1216 is switched to its conducting state conditionally from its nonconducting state, and threshold value Vth is typically about 0.4 volt.This conducting of transistor 1216 can make electric current flow to rail S2 by transistor 1212, transistor 1216 from Vcc, thus is pulled upward to rail S2 higher than the difference between the about diode voltage of Vbst and Vth, and this accelerates the switching of inverter circuit 1230.High siding track S2 can not be pulled upward to and exceed about diode voltage (being about 0.7 volt) higher than Vbst, because rail S2 is clamped to Vbst by the drain-source body diode (not shown) of transistor 1246.When Vx is for time negative, the switching of inverter circuit 1232 is accelerated in the conducting of transistor 1222 in a similar fashion.

Level shifter 1200 can realize one or more advantages that traditional level shifter cannot realize.Such as, some embodiment of level shifter 1200 is very fast, or in other words, introduces minimal propagation delay when complementary input signal INP, INN are converted to complementary output signal OUTP, OUTN.Such as, in certain embodiments, though wherein Vx current potential lower than during Vss when, transmission delay was less than for 7 nanoseconds.This of level shifter 1200 relative accelerating part ground due to contain cross-linked transistor 1246,1248 and as above when Vx is negative relative to Vss transistor 1216, transistor 1222 promote the fact of switching fast.Such as in order to conducting (sometimes referred to as " leading directly to ") while the control that prevents the delay owing to switching in gauge tap device 328 from causing and continued flow switch device 328,330, fast operating is important.

Again such as, some embodiment of level shifter 1200 is exercisable when Vcc-Vss and Vbst-Vx is low to moderate one volt, thus may realize operation at a low input voltages.And level shifter 1200 uses the fact of differential wave (such as complementary current signal 1208,1210) to contribute to suppressing the common mode transient between Vcc/Vss territory and Vbst/Vx territory.

The Multi-instance of MPPT controller 302 can be electrically coupled together.Such as, Figure 13 shows the power-supply system 1300 comprising N number of example of MPPT controller 302 in photovoltaic application, wherein, N be greater than one integer.In this document, can by the Reference numeral in use bracket (such as, MPPT controller 302 (1)) carry out reference items object particular instance, and come with reference to any this project (such as, MPPT controller 302) with the Reference numeral without bracket.

The input port 308 of each MPPT controller 302 is electrically coupled to the respective photovoltaic device 1304 of public photovoltaic module 1305.Photovoltaic device 1304 is such as the group of the photovoltaic cell of single photovoltaic cell or electrical interconnection.But, the configuration of photovoltaic device 1304 can be changed when not departing from its scope.Such as, in some alternative embodiments, photovoltaic device 1304 is discrete photovoltaic devices, instead of the part of public module.Again such as, in some other embodiments, two or more photovoltaic device 1304 has different configurations.Also across each input port 308 electric coupling input capacitor 1324 separately.

Output port 314 and load 1306 coupled in series electrical of MPPT controller 302.One or more output capacitor 1334 across load 1306 electric coupling, and is shared by each MPPT controller in N number of MPPT controller 302.But in some alternative embodiments, load 1306 comprises sizable electric capacity, and because omitted herein capacitor 1334.In addition, in some other alternate embodiments, each MPPT controller 302 has the respective capacitor (not shown) across its output port 314 electric coupling.

MPPT controller 302 uses the interconnection inductance 1336 of the output circuit 1332 on-off circuit 326 being electrically coupled to load 1306, using as energy storage inductor.Although this interconnection inductance is symbolically depicted as discrete component, in fact it is along the loop distribution forming output circuit 1332.But some alternate embodiments comprise the one or more discrete inductor (not shown) with output circuit 1332 coupled in series electrical.Such as, each MPPT controller 302 has in the embodiment across the respective capacitor of its output port 314 electric coupling wherein, typically needs each MPPT controller 302 to have respective with discrete inductor that is its output port 314 coupled in series electrical.

Each MPPT controller 302 works substantially in an identical manner, as described in relative to the power-supply system comprising single MPPT controller 302 example.Such as, each MPPT controller 302 regulates the voltage Vin across its input port 308, with make from its separately photovoltaic device 304 extract maximizes power.In certain embodiments, MPPT controller 302 relative to each other out of phase works, to prevent the constructive interference of the transition caused because on-off circuit 326 operates.

MPPT controller 302 can be revised as the place-exchange making its control and continued flow switch device.Such as, MPPT controller 302 can be revised as and make switching device 330 be gauge tap device and switching device 328 is afterflow devices, thus allows when without drived control switching device when boostrap circuit.Due to this amendment, output port 314 can across switching device 328 (instead of across switching device 330) electric coupling.

the combination of feature

When not departing from its scope, above-mentioned feature and following claimed feature can combine in many ways.Following example illustrate the combination that some are possible:

(A1) a MPPT maximum power point tracking controller, can comprise: input port, and described input port is used for being electrically coupled to power supply; Output port, described output port is used for being electrically coupled to load; Gauge tap device; And control subsystem.Gauge tap device can be suitable for repeatedly switching between its conducting state and nonconducting state, so that power is sent to output port from input port.Control subsystem can be suitable at least in part based on representing that the signal of the electric current flowing out output port controls the switching of gauge tap device, to regulate the voltage across input port, maximizes to make the signal representing the power exported from output port.

(A2) in the MPPT maximum power point tracking controller being expressed as (A1), described control subsystem can also be suitable for being based in part on the signal that represents the electric current flowing out output port and across the difference between the voltage of input port and reference voltage to control the switching of described gauge tap device.

(A3) in the MPPT maximum power point tracking controller being expressed as (A2), described control subsystem can also be suitable for the value changing reference voltage, maximizes to make the signal representing the power exported from output port.

(A4) in the arbitrary MPPT maximum power point tracking controller being expressed as (A2) or (A3), described control subsystem can also be suitable for being based in part on error signal that You – Kv* (Vin-Vref)+Ki*Io provides to control the switching of gauge tap device, wherein, Kv is the first zoom factor, Ki is factor Ⅱ, Vin is the voltage across input port, and Vref is reference voltage, and Io is the signal representing the electric current flowing out output port.

(A5) in any MPPT maximum power point tracking controller being expressed as (A2) to (A4), described control subsystem can also comprise multiplier, described multiplier be suitable for according to represent across the average voltage of output port scale signal with represent that the product flowing out the scale signal of the average current of output port determines to represent the signal of the power exported from output port.

(A6) in the MPPT maximum power point tracking controller being expressed as (A5), described control subsystem can also comprise: (a) voltage scaling subsystem, and described voltage scaling subsystem is suitable for by zooming in the first preset range across the signal of the average voltage of output port the scale signal generating and represent across the average voltage of output port by representing; And (b) electric current convergent-divergent subsystem, described electric current convergent-divergent subsystem is suitable for by representing that the signal of the average current flowing out output port zooms in the second preset range the scale signal generating and represent the average current flowing out output port.

(A7) in the MPPT maximum power point tracking controller being expressed as (A6), described electric current convergent-divergent subsystem can also be suitable for preventing the value of the scale signal representing the average current flowing out output port from dropping to below minimum threshold.

(A8) in the MPPT maximum power point tracking controller being expressed as (A7), described electric current convergent-divergent subsystem can also be suitable for, when representing that the signal of the average current flowing out output port is in a numerical range, positive offset amount being increased to the scale signal representing the average current flowing out output port.

(A9) in any MPPT maximum power point tracking controller being expressed as (A6) to (A8), described control subsystem can also comprise current filter subsystem, and described current filter subsystem is suitable for the signal by carrying out filtering to generate representing the average current flowing out output port to the signal of the electric current representing outflow output port.

(A10) in any MPPT maximum power point tracking controller being expressed as (A6) to (A10), described control subsystem can also comprise voltage filter subsystem, and described voltage filter subsystem is suitable for by carrying out filtering to generate across the signal of the voltage of output port the signal that represents across the average voltage of output port to representing.

(A11) in any MPPT maximum power point tracking controller being expressed as (A2) to (A10), described control subsystem can also be suitable for when the voltage drop across input port is below Second Threshold, suppresses the reduction of the value of reference voltage.

(A12) in any MPPT maximum power point tracking controller being expressed as (A2) to (A10), described control subsystem can also be suitable for, when suppressing the reduction of value of reference voltage can cause voltage drop across input port below the 3rd threshold value, suppressing the reduction of the value of reference voltage.

(A13) in any MPPT maximum power point tracking controller being expressed as (A2) to (A12), described control subsystem can also be suitable for when the voltage rise across input port is more than the 4th threshold value, suppresses the increase of the value of reference voltage.

(A14) in any MPPT maximum power point tracking controller being expressed as (A2) to (A13), described control subsystem can also be suitable for: (a) is when the order of the dutycycle in order to control gauge tap device is lower than the 5th threshold value, value with reference to voltage changes the first step-length, maximizes to make the signal representing the power exported from output port; And (b) is when the order of the dutycycle in order to control gauge tap device is more than or equal to the 6th threshold value, the value with reference to voltage changes the second step-length, maximizes to make the signal representing the power exported from output port; Wherein, the second step-length is less than the first step-length.

(A15) in the MPPT maximum power point tracking controller being expressed as (A14), the 5th threshold value can be identical with the 6th threshold value.

(A16) in any MPPT maximum power point tracking controller being expressed as (A2) to (A15), described control subsystem can also be suitable for: (a) is when the difference the signal representing the power exported from output port between the consecutive variations of the value of reference voltage is lower than the 7th threshold value, value with reference to voltage changes the 3rd step-length, maximizes to make the signal representing the power exported from output port; And (b) is when the difference the signal representing the power exported from output port between the consecutive variations of the value of reference voltage is more than or equal to the 8th threshold value, value with reference to voltage changes the 4th step-length, maximizes to make the signal representing the power exported from output port; Wherein, the 4th step-length is greater than the 3rd step-length.

(A17) in the MPPT maximum power point tracking controller being expressed as (A16), the 7th threshold value can be identical with the 8th threshold value.

(A18) in any MPPT maximum power point tracking controller being expressed as (A2) to (A17), described control subsystem can also be suitable for: (a) is when the order of the dutycycle in order to control gauge tap device is in the first numerical range, change the value of reference voltage with first rate, maximize to make the signal representing the power exported from output port; And (b) is when the order of the dutycycle in order to control gauge tap device is within the scope of second value, change the value of reference voltage with the second speed, maximize to make the signal representing the power exported from output port; Wherein, the second speed is greater than first rate.

(A19) in the MPPT maximum power point tracking controller being expressed as (A18), first numerical range can represent the dutycycle of gauge tap device zero and absolutely between order, and described second value scope can represent that the dutycycle of gauge tap device is less than zero or be greater than and absolutely order.

(A20) in any MPPT maximum power point tracking controller being expressed as (A2) to (A19), described control subsystem can also be suitable for the value increasing reference voltage in response to the value of the voltage across input port drops to below the 9th threshold value.

(A21) in any MPPT maximum power point tracking controller being expressed as (A2) to (A21), described control subsystem can also be suitable for when starting switch circuit, sets the initial magnitude of reference voltage at least in part based on the initial value of the voltage across input port.

(A22) in the MPPT maximum power point tracking controller being expressed as (A21), described control subsystem can also be suitable for when starting switch circuit, and the initial magnitude with reference to voltage is set as the mark of the voltage across input port.

(A23) in any MPPT maximum power point tracking controller being expressed as (A2) to (A22), described control subsystem can also be suitable in response to the value of the electric current of the signal designation outflow output port representing the electric current flowing out output port has dropped to below the tenth threshold level and reduce the value of reference voltage.

(A24) in the MPPT maximum power point tracking controller being expressed as (A23), described control subsystem can also be suitable in response to the value of the electric current of the signal designation outflow output port representing the electric current flowing out output port has dropped to below the 11 threshold level with fixed duty cycle operation-control switch device, wherein, the 11 threshold level is lower than the tenth threshold level.

(A25) in any MPPT maximum power point tracking controller being expressed as (A2) to (A24), described gauge tap device can electric coupling between the first terminal and the first terminal of output port of input port, and described MPPT maximum power point tracking controller can also comprise afterflow device, the electric coupling of described afterflow device is between the first terminal and the second terminal of output port of output port, wherein, described afterflow device is suitable for being the current supplying path flowed between the first terminal and the second terminal of output port when gauge tap device is in its nonconducting state.

(A26) in any MPPT maximum power point tracking controller being expressed as (A2) to (A25), gauge tap device and control subsystem can be the parts of common integrated circuit.

(A27) in any MPPT maximum power point tracking controller being expressed as (A2) to (A26): (a) described gauge tap device can comprise the field effect transistor of dynamic conditioning size; B () described MPPT maximum power point tracking controller can also comprise electric current reconstructing device subsystem, described electric current reconstructing device subsystem is suitable for generating the signal representing the electric current flowing out output port, wherein, electric current reconstructing device subsystem has the gain of the size of the field effect transistor depending on described dynamic conditioning size at least in part; And (c) described control subsystem can be suitable for the size reducing the field effect transistor of dynamic conditioning size when the value of the signal representing the electric current flowing out output port drops to below the 12 threshold value, thus increase the gain of electric current reconstructing device subsystem.

(B1) power-supply system, can comprise power supply and MPPT maximum power point tracking controller.Described MPPT maximum power point tracking controller can comprise: input port, and described input port is used for being electrically coupled to described power supply; Output port, described output port is used for being electrically coupled to load; Gauge tap device; And control subsystem.Gauge tap device can be suitable for repeatedly switching between its conducting state and nonconducting state, so that power is sent to output port from input port.Control subsystem can be suitable at least in part based on representing that the signal of the electric current flowing out output port controls the switching of gauge tap device, to regulate the voltage across input port, maximizes to make the signal representing the power exported from output port.

(B2) in the power-supply system being expressed as (B1), described power supply can comprise photovoltaic device.

(B3) in the power-supply system being expressed as (B2), described photovoltaic device can comprise the photovoltaic cell of multiple interconnection.

(B4) in the arbitrary power-supply system being expressed as (B2) or (B3), described photovoltaic device can comprise multi-junction photovoltaic battery.

(B5) in any power-supply system being expressed as (B1) to (B4), described control subsystem can be suitable for being based in part on the signal that represents the electric current flowing out output port and across the difference between the voltage of input port and reference voltage to control the switching of gauge tap device.

(B6) in the power-supply system being expressed as (B5), described control subsystem can also be suitable for the value changing reference voltage, maximizes to make the signal representing the power exported from output port.

(B7) in the arbitrary power-supply system being expressed as (B5) or (B6), described control subsystem can also be suitable for being based in part on error signal that You – Kv* (Vin-Vref)+Ki*Io provides to control the switching of gauge tap device, wherein, Kv is the first zoom factor, Ki is the second zoom factor, Vin is the voltage across input port, and Vref is reference voltage, and Io is the signal representing the electric current flowing out output port.

(B8) in any power-supply system being expressed as (B1) to (B7), described gauge tap device can electric coupling between the first terminal and the first terminal of output port of input port, and MPPT maximum power point tracking controller can also comprise afterflow device, the electric coupling of described afterflow device is between the first terminal and the second terminal of output port of output port, wherein, described afterflow device is suitable for when gauge tap device is in its nonconducting state is the current supplying path flowed between the first terminal of output port and the second terminal.

(B9) in any power-supply system being expressed as (B1) to (B8), described control subsystem can comprise multiplier, described multiplier be suitable for according to represent across the average voltage of output port scale signal with represent that the product flowing out the scale signal of the average current of output port determines to represent the signal of the power exported from output port.

(B10) in the power-supply system being expressed as (B9), described control subsystem can also be suitable for preventing the value of the scale signal representing the average current flowing out output port from dropping to below minimum threshold.

(B11) in any power-supply system being expressed as (B1) to (B10), gauge tap device and control subsystem can be the parts of common integrated circuit.

(B12) in the power-supply system being expressed as (B11), common integrated circuit and photovoltaic device can be common encapsulation.

(B13) any power-supply system being expressed as (B1) to (B12) can also comprise the one or more extra MPPT maximum power point tracking controller with described output port and load in series electric coupling, wherein, each extra MPPT maximum power point tracking controller is suitable for power to be sent to load from power supply extra separately.

(C1) for a method for operational maximum power point tracking control unit, described MPPT maximum power point tracking controller comprises: input port, and described input port is used for being electrically coupled to power supply; And output port, described output port is used for being electrically coupled to load, described method can comprise the following steps: (a) repeatedly switches described gauge tap device, so that power is sent to output port from input port between the conducting state and nonconducting state of the gauge tap device of described MPPT maximum power point tracking controller; And (b) is at least in part based on representing that the signal of the electric current flowing out output port controls the switching of gauge tap device, to regulate the value of the voltage across input port, maximize to make the signal representing the power exported from output port.

(C2) be expressed as the method for (C1), the signal that is based in part on and represents the electric current flowing out output port can also be comprised and across the difference between the value of the voltage of input port and reference voltage to control the switching of gauge tap device.

(C3) be expressed as the method for (C2), the value changing reference voltage can also be comprised, maximize to make the signal representing the power exported from output port.

(C4) either method of (C2) or (C3) is expressed as, can also comprise and be based in part on error signal that You – Kv* (Vin-Vref)+Ki*Io provides to control the switching of gauge tap device, wherein, Kv is the first zoom factor, Ki is the second zoom factor, Vin is the voltage across input port, and Vref is reference voltage, and Io is the signal representing the electric current flowing out output port.

(C5) be expressed as (C2) to any means of (C4), can also comprise by use multiplier by represent across the average voltage of output port signal with represent that the signal multiplication flowing out the average current of output port determines to represent the signal of the power exported from output port.

(C6) being expressed as the method for (C5), can also comprising representing that the signal of the electric current flowing out output port carries out filtering, to generate the signal representing the average current flowing out output port.

(C7) be expressed as any means of (C5) or (C6), the signal that can also comprise representing across the voltage of output port carries out filtering, to generate the signal of the average voltage represented across output power port.

(C8) be expressed as any means of (C5) to (C7), can also comprise and prevent the value of the signal representing the average current flowing out output port from dropping to below minimum threshold.

(C9) any means of (C2) to (C8) is expressed as, can also comprise: (a), when the dutycycle of gauge tap device is a hundred per cent dutycycle, stores the first sample of the signal representing the power exported from output port; B () reduces the first amount with reference to the value of voltage; C (), after the value with reference to voltage reduces the step of the first amount, stores the second sample of the signal representing the power exported from output port; Compared with second sample of the signal of d power that the first sample of the signal of the power represented from output port output exports from output port with expression by (); E (), when the first sample of the signal representing the power exported from output port is greater than the second sample of the signal representing the power exported from output port, increases the value of reference voltage; And (f) is when the second sample of the signal representing the power exported from output port is greater than the first sample of the signal representing the power exported from output port, reduces the value of reference voltage.

(C10) be expressed as any means of (C2) to (C9), can also comprise when the voltage drop across input port is below Second Threshold, suppress the reduction of the value of reference voltage.

(C11) be expressed as any means of (C2) to (C10), can also comprise when the voltage rise across input port is more than the 3rd threshold value, suppress the increase of the value of reference voltage.

(C12) any means of (C2) to (C11) is expressed as, can also comprise: (a) is when the order of the dutycycle in order to control gauge tap device is lower than the 4th threshold value, value with reference to voltage changes the first step-length, maximizes to make the signal representing the power exported from output port; And (b) is when the order of the dutycycle in order to control gauge tap device is more than or equal to the 5th threshold value, the value with reference to voltage changes the second step-length, maximizes to make the signal representing the power exported from output port; Wherein, the second step-length is less than the first step-length.

(C13) any means of (C2) to (C11) is expressed as, can also comprise: (a) is when the order of the dutycycle in order to control gauge tap device is in the first numerical range, change the value of reference voltage with first rate, maximize to make the signal representing the power exported from output port; And (b) is when the order of the dutycycle in order to control gauge tap device is within the scope of second value, change the value of reference voltage with the second speed, maximize to make the signal representing the power exported from output port; Wherein, the second speed is greater than first rate.

(C14) in the method being expressed as (C13), first numerical range can represent by the Duty ratio control of gauge tap device zero and absolutely between, and second value scope can represent the Duty ratio control of gauge tap device for being less than zero or be greater than absolutely.

(C15) be expressed as (C2) to any means of (C14), the value that can also comprise in response to the voltage across input port drops to below the 6th threshold value and increases the value of reference voltage.

(C16) be expressed as (C2) to any means of (C15), when can also be included in starting switch circuit, set the initial magnitude of reference voltage at least in part based on the initial value of the voltage across input port.

(C17) be expressed as the method for (C6), when can also be included in starting switch circuit, the initial magnitude with reference to voltage is set as the mark of the voltage across input port.

(C18) be expressed as (C2) to any means of (C17), the value that can also comprise in response to the electric current flowing out output port has dropped to below the 7th threshold level and has reduced the value of reference voltage.

(C19) method of (C18) is expressed as, can also comprise in response to the value of electric current flowing out output port drops to below the 8th threshold level with fixed duty cycle operation-control switch device, wherein, the 8th threshold level is lower than the 7th threshold level.

(C20) be expressed as any means of (C1) to (C19), can also comprise: (a) uses electric current reconstructing device subsystem to generate the signal representing the electric current flowing out output port; And (b) is when the value of the signal representing the electric current flowing out output port drops to below the 9th threshold value, reduces the size of the field effect transistor of the dynamic conditioning size of gauge tap device, thus increase the gain of electric current reconstructing device subsystem.

(D1) electronic filter, can comprise: (a) integrator subsystem, and described integrator subsystem is suitable for operating in bipolarity territory, with the AC compounent in filtering input signal; And (b) transconductance circuit, described transconductance circuit is suitable for operating in unipolarity territory, to generate the output current signal proportional with the mean value of input current signal.

(D2) in the electronic filter being expressed as (D1): integrator subsystem can be suitable for the integrator signal generating the mean value representing input current signal; And (b) transconductance circuit can comprise the first trsanscondutance amplifier, described first trsanscondutance amplifier is suitable for generating output current signal according to integrator signal.

(D3) in the electronic filter being expressed as (D2), described transconductance circuit can also comprise the second trsanscondutance amplifier, and described second trsanscondutance amplifier is suitable for the DC component generating input current signal according to integrator signal.

(D4) in any electronic filter being expressed as (D1) to (D3), integrator subsystem can comprise: (a) integrator, described integrator has reversed input terminal and non-inverting input terminal, and (b) resistance device, described resistance device is across the input terminal electric coupling of integrator; Wherein, the non-inverting input terminal of integrator is electrically coupled to the reference mode of electronic filter via voltage source, the reversed input terminal of integrator is electrically coupled to first node, and electronic filter is arranged so that input current signal flows out first node.

(E1) a kind of signal panntographic system, (a) mutual conductance subsystem can be comprised, described mutual conductance subsystem is suitable for input voltage signal to be converted to output current signal, and described mutual conductance subsystem comprises the programmable resistance being suitable for the gain setting described mutual conductance subsystem; And (b) steering logic, described steering logic is suitable for the resistance setting described programmable resistance, to adjust the gain of described mutual conductance subsystem, makes the value of output current signal at least equally large with first threshold.

(E2) in the signal panntographic system being expressed as (E1), described mutual conductance subsystem can also comprise: (a) transistor, and described transistor is electrically coupled to programmable resistance; And (b) amplifier, described amplifier is suitable for controlling transistor in response to input voltage signal to regulate the voltage across programmable resistance.

(E3) in the arbitrary signal panntographic system being expressed as (E1) or (E2), described steering logic can also be suitable in response to the first external signal and the gain of mutual conductance subsystem is set as minimum value.

(E4) in the arbitrary signal panntographic system being expressed as (E1) to (E3), described steering logic can also be suitable for the gain increasing progressively mutual conductance subsystem in response to the second external signal, until the value of output current signal is at least equally large with first threshold.

(E5) in the arbitrary signal panntographic system being expressed as (E1) to (E4), when the value that described steering logic can also be suitable for detecting output current signal exceedes Second Threshold, and wherein, Second Threshold is greater than first threshold.

(E6) in the signal panntographic system being expressed as (E5), described steering logic can also be suitable for generating the signal indicating the value of output current signal to exceed Second Threshold.

(E7) in the arbitrary signal panntographic system being expressed as (E1) to (E6), described mutual conductance system can also comprise current mirror, and described current mirror is suitable in response to the electric current flowing through programmable resistance and generates output current signal.

(F1) a kind of signal level shift unit for the Complementary input structure voltage signal in the first power domain being displaced to the complementary output voltage signal in second source territory, can comprise: (a) transconductance stage, described transconductance stage is in the first power domain, and described transconductance stage is suitable in response to Complementary input structure voltage signal and generates complementary current signal; And (b) load circuit, described load circuit is in second source territory, described load circuit is suitable in response to complementary current signal and generates complementary output voltage signal, wherein, described load circuit comprises the first inverter circuit and the second inverter circuit that are suitable for generating complementary output voltage signal in response to complementary current signal.

(F2) in the signal level shift unit being expressed as (F1): the high siding track of the first inverter circuit can be electrically coupled to the high siding track in second source territory by the first transistor; The high siding track of the second inverter circuit can be electrically coupled to the high siding track in second source territory by transistor seconds; And the first transistor and transistor seconds can cross-couplings.

(F3) in the signal level shift unit being expressed as (F2), each inverter circuit in inverter circuit can comprise: (a) high-side transistor, and described high-side transistor electric coupling is between the high siding track and the output node of inverter circuit of inverter circuit; And (b) low side transistors, described low side transistors electric coupling is between the output node and the reference rail in second source territory of inverter circuit; Wherein, described high-side transistor can be used to: when described low side transistors is in its conducting state, the high siding track output node of inverter circuit being pulled upward to phase inverter relative to the reference rail in second source territory current potential five ten at least percent.

(F4) in the arbitrary signal level shift unit being expressed as (F2) or (F3), described transconductance stage can be used to: when current potential lower than the reference rail of the first power domain of the current potential of the reference rail in second source territory, be driven into by electric current in the high siding track of the first inverter circuit and the second inverter circuit.

(G1) one is used for the system of the signal determining the power represented in MPPT maximum power point tracking (MPPT) controller, can comprise: (a) voltage filter subsystem, described voltage filter subsystem is suitable for the signal by carrying out filtering to generate the average voltage representing described output port to the signal represented across the voltage of the output port of MPPT controller; (b) current filter subsystem, described current filter subsystem is suitable for the signal by carrying out filtering to generate representing the average current flowing out output port to the signal of the electric current representing outflow output port; (c) voltage scaling subsystem, described voltage scaling subsystem is suitable for by zooming in the first preset range across the signal of the average voltage of output port the scale signal generating and represent across the average voltage of output port by representing; (d) electric current convergent-divergent subsystem, described electric current convergent-divergent subsystem is suitable for by representing that the signal of the average current flowing out output port zooms in the second preset range the scale signal generating and represent the average current flowing out output port; And (e) multiplier, described multiplier be suitable for according to represent across the average voltage of output port scale signal with represent that the product flowing out the scale signal of the average current of output port determines to represent the signal of power.

(G2) in the system being expressed as (G1), described multiplier can comprise: (a) first input end mouth, and described first input end mouth is suitable for receiving the scale signal represented across the average voltage of output port; (b) second input port, described second input port is suitable for receiving the scale signal representing the average current flowing out output port; (c) output port, described output port is suitable for providing the signal representing power; (d) first field effect transistor, described first field effect transistor and described first input end mouth coupled in series electrical; (e) second field effect transistor, described second field effect transistor and described second input port coupled in series electrical; (f) the 3rd field effect transistor, described 3rd field effect transistor and described output port coupled in series electrical; And (g) control circuit, described control circuit is suitable for controlling each field effect transistor in described first field effect transistor, described second field effect transistor and described 3rd field effect transistor, and making the value of the electric current flowed in described output port and (1) flow into the value of the electric current in described first input end mouth and (2), to flow into the product of the value of the electric current in described second input port proportional.

(G3) in the system being expressed as (G2), the grid of the first field effect transistor can be electrically coupled to the grid of the 3rd field effect transistor.

(G4) system of (G3) is expressed as, can also comprise: (a) forms the 4th field effect transistor and the 5th field effect transistor of current mirror, described current mirror is configured such that the value of the drain-source current flowing through the 5th field effect transistor equals Iref, and the value of the drain-source current flowing through the 4th field effect transistor equals Iref/m; And (b) first amplifier, described first amplifier is suitable for the grid of control first field effect transistor, makes the voltage that the voltage across the first field effect transistor equals across the 4th field effect transistor.

(G5) in the system being expressed as (G4), the grid of the second field effect transistor can be electrically coupled to the grid of the 4th field effect transistor and the grid of the 5th field effect transistor.

(G2) in the arbitrary system being expressed as (G4) or (G5), when transistor seconds, the 4th transistor and the 5th transistor are driven by common gate source voltage, second field effect transistor can have the channel resistance equaling R/m, and the 4th field effect transistor and the 5th field effect transistor can have the channel resistance equaling R separately.

(G7) any system of (G2) to (G6) is expressed as, the second amplifier and the 6th transistor can also be comprised, described second amplifier and described 6th transistor are configured to the value of electric current controlling to flow into output port, make the voltage that the voltage across the second field effect transistor equals across the 3rd field effect transistor.

(G8) in any system being expressed as (G1) to (G7), described electric current convergent-divergent subsystem can comprise: (a) mutual conductance subsystem, described mutual conductance subsystem is suitable for representing that the signal of the average current flowing out output port is converted to the scale signal representing the average current flowing out output port, described mutual conductance subsystem comprises programmable resistance, and described programmable resistance is suitable for setting the described gain across resistance subsystem; And (b) steering logic, described steering logic is suitable for the resistance setting described programmable resistance, to adjust the gain of described mutual conductance subsystem, make the value of the scale signal representing the average current flowing out output port at least equally large with first threshold.

(G9) in the system being expressed as (G8), described mutual conductance subsystem can also comprise: (a) transistor, and described transistor is electrically coupled to described programmable resistance; And (b) amplifier, described amplifier is suitable in response to the signal representing the average current flowing out output port and controls transistor to regulate the voltage across programmable resistance.

(G10) in the arbitrary system being expressed as (G8) or (G9), described steering logic can also be suitable in response to the first external signal and the gain of mutual conductance subsystem is set as minimum value.

(G11) in any system being expressed as (G8) to (G10), described steering logic can also be suitable for the gain increasing progressively mutual conductance subsystem in response to the second external signal, until represent that the value of the scale signal of the electric current flowing out output port is at least equally large with first threshold.

(G12) in any system being expressed as (G8) to (G11), described mutual conductance subsystem can also comprise current mirror, and described current mirror is suitable in response to the electric current flowing through programmable resistance and generates the scale signal representing the average current flowing out output port.

(G13) in any system being expressed as (G1) to (G12), described current filter subsystem can comprise: (a) integrator subsystem, described integrator subsystem is suitable for operating in bipolarity territory, represents the AC compounent in the signal of the electric current flowing out output port with filtering; And (b) transconductance circuit, described transconductance circuit is suitable for operating in unipolarity territory, to generate the signal representing the average current flowing out output port according to the mean value of the signal representing the electric current flowing out output port.

(G14) in the system being expressed as (G13): described integrator subsystem can be suitable for the integrator signal of the mean value generating the signal representing the electric current flowing out output port; And described transconductance circuit can comprise the first trsanscondutance amplifier, described first trsanscondutance amplifier is suitable for generating according to integrator signal the signal representing the average current flowing out output port.

(G15) in the system being expressed as (G14), described transconductance circuit can also comprise the second trsanscondutance amplifier, and described second trsanscondutance amplifier is suitable for the DC component generating the signal representing the electric current flowing out output port according to integrator signal.

(G16) in any system being expressed as (G13) to (G15), described integrator subsystem can comprise: (a) integrator, described integrator has reversed input terminal and non-inverting input terminal, and (b) resistance device, described resistance device is across the input terminal electric coupling of integrator; The non-inverting input terminal of described integrator is electrically coupled to reference mode via voltage source, the reversed input terminal of described integrator is electrically coupled to first node, and described current filter subsystem is arranged so that the signal representing the electric current flowing out output port flows out first node.

(H1) a kind of multiplier can comprise: (a) first input end mouth and the second input port; (b) output port; (c) first field effect transistor, described first field effect transistor and first input end mouth coupled in series electrical; (d) second field effect transistor, described second field effect transistor and the second input port coupled in series electrical; (e) the 3rd field effect transistor, described 3rd field effect transistor and output port coupled in series electrical; And (f) control circuit, described control circuit is suitable for each field effect transistor in control first field effect transistor, the second field effect transistor and the 3rd field effect transistor, and the product that the value making value and (1) of the electric current flowing into output port flow into the electric current of first input end mouth and (2) flow into the value of the electric current of the second input port is proportional.

(H2) in the multiplier being expressed as (H1), the grid of the first field effect transistor can be electrically coupled to the grid of the 3rd field effect transistor.

(H3) arbitrary multiplier of (H1) or (H2) is expressed as, can also comprise: (a) forms the 4th field effect transistor and the 5th field effect transistor of current mirror, described current mirror is configured such that the value of the drain-source current flowing through the 5th field effect transistor equals Iref, and the value of the drain-source current flowing through the 4th field effect transistor equals Iref/m; And (b) first amplifier, described first amplifier is suitable for the grid of control first field effect transistor, makes the voltage that the voltage across the first field effect transistor equals across the 4th field effect transistor.

(H4) in the multiplier being expressed as (H3), the grid of the second field effect transistor can be electrically coupled to the grid of the 4th field effect transistor and the grid of the 5th field effect transistor.

(H5) in the arbitrary multiplier being expressed as (H3) or (H4), when transistor seconds, the 4th transistor and the 5th transistor are driven by common gate source voltage, described second field effect transistor can have the channel resistance equaling R/m, and the 4th field effect transistor and the 5th field effect transistor can have the channel resistance equaling R separately.

(H6) any multiplier of (H1) to (H5) is expressed as, the second amplifier and the 6th transistor can also be comprised, described second amplifier and described 6th transistor are configured to the value controlling the electric current flowed in output port, make the voltage that the voltage across described second field effect transistor equals across the 3rd field effect transistor.

When not departing from its scope, can above method and system be made a change.Such as, when making suitably change to interlock circuit, P-channel field-effect transistor (PEFT) transistor can be utilized to replace N slot field-effect transistor, or vice versa.Again such as, when making suitably change to interlock circuit, bipolar junction transistor can be utilized to replace field effect transistor.Thus, it should be pointed out that comprise in the above description should be interpreted as illustrative and nonrestrictive meaning with the content that shows in accompanying drawing.Following claims are intended to cover general and special characteristic as herein described, and whole statements of the scope of the method and system presented, and due to the relation of language, whole statements of the scope of the method and system presented can be called and fall into wherein.

Claims (103)

1. a MPPT maximum power point tracking controller, comprising:

Input port, described input port is used for being electrically coupled to power supply;

Output port, described output port is used for being electrically coupled to load;

Gauge tap device, described gauge tap device is suitable for repeatedly switching between its conducting state and nonconducting state, so that power is sent to described output port from described input port; And

Control subsystem, described control subsystem is suitable at least in part based on representing that the signal of the electric current flowing out described output port controls the switching of described gauge tap device, to regulate the voltage across described input port, maximize to make the signal representing the power exported from described output port.

2. MPPT maximum power point tracking controller according to claim 1, described control subsystem is also suitable at least in part based on representing the described signal of the electric current flowing out described output port and controlling the switching of described gauge tap device across the difference between the described voltage of described input port and reference voltage.

3. MPPT maximum power point tracking controller according to claim 2, described control subsystem is also suitable for the value changing described reference voltage, to make to represent that the described signal of the power exported from described output port maximizes.

4. MPPT maximum power point tracking controller according to claim 3, described control subsystem is also suitable for being based in part on error signal that You – Kv* (Vin-Vref)+Ki*Io provides to control the switching of described gauge tap device, wherein, Kv is the first zoom factor, Ki is factor Ⅱ, Vin is the described voltage across described input port, and Vref is described reference voltage, and Io is the described signal representing the electric current flowing out described output port.

5. MPPT maximum power point tracking controller according to claim 4, the electric coupling of described gauge tap device is between the first terminal and the first terminal of described output port of described input port, described MPPT maximum power point tracking controller also comprises afterflow device, the electric coupling of described afterflow device is between the described the first terminal and the second terminal of described output port of described output port, described afterflow device is suitable for being the current supplying path flowed between the described the first terminal and described second terminal of described output port when described gauge tap device is in its nonconducting state.

6. MPPT maximum power point tracking controller according to claim 5, described control subsystem comprises multiplier, described multiplier be suitable for according to represent across the average voltage of described output port scale signal with represent that the product flowing out the scale signal of the average current of described output port determines to represent the described signal of the power exported from described output port.

7. MPPT maximum power point tracking controller according to claim 6, described control subsystem also comprises:

Voltage scaling subsystem, described voltage scaling subsystem is suitable for by zooming in the first preset range across the signal of the average voltage of described output port the described scale signal generating and represent across the average voltage of described output port by representing; And

Electric current convergent-divergent subsystem, described electric current convergent-divergent subsystem is suitable for by representing that the signal of the average current flowing out described output port zooms in the second preset range the described scale signal generating and represent the average current flowing out described output port.

8. MPPT maximum power point tracking controller according to claim 7, described electric current convergent-divergent subsystem is also suitable for preventing the value of the described scale signal representing the average current flowing out described output port from dropping to below minimum threshold.

9. MPPT maximum power point tracking controller according to claim 8, described electric current convergent-divergent subsystem is also suitable for, when representing that the described signal of the average current flowing out described output port is in the first numerical range, positive offset amount being increased to the described scale signal representing the average current flowing out described output port.

10. MPPT maximum power point tracking controller according to claim 7, described control subsystem also comprises current filter subsystem, and described current filter subsystem is suitable for the described signal by carrying out filtering to generate representing the average current flowing out described output port to the described signal of the electric current representing the described output port of outflow.

11. MPPT maximum power point tracking controllers according to claim 10, described control subsystem also comprises voltage filter subsystem, and described voltage filter subsystem is suitable for by carrying out filtering to generate across the signal of the voltage of described output port the described signal that represents across the average voltage of described output port to representing.

12. MPPT maximum power point tracking controllers according to claim 3, described control subsystem is also suitable for, when the described voltage drop across described input port is below threshold value, suppressing the reduction of the described value of described reference voltage.

13. MPPT maximum power point tracking controllers according to claim 3, described control subsystem is also suitable for, when suppressing the reduction of described value of described reference voltage can cause described voltage drop across described input port below threshold value, suppressing the reduction of the described value of described reference voltage.

14. MPPT maximum power point tracking controllers according to claim 3, described control subsystem is also suitable for, when the described voltage rise across described input port is more than threshold value, suppressing the increase of the described value of described reference voltage.

15. MPPT maximum power point tracking controllers according to claim 3, described control subsystem is also suitable for:

When the order of the dutycycle in order to control described gauge tap device is lower than first threshold, the described value of described reference voltage is changed the first step-length, to make to represent that the described signal of the power exported from described output port maximizes; And

When the order of the dutycycle in order to control described gauge tap device is more than or equal to Second Threshold, the described value of described reference voltage is changed the second step-length, to make to represent that the described signal of the power exported from described output port maximizes;

Described second step-length is less than described first step-length.

16. MPPT maximum power point tracking controllers according to claim 15, described first threshold is identical with described Second Threshold.

17. MPPT maximum power point tracking controllers according to claim 3, described control subsystem is also suitable for:

When difference between the consecutive variations of the value at described reference voltage of the described signal of the power that expression exports from described output port is lower than first threshold, the described value of described reference voltage is changed the first step-length, to make to represent that the described signal of the power exported from described output port maximizes; And

When difference between the consecutive variations of the value at described reference voltage of the described signal of the power that expression exports from described output port is more than or equal to Second Threshold, the described value of described reference voltage is changed the second step-length, to make to represent that the described signal of the power exported from described output port maximizes;

Described second step is grown up in described first step-length.

18. MPPT maximum power point tracking controllers according to claim 17, described first threshold is identical with described Second Threshold.

19. MPPT maximum power point tracking controllers according to claim 3, described control subsystem is also suitable for:

When the order of the dutycycle in order to control described gauge tap device is in the first numerical range, change the described value of described reference voltage with first rate, to make to represent that the described signal of the power exported from described output port maximizes; And

When the order of the described dutycycle in order to control described gauge tap device is within the scope of second value, change the described value of described reference voltage with the second speed, to make to represent that the described signal of the power exported from described output port maximizes;

Described second speed is greater than described first rate.

20. MPPT maximum power point tracking controllers according to claim 19, described first numerical range represent the described dutycycle of described gauge tap device zero and absolutely between order, and the described dutycycle of gauge tap device described in described second value Range Representation is less than zero or be greater than and absolutely order.

21. MPPT maximum power point tracking controllers according to claim 3, described control subsystem is also suitable for: the described value in response to the described voltage across described input port drops to below threshold value and increases the described value of described reference voltage.

22. MPPT maximum power point tracking controllers according to claim 3, described control subsystem is also suitable for: when starting described on-off circuit, sets the initial magnitude of described reference voltage at least in part based on the initial value of the described voltage across described input port.

23. MPPT maximum power point tracking controllers according to claim 22, described control subsystem is also suitable for: when starting described on-off circuit, the described initial magnitude of described reference voltage is set as the mark across the described voltage being described input port.

24. MPPT maximum power point tracking controllers according to claim 3, described control subsystem is also suitable for: the value that the described signal designation in response to the electric current representing the described output port of outflow flows out the electric current of described output port has dropped to below first threshold level and reduced the described value of described reference voltage.

25. MPPT maximum power point tracking controllers according to claim 24, described control subsystem is also suitable for: the value that the described signal designation in response to the electric current representing the described output port of outflow flows out the electric current of described output port has dropped to below Second Threshold level and operated described gauge tap device with fixed duty cycle, wherein, described Second Threshold level is lower than described first threshold level.

26. MPPT maximum power point tracking controller according to claim 1, described gauge tap device and described control subsystem are the parts of common integrated circuit.

27. MPPT maximum power point tracking controllers according to claim 1, wherein:

Described gauge tap device comprises the field effect transistor of dynamic conditioning size;

Described MPPT maximum power point tracking controller also comprises electric current reconstructing device subsystem, described electric current reconstructing device subsystem is suitable for generating the described signal representing the electric current flowing out described output port, and described electric current reconstructing device subsystem has the gain of the size of the field effect transistor depending on described dynamic conditioning size at least in part; And

Described control subsystem is suitable for the size reducing the field effect transistor of described dynamic conditioning size when the value of the described signal representing the electric current flowing out described output port drops to below threshold value, thus increases the described gain of described electric current reconstructing device subsystem.

28. 1 kinds of power-supply systems, comprising:

Power supply; And

MPPT maximum power point tracking controller, comprising:

Input port, described input port is electrically coupled to described power supply,

Output port, described output port is used for being electrically coupled to load,

Gauge tap device, described gauge tap device is suitable for repeatedly switching between its conducting state and nonconducting state, so that power is sent to described output port from described power supply, and

Control subsystem, described control subsystem is suitable at least in part based on representing that the signal of the electric current flowing out described output port controls the switching of described gauge tap device, to regulate the voltage across described input port, maximize to make the signal representing the power exported from described output port.

29. power-supply systems according to claim 28, described power supply comprises photovoltaic device.

30. power-supply systems according to claim 29, described photovoltaic device comprises the photovoltaic cell of multiple interconnection.

31. power-supply systems according to claim 29, described photovoltaic device comprises multi-junction photovoltaic battery.

32. power-supply systems according to claim 29, described control subsystem be suitable for being based in part on the described signal that represents the electric current flowing out described output port and across the difference between the described voltage of described input port and reference voltage to control the switching of described gauge tap device.

33. power-supply systems according to claim 32, described control subsystem is also suitable for the value changing described reference voltage, to make to represent that the described signal of the power exported from described output port maximizes.

34. power-supply systems according to claim 33, described control subsystem is also suitable for being based in part on error signal that You – Kv* (Vin-Vref)+Ki*Io provides to control the switching of described gauge tap device, wherein, Kv is the first zoom factor, Ki is the second zoom factor, Vin is the described voltage across described input port, and Vref is described reference voltage, and Io is the described signal representing the electric current flowing out described output port.

35. power-supply systems according to claim 34, the electric coupling of described gauge tap device is between the first terminal and the first terminal of described output port of described input port, described MPPT maximum power point tracking controller also comprises afterflow device, the electric coupling of described afterflow device is between the described the first terminal and the second terminal of described output port of described output port, and described afterflow device is suitable for being the current supplying path flowed between the described the first terminal and described second terminal of described output port when described gauge tap device is in its nonconducting state.

36. power-supply systems according to claim 35, described control subsystem comprises multiplier, described multiplier be suitable for according to represent across the average voltage of described output port scale signal with represent that the product flowing out the scale signal of the average current of described output port determines to represent the described signal of the power exported from described output port.

37. power-supply systems according to claim 36, described control subsystem is also suitable for preventing the value of the described scale signal representing the average current flowing out described output port from dropping to below minimum threshold.

38. power-supply system according to claim 29, described gauge tap device and described control subsystem are the parts of common integrated circuit.

39. according to power-supply system according to claim 38, described common integrated circuit and described photovoltaic device are common encapsulation.

40. power-supply systems according to claim 28, also comprise the one or more extra MPPT maximum power point tracking controller with described output port and described load in series electric coupling, each extra MPPT maximum power point tracking controller is suitable for power to be sent to described load from power supply extra separately.

41. 1 kinds of methods for operational maximum power point tracking control unit, described MPPT maximum power point tracking controller comprises the input port for being electrically coupled to power supply and the output port for being electrically coupled to load, said method comprising the steps of:

Described gauge tap device is repeatedly switched, so that power is sent to described output port from described input port between the conducting state and nonconducting state of the gauge tap device of described MPPT maximum power point tracking controller; And

At least in part based on representing that the signal of the electric current flowing out described output port controls the switching of described gauge tap device, to regulate the value of the voltage across described input port, maximize to make the signal representing the power exported from described output port.

42. methods according to claim 41, also comprise the described signal that is based in part on and represents the electric current flowing out described output port and across the difference between the described value of the described voltage of described input port and reference voltage to control the switching of described gauge tap device.

43. methods according to claim 42, also comprise the value changing described reference voltage, to make to represent that the described signal of the power exported from described output port maximizes.

44. methods according to claim 43, also comprise and be based in part on error signal that You – Kv* (Vin-Vref)+Ki*Io provides to control the switching of described gauge tap device, wherein, Kv is the first zoom factor, Ki is the second zoom factor, Vin is the described voltage across described input port, and Vref is described reference voltage, and Io is the described signal representing the electric current flowing out described output port.

45. methods according to claim 44, also comprise by use multiplier by represent across the average voltage of described output port signal with represent that the signal multiplication flowing out the average current of described output port determines to represent the described signal of the power exported from described output port.

46. methods according to claim 45, also comprise representing that the described signal of the electric current flowing out described output port carries out filtering, to generate the described signal representing the average current flowing out described output port.

47. methods according to claim 46, the signal also comprised representing across the voltage of described output port carries out filtering, to generate the described signal of the average voltage represented across described output port.

48. methods according to claim 47, also comprise and prevent the value of the described signal representing the average current flowing out described output port from dropping to below minimum threshold.

49. methods according to claim 43, also comprise:

When the dutycycle of described gauge tap device be absolutely dutycycle time, store the first sample of the described signal representing the power exported from described output port;

The described value of described reference voltage is reduced the first amount;

After the described value of described reference voltage is reduced the step of described first amount, store the second sample of the described signal representing the power exported from described output port;

By represent the described signal of the power that described first sample of the described signal of the power exported from described output port exports from described output port with expression described second sample compared with;

When described first sample of the described signal representing the power exported from described output port is greater than described second sample of the described signal representing the power exported from described output port, increase the described value of described reference voltage; And

When described second sample of the described signal representing the power exported from described output port is greater than described first sample of the described signal representing the power exported from described output port, reduce the described value of described reference voltage.

50. methods according to claim 43, also comprise when the described voltage drop across described input port is below threshold value, suppress the reduction of the described value of described reference voltage.

51. methods according to claim 43, also comprise when the described voltage rise across described input port is more than threshold value, suppress the increase of the described value of described reference voltage.

52. methods according to claim 43, also comprise:

When the order of the dutycycle in order to control described gauge tap device is lower than first threshold, the described value of described reference voltage is changed the first step-length, to make to represent that the described signal of the power exported from described output port maximizes; And

When the order of the dutycycle in order to control described gauge tap device is more than or equal to Second Threshold, the described value of described reference voltage is changed the second step-length, to make to represent that the described signal of the power exported from described output port maximizes;

Described second step-length is less than described first step-length.

53. methods according to claim 43, also comprise:

When the order of the dutycycle in order to control described gauge tap device is in the first numerical range, change the described value of described reference voltage with first rate, to make to represent that the described signal of the power exported from described output port maximizes; And

When the order of the described dutycycle in order to control described gauge tap device is within the scope of second value, change the described value of described reference voltage with the second speed, to make to represent that the described signal of the power exported from described output port maximizes;

Described second speed is greater than described first rate.

54. methods according to claim 53, described first numerical range represent by the described Duty ratio control of described gauge tap device zero and absolutely between, and described second value Range Representation by the described Duty ratio control of described gauge tap device for being less than zero or be greater than absolutely.

55. methods according to claim 43, the described value also comprised in response to the described voltage across described input port drops to below threshold value and increases the described value of described reference voltage.

56. methods according to claim 43, are also included in when starting described on-off circuit, set the initial magnitude of described reference voltage at least in part based on the initial value of the described voltage across described input port.

57. methods according to claim 56, when being also included in the described on-off circuit of startup, are set as yes the mark of the described voltage across described input port by the described initial magnitude of described reference voltage.

58. methods according to claim 43, also comprise in response to the value of electric current flowing out described output port drops to below first threshold level and reduce the described value of described reference voltage.

59. methods according to claim 58, also comprise in response to the value of electric current flowing out described output port drops to below Second Threshold level and operate described gauge tap device with fixed duty cycle, wherein, described Second Threshold level is lower than described first threshold level.

60. methods according to claim 41, also comprise:

Electric current reconstructing device subsystem is used to generate the described signal representing the electric current flowing out described output port; And

When the value of the described signal representing the electric current flowing out described output port drops to below threshold value, reduce the size of the field effect transistor of the dynamic conditioning size of described gauge tap device, thus increase the gain of described electric current reconstructing device subsystem.

61. the method for using MPPT maximum power point tracking controller to transmit electric power between power supply and load, comprise the following steps: at least in part based on representing that the signal flowing through the electric current of the energy storage inductor of described MPPT maximum power point tracking controller controls the switching of the gauge tap device of described MPPT maximum power point tracking controller, to regulate the voltage across described power supply, make: (a) is more than or equal to the voltage across described load across the described voltage of described power supply, and the signal that (b) makes expression be sent to the power of described load maximizes.

62. methods according to claim 61, also comprise: be based in part on the described signal that represents the electric current flowing out described output port and across the difference between the value of the described voltage of described power supply and reference voltage to control the switching of described gauge tap device.

63. methods according to claim 62, also comprise the value changing described reference voltage, to make to represent that the described signal of the power being sent to described load maximizes.

64. 1 kinds of multipliers, comprising:

First input end mouth and the second input port;

Output port;

First field effect transistor, described first field effect transistor and described first input end mouth coupled in series electrical;

Second field effect transistor, described second field effect transistor and described second input port coupled in series electrical;

3rd field effect transistor, described 3rd field effect transistor and described output port coupled in series electrical; And

Control circuit, described control circuit is suitable for controlling each field effect transistor in described first field effect transistor, described second field effect transistor and described 3rd field effect transistor, and making the value of the electric current flowing into described output port and (a) flow into the value of the electric current of described first input end mouth and (b), to flow into the product of the value of the electric current of described second input port proportional.

65. multiplier according to claim 64, the grid of described first field effect transistor is electrically coupled to the grid of described 3rd field effect transistor.

66. multipliers according to claim 65, also comprise:

4th field effect transistor and the 5th field effect transistor, described 4th field effect transistor and described 5th field effect transistor form current mirror, and described current mirror is configured such that the value of the drain-source current flowing through described 5th field effect transistor equals Iref and the value flowing through the drain-source current of described 4th field effect transistor equals Iref/m; And

First amplifier, described first amplifier is suitable for the described grid controlling described first field effect transistor, makes the voltage that the voltage across described first field effect transistor equals across described 4th field effect transistor.

67. multipliers according to claim 66, the grid of described second field effect transistor is electrically coupled to the grid of described 4th field effect transistor and the grid of described 5th field effect transistor.

68. multipliers according to claim 67, wherein, when described transistor seconds, described 4th transistor and described 5th transistor are driven by common gate source voltage, described second field effect transistor has the channel resistance equaling R/m, and described 4th field effect transistor and described 5th field effect transistor have the channel resistance equaling R separately.

69. multipliers according to claim 68, also comprise the second amplifier and the 6th transistor, described second amplifier and described 6th transistor are configured to the described value of electric current controlling to flow into described output port, make the voltage that the voltage across described second field effect transistor equals across described 3rd field effect transistor.

70. 1 kinds of electronic filters, comprising:

Integrator subsystem, described integrator subsystem is suitable for operating in bipolarity territory, with the AC compounent in filtering input signal; And

Transconductance circuit, described transconductance circuit is suitable for operating in unipolarity territory, to generate the output current signal proportional with the mean value of input current signal.

71. electronic filters according to claim 70, wherein:

Described integrator subsystem is suitable for the integrator signal generating the mean value representing described input current signal; And

Described transconductance circuit comprises the first trsanscondutance amplifier, and described first trsanscondutance amplifier is suitable for generating described output current signal according to integrator signal.

72. electronic filters according to claim 70, described integrator subsystem comprises:

Integrator, described integrator has reversed input terminal and non-inverting input terminal; And

Resistance device, described resistance device is across the described input end electric coupling of integrator;

The described non-inverting input terminal of described integrator is electrically coupled to the reference mode of described electronic filter via voltage source,

The described reversed input terminal of described integrator is electrically coupled to first node, and

Described electronic filter is arranged so that described input current signal flows out described first node.

73. according to the electronic filter described in claim 72, and described transconductance circuit also comprises the second trsanscondutance amplifier, and described second trsanscondutance amplifier is suitable for the DC component generating described input current signal according to described integrator signal.

74. 1 kinds, for carrying out the method for filtering to input signal, comprising:

AC compounent in bipolarity territory in input signal described in filtering; And

The DC component of described input signal is generated in unipolarity territory.

75. according to the method described in claim 74, is also included in the described DC component of input signal described in mirror image in described unipolarity territory, to generate the output signal of the mean value representing described input signal.

76. 1 kinds of signal panntographic systems, comprising:

Mutual conductance subsystem, described mutual conductance subsystem is suitable for input voltage signal to be converted to output current signal, and described mutual conductance subsystem comprises programmable resistance, and described programmable resistance is suitable for the gain setting described mutual conductance subsystem; And

Steering logic, described steering logic is suitable for the resistance setting described programmable resistance, to adjust the described gain of described mutual conductance subsystem, makes the value of described output current signal at least equally large with first threshold.

77. according to the signal panntographic system described in claim 76, and described mutual conductance subsystem also comprises:

Transistor, described transistor is electrically coupled to described programmable resistance; And

Amplifier, described amplifier is suitable in response to described input voltage signal and controls described transistor, to regulate the voltage across described programmable resistance.

78. according to the signal panntographic system described in claim 77, and described steering logic is also suitable in response to the first external signal and the gain of described mutual conductance subsystem is set as minimum value.

79. according to the signal panntographic system described in claim 78, and described steering logic is also suitable for the described gain increasing progressively described mutual conductance subsystem in response to the second external signal, until the described value of described output current signal is at least equally large with described first threshold.

80. according to the signal panntographic system described in claim 79, and when the described value that described steering logic is also suitable for detecting described output current signal exceedes Second Threshold, and wherein, described Second Threshold is greater than described first threshold.

81. signal panntographic systems according to Claim 8 described in 0, the described value that described steering logic is also suitable for generating the described output current signal of instruction exceedes the signal of described Second Threshold.

82. signal panntographic systems according to Claim 8 described in 1, described mutual conductance system also comprises current mirror, and described current mirror is suitable in response to the electric current flowing through described programmable resistance and generates described output current signal.

83. 1 kinds, for the Complementary input structure voltage signal in the first power domain being displaced to the signal level shift unit of the complementary output voltage signal in second source territory, comprising:

Transconductance stage, described transconductance stage in described first power domain, and is suitable in response to described Complementary input structure voltage signal and generates complementary current signal; And

Load circuit, described load circuit is in described second source territory, it is suitable in response to described complementary current signal and generates described complementary output voltage signal, described load circuit comprises the first inverter circuit and the second inverter circuit, and described first inverter circuit and described second inverter circuit are suitable in response to described complementary current signal and generate described complementary output voltage signal.

84. signal level shift units according to Claim 8 described in 3, wherein:

The high siding track of described first inverter circuit is electrically coupled to the high siding track in described second source territory by the first transistor;

The high siding track of described second inverter circuit is electrically coupled to the described high siding track in described second source territory by transistor seconds; And

Described the first transistor and described transistor seconds cross-couplings.

85. the signal level shift unit according to Claim 8 described in 4, each inverter circuit in described inverter circuit comprises:

High-side transistor, described high-side transistor electric coupling is between the described high siding track and the output node of described inverter circuit of described inverter circuit; And

Low side transistors, described low side transistors electric coupling is between the described output node and the reference rail in described second source territory of described inverter circuit;

Described high-side transistor can be used to: when described low side transistors is in its conducting state, the described high siding track described output node of described inverter circuit being pulled upward to described phase inverter relative to the reference rail in described second source territory current potential five ten at least percent.

86. signal level shift units according to Claim 8 described in 5, described transconductance stage can be used to: when current potential lower than the reference rail of described first power domain of the current potential of the reference rail in described second source territory, be driven into by electric current in the described high siding track of described first inverter circuit and described second inverter circuit.

87. 1 kinds, for determining the system of the signal of the power represented in MPPT maximum power point tracking (MPPT) controller, comprising:

Voltage filter subsystem, described voltage filter subsystem is suitable for by carrying out filtering to generate across the signal of the voltage of the output port of described MPPT controller the signal that represents across the average voltage of described output port to representing;

Current filter subsystem, described current filter subsystem is suitable for the signal by carrying out filtering to generate representing the average current flowing out described output port to the signal of the electric current representing the described output port of outflow;

Voltage scaling subsystem, described voltage scaling subsystem is suitable for by zooming in the first preset range across the described signal of the average voltage of described output port the scale signal generating and represent across the average voltage of described output port by representing;

Electric current convergent-divergent subsystem, described electric current convergent-divergent subsystem is suitable for by representing that the described signal of the average current flowing out described output port zooms in the second preset range the scale signal generating and represent the average current flowing out described output port; And

Multiplier, described multiplier be suitable for according to represent across the average voltage of described output port described scale signal with represent that the product flowing out the described scale signal of the average current of described output port determines to represent the described signal of power.

88. systems according to Claim 8 described in 7, described multiplier comprises:

First input end mouth, described first input end mouth is suitable for receiving the described scale signal represented across the average voltage of described output port;

Second input port, described second input port is suitable for receiving the described scale signal representing the average current flowing out described output port;

Output port, described output port is suitable for providing the described signal representing power;

First field effect transistor, described first field effect transistor and described first input end mouth coupled in series electrical;

Second field effect transistor, described second field effect transistor and described second input port coupled in series electrical;

3rd field effect transistor, described 3rd field effect transistor and described output port coupled in series electrical; And

Control circuit, described control circuit is suitable for controlling each field effect transistor in described first field effect transistor, described second field effect transistor and described 3rd field effect transistor, and the product that the value making the value of the electric current flowing into described output port and (a) flow into the electric current of described first input end mouth and (b) flow into the value of the electric current of described second input port is proportional.

89. systems according to Claim 8 described in 8, the grid of described first field effect transistor is electrically coupled to the grid of described 3rd field effect transistor.

90. systems according to Claim 8 described in 9, also comprise:

4th field effect transistor and the 5th field effect transistor, described 4th field effect transistor and described 5th field effect transistor form current mirror, and described current mirror is configured such that the value of the drain-source current flowing through described 5th field effect transistor equals Iref and the value flowing through the drain-source current of described 4th field effect transistor equals Iref/m; And

First amplifier, described first amplifier is suitable for the described grid controlling described first field effect transistor, makes the voltage that the voltage across described first field effect transistor equals across described 4th field effect transistor.

91. according to the system described in claim 90, and the grid of described second field effect transistor is electrically coupled to the grid of described 4th field effect transistor and the grid of described 5th field effect transistor.

92. according to the system described in claim 91, when described transistor seconds, described 4th transistor and described 5th transistor are driven by common gate source voltage, described second field effect transistor has the channel resistance equaling R/m, and described 4th field effect transistor and described 5th field effect transistor have the channel resistance equaling R separately.

93. according to the system described in claim 92, also comprise the second amplifier and the 6th transistor, described second amplifier and described 6th transistor are configured to the described value of electric current controlling to flow into described output port, make the voltage that the voltage across described second field effect transistor equals across described 3rd field effect transistor.

94. systems according to Claim 8 described in 8, described electric current convergent-divergent subsystem comprises:

Mutual conductance subsystem, described mutual conductance subsystem is suitable for representing that the described signal of the average current flowing out described output port is converted to the described scale signal representing the average current flowing out described output port, described mutual conductance subsystem comprises programmable resistance, and described programmable resistance is suitable for setting the described gain across resistance subsystem; And

Steering logic, described steering logic is suitable for the resistance setting described programmable resistance, to adjust the described gain of described mutual conductance subsystem, makes the value of the described scale signal representing the average current flowing out described output port at least equally large with first threshold.

95. according to the system described in claim 94, and described mutual conductance subsystem also comprises:

Transistor, described transistor is electrically coupled to described programmable resistance; And

Amplifier, described amplifier is suitable in response to the described signal representing the average current flowing out described output port and controls described transistor, to regulate the voltage across described programmable resistance.

96. according to the system described in claim 95, and described steering logic is also suitable in response to the first external signal and the gain of described mutual conductance subsystem is set as minimum value.

97. according to the system described in claim 96, described steering logic is also suitable for the described gain increasing progressively described mutual conductance subsystem in response to the second external signal, until represent that the described value of the described scale signal of the electric current flowing out described output port is at least equally large with described first threshold.

98. according to the system described in claim 97, and described mutual conductance subsystem also comprises current mirror, and described current mirror is suitable in response to the electric current flowing through described programmable resistance and generates the described scale signal representing the average current flowing out described output port.

99. according to the system described in claim 94, and described current filter subsystem comprises:

Integrator subsystem, described integrator subsystem is suitable for operating in bipolarity territory, represents the AC compounent in the described signal of the electric current flowing out described output port with filtering; And

Transconductance circuit, described transconductance circuit is suitable for operating in unipolarity territory, to generate the described signal representing the average current flowing out described output port according to the mean value of the described signal representing the electric current flowing out described output port.

100. according to the system described in claim 99, wherein:

Described integrator subsystem is suitable for the integrator signal of the mean value generating expression one signal, and described signal represents the electric current flowing out described output port; And

Described transconductance circuit comprises the first trsanscondutance amplifier, and described first trsanscondutance amplifier is suitable for generating according to described integrator signal the described signal representing the average current flowing out described output port.

101. according to the system described in claim 100, and described integrator subsystem comprises:

Integrator, described integrator has reversed input terminal and non-inverting input terminal; And

Resistance device, described resistance device is across the described input end electric coupling of integrator;

The described non-inverting input terminal of described integrator is electrically coupled to reference mode via voltage source,

The described reversed input terminal of described integrator is electrically coupled to first node, and

Described current filter subsystem is arranged so that and represents that the described signal of the electric current flowing out described output port flows out described first node.

102. according to the system described in claim 101, and described transconductance circuit also comprises the second trsanscondutance amplifier, and described second trsanscondutance amplifier is suitable for the DC component generating the described signal representing the electric current flowing out described output port according to described integrator signal.

103. one kinds, for determining the method for the signal of the power represented in MPPT maximum power point tracking (MPPT) controller, comprise the following steps:

Filtering is carried out, to obtain the signal representing the average current flowing out described output port to the signal of the electric current representing the output port flowing out described MPPT controller;

Filtering is carried out, to obtain the signal of the average voltage represented across described output port to the signal represented across the voltage of described output port;

Convergent-divergent represents the described signal of the average current flowing out described output port, to obtain the scale signal representing the average current flowing out described output port;

Convergent-divergent represents the described signal of the average voltage across described output port, to obtain the scale signal of the average voltage represented across described output port; And

To represent that the described scale signal of the average current flowing out described output port is multiplied by the described scale signal represented across the average voltage of described output port, to obtain the described signal representing power.