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19 pages, 6931 KiB  
Article
A Hybrid Deep Learning Framework for OFDM with Index Modulation Under Uncertain Channel Conditions
by Md Abdul Aziz, Md Habibur Rahman, Rana Tabassum, Mohammad Abrar Shakil Sejan, Myung-Sun Baek and Hyoung-Kyu Song
Mathematics 2024, 12(22), 3583; https://doi.org/10.3390/math12223583 - 15 Nov 2024
Viewed by 537
Abstract
Index modulation (IM) is considered a promising approach for fifth-generation wireless systems due to its spectral efficiency and reduced complexity compared to conventional modulation techniques. However, IM faces difficulties in environments with unpredictable channel conditions, particularly in accurately detecting index values and dynamically [...] Read more.
Index modulation (IM) is considered a promising approach for fifth-generation wireless systems due to its spectral efficiency and reduced complexity compared to conventional modulation techniques. However, IM faces difficulties in environments with unpredictable channel conditions, particularly in accurately detecting index values and dynamically adjusting index assignments. Deep learning (DL) offers a potential solution by improving detection performance and resilience through the learning of intricate patterns in varying channel conditions. In this paper, we introduce a robust detection method based on a hybrid DL (HDL) model designed specifically for orthogonal frequency-division multiplexing with IM (OFDM-IM) in challenging channel environments. Our proposed HDL detector leverages a one-dimensional convolutional neural network (1D-CNN) for feature extraction, followed by a bidirectional long short-term memory (Bi-LSTM) network to capture temporal dependencies. Before feeding data into the network, the channel matrix and received signals are preprocessed using domain-specific knowledge. We evaluate the bit error rate (BER) performance of the proposed model using different optimizers and equalizers, then compare it with other models. Moreover, we evaluate the throughput and spectral efficiency across varying SNR levels. Simulation results demonstrate that the proposed hybrid detector surpasses traditional and other DL-based detectors in terms of performance, underscoring its effectiveness for OFDM-IM under uncertain channel conditions. Full article
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Figure 1
<p>Generalized data transmission process for an OFDM-IM system.</p>
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<p>Structure of the proposed HDL detector for OFDM-IM systems.</p>
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<p>The internal configuration of an LSTM cell.</p>
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<p>Training loss of the proposed HDL model for different equalizers with data setup <math display="inline"><semantics> <mrow> <mo>(</mo> <mi>N</mi> <mo>,</mo> <mi>A</mi> <mo>,</mo> <mi>M</mi> <mo>)</mo> <mo>=</mo> <mo>(</mo> <mn>4</mn> <mo>,</mo> <mn>1</mn> <mo>,</mo> <mn>4</mn> <mo>)</mo> </mrow> </semantics></math>: (<b>a</b>) training loss for the ZF equalizer, (<b>b</b>) training loss for the MMSE equalizer, and (<b>c</b>) training loss for the DFE equalizer.</p>
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<p>Training loss of the proposed HDL model for different modulation orders and data combinations with the ZF equalizer: (<b>a</b>) training loss for the <math display="inline"><semantics> <mrow> <mo>(</mo> <mi>N</mi> <mo>,</mo> <mi>A</mi> <mo>,</mo> <mi>M</mi> <mo>)</mo> <mo>=</mo> <mo>(</mo> <mn>4</mn> <mo>,</mo> <mn>1</mn> <mo>,</mo> <mn>4</mn> <mo>)</mo> </mrow> </semantics></math> setup, (<b>b</b>) training loss for the <math display="inline"><semantics> <mrow> <mo>(</mo> <mi>N</mi> <mo>,</mo> <mi>A</mi> <mo>,</mo> <mi>M</mi> <mo>)</mo> <mo>=</mo> <mo>(</mo> <mn>8</mn> <mo>,</mo> <mn>2</mn> <mo>,</mo> <mn>8</mn> <mo>)</mo> </mrow> </semantics></math> setup, and (<b>c</b>) training loss for the <math display="inline"><semantics> <mrow> <mo>(</mo> <mi>N</mi> <mo>,</mo> <mi>A</mi> <mo>,</mo> <mi>M</mi> <mo>)</mo> <mo>=</mo> <mo>(</mo> <mn>8</mn> <mo>,</mo> <mn>4</mn> <mo>,</mo> <mn>16</mn> <mo>)</mo> </mrow> </semantics></math> setup.</p>
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<p>The confusion matrix of the proposed HDL-based model.</p>
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<p>Performance of the HDL-based detector with (<b>a</b>) different learning rates and (<b>b</b>) different batch sizes in for the <math display="inline"><semantics> <mrow> <mo>(</mo> <mn>4</mn> <mo>,</mo> <mn>1</mn> <mo>,</mo> <mn>4</mn> <mo>)</mo> </mrow> </semantics></math> data combination.</p>
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<p>Performance of the HDL-based detector at various training SNRs for the <math display="inline"><semantics> <mrow> <mo>(</mo> <mn>4</mn> <mo>,</mo> <mn>1</mn> <mo>,</mo> <mn>4</mn> <mo>)</mo> </mrow> </semantics></math> data configuration.</p>
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<p>Performance of the proposed HDL-based detector with various equalizers for the <math display="inline"><semantics> <mrow> <mo>(</mo> <mn>4</mn> <mo>,</mo> <mn>1</mn> <mo>,</mo> <mn>4</mn> <mo>)</mo> </mrow> </semantics></math> data configuration.</p>
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<p>BER performance of the proposed HDL-based detector utilizing different optimizers for the <math display="inline"><semantics> <mrow> <mo>(</mo> <mn>4</mn> <mo>,</mo> <mn>1</mn> <mo>,</mo> <mn>4</mn> <mo>)</mo> </mrow> </semantics></math> data configuration.</p>
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<p>BER performance of the proposed HDL-based detector for various modulation orders and data setup.</p>
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<p>BER performance comparison of the proposed HDL-based detector with other detectors under imperfect CSI conditions for the <math display="inline"><semantics> <mrow> <mo>(</mo> <mn>4</mn> <mo>,</mo> <mn>1</mn> <mo>,</mo> <mn>4</mn> <mo>)</mo> </mrow> </semantics></math> data combinations.</p>
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<p>Throughput and SE of the proposed HDL-based OFDM-IM system: (<b>a</b>) throughput performance and (<b>b</b>) SE performance.</p>
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18 pages, 1618 KiB  
Article
MIMO Signal Detection Based on IM-LSTMNet Model
by Xiaoli Huang, Yumiao Yuan and Jingyu Li
Electronics 2024, 13(16), 3153; https://doi.org/10.3390/electronics13163153 - 9 Aug 2024
Cited by 1 | Viewed by 1109
Abstract
Signal detection is crucial in multi-input multi-output orthogonal frequency division multiplexing (MIMO-OFDM) systems, yet classical detection methods often struggle with nonlinear issues in wireless channels. To handle this challenge, we propose a novel signal detection method for MIMO-OFDM system based on the fractional [...] Read more.
Signal detection is crucial in multi-input multi-output orthogonal frequency division multiplexing (MIMO-OFDM) systems, yet classical detection methods often struggle with nonlinear issues in wireless channels. To handle this challenge, we propose a novel signal detection method for MIMO-OFDM system based on the fractional Fourier transform (FrFT), leveraging the robust time series processing capabilities of long short-term memory (LSTM) networks. Our innovative approach, termed IM-LSTMNet, integrates LSTM with convolutional neural networks (CNNs) and incorporates a Squeeze and Excitation Network to emphasize critical information, enhancing neural network performance. The proposed IM-LSTMNet is applied to the FrFT-based MIMO-OFDM system to improve signal detection performance. We compare the detection results of IM-LSTMNet with zero forcing (ZF), minimum mean square error (MMSE), simple LSTM neural network, and CNN–LSTM network by evaluating the bit error rate. Experimental results demonstrate that IM-LSTMNet outperforms ZF, MMSE, LSTM, and other methods, significantly enhancing system signal detection performance. This work offers a promising advancement in MIMO-OFDM signal detection, presenting a deep learning-based solution that effectively improves the system signal detection performance. Full article
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<p>MIMO system structure diagram.</p>
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<p>Flow chart of the IM-LSTMNet model detecting the MIMO-OFDM signal based on FrFT.</p>
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<p>Block diagram of the FrFT-based MIMO-OFDM system.</p>
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<p>IM-LSTMNet frame diagram.</p>
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<p>Convolutional neural network module diagram.</p>
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<p>Squeeze-and-Excitation Network.</p>
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<p>LSTM structure diagram.</p>
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<p>Framework diagram for the detection of the MIMO-OFDM signal by a neural network.</p>
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<p>SNR = 10 dB; IM-LSTMNet model training diagram.</p>
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<p>SNR = 10 dB; IM-LSTMNet model loss diagram.</p>
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<p>The MIMO-OFDM system’s BER with FrFT order of 1.</p>
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<p>The BER of IM-LSTMNet and traditional algorithms under different orders.</p>
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<p>The BER of IM-LSTMNet and other neural network algorithms at different orders.</p>
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<p>The BER of IM-LSTMNet and the traditional algorithms under different subcarrier numbers.</p>
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<p>The BER of IM-LSTMNet and other neural network algorithms under different subcarrier numbers.</p>
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<p>The BER of IM-LSTMNet and the traditional algorithms with or without CP.</p>
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<p>The BER of IM-LSTMNet and other neural network algorithms with or without CP.</p>
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<p>The BER of the neural network algorithm under different values of H.</p>
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22 pages, 3060 KiB  
Article
Sparse Reconstruction-Based Joint Signal Processing for MIMO-OFDM-IM Integrated Radar and Communication Systems
by Yang Wang, Yunhe Cao, Tat-Soon Yeo, Yuanhao Cheng and Yulin Zhang
Remote Sens. 2024, 16(10), 1773; https://doi.org/10.3390/rs16101773 - 16 May 2024
Cited by 3 | Viewed by 966
Abstract
Multiple-input multiple-output orthogonal frequency division multiplexing (MIMO-OFDM) technology is widely used in integrated radar and communication systems (IRCSs). Moreover, index modulation (IM) is a reliable OFDM transmission scheme in the field of communication, which transmits information by arranging several distinguishable constellations. In this [...] Read more.
Multiple-input multiple-output orthogonal frequency division multiplexing (MIMO-OFDM) technology is widely used in integrated radar and communication systems (IRCSs). Moreover, index modulation (IM) is a reliable OFDM transmission scheme in the field of communication, which transmits information by arranging several distinguishable constellations. In this paper, we propose a sparse reconstruction-based joint signal processing scheme for integrated MIMO-OFDM-IM systems. Combining the advantages of MIMO and OFDM-IM technologies, the integrated MIMO-OFDM-IM signal design is realized through the reasonable allocation of bits and subcarriers, resulting in better intercarrier interference (ICI) resistance and a higher transmission efficiency. Taking advantage of the sparseness of OFDM-IM, an improved target parameter estimation method based on sparse signal reconstruction is explored to eliminate the influence of empty subcarriers on the matched filtering at the receiver side. In addition, an improved sequential Monte Carlo signal detection method is introduced to realize the efficient detection of communication signals. The simulation results show that the proposed integrated system is 5 dB lower in the peak sidelobe ratio (PSLR) and 1.5 ×105 lower in the number of complex multiplications than the latest MIMO-OFDM system and can achieve almost the same parameter estimation performance. With the same spectral efficiency, it has a lower bit error rate (BER) than existing methods. Full article
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Graphical abstract

Graphical abstract
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<p>Schematic diagram of the proposed MIMO-OFDM integrated system model.</p>
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<p>Schematic diagram of MIMO-OFDM-IM integrated signal design in transmitter.</p>
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<p>Flow chart of the joint signal processing schemes in the proposed system.</p>
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<p>Flowchart of the conventional processing.</p>
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<p>The PSLR performance. (<b>a</b>) The variation in PSLR with SNR. (<b>b</b>) The variation in PSLR with the number of activated subcarriers (SNR = 10 dB).</p>
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<p>The variation in PSLR with SNR under different number of activated subcarriers.</p>
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<p>The variation in MSEs of range and velocity estimation with SNR under different methods (<math display="inline"><semantics> <msub> <mi>N</mi> <mi>r</mi> </msub> </semantics></math> = <math display="inline"><semantics> <msub> <mi>N</mi> <mi>t</mi> </msub> </semantics></math> = 4, <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>c</mi> <mo>_</mo> <mi>s</mi> <mi>u</mi> <mi>b</mi> </mrow> </msub> </semantics></math> = 8, <span class="html-italic">K</span> = 4, <span class="html-italic">H</span> = 4). (<b>a</b>) Range estimation. (<b>b</b>) Velocity estimation.</p>
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<p>Complexity comparison. (<b>a</b>) The variation in number of complex multiplications with the number of activated subcarriers. (<b>b</b>) The variation in number of complex multiplications with the number of transmitting antennas.</p>
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<p>The BER performance of different information detection methods under the proposed integrated MIMO-OFDM-IM system (<math display="inline"><semantics> <msub> <mi>N</mi> <mi>r</mi> </msub> </semantics></math> = <math display="inline"><semantics> <msub> <mi>N</mi> <mi>t</mi> </msub> </semantics></math> = 4). (<b>a</b>) <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>c</mi> <mo>_</mo> <mi>s</mi> <mi>u</mi> <mi>b</mi> </mrow> </msub> </semantics></math> = 8, <span class="html-italic">K</span> = 3; (<b>b</b>) <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>c</mi> <mo>_</mo> <mi>s</mi> <mi>u</mi> <mi>b</mi> </mrow> </msub> </semantics></math> = 8, <span class="html-italic">K</span> = 6.</p>
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<p>The BER performance of different information detection methods under the proposed integrated MIMO-OFDM-IM system (<math display="inline"><semantics> <msub> <mi>N</mi> <mi>r</mi> </msub> </semantics></math> = <math display="inline"><semantics> <msub> <mi>N</mi> <mi>t</mi> </msub> </semantics></math> = 8). (<b>a</b>) <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>c</mi> <mo>_</mo> <mi>s</mi> <mi>u</mi> <mi>b</mi> </mrow> </msub> </semantics></math> = 8, <span class="html-italic">K</span> = 3; (<b>b</b>) <math display="inline"><semantics> <msub> <mi>N</mi> <mrow> <mi>c</mi> <mo>_</mo> <mi>s</mi> <mi>u</mi> <mi>b</mi> </mrow> </msub> </semantics></math> = 8, <span class="html-italic">K</span> = 6.</p>
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<p>The variation in radar–communication trade-off curve with the number of activated subcarriers under different SNRs (<math display="inline"><semantics> <msub> <mi>N</mi> <mi>r</mi> </msub> </semantics></math> = <math display="inline"><semantics> <msub> <mi>N</mi> <mi>t</mi> </msub> </semantics></math> = 4). (<b>a</b>) SNR = 6 dB; (<b>b</b>) SNR = 12 dB.</p>
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16 pages, 562 KiB  
Article
Vector Approximate Message Passing Based OFDM-IM Detection for Underwater Acoustic Communications
by Xiao Feng, Feng Tian, Mingzhang Zhou, Haixin Sun and Zeyad A. H. Qasem
Entropy 2023, 25(12), 1667; https://doi.org/10.3390/e25121667 - 17 Dec 2023
Viewed by 1285
Abstract
Orthogonal frequency division multiplexing with index modulation (OFDM-IM) has great potential for the implementation of high spectral-efficiency underwater acoustic (UWA) communications. However, general receivers consisting of the optimal maximum likelihood detection suffer from high computational load, which prohibits real-time data transmissions in underwater [...] Read more.
Orthogonal frequency division multiplexing with index modulation (OFDM-IM) has great potential for the implementation of high spectral-efficiency underwater acoustic (UWA) communications. However, general receivers consisting of the optimal maximum likelihood detection suffer from high computational load, which prohibits real-time data transmissions in underwater scenarios. In this paper, we propose a detection based on a vector approximate message passing (VAMP) algorithm for UWA OFDM-IM communications. Firstly, a VAMP framework with a non-loopy factor graph for index detection is formulated. Secondly, by utilizing the sparsity inherently existing in OFDM-IM symbols, a novel shrinkage function is derived based on the minimum mean square error criterion, which guarantees better posterior estimation. To reduce the errors from estimated non-existing indices, one trick is utilized to search the elements from the look-up table with the minimal Euclidean distance for the replacement of erroneously estimated indices. Experiments verify the advantages of the proposed detector in terms of low complexity, robustness and effectiveness compared with the state-of-art benchmarks. Full article
(This article belongs to the Section Multidisciplinary Applications)
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<p>OFDM-IM system for UWA communications.</p>
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<p>Factor graph of VAMP based detection.</p>
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<p>BER performance of the proposed detector with different implementation forms.</p>
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<p>BER comparisons of detectors with different modulation methods. (<b>a</b>) BER of ML detector with different residual CFO effects when CFO = 0.2; (<b>b</b>) BER comparisons of detectors with CFO compensations when CFO = [0.05 0.2].</p>
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<p>Channel error effects on BER comparisons of detectors when <math display="inline"><semantics> <msup> <mi>ξ</mi> <mn>2</mn> </msup> </semantics></math> = [0.01 0.1].</p>
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<p>BER comparisons of detectors with different modulation methods. (<b>a</b>) BPSK; (<b>b</b>) QPSK; (<b>c</b>) 8PSK; (<b>d</b>) 16QAM.</p>
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<p>BER comparisons of detectors with different subcarrier allocations. (<b>a</b>) (4, 3, 4); (<b>b</b>) (8, 3, 4); (<b>c</b>) (8, 2, 2); (<b>d</b>) (8, 4, 2).</p>
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<p>Channel impulse response with different setting parameters. (<b>a</b>) Channel 1; (<b>b</b>) Channel 2.</p>
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<p>BER comparisons of detectors over different UWA channels. (<b>a</b>) BER over channel 1; (<b>b</b>) BER over channel 2.</p>
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<p>Real channel and BER comparisons of detectors. (<b>a</b>) Real channel from Wuyuan Bay; (<b>b</b>) BER over Wuyuan Bay channel.</p>
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17 pages, 1426 KiB  
Article
Efficient Index Modulation-Based MIMO OFDM Data Transmission and Detection for V2V Highly Dispersive Channels
by J. Alberto Del Puerto-Flores, Francisco R. Castillo-Soria, Carlos A. Gutiérrez and Fernando Peña-Campos
Mathematics 2023, 11(12), 2773; https://doi.org/10.3390/math11122773 - 20 Jun 2023
Cited by 4 | Viewed by 1934
Abstract
Vehicle-to-vehicle (V2V) communication networks are based on vehicles that wirelessly exchange data, traffic congestion, and safety warnings between them. The design of new V2V systems requires increasingly energetically and spectrally efficient systems. Conventional multiple-input–multiple-output (MIMO) orthogonal frequency division multiplexing (OFDM) systems have been [...] Read more.
Vehicle-to-vehicle (V2V) communication networks are based on vehicles that wirelessly exchange data, traffic congestion, and safety warnings between them. The design of new V2V systems requires increasingly energetically and spectrally efficient systems. Conventional multiple-input–multiple-output (MIMO) orthogonal frequency division multiplexing (OFDM) systems have been used successfully for the last decade. However, MIMO-OFDM systems need to be improved to face future communication networks in high-mobility environments. This article proposes an efficient index modulation (IM)-based MIMO-OFDM system for V2V channels. The proposed transmission system is evaluated in high Doppler-spread channels. The results demonstrate that the proposed scheme reduces the required computational complexity in data detection and exhibits gains of up to 3 dB in bit error rate (BER) performance when compared to the conventional MIMO-OFDM system under the same conditions and parameters, along with achieving superior spectral efficiency. The results show the viability of implementing the proposed system in practical applications for high-transmission-rate V2V channels. Full article
(This article belongs to the Special Issue Advances in Communication Systems, IoT and Blockchain)
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<p>MIMO-OFDM-IM transmitter proposed.</p>
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<p>Block diagram of proposed MIMO-OFDM-IM receiver.</p>
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<p>Comparison of the MSEs for the channel estimator in the proposed MIMO-OFDM-IM system versus a conventional MIMO-OFDM.</p>
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<p>BER-vs-<math display="inline"><semantics> <mrow> <msub> <mi>E</mi> <mi>b</mi> </msub> <mo>/</mo> <msub> <mi>N</mi> <mn>0</mn> </msub> </mrow> </semantics></math> comparison of different detection algorithms for MIMO-OFDM-IM and MIMO-OFDM with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>t</mi> </msub> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>r</mi> </msub> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math>, and 4-QAM data modulation.</p>
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<p>BER-vs-<math display="inline"><semantics> <mrow> <msub> <mi>E</mi> <mi>b</mi> </msub> <mo>/</mo> <msub> <mi>N</mi> <mn>0</mn> </msub> </mrow> </semantics></math> comparison of different detection algorithms for MIMO-OFDM-IM and MIMO-OFDM with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>t</mi> </msub> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>r</mi> </msub> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math>.</p>
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<p>BER-vs-<math display="inline"><semantics> <mrow> <msub> <mi>E</mi> <mi>b</mi> </msub> <mo>/</mo> <msub> <mi>N</mi> <mn>0</mn> </msub> </mrow> </semantics></math> comparison of different detection algorithms for MIMO-OFDM-IM and MIMO-OFDM with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>t</mi> </msub> <mo>=</mo> <mn>4</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>r</mi> </msub> <mo>=</mo> <mn>4</mn> </mrow> </semantics></math>.</p>
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<p>BER-vs-<math display="inline"><semantics> <mrow> <msub> <mi>E</mi> <mi>b</mi> </msub> <mo>/</mo> <msub> <mi>N</mi> <mn>0</mn> </msub> </mrow> </semantics></math> comparison of different detection algorithms for MIMO-OFDM-IM and MIMO-OFDM with <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>t</mi> </msub> <mo>=</mo> <mn>4</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>r</mi> </msub> <mo>=</mo> <mn>4</mn> </mrow> </semantics></math> under conditions of high transmission rates.</p>
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45 pages, 46634 KiB  
Review
A Survey on Physical Layer Techniques and Challenges in Underwater Communication Systems
by Naveed Ur Rehman Junejo, Mariyam Sattar, Saifullah Adnan, Haixin Sun, Abuzar B. M. Adam, Ahmad Hassan and Hamada Esmaiel
J. Mar. Sci. Eng. 2023, 11(4), 885; https://doi.org/10.3390/jmse11040885 - 21 Apr 2023
Cited by 15 | Viewed by 5449
Abstract
In the past decades, researchers/scientists have paid attention to the physical layer of underwater communications (UWCs) due to a variety of scientific, military, and civil tasks completed beneath water. This includes numerous activities critical for communication, such as survey and monitoring of oceans, [...] Read more.
In the past decades, researchers/scientists have paid attention to the physical layer of underwater communications (UWCs) due to a variety of scientific, military, and civil tasks completed beneath water. This includes numerous activities critical for communication, such as survey and monitoring of oceans, rescue, and response to disasters under the sea. Till the end of the last decade, many review articles addressing the history and survey of UWC have been published which were mostly focused on underwater sensor networks (UWSN), routing protocols, and underwater optical communication (UWOC). This paper provides an overview of underwater acoustic (UWA) physical layer techniques including cyclic prefix orthogonal frequency division multiplexing (CP-OFDM), zero padding orthogonal frequency division multiplexing (ZP-OFDM), time-domain synchronization orthogonal frequency division multiplexing (TDS-OFDM), multiple input multiple output orthogonal frequency division multiplexing (MIMO-OFDM), generalized frequency division multiplexing (GFDM), unfiltered orthogonal frequency division multiplexing (UF-OFDM), continuous phase modulation orthogonal frequency division multiplexing (CPM-OFDM), filter bank multicarrier (FBMC) modulation, MIMO, spatial modulation technologies (SMTs), and orthogonal frequency division multiplexing index modulation (OFDM-IM). Additionally, this paper provides a comprehensive review of UWA channel modeling problems and challenges, such as transmission loss, propagation delay, signal-to-noise ratio (SNR) and distance, multipath effect, ambient noise effect, delay spread, Doppler effect modeling, Doppler shift estimation. Further, modern technologies of the physical layer of UWC have been discussed. This study also discusses the different modulation technology in terms of spectral efficiency, computational complexity, date rate, bit error rate (BER), and energy efficiency along with their merits and demerits. Full article
(This article belongs to the Special Issue Underwater Perception and Sensing with Robotic Sensors and Networks)
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<p>Outline of UWA physical layer technologies, channel problems, and challenges.</p>
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<p>Orthogonality concept of subcarriers in OFDM.</p>
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<p>Demonstration of OFDM data in the time and frequency domain.</p>
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<p>Block diagram of OFDM transmitter [<a href="#B76-jmse-11-00885" class="html-bibr">76</a>].</p>
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<p>Block diagram of OFDM receiver [<a href="#B76-jmse-11-00885" class="html-bibr">76</a>].</p>
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<p>The transmitting process of ZP-OFDM and CP-OFDM [<a href="#B75-jmse-11-00885" class="html-bibr">75</a>].</p>
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<p>The receiving process of CP-OFDM and ZP-OFDM [<a href="#B75-jmse-11-00885" class="html-bibr">75</a>].</p>
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<p>OFDM receiver for UWACs [<a href="#B75-jmse-11-00885" class="html-bibr">75</a>].</p>
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<p>TDS-OFDM for the UWA channel [<a href="#B81-jmse-11-00885" class="html-bibr">81</a>].</p>
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<p>CP-OFDM, ZP-OFDM, and TDS-OFDM signal structure (<b>a</b>) time domain (<b>b</b>) frequency domain [<a href="#B94-jmse-11-00885" class="html-bibr">94</a>].</p>
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<p>The frame structure of the received signal (<b>a</b>) conventional TDS-OFDM (<b>b</b>) The DPN-TDS-OFDM (<b>c</b>) TDS-OFDM based on CS [<a href="#B94-jmse-11-00885" class="html-bibr">94</a>].</p>
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<p>GFDM transceiver block diagram of UWA.</p>
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<p>Transceiver block diagram of CPM-OFDM for UWAC [<a href="#B101-jmse-11-00885" class="html-bibr">101</a>].</p>
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<p>Temperature and depth-dependent speed variation.</p>
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<p>Different noise variances in UWC.</p>
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<p>Ray tracing for the representation of multipath channel [<a href="#B164-jmse-11-00885" class="html-bibr">164</a>].</p>
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<p>The range-dependent SNR for UWA links as a function of frequency [<a href="#B150-jmse-11-00885" class="html-bibr">150</a>].</p>
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<p>Doppler shifts varying effects over OFDM subcarriers [<a href="#B175-jmse-11-00885" class="html-bibr">175</a>].</p>
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<p>Underwater wireless communication modern technologies.</p>
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12 pages, 2045 KiB  
Article
Passive Backscatter Communication Scheme for OFDM-IM with Dynamic Carrier Activation
by Shibao Li and Rui Lu
Sensors 2023, 23(8), 3841; https://doi.org/10.3390/s23083841 - 9 Apr 2023
Viewed by 1782
Abstract
Multicarrier backscattering has been proposed to improve the communication rate, but the complex circuit structure of multicarrier backscattering devices requires more power consumption, resulting in devices far away from the radio frequency (RF) source without enough power to maintain communication, which greatly reduces [...] Read more.
Multicarrier backscattering has been proposed to improve the communication rate, but the complex circuit structure of multicarrier backscattering devices requires more power consumption, resulting in devices far away from the radio frequency (RF) source without enough power to maintain communication, which greatly reduces the limited communication range in backscattering. To solve this problem, this paper introduces carrier index modulation (IM) into orthogonal frequency division multiplexing (OFDM) backscattering and proposes a dynamic subcarrier activated OFDM-IM uplink communication scheme suitable for passive backscattering devices. When the existing power collection level of the backscatter device is detected, only a subset of carrier modulation is activated using part of the circuit modules to reduce the power threshold required for device activation. The activated subcarriers are mapped by a block-wise combined index using the look-up table method, which can not only transmit information using traditional constellation modulation but also carry additional information through the frequency domain carrier index. Monte Carlo experiments show that this scheme can effectively increase the communication distance and improve the spectral efficiency of low-order modulation backscattering when the power of the transmitting source is limited. Full article
(This article belongs to the Topic Wireless Sensor Networks)
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<p>Structure of a multicarrier backscatter device.</p>
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<p>Spatial model in an annulus coverage of backscatter devices.</p>
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<p>OFDM backscatter flow with index modulation.</p>
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<p>Comparison of the constellation diagrams between conventional (<b>A</b>) OFDM and (<b>B</b>) OFDM-IM.</p>
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<p>(<b>a</b>) Number of activations of different power devices at the transmitter. (<b>b</b>) Activation distance of different power devices at the transmitter.</p>
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<p>Decoding number comparison under different SNR.</p>
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<p>Reflection coefficient and number of device decodes.</p>
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<p>Bit rate of OFDM and OFDM-IM under BPSK modulation.</p>
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17 pages, 1126 KiB  
Article
A Hybrid PAPR Reduction Scheme in OFDM-IM Using Phase Rotation Factors and Dither Signals on Partial Sub-Carriers
by Si-Yu Zhang and Hui Zheng
Entropy 2022, 24(10), 1335; https://doi.org/10.3390/e24101335 - 22 Sep 2022
Cited by 3 | Viewed by 1697
Abstract
As a multi-carrier modulation technique, a high peak-to-average power ratio (PAPR) is a common issue suffered by orthogonal frequency division multiplexing with index modulation (OFDM-IM) due to its system structure. High PAPR may cause signal distortion, which affects correct symbol transmission. This paper [...] Read more.
As a multi-carrier modulation technique, a high peak-to-average power ratio (PAPR) is a common issue suffered by orthogonal frequency division multiplexing with index modulation (OFDM-IM) due to its system structure. High PAPR may cause signal distortion, which affects correct symbol transmission. This paper tries to inject dither signals to the inactive (idle) sub-carriers, which is a unique transmission structure of OFDM-IM, to reduce PAPR. Unlike the previous works, which utilize all idle sub-carriers, the proposed PAPR reduction scheme utilizes selected partial sub-carriers. This method performs well in terms of bit error rate (BER) performance and energy efficiency, which are obvious drawbacks of the previous PAPR reduction works due to the introduction of dither signals. In addition, in this paper, phase rotation factors are combined with the dither signals to compensate for the PAPR reduction performance degradation due to the insufficient use of partial idle sub-carriers. Moreover, an energy detection scheme is designed and proposed in this paper in order to distinguish the index of phase rotation factor used for transmission. It is shown by extensive simulation results that the proposed hybrid PAPR reduction scheme is able to implement an impressive PAPR reduction performance among existing dither signa-based schemes as well as classical distortion-less PAPR reduction schemes. In addition, the proposed method obtains better error performance and energy efficiency than that of the previous works. At the error probability 104, the proposed method can achieve around 5 dB gain compared to the conventional dither signal-based schemes Full article
(This article belongs to the Section Signal and Data Analysis)
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<p>Sub-block grouping of an OFDM-IM system.</p>
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<p>Mapping rules of OFDM-IM when <math display="inline"><semantics> <mrow> <mi>n</mi> <mo>=</mo> <mn>4</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mi>k</mi> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math>.</p>
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<p>Transmitter structure of the scheme in [<a href="#B17-entropy-24-01335" class="html-bibr">17</a>].</p>
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<p>Transmitter structure of the S.1 scheme.</p>
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<p>A BER performance comparison among the original OFDM-IM, S.1 scheme, and the <math display="inline"><semantics> <mrow> <mi>D</mi> <mi>i</mi> <mi>t</mi> <mi>h</mi> <mi>e</mi> <mi>r</mi> </mrow> </semantics></math> scheme [<a href="#B17-entropy-24-01335" class="html-bibr">17</a>].</p>
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<p>A CCDF comparison among the original OFDM-IM, S.1 scheme, and the <math display="inline"><semantics> <mrow> <mi>D</mi> <mi>i</mi> <mi>t</mi> <mi>h</mi> <mi>e</mi> <mi>r</mi> </mrow> </semantics></math> scheme [<a href="#B17-entropy-24-01335" class="html-bibr">17</a>].</p>
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<p>Transmitter structure of the proposed hybrid scheme.</p>
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<p>The IER of the proposed hybrid PAPR reduction scheme using different <span class="html-italic">U</span>, <span class="html-italic">V</span>, and <math display="inline"><semantics> <mi>β</mi> </semantics></math>.</p>
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<p>The CCDF performance comparison among the proposed scheme, the SLM scheme, the PTS scheme, the <math display="inline"><semantics> <mrow> <mi>D</mi> <mi>i</mi> <mi>t</mi> <mi>h</mi> <mi>e</mi> <mi>r</mi> </mrow> </semantics></math> scheme [<a href="#B17-entropy-24-01335" class="html-bibr">17</a>], the S.1 scheme, and the original OFDM-IM signal.</p>
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<p>The BER performance comparison among the proposed schemes, the <math display="inline"><semantics> <mrow> <mi>D</mi> <mi>i</mi> <mi>t</mi> <mi>h</mi> <mi>e</mi> <mi>r</mi> </mrow> </semantics></math> scheme [<a href="#B17-entropy-24-01335" class="html-bibr">17</a>], and the original OFDM-IM signal.</p>
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12 pages, 3915 KiB  
Communication
Orthogonal Subblock Division Multiple Access for OFDM-IM-Based Multi-User VLC Systems
by Yungui Nie, Jiamin Chen, Wanli Wen, Min Liu, Xiong Deng and Chen Chen
Photonics 2022, 9(6), 373; https://doi.org/10.3390/photonics9060373 - 25 May 2022
Cited by 7 | Viewed by 2103
Abstract
In this paper, we propose and experimentally demonstrate an orthogonal subblock division multiple access (OSDMA) scheme for orthogonal frequency division multiplexing with index modulation (OFDM-IM)-based multi-user visible light communication (MU-VLC) systems, where both single-mode index modulation (SM-IM) and dual-mode index modulation (DM-IM) are [...] Read more.
In this paper, we propose and experimentally demonstrate an orthogonal subblock division multiple access (OSDMA) scheme for orthogonal frequency division multiplexing with index modulation (OFDM-IM)-based multi-user visible light communication (MU-VLC) systems, where both single-mode index modulation (SM-IM) and dual-mode index modulation (DM-IM) are considered. In order to overcome the low-pass frequency response and the light-emitting diodes (LED) nonlinearity issues of practical MU-VLC systems, OSDMA is employed together with discrete Fourier transform spreading (DFT-S) and interleaving. The feasibility and superiority of the proposed scheme have been successfully verified via both simulations and hardware experiments. More specifically, we evaluate and compare the peak-to-average power ratio (PAPR) performance and the bit error rate (BER) performance of OFDM-SM-IM, DFT-S-OFDM-SM-IM, OFDM-DM-IM and DFT-S-OFDM-DM-IM without and with interleaving. Experimental results show that remarkable distance extensions can be achieved by employing DFT spreading and interleaving for both SM-IM and DM-IM in a two-user OSDMA-VLC system. Full article
(This article belongs to the Special Issue Next-Generation Optical Wireless Communication (OWC))
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<p>Block diagrams of the <span class="html-italic">K</span>-user OSDMA-MU-VLC system with DFT-spreading and interleaving: (<b>a</b>) transmitter and (<b>b</b>) receiver.</p>
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<p>Illustration of transmitted spectrum (<b>a</b>) without interleaving and (<b>b</b>) with interleaving, and received spectrum (<b>c</b>) without interleaving and (<b>d</b>) with interleaving.</p>
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<p>PAPR comparison of OFDM-SM-IM, DFT-S-OFDM-SM-IM, OFDM-DM-IM, and DFT-S-OFDM-DM-IM.</p>
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<p>Simulation BER vs. SNR for (<b>a</b>) OFDM-SM-IM and DFT-S-OFDM-SM-IM and (<b>b</b>) OFDM-DM-IM and DFT-S-OFDM-DM-IM without and with interleaving over the low-pass VLC channel (w/o: without, w/: with, interl.: interleaving).</p>
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<p>(<b>a</b>) Experimental setup of a two-user OSDMA-VLC system and (<b>b</b>) the photo of the experimental system.</p>
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<p>EOE frequency response of the experimental VLC system.</p>
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<p>Average received SNR vs. IFFT/FFT length of the DFT-S-OFDM signal (w/o: without, w/: with, interl.: interleaving).</p>
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<p>Measured BER vs. distance for (<b>a</b>) DFT-S-OFDM-SM-IM without and with interleaving and (<b>b</b>) DFT-S-OFDM-DM-IM without and with interleaving (w/o: without, w/: with, interl.: interleaving).</p>
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<p>Average BER vs. distance for (<b>a</b>) OFDM-SM-IM and DFT-S-OFDM-SM-IM without and with interleaving and (<b>b</b>) OFDM-DM-IM and DFT-S-OFDM-DM-IM without and with interleaving (w/o: without, w/: with, interl.: interleaving).</p>
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<p>The received constellation diagrams for: (<b>a</b>) OFDM-SM-IM, 16QAM, 50 cm, without interleaving, (<b>b</b>) DFT-S-OFDM-SM-IM, 16QAM, 50 cm, without interleaving, (<b>c</b>) OFDM-SM-IM, 16QAM, 50 cm, with interleaving, (<b>d</b>) DFT-S-OFDM-SM-IM, 16QAM, 50 cm, with interleaving, (<b>e</b>) OFDM-DM-IM, circular (7,1)QAM, 60 cm, without interleaving, (<b>f</b>) DFT-S-OFDM-DM-IM, circular (7,1)QAM, 60 cm, without interleaving, (<b>g</b>) OFDM-DM-IM, circular (7,1)QAM, 60 cm, with interleaving, and (<b>h</b>) DFT-S-OFDM-DM-IM, circular (7,1)QAM, 60 cm, with interleaving.</p>
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13 pages, 3116 KiB  
Article
Deep Learning-Based Next-Generation Waveform for Multiuser VLC Systems
by Hafiz M. Asif, Affan Affan, Naser Tarhuni and Kaamran Raahemifar
Sensors 2022, 22(7), 2771; https://doi.org/10.3390/s22072771 - 4 Apr 2022
Cited by 3 | Viewed by 2475
Abstract
Due to the growing number of users, power, and spectral effectiveness, most communication systems are complex and difficult to implement on a large scale. Artificial Intelligence (AI) has played an outstanding role in the implementation of theoretical systems in the real world, with [...] Read more.
Due to the growing number of users, power, and spectral effectiveness, most communication systems are complex and difficult to implement on a large scale. Artificial Intelligence (AI) has played an outstanding role in the implementation of theoretical systems in the real world, with less complexity achieving better results. In this direction, we compare the Non-Orthogonal Multiple Access (NOMA) technique for a multiuser Visible Light Communication (VLC) system with Successive Interference Cancellation (SIC) for two types of detectors: (1) the deep learning-based system and (2) the traditional maximum likelihood (ML) decoder-based system. For multiplexing, we compare the variations of novel Orbital Angular Momentum (OAM) multiplexing and Orthogonal Frequency Division Multiplexing (OFDM) with Index Modulation (IM). In this article, we implement OFDM-IM and OAM-IM for four users for the Gaussian fading MIMO Line-of-Sight (LoS) and Non-Line-of-Sight (NLoS) VLC channels. The suggested systems’ bit error rate (BER) performances are compared in simulations for a wide range of Signal-to-Noise Ratios (SNRs), which shows that deep learning-based systems outperform the ML-based system for both users to ensure better decoding at the receiver end, especially at higher SNR values. The detection error is lower in a deep learning-based system at around 20% and around 30% for low SNR and high SNR values, respectively. Full article
(This article belongs to the Special Issue Millimeter-Wave Communications for 5G and Beyond)
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<p>Waveforms of OAM and SAM.</p>
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<p>Multiple access using CDMA and NOMA.</p>
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<p>System block diagram of OAM-IM.</p>
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<p>OFDM-IM transmitter system block diagram.</p>
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<p>Receiver block diagram of OFDM-IM.</p>
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<p>VLC channel MIMO configuration.</p>
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<p>Framework of NOMA.</p>
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<p>Proposed CNN-based NOMA-SIC multiuser system.</p>
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<p>User 1 and user 2 BER of OFDM-IM and OAM-IM for LoS/NLoS VLC channel.</p>
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<p>User 3 and user 4 BER of OFDM-IM and OAM-IM for LoS/NLoS VLC channel.</p>
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17 pages, 4279 KiB  
Article
A Random Subcarrier-Selection Method Based on Index Modulation for Secure Transmission
by Tao Zhan, Jiangong Chen, Shan Luan and Xia Lei
Sensors 2022, 22(7), 2676; https://doi.org/10.3390/s22072676 - 31 Mar 2022
Viewed by 1659
Abstract
Recently, a frequency diverse array (FDA) has been employed in an orthogonal frequency division multiplexing (OFDM) transmitter to achieve secure wireless communication without mathematical encryption. However, an insecure coupling effect arises if the frequency increments are linearly assigned to all antenna elements. To [...] Read more.
Recently, a frequency diverse array (FDA) has been employed in an orthogonal frequency division multiplexing (OFDM) transmitter to achieve secure wireless communication without mathematical encryption. However, an insecure coupling effect arises if the frequency increments are linearly assigned to all antenna elements. To solve this problem, random subcarrier-selection methods are proposed; however, the challenge lies in the random selection of subcarriers. Inspired by the randomness of index modulation (IM), this paper proposes a low complexity random subcarrier-selection method based on index modulation (RSCS-IM). Specifically, this work conducted analysis on the spectral efficiency (SE) of our system and the computational complexity of RSCS-IM, which works out a closed-form expression of the BER performance of a desired position and validates the theoretical outcomes through simulation. Full article
(This article belongs to the Special Issue System Design and Signal Processing for 6G Wireless Communications)
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<p>The principle of block interleaving.</p>
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<p>Flow chart of PSS Plus RP.</p>
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<p>Array Structure of the FDA OFDM-IM Transmitter.</p>
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<p>Flow chart of RSCS-IM.</p>
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<p>Block diagram of the FDA OFDM-IM system.</p>
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<p>Simulation comparison of the random degree. (<b>a</b>) <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>s</mi> </msub> <mo>=</mo> <mn>512</mn> <mo>.</mo> </mrow> </semantics></math> (<b>b</b>) <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>s</mi> </msub> <mo>=</mo> <mn>1024</mn> </mrow> </semantics></math>.</p>
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<p>The computational complexity of RSCS-IM and PSS Plus RP. (<b>a</b>) <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>s</mi> </msub> <mo>=</mo> <mn>512</mn> <mo>.</mo> </mrow> </semantics></math> (<b>b</b>) <math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>s</mi> </msub> <mo>=</mo> <mn>1024</mn> </mrow> </semantics></math>.</p>
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<p>3-D performance surface of a uniform FDA.</p>
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<p>3-D performance surface of BER versus the direction angle and distance (<math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>s</mi> </msub> <mo>=</mo> <mn>512</mn> </mrow> </semantics></math>). (<b>a</b>) 3-D performance surface of BER using PSS Plus RP; (<b>b</b>) 3-D performance surface of BER using RSCS-IM.</p>
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<p>3-D performance surface of BER versus the direction angle and distance (<math display="inline"><semantics> <mrow> <msub> <mi>N</mi> <mi>s</mi> </msub> <mo>=</mo> <mn>1024</mn> </mrow> </semantics></math>). (<b>a</b>) 3-D performance surface of BER using PSS Plus RP; (<b>b</b>) 3-D performance surface of BER using RSCS-IM.</p>
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<p>BER performance versus <math display="inline"><semantics> <mrow> <msub> <mi>E</mi> <mi>b</mi> </msub> <mo>/</mo> <msub> <mi>N</mi> <mn>0</mn> </msub> </mrow> </semantics></math> of Bob.</p>
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<p>BER performance versus SNR of Eve under RSCS-IM and PSS Plus RP schemes with different <math display="inline"><semantics> <msub> <mi>N</mi> <mi>T</mi> </msub> </semantics></math>.</p>
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35 pages, 16121 KiB  
Article
Optical Channel Selection Avoiding DIPP in DSB-RFoF Fronthaul Interface
by Zbigniew Zakrzewski
Entropy 2021, 23(11), 1554; https://doi.org/10.3390/e23111554 - 22 Nov 2021
Cited by 7 | Viewed by 2491
Abstract
The paper presents a method of selecting an optical channel for transporting the double-sideband radio-frequency-over-fiber (DSB-RFoF) radio signal over the optical fronthaul path, avoiding the dispersion-induced power penalty (DIPP) phenomenon. The presented method complements the possibilities of a short-range optical network working in [...] Read more.
The paper presents a method of selecting an optical channel for transporting the double-sideband radio-frequency-over-fiber (DSB-RFoF) radio signal over the optical fronthaul path, avoiding the dispersion-induced power penalty (DIPP) phenomenon. The presented method complements the possibilities of a short-range optical network working in the flexible dense wavelength division multiplexing (DWDM) format, where chromatic dispersion compensation is not applied. As part of the study, calculations were made that indicate the limitations of the proposed method and allow for the development of an algorithm for effective optical channel selection in the presence of the DIPP phenomenon experienced in the optical link working in the intensity modulation–direct detection (IM-DD) technique. Calculations were made for three types of single-mode optical fibers and for selected microwave radio carriers that are used in current systems or will be used in next-generation wireless communication systems. In order to verify the calculations and theoretical considerations, a computer simulation was performed for two types of optical fibers and for two selected radio carriers. In the modulated radio signal, the cyclic-prefix orthogonal frequency division multiplexing (CP-OFDM) format and the 5G numerology were used. Full article
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<p>Functional splits proposed by 3GPP [<a href="#B13-entropy-23-01554" class="html-bibr">13</a>] in NG-RAN with an example of IF/RF extensions proposed by the author for A-RoF functions introduced into the distributed unit (DU) and the radio unit (RU) (green blocks and options) [<a href="#B21-entropy-23-01554" class="html-bibr">21</a>]. Optical BH/MH/FH and their maximal links could be realized in mobile 5G systems [<a href="#B40-entropy-23-01554" class="html-bibr">40</a>].</p>
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<p>Modeled attenuation characteristics of single-mode optical fibers in range of single-modality limited by the cut-off wavelength [<a href="#B41-entropy-23-01554" class="html-bibr">41</a>,<a href="#B42-entropy-23-01554" class="html-bibr">42</a>,<a href="#B43-entropy-23-01554" class="html-bibr">43</a>].</p>
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<p>Modeled characteristics of the chromatic dispersion coefficient of the single-mode optical fibers in range of single-modality limited by the cut-off wavelength [<a href="#B41-entropy-23-01554" class="html-bibr">41</a>,<a href="#B42-entropy-23-01554" class="html-bibr">42</a>,<a href="#B43-entropy-23-01554" class="html-bibr">43</a>].</p>
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<p>Example of the optical fronthaul path assembled with use of different standards of the single-mode optical fibers.</p>
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<p>Averaged characteristics of the chromatic dispersion coefficients for the exemplary optical fronthaul paths.</p>
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<p>Dispersion induced power penalty—carrier-to-interference ratio obtained after propagation over G.652D or G.657A single-mode fiber and direct detection in photodetector: (<b>a</b>) calculated values for the five selected RF carriers as a function of the optical fronthaul path length; (<b>b</b>) calculated values for the five selected optical fronthaul path lengths as a function of the RF carrier.</p>
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<p>Dispersion induced power penalty—carrier-to-interference ratio obtained after propagation over G.655D single-mode non-zero dispersion-shifted fiber and direct detection in photodetector: (<b>a</b>) calculated values for the five selected RF carriers as a function of the optical fronthaul path length; (<b>b</b>) calculated values for the five selected optical fronthaul path lengths as a function of the RF carrier.</p>
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<p>Dispersion-induced power penalty—carrier-to-interference ratio obtained after propagation over G.655E single-mode non-zero dispersion shifted fiber and direct detection in photodetector: (<b>a</b>) calculated values for the five selected RF carriers as a function of the optical fronthaul path length; (<b>b</b>) calculated values for the five selected optical fronthaul path lengths as a function of the RF carrier.</p>
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<p>The results of the dispersion-induced power penalty calculations, taking into account the 3 dB and 10 dB thresholds, obtained in the range of the S, C and L optical bands for the fronthaul path based on the G.652D or G.657A optical fiber of variable length: (<b>a</b>) <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mrow> <mi>R</mi> <mi>F</mi> </mrow> </msub> <mo>=</mo> <mn>12</mn> <mrow> <mo> </mo> <mi>GHz</mi> </mrow> </mrow> </semantics></math>; (<b>b</b>) <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mrow> <mi>R</mi> <mi>F</mi> </mrow> </msub> <mo>=</mo> <mn>28</mn> <mrow> <mo> </mo> <mi>GHz</mi> </mrow> </mrow> </semantics></math>; (<b>c</b>) <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mrow> <mi>R</mi> <mi>F</mi> </mrow> </msub> <mo>=</mo> <mn>60</mn> <mrow> <mo> </mo> <mi>GHz</mi> </mrow> </mrow> </semantics></math>; (<b>d</b>) <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mrow> <mi>R</mi> <mi>F</mi> </mrow> </msub> <mo>=</mo> <mn>84</mn> <mrow> <mo> </mo> <mi>GHz</mi> </mrow> </mrow> </semantics></math>.</p>
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<p>The results of the dispersion-induced power penalty calculations, taking into account the 3 dB and 10 dB thresholds, obtained in the range of the S, C and L optical bands for the fronthaul path based on the G.655D optical fiber of variable length: (<b>a</b>) <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mrow> <mi>R</mi> <mi>F</mi> </mrow> </msub> <mo>=</mo> <mn>12</mn> <mrow> <mo> </mo> <mi>GHz</mi> </mrow> </mrow> </semantics></math>; (<b>b</b>) <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mrow> <mi>R</mi> <mi>F</mi> </mrow> </msub> <mo>=</mo> <mn>28</mn> <mrow> <mo> </mo> <mi>GHz</mi> </mrow> </mrow> </semantics></math>; (<b>c</b>) <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mrow> <mi>R</mi> <mi>F</mi> </mrow> </msub> <mo>=</mo> <mn>60</mn> <mrow> <mo> </mo> <mi>GHz</mi> </mrow> </mrow> </semantics></math>; (<b>d</b>) <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mrow> <mi>R</mi> <mi>F</mi> </mrow> </msub> <mo>=</mo> <mn>84</mn> <mrow> <mo> </mo> <mi>GHz</mi> </mrow> </mrow> </semantics></math>.</p>
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<p>The results of the dispersion-induced power penalty calculations, taking into account the 3 dB and 10 dB thresholds, obtained in the range of the S, C and L optical bands for the fronthaul path based on the G.655E optical fiber of variable length: (<b>a</b>) <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mrow> <mi>R</mi> <mi>F</mi> </mrow> </msub> <mo>=</mo> <mn>12</mn> <mrow> <mo> </mo> <mi>GHz</mi> </mrow> </mrow> </semantics></math>; (<b>b</b>) <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mrow> <mi>R</mi> <mi>F</mi> </mrow> </msub> <mo>=</mo> <mn>28</mn> <mrow> <mo> </mo> <mi>GHz</mi> </mrow> </mrow> </semantics></math>; (<b>c</b>) <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mrow> <mi>R</mi> <mi>F</mi> </mrow> </msub> <mo>=</mo> <mn>60</mn> <mrow> <mo> </mo> <mi>GHz</mi> </mrow> </mrow> </semantics></math>; (<b>d</b>) <math display="inline"><semantics> <mrow> <msub> <mi>f</mi> <mrow> <mi>R</mi> <mi>F</mi> </mrow> </msub> <mo>=</mo> <mn>84</mn> <mrow> <mo> </mo> <mi>GHz</mi> </mrow> </mrow> </semantics></math>.</p>
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<p>DIPP-CIR as a function of the optical wavelength for selected radio carrier frequencies and the 20 km optical path created on the basis of the G.652D or G.657A optical fiber: (<b>a</b>) calculation results without selection; (<b>b</b>) 3 dB cut-off optical access ranges; (<b>c</b>) 10 dB cut-off optical access ranges.</p>
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<p>DIPP-CIR as a function of the optical wavelength for selected radio carrier frequencies and the 20 km optical path created on the basis of the G.655D optical fiber: (<b>a</b>) calculation results without selection; (<b>b</b>) 3 dB cut-off optical access ranges; (<b>c</b>) 10 dB cut-off optical access ranges.</p>
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<p>DIPP-CIR as a function of the optical wavelength for selected radio carrier frequencies and the 20 km optical path created on the basis of the G.655E optical fiber: (<b>a</b>) calculation results without selection; (<b>b</b>) 3 dB cut-off optical access ranges; (<b>c</b>) 10 dB cut-off optical access ranges.</p>
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<p>Differential DIPP-CIR as a function of the optical wavelength for selected radio carrier frequencies and the 20 km optical path created on the basis of the G.652D or G.657A optical fiber, and for selected radio channel widths: (<b>a</b>) 50 MHz; (<b>b</b>) 100 MHz; (<b>c</b>) 200 MHz; (<b>d</b>) 400 MHz.</p>
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<p>Differential DIPP-CIR as a function of the optical wavelength for selected radio carrier frequencies and the 20 km optical path created on the basis of the G.655D optical fiber, and for selected radio channel widths: (<b>a</b>) 50 MHz; (<b>b</b>) 100 MHz; (<b>c</b>) 200 MHz; (<b>d</b>) 400 MHz.</p>
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<p>Differential DIPP-CIR as a function of the optical wavelength for selected radio carrier frequencies and the 20 km optical path created on the basis of the G.655E optical fiber, and for selected radio channel widths: (<b>a</b>) 50 MHz; (<b>b</b>) 100 MHz; (<b>c</b>) 200 MHz; (<b>d</b>) 400 MHz.</p>
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<p>Calculation results of relative sideband delay in the optical channel (length of optical path/link is equal to 20 km and the radio channel frequency bandwidth for CP-OFDM modulation format is equal to 100 MHz).</p>
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<p>Optical channel selection algorithm based on DIPP-CIR calculations at two decision thresholds.</p>
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<p>Simulation diagram prepared on the VPIphotonics Design Suite 11.1 platform, presenting three fronthaul parts, configured for downlink transmission: BBU + DU cloud side, fiber-optic path/link and AAU/O-RRH as an antenna side.</p>
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<p>Example optical power spectrum of RFoF signal (<span class="html-italic">f</span><sub>RF</sub> = 60 GHz, G.655D fiber, optical channel no. 26 (195.7 THz), 4096 subcarriers, <span class="html-italic">µ</span> = 2): (<b>a</b>) inserted into the optical single-mode fiber/path, (<b>b</b>) at the photodetector input.</p>
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<p>Example radio power spectrum of RF signal (<span class="html-italic">f</span><sub>RF</sub> = 60 GHz, 4096 subcarriers, <span class="html-italic">µ</span> = 2, 1.835 Gbps, Δ<span class="html-italic">f</span><sub>RF</sub> = 247.7 MHz): (<b>a</b>) input signal; (<b>b</b>) output signal transported over G.655D fiber in optical channel no. 26 (195.7 THz); (<b>c</b>) output signal transported over G.655D fiber in optical channel no. 14 (194.5 THz).</p>
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<p>Example constellations of 256-QAM signal (<span class="html-italic">f</span><sub>RF</sub> = 60 GHz, G.655D fiber, <span class="html-italic">µ</span> = 2): (<b>a</b>) demodulated output signal transported over G.655D fiber in optical channel no. 26 (195.7 THz); (<b>b</b>) demodulated output signal transported over G.655D fiber in optical channel no. 14 (194.5 THz).</p>
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<p>Example radio power spectrum of RF signal (<span class="html-italic">f</span><sub>RF</sub> = 60 GHz, 4096 subcarriers, <span class="html-italic">µ</span> = 3, <span class="html-italic">R<sub>b</sub></span> = 2.752 Gbps, Δ<span class="html-italic">f</span><sub>RF</sub> = 491.5 MHz): (<b>a</b>) input signal; (<b>b</b>) output signal transported over G.655D fiber in optical channel no. 26 (195.7 THz); (<b>c</b>) output signal transported over G.655D fiber in optical channel no. 14 (194.5 THz).</p>
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<p>Example constellations of 64-QAM signal (<span class="html-italic">f</span><sub>RF</sub> = 60 GHz, G.655D fiber, <span class="html-italic">µ</span> = 3): (<b>a</b>) demodulated output signal transported over G.655D fiber in optical channel no. 26 (195.7 THz); (<b>b</b>) demodulated output signal transported over G.655D fiber in optical channel no. 14 (194.5 THz).</p>
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<p>Simulation results presenting SER as a quality parameter of the selected CP-OFDM signals transported over the G.652D/G.657A single-mode fiber fronthaul (<span class="html-italic">L</span> = 20 km): (<b>a</b>) for radio carrier <span class="html-italic">f<sub>RF</sub></span> = 60 GHz and the calculated optical 10 dB subband: 193.1630–194.7505 THz; (<b>b</b>) for radio carrier <span class="html-italic">f<sub>RF</sub></span> = 28 GHz and the calculated optical 10 dB subband: 190.0130–197.2505 THz.</p>
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<p>Simulation results presenting SER as a quality parameter of the selected CP-OFDM signals transported over the G.655D non-zero dispersion-shifted single-mode fiber fronthaul (<span class="html-italic">L</span> = 20 km): (<b>a</b>) for radio carrier <span class="html-italic">f<sub>RF</sub></span> = 60 GHz and the calculated optical 10 dB subband: 194.5130–196.7255 THz; (<b>b</b>) for radio carrier <span class="html-italic">f<sub>RF</sub></span> = 28 GHz and the calculated optical 10 dB subband: 184.4880–191.1068 THz.</p>
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25 pages, 540 KiB  
Article
Null Subcarrier Index Modulation in OFDM Systems for 6G and Beyond
by Tuncay Eren and Aydin Akan
Sensors 2021, 21(21), 7263; https://doi.org/10.3390/s21217263 - 31 Oct 2021
Cited by 6 | Viewed by 5080
Abstract
Computational complexity is one of the drawbacks of orthogonal frequency division multiplexing (OFDM)-index modulation (IM) systems. In this study, a novel IM technique is proposed for OFDM systems by considering the null subcarrier locations (NSC-OFDM-IM) within a predetermined group in the frequency domain. [...] Read more.
Computational complexity is one of the drawbacks of orthogonal frequency division multiplexing (OFDM)-index modulation (IM) systems. In this study, a novel IM technique is proposed for OFDM systems by considering the null subcarrier locations (NSC-OFDM-IM) within a predetermined group in the frequency domain. So far, a variety of index modulation techniques have been proposed for OFDM systems. However, they are almost always based on modulating the active subcarrier indices. We propose a novel index modulation technique by employing the part of the transmitted bit group into the null subcarrier location index within the predefined size of the subgroup. The novelty comes from modulating null subcarriers rather than actives and reducing the computational complexity of the index selection and index detection algorithms at the transmitter and receiver, respectively. The proposed method is physically straightforward and easy to implement owing to the size of the subgroups, which is defined as a power of two. Based on the results of our simulations, it appeared that the proposed NSC-OFDM-IM does not suffer from any performance degradation compared to the existing OFDM-IM, while achieving better bit error rate (BER) performance and improved spectral efficiency (SE) compared to conventional OFDM. Moreover, in terms of computational complexity, the proposed approach has a significantly reduced complexity over the traditional OFDM-IM scheme. Full article
(This article belongs to the Special Issue Flexible Radio Access Techniques for 5G and Beyond)
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Figure 1
<p>Conventional OFDM system.</p>
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<p>OFDM-IM system transmitter.</p>
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<p>The subgroups in the frequency domain.</p>
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<p>The proposed NSC-OFDM-IM transmitter.</p>
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<p>The proposed NSC-OFDM-IM receiver.</p>
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<p>Example of the NSC-OFDM-IM transmitter.</p>
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<p>Frequency domain illustration of the modulated example carriers.</p>
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<p>BER performance comparison between the proposed NSC-OFDM-IM and conventional OFDM-IM/OFDM, where the BPSK modulation was adopted.</p>
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<p>Comparison of the proposed NSC-OFDM-IM with conventional OFDM/OFDM-IM in terms of spectral efficiency, where the BPSK modulation was adopted.</p>
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<p>BER performance comparison between the proposed NSC-OFDM-IM and conventional OFDM-IM/OFDM, where 4-QAM modulation was adopted.</p>
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<p>Succession rate of the null carrier indices for the proposed NSC-OFDM-IM system.</p>
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<p>Comparison of the proposed NSC-OFDM-IM with conventional OFDM/OFDM-IM in terms of spectral efficiency, where 4-QAM modulation was adopted.</p>
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<p>BER performance comparison between the proposed NSC-OFDM-IM and conventional OFDM-IM/OFDM, where 8-PSK modulation was adopted.</p>
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<p>Comparison of the proposed NSC-OFDM-IM with conventional OFDM/OFDM-IM in terms of spectral efficiency, where 8-PSK modulation was adopted.</p>
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<p>Performance of the proposed NSC-OFDM-IM without applying the LLR detection.</p>
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17 pages, 4156 KiB  
Article
A CMOS RF Receiver with Improved Resilience to OFDM-Induced Second-Order Intermodulation Distortion for MedRadio Biomedical Devices and Sensors
by Yongho Lee, Shinil Chang, Jungah Kim and Hyunchol Shin
Sensors 2021, 21(16), 5303; https://doi.org/10.3390/s21165303 - 5 Aug 2021
Cited by 3 | Viewed by 2919
Abstract
A MedRadio RF receiver integrated circuit for implanted and wearable biomedical devices must be resilient to the out-of-band (OOB) orthogonal frequency division modulation (OFDM) blocker. As the OFDM is widely adopted for various broadcasting and communication systems in the ultra-high frequency (UHF) band, [...] Read more.
A MedRadio RF receiver integrated circuit for implanted and wearable biomedical devices must be resilient to the out-of-band (OOB) orthogonal frequency division modulation (OFDM) blocker. As the OFDM is widely adopted for various broadcasting and communication systems in the ultra-high frequency (UHF) band, the selectivity performance of the MedRadio RF receiver can severely deteriorate by the second-order intermodulation (IM2) distortion induced by the OOB OFDM blocker. An analytical investigation shows how the OFDM-induced IM2 distortion power can be translated to an equivalent two-tone-induced IM2 distortion power. It makes the OFDM-induced IM2 analysis and characterization process for a MedRadio RF receiver much simpler and more straightforward. A MedRadio RF receiver integrated circuit with a significantly improved resilience to the OOB IM2 distortion is designed in 65 nm complementary metal-oxide-semiconductor (CMOS). The designed RF receiver is based on low-IF architecture, comprising a low-noise amplifier, single-to-differential transconductance stage, quadrature passive mixer, trans-impedance amplifier (TIA), image-rejecting complex bandpass filter, and fractional phase-locked loop synthesizer. We describe design techniques for the IM2 calibration through the gate bias tuning at the mixer, and the dc offset calibration that overcomes the conflict with the preceding IM2 calibration through the body bias tuning at the TIA. Measured results show that the OOB carrier-to-interference ratio (CIR) performance is significantly improved by 4–11 dB through the proposed IM2 calibration. The measured maximum tolerable CIR is found to be between −40.2 and −71.2 dBc for the two-tone blocker condition and between −70 and −77 dBc for the single-tone blocker condition. The analytical and experimental results of this work will be essential to improve the selectivity performance of a MedRadio RF receiver against the OOB OFDM-blocker-induced IM2 distortion and, thus, improve the robustness of the biomedical devices in harsh wireless environments in the MedRadio and UHF bands. Full article
(This article belongs to the Special Issue Advanced CMOS Integrated Circuit Design and Application)
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<p>Two-tone blocker effects. (<b>a</b>) Third-order intermodulation effect for the close-in blocker, (<b>b</b>) second-order intermodulation effects for the far-out blocker.</p>
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<p>IM2 distortions induced by the multi-tone OFDM blocker.</p>
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<p>The MedRadio RF receiver architecture.</p>
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<p>Complex biquad. (<b>a</b>) Block diagram, (<b>b</b>) transfer characteristics, (<b>c</b>) operational amplifier schematic.</p>
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<p>Circuit schematic of the RF front end.</p>
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<p>Simulation results of the IM2 calibration.</p>
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<p>Chip micrograph.</p>
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<p>Measured S<sub>11</sub> of the receiver.</p>
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<p>Measured gain and noise figure of the RF front end.</p>
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<p>Measured frequency response of the complex BPF.</p>
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<p>Measured phase noise of the PLL synthesizer.</p>
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<p>IM2 calibration performance measurements. (<b>a</b>) Spectrum, (<b>b</b>) results over the UHF band.</p>
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<p>Measured maximum tolerable CIR against two-tone blocker.</p>
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<p>Measured maximum tolerable CIR against single-tone blocker.</p>
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<p>Measured single-tone 1 dB desensitization.</p>
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11 pages, 315 KiB  
Article
Hybrid Adaptive Bias OFDM-Based IM/DD Visible Light Communication System
by Huandong Hong and Zhengquan Li
Photonics 2021, 8(7), 257; https://doi.org/10.3390/photonics8070257 - 5 Jul 2021
Cited by 8 | Viewed by 2557
Abstract
Conventional optical orthogonal frequency division multiplexing (OFDM) schemes, such as adaptively biased optical OFDM (ABO-OFDM) and hybrid asymmetrically clipped optical OFDM (HACO-OFDM), are unable to tap all the resources of the subcarriers and only achieve relatively high power efficiency. In this paper, a [...] Read more.
Conventional optical orthogonal frequency division multiplexing (OFDM) schemes, such as adaptively biased optical OFDM (ABO-OFDM) and hybrid asymmetrically clipped optical OFDM (HACO-OFDM), are unable to tap all the resources of the subcarriers and only achieve relatively high power efficiency. In this paper, a hybrid adaptive bias optical OFDM (HABO-OFDM) scheme for visible light communication (VLC) is proposed to improve spectral efficiency and power efficiency. In the proposed HABO-OFDM scheme, different optical OFDM components are combined for transmission at the same time, and the adaptive bias is designed to ensure the non-negativity, as well as obtaining significantly high power efficiency. Meanwhile, the implementation complexity of the HABO-OFDM receiver is notably lower than the conventional superimposed optical OFDM schemes. Simulation results show that the proposed HABO-OFDM scheme outperforms ABO-OFDM and HACO-OFDM in terms of both peak-to-average-power ratio (PAPR) and power efficiency. The PAPR performance of HABO-OFDM is about 3.2 dB lower than that of HACO-OFDM and 1.7 dB lower than that of ABO-OFDM. Moreover, we can see that the Eb(elec)/N0 required for HABO-OFDM to reach the BER target is lower than the other two schemes at the Bit rate/Normalized bandwidth range of 3.5 to 8.75, which means that the power efficiency of HABO-OFDM is higher in this range. Full article
(This article belongs to the Special Issue Visible Light Communication (VLC))
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<p>Block diagram structure of the transmitter of the proposed HABO-OFDM system.</p>
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<p>Block diagram structure of the receiver of the proposed HABO-OFDM system.</p>
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<p>Comparison of the BER performance for HACO-OFDM, ABO-OFDM, and HABO-OFDM.</p>
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<p>CCDF curves of the PAPR for HACO-OFDM, ABO-OFDM, and HABO-OFDM.</p>
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<p>BER of HACO-OFDM, ABO-OFDM, and HABO-OFDM versus <math display="inline"><semantics> <mrow> <msub> <mi>E</mi> <mrow> <mi>b</mi> <mo>(</mo> <mi>e</mi> <mi>l</mi> <mi>e</mi> <mi>c</mi> <mo>)</mo> </mrow> </msub> <mo>/</mo> <msub> <mi>N</mi> <mn>0</mn> </msub> </mrow> </semantics></math> when the clipping ratio is set to 9 dB.</p>
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<p>Comparison of <math display="inline"><semantics> <msub> <mrow> <mo>〈</mo> <msub> <mi>E</mi> <mrow> <mi>b</mi> <mo>(</mo> <mi>e</mi> <mi>l</mi> <mi>e</mi> <mi>c</mi> <mo>)</mo> </mrow> </msub> <mo>/</mo> <msub> <mi>N</mi> <mn>0</mn> </msub> <mo>〉</mo> </mrow> <mrow> <mi>B</mi> <mi>E</mi> <mi>R</mi> </mrow> </msub> </semantics></math> for HACO-OFDM for different proportions of electric power.</p>
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<p>Comparison of <math display="inline"><semantics> <msub> <mrow> <mo>〈</mo> <msub> <mi>E</mi> <mrow> <mi>b</mi> <mo>(</mo> <mi>e</mi> <mi>l</mi> <mi>e</mi> <mi>c</mi> <mo>)</mo> </mrow> </msub> <mo>/</mo> <msub> <mi>N</mi> <mn>0</mn> </msub> <mo>〉</mo> </mrow> <mrow> <mi>B</mi> <mi>E</mi> <mi>R</mi> </mrow> </msub> </semantics></math> for HABO-OFDM for different proportions of electric power.</p>
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<p><math display="inline"><semantics> <msub> <mrow> <mo>〈</mo> <msub> <mi>E</mi> <mrow> <mi>b</mi> <mo>(</mo> <mi>e</mi> <mi>l</mi> <mi>e</mi> <mi>c</mi> <mo>)</mo> </mrow> </msub> <mo>/</mo> <msub> <mi>N</mi> <mn>0</mn> </msub> <mo>〉</mo> </mrow> <mrow> <mi>B</mi> <mi>E</mi> <mi>R</mi> </mrow> </msub> </semantics></math> required for the BER target of <math display="inline"><semantics> <msup> <mn>10</mn> <mrow> <mo>−</mo> <mn>3</mn> </mrow> </msup> </semantics></math> versus Bit rate/Normalized bandwidth.</p>
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