CN106982022A - A kind of starting method of no electrolytic capacitor inverter permagnetic synchronous motor - Google Patents
A kind of starting method of no electrolytic capacitor inverter permagnetic synchronous motor Download PDFInfo
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- H—ELECTRICITY
- H02—GENERATION; CONVERSION OR DISTRIBUTION OF ELECTRIC POWER
- H02P—CONTROL OR REGULATION OF ELECTRIC MOTORS, ELECTRIC GENERATORS OR DYNAMO-ELECTRIC CONVERTERS; CONTROLLING TRANSFORMERS, REACTORS OR CHOKE COILS
- H02P6/00—Arrangements for controlling synchronous motors or other dynamo-electric motors using electronic commutation dependent on the rotor position; Electronic commutators therefor
- H02P6/20—Arrangements for starting
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Abstract
The invention discloses a kind of starting method of no electrolytic capacitor inverter permagnetic synchronous motor, including：AC power AC, inductance L, uncontrollable rectifier bridge BR, thin-film capacitor C, power model, permagnetic synchronous motor, and software computing unit：Motor speed calculates unit, CLARK converter units, PARK converter units, speed regulator unit, current regulator, PARK inverse transformation blocks, SVPWM computing units, speed regulator output is multiplied into a control with changed scale coefficient being directly proportional to DC bus-bar voltage, q shaft currents i is used asqSet-point.Starting method proposed by the present invention is on the premise of setting speed regulator proportional gain factor as big as possible, obtaining electric motor starting torque as big as possible, actual q shaft current set-points can be automatically adjusted according to the size of starting duty, effectively suppress inverter startup electric current crosses flow problem.
Description
Technical field
The present invention relates to motor control technology field, more particularly to a kind of no electrolytic capacitor inverter permagnetic synchronous motor
Starting method.
Background technology
As design of electrical motor, motor manufacturing level and material property are substantially improved, simultaneous Power Electronic Technique
High speed development, the motor inverter system based on vector control technology is excellent with its high power density, high reliability and low cost etc.
Point is widely used in the fields such as electric automobile, Digit Control Machine Tool, robot, convertible frequency air-conditioner.Conventional inverter prime is industrial frequency AC
Input can not control rectifier, the bus stable busbar voltage of big capacitance electrochemical capacitor, electrochemical capacitor volume greatly, restricted lifetime,
This strongly limits the miniaturization of system and service life.On the other hand, big capacitance electrochemical capacitor filtering causes power network on bus
Side produces serious harmonic pollution, in recent years in the country /region such as China and Europe, and the power supply high order produced for inverter is humorous
The limitation standard of ripple is more and more stricter, and the 3C certifications of such as China provide to be less than every phase current 16A domestic air-conditioning system, respectively
Primary current harmonic limits must are fulfilled for IEC6100-3-2 A class standards.For improve current on line side quality, big electrochemical capacitor it is inverse
Becoming device system needs to increase PFC (PFC) circuit, and which again increases the loss of system and cost.It is above-mentioned in order to solve
Problem, Japanese Changgong University of Science and Technology Kazuya Inazuma, Hiroaki Utsugi, Kiyoshi Ohishi et al. exists《IEEE
TRANSACTIONS ON INDUSTRIAL ELECTRONICS》(VOL.60, NO.10, OCTOBER 2013, p4427~
4437) a kind of no electrolytic capacitor inverter topology and its control method (High-Power-Factor are proposed on magazine
Single-Phase Diode Rectifier Driven by Repetitively Controlled IPM Motor), use
Capacitance only has the big capacitance electrochemical capacitor in the thin-film capacitor substitution conventional inverter of tens microfarads, passes through the instantaneous of controlled motor
The form fit of power and AC-input voltage, can not only realize the speed governing of motor, and can reduce the humorous of input current
Ripple, so as to realize the high power factor of motor inverter.But this no electrolytic capacitor inverter technology scheme is just for electricity
Machine steady state operating condition, the starting control scheme of motor is not referred to.
And speed regulator design is base in the important step of permagnetic synchronous motor vector controlled start-up strategy, starting technique
In PI adjust speed regulator proportional gain factor and integration gain factor be according to load characteristic and hardware circuit excessively stream, mistake
Pressure threshold value is come what is be configured, and the output of PI speed regulators directly determines the size of q shaft current iq set-points.PI speed is adjusted
The proportional gain factor value of device is bigger, and the starting torque of motor is bigger, dynamic characteristic is better, but the starting current of inverter
It is bigger, inverter overcurrent damage may be caused when situation is serious；And when the proportional gain factor value of PI speed regulators is less than normal
When, the dynamic response characteristic and carrying load ability of system will be deteriorated.For no electrolytic capacitor inverter, due to using capacitance
Less thin-film capacitor is as filter capacitor, and DC bus-bar voltage falls seriously in motor starting process, causes electric motor starting power
How the decline of square, optimal speed regulator parameter is chosen according to the situation of load, the starting torque of motor is reached maximum
And the excessively stream of hardware system, overpressure problems are occurred without, it is a very important research topic.
The content of the invention
The present invention proposes a kind of starting method of no electrolytic capacitor inverter permagnetic synchronous motor, by speed regulator
Output multiplies control with changed scale coefficient as q shaft current set-pointsAnd this control with changed scale coefficient and DC bus-bar voltage instantaneous value are into just
Than.Because no electrolytic capacitor inverter lands rapidly in start-up period busbar voltage with the rising of motor speed, bus electricity
The amplitude of drop of pressure reflects the size of load indirectly, and the present invention can set speed regulator proportional gain system as big as possible
Number, obtain big electric motor starting torque as far as possible on the premise of, actual q shaft currents are automatically adjusted according to the size of starting duty
Set-point, effectively suppress inverter startup electric current crosses flow problem.
The present invention can be achieved through the following technical solutions：
A kind of starting method of no electrolytic capacitor inverter permagnetic synchronous motor, system hardware includes：AC power AC, electricity
Feel L, uncontrollable rectifier bridge BR, thin-film capacitor C, power model, permagnetic synchronous motor, and software computing unit includes：Motor turns
Fast computing unit, CLARK converter units, PARK converter units, speed regulator unit, current regulator, PARK inverse transformation lists
Member, SVPWM computing units, the described method comprises the following steps：
S11：Current acquisition sensor passes through sampled measurements to motor stator phase current iu、iv, and obtain the 3rd by calculating
Phase stator current iw=-iu-iv, measure the DC bus-bar voltage V at the thin-film capacitor endc, calculate average voltage Vavg, calculate
Proportionality coefficient k=Vc/Vavg, proportionality coefficient k is a variable, with DC bus-bar voltage VcIt is directly proportional；
S12：Position sensor detects the rotor position angle θ of motor, and the machinery that motor is obtained to rotor position angle θ differential turns
Fast ωr=d θ/dt；
S13：It is supplied to the PARK converter units and the PARK inverse transformation blocks to be calculated rotor position angle θ,
By motor stator phase current iu、iv、iwThe d axis components i of motor stator electric current is obtained by carrying out CLARK conversion and PARK conversiond
With q axis components iq；
S14：Speed regulator adjusts control, given rotating speed ω using PIsetInputted as speed regulator, above-mentioned steps
Obtained motor actual speed ω is calculated in S12rFed back as speed regulator, speed regulator is output as stator current is,
D shaft current reference quantities are setIt is speed regulator output and control with changed scale coefficient k product to set q shaft currents reference quantity：
S15：Current regulator adjusts control, d, q shaft current reference quantity using PIFor the defeated of current regulator
Enter d, q shaft current component i for calculating and obtaining in amount, above-mentioned steps S13d、iqIt is used as the feedback of current regulator, current regulator
Output as d, q coordinate system component of voltage Vd、Vq；
S16：The V of the component of voltaged、VqAccording to rotor position angle θ, α, β rectangular co-ordinate are calculated by PARK inverse transformations
The component of voltage V of systemα、Vβ；
S17：The component of voltage Vα、VβSix IGBT power tubes in power model are calculated by SVPWM computing units to lead
Logical dutycycle, produces corresponding 6 road pwm signal；
S18：The logical drive permagnetic synchronous motor work that the power model is provided by 6 road pwm signals.
Methods described combines the output of speed regulator with d-c bus voltage value, based on step S14 method
Calculate q shaft current set-pointsThis method can improve the starting capability of motor, while effectively reducing the starting current of inverter.
Further, the capacitance of thin-film capacitor C described in inverter is less than 50 microfarads.
Further, d, q shaft voltage equation of permagnetic synchronous motor are：
D, q axle flux linkage equations are：
The electromagnetic torque equation of permagnetic synchronous motor is：
Tem=pn(ψdiq-ψqid) (3)
In formula (1), (2), (3)：Vd、Vq、id、iqRespectively d, q shaft voltage and electric current；RsFor stator resistance；Ld、LqRespectively
For d, q axle inductance；ψd、ψqRespectively d, q axle magnetic linkage；ψfFor permanent magnet flux linkage；ω is angular rate；pnFor motor number of pole-pairs；Tem
For electromagnetic torque；
The equation of motion of permagnetic synchronous motor is：
In formula：J is the rotary inertia of rotor；ωrFor mechanical angular speed；B is viscous damping coefficient；TLTurn for load
Square.
Further, using the speed control adjusted based on PI, stator current i is calculated as followss：
K in formulapRepresent speed control proportional gain factor, kiRepresent speed control integration gain factor, ωrFor motor
Actual speed, ωsetFor the given speed of motor, τ represents the time, and t represents current time.
Further, d, q shaft current set-pointI is exported by speed regulatorsMultiply a proportionality coefficient k to draw：
U in formulacFor the DC bus-bar voltage at thin-film capacitor end, uavgFor busbar voltage average value, k is one and started
The proportionality coefficient changed in journey, with DC bus-bar voltage ucIt is directly proportional.
Brief description of the drawings：
Fig. 1 is the vector controlled block diagram used in the electric motor starting stage of the present invention；
Fig. 2 is starting control flow chart of the invention；
Fig. 3 is scheme 1 starting characteristic curve (Kp=0.006, TL=1.0Nm)；
Fig. 4 is scheme 2 starting characteristic curve (Kp=0.004, TL=1.0Nm)；
Fig. 5 is scheme 3 starting characteristic curve (Kp=0.004, TL=1.5Nm)；
Fig. 6 is scheme 4 starting characteristic curve (Kp=0.006, TL=1.0Nm)；
Fig. 7 is scheme 5 starting characteristic curve (Kp=0.006, TL=2.0Nm).
Embodiment
The present invention is described in detail with specific embodiment below in conjunction with the accompanying drawings.The present embodiment is with technical solution of the present invention
Premised on implemented, but protection scope of the present invention is not limited to following embodiments.
It is used as the specific embodiment of the present invention, a kind of permagnetic synchronous motor no electrolytic capacitor inversion of the invention
Device is as shown in figure 1, system hardware includes：AC power AC, inductance L, uncontrollable rectifier bridge BR, thin-film capacitor C, power model, forever
Magnetic-synchro motor.
Software computing unit includes：Motor speed calculates unit, CLARK converter units, PARK converter units, speed regulation
Device unit, current regulator, PARK inverse transformation blocks, SVPWM computing units etc..
Different from the microfarad of capacitance in the conventional inverter hundreds of even electrochemical capacitor of thousands of microfarads, film in present system
Electric capacity C capacitance only has tens microfarads, specifically, the capacitance of the thin-film capacitor C is less than 50 microfarads, it is more specifically, described thin
Membrane capacitance C capacitance is 20 μ F.
In addition, circuit inputs 220V/50Hz alternating current, the inductance L sizes used is 5mH.
There is provided a kind of electroless electricity as shown in Figure 2 for the starting control flow chart that the present invention is used in the electric motor starting stage
Hold the starting method of inverter permagnetic synchronous motor, comprise the following steps：
S11：Current acquisition sensor passes through sampled measurements to motor stator phase current iu、iv, and obtain the 3rd by calculating
Phase stator current iw=-iu-iv.Measure the DC bus-bar voltage V at thin-film capacitor endc, calculate average voltage Vavg, calculate ratio
Coefficient k=Vc/Vavg, proportionality coefficient k is a variable, with DC bus-bar voltage VcIt is directly proportional.
S12：Position sensor detects the rotor position angle θ of motor, and the machinery that motor is obtained to rotor position angle θ differential turns
Fast ωr=d θ/dt.
S13：It is supplied to Park conversion and its inverse transformation to be calculated rotor position angle θ, by motor stator phase current iu、
iv、iwThe d axis components i of motor stator electric current is obtained by carrying out CLARK conversion and PARK conversiondWith q axis components iq。
S14：Speed regulator adjusts control, given rotating speed ω using PIsetInputted as speed regulator, above-mentioned steps
Obtained motor actual speed ω is calculated in S12rFed back as speed regulator, speed regulator is output as stator current is。
D shaft current reference quantities are setIt is speed regulator output and control with changed scale coefficient k product to set q shaft currents reference quantity：
S15：Current regulator adjusts control, d, q shaft current reference quantity using PIFor the defeated of current regulator
Enter d, q shaft current component i for calculating and obtaining in amount, above-mentioned steps S13d、iqIt is used as the feedback of current regulator, current regulator
Output as d, q coordinate system component of voltage Vd、Vq。
S16：The V of the component of voltaged、VqAccording to rotor position angle θ, α, β rectangular co-ordinate are calculated by PARK inverse transformations
The component of voltage V of systemα、Vβ。
S17：The component of voltage Vα、VβSix IGBT power tubes in power model are calculated by SVPWM computing units to lead
Logical dutycycle, produces corresponding 6 road pwm signal.
S18：The logical drive permagnetic synchronous motor work that power model is provided by 6 road pwm signals.
The present invention combines the output of speed regulator with d-c bus voltage value, and q is calculated by step S14 method
Shaft current set-pointThis method can improve the starting torque of motor, while effectively reducing the starting current of inverter.
Wherein, permagnetic synchronous motor in d, q shaft voltage equation is in vector controlled of the embodiment of the present invention：
D, q axle flux linkage equations are：
The electromagnetic torque equation of permagnetic synchronous motor is：
Tem=pn(ψdiq-ψqid) (3)
In formula (1), (2), (3)：Vd、Vq、id、iqRespectively d, q shaft voltage and electric current；RsFor stator resistance；Ld、LqRespectively
For d, q axle inductance；ψd、ψqRespectively d, q axle magnetic linkage；ψfFor permanent magnet flux linkage；ω is angular rate；pnFor motor number of pole-pairs；Tem
For electromagnetic torque.
The equation of motion of permagnetic synchronous motor is：
In formula：J is the rotary inertia of rotor；ωrFor mechanical angular speed；B is viscous damping coefficient；TLTurn for load
Square.
The parameter of the present embodiment permagnetic synchronous motor is as follows：Rated direct voltage 310V；Rated power 1200W；Mechanical angle
Speed omegar600~12000r/min of excursion；Number of pole-pairs pnFor 2；Stator resistance RsFor 0.65 Ω；Stator d-axis inductance Ld
For 8.8mH；Stator quadrature axis inductance LqFor 14.4mH；Back emf coefficient Ke is 26.5V/krpm；The rotary inertia J of rotor is
7.6*10-4kg*m2；Electric motor starting load torque TLIt is set to 1.0~2.0Nm.
The speed control adjusted based on PI is used in start-up program of the embodiment of the present invention, stator electricity is calculated as follows
Flow is：
K in formulapRepresent speed control proportional gain factor, kiRepresent speed control integration gain factor, ωrFor motor
Actual speed, ωsetFor the given speed of motor, τ represents the time, and t represents current time.
In order to prove the superiority of starting method of the present invention, the present embodiment is on MATLAB platforms using two kinds of differences
Calculation formula calculate d, q shaft current set-point
The first computational methods is identical with the method used in big capacitance electrochemical capacitor inverter in the prior art, d, q axle
Given value of current valueI is exported by speed regulatorsIt is calculated as follows with angle of torsion β：
Second of computational methods, d, q shaft current set-pointCalculate, adjusted by speed by thinking proposed by the present invention
Device exports isMultiply a proportionality coefficient k to draw：
U in formulacFor the DC bus-bar voltage at thin-film capacitor end, uavgFor busbar voltage average value, k is one and started
The proportionality coefficient changed in journey, with DC bus-bar voltage ucIt is directly proportional.
Formula (6) is respectively adopted in the embodiment of the present invention or formula (7) is calculatedThe different speed regulator by setting
Proportional gain factor kpWith different load torque values TL, to electric motor starting speed, q shaft currents i under different start-up programsq, bus
Voltage Vc, AC input current Iac, load starting ability contrasted.As table 1 below gives the ratio of five kinds of start-up programs
Gain coefficient kp, load torque TLWith AC input current IacPeak value.The integration of five kinds of start-up program PI speed regulators increases
Beneficial coefficient ki0.1 is all taken, integration period all takes 0.001s.The saturation value of the present embodiment medium velocity adjuster is set to 15A, hardware system
Excessively stream of uniting threshold value is 18A, the given speed ω of motorsetFor 2000r/min.
The contrast of 1 five kinds of start-up programs of table
Embodiment scheme 1, scheme 2, scheme 3 and the starting side used in the prior art in big capacitance electrochemical capacitor inverter
Method is identical, and d, q shaft current set-point calculation basis are formula (6)；And embodiment scheme 4, scheme 5 employ it is proposed by the present invention
Start-up program, d, q shaft current set-point calculation basis is formula (7).If Fig. 3~Fig. 6 is respectively the corresponding starting of five kinds of schemes
Characteristic curve.When scheme 1, scheme 2, scheme 3 are calculated using formula (6), angle of torsion β takes 0 °,
For no electrolytic capacitor inverter, thin-film electro has one several milliseconds of charging process when system is just upper electric, therefore
Motor is all assumed to be what is started since 0.02s in Fig. 3~Fig. 6 five kinds of schemes, and the at this moment charging of conductive film electric capacity is
Complete, terminal voltage has been stablized in 310V.
Such as the starting characteristic curve that Fig. 3 is scheme 1, the load torque T of scheme 1LFor 1.0Nm, speed regulator ratio increases
Beneficial coefficient kp0.006 is taken, due to rotor inertia (J=7.6*10-4kg*m2) effect, it is one that the speed of motor, which rises,
The process gradually risen, and given speed ωsetFor 2000r/min, scheme 1 calculates q shaft current set-points using formula (6)
The q shaft currents i of systemq14.8A is just risen in the 0.002s of (0.02s~0.022s), correspondingly AC input current
IacAlso in 0.002s on be flushed to peak value 19.3A.The starting current of scheme 1 has exceeded hardware excessively stream threshold value 18A.The motor of scheme 1
It is stable in given rotating speed 2000r/min by 0.55s.
In order to reduce the starting current of system, an effective method is appropriate reduction speed regulator proportional gain factor
kp, scheme 2 is by proportional gain factor k on the basis of scheme 1pReduce obtained scheme.Such as the starting characteristic that Fig. 4 is scheme 2
Curve, load torque TLIt is still 1.0Nm, but proportional gain factor kpIt is reduced to 0.004.The q shaft currents i of systemq(0.02s~
9.0A, input current I are only risen in 0.002s 0.022s)acIt is that peak value 14.5A is reached near 0.0145s.Scheme 2
By reducing speed regulator proportional gain factor kp, starting current peak value is fallen below into 14.5A from 19.3A, system is so met
The requirement of system hardware.The dynamic response time of the motor of scheme 2 has increased slightly compared with scheme 1, stable in given rotating speed by 0.75s
2000r/min。
In order to investigate reduction proportional gain factor kpInfluence to load starting ability, increases negative on the basis of scheme 2
Set torque obtains scheme 3.Such as the starting characteristic curve that Fig. 5 is scheme 3, proportional gain factor kpFor 0.004, load torque TLIncrease
1.5Nm is added to, at this moment starting current peakedness ratio scheme 2 is significantly increased, peak value 16.5A is reached at 0.06s, close to hardware excessively stream
Threshold value 18A.The motor dynamics response time of scheme 3 further increases, just stable in given rotating speed 2000r/min by 0.80s.
Proportional gain factor kpFor 0.004 when, load torque TLWhen continuing to increase to 2.0Nm, motor can not be started smoothly.
Integration scenario 1,2,3 is visible, and prior art calculates q shaft current set-points by formula (6)Need according to load
Situation continues to optimize proportional gain factor kpValue, is only possible to excessively stream not only occur but also obtains larger starting torque, and this gives system
Control adds difficulty.
Scheme 4 is starting method of the invention, and load torque and proportional gain factor are identical with scheme 1, load torque TL
For 1.0Nm, speed regulator proportional gain factor kp0.006 is taken, q shaft current set-points are calculated by formula (7)If Fig. 6 is side
The starting characteristic curve of case 4.Because q shaft current set-pointsDetermined simultaneously with busbar voltage by speed regulator output, q axles electricity
Flow iq15.1A, AC input current I are just risen in the 0.005s of (0.02s~0.025s)acJust rise near 0.083s
To peak value 6.5A, this is greatly reduced than the peak value 19.3A of scheme 1.And the dynamic responding speed of the motor of scheme 4 is suitable with scheme 1,
It is stable in given rotating speed 2000r/min at 0.6s.
In order to further investigate the load starting ability of the present invention, continue increase load torque on the basis of scheme 4 and obtain
To scheme 5.The speed regulator proportional gain factor k of scheme 5pTake 0.006, load torque TLFor 2.0Nm.As Fig. 7 is scheme 5
Starting characteristic curve, input current IacPeak value 10.1A is reached near 0.4s, hardware excessively stream threshold value 18A is significantly less than；Motor exists
It is stable in given rotating speed near 0.8s.Importantly, using with the identical proportional gain factor k of scheme 4p, load torque TLIncrease
Can also smoothly it be started to 2.0N motors greatly；And for scheme 3, as load torque TLWhen increasing to 2.0Nm, motor can not be suitable
Profit is started.Prove present invention a further advantage in addition to it can reduce starting current：Started with the bringing onto load more stronger than scheme 1,2,3
Ability.
Five kinds of start-up programs of summary are visible, using the starting method of the present invention, calculate q shaft currents by formula (7) and give
Definite valueTake same proportional gain factor kp, system start electric current can be substantially reduced, while having stronger load starting
Ability.
Scheme 4 described above, scheme 5 are the preferred embodiment of the present invention, it is noted that for the general of the art
For logical technical staff, under the premise without departing from the principles of the invention, some improvements and modifications can also be made, these improve and
Retouching is also considered as protection scope of the present invention.
Claims (3)
1. a kind of starting method of no electrolytic capacitor inverter permagnetic synchronous motor, system hardware includes：AC power AC, inductance
L, uncontrollable rectifier bridge BR, thin-film capacitor C, power model, permagnetic synchronous motor, and software computing unit include：Motor speed
Computing unit, CLARK converter units, PARK converter units, speed regulator unit, current regulator, PARK inverse transformation blocks,
SVPWM computing units, it is characterised in that comprise the following steps：
S11：Current acquisition sensor passes through sampled measurements to motor stator phase current iu、iv, and determined by calculating acquisition third phase
Electron current iw=-iu-iv, measure the DC bus-bar voltage V at the thin-film capacitor endc, calculate average voltage Vavg, calculate ratio
Coefficient k=Vc/Vavg, proportionality coefficient k is a variable, with DC bus-bar voltage VcIt is directly proportional；
S12：Position sensor detects the rotor position angle θ of motor, and the mechanical separator speed ω of motor is obtained to rotor position angle θ differentialr
=d θ/dt；
S13：It is supplied to the PARK converter units and the PARK inverse transformation blocks to be calculated rotor position angle θ, by electricity
Machine stator phase current iu、iv、iwThe d axis components i of motor stator electric current is obtained by carrying out CLARK conversion and PARK conversiondAnd q
Axis component iq；
S14：Speed regulator adjusts control, given rotating speed ω using PIsetInputted as speed regulator, in above-mentioned steps S12
Calculate obtained motor actual speed ωrFed back as speed regulator, speed regulator is output as stator current is, d is set
Shaft current reference quantityIt is speed regulator output and control with changed scale coefficient k product to set q shaft currents reference quantity：
S15：Current regulator adjusts control, d, q shaft current reference quantity using PIFor the input of current regulator
Obtained d, q shaft current component i is calculated in amount, above-mentioned steps S13d、iqAs the feedback of current regulator, current regulator
Export the component of voltage V as d, q coordinate systemd、Vq；
S16：The V of the component of voltaged、VqAccording to rotor position angle θ, α, β rectangular coordinate system are calculated by PARK inverse transformations
Component of voltage Vα、Vβ；
S17：The component of voltage Vα、VβCalculate what six IGBT power tubes in power model were turned on by SVPWM computing units
Dutycycle, produces corresponding 6 road pwm signal；
S18：The logical drive permagnetic synchronous motor work that the power model is provided by 6 road pwm signals.
2. a kind of starting method of no electrolytic capacitor inverter permagnetic synchronous motor according to claim 1, its feature exists
Combine in by the output of speed regulator with d-c bus voltage value, q shaft current set-points are calculated by step S14 methodThis method can improve the starting capability of motor, while effectively reducing the starting current of inverter.
3. a kind of starting method of no electrolytic capacitor inverter permagnetic synchronous motor according to claim 1, its feature exists
The thin-film capacitor C capacitance described in inverter is less than 50 microfarads.
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Cited By (7)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| CN107689761A (en) * | 2017-10-26 | 2018-02-13 | 哈尔滨工业大学 | Damping control method in no electrolytic capacitor permanent magnet synchronous electric air conditioner drive system |
| CN108768236A (en) * | 2018-06-07 | 2018-11-06 | 深圳市道通智能航空技术有限公司 | Motor control method, device, electron speed regulator and unmanned vehicle |
| CN108988717A (en) * | 2018-07-27 | 2018-12-11 | 奥克斯空调股份有限公司 | A kind of driving method, device and air conditioner |
| CN109245629A (en) * | 2018-10-09 | 2019-01-18 | 佛山市顺德区和而泰电子科技有限公司 | The FOC control system of no electrolytic capacitor magneto |
| WO2019043126A1 (en) * | 2017-08-31 | 2019-03-07 | Eaton Intelligent Power Limited | System and method for stability control in adjustable speed drive with dc link thin film capacitor |
| CN110601623A (en) * | 2019-07-30 | 2019-12-20 | 广东工业大学 | Method for reducing DC bus voltage ripple amplitude of permanent magnet synchronous motor frequency converter |
| CN113691177A (en) * | 2021-08-27 | 2021-11-23 | 哈尔滨工业大学 | Bus voltage control method for driving system of permanent magnet synchronous motor without electrolytic capacitor |
Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US8872452B2 (en) * | 2012-06-08 | 2014-10-28 | Hyundai Mobis Co., Ltd. | Method for operating motor of motor-driven power steering |
| CN104953916A (en) * | 2015-07-14 | 2015-09-30 | 东南大学 | Novel speed controller based on speed regulating system of permanent magnet synchronous motor |
| CN105162381A (en) * | 2015-08-24 | 2015-12-16 | 华中科技大学 | Electrolytic capacitor-free variable frequency driving control system and control method based on proportional resonant (PR) adjustment |
| CN106059419A (en) * | 2016-06-22 | 2016-10-26 | 广东工业大学 | Permanent magnet synchronous motor parallel vector control scheme |
-
2017
- 2017-04-27 CN CN201710289775.9A patent/CN106982022A/en not_active Withdrawn
Patent Citations (4)
| Publication number | Priority date | Publication date | Assignee | Title |
|---|---|---|---|---|
| US8872452B2 (en) * | 2012-06-08 | 2014-10-28 | Hyundai Mobis Co., Ltd. | Method for operating motor of motor-driven power steering |
| CN104953916A (en) * | 2015-07-14 | 2015-09-30 | 东南大学 | Novel speed controller based on speed regulating system of permanent magnet synchronous motor |
| CN105162381A (en) * | 2015-08-24 | 2015-12-16 | 华中科技大学 | Electrolytic capacitor-free variable frequency driving control system and control method based on proportional resonant (PR) adjustment |
| CN106059419A (en) * | 2016-06-22 | 2016-10-26 | 广东工业大学 | Permanent magnet synchronous motor parallel vector control scheme |
Non-Patent Citations (1)
| Title |
|---|
| 尹泉: "无电解电容逆变器永磁同步电机驱动系统控制研究", 《电气传动》 * |
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| US10333444B2 (en) | 2017-08-31 | 2019-06-25 | Eaton Intelligent Power Limited | System and method for stability control in adjustable speed drive with DC link thin film capacitor |
| CN107689761A (en) * | 2017-10-26 | 2018-02-13 | 哈尔滨工业大学 | Damping control method in no electrolytic capacitor permanent magnet synchronous electric air conditioner drive system |
| CN107689761B (en) * | 2017-10-26 | 2019-11-08 | 哈尔滨工业大学 | Damping control method in no electrolytic capacitor permanent magnet synchronous electric air conditioner drive system |
| CN108768236A (en) * | 2018-06-07 | 2018-11-06 | 深圳市道通智能航空技术有限公司 | Motor control method, device, electron speed regulator and unmanned vehicle |
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| CN109245629A (en) * | 2018-10-09 | 2019-01-18 | 佛山市顺德区和而泰电子科技有限公司 | The FOC control system of no electrolytic capacitor magneto |
| CN110601623A (en) * | 2019-07-30 | 2019-12-20 | 广东工业大学 | Method for reducing DC bus voltage ripple amplitude of permanent magnet synchronous motor frequency converter |
| CN113691177A (en) * | 2021-08-27 | 2021-11-23 | 哈尔滨工业大学 | Bus voltage control method for driving system of permanent magnet synchronous motor without electrolytic capacitor |
| CN113691177B (en) * | 2021-08-27 | 2023-10-27 | 哈尔滨工业大学 | Bus voltage control method for electrolytic capacitor-free permanent magnet synchronous motor driving system |
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