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Search Results (528)

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Keywords = permanent magnet synchronous machine

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23 pages, 5302 KiB  
Article
A Novel Method for Automatically and Accurately Diagnosing Demagnetization Fault in Direct-Drive PMSMs Using Three PNNs
by Yiyong Xiong, Jinghong Zhao, Sinian Yan, Kun Wei and Haiwen Zhou
Appl. Sci. 2024, 14(24), 11943; https://doi.org/10.3390/app142411943 - 20 Dec 2024
Viewed by 293
Abstract
Direct-drive permanent magnet synchronous machines (DDPMSMs) have recently become an ideal candidate for applications such as military, robotics, electric vehicles, etc. These machines eliminate the need for a transmission mechanism and excitation coil circuits, which enhances the system’s overall efficiency and decreases the [...] Read more.
Direct-drive permanent magnet synchronous machines (DDPMSMs) have recently become an ideal candidate for applications such as military, robotics, electric vehicles, etc. These machines eliminate the need for a transmission mechanism and excitation coil circuits, which enhances the system’s overall efficiency and decreases the likelihood of failures. However, it may incur demagnetization faults. Due to the characteristic of having a large number of pole pairs, this type of machine exhibits numerous demagnetization fault modes, which poses a challenge in locating demagnetization faults. This paper proposed a probabilistic neural network (PNN)-based diagnostic system to detect and locate demagnetization faults in DDPMSMs, using information obtained through three toroidal-yoke-type search coils arranged at the bottom of the stator slot. A rotor partition method is proposed to solve the problem of demagnetization fault location difficulty caused by various fault modes. Demagnetization fault location is achieved by sequentially diagnosing the condition of each partition of permanent magnets. Three demagnetization fault identified signals (DFISs) are constructed by the voltage of the three toroidal-yoke coils, which are used as inputs of PNNs. Three PNNs have been designed to map the extracted features and their corresponding types of demagnetization faults. The database for training and testing the PNNs is generated from a DDPMSM with different demagnetization conditions and different operating conditions, which are established through an experimentally validated mathematical model, an FEM model, and experiments. The simulation and experimental test results showed that the accuracy in diagnosing the location of the demagnetization fault is 99.2% when the demagnetization severity is 10%, which demonstrates the effectiveness of the proposed three PNN-based diagnostic approach. Full article
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Figure 1

Figure 1
<p>Placement scheme of toroidal-yoke-search coil.</p>
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<p>The waveforms of <span class="html-italic">SI</span><sub>m−2</sub>. (<b>a</b>) Mode 1 to 6. (<b>b</b>) Modes 6, 7, and 8.</p>
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<p>The waveforms of <span class="html-italic">SI</span><sub>m−2</sub> under Mode 7 with 100% demagnetization and Mode 8 with 50% demagnetization.</p>
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<p>Normalized <span class="html-italic">SI</span><sub>m</sub> under six different demagnetization fault modes.</p>
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<p>The waveforms of normalized <span class="html-italic">SI</span><sub>a1-2</sub>. (<b>a</b>) Mode 6H, Mode 7H, Mode 6D, Mode 8H, and Mode 8D. (<b>b</b>) Mode 7D and Mode 8H.</p>
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<p>The waveforms of <span class="html-italic">SI</span><sub>a2-2</sub> under Cas 7D or Mode 8H.</p>
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<p>Corresponding relationship between the pole pair number and the electric cycle number of DFISs.</p>
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<p><span class="html-italic">SI</span><sub>m</sub> under different loading conditions of the machine.</p>
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<p><span class="html-italic">SI</span><sub>m</sub> under various speeds of the machine.</p>
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<p>The process for automatically diagnosing demagnetization faults using three PNNs.</p>
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<p>Architecture of the PNN.</p>
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<p>The training results of the three PNNs. (<b>a</b>) The first PNN. (<b>b</b>) The second PNN. (<b>c</b>) The third PNN.</p>
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<p>The testing results of the three PNNs. (<b>a</b>) The first PNN. (<b>b</b>) The second PNN. (<b>c</b>) The third PNN.</p>
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<p>Experimental setup.</p>
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<p>The experimental results of the voltage of TYC1, TYC2, and SI<sub>m</sub> under healthy conditions. (<b>a</b>) The voltage waveform of TYC1 and TYC2. (<b>b</b>) The voltage waveform of <span class="html-italic">SI</span><sub>m</sub>.</p>
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<p>The experimental results of residual voltage of under fault3. (<b>a</b>) The residual voltage of TYC1, TYC2, and TYC3. (<b>b</b>) The residual voltage waveform of <span class="html-italic">S</span><sub>m</sub> and <span class="html-italic">S</span><sub>a1</sub>.</p>
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18 pages, 1356 KiB  
Article
Permanent Magnets in Sustainable Energy: Comparative Life Cycle Analysis
by Svetlana Orlova and Anton Rassõlkin
Energies 2024, 17(24), 6384; https://doi.org/10.3390/en17246384 - 18 Dec 2024
Viewed by 433
Abstract
This study addresses the environmental challenges associated with high-performance rare-earth magnets, particularly NdFeB, which are essential in green and digital technologies. By employing Life Cycle Assessment (LCA) with openLCA software, we evaluate the environmental impacts across the life cycles of ferrite, NdFeB, and [...] Read more.
This study addresses the environmental challenges associated with high-performance rare-earth magnets, particularly NdFeB, which are essential in green and digital technologies. By employing Life Cycle Assessment (LCA) with openLCA software, we evaluate the environmental impacts across the life cycles of ferrite, NdFeB, and MnAlC magnets, focusing on extraction, processing, and recycling. Various studies have explored different aspects of the LCA of NdFeB magnets, focusing on production methods, recycling processes, and the environmental impacts of different rare-earth sources. A comparative LCA highlights the significant environmental footprint of rare-earth magnets, underscoring the role of functional unit selection: when assessed per unit of energy density, the environmental impact of NdFeB magnets aligns more closely with alternatives. Methodological issues such as data quality, choice of functional units, and system complexity affect LCA accuracy, as inconsistencies in data or scope led to potential distortions in environmental assessments. This research also explores manganese-based magnets as viable alternatives to reduce reliance on rare-earth materials. Legislative initiatives, including the EU’s Ecodesign Directive and Critical Raw Materials Act, support sustainable management practices to ensure reliable material supply while promoting environmental protection. This paper highlights the importance of sustainable magnetic materials, emphasizing the need for interdisciplinary research to balance technological efficiency and environmental impact, especially as rare-earth magnet demand rises with the transition to renewable energy sources. Full article
(This article belongs to the Section A: Sustainable Energy)
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<p>Projected NdFeB magnet consumption by application segment (2022–2032) [<a href="#B12-energies-17-06384" class="html-bibr">12</a>].</p>
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<p>Magnetic parameters of permanent magnets (Nd<sub>2</sub>Fe<sub>14</sub>B [<a href="#B14-energies-17-06384" class="html-bibr">14</a>] AlNiCo [<a href="#B15-energies-17-06384" class="html-bibr">15</a>] SrFe<sub>12</sub>O<sub>19</sub> [<a href="#B16-energies-17-06384" class="html-bibr">16</a>], BaFe<sub>12</sub>O<sub>19</sub> [<a href="#B17-energies-17-06384" class="html-bibr">17</a>], SmCo<sub>5</sub>, [<a href="#B18-energies-17-06384" class="html-bibr">18</a>] Sm<sub>2</sub>Co<sub>17</sub> [<a href="#B19-energies-17-06384" class="html-bibr">19</a>], and MnAlC [<a href="#B20-energies-17-06384" class="html-bibr">20</a>]).</p>
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<p>Ferrite permanent magnet production process [<a href="#B21-energies-17-06384" class="html-bibr">21</a>].</p>
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<p>NdFeB permanent magnet production process [<a href="#B25-energies-17-06384" class="html-bibr">25</a>].</p>
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<p>Environmental, resource depletion, and human health impact comparison of NdFeB, ferrite, and MnAlC across various impact categories for functional unit 1 kg of mass.</p>
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<p>Environmental, resource depletion, and human health impact comparison of NdFeB, ferrite, and MnAlC across various impact categories for functional unit 1 kJ/m<sup>3</sup> of maximum energy product.</p>
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15 pages, 8380 KiB  
Article
Design and Analysis of a Low Torque Ripple Permanent Magnet Synchronous Machine for Flywheel Energy Storage Systems
by Yubo Sun, Zhenghui Zhao and Qian Zhang
Energies 2024, 17(24), 6337; https://doi.org/10.3390/en17246337 - 16 Dec 2024
Viewed by 381
Abstract
Flywheel energy storage systems (FESS) are technologies that use a rotating flywheel to store and release energy. Permanent magnet synchronous machines (PMSMs) are commonly used in FESS due to their high torque and power densities. One of the critical requirements for PMSMs in [...] Read more.
Flywheel energy storage systems (FESS) are technologies that use a rotating flywheel to store and release energy. Permanent magnet synchronous machines (PMSMs) are commonly used in FESS due to their high torque and power densities. One of the critical requirements for PMSMs in FESS is low torque ripple. Therefore, a PMSM with eccentric permanent magnets is proposed and analyzed in this article to reduce torque ripple. Cogging torque, a significant contributor to torque ripple, is investigated by a combination of finite element analysis and the analytical method. An integer-slot distribution winding structure is adopted to reduce vibration and noise. Moreover, the effects of eccentric permanent magnets and harmonic injection on the cogging torque are analyzed and compared. In addition, the electromagnetic performance is analyzed, and the torque ripple is found to be 3.1%. Finally, a prototype is built and tested, yielding a torque ripple of 3.9%, to verify the theoretical analysis. Full article
(This article belongs to the Special Issue Energy, Electrical and Power Engineering: 3rd Edition)
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Figure 1
<p>Topology of proposed PMSM.</p>
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<p>Winding connection.</p>
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<p>Analysis model of surface-mounted PMSM.</p>
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<p>Bread-type eccentric permanent magnet.</p>
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<p>Influence of eccentricity on torque performance.</p>
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<p>Cogging torque of PMSM with different permanent magnets.</p>
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<p>Air gap magnetic densities of PMSM with different permanent magnets. (<b>a</b>) Radial air gap magnetic densities. (<b>b</b>) Tangential air gap magnetic densities. (<b>c</b>) Harmonic order.</p>
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<p>Cogging torque contribution of different harmonics. (<b>a</b>) PMSM with original permanent magnets. (<b>b</b>) PMSM with eccentric permanent magnets.</p>
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<p>Permanent magnet with third harmonic injection.</p>
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<p>Cogging torque of PMSM with harmonic injection. (<b>a</b>) Effect of harmonic injection. (<b>b</b>) Contribution of harmonics.</p>
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<p>Load electromagnetic performance. (<b>a</b>) Magnetic field line. (<b>b</b>) Magnetic flux density.</p>
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<p>Back electromotive force of PMSM.</p>
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<p>Torque performance of PMSM. (<b>a</b>) Cogging torque. (<b>b</b>) Torque.</p>
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<p>Vibration acceleration of PMSM with different permanent magnets.</p>
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<p>Prototype.</p>
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<p>Experimental platform.</p>
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<p>Vibration and noise test platform.</p>
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<p>Comparison of experimental and simulated results. (<b>a</b>) Back electromotive force of prototype. (<b>b</b>) Comparison of back electromotive force coefficient.</p>
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<p>Experimental results. (<b>a</b>) Torque. (<b>b</b>) Vibration acceleration.</p>
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27 pages, 13815 KiB  
Article
Unconventional Structures of Asynchronous Motors with Two Stators and Single-Rotor Radial Air Gaps in the Context of Their Applicability Assessment
by Mihail-Florin Stan, Iulian Bancuta, Elena-Otilia Virjoghe, Adela-Gabriela Husu and Cosmin Cobianu
Energies 2024, 17(24), 6237; https://doi.org/10.3390/en17246237 - 11 Dec 2024
Viewed by 350
Abstract
The fundamental idea underlying the research presented in this paper was the desire to use less magnetically charged areas of the general construction of induction machines by increasing the active working surface by interposing a new internal stator armature. This results in a [...] Read more.
The fundamental idea underlying the research presented in this paper was the desire to use less magnetically charged areas of the general construction of induction machines by increasing the active working surface by interposing a new internal stator armature. This results in a new air gap and foreshadows the advantage of increasing the torques developed by the motor considered, compared to the equivalent standard motor, at the same volume of iron. The following research-validation methods were followed: theoretical studies (analytical simulation and FEM), an experimental model (prototype), and testing on the experimental platform. We recall obtaining solid conclusions on the technological construction, functional and energy characteristics, as well as superior performances of over 50% regarding electromagnetic torques compared to the equivalent classic version. The prototype of this type of machine was surprising due to the ease with which the rotor can be rotated, highlighting the reduced inertia. In conclusion, concerning the problem addressed and the objectives pursued, the research had, in essence, an applied and experimental nature. The recent development of permanent-magnet synchronous motor constructions has led to the concept of creating such motors in the constructive configuration specified in the paper (two stators and two radial air gaps). Full article
(This article belongs to the Section F: Electrical Engineering)
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Figure 1
<p>(<b>a</b>) Intermediate rotor with a three-phase winding; (<b>b</b>) Intermediate rotor with cage windings; (<b>c</b>) Tandem motor with two rotors.</p>
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<p>The connection scheme of the stator windings in the asynchronous version.</p>
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<p>The rotor cage. (<b>a</b>) The solution with a row of bars with semi-open rotor notches; (<b>b</b>) The solution with two cages separated by an isthmus, with closed notches.</p>
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<p>The variant with closed notches. (<b>a</b>) Distribution of equipotential in geometry with closed notches and rotor isthmus; (<b>b</b>) Effect of notch closure on machine reactance.</p>
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<p>Constructive variants with different numbers of bars: (<b>a</b>) Variant with 20 bars; (<b>b</b>) Variant with 28 bars.</p>
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<p>Arrangement of rotor notches: (<b>a</b>) The case of the 7 mm bar; (<b>b</b>) The case of the 9 mm bar.</p>
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<p>Examples of two types of notches: small (<b>A</b>) and large (<b>B</b>).</p>
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<p>(<b>a</b>) Transverse geometry; (<b>b</b>) The discretization network.</p>
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<p>(<b>a</b>) Magnetic flux at idle operation; (<b>b</b>) Magnetic induction at idle operation.</p>
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<p>(<b>a</b>) Magnetic induction in the outer space; (<b>b</b>) Magnetic induction in the inner space.</p>
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<p>(<b>a</b>) Magnetic flux at idle operation; (<b>b</b>) Magnetic induction at idle operation.</p>
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<p>(<b>a</b>) Magnetic induction in the outer space; (<b>b</b>) Magnetic induction in the inner space.</p>
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<p>(<b>a</b>) Magnetic flux at idle operation; (<b>b</b>) Magnetic induction at idle operation.</p>
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<p>(<b>a</b>) Magnetic induction in the outer space; (<b>b</b>) Magnetic induction in the inner space.</p>
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<p>Connection diagram for Test Report 1.</p>
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<p>Line voltage at idle [V]—No load current [A] characteristic.</p>
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<p>Power absorbed at idle [W]—Line voltage at idle [V] characteristic.</p>
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<p>Power factor at idle—Line voltage at idle [V] characteristic.</p>
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<p>Short-circuit phase current [A]—Line voltage at short-circuit operation [V] characteristic.</p>
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<p>Power absorbed at short circuit [W]—Line voltage at short-circuit [V] characteristic.</p>
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<p>Short circuit current calculated [A]—Line voltage at short-circuit [V] characteristic.</p>
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<p>Connection diagram for Test Report 2.</p>
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<p>Power factor at idle—Line voltage at idle [V] characteristic.</p>
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<p>Power absorbed at idle [W]—Line voltage at idle [V] characteristic.</p>
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<p>Line voltage at idle [V]—No-load current [A] characteristic.</p>
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<p>Short circuit current calculated [A]—Line voltage at short-circuit operation [V] characteristic.</p>
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<p>Power absorbed at short-circuit [W]—Line voltage at short-circuit [V] characteristic.</p>
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<p>Short-circuit phase current [A]—Line voltage at short-circuit [V] characteristic.</p>
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<p>The connection diagram develops torques in the same direction.</p>
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<p>The connection diagram develops torques in the opposite direction.</p>
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<p>Power factor at idle—Line voltage at idle [V] characteristic.</p>
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<p>Power absorbed at idle [W]—Line voltage at idle [V] characteristic.</p>
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<p>Line voltage at idle [V]—No-load current [A] characteristic.</p>
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<p>Short circuit current calculated [A]—Line voltage at short-circuit operation [V] characteristic.</p>
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<p>Power absorbed at short-circuit [W]—Line voltage at short-circuit [V] characteristic.</p>
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<p>Short circuit current calculated [A]—Line voltage at short-circuit [V] characteristic.</p>
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<p>The connection diagram in load operation.</p>
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<p>Power factor—Useful power [W] characteristic.</p>
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<p>Slip [%]—Useful power [W] characteristic.</p>
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<p>Yield [%]—Useful power [W] characteristic.</p>
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<p>Absorbed current [A]—Useful power [W] characteristic.</p>
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35 pages, 15787 KiB  
Review
Recent Developments and Trends in High-Performance PMSM for Aeronautical Applications
by Chendong Liao, Nicola Bianchi and Zhuoran Zhang
Energies 2024, 17(23), 6199; https://doi.org/10.3390/en17236199 - 9 Dec 2024
Viewed by 523
Abstract
Permanent magnet synchronous machines (PMSMs) have been widely used in various applications such as robotics, electric vehicles, and aerospace due to their fast dynamic response, high-power/torque density, and high efficiency. These features make them attractive candidates for aeronautical applications, where the weight and [...] Read more.
Permanent magnet synchronous machines (PMSMs) have been widely used in various applications such as robotics, electric vehicles, and aerospace due to their fast dynamic response, high-power/torque density, and high efficiency. These features make them attractive candidates for aeronautical applications, where the weight and volume of onboard systems are critically important. This paper aims to provide an overview of recent developments in PMSMs. Key design considerations for aeronautical PMSMs across different applications are highlighted based on the analysis of industrial cases and research literature. Additionally, emerging techniques that are vital in enhancing the performance of aeronautical PMSMs are discussed. Full article
(This article belongs to the Special Issue Energy, Electrical and Power Engineering: 3rd Edition)
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<p>The No-bleed architecture of the MEA Boeing 787 Dreamliner [<a href="#B4-energies-17-06199" class="html-bibr">4</a>].</p>
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<p>E-fan developed by Airbus.</p>
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<p>Classification of aircraft electric propulsion architectures [<a href="#B4-energies-17-06199" class="html-bibr">4</a>].</p>
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<p>Full-scale 1 MW motor drive demonstrator for turbo-electric propulsion developed by MIT [<a href="#B12-energies-17-06199" class="html-bibr">12</a>].</p>
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<p>Different PMSM topologies (<b>a</b>) interior PM (<b>b</b>) PM-assisted synchronous reluctance (<b>c</b>) interior PM outer rotor (OR) (<b>d</b>) surface-mounted PM linear (<b>e</b>) surface-mounted PM (<b>f</b>) surface-inset PM (<b>g</b>) surface-mounted Halbach PM array (<b>h</b>) surface-mounted PM OR (<b>i</b>) consequent pole surface-inset PM (<b>j</b>) surface-mounted PM axial flux.</p>
Full article ">Figure 5 Cont.
<p>Different PMSM topologies (<b>a</b>) interior PM (<b>b</b>) PM-assisted synchronous reluctance (<b>c</b>) interior PM outer rotor (OR) (<b>d</b>) surface-mounted PM linear (<b>e</b>) surface-mounted PM (<b>f</b>) surface-inset PM (<b>g</b>) surface-mounted Halbach PM array (<b>h</b>) surface-mounted PM OR (<b>i</b>) consequent pole surface-inset PM (<b>j</b>) surface-mounted PM axial flux.</p>
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<p>Maximum rotor linear velocity of PM motors for electric vehicles [<a href="#B31-energies-17-06199" class="html-bibr">31</a>,<a href="#B32-energies-17-06199" class="html-bibr">32</a>,<a href="#B33-energies-17-06199" class="html-bibr">33</a>,<a href="#B34-energies-17-06199" class="html-bibr">34</a>,<a href="#B35-energies-17-06199" class="html-bibr">35</a>,<a href="#B36-energies-17-06199" class="html-bibr">36</a>,<a href="#B37-energies-17-06199" class="html-bibr">37</a>,<a href="#B38-energies-17-06199" class="html-bibr">38</a>,<a href="#B39-energies-17-06199" class="html-bibr">39</a>,<a href="#B40-energies-17-06199" class="html-bibr">40</a>].</p>
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<p>Radial-axial magnetic flux path in hybrid excited PM machine [<a href="#B50-energies-17-06199" class="html-bibr">50</a>].</p>
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<p>Structure of electric-driven actuators (<b>a</b>) EHA [<a href="#B60-energies-17-06199" class="html-bibr">60</a>] (<b>b</b>) EMA [<a href="#B57-energies-17-06199" class="html-bibr">57</a>].</p>
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<p>The architecture of the three-stage wound-field synchronous SG.</p>
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<p>Typical dual-spool turbofan engine with integrated drive generator (IDG) [<a href="#B105-energies-17-06199" class="html-bibr">105</a>].</p>
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<p>Mechanically failed doubly-salient SG (airgap length = 0.7 mm) (<b>a</b>) rotor (<b>b</b>) stator.</p>
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<p>N3-X Aircraft with a Turboelectric Distributed Propulsion [<a href="#B130-energies-17-06199" class="html-bibr">130</a>].</p>
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<p>Evolution of the hybrid winding configuration [<a href="#B129-energies-17-06199" class="html-bibr">129</a>].</p>
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<p>Temperature dependence of (BH)max for (<b>a</b>) established permanent magnet (PM) materials compared with (<b>b</b>) emerging PM materials [<a href="#B136-energies-17-06199" class="html-bibr">136</a>].</p>
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<p>Temperature-dependent magnetic properties of Fe<sub>16</sub>N<sub>2</sub> low-temperature nitride foil and NdFeB magnets N40 and N52 [<a href="#B139-energies-17-06199" class="html-bibr">139</a>].</p>
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<p>Tested hysteresis loop of high-performance CoFe alloy 1j22.</p>
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<p>Core losses dependency on sheet thickness.</p>
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<p>Lightweight PM rotor made of composites [<a href="#B164-energies-17-06199" class="html-bibr">164</a>].</p>
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<p>Different heat sink designs realized by AM [<a href="#B177-energies-17-06199" class="html-bibr">177</a>].</p>
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<p>Cooling fins integrated with the stator core.</p>
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<p>Typical cooling techniques for high-power density electric machines.</p>
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<p>Schematic representation of Copper-Water heat pipe together with alternative wick constructions [<a href="#B194-energies-17-06199" class="html-bibr">194</a>].</p>
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41 pages, 7143 KiB  
Review
Overview of IoT Security Challenges and Sensors Specifications in PMSM for Elevator Applications
by Eftychios I. Vlachou, Vasileios I. Vlachou, Dimitrios E. Efstathiou and Theoklitos S. Karakatsanis
Machines 2024, 12(12), 839; https://doi.org/10.3390/machines12120839 - 22 Nov 2024
Viewed by 680
Abstract
The applications of the permanent magnet synchronous motor (PMSM) are the most seen in the elevator industry due to their high efficiency, low losses and the potential for high energy savings. The Internet of Things (IoT) is a modern technology which is being [...] Read more.
The applications of the permanent magnet synchronous motor (PMSM) are the most seen in the elevator industry due to their high efficiency, low losses and the potential for high energy savings. The Internet of Things (IoT) is a modern technology which is being incorporated in various industrial applications, especially in electrical machines as a means of control, monitoring and preventive maintenance. This paper is focused on reviewing the use PMSM in lift systems, the application of various condition monitoring techniques and real-time data collection techniques using IoT technology. In addition, we focus on different categories of industrial sensors, their connectivity and the standards they should meet for PMSMs used in elevator applications. Finally, we analyze various secure ways of transmitting data on different platforms so that the transmission of information takes into account possible unwanted instructions from exogenous factors. Full article
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<p>Flow diagram of the experimental setup [<a href="#B45-machines-12-00839" class="html-bibr">45</a>].</p>
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<p>Vibration measurements per ISO 10816-3.</p>
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<p>Vibration measurements per ISO 10816:8:2014 [<a href="#B52-machines-12-00839" class="html-bibr">52</a>].</p>
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<p>Point placement vibration sensors in PMSM [<a href="#B55-machines-12-00839" class="html-bibr">55</a>].</p>
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<p>Curve Temperature-Torque PMSM for different loads [<a href="#B56-machines-12-00839" class="html-bibr">56</a>].</p>
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<p>Position temperature sensors in IPMSM [<a href="#B57-machines-12-00839" class="html-bibr">57</a>].</p>
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<p>Installation of current sensors in PMSM for elevator systems: (<b>a</b>) stator windings [<a href="#B61-machines-12-00839" class="html-bibr">61</a>]; (<b>b</b>) distribution board [<a href="#B62-machines-12-00839" class="html-bibr">62</a>].</p>
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<p>Condition monitoring in elevator systems based on IoT [<a href="#B23-machines-12-00839" class="html-bibr">23</a>].</p>
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<p>Percentage of faults in the PMSM: (<b>a</b>) low voltage; (<b>b</b>) high voltage [<a href="#B71-machines-12-00839" class="html-bibr">71</a>].</p>
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<p>Negative sequence current with various load alternations [<a href="#B88-machines-12-00839" class="html-bibr">88</a>].</p>
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<p>Hilbert–Huang Transform spectrum: (<b>a</b>) 3000 rpm; (<b>b</b>) 6000 rpm [<a href="#B113-machines-12-00839" class="html-bibr">113</a>].</p>
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<p>Microscopic view of the bearing: (<b>a</b>) Healthy; (<b>b</b>) Damaged [<a href="#B138-machines-12-00839" class="html-bibr">138</a>].</p>
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<p>CWT time–frequency diagram: (<b>a</b>) bearing outer ring fault; (<b>b</b>) bearing inner ring fault [<a href="#B141-machines-12-00839" class="html-bibr">141</a>].</p>
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<p>Procedure for creating magnetic faults [<a href="#B191-machines-12-00839" class="html-bibr">191</a>]: (<b>a</b>) PMSM internal magnet structure; (<b>b</b>) demagnetization fault.</p>
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<p>The number of studied publications: (<b>a</b>) percentage distribution of topics in the reports investigated; (<b>b</b>) total publications per year.</p>
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<p>Flowchart of Modbus attacks [<a href="#B202-machines-12-00839" class="html-bibr">202</a>].</p>
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<p>Schematic diagram of Zigbee network in elevators [<a href="#B230-machines-12-00839" class="html-bibr">230</a>].</p>
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<p>Experimental setup for condition monitoring in elevator system.</p>
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<p>Proposed method for a dual system (wired and wireless) for fault diagnosis, condition monitoring and detection of security attacks on an elevator system.</p>
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28 pages, 5151 KiB  
Article
Efficiency Analysis and Optimization of Two-Speed-Region Operation of Permanent Magnet Synchronous Motor Taking into Account Iron Loss Based on Linear Non-Equilibrium Thermodynamics
by Ihor Shchur, Yurii Biletskyi and Bohdan Kopchak
Machines 2024, 12(11), 826; https://doi.org/10.3390/machines12110826 - 20 Nov 2024
Viewed by 607
Abstract
In this article, the linear non-equilibrium thermodynamic approach is used to mathematically describe the energy regularities of an interior permanent magnet synchronous motor (IPMSM), taking into account iron loss. The IPMSM is considered a linear power converter (PC) that is multiple-linearized at operating [...] Read more.
In this article, the linear non-equilibrium thermodynamic approach is used to mathematically describe the energy regularities of an interior permanent magnet synchronous motor (IPMSM), taking into account iron loss. The IPMSM is considered a linear power converter (PC) that is multiple-linearized at operating points with a given angular velocity and load torque. A universal description of such a PC by a system of dimensionless parameters and characteristics made it possible to analyze the perfection of energy conversion in the object. For IPMSM, taking into account iron loss, a mathematical model of the corresponding PC has been built, and an algorithm and research program have been developed, which is valid in a wide range of machine speed regulations. This allows you to choose the optimal points of PC operation according to the maximum efficiency criteria and obtain the efficiency maps for IPMSM in different speed regions. The results of the studies demonstrate the effectiveness of the proposed method for determining the references of the d and q components of the armature current for both the loss-minimization strategy at the constant torque range of motor speed and the flux-weakening strategy in the constant power range. Full article
(This article belongs to the Section Electromechanical Energy Conversion Systems)
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<p>Substitute scheme of the IPMSM taking into account iron loss: (<b>a</b>) in relation to the coordinate <span class="html-italic">d</span>, (<b>b</b>) in relation to the coordinate <span class="html-italic">q</span>. The arrows show the directions of currents and voltages, which are assumed to be positive in mathematical descriptions.</p>
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<p>Dependency of the PC efficiency on the reduced force ratio at different degrees of coupling.</p>
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<p>Dependencies obtained for the studied SPMSM taking into account iron loss: (<b>a</b>) in the entire range of changes in Zχ; (<b>b</b>) enlarged fragment in the zone of maximum values of <span class="html-italic">η</span>.</p>
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<p>Dependencies of the operating mode parameter <span class="html-italic">Zχ</span> on the main operating coordinates of the studied machine: (<b>a</b>) from the angular velocity <span class="html-italic">ω</span> at constant values of the relative load torque <span class="html-italic">T</span><sub>L</sub><sup>*</sup>; (<b>b</b>) from the load torque <span class="html-italic">T</span><sub>L</sub> at constant values of the relative angular velocity <span class="html-italic">ω</span><sup>*</sup>.</p>
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<p>Efficiency map obtained for the studied SPMSM.</p>
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<p>Flow chart of the algorithm for calculating the value of the <span class="html-italic">d</span>-component of the IPMSM armature current that is optimal from the point of view of minimum losses.</p>
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<p>Dependencies of the PC degree of coupling <span class="html-italic">q</span> (<b>a</b>), the operating point parameter <span class="html-italic">Zχ</span> (<b>b</b>) and the energy efficiency <span class="html-italic">η</span> (<b>c</b>) of IPMSM operation without taking into account the iron loss based on the value of the armature current component <span class="html-italic">i<sub>d</sub></span><sub>0</sub> at the nominal angular velocity of the machine for a series values of the load torque.</p>
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<p>Dependencies of the PC degree of coupling <span class="html-italic">q</span> (<b>a</b>), the operating point parameter <span class="html-italic">Zχ</span> (<b>b</b>) and the energy efficiency <span class="html-italic">η</span> (<b>c</b>) of the IPMSM operation taking into account the iron loss based on the value of the armature current component <span class="html-italic">i<sub>d</sub></span><sub>0</sub> at the nominal angular velocity of the machine for a series of values of the load torque.</p>
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<p>Dependencies of the value of the optimal <span class="html-italic">d</span>-component of the armature current (<b>a</b>) and the amplitude of the linear armature voltage (<b>b</b>) of the studied IPMSM on its angular velocity and load torque.</p>
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<p>Efficiency map of the studied IPMSM operation in the ME region of speed regulation.</p>
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<p>Dependencies of the components of IPMSM power losses taking into account iron loss from the load torque at the nominal motor angular velocity.</p>
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<p>Dependences of the amplitudes of the armature voltage (<b>a</b>) and current (<b>b</b>) vectors of the IPMSM on the value of the armature current component <span class="html-italic">i<sub>d</sub></span><sub>0</sub> at a machine angular velocity of 150 s<sup>−1</sup> for the maximum value of the load torque of 38 Nm.</p>
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<p>Dependencies of the PC degree of coupling <span class="html-italic">q</span> (<b>a</b>), the operating point parameter <span class="html-italic">Zχ</span> (<b>b</b>) and the energy efficiency <span class="html-italic">η</span> (<b>c</b>) of the IPMSM operation taking into account the iron loss on the value of the armature current component <span class="html-italic">i<sub>d</sub></span><sub>0</sub> at a machine angular velocity of 150 s<sup>−1</sup> for the maximum value of the load torque of 38 Nm.</p>
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<p>Dependencies of the <span class="html-italic">d</span>-component value of the armature current for the studied IPMSM operation in the region of angular velocity regulation with a constant power.</p>
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<p>Efficiency map of the studied IPMSM operation in the FW region of speed regulation.</p>
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<p>Dependencies of the components of IPMSM power losses from the load torque at the relative angular velocity of the motor <span class="html-italic">ω</span><sup>*</sup> = 1.5.</p>
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<p>Functional scheme of vector-controlled IPMSM drive with MEC and FW control.</p>
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<p>Dependencies of the necessary corrective value of the <span class="html-italic">d</span>-component of the armature current Δ<span class="html-italic">i<sub>d</sub></span><sub>0</sub> based on the deviation of the invertor voltage from the set value at different load torques for three values of the studied IPMSM angular velocity: (<b>a</b>) 125 s<sup>−1</sup>, (<b>b</b>) 175 s<sup>−1</sup> and 200 s<sup>−1</sup>.</p>
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22 pages, 6230 KiB  
Article
FEA-Based Design Procedure for IPMSM and IM for a Hybrid Electric Vehicle
by Emad Roshandel, Amin Mahmoudi, Wen L. Soong, Solmaz Kahourzade and Nathan Kalisch
Appl. Sci. 2024, 14(22), 10743; https://doi.org/10.3390/app142210743 - 20 Nov 2024
Viewed by 537
Abstract
This paper describes the detailed design procedure of electric machines using finite element analysis (FEA). The proposed method uses the available findings from the literature and FEA results for the design procedure. In addition to electromagnetic analysis, thermal analysis is executed to examine [...] Read more.
This paper describes the detailed design procedure of electric machines using finite element analysis (FEA). The proposed method uses the available findings from the literature and FEA results for the design procedure. In addition to electromagnetic analysis, thermal analysis is executed to examine the capability of the designed machines for handling the load in terms of thermal limits. It allows for considering the normal and overload performance of the electric machines during design. The proposed design procedure is used for designing a 100 kW induction machine (IM) and interior permanent magnet synchronous machine (IPMSM) for a parallel hybrid electric vehicle (HEV). The differences between the performance parameters of the studied machines are discussed, and the advantages and disadvantages of each design are highlighted. The designed machines are compared with commercially available electrical machines in terms of performance and power density. The comparison demonstrates that the developed machines can offer comparable performance to other designs. Full article
(This article belongs to the Special Issue Recent Developments in Electric Vehicles)
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<p>The schematic of the proposed HEV transmission system, reprinted with permission from IEEE.</p>
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<p>The schematic of the proposed spiral cooling system for the stators of both machines.</p>
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<p>The design flowchart of the studied 100 kW interior permanent magnet synchronous machine.</p>
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<p>Two-dimensional FEA results of the studied PMSM V-shape rotors for different rotor magnet angles. The maximum continuous power (MCP) is reported @2800 rpm with Class F temperature rise. <span class="html-italic">I<sub>sc</sub></span> is the short circuit current.</p>
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<p>Stacked bar graphs of the losses of the three PMSM designs obtained from 2D FEA.</p>
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<p>The proposed step-by-step design process for the induction machine design.</p>
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<p>Effect of the number of rotor bars: (<b>a</b>) 2D FEA results of torque ripple at rated torque, (<b>b</b>) 2D FEA results of performance parameters, (<b>c</b>) 3D FEA results of hot spot temperatures. The current, torque, and output power are per unit based on their rated values which are 120 A, 260 Nm, and 80 kW, respectively.</p>
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<p>Two-dimensional FEA results of the IM loss breakdown for different numbers of rotor bars.</p>
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<p>(<b>a</b>) Cross-section of the designed induction machine, (<b>b</b>) flux density distribution in the full-load operating condition.</p>
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<p>Two-dimensional FEA output power results: (<b>a</b>) IPMSM, (<b>b</b>) IM.</p>
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<p>Two-dimensional FEA efficiency map results: (<b>a</b>) IPMSM, (<b>b</b>) IM.</p>
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<p>Two-dimensional FEA power factor results: (<b>a</b>) IPMSM, (<b>b</b>) IM.</p>
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<p>Three-dimensional FEA results of the transient thermal analysis of the designed machines: (<b>a</b>) IPMSM, (<b>b</b>) IM.</p>
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<p>Two-dimensional FEA results of induction machines with different numbers of poles designed using the proposed process: (<b>a</b>) output power considering the thermal limit, (<b>b</b>) core loss/weight (bars) and weight (line).</p>
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22 pages, 3414 KiB  
Article
Symmetrical Short-Circuit Behavior Prediction of Rare-Earth Permanent Magnet Synchronous Motors
by Fabian Eichin, Maarten Kamper, Stiaan Gerber and Rong-Jie Wang
World Electr. Veh. J. 2024, 15(11), 536; https://doi.org/10.3390/wevj15110536 - 19 Nov 2024
Viewed by 880
Abstract
Since the advent of rare-earth permanent magnet (PM) materials, PM synchronous machines (PMSMs) have become popular in power generation, industrial drives, and e-mobility. However, rare-earth PMs in PMSMs are prone to temperature- and operation-related irreversible demagnetization. Additionally, faults can endanger components like inverters, [...] Read more.
Since the advent of rare-earth permanent magnet (PM) materials, PM synchronous machines (PMSMs) have become popular in power generation, industrial drives, and e-mobility. However, rare-earth PMs in PMSMs are prone to temperature- and operation-related irreversible demagnetization. Additionally, faults can endanger components like inverters, batteries, and mechanical structures. Designing a fault-tolerant machine requires considering these risks during the PMSM design phase. Traditional transient finite element analysis is time-consuming, but fast analytical simulation methods provide viable alternatives. This paper evaluates methods for analyzing dynamic three-phase short-circuit (3PSC) events in PMSMs. Experimental measurements on a PMSM prototype serve as benchmarks. The results show that accounting for machine saturation reduces discrepancies between measured and predicted outcomes by 20%. While spatial harmonic content and sub-transient reactance can be neglected in some cases, caution is required in other scenarios. Eddy currents in larger machines significantly impact 3PSC dynamics. This work provides a quick assessment based on general machine parameters, improving fault-tolerant PMSM design. Full article
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<p>Cross-section of the PMSM under study. This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Identified phase currents during a 3PSC (solid lines) compared to measured phase current (dashed line). This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Circuit representation of d–axis circuit Equation (4), (<b>a</b>) and q–axis Equation (5), (<b>b</b>).</p>
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<p>Comparison of the analytical solution (solid) and numerical solution (dotted) for the dq-currents during a 3PSC event. This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Simulated short-circuit phase currents from the linear <math display="inline"><semantics> <mrow> <mi>d</mi> <mi>q</mi> </mrow> </semantics></math> model and the measured phase current for one phase (dashed curve), with (<b>top</b>) nominal inductance values and (<b>bottom</b>) inductance values adjusted to fit the measurements. This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Rotor speed-dependent dynamic short circuit.</p>
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<p>Rotor speed-dependent steady-state and peak (dashed line) 3PSC currents.</p>
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<p>Block diagram of (17), incorporating LUTs that contain the relationship between the flux linkage and current vector. This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Inverted flux linkage map for the q-axis current, where the current is a function of the flux linkage vector, showing saturation effects at high currents. This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Simulated short-circuit phase currents from the flux linkage map-based integration model (solid lines) alongside the measured phase current for one phase (dashed curve). This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Time-stepping 2D FEA simulation (solid lines) versus measured phase currents. This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Material behavior with increased saturation at a high field strength (dashed line) during a 3PSC event. This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Phase current (dashed line) observed during a 3PSC event assuming stronger saturation (according to <a href="#wevj-15-00536-f012" class="html-fig">Figure 12</a>). This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Short-circuit phase currents using the extended flux linkage map-based integration model (flux linkage Map Ext.) (solid lines) compared to the measured phase current of one phase (dashed curve). This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Short-circuit torque using the flux linkage map-based integration model (solid lines) compared to the measured torque (dashed curve). This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Relative error of the proposed methods compared to experimental measurements. This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Flux density during a 3PSC in a typical IPMSM traction motor with a V-shaped PM design and a rated power of roughly 300 kW.</p>
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<p>BEMF harmonic content of the two studied motors.</p>
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<p>Simulated BEMF of V-shaped traction motor IPMSM (solid) and calculated BEMF from Fourier series according to (23) (dashed).</p>
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<p>Inverted flux linkage map in a stationary frame with three input variables.</p>
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<p>Short-circuit phase currents using the extended flux linkage map-based integration model (solid lines) compared with the measured phase current of one phase (dashed curve).</p>
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<p>3PSC torque computed from presented 2D/3D flux linkage map models (solid) and transient FEA (dashed).</p>
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<p>Peak eddy currents during the 3PSC obtained from time-stepping 3D FEA. This figure has been reproduced with permission from the IET, 2023.</p>
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<p>Peak eddy currents in a large PMG with V-shaped PMs during a 3PSC obtained from time-stepping 2D FEA.</p>
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<p>Remnant PM flux density illustrating partial irreversible demagnetization after a 3PSC, with red domains indicating full recovery in the baseline design (<b>left</b>) and the robust design (<b>right</b>).</p>
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50 pages, 12756 KiB  
Article
A New Paradigm in AC Drive Control: Data-Driven Control by Learning Through the High-Efficiency Data Set—Generalizations and Applications to a PMSM Drive Control System
by Madalin Costin and Ion Bivol
Sensors 2024, 24(22), 7313; https://doi.org/10.3390/s24227313 - 15 Nov 2024
Viewed by 706
Abstract
This paper presents a new means to control the processes involving energy conversion. Electric machines fed by electronic converters provide a useful power defined by the inner product of two generalized energetic variables: effort and flow. The novelty in this paper is controlling [...] Read more.
This paper presents a new means to control the processes involving energy conversion. Electric machines fed by electronic converters provide a useful power defined by the inner product of two generalized energetic variables: effort and flow. The novelty in this paper is controlling the desired energetic variables by a Data-Driven Control (DDC) law, which comprises the effort and flow and the corresponding process control. The same desired useful power might be obtained with different controls at different efficiencies. Solving the regularization problem is based on building a knowledge database that contains the maximum efficiency points. Knowing a reasonable number of optimal efficiency operation points, an interpolation Radial Base Function (RBF) control was built. The RBF algorithm can be found by training and testing the optimal controls for any admissible operation points of the process. The control scheme developed for Permanent Magnet Synchronous Motor (PMSM) has an inner DDC loop that performs converter control based on measured speed and demanded torque by the outer loop, which handles the speed. A comparison of the DDC with the Model Predictive Control (MPC) of the PMSM highlights the advantages of the new control method: the method is free from the process nature and guarantees higher efficiency. Full article
(This article belongs to the Special Issue Magnetoelectric Sensors and Their Applications)
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<p>The diagram of the macroscopic energy flow conversion.</p>
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<p>The transition from MBC to MFC: (<b>a</b>) The basis control scheme; (<b>b</b>) Stored data from MPC running; (<b>c</b>) Designing of MFC strategy: trainning phase; (<b>d</b>) Designing of MFC strategy: testing phase.</p>
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<p>The RBF-NN used for obtaining the plant input.</p>
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<p>A combined control structure with linear PI outer control loop and DDC inner control. Designing of DDC strategy: (<b>a</b>) Training phase; (<b>b</b>) Testing phase.</p>
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<p>The principle of the DDC strategy applied to an AC motor: (<b>a</b>) Stage I: Stored data from MPC cascade control running; (<b>b</b>) Stage II: Training of testing the RBF-NN DDC control; (<b>c</b>) Stage III: Testing of the DDC control.</p>
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<p>Power structure of the PMSM drive.</p>
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<p>Space vector diagram of a PMSM with rotor system frame orientation.</p>
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<p>The <span class="html-italic">dq</span> equivalent circuit scheme of PMSM.</p>
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<p>The voltage space vector according to their corresponding switching states.</p>
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<p>The MPC control PMSM drive.</p>
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<p>Training phase of the DDC controller of PMSM.</p>
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<p>The DDC control structure of a PMSM drive.</p>
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<p>A schematic representation of the DDC control of the PMSM drive system.</p>
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<p>The torque-speed characteristics under iso-efficiency curves of a PMSM drive.</p>
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<p>Transformation of the multi-valued efficiency map into a single-valued function.</p>
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<p>The database grid steps design of closed-loop applications.</p>
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<p>The moving window filter structure.</p>
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<p>The pseudocode format of the MPC algorithm of a PMSM drive control.</p>
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<p>The DDC control algorithm of a PMSM drive control.</p>
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<p>The efficiency surface vs. speed and torque.</p>
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<p>The <span class="html-italic">d</span>-axis voltage surface vs. speed and torque.</p>
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<p>The <span class="html-italic">q</span>-axis voltage surface vs. speed and torque.</p>
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<p>The speed-tracking results for MPC and DDC control strategies.</p>
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<p>The current results obtained for MPC and DDC control strategies.</p>
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<p>Load and electromagnetic torques for MPC and DDC control strategies.</p>
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<p>Voltage components for MPC and DDC control strategies.</p>
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<p>Current magnitude for MPC and DDC control strategies.</p>
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<p>Voltage magnitude for MPC and DDC control strategies.</p>
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<p>Efficiency of PMSM for MPC and DDC control strategies.</p>
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<p>Average efficiency of PMSM for MPC and DDC control strategies.</p>
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<p>Phase current of PMSM for MPC and DDC control strategies.</p>
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<p>The tracking results of speed obtained via MPC and DDC control laws.</p>
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<p>The <span class="html-italic">dq</span> current obtained for MPC and DDC control laws.</p>
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<p>Load torque disturbance rejection for MPC and DDC control strategies.</p>
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<p>Voltage obtained by MPC and DDC control strategies.</p>
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<p>Current magnitude given by MPC and DDC control algorithms.</p>
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<p>Voltage magnitude given by MPC and DDC control algorithms.</p>
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<p>The efficiency of PMSM obtained by using MPC and DDC control algorithms.</p>
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<p>Average efficiency of PMSM provided by using MPC and DDC control algorithms.</p>
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<p>Phase current for MPC and DDC control algorithms.</p>
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13 pages, 3915 KiB  
Article
Fast Prediction of Characteristics in Wound Rotor Synchronous Condenser Using Subdomain Modeling
by Manh-Dung Nguyen, Tae-Seong Kim, Kyung-Hun Shin, Gang-Hyeon Jang and Jang-Young Choi
Mathematics 2024, 12(22), 3526; https://doi.org/10.3390/math12223526 - 12 Nov 2024
Viewed by 495
Abstract
Wound rotor synchronous condensers (WRSCs) are DC-excited rotor machines that utilize rotor winding instead of permanent magnets. Their voltage regulator controls the rotor field to generate or absorb reactive power, thereby regulating grid voltage or improving power factor. A key characteristic of a [...] Read more.
Wound rotor synchronous condensers (WRSCs) are DC-excited rotor machines that utilize rotor winding instead of permanent magnets. Their voltage regulator controls the rotor field to generate or absorb reactive power, thereby regulating grid voltage or improving power factor. A key characteristic of a WRSC is the compounding curve, which shows the required rotor current under specific stator current and voltage conditions. This paper presents an approach for quickly calculating the electromagnetic parameters of a WRSC using a mathematical method. After determining magnetic flux density, induced voltage, and inductance through analytical methods, the Park and Clarke transformations are applied to derive the dq-frame quantities, enabling prediction of active and reactive powers and compounding curve characteristics. The 60 Hz model was evaluated through comparison with finite element method (FEM) simulations. Results of flux density, induced voltage, and the compounding curve under varying rotor and stator current conditions showed that the proposed method achieved comparable performance to FEM simulation while reducing computational time by half. Full article
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<p>(<b>a</b>) Wound rotor synchronous condenser and (<b>b</b>) a simplified model.</p>
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<p>Illustration of compounding curves.</p>
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<p>(<b>a</b>) Mesh operation (29,242 elements) and (<b>b</b>) flux density distribution at <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>f</mi> </mrow> </msub> <mo>=</mo> <mn>1</mn> <mo> </mo> <mi mathvariant="normal">k</mi> <mi mathvariant="normal">A</mi> <mo>;</mo> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>d</mi> </mrow> </msub> <mo>=</mo> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>q</mi> </mrow> </msub> <mo>=</mo> <mo>−</mo> <mn>0.5</mn> <mo> </mo> <mi mathvariant="normal">k</mi> <mi mathvariant="normal">A</mi> </mrow> </semantics></math>.</p>
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<p>Flux density at the air gap and induced voltage in case of (<b>a</b>,<b>b</b>) <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>f</mi> </mrow> </msub> <mo>=</mo> <mn>1</mn> <mo> </mo> <mi mathvariant="normal">k</mi> <mi mathvariant="normal">A</mi> <mo>;</mo> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>d</mi> </mrow> </msub> <mo>=</mo> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>q</mi> </mrow> </msub> <mo>=</mo> <mn>0</mn> <mo> </mo> <mi mathvariant="normal">k</mi> <mi mathvariant="normal">A</mi> </mrow> </semantics></math>, (<b>c</b>,<b>d</b>) <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>f</mi> </mrow> </msub> <mo>=</mo> <mn>1</mn> <mo> </mo> <mi mathvariant="normal">k</mi> <mi mathvariant="normal">A</mi> <mo>;</mo> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>d</mi> </mrow> </msub> <mo>=</mo> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>q</mi> </mrow> </msub> <mo>=</mo> <mo>−</mo> <mn>0.5</mn> <mo> </mo> <mi mathvariant="normal">k</mi> <mi mathvariant="normal">A</mi> </mrow> </semantics></math>, and (<b>e</b>,<b>f</b>) <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>f</mi> </mrow> </msub> <mo>=</mo> <mn>1.5</mn> <mo> </mo> <mi mathvariant="normal">k</mi> <mi mathvariant="normal">A</mi> <mo>;</mo> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>d</mi> </mrow> </msub> <mo>=</mo> <mo>−</mo> <mn>0.5</mn> <mo>;</mo> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>q</mi> </mrow> </msub> <mo>=</mo> <mo>−</mo> <mn>1</mn> <mo> </mo> <mi mathvariant="normal">k</mi> <mi mathvariant="normal">A</mi> </mrow> </semantics></math>, respectively.</p>
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<p>Compounding curves of the calculation and the FEM under different conditions of maximum stator voltage.</p>
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16 pages, 37894 KiB  
Article
High-Precision Rotor Position Fitting Method of Permanent Magnet Synchronous Machine Based on Hall-Effect Sensors
by Kaining Qu, Pengfei Pang and Wei Hua
Energies 2024, 17(22), 5625; https://doi.org/10.3390/en17225625 - 10 Nov 2024
Viewed by 739
Abstract
The high-performance vector control technology of permanent magnet synchronous machines (PMSMs) relies on high-precision rotor position. The Hall-effect sensor has the advantages of low cost, simple installation, and strong anti-interference ability. However, it can only provide six discrete rotor angles in an electrical [...] Read more.
The high-performance vector control technology of permanent magnet synchronous machines (PMSMs) relies on high-precision rotor position. The Hall-effect sensor has the advantages of low cost, simple installation, and strong anti-interference ability. However, it can only provide six discrete rotor angles in an electrical cycle, which makes high-precision vector control of PMSMs difficult. Hence, to obtain the necessary rotor position of PMSMs, a rotor position fitting method combining the Hall signal and machine flux information is proposed. Firstly, the rotor position signal output by the Hall-effect sensors is used to calibrate and update the stator flux obtained under pure integration. Then, based on the corrected stator flux and its relationship with current and angle, the rotor position and speed are obtained. Experimental verification shows that the rotor position observer combining Hall signal and flux information can reduce the initial value bias and integral drift caused by traditional average speed method hysteresis and pure integration method calculation of flux and can quickly and accurately track and estimate the rotor position, achieving high-performance vector control of PMSMs. Full article
(This article belongs to the Special Issue Designs and Control of Electrical Machines and Drives)
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<p>Hall-effect Sensors.</p>
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<p>Hall installation mode and output signals (<b>a</b>) 120° Hall-effect installation, (<b>b</b>) Hall-effect output signals.</p>
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<p>Relation of Hall signal and rotor position.</p>
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<p>Estimation principle by average velocity method.</p>
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<p>Hall signal delay under digital control system.</p>
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<p>Structure of position vector tracking observer.</p>
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<p>Bode diagram of position vector tracking observer based on back EMF.</p>
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<p>Stator flux observer combined with flux linkage information and Hall signal.</p>
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<p>Input voltage calculation for the flux observer.</p>
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<p>Rotor position observer combined with flux linkage information and Hall signal.</p>
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<p>The experiment platform.</p>
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<p>Flux linkage waveforms under three conditions (<b>a</b>) Flux linkage before correction, (<b>b</b>) Flux linkage at discrete Hall points, (<b>c</b>) Flux linkage under Hall signal correction.</p>
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<p>Comparison of no-load starting rotor positions (<b>a</b>) Average speed, (<b>b</b>) Vector tracking, (<b>c</b>) Flux-Hall.</p>
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<p>Comparison of on-rated-load starting rotor positions.</p>
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<p>Estimated rotor angle errors under three initial positions (<b>a</b>) The Hall intermediate angle, (<b>b</b>) 25° advanced, (<b>c</b>) 25° delayed.</p>
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<p>Comparison of <math display="inline"><semantics> <mrow> <mi>d</mi> <mi>q</mi> </mrow> </semantics></math>-frame currents waveforms. Comparison of <math display="inline"><semantics> <mrow> <mi>d</mi> <mi>q</mi> </mrow> </semantics></math>-frame currents waveforms (<b>a</b>) Average speed, (<b>b</b>) Flux-Hall.</p>
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<p>Comparison of rotor positions under a speed change from 300/min to 1800/min (<b>a</b>) Average speed, (<b>b</b>) Flux-Hall, (<b>c</b>) Angle error.</p>
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<p>Rotor position during forward and reverse switching (<b>a</b>) Average speed, (<b>b</b>) Flux-Hall.</p>
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<p>Stator current and rotor position at 750/min (<b>a</b>) Average speed, (<b>b</b>,<b>c</b>) Flux-Hall.</p>
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<p>Rotor position under different inductance (<b>a</b>) <math display="inline"><semantics> <mrow> <mover accent="true"> <mrow> <mi>L</mi> </mrow> <mo stretchy="false">^</mo> </mover> <mo>=</mo> <mn>0.8</mn> <mi>L</mi> </mrow> </semantics></math>, (<b>b</b>) <math display="inline"><semantics> <mrow> <mover accent="true"> <mrow> <mi>L</mi> </mrow> <mo stretchy="false">^</mo> </mover> <mo>=</mo> <mn>1.2</mn> <mi>L</mi> </mrow> </semantics></math>, (<b>c</b>) <math display="inline"><semantics> <mrow> <mover accent="true"> <mrow> <mi>L</mi> </mrow> <mo stretchy="false">^</mo> </mover> <mo>=</mo> <mi>L</mi> </mrow> </semantics></math>.</p>
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<p>Rotor position under different resistance (<b>a</b>) <math display="inline"><semantics> <mrow> <mover accent="true"> <mrow> <mi>R</mi> </mrow> <mo stretchy="false">^</mo> </mover> <mo>=</mo> <mn>0.8</mn> <mi>R</mi> </mrow> </semantics></math>, (<b>b</b>) <math display="inline"><semantics> <mrow> <mover accent="true"> <mrow> <mi>R</mi> </mrow> <mo stretchy="false">^</mo> </mover> <mo>=</mo> <mn>1.2</mn> <mi>R</mi> </mrow> </semantics></math>, (<b>c</b>) <math display="inline"><semantics> <mrow> <mover accent="true"> <mrow> <mi>R</mi> </mrow> <mo stretchy="false">^</mo> </mover> <mo>=</mo> <mi>R</mi> </mrow> </semantics></math>.</p>
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24 pages, 6414 KiB  
Article
Robust Driving Control Design for Precise Positional Motions of Permanent Magnet Synchronous Motor Driven Rotary Machines with Position-Dependent Periodic Disturbances
by Syh-Shiuh Yeh and Zhi-Hong Liu
Machines 2024, 12(11), 771; https://doi.org/10.3390/machines12110771 - 1 Nov 2024
Viewed by 797
Abstract
Position-dependent periodic disturbances often limit the accuracy and smoothness of the positional motion of permanent magnet synchronous motor (PMSM)-driven rotary machines. Because the period of these disturbances varies with the motion velocity of the rotary machine, spatial domain control methods such as spatial [...] Read more.
Position-dependent periodic disturbances often limit the accuracy and smoothness of the positional motion of permanent magnet synchronous motor (PMSM)-driven rotary machines. Because the period of these disturbances varies with the motion velocity of the rotary machine, spatial domain control methods such as spatial iterative learning control (SILC) and spatial repetitive control (SRC) have been proposed and applied to improve rotary machine motion control designs. However, problems with learning period convergence and rotary machine dynamics significantly affect transient motion, further constraining the overall motion performance. To address these challenges, this study developed a robust driving control (RDC) that integrates a robust control design with position-dependent periodic disturbance feedforward compensation, rotary machine dynamics compensation, and proportional–proportional integral feedback control. A position-dependent periodic disturbance model was developed using multiple position–sinusoidal signals and identified using a spatial fast Fourier transform. RDC compensates for disturbances and dynamics and considers the effects of model parameter uncertainty and modeling error on the stability of the control system. Several motion control experiments were conducted on a PMSM test bench to compare the RDC, SILC, and SRC. The experimental results demonstrated that although both SILC and SRC can effectively suppress position-dependent periodic disturbances, SILC provides slower position error convergence owing to the learning process, and SILC and SRC result in significant position errors because of the influence of the PMSM-driven rotary machine dynamics. RDC not only suppresses position-dependent periodic disturbances, but also significantly reduces position errors with a reduction rate of 90%. Therefore, the RDC developed in this study effectively suppressed position-dependent periodic disturbances and significantly improved both the transient-state and steady-state position-tracking performances of the PMSM-driven rotary machine. Full article
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<p>P-PI feedback control and compensation: (<b>a</b>) P-PI feedback control structure. (<b>b</b>) P-PI feedback-and-compensation control structure [<a href="#B33-machines-12-00771" class="html-bibr">33</a>].</p>
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<p>SILC design based on P-PI feedback control structure.</p>
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<p>SRC design based on the P-PI feedback control structure.</p>
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<p>RDC design based on the P-PI feedback-and-compensation control structure.</p>
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<p>The PMSM test bench used in this study.</p>
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<p>Position-dependent periodic disturbance estimation results (for a complete turn).</p>
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<p>Spatial FFT of the position-dependent periodic disturbance (corresponding to <a href="#machines-12-00771-f006" class="html-fig">Figure 6</a>).</p>
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<p>Position-dependent periodic disturbance estimation and modeling.</p>
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<p>Experimental results of the drive motor operating for ten turns (SILC).</p>
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<p>Experimental results of transient-state and steady-state operation of the drive motor (SILC) (circular angle axis unit: degree; radial axis unit: radian).</p>
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<p>Experimental results of drive motor operating for ten turns (SRC).</p>
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<p>Experimental results of transient-state and steady-state operation of the drive motor (SRC) (circular angle axis unit: degree; radial axis unit: radian).</p>
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<p>Experimental results of the drive motor operating for ten turns (RDC).</p>
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<p>Experimental results of transient-state and steady-state operation of the drive motor (RDC) (circular angle axis unit: degree; radial axis unit: radian).</p>
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<p>Position error in the drive motor operating process (left: first three turns; right: tenth turn).</p>
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<p>Comparison of MAX and AVG position errors (left: MAX; right: AVG).</p>
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21 pages, 10520 KiB  
Article
The Design of Improved Series Hybrid Power System Based on Compound-Wing VTOL
by Siqi An, Guichao Cai, Xu Peng, Mingxiao Dai and Guolong Yang
Drones 2024, 8(11), 634; https://doi.org/10.3390/drones8110634 - 1 Nov 2024
Viewed by 845
Abstract
Hybrid power systems are now widely utilized in a variety of vehicle platforms due to their efficacy in reducing pollution and enhancing energy utilization efficiency. Nevertheless, the existing vehicle hybrid systems are of a considerable size and weight, rendering them unsuitable for integration [...] Read more.
Hybrid power systems are now widely utilized in a variety of vehicle platforms due to their efficacy in reducing pollution and enhancing energy utilization efficiency. Nevertheless, the existing vehicle hybrid systems are of a considerable size and weight, rendering them unsuitable for integration into 25 kg compound-wing UAVs. This study presents a design solution for a compound-wing vertical takeoff and landing unmanned aerial vehicle (VTOL) equipped with an improved series hybrid power system. The system comprises a 48 V lithium polymer battery(Li-Po battery), a 60cc internal combustion engine (ICE), a converter, and a dedicated permanent magnet synchronous machine (PMSM) with four motors, which collectively facilitate dual-directional energy flow. The four motors serve as a load and lift assembly, providing the requisite lift during the take-off, landing, and hovering phases, and in the event of the ICE thrust insufficiency, as well as forward thrust during the level cruise phase by mounting the variable pitch propeller directly on the ICE. The entire hybrid power system of the UAV undergoes numerical modeling and experimental simulation to validate the feasibility of the complete hybrid power configuration. The validation is achieved by comparing and analyzing the results of the numerical simulations with ground tests. Moreover, the effectiveness of this hybrid power system is validated through the successful completion of flight test experiments. The hybrid power system has been demonstrated to significantly enhance the endurance of vertical flight for a compound-wing VTOL by more than 25 min, thereby establishing a solid foundation for future compound-wing VTOLs to enable multi-destination flights and multiple takeoffs and landings. Full article
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<p>Two typical configurations of the UAV.</p>
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<p>Typical multi-points flight mission profile.</p>
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<p>(<b>a</b>) Typical configuration of the compound-wing VTOL; (<b>b</b>) 25 kg MTOW compound-wing VTOL prototype.</p>
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<p>The improved series hybrid architecture and three different energy paths of the hybrid power system under different thrust modes. (<b>a</b>) The diagram illustrates the bidirectional flow path of energy throughout the hybrid system; (<b>b</b>) energy flow path in the full thrust mode, illustrates that in the case of vertical lift; (<b>c</b>) illustrates the energy flow path in cruise mode, in which the UAV is airborne; (<b>d</b>) energy flow path in the emergency thrust mode, shows the emergency mode.</p>
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<p>Selecting or designing the five main components of the system, the second floor of the diagram shows the main factors to consider and the third floor shows the main system components.</p>
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<p>(<b>a</b>) Piston ICE that drives a propeller in the cruise mode to provide the forward thrust for the aircraft. It also drives the PMSM to generate AC, which is passed through a rectifier to charge the batteries used in the drogue phase; (<b>b</b>) the Li-Po battery used in drones is designed as a single unit, usually a single unit with a voltage of 3.8 V to 4.2 V. The power system battery is made up of 12 pieces connected in parallel to ensure that the dropping voltage reaches 48 V and above.</p>
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<p>(<b>a</b>) This is a multi-rotor brushless DC motor. It is DC powered to generate the upward lift; (<b>b</b>) this is a permanent magnet synchronous motor (PMSM), which is driven by an internal combustion engine for the generation of AC; (<b>c</b>) this is a three-phase bridge rectifier in the VTOL, which is a device that is used to convert AC to DC.</p>
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<p>The general character map of the ICE.</p>
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<p>The R-int model of battery.</p>
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<p>(<b>a</b>) Shows five connections. The lower three interfaces in the diagram access the three-phase AC generated by the synchronous motor and the DC is connected via the upper two connectors; (<b>b</b>) shows the rectifier circuit working principle.</p>
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<p>The schematic diagram of VPP.</p>
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<p>The thrust performance of the 17-inch, 20-inch, and 22-inch propellers.</p>
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<p>The simulation configuration of VPP.</p>
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<p>(<b>a</b>) The output thrust character (2D) of VPP; (<b>b</b>) the output thrust character (3D) of VPP.</p>
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<p>(<b>a</b>): Simulation thrust from VPP compared with demanded thrust; (<b>b</b>): simulation electric load that represents the lift on rotor.</p>
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<p>Simulation of ICE rotational speed, SOC, throttle opening, and generated power versus time.</p>
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<p>The specifically made ground test bench.</p>
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<p>The ground experiment of the entire hybrid power system.</p>
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<p>Flight profile data from ground experiment.</p>
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<p>(<b>a</b>) The output thrust character of the VPP (ground experiment); (<b>b</b>) difference between measured data from the ground experiment and numerically simulated values.</p>
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<p>The configuration of the hybrid compound-wing VTOL.</p>
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<p>The hovering experiment of compound-wing VTOL.</p>
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<p>The flight data based on the hovering experiment of compound-wing VTOL.</p>
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14 pages, 9408 KiB  
Article
General Fault-Tolerant Operation of Electric-Drive-Reconstructed Onboard Charger Incorporating Asymmetrical Six-Phase Drive for EVs
by Xing Liu, Xunhui Cheng, Hui Yang and Yuhao Zhang
World Electr. Veh. J. 2024, 15(11), 488; https://doi.org/10.3390/wevj15110488 - 27 Oct 2024
Viewed by 474
Abstract
In this paper, the fault-tolerant operation of an electric-drive-reconstructed onboard charger (EDROC) designed on the basis of an asymmetrical six-phase permanent magnet synchronous machine (ASPMSM) drive is studied and discussed for cases where an open-phase fault (OPF) occurs in any phase. The fault-tolerant [...] Read more.
In this paper, the fault-tolerant operation of an electric-drive-reconstructed onboard charger (EDROC) designed on the basis of an asymmetrical six-phase permanent magnet synchronous machine (ASPMSM) drive is studied and discussed for cases where an open-phase fault (OPF) occurs in any phase. The fault-tolerant operation is realized by rearranging the stator currents, aiming to eliminate the rotating field caused by the OPFs and to ensure the balance of grid currents. Each faulty case is discussed, and the rearranging scheme of stator currents is deduced. Meanwhile, a controller shared for both healthy and faulty cases is designed. Finally, some experiments are conducted to verify the theoretical analyses. Full article
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<p>Topology of the studied electric-drive-reconstructed onboard charger (EDROC).</p>
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<p>Decoupled current trajectories in the healthy case: (<b>a</b>) torque-generation-related components; (<b>b</b>) torque-generation-unrelated components.</p>
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<p>Decoupled current trajectories in different faulty cases: (<b>a</b>) Winding A1 is faulty; (<b>b</b>) Winding A2 is faulty; (<b>c</b>) Winding B1 is faulty; (<b>d</b>) Winding B2 is faulty; (<b>e</b>) Winding C1 is faulty; (<b>f</b>) Winding C2 is faulty.</p>
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<p>Current phasor diagram in relation to phase <span class="html-italic">a</span>.</p>
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<p>Decoupled current trajectories of fault-tolerant operations: (<b>a</b>) Winding A1 is faulty; (<b>b</b>) Winding A2 is faulty; (<b>c</b>) Winding B1 is faulty; (<b>d</b>) Winding B2 is faulty; (<b>e</b>) Winding C1 is faulty; (<b>f</b>) Winding C2 is faulty.</p>
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<p>Decoupled current trajectories of fault-tolerant operations: (<b>a</b>) Winding A1 is faulty; (<b>b</b>) Winding A2 is faulty; (<b>c</b>) Winding B1 is faulty; (<b>d</b>) Winding B2 is faulty; (<b>e</b>) Winding C1 is faulty; (<b>f</b>) Winding C2 is faulty.</p>
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<p>Controller designed for the studied EDROC.</p>
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<p>Experimental prototype.</p>
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<p>Experimental results in healthy case: (<b>a</b>) winding currents, grid currents, and charging voltage; (<b>b</b>) grid voltage and currents; (<b>c</b>) decoupled current trajectories and shaft speed.</p>
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<p>Experimental results of winding currents, grid currents, and charging voltage in faulty cases with fault-tolerant control: (<b>a</b>) Winding A1 is damaged; (<b>b</b>) Winding A2 is damaged; (<b>c</b>) Winding B1 is damaged; (<b>d</b>) Winding B2 is damaged; (<b>e</b>) Winding C1 is damaged; (<b>f</b>) Winding C2 is damaged.</p>
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<p>Experimental results of winding currents, grid currents, and charging voltage in faulty cases with fault-tolerant control: (<b>a</b>) Winding A1 is damaged; (<b>b</b>) Winding A2 is damaged; (<b>c</b>) Winding B1 is damaged; (<b>d</b>) Winding B2 is damaged; (<b>e</b>) Winding C1 is damaged; (<b>f</b>) Winding C2 is damaged.</p>
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<p>Experimental results of decoupled current trajectories and shaft speed in faulty cases with fault-tolerant control: (<b>a</b>) Winding A1 is damaged; (<b>b</b>) Winding A2 is damaged; (<b>c</b>) Winding B1 is damaged; (<b>d</b>) Winding B2 is damaged; (<b>e</b>) Winding C1 is damaged; (<b>f</b>) Winding C2 is damaged.</p>
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<p>Experimental results of decoupled current trajectories and shaft speed in faulty cases with fault-tolerant control: (<b>a</b>) Winding A1 is damaged; (<b>b</b>) Winding A2 is damaged; (<b>c</b>) Winding B1 is damaged; (<b>d</b>) Winding B2 is damaged; (<b>e</b>) Winding C1 is damaged; (<b>f</b>) Winding C2 is damaged.</p>
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