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Search Results (1,395)

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Keywords = millimeter-wave

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27 pages, 1409 KiB  
Article
Adaptive Handover Management in High-Mobility Networks for Smart Cities
by Yahya S. Junejo, Faisal K. Shaikh, Bhawani S. Chowdhry and Waleed Ejaz
Computers 2025, 14(1), 23; https://doi.org/10.3390/computers14010023 - 14 Jan 2025
Abstract
The seamless handover of mobile devices is critical for maximizing the potential of smart city applications, which demand uninterrupted connectivity, ultra-low latency, and performance in diverse environments. Fifth-generation (5G) and beyond-5G networks offer advancements in massive connectivity and ultra-low latency by leveraging advanced [...] Read more.
The seamless handover of mobile devices is critical for maximizing the potential of smart city applications, which demand uninterrupted connectivity, ultra-low latency, and performance in diverse environments. Fifth-generation (5G) and beyond-5G networks offer advancements in massive connectivity and ultra-low latency by leveraging advanced technologies like millimeter wave, massive machine-type communication, non-orthogonal multiple access, and beam forming. However, challenges persist in ensuring smooth handovers in dense deployments, especially in higher frequency bands and with increased user mobility. This paper presents an adaptive handover management scheme that utilizes reinforcement learning to optimize handover decisions in dynamic environments. The system selects the best target cell from the available neighbor cell list by predicting key performance indicators, such as reference signal received power and the signal–interference–noise ratio, while considering the fixed time-to-trigger and hysteresis margin values. It dynamically adjusts handover thresholds by incorporating an offset based on real-time network conditions and user mobility patterns. This adaptive approach minimizes handover failures and the ping-pong effect. Compared to the baseline LIM2 model, the proposed system demonstrates a 15% improvement in handover success rate, a 3% improvement in user throughput, and an approximately 6 sec reduction in the latency at 200 km/h speed in high-mobility scenarios. Full article
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<p>Learning model for handover in 5G NR.</p>
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<p>Handover signaling messages.</p>
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<p>Proposed network mechanism.</p>
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<p>Handover event A5.</p>
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<p>Handover success rate when total number of UE is 500 versus (<b>a</b>) speed and (<b>b</b>) SINR.</p>
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<p>UE handover delay versus (<b>a</b>) speed and (<b>b</b>) SINR.</p>
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<p>Throughput versus (<b>a</b>) speed, (<b>b</b>) SINR, and (<b>c</b>) when number of pieces of UE is fixed.</p>
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<p>Latency versus (<b>a</b>) speed and (<b>b</b>) SINR.</p>
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<p>Packet loss ratio versus (<b>a</b>) speed and (<b>b</b>) SINR.</p>
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18 pages, 28462 KiB  
Article
Optimized Airborne Millimeter-Wave InSAR for Complex Mountain Terrain Mapping
by Futai Xie, Wei Wang, Xiaopeng Sun, Si Xie and Lideng Wei
Sensors 2025, 25(2), 424; https://doi.org/10.3390/s25020424 - 13 Jan 2025
Viewed by 278
Abstract
The efficient acquisition and processing of large-scale terrain data has always been a focal point in the field of photogrammetry. Particularly in complex mountainous regions characterized by clouds, terrain, and airspace environments, the window for data collection is extremely limited. This paper investigates [...] Read more.
The efficient acquisition and processing of large-scale terrain data has always been a focal point in the field of photogrammetry. Particularly in complex mountainous regions characterized by clouds, terrain, and airspace environments, the window for data collection is extremely limited. This paper investigates the use of airborne millimeter-wave InSAR systems for efficient terrain mapping under such challenging conditions. The system’s potential for technical application is significant due to its minimal influence from cloud cover and its ability to acquire data in all-weather and all-day conditions. Focusing on the key factors in airborne InSAR data acquisition, this study explores advanced route planning and ground control measurement techniques. Leveraging radar observation geometry and global SRTM DEM data, we simulate layover and shadow effects to formulate an optimal flight path design. Additionally, the study examines methods to reduce synchronous ground control points in mountainous areas, thereby enhancing the rapid acquisition of terrain data. The results demonstrate that this approach not only significantly reduces field work and aviation costs but also ensures the accuracy of the mountain surface data generated by airborne millimeter-wave InSAR, offering substantial practical application value by reducing field work and aviation costs while maintaining data accuracy. Full article
(This article belongs to the Section Remote Sensors)
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<p>View extend diagram.</p>
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<p>Shadow and layover schematic diagram, where grey area represents an object on the ground.</p>
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<p>Convert DEM data to radar coordinate system.</p>
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<p>The main basic data for calculating R_Index.</p>
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<p>The evolution of different headings affected by terrain.</p>
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<p>Flight path design, where (<b>a</b>) is the original flight path and (<b>b</b>) is the improved flight path of saving U-turn time by adjusting flight sequence from 1 to 6.</p>
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<p>Work flow chart of flight path design.</p>
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<p>Radar antenna observation geometry diagram.</p>
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<p>(<b>a</b>) Corner reflector placement position measurement and (<b>b</b>) corner reflector layout.</p>
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<p>The imaging results of corner reflector diagram on radar image is shown in (<b>a</b>), and (<b>b</b>) is the corner reflector that was damaged and moved out of its original position.</p>
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<p>Supplementary control point measurements after the flight.</p>
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<p>Measurement error experiment of manually adding control points.</p>
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<p>Airborne InSAR data processing flow chart.</p>
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<p>Working area.</p>
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<p>The relationship between the area proportion affected by terrain and flight heading angle.</p>
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<p>(<b>a</b>) Designed flight paths with the fix interval and (<b>b</b>) simulation results of equally spaced flight paths; there are gaps between each strip in the mountain area.</p>
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<p>(<b>a</b>) Designed flight paths, which are denser in the mountain area, and (<b>b</b>) simulation calculation results of strip coverage with denser flight paths in the mountain area and overlay shadow distribution.</p>
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<p>(<b>a</b>) Control point distribution. (<b>b</b>) Elevation inversion results.</p>
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<p>(<b>a</b>) Field control point measurement sample areas. (<b>b</b>) Distribution of ground check points.</p>
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9 pages, 6003 KiB  
Article
W-Band GaAs pHEMT Power Amplifier MMIC Stabilized Using Network Determinant Function
by Seong-Hee Han and Dong-Wook Kim
Micromachines 2025, 16(1), 81; https://doi.org/10.3390/mi16010081 - 12 Jan 2025
Viewed by 437
Abstract
This paper presents a W-band power amplifier monolithic microwave integrated circuit (MMIC) that is designed for high-precision millimeter-wave systems and fabricated using a 0.1 µm GaAs pHEMT process. The amplifier’s stability was evaluated using the network determinant function, ensuring robust performance under both [...] Read more.
This paper presents a W-band power amplifier monolithic microwave integrated circuit (MMIC) that is designed for high-precision millimeter-wave systems and fabricated using a 0.1 µm GaAs pHEMT process. The amplifier’s stability was evaluated using the network determinant function, ensuring robust performance under both linear and nonlinear conditions. Simultaneous matching for gain and output power was achieved with minimal passive elements. The developed power amplifier MMIC exhibits a linear gain exceeding 20 dB and an input return loss greater than 6 dB across the 88–98 GHz range. It delivers an output power of 23.8–24.1 dBm with a power gain of 17.3–17.9 dB in the 88–97 GHz range and achieves a maximum power-added efficiency (PAE) of 24% at 94 GHz. Full article
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<p>Circuit schematic of the W-band power amplifier.</p>
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<p>Simulated source pull and load pull results of the 4 × 50 μm transistor: (<b>a</b>) load pull; (<b>b</b>) source pull.</p>
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<p>Stability check using K and NDF: (<b>a</b>) Test sample sub-circuit; (<b>b</b>) NDF graphs; (<b>c</b>) Encirclements (sample circuit 1: R = 50 Ω, C = 1 pF, sample circuit 2: R = 50 Ω, C = 6.8 pF).</p>
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<p>NDF graphs of the designed W-band power amplifier MMIC: (<b>a</b>) polar chart; (<b>b</b>) encirclements.</p>
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<p>NDF graphs of the designed W-band power amplifier MMIC during nonlinear operation: (<b>a</b>) polar chart at 94 GHz; (<b>b</b>) encirclements.</p>
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<p>Photograph of the fabricated W-band power amplifier MMIC.</p>
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<p>Measured S-parameter results of the W-band power amplifier MMIC.</p>
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<p>Large-signal measurement results of the W-band power amplifier MMIC: (<b>a</b>) Output power performance with input power at 94 GHz; (<b>b</b>) Saturated output power and power gain in the 88–97 GHz region.</p>
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12 pages, 7989 KiB  
Article
Compact Tri-Band Bandpass Filter with Wide Upper Stopband Based on Spoof Surface Plasmon Polaritons and Open-/Short-Circuited Stubs
by Baoping Ren, Wenjian Chen, Xiaoyan Zhang, Xuehui Guan and Kai-Da Xu
Electronics 2025, 14(2), 285; https://doi.org/10.3390/electronics14020285 - 12 Jan 2025
Viewed by 266
Abstract
In this paper, a new U-shaped ring spoof surface plasmon polariton (SSPP) structure is proposed as part of a bandpass filter (BPF) combined with short-circuited stubs (SCSs). The U-shaped ring unit offers miniaturization and multiple adjustable parameters. Furthermore, the lower and upper cutoff [...] Read more.
In this paper, a new U-shaped ring spoof surface plasmon polariton (SSPP) structure is proposed as part of a bandpass filter (BPF) combined with short-circuited stubs (SCSs). The U-shaped ring unit offers miniaturization and multiple adjustable parameters. Furthermore, the lower and upper cutoff frequencies of the passband for the BPF can be adjusted by modifying the structural parameters of the SSPP units and SCSs, respectively. To validate the design, a prototype filter was first created with a frequency range of 2 to 3.7 GHz for the passband and an extended stopband that reached up to 15 GHz. On the basis of the designed BPF, a tri-band filter was realized by introducing multiple transmission zeros by loading multiple open-circuited stubs (OCSs) onto the transmission portion of SSPPs. The center frequencies of the three passbands were 1.20 GHz, 2.03 GHz, and 2.96 GHz, respectively. At the same time, the upper stopband rejection reached up to 12 GHz with an attenuation of −30 dB, about 10 times the center frequency of the first passband. The experimental results demonstrate a strong correlation between the measured and simulated outcomes, thereby validating the proposed structure and design methodology. Notably, the filter measures only 0.38λg × 0.13λg, highlighting its compact size as a significant advantage. Full article
(This article belongs to the Section Microwave and Wireless Communications)
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<p>(<b>a</b>). Configurations of a conventional rectangular-shaped SSPP unit (Type A), (<b>b</b>) ring-shaped SSPP unit (Type B), and (<b>c</b>) the proposed U-shaped ring SSPP unit (Type C).</p>
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<p>Dispersion curves of Type A, Type B, and Type C.</p>
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<p>Dispersion curves of Type C at different parameters (<b>a</b>) <span class="html-italic">h</span> and (<b>b</b>) <span class="html-italic">s</span>.</p>
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<p>Schematic of the designed BPF structure using U-shaped ring SSPPs and SCSs.</p>
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<p>The simulated |S<sub>21</sub>| of the proposed BPF under different (<b>a</b>) heights <span class="html-italic">h</span><sub>4</sub> and (<b>b</b>) groove depths <span class="html-italic">s</span> of the proposed U-shaped ring SSPPs and (<b>c</b>) lengths <span class="html-italic">l</span><sub>1</sub> of SCSs.</p>
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<p>Simulated S-parameters of the designed wide-stopband filter.</p>
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<p>The schematic diagram of the designed tri-band BPF.</p>
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<p>The simulated |S<sub>21</sub>| of different parameters of open stubs. (<b>a</b>) <span class="html-italic">l</span><sub>2</sub>; (<b>b</b>) <span class="html-italic">l</span><sub>3</sub>; (<b>c</b>) <span class="html-italic">g</span><sub>1.</sub></p>
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<p>Photographs of the fabricated tri-band BPF.</p>
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<p>Photograph of Keysight E5071C network analyzer measuring fabricated tri-band BPF.</p>
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<p>Simulated and measured S-parameters of the designed tri-band BPF.</p>
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<p>Simulated electric field profiles of tri-band BPF based on U-shaped ring SSPP cells and open-/short-circuited stubs at (<b>a</b>) 1.20 GHz, (<b>b</b>) 2.03 GHz, (<b>c</b>) 2.96 GHz, and (<b>d</b>) 12 GHz.</p>
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34 pages, 4642 KiB  
Article
BWFER-YOLOv8: An Enhanced Cascaded Framework for Concealed Object Detection
by Khalid Ijaz, Ikramullah Khosa, Ejaz A. Ansari, Syed Farooq Ali, Asif Hussain and Faran Awais Butt
Appl. Sci. 2025, 15(2), 690; https://doi.org/10.3390/app15020690 - 12 Jan 2025
Viewed by 299
Abstract
Contact-free concealed object detection using passive millimeter-wave imaging (PMMWI) sensors is a challenging task due to a low signal-to-noise ratio (SNR) and nonuniform illumination affecting the captured image’s quality. The nonuniform illumination also generates a higher false positive rate due to the limited [...] Read more.
Contact-free concealed object detection using passive millimeter-wave imaging (PMMWI) sensors is a challenging task due to a low signal-to-noise ratio (SNR) and nonuniform illumination affecting the captured image’s quality. The nonuniform illumination also generates a higher false positive rate due to the limited ability to differentiate small hidden objects from the background of images. Several concealed object detection models have demonstrated outstanding performance but failed to combat the above-mentioned challenges concurrently. This paper proposes a novel three-stage cascaded framework named BWFER-YOLOv8, which implements a new alpha-reshuffled bootstrap random sampling method in the first stage, followed by image reconstruction using an adaptive Wiener filter in the second stage. The third stage uses a novel FER-YOLOv8 architecture with a custom-designed feature extraction and regularization (FER) module and multiple regularized convolution (Conv_Reg) modules for better generalization capability. The comprehensive quantitative and qualitative analysis reveals that the proposed framework outperforms the state-of-the-art tiny YOLOv3 and YOLOv8 models by achieving 98.1% precision and recall in detecting concealed weapons. The proposed framework significantly reduces the false positive rate, by up to 1.8%, in the detection of hidden small guns. Full article
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<p>Total terrorism deaths by country in 2022–2023.</p>
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<p>Bibliographic overview of research papers on concealed object detection.</p>
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<p>Trend in various architectures used for concealed weapon detection over last three years.</p>
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<p>PMMW imaging data samples. (<b>a</b>) Optical image with thick clothes. (<b>b</b>) PMMW image. (<b>c</b>) Optical image with thin clothes. (<b>d</b>) PMMW image containing concealed gun. (<b>e</b>) Real-time signature of metal gun.</p>
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<p>Class-imbalanced PMMW image dataset.</p>
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<p>Flowchart of proposed alpha-reshuffled bootstrap random sampling method.</p>
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<p>Comparison between the original and filtered images. (<b>a</b>–<b>d</b>) Original images. (<b>e</b>–<b>h</b>) Filtered images.</p>
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<p>YOLOv8 algorithm.</p>
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<p>The architecture of proposed YOLOv8 algorithm.</p>
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<p>The architectures of the FER and Conv_Reg modules. (<b>a</b>) FER module. (<b>b</b>) Conv_Reg module.</p>
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<p>Proposed framework of research methodology.</p>
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<p>The proposed FER-YOLOv8 architecture’s configuration.</p>
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<p>Confusion matrices of various YOLO models. (<b>a</b>) Tiny YOLOv3. (<b>b</b>) YOLOv8n. (<b>c</b>) YOLOv8m. (<b>d</b>) YOLOv8n-WF. (<b>e</b>) YOLOv8m-WF. (<b>f</b>) Proposed FER-YOLOv8.</p>
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<p>Comparison of mean average precision of various models in percent (%).</p>
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<p>Comparison of mean average precision (mAP) of IoU thresholds ranging from 0.5 to 0.95 of various models in percent (%).</p>
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<p>Comparison of F1-confidence curves of various YOLO models. (<b>a</b>) Tiny YOLOv3 F1-confidence curves. (<b>b</b>) YOLOv8n F1-confidence curves. (<b>c</b>) YOLOv8n-WF F1-confidence curves. (<b>d</b>) YOLOv8m F1-confidence curves. (<b>e</b>) YOLOv8m-WF F1-confidence curves. (<b>f</b>) Proposed FER-YOLOv8 F1-confidence curves.</p>
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<p>Precision–recall curves of tiny YOLOv3 and proposed FER-YOLOv8 models. (<b>a</b>) Tiny YOLOv3 PR curves. (<b>b</b>) Proposed FER-YOLOv8 PR curves.</p>
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<p>Comparison of precision–recall curves of various YOLO models. (<b>a</b>) YOLOv8n PR curves. (<b>b</b>) YOLOv8n-WF PR curves. (<b>c</b>) YOLOv8m PR curves. (<b>d</b>) YOLOv8m-WF PR curves.</p>
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<p>Comparison of computational complexity of various YOLO models.</p>
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<p>Qualitative analysis of the trained models on an accurately detected positive sample. (<b>a</b>) Positive sample from ground truth. (<b>b</b>) Tiny YOLOv3 prediction. (<b>c</b>) YOLOv8n prediction. (<b>d</b>) YOLOv8n-WF prediction. (<b>e</b>) YOLOv8m prediction. (<b>f</b>) YOLOv8m-WF prediction. (<b>g</b>) Proposed FER-YOLOv8 prediction.</p>
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<p>Violin plots showing the distribution of the confidence scores of various models on a test dataset. (<b>a</b>) Tiny YOLOv3 confidence score distribution. (<b>b</b>) YOLOv8n confidence score distribution. (<b>c</b>) YOLOv8n-WF confidence score distribution. (<b>d</b>) YOLOv8m confidence score distribution. (<b>e</b>) YOLOv8m-WF confidence score distribution. (<b>f</b>) Proposed FER-YOLOv8 confidence score distribution.</p>
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<p>Qualitative analysis of the trained models on the falsely detected positive sample. (<b>a</b>) Negative sample from ground truth. (<b>b</b>) Tiny YOLOv3 prediction. (<b>c</b>) YOLOv8n prediction. (<b>d</b>) YOLOv8n-WF prediction. (<b>e</b>) YOLOv8m prediction. (<b>f</b>) YOLOv8m-WF prediction. (<b>g</b>) Proposed FER-YOLOv8 prediction.</p>
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<p>Comparison of feature maps of first layer of various YOLO models.</p>
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33 pages, 41733 KiB  
Review
A Review of Foreign Object Debris Detection on Airport Runways: Sensors and Algorithms
by Jingfeng Shan, Lapo Miccinesi, Alessandra Beni, Lorenzo Pagnini, Andrea Cioncolini and Massimiliano Pieraccini
Remote Sens. 2025, 17(2), 225; https://doi.org/10.3390/rs17020225 - 9 Jan 2025
Viewed by 400
Abstract
The detection of Foreign Object Debris (FOD) is crucial for maintaining safety in critical areas like airport runways. This paper presents a comprehensive review of FOD detection technologies, covering traditional, radar-based, and artificial intelligence (AI)-driven methods. Manual visual inspection and optical sensors, while [...] Read more.
The detection of Foreign Object Debris (FOD) is crucial for maintaining safety in critical areas like airport runways. This paper presents a comprehensive review of FOD detection technologies, covering traditional, radar-based, and artificial intelligence (AI)-driven methods. Manual visual inspection and optical sensors, while widely used, are limited in scalability and reliability under adverse conditions. Radar technologies, such as millimeter-wave radar and synthetic aperture radar, offer robust performance, with advancements in algorithms and sensor fusion significantly enhancing their effectiveness. AI approaches, employing supervised and unsupervised learning, demonstrate potential for automating detection and improving precision, although challenges such as limited datasets and high computational demands persist. This review consolidates the recent progress across these domains, highlighting the need for integrated systems that combine radar and AI to improve adaptability, scalability, and small-FOD detection. By addressing these limitations, the study provides insights into future research directions and the development of innovative FOD detection solutions, contributing to safer and more efficient operational environments. Full article
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<p>Number of papers per year.</p>
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<p>iFerret system [<a href="#B15-remotesensing-17-00225" class="html-bibr">15</a>].</p>
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<p>(<b>a</b>) Images of FOD under test; (<b>b</b>) detection result [<a href="#B14-remotesensing-17-00225" class="html-bibr">14</a>]; (<b>c</b>) FOD detection rover [<a href="#B19-remotesensing-17-00225" class="html-bibr">19</a>].</p>
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<p>Demonstration of radar working principle. (<b>a</b>) Detection with radar; (<b>b</b>) 1D range profile; (<b>c</b>) 2D SAR image; (<b>d</b>) 3D SAR image.</p>
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<p>(<b>a</b>) FOD detection system for controlled environments; (<b>b</b>) FOD detection system for operational environments; (<b>c</b>) images of FOD under test; (<b>d</b>) detection results [<a href="#B53-remotesensing-17-00225" class="html-bibr">53</a>].</p>
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<p>(<b>a</b>) Original detection result; (<b>b</b>) detection result after denosing [<a href="#B55-remotesensing-17-00225" class="html-bibr">55</a>].</p>
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<p>FOD detection prototypes. (<b>a</b>) Before IAA processing; (<b>b</b>) after IAA processing [<a href="#B60-remotesensing-17-00225" class="html-bibr">60</a>].</p>
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<p>Workflow of supervised learning.</p>
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<p>(<b>a</b>) The architecture of spatial transformer network; (<b>b</b>) CNN architecture for FOD classification [<a href="#B87-remotesensing-17-00225" class="html-bibr">87</a>].</p>
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<p>(<b>a</b>) ResNet-101 framework; (<b>b</b>) SPP network framework [<a href="#B91-remotesensing-17-00225" class="html-bibr">91</a>].</p>
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<p>Detailed structure diagram of attention module [<a href="#B11-remotesensing-17-00225" class="html-bibr">11</a>].</p>
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<p>Qualitative comparison between the proposed method and other methods on FOD dataset [<a href="#B113-remotesensing-17-00225" class="html-bibr">113</a>].</p>
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<p>(<b>a</b>) Original signal; (<b>b</b>) detection result with VMD-SVDD method [<a href="#B117-remotesensing-17-00225" class="html-bibr">117</a>].</p>
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18 pages, 3386 KiB  
Article
Adaptive Filtering for Channel Estimation in RIS-Assisted mmWave Systems
by Shuying Shao, Tiejun Lv and Pingmu Huang
Sensors 2025, 25(2), 297; https://doi.org/10.3390/s25020297 - 7 Jan 2025
Viewed by 327
Abstract
The advent of millimeter-wave (mmWave) massive multiple-input multiple-output (MIMO) systems, coupled with reconfigurable intelligent surfaces (RISs), presents a significant opportunity for advancing wireless communication technologies. This integration enhances data transmission rates and broadens coverage areas, but challenges in channel estimation (CE) remain due [...] Read more.
The advent of millimeter-wave (mmWave) massive multiple-input multiple-output (MIMO) systems, coupled with reconfigurable intelligent surfaces (RISs), presents a significant opportunity for advancing wireless communication technologies. This integration enhances data transmission rates and broadens coverage areas, but challenges in channel estimation (CE) remain due to the limitations of the signal processing capabilities of RIS. To address this, we propose an adaptive channel estimation framework comprising two algorithms: log-sum normalized least mean squares (Log-Sum NLMS) and hybrid normalized least mean squares-normalized least mean fourth (Hybrid NLMS-NLMF). These algorithms leverage the sparse nature of mmWave channels to improve estimation accuracy. The Log-Sum NLMS algorithm incorporates a log-sum penalty in its cost function for faster convergence, while the Hybrid NLMS-NLMF employs a mixed error function for better performance across varying signal-to-noise ratio (SNR) conditions. Our analysis also reveals that both algorithms have lower computational complexity compared to existing methods. Extensive simulations validate our findings, with results illustrating the performance of the proposed algorithms under different parameters, demonstrating significant improvements in channel estimation accuracy and convergence speed over established methods, including NLMS, sparse exponential forgetting window least mean square (SEFWLMS), and sparse hybrid adaptive filtering algorithms (SHAFA). Full article
(This article belongs to the Section Communications)
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<p>The RIS-aided wireless communication systems.</p>
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<p>Adaptive filter framework.</p>
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<p>NMSE of different estimation algorithms versus SNR.</p>
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<p>NMSE of different estimation algorithms versus number of iterations at an SNR of 3 dB.</p>
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<p>NMSE of different estimation algorithms versus number of iterations at an SNR of 13 dB.</p>
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<p>Impact of the parameter <math display="inline"><semantics> <mi>α</mi> </semantics></math> on the NMSE performance of the Hybrid NLMS-NLMF algorithm.</p>
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<p>Impact of the parameter <math display="inline"><semantics> <mi>α</mi> </semantics></math> on the convergence trend of the Hybrid NLMS-NLMF algorithm at an SNR of 10 dB.</p>
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<p>Impact of the parameter <math display="inline"><semantics> <mi>ρ</mi> </semantics></math> on the NMSE performance of the Hybrid NLMS-NLMF algorithm.</p>
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<p>Impact of the parameter <math display="inline"><semantics> <mi>ρ</mi> </semantics></math> on the convergence trend of the Hybrid NLMS-NLMF algorithm at an SNR of 10 dB.</p>
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<p>Impact of the parameter <math display="inline"><semantics> <mi>μ</mi> </semantics></math> on the NMSE performance of the Hybrid NLMS-NLMF algorithm.</p>
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<p>Impact of the parameter <math display="inline"><semantics> <mi>μ</mi> </semantics></math> on the convergence trend of the Hybrid NLMS-NLMF algorithm at an SNR of 10 dB.</p>
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<p>Impact of RIS elements on the NMSE performance of the Hybrid NLMS-NLMF algorithm.</p>
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22 pages, 2943 KiB  
Article
Characterization of 77 GHz Radar Backscattering from Sea Surfaces at Low Incidence Angles: Preliminary Results
by Qinghui Xu, Chen Zhao, Zezong Chen, Sitao Wu, Xiao Wang and Lingang Fan
Remote Sens. 2025, 17(1), 116; https://doi.org/10.3390/rs17010116 - 1 Jan 2025
Viewed by 439
Abstract
Millimeter-wave (MMW) radar is capable of providing high temporal–spatial measurements of the ocean surface. Some topics, such as the characterization of the radar echo, have attracted widespread attention from researchers. However, most existing research studies focus on the backscatter of the ocean surface [...] Read more.
Millimeter-wave (MMW) radar is capable of providing high temporal–spatial measurements of the ocean surface. Some topics, such as the characterization of the radar echo, have attracted widespread attention from researchers. However, most existing research studies focus on the backscatter of the ocean surface at low microwave bands, while the sea surface backscattering mechanism in the 77 GHz frequency band remains not well interpreted. To address this issue, in this paper, the investigation of the scattering mechanism is carried out for the 77 GHz frequency band ocean surface at small incidence angles. The backscattering coefficient is first simulated by applying the quasi-specular scattering model and the corrected scattering model of geometric optics (GO4), using two different ocean wave spectrum models (the Hwang spectrum and the Kudryavtsev spectrum). Then, the dependence of the sea surface normalized radar cross section (NRCS) on incidence angles, azimuth angles, and sea states are investigated. Finally, by comparison between model simulations and the radar-measured data, the 77 GHz frequency band scattering characterization of sea surfaces at the near-nadir incidence is verified. In addition, experimental results from the wave tank are shown, and the difference in the scattering mechanism is further discussed between water surfaces and oceans. The obtained results seem promising for a better understanding of the ocean surface backscattering mechanism in the MMW frequency band. It provides a new method for fostering the usage of radar technologies for real-time ocean observations. Full article
(This article belongs to the Topic Radar Signal and Data Processing with Applications)
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<p>The geometry for MMW radar observations.</p>
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<p>Experimental set-up for sea surface observations. The device in the blue circle is the UAV with the MMW radar. The red circle is the site of the wave buoy.</p>
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<p>Experimental set-up in the wave tank. The radar was fixed on the stationary red bridge at a height of about <math display="inline"><semantics> <mrow> <mn>13.5</mn> </mrow> </semantics></math> m.</p>
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<p>The range spectrum of single-chirp signal for the sea surface observation.</p>
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<p>The attitude of the UAV platform.</p>
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<p>Experimental set-up for the external calibration. (<b>a</b>) The geometry for the external calibration. The UAV with the MMW radar hovered in the air, and the trihedral corner reflector was placed on the ground. (<b>b</b>) The measurement environment from the view of the camera in the UAV.</p>
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<p>The simulated NRCS from two theoretical electromagnetic scattering models versus incidence angle with four sea states (<math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math>) in the 77 GHz frequency band. (<b>a</b>) Results from the Gaussian QS (QS-G) model in the upwind direction. (<b>b</b>) Results from the Gaussian GO4 (GO4-G) model in the upwind direction. (<b>c</b>) Results from the QS model in the crosswind direction. (<b>d</b>) Results from the GO4 mode in the crosswind direction.</p>
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<p>The simulated NRCS from two scattering models versus incidence angle with four sea states (<math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math>) in the 77 GHz frequency band. (<b>a</b>) Results from the QS model in the upwind direction. (<b>b</b>) Results from the GO4 model in the upwind direction. (<b>c</b>) Results from the QS model in the crosswind direction. (<b>d</b>) Results from the GO4 mode in the crosswind direction.</p>
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<p>The NRCS versus the <math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math> under three incidence angles (<math display="inline"><semantics> <msup> <mn>5</mn> <mo>∘</mo> </msup> </semantics></math>, <math display="inline"><semantics> <msup> <mn>10</mn> <mo>∘</mo> </msup> </semantics></math>, and <math display="inline"><semantics> <msup> <mn>15</mn> <mo>∘</mo> </msup> </semantics></math> incidence angles) for two sea spectrum models. (<b>a</b>) Results from the H spectrum in upwind directions. (<b>b</b>) Results from the K spectrum in upwind directions. (<b>c</b>) Results from the H spectrum in crosswind directions. (<b>d</b>) Results from the K spectrum in crosswind directions.</p>
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<p>The error <math display="inline"><semantics> <mrow> <mi>e</mi> <mi>r</mi> <mi>r</mi> </mrow> </semantics></math> as a function of <math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math> using the K spectrum. Curves with circles and squares represent the results in upwind and crosswind directions.</p>
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<p>The simulated NRCS versus azimuth angles with two sea states in the 77 GHz frequency band by the H spectrum and K spectrum, at different incidence angles. (<b>a</b>–<b>c</b>) Results from the <math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math> of <math display="inline"><semantics> <mrow> <mn>0.45</mn> </mrow> </semantics></math> m at <math display="inline"><semantics> <msup> <mn>5</mn> <mo>∘</mo> </msup> </semantics></math> incidence, <math display="inline"><semantics> <msup> <mn>10</mn> <mo>∘</mo> </msup> </semantics></math> incidence, and <math display="inline"><semantics> <msup> <mn>15</mn> <mo>∘</mo> </msup> </semantics></math> incidence. (<b>d</b>–<b>f</b>) Results from the <math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math> of <math display="inline"><semantics> <mrow> <mn>1.08</mn> </mrow> </semantics></math> m.</p>
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<p>The error <math display="inline"><semantics> <mrow> <mi>e</mi> <mi>r</mi> <mi>r</mi> </mrow> </semantics></math> as a function of azimuth angles using the H spectrum. The blue solid line, the green dotted line, and red dotted line represent the results obtained from the <math display="inline"><semantics> <msup> <mn>5</mn> <mo>∘</mo> </msup> </semantics></math>, <math display="inline"><semantics> <msup> <mn>10</mn> <mo>∘</mo> </msup> </semantics></math>, and <math display="inline"><semantics> <msup> <mn>15</mn> <mo>∘</mo> </msup> </semantics></math> incidences, respectively.</p>
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<p>The obtained NRCS versus incidence angles with six sea states in upwind directions. (<b>a</b>) Ocean surfaces with the <math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math> of <math display="inline"><semantics> <mrow> <mn>0.33</mn> </mrow> </semantics></math> m. (<b>b</b>) Ocean surfaces with the <math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math> of <math display="inline"><semantics> <mrow> <mn>0.40</mn> </mrow> </semantics></math> m. (<b>c</b>) Ocean surfaces with the <math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math> of <math display="inline"><semantics> <mrow> <mn>0.43</mn> </mrow> </semantics></math> m. (<b>d</b>) Ocean surfaces with the <math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math> of <math display="inline"><semantics> <mrow> <mn>0.48</mn> </mrow> </semantics></math> m. (<b>e</b>) Ocean surfaces with the <math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math> of <math display="inline"><semantics> <mrow> <mn>0.52</mn> </mrow> </semantics></math> m. (<b>f</b>) Ocean surfaces with the <math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math> of <math display="inline"><semantics> <mrow> <mn>0.63</mn> </mrow> </semantics></math> m. Errorbars are <math display="inline"><semantics> <mrow> <mo>±</mo> <mn>1</mn> </mrow> </semantics></math> standard deviation.</p>
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<p>Comparison of the NRCS (in dB) obtained from the upwind directions in near-nadir-radar sea surface observations. The <math display="inline"><semantics> <msub> <mi>H</mi> <mi>s</mi> </msub> </semantics></math> of six datasets are <math display="inline"><semantics> <mrow> <mn>0.33</mn> </mrow> </semantics></math> m, <math display="inline"><semantics> <mrow> <mn>0.40</mn> </mrow> </semantics></math> m, <math display="inline"><semantics> <mrow> <mn>0.43</mn> </mrow> </semantics></math> m, <math display="inline"><semantics> <mrow> <mn>0.48</mn> </mrow> </semantics></math> m, <math display="inline"><semantics> <mrow> <mn>0.52</mn> </mrow> </semantics></math> m, and <math display="inline"><semantics> <mrow> <mn>0.63</mn> </mrow> </semantics></math> m, respectively. Errorbars are <math display="inline"><semantics> <mrow> <mo>±</mo> <mn>1</mn> </mrow> </semantics></math> standard deviation.</p>
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<p>The obtained NRCS from the wave tank observation in the upwind direction. (<b>a</b>) The irregular wave water surfaces. (<b>b</b>) The wave tank experiments with regular waves.</p>
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<p>The relative NRCS as a function of <math display="inline"><semantics> <mi>θ</mi> </semantics></math> for the results obtained from water and ocean surfaces in the 77 GHz frequency band. The results from two observations are shown in the red triangle line and green rhombus line, respectively. Curves with circles represent the relative difference (in dB) between the results from water and sea surfaces.</p>
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<p>Wave profile from regular waves in the wave tank.</p>
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20 pages, 11484 KiB  
Article
Tunable Filters Using Defected Ground Structures at Millimeter-Wave Frequencies
by Kaushik Annam, Birhanu Alemayehu, Eunsung Shin and Guru Subramanyam
Micromachines 2025, 16(1), 60; https://doi.org/10.3390/mi16010060 - 31 Dec 2024
Viewed by 504
Abstract
This paper explores the potential of phase change materials (PCM) for dynamically tuning the frequency response of a dumbbell u-slot defected ground structure (DGS)-based band stop filter. The DGSs are designed using co-planar waveguide (CPW) line structure on top of a barium strontium [...] Read more.
This paper explores the potential of phase change materials (PCM) for dynamically tuning the frequency response of a dumbbell u-slot defected ground structure (DGS)-based band stop filter. The DGSs are designed using co-planar waveguide (CPW) line structure on top of a barium strontium titanate (Ba0.6Sr0.4TiO3) (BST) thin film. BST film is used as the high-dielectric material for the planar DGS. Lower insertion loss of less than −2 dB below the lower cutoff frequency, and enhanced band-rejection with notch depth of −39.64 dB at 27.75 GHz is achieved by cascading two-unit cells, compared to −12.26 dB rejection with a single-unit cell using BST thin film only. Further tunability is achieved by using a germanium telluride (GeTe) PCM layer. The electrical properties of PCM can be reversibly altered by transitioning between amorphous and crystalline phases. We demonstrate that incorporating a PCM layer into a DGS device allows for significant tuning of the resonance frequency: a shift in resonance frequency from 30.75 GHz to 33 GHz with a frequency shift of 2.25 GHz is achieved, i.e., 7.32% tuning is shown with a single DGS cell. Furthermore, by cascading two DGS cells with PCM, an even wider tuning range is achievable: a shift in resonance frequency from 27 GHz to 30.25 GHz with a frequency shift of 3.25 GHz is achieved, i.e., 12.04% tuning is shown by cascading two DGS cells. The results are validated through simulations and measurements, showcasing excellent agreement. Full article
(This article belongs to the Special Issue Microwave Passive Components, 2nd Edition)
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<p>Dumbbell DGS on CPW line.</p>
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<p>U-slot DGS on CPW line.</p>
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<p>Dumbbell u-slot DGS on CPW line.</p>
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<p>Schematic representation of the fabrication process of a dumbbell u-slot DGS using CPW line configuration with BST thin film.</p>
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<p>(<b>a</b>) Simulated frequency response of dumbbell u-slot DGS. (<b>b</b>) Measured frequency response of dumbbell u-slot DGS. (<b>c</b>) Simulated vs. measured S<sub>21</sub> frequency response of dumbbell u-slot DGS.</p>
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<p>(<b>a</b>) Simulated frequency response of dumbbell u-slot DGS. (<b>b</b>) Measured frequency response of dumbbell u-slot DGS. (<b>c</b>) Simulated vs. measured S<sub>21</sub> frequency response of dumbbell u-slot DGS.</p>
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<p>Simulated vs. measured S<sub>21</sub> frequency response of dumbbell DGS.</p>
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<p>Simulated vs. measured S<sub>21</sub> frequency response of u-slot DGS.</p>
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<p>Circuit model for dumbbell u-slot DGS.</p>
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<p>Dumbbell u-slot DGS cascade.</p>
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<p>(<b>a</b>) Simulated frequency response of cascaded dumbbell u-slot DGS. (<b>b</b>) Measured frequency response of cascaded dumbbell u-slot DGS. (<b>c</b>) Simulated vs. measured S<sub>21</sub> frequency response of cascaded dumbbell u-slot DGS.</p>
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<p>(<b>a</b>) Simulated frequency response of cascaded dumbbell u-slot DGS. (<b>b</b>) Measured frequency response of cascaded dumbbell u-slot DGS. (<b>c</b>) Simulated vs. measured S<sub>21</sub> frequency response of cascaded dumbbell u-slot DGS.</p>
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<p>Circuit model for cascaded dumbbell u-slot DGS.</p>
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<p>Schematic model vs. measured S<sub>21</sub> frequency response of cascade dumbbell u-slot DGS.</p>
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<p>Dumbbell u-slot DGS on CPW line with PCM.</p>
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<p>Schematic representation of the fabrication process of a dumbbell u-slot DGS using CPW line configuration with BST and GeTe thin films.</p>
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<p>Frequency response of dumbbell u-slot DGS with PCM. (<b>a</b>) Simulation—amorphous state. (<b>b</b>) Simulation—crystalline state. (<b>c</b>) Measured—amorphous state. (<b>d</b>) Measured—crystalline state. (<b>e</b>) Simulation vs measured S<sub>21</sub>—amorphous state. (<b>f</b>) Simulation vs measured S<sub>21</sub>—crystalline state.</p>
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<p>Frequency response of dumbbell u-slot DGS with PCM. (<b>a</b>) Simulation—amorphous state. (<b>b</b>) Simulation—crystalline state. (<b>c</b>) Measured—amorphous state. (<b>d</b>) Measured—crystalline state. (<b>e</b>) Simulation vs measured S<sub>21</sub>—amorphous state. (<b>f</b>) Simulation vs measured S<sub>21</sub>—crystalline state.</p>
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<p>Frequency response of dumbbell u-slot DGS with PCM. (<b>a</b>) Simulation—amorphous state. (<b>b</b>) Simulation—crystalline state. (<b>c</b>) Measured—amorphous state. (<b>d</b>) Measured—crystalline state. (<b>e</b>) Simulation vs measured S<sub>21</sub>—amorphous state. (<b>f</b>) Simulation vs measured S<sub>21</sub>—crystalline state.</p>
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<p>Dumbbell u-slot DGS with PCM cascade.</p>
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<p>Frequency response of dumbbell u-slot DGS cascade with PCM. (<b>a</b>) Simulation—amorphous state. (<b>b</b>) Simulation—crystalline state. (<b>c</b>) Measured—amorphous state. (<b>d</b>) Measured—crystalline state. (<b>e</b>) Simulation vs measured—amorphous state. (<b>f</b>) Simulation vs measured—crystalline state.</p>
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<p>Frequency response of dumbbell u-slot DGS cascade with PCM. (<b>a</b>) Simulation—amorphous state. (<b>b</b>) Simulation—crystalline state. (<b>c</b>) Measured—amorphous state. (<b>d</b>) Measured—crystalline state. (<b>e</b>) Simulation vs measured—amorphous state. (<b>f</b>) Simulation vs measured—crystalline state.</p>
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<p>Frequency response of dumbbell u-slot DGS cascade with PCM. (<b>a</b>) Simulation—amorphous state. (<b>b</b>) Simulation—crystalline state. (<b>c</b>) Measured—amorphous state. (<b>d</b>) Measured—crystalline state. (<b>e</b>) Simulation vs measured—amorphous state. (<b>f</b>) Simulation vs measured—crystalline state.</p>
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15 pages, 2718 KiB  
Article
Protein-Based Mechanism of Wheat Growth Under Salt Stress in Seeds Irradiated with Millimeter Waves
by Setsuko Komatsu, Rachel Koh, Hisateru Yamaguchi, Keisuke Hitachi and Kunihiro Tsuchida
Int. J. Mol. Sci. 2025, 26(1), 253; https://doi.org/10.3390/ijms26010253 - 30 Dec 2024
Viewed by 378
Abstract
Wheat is one of the most extensively grown crops in the world; however, its productivity is reduced due to salinity. This study focused on millimeter wave (MMW) irradiation to clarify the salt-stress tolerance mechanism in wheat. In the present study, wheat-root growth, which [...] Read more.
Wheat is one of the most extensively grown crops in the world; however, its productivity is reduced due to salinity. This study focused on millimeter wave (MMW) irradiation to clarify the salt-stress tolerance mechanism in wheat. In the present study, wheat-root growth, which was suppressed to 77.6% of the control level under salt stress, was recovered to the control level by MMW irradiation. To reveal the salt-stress tolerance mechanism of MMW irradiation on wheat, a proteomic analysis was conducted. Proteins related to cell cycle, proliferation, and transport in biological processes, as well as proteins related to the nucleus, cytoskeleton, and cytoplasm within cellular components, were inversely correlated with the number of proteins. The results of the proteomic analysis were verified by immunoblot and other analyses. Among the proteins related to the scavenging reactive-oxygen species, superoxide dismutase and glutathione reductase accumulated under salt stress and further increased in the MMW-irradiated wheat. Among pathogen-related proteins, pathogenesis-related protein 1 and the Bowman–Birk proteinase inhibitor decreased under salt stress and recovered to the control level in the MMW-irradiated wheat. The present results indicate that MMW irradiation of wheat seeds improves plant-growth recovery from salt stress through regulating the reactive oxygen species-scavenging system and the pathogen-related proteins. These genes may contribute to the development of salt-stress-tolerant wheat through marker-assisted breeding and genome editing. Full article
(This article belongs to the Collection Feature Papers in Molecular Plant Sciences)
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<p>Morphological effects on MMW-irradiated wheat treated with salt stress. Wheat seeds were irradiated with or without MMW and sown. For nontreated groups, wheat seedlings were collected 5 days after sowing (<a href="#app1-ijms-26-00253" class="html-app">Figure S1</a>). For the salt-stress groups, 3-day-old wheat plants were subjected to salt stress for 2 days and collected (<b>A</b>). As seedling collection, leaf (green column) and root (orange column) were collected. As morphological parameters, leaf length (<b>B</b>), leaf-fresh weight (<b>C</b>), main-root length (<b>D</b>), and total-root fresh weight (<b>E</b>) were measured. The bar in the picture indicates 10 mm. Data are shown as the mean ± SD from 3 independent biological replicates (<a href="#app1-ijms-26-00253" class="html-app">Figure S2</a>), with 10 plants per each replicate. Asterisks indicate significant changes between the 2 groups using Student’s <span class="html-italic">t</span>-test (* <span class="html-italic">p</span> &lt; 0.05).</p>
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<p>Summary of whole-proteomic data for 12 wheat samples based on principal-component analysis. Wheat seeds irradiated with or without MMW were sown, and the 3-day-old seedlings were treated with or without salt stress for 2 days. Roots from 4 groups were collected, which were unirradiated/nontreated (orange), irradiated/nontreated (blue), unirradiated/salt stress (red), and irradiated/salt stress (green). Proteomics was carried out on three independent biological replicates for each treatment. Principal-component analysis was conducted using Proteome Discoverer.</p>
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<p>Functional categorization of differentially abundant proteins using proteomic analysis. Wheat seeds were irradiated with (irradiated) or without (unirradiated) MMW, and the seedlings were treated with (salt stress) or without (nontreated) salt stress. After the proteomic analysis of proteins extracted from the roots, functional classification of significantly increased (orange) and decreased (blue) proteins (<span class="html-italic">p</span> &lt; 0.05) from unirradiated (<b>A</b>) or irradiated (<b>B</b>) wheat treated with or without salt stress was performed using gene-ontology analysis (<a href="#app1-ijms-26-00253" class="html-app">Tables S3 and S4</a>).</p>
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<p>Immunoblot analysis of proteins changed in the ROS-scavenging system of wheat irradiated with MMW under salt stress. Wheat seeds irradiated with or without MMW were sown, and seedlings were treated with or without salt stress. Proteins extracted from the root and leaf of wheat were separated on SDS-polyacrylamide gel by electrophoresis. Coomassie-brilliant blue staining pattern was used as a loading control (<a href="#app1-ijms-26-00253" class="html-app">Figure S3</a>). Proteins transferred onto membranes were cross-reacted with anti-SOD 1 (Cu/Zn SOD) (<b>A</b>), GR (<b>B</b>), and APX (<b>C</b>,<b>D</b>) antibodies. The integrated density of the bands was calculated with ImageJ software. Data are shown as the mean ± SD from 3 independent biological replicates (<a href="#app1-ijms-26-00253" class="html-app">Figures S4–S6</a>). Statistical analysis is the same as in <a href="#ijms-26-00253-f001" class="html-fig">Figure 1</a> (*, <span class="html-italic">p</span> &lt; 0.05; **, <span class="html-italic">p</span> &lt; 0.01; and ***, <span class="html-italic">p</span> &lt; 0.001).</p>
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<p>Immunoblot analysis of proteins involved in pathogen resistance in wheat irradiated with MMW under salt stress. The experimental procedures were the same as in <a href="#ijms-26-00253-f004" class="html-fig">Figure 4</a>. The membranes were cross-reacted with anti-pathogenesis-related protein 1 (<b>A</b>), chitinase (<b>B</b>), thaumatin (<b>C</b>), and Bowman–Birk proteinase inhibitor (<b>D</b>) antibodies. Data are shown as the mean ± SD from 3 independent biological replicates (<a href="#app1-ijms-26-00253" class="html-app">Figures S7–S10</a>). The statistical analysis is the same as in <a href="#ijms-26-00253-f001" class="html-fig">Figure 1</a> (*, <span class="html-italic">p</span> &lt; 0.05; **, <span class="html-italic">p</span> &lt; 0.01; and ***, <span class="html-italic">p</span> &lt; 0.001).</p>
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<p>The expression of gene-encoding nucleoporin in wheat irradiated with MMW under salt stress. Wheat seeds were irradiated with or without MMW, and seedlings were treated with or without salt stress. After isolating total RNA from root and leaf samples, <span class="html-italic">18S rRNA</span> (<b>A</b>)—specific and <span class="html-italic">nucleoporin</span> (<b>B</b>)—specific oligonucleotides were amplified using PCR. <span class="html-italic">18S rRNA</span> was used as an internal control. After agarose-gel electrophoresis, the integrated densities of bands were calculated using ImageJ software. Data are shown as the mean ± SD from 3 independent biological replicates.</p>
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<p>The starch contents in wheat irradiated with MMW under salt stress. Wheat seeds were irradiated with or without MMW, and seedlings were treated with or without salt stress. Starch was extracted from roots and leaves. A portion (10 mg) of samples was ground in 1 mL of phosphate-buffered saline. Free glucose and small oligosaccharides were removed with ethanol. After centrifugation, the soluble starch in the pellet was extracted with 1 mL of water. The contents were analyzed using a Starch Assay Kit. The picture shows the color of the sample after the reaction. Data are shown as the mean ± SD from three independent biological replicates. Statistical analysis is the same as in <a href="#ijms-26-00253-f001" class="html-fig">Figure 1</a> (*, <span class="html-italic">p</span> &lt; 0.05).</p>
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15 pages, 4321 KiB  
Article
Feasibility Study of Real-Time Speech Detection and Characterization Using Millimeter-Wave Micro-Doppler Radar
by Nati Steinmetz and Nezah Balal
Remote Sens. 2025, 17(1), 91; https://doi.org/10.3390/rs17010091 - 29 Dec 2024
Viewed by 538
Abstract
This study presents a novel approach to remote speech recognition using a millimeter-wave micro-Doppler radar system operating at 94 GHz. By detecting micro-Doppler speech-related vibrations, the system enables non-contact and privacy-preserving speech recognition. Initial experiments used a piezoelectric crystal to simulate vocal cord [...] Read more.
This study presents a novel approach to remote speech recognition using a millimeter-wave micro-Doppler radar system operating at 94 GHz. By detecting micro-Doppler speech-related vibrations, the system enables non-contact and privacy-preserving speech recognition. Initial experiments used a piezoelectric crystal to simulate vocal cord vibrations, followed by tests with actual human speech. Advanced signal processing techniques, including short-time Fourier transform (STFT), were used to generate spectrograms and reconstruct speech signals. The system demonstrated high accuracy, with cross-correlation analysis quantitatively confirming a strong correlation between radar-reconstructed and original audio signals. These results validate the effectiveness of detecting and characterizing speech-related vibrations without direct audio recording. The findings have significant implications for applications in noisy industrial environments, enabling robust voice interaction capabilities, as well as in healthcare diagnostics and assistive technologies, where contactless and privacy-preserving solutions are essential. Future research will explore diverse real-world scenarios and the integration of advanced signal processing and machine learning techniques to further enhance accuracy and robustness. Full article
(This article belongs to the Special Issue Remote Sensing in 2024)
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<p>CW micro-Doppler radar.</p>
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<p>Integration time as a function of carrier frequency for different velocity resolutions. The curves illustrate the inverse relationship between carrier frequency and integration time, showing that higher carrier frequencies enable shorter integration times for achieving desired velocity resolutions. This highlights the advantage of millimeter-wave frequencies for rapid and precise measurements.</p>
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<p>Signal Processing Flowchart for Radar-Based Speech Recognition.</p>
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<p>Schematic diagram of the experimental setup.</p>
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<p>Spectrograms of directly recorded audio (<b>a</b>) and radar return (<b>b</b>) for chirp signal measurement.</p>
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<p>Spectrograms of directly recorded audio (<b>a</b>) and radar return (<b>b</b>) for an audio file measurement.</p>
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<p>Spectrograms of radar return (<b>a</b>) and directly recorded audio (<b>b</b>) for a single-frequency tone measurement.</p>
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<p>Time domain representations of the high-quality microphone signal (<b>a</b>) and the noisy MMW radar signal (<b>b</b>) captured simultaneously.</p>
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<p>Frequency spectra of the microphone signal (<b>a</b>) and the MMW radar signal (<b>b</b>).</p>
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<p>Comparison of the original microphone signal (dotted yellow line), noisy radar signal reflected from the subject’s throat (solid blue line), and Wiener-filtered radar signal (dashed red line). Note how the filtered signal closely resembles the original microphone signal.</p>
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<p>Cross-correlation between the original microphone signal and the processed radar signal.</p>
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20 pages, 8171 KiB  
Article
Alignment of Fabry–Pérot Cavities for Optomechanical Acceleration Measurements
by Marina Rezinkina and Claus Braxmaier
Photonics 2025, 12(1), 15; https://doi.org/10.3390/photonics12010015 - 27 Dec 2024
Viewed by 396
Abstract
The wave optics processes in a Fabry–Pérot cavity with a length of about tens of millimeters are considered. Such cavities are used, among other applications, in optomechanical accelerometers for precise measurement of displacement of moving elements. A Fabry–Pérot cavity formed by a spherical [...] Read more.
The wave optics processes in a Fabry–Pérot cavity with a length of about tens of millimeters are considered. Such cavities are used, among other applications, in optomechanical accelerometers for precise measurement of displacement of moving elements. A Fabry–Pérot cavity formed by a spherical and flat mirror is considered. The influence of parameters characterizing the alignment of the Fabry–Pérot cavity mirrors and the laser beam on the appearance of the higher order modes is investigated using numerical modeling. It is shown that the angle of inclination of the flat mirror of the cavity greatly affects the occurrence of higher order modes in addition to the fundamental mode. The levels of displacement of the axis of a spherical mirror in the vertical direction which do not cause the emergence of higher order modes is shown. The influence of the degree of displacement of the laser beam axis in the vertical direction relative to the symmetry axis of the Fabry–Pérot cavity is also investigated. Full article
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Figure 1

Figure 1
<p>Computational domain with grid. <span class="html-italic">y</span> = 0 corresponds to the cavity axis of symmetry.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>).</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) at the vertical displacement level <span class="html-italic">a<sub>y</sub></span>/<span class="html-italic">w</span><sub>0</sub> = 0.15.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) at the displacement level <span class="html-italic">a<sub>y</sub></span>/<span class="html-italic">w</span><sub>0</sub> = 0.3.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) for the case of one flat and one curved mirror of the Fabry–Pérot cavity. <span class="html-italic">A</span><sub>1</sub> = 0.99, <span class="html-italic">A</span><sub>2</sub> = 0.01.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) at the level of the plane mirror tilt α = 0.003°. <span class="html-italic">A</span><sub>1</sub> = 0.97, <span class="html-italic">A</span><sub>2</sub> = 0.02, and <span class="html-italic">A</span><sub>3</sub> = 0.01.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) at the level of the plane mirror tilt α = 0.01°. <span class="html-italic">A</span><sub>1</sub> = 0.84, <span class="html-italic">A</span><sub>2</sub> = 0.16.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) at the level of the plane mirror tilt α = 0.012°. <span class="html-italic">A</span><sub>1</sub> = 0.78, <span class="html-italic">A</span><sub>2</sub> = 0.22.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) at the level of the plane mirror tilt α = 0.014°. <span class="html-italic">A</span><sub>1</sub> = 0.73, <span class="html-italic">A</span><sub>2</sub> = 0.27.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) at the level of the plane mirror tilt α = 0.015°. <span class="html-italic">A</span><sub>1</sub> = 0.69, <span class="html-italic">A</span><sub>2</sub> = 0.295, and <span class="html-italic">A</span><sub>3</sub> = 0.015.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) at the level of the plane mirror tilt α = 0.02°. <span class="html-italic">A</span><sub>1</sub> = 0.53, <span class="html-italic">A</span><sub>2</sub> = 0.39, and <span class="html-italic">A</span><sub>3</sub> = 0.08.</p>
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<p>Calculated dependencies of the normalized amplitude of the fundamental mode <span class="html-italic">A</span><sub>1</sub>: (<b>a</b>)—<span class="html-italic">A</span><sub>1</sub> (α); (<b>b</b>)—<span class="html-italic">A</span><sub>1</sub> (<span class="html-italic">b<sub>R</sub></span>); and (<b>c</b>)—<span class="html-italic">A</span><sub>1</sub> (Δ<span class="html-italic">H</span>) (where curve 1 corresponds to the case of absence of displacements of α and <span class="html-italic">b<sub>R</sub></span>; curve 2 corresponds to the case of the levels of displacements of α and <span class="html-italic">b<sub>R</sub></span>: α = 0.003°, <span class="html-italic">b<sub>R</sub></span> = <span class="html-italic">h<sub>cav</sub></span> × 0.005 = 0.03 mm). A high-frequency mode with the normalized amplitude <span class="html-italic">A</span><sub>2 =</sub> 1 − <span class="html-italic">A</span><sub>1</sub> appears at 0.5 &lt; <span class="html-italic">A</span><sub>1</sub> ≤ 0.97; at <span class="html-italic">A</span><sub>1</sub> &lt; 0.5, the wave splits into three or more modes.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) for the level of the spherical Fabry–Pérot cavity mirror axis displacement in the vertical direction <span class="html-italic">b<sub>R</sub></span> = <span class="html-italic">h<sub>cav</sub></span> × 0.05 = 0.3 mm. <span class="html-italic">A</span><sub>0</sub> = 0.15, <span class="html-italic">A</span><sub>1</sub> = 0.32, <span class="html-italic">A</span><sub>2</sub> = 0.3, <span class="html-italic">A</span><sub>3</sub> = 0.17, <span class="html-italic">A</span><sub>4</sub> = 0.05, and <span class="html-italic">A</span><sub>5</sub> = 0.01 (where <span class="html-italic">A<sub>n</sub></span> is the normalized amplitude of the <span class="html-italic">n</span>–mode).</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) for the level of the spherical Fabry–Pérot cavity mirror axis displacement in the vertical direction <span class="html-italic">b<sub>R</sub></span> = <span class="html-italic">h<sub>cav</sub></span> × 0.02 = 0.12 mm. <span class="html-italic">A</span><sub>1</sub> = 0.72, <span class="html-italic">A</span><sub>2</sub> = 0.27, and <span class="html-italic">A</span><sub>3</sub> = 0.01.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) for the level of the spherical Fabry–Pérot cavity mirror axis displacement in the vertical direction <span class="html-italic">b<sub>R</sub></span> = <span class="html-italic">h<sub>cav</sub></span> × 0.01 = 0.06 mm. <span class="html-italic">A</span><sub>1</sub> = 0.91, <span class="html-italic">A</span><sub>2</sub> = 0.09.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) for the level of the spherical Fabry–Pérot cavity mirror axis displacement in the vertical direction <span class="html-italic">b<sub>R</sub></span> = <span class="html-italic">h<sub>cav</sub></span> × 0.005 = 0.03 mm. <span class="html-italic">A</span><sub>1</sub> = 0.97, <span class="html-italic">A</span><sub>2</sub> = 0.018, and <span class="html-italic">A</span><sub>3</sub> = 0.012.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>), (<b>c</b>) for the level of the offset of the laser beam axis Δ<span class="html-italic">H</span> = 0.06 × <span class="html-italic">D<sub>L</sub></span> = 0.03 mm. <span class="html-italic">A</span><sub>1</sub> = 0.97, <span class="html-italic">A</span><sub>2</sub> = 0.03.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>), (<b>c</b>) for the level of the offset of the laser beam axis Δ<span class="html-italic">H</span> = 0.125 × <span class="html-italic">D<sub>L</sub></span> = 0.0625 mm. <span class="html-italic">A</span><sub>1</sub> = 0.91, <span class="html-italic">A</span><sub>2</sub> = 0.09.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>), (<b>c</b>) for the level of the offset of the laser beam axis Δ<span class="html-italic">H</span> = 0.25 × <span class="html-italic">D<sub>L</sub></span> = 0.125 mm. <span class="html-italic">A</span><sub>1</sub> = 0.70, <span class="html-italic">A</span><sub>2</sub> = 0.29, and <span class="html-italic">A</span><sub>3</sub> = 0.01.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>), (<b>c</b>) for the level of the offset of the laser beam axis Δ<span class="html-italic">H</span> = 0.5 × <span class="html-italic">D<sub>L</sub></span> = 0.25 mm. <span class="html-italic">A</span><sub>1</sub> = 0.40, <span class="html-italic">A</span><sub>2</sub> = 0.26, and <span class="html-italic">A</span><sub>3</sub> = 0.08.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) for the levels of the offsets α = 0.003°, <span class="html-italic">b<sub>R</sub></span> = 0, Δ<span class="html-italic">H</span> = −0.06 × <span class="html-italic">D<sub>L</sub></span> = −0.03 mm. <span class="html-italic">A</span><sub>1</sub> = 0.92, <span class="html-italic">A</span><sub>2</sub> = 0.075, and <span class="html-italic">A</span><sub>3</sub> = 0.005.</p>
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<p>Calculated curves of the resonance sweep for the frequency range, including the two main resonant frequencies (<b>a</b>) and near the first resonance (<b>b</b>) for the levels of the offsets α = 0, <span class="html-italic">b<sub>R</sub></span> = <span class="html-italic">h<sub>cav</sub></span> × 0.005 = 0.03 mm, and Δ<span class="html-italic">H</span> = −0.06 × <span class="html-italic">D<sub>L</sub></span> = −0.03 mm. <span class="html-italic">A</span><sub>1</sub> = 0.91, <span class="html-italic">A</span><sub>2</sub> = 0.085, and <span class="html-italic">A</span><sub>3</sub> = 0.005.</p>
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22 pages, 6720 KiB  
Article
Gridless DOA Estimation with Extended Array Aperture in Automotive Radar Applications
by Pengyu Jiang, Silin Gao, Jie Zhao, Zhe Zhang and Bingchen Zhang
Remote Sens. 2025, 17(1), 33; https://doi.org/10.3390/rs17010033 - 26 Dec 2024
Viewed by 368
Abstract
Millimeter-wave automotive radar has become an essential tool for autonomous driving, providing reliable sensing capabilities under various environmental conditions. To reduce hardware size and cost, sparse arrays are widely employed in automotive radar systems. Additionally, because the targets detected by automotive radar typically [...] Read more.
Millimeter-wave automotive radar has become an essential tool for autonomous driving, providing reliable sensing capabilities under various environmental conditions. To reduce hardware size and cost, sparse arrays are widely employed in automotive radar systems. Additionally, because the targets detected by automotive radar typically exhibit sparsity, compressed sensing-based algorithms have been utilized for sparse array reconstruction, achieving superior performance. However, traditional compressed sensing algorithms generally assume that targets are located on a finite set of grid points and perform sparse reconstruction based on predefined grids. When targets are off-grid, significant off-grid errors can occur. To address this issue, we propose an automotive radar sparse reconstruction algorithm based on accelerated Atomic Norm Minimization (ANM). By using the Iterative Vandermonde Decomposition and Shrinkage Threshold (IVDST) algorithm, we can achieve fast ANM, which effectively mitigates off-grid errors while reducing reconstruction complexity. Furthermore, we adopt a Generalized Likelihood Ratio Test (GLRT) detector to eliminate noise and clutter in the automotive radar operating environment. Simulation results show that our proposed algorithm significantly improves reconstruction accuracy compared to the iterative soft threshold (IST) algorithm while maintaining the same computational complexity. The effectiveness of the proposed algorithm in practical applications is further validated through real-world data experiments, demonstrating its superior capability in clutter elimination. Full article
(This article belongs to the Topic Multi-Sensor Integrated Navigation Systems)
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Graphical abstract

Graphical abstract
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<p>Schematic diagram of sparse array automotive radar.</p>
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<p>Schematic diagram of nested array. <span class="html-fig-inline" id="remotesensing-17-00033-i001"><img alt="Remotesensing 17 00033 i001" src="/remotesensing/remotesensing-17-00033/article_deploy/html/images/remotesensing-17-00033-i001.png"/></span>: array element of dense subarray <span class="html-fig-inline" id="remotesensing-17-00033-i002"><img alt="Remotesensing 17 00033 i002" src="/remotesensing/remotesensing-17-00033/article_deploy/html/images/remotesensing-17-00033-i002.png"/></span>: array element of sparse subarray.</p>
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<p>Examples of difference co-array for nested array: (<b>a</b>) nested array; (<b>b</b>) difference co-array. <span class="html-fig-inline" id="remotesensing-17-00033-i001"><img alt="Remotesensing 17 00033 i001" src="/remotesensing/remotesensing-17-00033/article_deploy/html/images/remotesensing-17-00033-i001.png"/></span>: array element of dense subarray <span class="html-fig-inline" id="remotesensing-17-00033-i002"><img alt="Remotesensing 17 00033 i002" src="/remotesensing/remotesensing-17-00033/article_deploy/html/images/remotesensing-17-00033-i002.png"/></span>: array element of sparse subarray <span class="html-fig-inline" id="remotesensing-17-00033-i003"><img alt="Remotesensing 17 00033 i003" src="/remotesensing/remotesensing-17-00033/article_deploy/html/images/remotesensing-17-00033-i003.png"/></span>: vacant array element <span class="html-fig-inline" id="remotesensing-17-00033-i004"><img alt="Remotesensing 17 00033 i004" src="/remotesensing/remotesensing-17-00033/article_deploy/html/images/remotesensing-17-00033-i004.png"/></span>: difference co-array element.</p>
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<p>Flowchart of the proposed method.</p>
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<p>Comparative reconstruction results for DBF, IST and IVDST under varying off-grid conditions. (<b>a</b>) SLA with 0° off-grid; (<b>b</b>) SLA with 0.5° off-grid; (<b>c</b>) SLA with 2.5° off-grid; (<b>d</b>) VLA with 0° off-grid; (<b>e</b>) VLA with 0.5° off-grid; (<b>f</b>) VLA with 2.5° off-grid.</p>
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<p>Reconstruction performance curve of IST+SLA, IST+VLA, IVDST+SLA and IVDST+VLA versus the SNR: (<b>a</b>) on-grid; (<b>b</b>) 0.5° off-grid.</p>
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<p>Impact of SNR on convergence speed.</p>
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<p>RMSE curves of different snapshot numbers.</p>
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<p>RMSE curves of different target numbers.</p>
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<p>Comparison of processing time under different number of array elements: (<b>a</b>) IST, MUSIC, OMP, SDP-ANM and IVDST-ANM; (<b>b</b>) IST, MUSIC, OMP, and IVDST-ANM.</p>
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<p>Automotive Radar 1 experimental scenario.</p>
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<p>DOA estimation results of IST and IVDST: (<b>a</b>) IST+SLA; (<b>b</b>) IST+VLA; (<b>c</b>) IVDST+SLA; (<b>d</b>) IVDST+VLA.</p>
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<p>DOA estimation results of different arrays: (<b>a</b>) Array 1: <math display="inline"><semantics> <mrow> <mfenced close="}" open="{"> <mrow> <mn>1</mn> <mo>,</mo> <mn>3</mn> <mo>,</mo> <mn>4</mn> <mo>,</mo> <mn>5</mn> <mo>,</mo> <mn>10</mn> </mrow> </mfenced> <mi>d</mi> </mrow> </semantics></math>; (<b>b</b>) Array 2: <math display="inline"><semantics> <mrow> <mfenced close="}" open="{"> <mrow> <mn>1</mn> <mo>,</mo> <mn>3</mn> <mo>,</mo> <mn>4</mn> <mo>,</mo> <mn>7</mn> <mo>,</mo> <mn>10</mn> <mo>,</mo> <mn>13</mn> </mrow> </mfenced> <mi>d</mi> </mrow> </semantics></math>; (<b>c</b>) Array 3: <math display="inline"><semantics> <mrow> <mfenced close="}" open="{"> <mrow> <mn>1</mn> <mo>,</mo> <mn>3</mn> <mo>,</mo> <mn>4</mn> <mo>,</mo> <mn>5</mn> <mo>,</mo> <mn>7</mn> <mo>,</mo> <mn>10</mn> <mo>,</mo> <mn>13</mn> </mrow> </mfenced> <mi>d</mi> </mrow> </semantics></math>.</p>
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<p>Radar sampling environment for the first dataset. A is the stationary slanted vehicle, B is the moving electric bicycle and C is the streetlight.</p>
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<p>Reconstructed 2D point cloud image of <a href="#remotesensing-17-00033-f014" class="html-fig">Figure 14</a>: (<b>a</b>) without using GLRT detector; (<b>b</b>) using GLRT detector. A is the stationary slanted vehicle, B is the moving electric bicycle, C is the streetlight and f1 is the false target.</p>
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<p>Radar sampling environment for the second dataset. E is the two corner reflectors, F is the roadblock, G is the streetlight, H is the traffic light, and I is the streetlight.</p>
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<p>Reconstructed 2D point cloud image of <a href="#remotesensing-17-00033-f016" class="html-fig">Figure 16</a>: (<b>a</b>) without using GLRT detector; (<b>b</b>) using GLRT detector. E is the two corner reflectors, F is the roadblock, G is the streetlight, H is the traffic light, I is the streetlight, and f2, f3 are the false targets.</p>
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12 pages, 4856 KiB  
Article
Substrate Integrated Waveguide on Glass with Vacuum-Filled Tin Through Glass Vias for Millimeter-Wave Applications
by Seung-Han Chung, Ho-Sun Yeom, Che-Heung Kim, Yong-Kweon Kim, Seung-Ki Lee, Chang-Wook Baek and Jae-Hyoung Park
Micromachines 2025, 16(1), 12; https://doi.org/10.3390/mi16010012 - 26 Dec 2024
Viewed by 317
Abstract
This paper presents a novel approach to fabricate substrate integrated waveguides (SIWs) on glass substrates with tin (Sn) through glass vias (TGVs) tailored for millimeter-wave applications. The fabrication process employs a custom-designed vacuum suctioning system to rapidly fill precise TGV holes in the [...] Read more.
This paper presents a novel approach to fabricate substrate integrated waveguides (SIWs) on glass substrates with tin (Sn) through glass vias (TGVs) tailored for millimeter-wave applications. The fabrication process employs a custom-designed vacuum suctioning system to rapidly fill precise TGV holes in the glass substrate, which are formed by wafer-level glass reflow micromachining techniques with molten tin in a minute. This method offers a very fast and cost-effective alternative for complete via filling without voids compared to the conventional metallization techniques such as electroplating or sputtering. An SIW with a 3-dB cutoff frequency of 17.2 GHz was fabricated using the proposed process. The fabricated SIW shows an average insertion loss of 1.65 ± 0.54 dB across the 20–35 GHz range. These results highlight the potential of glass substrates with tin TGVs for fabricating millimeter-wave devices. Full article
(This article belongs to the Special Issue Microwave Passive Components, 2nd Edition)
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<p>Conceptual 3D view of the proposed SIW with tin TGVs.</p>
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<p>Top view of the SIW with design parameters.</p>
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<p>Simulated <span class="html-italic">S</span>-parameters of the SIWs with copper, tin, and low-resistive silicon TGVs.</p>
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<p>Overall fabrication process of the proposed SIW with tin TGVs.</p>
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<p>Vacuum suctioning system for fabricating tin TGVs: (<b>a</b>) Schematic view of the vacuum suctioning system. (<b>b</b>) Image of the vacuum suction chuck.</p>
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<p>Fabrication results: (<b>a</b>) Image of the wafer after chemical mechanical processing of the glass-reflowed substrate. Silicon TGVs are embedded in the reflowed glass. (<b>b</b>) Image of the fabricated SIW with tin TGVs. (<b>c</b>) FE-SEM cross-sectional image of the SIW with tin TGVs. The tin is filled into the TGV holes in the glass without voids.</p>
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<p>Experimental setup for measuring <span class="html-italic">S</span>-parameters of the fabricated SIW with tin TGVs.</p>
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<p>Measured <span class="html-italic">S</span>-parameters of the fabricated SIW with tin TGVs compared with the simulation results.</p>
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22 pages, 4321 KiB  
Article
Real-Time Interference Mitigation for Reliable Target Detection with FMCW Radar in Interference Environments
by Youlong Weng, Ziang Zhang, Guangzhi Chen, Yaru Zhang, Jiabao Chen and Hongzhan Song
Remote Sens. 2025, 17(1), 26; https://doi.org/10.3390/rs17010026 - 25 Dec 2024
Viewed by 425
Abstract
Frequency-modulated continuous-wave (FMCW) millimeter-wave (mmWave) radar systems are increasingly utilized in environmental sensing due to their high range resolution and robust sensing ability in severe weather environments. However, mutual interference among radar systems significantly degrades the target detection capability. Recent advancements in interference [...] Read more.
Frequency-modulated continuous-wave (FMCW) millimeter-wave (mmWave) radar systems are increasingly utilized in environmental sensing due to their high range resolution and robust sensing ability in severe weather environments. However, mutual interference among radar systems significantly degrades the target detection capability. Recent advancements in interference mitigation utilizing deep learning (DL) approaches have demonstrated promising results. DL-based approaches typically have high computational costs, which makes them unsuitable for real-time applications with strict latency requirements and limited computing resources. In this paper, we propose an efficient solution for real-time radar interference mitigation. A lightweight transformer, which is smaller and faster than the baseline transformer, is designed to reduce interference. The integration of linear attention mechanisms with depthwise separable convolutions significantly reduces the network’s computational complexity while maintaining a comparable performance. In addition, a two-stage knowledge distillation (KD) process is deployed to compress the network and enhance its efficiency. The staged distillation approach alleviates the training difficulties associated with substantial differences between the teacher and student networks. Both simulated and real-world experiments demonstrate that the proposed method outperforms the state-of-the-art methods while achieving high processing speeds. Full article
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Figure 1
<p>The scenario in which mutual interference occurs.</p>
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<p>The IF signal with interferences in the time domain and resulted range profile.</p>
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<p>The overall framework of the baseline model RIMformer.</p>
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<p>Structure of RIMformer block.</p>
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<p>Architecture diagram for two-stage KD.</p>
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<p>Optimizing KD through dynamic loss balancing.</p>
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<p>Comparison of the output of different models in ablation experiments in the form of RD maps.</p>
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<p>Comparison of results from different training methods.</p>
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<p>Comparison of the output of different models trained by different methods in the form of RD maps.</p>
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<p>The performance of models trained by the three different ways at different SNRs.</p>
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<p>Comparison of time-domain waveforms and time-frequency plots after interference suppression.</p>
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<p>Comparison of RD maps for different interference suppression methods.</p>
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<p>Setup of measured experiments.</p>
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<p>The time-domain waveforms and range profiles in measured experiments. (<b>a</b>) The time-domain waveforms without and with interference in scenario 1. (<b>b</b>) The time-domain waveforms without and with interference in scenario 2. (<b>c</b>) The range profiles without and with interference in scenario 1. (<b>d</b>) The range profiles without and with interference in scenario 2. (<b>e</b>) Range profiles comparison after interference suppression in scenario 1. (<b>f</b>) Range profiles comparison after interference suppression in scenario 2.</p>
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<p>Comparison of quantitative results for different SNRs.</p>
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