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15 pages, 8380 KiB  
Article
Design and Analysis of a Low Torque Ripple Permanent Magnet Synchronous Machine for Flywheel Energy Storage Systems
by Yubo Sun, Zhenghui Zhao and Qian Zhang
Energies 2024, 17(24), 6337; https://doi.org/10.3390/en17246337 - 16 Dec 2024
Viewed by 381
Abstract
Flywheel energy storage systems (FESS) are technologies that use a rotating flywheel to store and release energy. Permanent magnet synchronous machines (PMSMs) are commonly used in FESS due to their high torque and power densities. One of the critical requirements for PMSMs in [...] Read more.
Flywheel energy storage systems (FESS) are technologies that use a rotating flywheel to store and release energy. Permanent magnet synchronous machines (PMSMs) are commonly used in FESS due to their high torque and power densities. One of the critical requirements for PMSMs in FESS is low torque ripple. Therefore, a PMSM with eccentric permanent magnets is proposed and analyzed in this article to reduce torque ripple. Cogging torque, a significant contributor to torque ripple, is investigated by a combination of finite element analysis and the analytical method. An integer-slot distribution winding structure is adopted to reduce vibration and noise. Moreover, the effects of eccentric permanent magnets and harmonic injection on the cogging torque are analyzed and compared. In addition, the electromagnetic performance is analyzed, and the torque ripple is found to be 3.1%. Finally, a prototype is built and tested, yielding a torque ripple of 3.9%, to verify the theoretical analysis. Full article
(This article belongs to the Special Issue Energy, Electrical and Power Engineering: 3rd Edition)
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Figure 1
<p>Topology of proposed PMSM.</p>
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<p>Winding connection.</p>
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<p>Analysis model of surface-mounted PMSM.</p>
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<p>Bread-type eccentric permanent magnet.</p>
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<p>Influence of eccentricity on torque performance.</p>
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<p>Cogging torque of PMSM with different permanent magnets.</p>
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<p>Air gap magnetic densities of PMSM with different permanent magnets. (<b>a</b>) Radial air gap magnetic densities. (<b>b</b>) Tangential air gap magnetic densities. (<b>c</b>) Harmonic order.</p>
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<p>Cogging torque contribution of different harmonics. (<b>a</b>) PMSM with original permanent magnets. (<b>b</b>) PMSM with eccentric permanent magnets.</p>
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<p>Permanent magnet with third harmonic injection.</p>
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<p>Cogging torque of PMSM with harmonic injection. (<b>a</b>) Effect of harmonic injection. (<b>b</b>) Contribution of harmonics.</p>
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<p>Load electromagnetic performance. (<b>a</b>) Magnetic field line. (<b>b</b>) Magnetic flux density.</p>
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<p>Back electromotive force of PMSM.</p>
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<p>Torque performance of PMSM. (<b>a</b>) Cogging torque. (<b>b</b>) Torque.</p>
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<p>Vibration acceleration of PMSM with different permanent magnets.</p>
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<p>Prototype.</p>
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<p>Experimental platform.</p>
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<p>Vibration and noise test platform.</p>
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<p>Comparison of experimental and simulated results. (<b>a</b>) Back electromotive force of prototype. (<b>b</b>) Comparison of back electromotive force coefficient.</p>
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<p>Experimental results. (<b>a</b>) Torque. (<b>b</b>) Vibration acceleration.</p>
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17 pages, 9016 KiB  
Article
Optimization of an Asymmetric-Rotor Permanent Magnet-Assisted Synchronous Reluctance Motor for Improved Anti-Demagnetization Performance
by Feng Xing, Jiajia Zhang, Feng Zuo and Yuge Gao
Appl. Sci. 2024, 14(23), 11233; https://doi.org/10.3390/app142311233 - 2 Dec 2024
Viewed by 561
Abstract
Permanent magnet-assisted synchronous reluctance motors (PMA-SynRMs) are widely used in various fields due to their significant advantages, including strong torque output, high efficiency, excellent speed regulation, and low cost. The PMA-SynRM with asymmetric-rotor structure has a weaker anti-demagnetization performance than the conventional PMA-SynRM [...] Read more.
Permanent magnet-assisted synchronous reluctance motors (PMA-SynRMs) are widely used in various fields due to their significant advantages, including strong torque output, high efficiency, excellent speed regulation, and low cost. The PMA-SynRM with asymmetric-rotor structure has a weaker anti-demagnetization performance than the conventional PMA-SynRM due to its multi-layer and thin permanent magnets construction. According to the finite element (FEM) simulation analysis, the anti-demagnetization performance of the asymmetric-rotor PMA-SynRM can be improved by adding bypass magnetic bridges on the ribs of the flux barriers and by changing the positions of the permanent magnets. The rotor structure of the proposed model is globally optimized by combining the two methods. Anti-demagnetization performance is improved as much as possible under the premise of ensuring the torque performance of the basic model. After multi-objective optimization, there is almost no difference between the optimized model and the basic model in terms of no-load air-gap flux density, no-load Back-electromotive force (EMF), and average torque. The maximum demagnetization rate of the optimized model is reduced by 81.44% compared with the basic model, and the anti-demagnetization performance is significantly improved. At the same time, the torque ripple is also reduced by 44.14%, which is obviously reduced. Compared with the basic model, the optimized model has better stability and reliability. Full article
(This article belongs to the Collection Modeling, Design and Control of Electric Machines: Volume II)
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Figure 1
<p>Basic model stator-rotor topology. (<b>a</b>) Stator and winding structure. (<b>b</b>) Rotor structure.</p>
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<p>Simplified vector diagram of the basic model002E.</p>
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<p>Distribution of demagnetization rate of the basic model.</p>
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<p>Parameter diagram of the single-pole topology of the proposed model rotor.</p>
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<p>Mesh section of the proposed model rotor.</p>
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<p>Effect of rib bypass magnetic bridge width <span class="html-italic">d</span> and height <span class="html-italic">h</span> on demagnetization.</p>
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<p>Effect of flux barrier angle <span class="html-italic">C</span>3 and permanent magnet drop height <span class="html-italic">H</span> on demagnetization.</p>
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<p>Multi-objective optimization flowchart.</p>
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<p>Sensitivity analysis results.</p>
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<p>Multi-objective optimization results.</p>
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<p>Optimized model rotor single-pole topology.</p>
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<p>Comparison of no-load flux density between the basic and optimized models. (<b>a</b>) Waveform diagram of flux density. (<b>b</b>) Harmonic decomposition of flux density.</p>
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<p>Comparison of the no-load Back-EMF of the basic model and the optimized model. (<b>a</b>) Back-EMF waveform diagram. (<b>b</b>) Harmonic decomposition of Back-EMF.</p>
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<p>Average torque of the basic and optimized models for different current phase angles.</p>
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<p>Flux density cloud at peak torque for the two models. (<b>a</b>) Basic model. (<b>b</b>) Optimized model.</p>
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<p>Comparison of torque waveforms of basic and optimized models.</p>
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<p>Comparison of the maximum demagnetization rate of permanent magnets between the basic and optimized models.</p>
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<p>Distribution of demagnetization rate of the optimized model permanent magnets.</p>
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22 pages, 13437 KiB  
Article
A Novel Approach to Ripple Cancellation for Low-Speed Direct-Drive Servo in Aerospace Applications
by Xin Zhang, Ziting Wang, Chaoping Bai and Shuai Zhang
Aerospace 2024, 11(10), 834; https://doi.org/10.3390/aerospace11100834 - 10 Oct 2024
Viewed by 785
Abstract
Low-frequency harmonic interference is an important factor that affects the performance of low-speed direct-drive servo systems. In order to improve the low-speed smoothness of direct-drive servo, firstly, the causes of the first and second harmonics of electromagnetic torque and tooth harmonics are analyzed [...] Read more.
Low-frequency harmonic interference is an important factor that affects the performance of low-speed direct-drive servo systems. In order to improve the low-speed smoothness of direct-drive servo, firstly, the causes of the first and second harmonics of electromagnetic torque and tooth harmonics are analyzed based on the mathematical model of PMSM (permanent magnet synchronous motor) and the principle of vector control. Accordingly, the CC-EUMA (Electrical angle Update and Mechanical angle Assignment algorithm for Center Current) and SL-DQPR (Double Quasi-Proportional Resonant control algorithm for Speed Loop) algorithm are proposed. Second, to confirm the algorithm’s efficacy, the harmonic environment is simulated using Matlab/Simulink, and the built harmonic suppression module is simulated and analyzed. Then, a miniaturized, fully digital drive control system is built based on the architecture of the Zynq-7000 series chips. Finally, the proposed suppression algorithm is verified at the board level. According to the experimental results, the speed ripple decreases to roughly one-third of its initial value after the algorithm is included. This effectively delays the speed ripple’s low-speed deterioration and provides a new idea for the low-speed control of the space direct-drive servo system. Full article
(This article belongs to the Special Issue Aircraft Electric Power System: Design, Control, and Maintenance)
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<p>Double closed-loop servo system under the action of cogging torque.</p>
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<p>The algorithm of CC-EUMA.</p>
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<p>Amplitude–frequency characteristics of the PR controller: (<b>a</b>) <math display="inline"><semantics> <mrow> <msub> <mi>k</mi> <mi>p</mi> </msub> </mrow> </semantics></math> is a variable constant, <math display="inline"><semantics> <mrow> <msub> <mi>k</mi> <mi>r</mi> </msub> </mrow> </semantics></math> is an invariant constant; (<b>b</b>) <math display="inline"><semantics> <mrow> <msub> <mi>k</mi> <mi>p</mi> </msub> </mrow> </semantics></math> is an invariable constant, and <math display="inline"><semantics> <mrow> <msub> <mi>k</mi> <mi>r</mi> </msub> </mrow> </semantics></math> is a variant constant.</p>
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<p>Amplitude–frequency characteristics of the QPR controller. (<b>a</b>) <math display="inline"><semantics> <mrow> <msub> <mi>k</mi> <mi>p</mi> </msub> </mrow> </semantics></math> is a variable constant, <math display="inline"><semantics> <mrow> <msub> <mi>k</mi> <mi>r</mi> </msub> </mrow> </semantics></math> is an invariant constant; (<b>b</b>) <math display="inline"><semantics> <mrow> <msub> <mi>k</mi> <mi>p</mi> </msub> </mrow> </semantics></math> is an invariable constant, and <math display="inline"><semantics> <mrow> <msub> <mi>k</mi> <mi>r</mi> </msub> </mrow> </semantics></math> is a variant constant.</p>
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<p>Baud diagram of the system before and after parallel QPR control in a speed loop.</p>
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<p>DC bias module used to simulate torque current’s first harmonic.</p>
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<p>CC-EUMA algorithm module.</p>
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<p>Simulation results of speed before and after adding CC-EUMA: (<b>a</b>) before adding CC-EUMA; (<b>b</b>) after adding CC-EUMA.</p>
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<p>Simulation results of speed FFT before and after adding CC-EUMA: (<b>a</b>) before adding CC-EUMA; (<b>b</b>) after adding CC-EUMA.</p>
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<p>Module structure for torque current simulation of the second and tooth harmonics: (<b>a</b>) analog second harmonic; (<b>b</b>) analog tooth harmonic.</p>
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<p>SL-DQPR algorithm module.</p>
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<p>Simulation results of speed before and after adding SL-DQPR: (<b>a</b>) before adding SL-DQPR; (<b>b</b>) after adding SL-DQPR.</p>
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<p>Simulation results of speed FFT before and after adding SL-DQPR: (<b>a</b>) before adding SL-DQPR; (<b>b</b>) after adding SL-DQPR.</p>
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<p>Servo system architecture.</p>
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<p>Structure of the drive controller.</p>
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<p>Software architecture of PMSM low-speed direct-drive servo system.</p>
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<p>Operational interface of the master computer system.</p>
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<p>Experimental platform for the servo system.</p>
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<p>Internal hardware components of the drive controller.</p>
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<p>Timing control flow of the system.</p>
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<p>Speed and speed FFT before and after adding CC-EUMA at 50 rpm: (<b>a</b>) speed; (<b>b</b>) speed FFT.</p>
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<p>Speed and speed FFT before and after adding CC-EUMA at 40 rpm: (<b>a</b>) speed; (<b>b</b>) speed FFT.</p>
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<p>Speed and speed FFT before and after adding CC-EUMA at 30 rpm: (<b>a</b>) speed; (<b>b</b>) speed FFT.</p>
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<p>Speed and speed FFT before and after adding CC-EUMA at 20 rpm: (<b>a</b>) speed; (<b>b</b>) speed FFT.</p>
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<p>Speed and speed FFT before and after adding CC-EUMA at 10 rpm: (<b>a</b>) speed; (<b>b</b>) speed FFT.</p>
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<p>Speed and speed FFT before and after adding SL-DQPR at 50 rpm: (<b>a</b>) speed; (<b>b</b>) speed FFT.</p>
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<p>Speed and speed FFT before and after adding SL-DQPR at 40 rpm: (<b>a</b>) speed; (<b>b</b>) speed FFT.</p>
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<p>Speed and speed FFT before and after adding SL-DQPR at 30 rpm: (<b>a</b>) speed; (<b>b</b>) speed FFT.</p>
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<p>Speed and speed FFT before and after adding SL-DQPR at 20 rpm: (<b>a</b>) speed; (<b>b</b>) speed FFT.</p>
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<p>Speed and speed FFT before and after adding SL-DQPR at 10 rpm: (<b>a</b>) speed; (<b>b</b>) speed FFT.</p>
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<p>The speed ripples of adding CC-EUMA and SL-DQPR at the same time.</p>
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14 pages, 15754 KiB  
Article
Development of Second Prototype of Twin-Driven Magnetorheological Fluid Actuator for Haptic Device
by Takehito Kikuchi, Asaka Ikeda, Rino Matsushita and Isao Abe
Micromachines 2024, 15(10), 1184; https://doi.org/10.3390/mi15101184 - 25 Sep 2024
Viewed by 713
Abstract
Magnetorheological fluids (MRFs) are functional fluids that exhibit rapid and reproducible rheological responses to external magnetic fields. An MRF has been utilized to develop a haptic device with precise haptic feedback for teleoperative surgical systems. To achieve this, we developed several types of [...] Read more.
Magnetorheological fluids (MRFs) are functional fluids that exhibit rapid and reproducible rheological responses to external magnetic fields. An MRF has been utilized to develop a haptic device with precise haptic feedback for teleoperative surgical systems. To achieve this, we developed several types of compact MRF clutches for haptics (H-MRCs) and integrated them into a twin-driven MRF actuator (TD-MRA). The first TD-MRA prototype was successfully used to generate fine haptic feedback for operators. However, undesirable torque ripples were observed due to shaft misalignment and the low rigidity of the structure. Additionally, the detailed torque control performance was not evaluated from both static and dynamic current inputs. The objective of this study is to develop a second prototype to reduce torque ripple by improving the structure and evaluating its static and dynamic torque performance. Torque performance was measured using both constant and stepwise current inputs. The coefficient of variance of the torque was successfully reduced by half due to the structural redesign. Although the time constants of the H-MRC were less than 10 ms, those of the TD-MRA were less than 20 ms under all conditions. To address the slower downward output response, we implemented an improved input method, which successfully halved the response time. Full article
(This article belongs to the Special Issue Magnetorheological Materials and Application Systems)
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Figure 1
<p>MR fluid clutch for haptics (H-MRC).</p>
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<p>Basic structure of TD-MRA for haptics.</p>
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<p>First prototype of 0.3 Nm-Class Twin-driven MR Fluid Actuator (TD-MRA 1st).</p>
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<p>Second prototype of 0.3 Nm-Class Twin-driven MR Fluid Actuator (TD-MRA 2nd).</p>
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<p>Comparison of dimension for two devices (Upper: 1<sup>st</sup> prototype, lower: 2<sup>nd</sup> prototype).</p>
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<p>Signal diagram of measurement system.</p>
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<p>Profile of input current and definition of time constant.</p>
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<p>Results of static test (time profile).</p>
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<p>Results of static test (time profile).</p>
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<p>Results of static test (average values).</p>
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<p>Results of Dynamic test at 10 rpm.</p>
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<p>Results of Dynamic test at 10 rpm.</p>
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<p>Results of Dynamic test at 30 rpm.</p>
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<p>Results of Dynamic test at 60 rpm.</p>
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<p>Profile of modified input current.</p>
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<p>Results of Dynamic test with modified input at 10 rpm.</p>
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<p>Results of Dynamic test with modified input at 30 rpm.</p>
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<p>Results of Dynamic test with modified input at 60 rpm.</p>
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13 pages, 4189 KiB  
Article
Electromagnetic and Mechanical Stress Analysis of a 5 MW High-Pole Non-Overlap Winding Wound-Rotor Synchronous Wind Generator
by Karen S. Garner and Udochukwu B. Akuru
Energies 2024, 17(18), 4585; https://doi.org/10.3390/en17184585 - 12 Sep 2024
Viewed by 957
Abstract
Utilizing non-overlap windings has emerged as a favourable choice for minimizing electrical machine manufacturing costs, among other benefits. Nevertheless, it is widely acknowledged that these windings exhibit a notable level of harmonic contents in the resultant magnetomotive force, which can detrimentally impact machine [...] Read more.
Utilizing non-overlap windings has emerged as a favourable choice for minimizing electrical machine manufacturing costs, among other benefits. Nevertheless, it is widely acknowledged that these windings exhibit a notable level of harmonic contents in the resultant magnetomotive force, which can detrimentally impact machine performance, particularly in terms of torque ripple. In the context of wind energy conversion, maintaining low torque ripple is an essential and demanding prerequisite. Medium-speed wind generators present a good trade-off between high energy yield and low gearbox ratios. So far, medium-speed non-overlap winding wound-rotor synchronous generator (WRSG) technologies have been limited to 10/12 and the less common 16/18 pole/slot combinations. In this study, the analysis of a high-pole number combination (24/27 pole/slots) non-overlap WRSG is carried out to theoretically and comparatively predict the electromagnetic and radial force mechanical stress performance analysis with the 16/18 machine with a phase-shifted non-overlap winding (PSW), at 5 MW power level. The study, which is founded on the finite element analysis (FEA) technique, shows that the 24/27 machine exhibits comparable average torque and torque ripple, lower core losses and significantly reduced radial forces compared to the 16/18 PSW-WRSG. However, the 16/18 PSW-WRSG has a 50% reduction in the radial forces compared to the conventional 16/18 non-overlap winding. Experimental vibration analysis of a 3 kW 16/18 WRSG test machine confirms the radial force and vibration reduction in the phase-shifted winding. Full article
(This article belongs to the Special Issue Energy, Electrical and Power Engineering: 3rd Edition)
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<p>Base models of the 5 MW NOW-WRSGs drawn in 2D FEA software: (<b>a</b>) 16/18 pole/slots and (<b>b</b>) 24/27 pole/slots. <b>Stator:</b> brown, green and yellow colours represent the armature winding of Phase A, B and C coil sides moving in and out of slots, respectively. <b>Rotor:</b> red and blue colours represent field winding coil sides moving in and out of slots, respectively.</p>
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<p>Comparison of the MMF harmonic spectrum for the different poles/slots NOW-WRSGs.</p>
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<p>FEA-simulated flux distribution plots of the 5 MW NOW-WRSGs at rated conditions: (<b>a</b>) 16/18 pole/slots and (<b>b</b>) 24/27 pole/slots. <b>Stator:</b> brown, green and yellow colours represent the armature winding of Phase A, B and C coil sides moving in and out of slots, respectively. <b>Rotor:</b> red and blue colours represent field winding coil sides moving in and out of slots, respectively.</p>
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<p>FEA-simulated instantaneous torque comparison for the different poles/slots NOW-WRSGs under rated <span class="html-italic">q</span>-axis and field currents.</p>
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<p>FEA-simulated flux density plots of the 5 MW NOW-WRSGs at rated conditions: (<b>a</b>) 16/18 pole/slots and (<b>b</b>) 24/27 pole/slots.</p>
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<p>FEA-simulated radial flux density waveforms around the airgap of the different poles/slots NOW-WRSG at different simulation times: (<b>a</b>) <span class="html-italic">t</span> = 0.1 ms and (<b>b</b>) <span class="html-italic">t</span> = 100 ms.</p>
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<p>Comparison of the radial forces present in different poles/slots NOW-WRSGs at <span class="html-italic">t</span> = 100 ms.</p>
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<p>FE model of the 3 kW 16/18 NOW-WRSG prototype machine.</p>
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<p>Experimental setup of (<b>a</b>) the 3 kW 16/18 WRSG test machine workbench [<a href="#B10-energies-17-04585" class="html-bibr">10</a>] and (<b>b</b>) accelerometer placement.</p>
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<p>Measured vibration of the 3 kW 16/18 WRSG test machine with the non-overlap and phase-shifted windings at full load.</p>
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22 pages, 16164 KiB  
Article
Reducing Noise and Impact of High-Frequency Torque Ripple Caused by Injection Voltages by Using Self-Regulating Random Model Algorithm for SynRMs Sensorless Speed Control
by Yibo Guo, Lingyun Pan, Yang Yang, Yimin Gong and Xiaolei Che
Electronics 2024, 13(16), 3327; https://doi.org/10.3390/electronics13163327 - 22 Aug 2024
Viewed by 856
Abstract
For the sensorless control in a low-speed range of synchronous reluctance motors (SynRMs), injecting random high-frequency (HF) square-wave-type voltages has become a widely used and technologically mature method. It can solve the noise problem of traditional injection signal methods. However, all injection signal [...] Read more.
For the sensorless control in a low-speed range of synchronous reluctance motors (SynRMs), injecting random high-frequency (HF) square-wave-type voltages has become a widely used and technologically mature method. It can solve the noise problem of traditional injection signal methods. However, all injection signal methods will cause problems such as torque ripple, which causes speed fluctuations. This article proposes a self-regulating random model algorithm for the random injection signal method, which includes a quantity adaptive module for adding additional random processes, an evaluation module for evaluating torque deviation degree, and an updated model module that is used to receive signals from the other two modules and complete model changes and output random model elements. The main function of this algorithm is to create a model that updates to suppress the evaluation value deviation based on the evaluation situation and outputs an optimal sequence of random numbers, thereby limiting speed bias always in a small range; this can reduce unnecessary changes in the output value of the speed regulator. The feasibility and effectiveness of the proposed algorithm and control method have been demonstrated in experiments based on a 5-kW synchronous reluctance motor. Full article
(This article belongs to the Special Issue Power Electronics in Renewable Systems)
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<p>The schematic diagram of the injection voltage of the <span class="html-italic">d</span>-axis.</p>
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<p>Configuration of adaptive speed estimator.</p>
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<p>PLL for calculating electrical angle.</p>
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<p>Using adaptive velocity estimator and PLL to obtain motor speed and electrical angle.</p>
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<p>The schematic diagram of the eight basic injection voltages and corresponding induced currents in <span class="html-italic">d</span>-axis. (<b>a</b>) <math display="inline"><semantics> <mrow> <mi>φ</mi> <mo>=</mo> <mn>0</mn> <mo>°</mo> </mrow> </semantics></math>. (<b>b</b>) <math display="inline"><semantics> <mrow> <mi>φ</mi> <mo>=</mo> <mn>45</mn> <mo>°</mo> </mrow> </semantics></math>. (<b>c</b>) <math display="inline"><semantics> <mrow> <mi>φ</mi> <mo>=</mo> <mn>90</mn> <mo>°</mo> </mrow> </semantics></math>. (<b>d</b>) <math display="inline"><semantics> <mrow> <mi>φ</mi> <mo>=</mo> <mn>135</mn> <mo>°</mo> </mrow> </semantics></math>. (<b>e</b>) <math display="inline"><semantics> <mrow> <mi>φ</mi> <mo>=</mo> <mn>180</mn> <mo>°</mo> </mrow> </semantics></math>. (<b>f</b>) <math display="inline"><semantics> <mrow> <mi>φ</mi> <mo>=</mo> <mn>225</mn> <mo>°</mo> </mrow> </semantics></math>. (<b>g</b>) <math display="inline"><semantics> <mrow> <mi>φ</mi> <mo>=</mo> <mn>270</mn> <mo>°</mo> </mrow> </semantics></math>. (<b>h</b>) <math display="inline"><semantics> <mrow> <mi>φ</mi> <mo>=</mo> <mn>315</mn> <mo>°</mo> </mrow> </semantics></math>.</p>
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<p>Reference diagram for calculating the impact of injected voltage on speed. (<b>a</b>) No.1. (<b>b</b>) No.2.</p>
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<p>The variation in SynRM <span class="html-italic">dq</span>-axis inductance due to saturation effect.</p>
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<p>The summed-up value of the speed bias of using RVIM according to <a href="#electronics-13-03327-t002" class="html-table">Table 2</a>.</p>
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<p>Overall diagram of self-regulating random model algorithm.</p>
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<p>Principle diagram of the quantity adaptive module.</p>
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<p>Update Model Module. (<b>a</b>) Overall logic diagram. (<b>b</b>) Schematic diagram of model state changes.</p>
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<p>Flowchart of using the self-regulating random model algorithm to output injection voltage.</p>
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<p>Block diagram of speed sensorless control system for SynRMs using self-regulating random model algorithm.</p>
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<p>PSD results of the induced current of three different control methods.</p>
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<p>Experimental platform display diagram.</p>
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<p>The output signal from quantity adaptive module and the number of active elements.</p>
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<p>The evaluation result value and the injection voltage number.</p>
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<p>Sampling results of current, speed, and torque during motor running at 100 rpm. (<b>a</b>) SRRMM with no load. (<b>b</b>) RVIM with no load. (<b>c</b>) SRRMM with 50% rated load. (<b>d</b>) RVIM with 50% rated load. (<b>e</b>) SRRMM with rated load. (<b>f</b>) RVIM with rated load.</p>
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<p>Sampling results of current and speed during motor start-up to 100 rpm. (<b>a</b>) SRRMM with no load. (<b>b</b>) RVIM with no load. (<b>c</b>) SRRMM with rated load. (<b>d</b>) RVIM with rated load.</p>
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<p>Sampling results of current and speed of the motor from −100 rpm to 100 rpm. (<b>a</b>) SRRMM with no load. (<b>b</b>) RVIM with no load. (<b>c</b>) SRRMM with rated load. (<b>d</b>) RVIM with rated load.</p>
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<p>Sampling results of current and speed during acceleration and deceleration of the motor between 100 rpm and 150 rpm. (<b>a</b>) SRRMM with no-load. (<b>b</b>) RVIM with no-load. (<b>c</b>) SRRMM with rated load. (<b>d</b>) RVIM with rated load.</p>
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<p>Collecting the noise level generated by the motor using Smart Sensor AS804B.</p>
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<p>Record of voltage injection times for each number.</p>
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<p>During steady state of the motor, phase current image, corresponding PSD calculation results, and Fourier transform results display diagram. (<b>a</b>) OVIM with 2.5 kHz injection voltage with no load. (<b>b</b>) OVIM with 1.25 kHz injection voltage with no load. (<b>c</b>) RVIM with no load. (<b>d</b>) SRRMM with no load. (<b>e</b>) OVIM with 2.5 kHz injection voltage with rated load. (<b>f</b>) OVIM with 1.25 kHz injection voltage with rated load. (<b>g</b>) RVIM with rated load. (<b>h</b>) SRRMM with rated load.</p>
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12 pages, 5791 KiB  
Article
Analysis and Suppression of Spoke-Type Permanent Magnet Machines Cogging Torque with Different Conditions for Electric Vehicles
by Jinlin Huang and Chen Wang
World Electr. Veh. J. 2024, 15(8), 376; https://doi.org/10.3390/wevj15080376 - 19 Aug 2024
Viewed by 717
Abstract
Spoke-type permanent magnet (STPM) machines have high power density and low cost due to flux concentrated effect and high air-gap flux density, but they can cause high cogging torque and torque ripple. To reduce the cogging torque, the analytical model considering a rotor [...] Read more.
Spoke-type permanent magnet (STPM) machines have high power density and low cost due to flux concentrated effect and high air-gap flux density, but they can cause high cogging torque and torque ripple. To reduce the cogging torque, the analytical model considering a rotor slot is established and compared with the finite element mothed (FEM). Then, the cogging torque production mechanism is revealed and analyzed under different conditions, which provides direction to optimize the cogging torque STPM machines. The harmonic content of cogging torque under different conditions is obtained based on the freezing permeability (FP) method. It is found that the fundamental waves mainly generate the cogging torque under a no-load condition, and it is mainly generated by the second harmonics under an on-load condition. In addition, the optimization method is introduced and researched, including rotor slot width, uneven rotor core, and so on. Finally, a 50 kW STPM machine prototype is manufactured and tested to verify the accuracy and efficiency of the analysis method. Full article
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<p>Topology of the STPM machine.</p>
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<p>Cogging torques at no−load with different methods.</p>
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<p>Cogging torque under no−load. (<b>a</b>) Waveform. (<b>b</b>) Harmonic spectrum.</p>
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<p>Cogging torque with on−load. (<b>a</b>) Waveforms. (<b>b</b>) Harmonic.</p>
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<p>Cogging torque versus different rotor slots under no load. (<b>a</b>) Waveform. (<b>b</b>) Harmonic.</p>
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<p>Cogging torque versus different rotor slots under on-load. (<b>a</b>) Waveforms. (<b>b</b>) Harmonic.</p>
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<p>Uneven rotor core structure.</p>
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<p>Cogging torque versus different uneven rotor core distance under no-load. (<b>a</b>) Waveforms. (<b>b</b>) Harmonic.</p>
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<p>Cogging torque versus different uneven rotor core distance under on-load. (<b>a</b>) Waveforms. (<b>b</b>) Harmonic.</p>
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<p>Uneven stator core structure.</p>
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<p>Cogging torque versus different uneven stator core distance under no-load. (<b>a</b>) Waveforms. (<b>b</b>) Harmonic.</p>
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<p>Cogging torque versus different uneven stator core distance under on-load. (<b>a</b>) Waveforms. (<b>b</b>) Harmonic.</p>
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<p>Stator auxiliary slot designs. (<b>a</b>) One auxiliary slot. (<b>b</b>) Two auxiliary slots. (<b>c</b>) Three auxiliary slots. (<b>d</b>) Four auxiliary slots.</p>
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<p>Cogging torque with different auxiliary slots under no−load. (<b>a</b>) Waveform. (<b>b</b>) Harmonics.</p>
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<p>Cogging torques of STPM machine with different auxiliary slots under on−load. (<b>a</b>) Waveform. (<b>b</b>) Harmonics.</p>
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<p>STPM machine with a rotor slot prototype test platform.</p>
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<p>Line back-EMF under 4800 r/min. (<b>a</b>) Waveform. (<b>b</b>) Harmonic spectra.</p>
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<p>Torque versus phase current. (<b>a</b>) Waveforms. (<b>b</b>) Phase current waveform.</p>
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20 pages, 61711 KiB  
Article
Harmonic Suppression in Permanent Magnet Synchronous Motor Currents Based on Quasi-Proportional-Resonant Sliding Mode Control
by Kelu Wu, Yongchao Zhang, Wenqi Lu, Yubao Qi and Weimin Shi
Appl. Sci. 2024, 14(16), 7206; https://doi.org/10.3390/app14167206 - 16 Aug 2024
Cited by 1 | Viewed by 967
Abstract
The output voltage of inverters is influenced by nonlinear factors such as dead time and voltage drops, injecting low-order harmonics. This results in fifth and seventh harmonic distortions in the stator current, causing periodic torque ripples and significantly affecting the control precision of [...] Read more.
The output voltage of inverters is influenced by nonlinear factors such as dead time and voltage drops, injecting low-order harmonics. This results in fifth and seventh harmonic distortions in the stator current, causing periodic torque ripples and significantly affecting the control precision of Permanent Magnet Synchronous Motors (PMSMs). To address this issue, this paper proposes a control strategy named quasi-proportional-resonant sliding mode control (QPR-SMC). Initially, sliding mode control is employed as the current controller to enhance disturbance rejection capability and provide a rapid dynamic response. Subsequently, a quasi-proportional-resonant controller is introduced to extract the sixth harmonic component from the current, which is then used as a compensation term for the sliding mode control surface. Finally, the current tracking error and the compensation term are combined as inputs to the sliding mode control law, forming a current error-proportional resonant-sliding mode control surface. This approach enhances the harmonic suppression capability of the system. The results demonstrate that the proposed method effectively reduces the fifth and seventh harmonic components in the three-phase current and mitigates motor jitter by suppressing the sixth harmonic in the d–q coordinate system. Full article
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<p>Bode plot of the ideal resonant controller and the quasi-resonant controller.</p>
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<p>Principles of harmonic suppression based on QPR.</p>
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<p>Bode plot of the quasi-proportional-resonant controller with different parameter values.</p>
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<p>Bode plot of the quasi-proportional-resonant controller with <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>k</mi> </mrow> <mrow> <mi>p</mi> </mrow> </msub> <mo> </mo> </mrow> </semantics></math>= 0.1, <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>k</mi> </mrow> <mrow> <mi>r</mi> </mrow> </msub> <mo> </mo> </mrow> </semantics></math>= 80, and <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>w</mi> </mrow> <mrow> <mi>c</mi> <mo> </mo> </mrow> </msub> </mrow> </semantics></math> = 2 rad/s.</p>
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<p>Bode plot of the system.</p>
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<p>A system control block diagram.</p>
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<p>A structural block diagram of the current error-proportional resonant-sliding mode control surface.</p>
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<p>The motor drive test platform.</p>
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<p>Phase current and load torque waveforms at low speed (450 r/min). (<b>a</b>) Phase current waveform. (<b>b</b>) Load torque waveform.</p>
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<p>Frequency spectrum of the phase current at low speed.</p>
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<p>Phase current and load torque waveforms at low speed (1125 r/min). (<b>a</b>) Phase current waveform. (<b>b</b>) Load torque waveform.</p>
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<p>Frequency spectrum of the phase current at medium speed.</p>
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<p>Phase current and load torque waveforms at low speed (2250 r/min). (<b>a</b>) Phase current waveform. (<b>b</b>) Load torque waveform.</p>
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<p>Frequency spectrum of the phase current at high speed.</p>
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<p>Phase current and torque waveforms at low speed (450 r/min) under the QPR-PI and QPR-SMC control strategies. (<b>a</b>) Phase current waveform under the QPR-PI control strategy. (<b>b</b>) Torque waveform under the QPR-PI control strategy. (<b>c</b>) Phase current waveform under the QPR-SMC control strategy. (<b>d</b>) Torque waveform under the QPR-SMC control strategy.</p>
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<p>Frequency spectrum of the phase current at low speed: (<b>a</b>) under the QPR-PI control strategy; (<b>b</b>) under the QPR-SMC control strategy.</p>
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<p>Phase current and torque waveforms at low speed (1125 r/min) under the QPR-PI and QPR-SMC control strategies. (<b>a</b>) Phase current waveform under the QPR-PI control strategy. (<b>b</b>) Torque waveform under the QPR-PI control strategy. (<b>c</b>) Phase current waveform under the QPR-SMC control strategy. (<b>d</b>) Torque waveform under the QPR-SMC control strategy.</p>
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<p>Frequency spectrum of the phase current at medium speed: (<b>a</b>) under the QPR-PI control strategy; (<b>b</b>) under the QPR-SMC control strategy.</p>
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<p>Phase current and torque waveforms at low speed (2250 r/min) under the QPR-PI and QPR-SMC control strategies. (<b>a</b>) Phase current waveform under the QPR-PI control strategy. (<b>b</b>) Torque waveform under the QPR-PI control strategy. (<b>c</b>) Phase current waveform under the QPR-SMC control strategy. (<b>d</b>) Torque waveform under the QPR-SMC control strategy.</p>
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<p>Frequency spectrum of the phase current at high speed: (<b>a</b>) under the QPR-PI control strategy; (<b>b</b>) under the QPR-SMC control strategy.</p>
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<p>Harmonic analysis results for PI, QPR-PI, and QPR-SMC control methods at different speeds: (<b>a</b>) Suppression results at low speed; (<b>b</b>) Suppression results at medium speed; (<b>c</b>) Suppression results at high speed.</p>
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17 pages, 7956 KiB  
Article
A High Torque Density Dual-Stator Flux-Reversal-Machine with Multiple Poles Halbach Excitation on Outer Stator
by Siwei Tang, Yuanying Xu, Chao He and Jiquan Yang
Actuators 2024, 13(8), 275; https://doi.org/10.3390/act13080275 - 23 Jul 2024
Viewed by 1014
Abstract
This paper proposes a high torque density dual-stator flux-reversal-machine with multiple poles Halbach excitation (MPHE-DSFRM), which uses two pole pairs’ numbers (PPNs) of PM excitation on one outer stator tooth, and one PPN of PM excitation on one inner stator tooth. The introduction [...] Read more.
This paper proposes a high torque density dual-stator flux-reversal-machine with multiple poles Halbach excitation (MPHE-DSFRM), which uses two pole pairs’ numbers (PPNs) of PM excitation on one outer stator tooth, and one PPN of PM excitation on one inner stator tooth. The introduction of different PPNs of PM excitation on the outer and the inner stators can optimize magnetic circuit and airgap flux density. A Halbach array is formed by inserting three pieces of circumferentially magnetized PMs into four pieces of radially magnetized permanent magnets (PMs) on the outer stator, which aims to further enhance torque density, and reduce torque ripple. Based on the flux modulation effect, the analytical modeling of the proposed MPHE-DSFRM is established, together with the evolution process, and the working principle is presented. Then, the key design parameters of MPHE-DSFRM are optimized to achieve high torque density and low torque ripple for high torque quality. Three representative DSFRMs and a conventional FRM are designed and analyzed, and they share the same design key parameters, including PM usage, outer radius of the outer stator, and active airgap length. The electromagnetic performances, including airgap flux density, back electromotive force (back-EMF), and torque characteristics, are analyzed and compared by finite element analysis (FEA). The calculated results show that the proposed MPHE-DSFRM can provide high torque density and high PM utilization. Full article
(This article belongs to the Section High Torque/Power Density Actuators)
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<p>The topology of the proposed MPHE-DSFRM.</p>
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<p>Topology of FRM with different poles of PMs on one stator tooth.</p>
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<p>Comparison of FRM with different poles of PMs on one stator tooth. (<b>a</b>) Flux linkage waveforms. (<b>b</b>) Steady torque waveforms.</p>
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<p>Trend of amplitude of flux linkage following different rotor pole numbers.</p>
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<p>Evolution process of the proposed MPHE-DSFRM from FRM.</p>
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<p>The harmonics distributions of airgap flux density of the proposed MPHE-DSFRM. (<b>a</b>) Outer airgap. (<b>b</b>) Inner airgap.</p>
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<p>Definition of the position relationship of two stators in MPHE-DSFRM.</p>
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<p>Variations of <span class="html-italic">T<sub>avg</sub></span> and <span class="html-italic">T<sub>rip</sub></span> to <span class="html-italic">θ<sub>T</sub></span>.</p>
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<p>Definition of the PM width in the proposed MPHE-DSFRM.</p>
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<p>Variation of <span class="html-italic">T<sub>avg</sub></span> and <span class="html-italic">T<sub>rip</sub></span> to <span class="html-italic">θ<sub>PM</sub></span>.</p>
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<p>Definition of design parameters for the rotor. (<b>a</b>) <span class="html-italic">θ<sub>p</sub></span> and <span class="html-italic">θ<sub>r</sub></span>. (<b>b</b>) <span class="html-italic">θ<sub>q</sub></span>.</p>
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<p>Variation of <span class="html-italic">T<sub>avg</sub></span> and <span class="html-italic">T<sub>rip</sub></span> to parameters. (<b>a</b>) <span class="html-italic">θ<sub>p</sub></span>. (<b>b</b>) <span class="html-italic">θ<sub>r</sub></span>. (<b>c</b>) <span class="html-italic">θ<sub>q</sub></span>.</p>
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<p>Sensitivity analysis of optimization objectives <span class="html-italic">T<sub>avg</sub></span> and <span class="html-italic">T<sub>rip</sub></span>.</p>
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<p>Geometric configurations of investigated models.</p>
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<p>Harmonic spectra of airgap flux density at no-load state. (<b>a</b>) Outer airgap. (<b>b</b>) Inner airgap.</p>
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<p>No-load magnetic field distribution. (<b>a</b>) Model I. (<b>b</b>) Model II. (<b>c</b>) Model III. (<b>d</b>) Model IV.</p>
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<p>Comparison of back-EMFs of four models at no-load state. (<b>a</b>) Back-EMF waveforms. (<b>b</b>) Corresponding harmonic spectra.</p>
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<p>Comparison of torque characteristics of four investigated models. (<b>a</b>) Cogging torque at no-load. (<b>b</b>) Steady torque at rated state.</p>
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<p>Average torque amplitudes versus current angle of four investigated models.</p>
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<p>The torque characteristics against copper losses. (<b>a</b>) Average torque value. (<b>b</b>) Torque ripple.</p>
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25 pages, 13011 KiB  
Article
A New Torque Control Approach for Torque Ripple Minimisation in Switched Reluctance Drives
by Ali Abdel-Aziz, Mohamed Elgenedy and Barry Williams
Energies 2024, 17(13), 3334; https://doi.org/10.3390/en17133334 - 7 Jul 2024
Viewed by 1412
Abstract
The switched reluctance motor (SRM) has many merits, such as robustness, a simple construction, low cost, and no permanent magnets. However, its deployment in servo applications is restrained due to acoustic noise and torque ripple (TR). This paper presents a new torque control [...] Read more.
The switched reluctance motor (SRM) has many merits, such as robustness, a simple construction, low cost, and no permanent magnets. However, its deployment in servo applications is restrained due to acoustic noise and torque ripple (TR). This paper presents a new torque control approach for TR reduction in switched reluctance drives. The approach is based on the maximum utilisation of the available dc-link voltage, hence extending the zero torque-ripple speed range. The approach is suitable for an SRM with any number of phases and stator/rotor poles. Soft switching control is deployed, which reduces switching losses. At any instant (regardless of the number of phases being conducted simultaneously), only one phase current is controlled. The well-established torque-sharing function concept is adapted and generalised to cater for more than two phases conducting simultaneously. MATLAB/Simulink confirmation simulations are based on the widely studied four-phase 8/6, 4 kW, 1500 rpm SRM. Full article
(This article belongs to the Section E: Electric Vehicles)
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<p>Block diagram: (<b>a</b>) conventional TSF and (<b>b</b>) proposed TCF.</p>
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<p>Typical voltage and current waveforms using ASHB.</p>
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<p>Illustration of the proposed TCF in mode #1.</p>
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<p>Flowchart of the proposed TCF in mode #1.</p>
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<p>Illustration of the proposed TCF in mode #2.</p>
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<p>Flowchart of the proposed TCF in mode #2.</p>
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<p>SRM performance at FLT and 1065 rpm using proposed TCF in mode #1: (<b>a</b>) flux linkage waveform, (<b>b</b>) rate of change of flux linkage (voltage demand), (<b>c</b>) current waveforms, and (<b>d</b>) torque waveforms.</p>
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<p>SRM performance at FLT and 1765 rpm using proposed TCF in mode #2: (<b>a</b>) flux linkage waveform, (<b>b</b>) rate of change of flux linkage (voltage demand), (<b>c</b>) current waveforms, and (<b>d</b>) torque waveforms.</p>
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<p>Current profiles at FLT and different speed limits.</p>
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<p>SRM performance at 100% FLT and 1065 rpm and 25% FLT and 2045 rpm using TCF mode #1: (<b>a</b>) rate of change of flux linkage (voltage demand), (<b>b</b>) current waveforms, and (<b>c</b>) torque waveforms.</p>
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<p>SRM performance at 100% FLT and 1765 rpm and 25% FLT and 2600 rpm using TCF mode #2: (<b>a</b>) rate of change of flux linkage (voltage demand), (<b>b</b>) current waveforms, and (<b>c</b>) torque waveforms.</p>
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<p>Effect of turn-on angle: (<b>a</b>) flux linkage waveform, (<b>b</b>) rate of change of flux linkage (voltage demand), (<b>c</b>) current waveforms, and (<b>d</b>) torque waveforms.</p>
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<p>Comparison of SRM performance at FLT and 1000 rpm using the proposed TCF and conventional TR-minimisation methods: (<b>a</b>) torque waveforms and (<b>b</b>) current waveforms.</p>
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<p>Comparison of SRM performance at FLT and 1750 rpm using the proposed TCF and conventional TR-minimisation methods: (<b>a</b>) torque waveforms and (<b>b</b>) current waveforms.</p>
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<p>Inductance profile.</p>
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<p>SRM single-phase equivalent circuit.</p>
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<p>SRM single-phase simulation diagram using LUTs.</p>
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<p>Simulation of SRM mechanical part.</p>
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<p>SRM 3D FEA model.</p>
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<p>Flux linkage–current–angle characteristics.</p>
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<p>Torque–current–angle characteristics.</p>
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16 pages, 10612 KiB  
Article
Sinusoidal Rotor Core Shape for Low Torque Ripple in Hollow-Cup Machines
by Liu Zhang, Zhanpeng Cui, Pengfei Song, Liming Wang and Xikai Liu
Energies 2024, 17(13), 3168; https://doi.org/10.3390/en17133168 - 27 Jun 2024
Cited by 1 | Viewed by 677
Abstract
Due to the configuration of coreless stators and two synchronously rotated rotors, hollow-cup machines (HCMs) enjoy the merits of negligible cogging torque and core loss. Consequently, HCMs have been successfully employed as high-speed electric machines in the aerospace field, which requires high precision [...] Read more.
Due to the configuration of coreless stators and two synchronously rotated rotors, hollow-cup machines (HCMs) enjoy the merits of negligible cogging torque and core loss. Consequently, HCMs have been successfully employed as high-speed electric machines in the aerospace field, which requires high precision and low thermal dissipation. However, the permanent magnet (PM) thickness and air-gap length of conventional HCM are uniform, resulting in various harmonics in the air-gap flux density as well as back-EMF. These harmonics inevitably produce an electromagnetic torque ripple, which has not met the increasing demand for ultraprecision in recent years. Since the inner rotor of HCMs only consists of an iron core, this paper proposes a novel sinusoidal-shaped inner rotor, which can change the harmonics of air-gap permeance, to adjust the harmonics of air-gap flux density and back-EMF. HCMs with the proposed inner rotors have a significant 87% reduction in torque ripple compared to conventional HCMs. Meanwhile, compared to conventional methods, HCMs with the proposed inner rotor exhibit comparable torque ripple and higher average torque. Full article
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<p>Topology of a conventional HCM.</p>
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<p>Air gap MMF generated by tile-shaped PMs.</p>
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<p>Air-gap permeance.</p>
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<p>Topology of HCM with proposed sinusoidal-shaped inner rotor.</p>
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<p>Phases of back-EMF harmonics versus phases of second, fourth, sixth, and eighth injected harmonics. (<b>a</b>) Fifth back-EMF harmonic; (<b>b</b>) seventh back-EMF harmonic.</p>
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<p>Amplitudes of back-EMF harmonics versus phases of second, fourth, sixth, and eighth injected harmonics. (<b>a</b>) Fifth back-EMF harmonic; (<b>b</b>) seventh back-EMF harmonic.</p>
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<p>Torque performance versus second, fourth, sixth, and eighth injected harmonic phases. (<b>a</b>) Average torque; (<b>b</b>) torque ripple.</p>
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<p>Amplitudes of the fifth and seventh back-EMF harmonics versus amplitudes of injected harmonics. (<b>a</b>) Second injected harmonic; (<b>b</b>) fourth injected harmonic; (<b>c</b>) sixth injected harmonic; (<b>d</b>) eighth injected harmonic.</p>
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<p>Torque performances versus amplitudes of second, fourth, sixth, and eighth injected harmonics. (<b>a</b>) Average torque; (<b>b</b>) torque ripple.</p>
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<p>Torque performance of the sixth harmonic injection. (<b>a</b>) Average torque; (<b>b</b>) torque ripple.</p>
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<p>Open-circuit radial air-gap flux densities. (<b>a</b>) Waveforms; (<b>b</b>) spectra.</p>
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<p>Open-circuit inductances. (<b>a</b>) <span class="html-italic">D</span>-axis inductances; (<b>b</b>) <span class="html-italic">Q</span>-axis inductances.</p>
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<p>Phase back-EMFs. (<b>a</b>) Waveforms; (<b>b</b>) spectra.</p>
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<p>On-load phase voltages. (<b>a</b>) Waveforms; (<b>b</b>) spectra.</p>
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<p>Rated torques. (<b>a</b>) Waveforms; (<b>b</b>) spectra.</p>
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<p>Illustration of conventional PM-shaping methods. (<b>a</b>) Bow-shaped PM; (<b>b</b>) PM with harmonic injection.</p>
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<p>Rated torque comparison between proposed sinusoidal-shaped inner rotor and conventional PM-shaping methods.</p>
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<p>Rated torque waveforms of HCMs with conventional methods of torque ripple reduction.</p>
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<p>Photos of the prototype machine. (<b>a</b>) Laminations; (<b>b</b>) rotors; (<b>c</b>) stator.</p>
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<p>Static test rig for rated torque measurement.</p>
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<p>Screenshot of measured phase back-EMFs below 2000 rpm.</p>
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<p>Comparison between 2D FE-predicted and measured phase back-EMFs below 2000 rpm. (<b>a</b>) Waveforms; (<b>b</b>) spectra.</p>
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<p>Comparison between 2D FE predicted and measured rated torques.</p>
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19 pages, 6540 KiB  
Article
Research on Torque Performance of Marine Hybrid Excitation Synchronous Motors Based on PSO Optimization of Magnetic Permeability Structure
by Qingliang Yang, Wendong Zhang and Chaohui Zhao
J. Mar. Sci. Eng. 2024, 12(7), 1064; https://doi.org/10.3390/jmse12071064 - 25 Jun 2024
Cited by 1 | Viewed by 793
Abstract
The rotor magnetic shunt structure hybrid excitation synchronous motor (RMS-HESM) has been widely used in marine propulsion due to its advantages of low loss and high efficiency. The objective of this paper is to improve the output torque capability of the hybrid excitation [...] Read more.
The rotor magnetic shunt structure hybrid excitation synchronous motor (RMS-HESM) has been widely used in marine propulsion due to its advantages of low loss and high efficiency. The objective of this paper is to improve the output torque capability of the hybrid excitation motor with a rotor magnetic shunt structure by conducting a multi-objective optimization design for the magnetic permeability structure. The first step involved establishing a mathematical analytical model of average torque and torque ripple based on the fundamental principle of motor magnetization. Next, the parameters of the magnetic permeability structure were designed and analyzed using the finite element simulation method. The impact of the variations in the parameters of the magnetic permeability structure on motor torque and no−load back electromotive force was examined. Additionally, a sensitivity analysis was performed on the design variables of the magnetic permeability structure, leading to the determination of optimization parameters based on the obtained results. The adaptive inertia weight-based particle swarm algorithm (PSO) was employed to conduct a multi-objective optimization design analysis. A comparative analysis on the average torque, torque ripple, and no−load back electromotive force of the motor before and after optimization was performed using the Maxwell and Workbench and Optislong joint simulation tools. This enhancement significantly improves the torque performance of the marine motor while simultaneously optimizing the no−load back electromotive force. Full article
(This article belongs to the Section Ocean Engineering)
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<p>Schematic diagram of RMS-HESM structure.</p>
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<p>Magnetic structure cross-sectional view.</p>
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<p>Flux path of RMS-HESM.</p>
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<p>Equivalent magnetic circuit diagram of the motor at the magnetic shunt point. (<b>a</b>) Equivalent magnetic circuit of HESM; (<b>b</b>) Simplified magnetic circuit of HESM.</p>
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<p>Analysis of the impact of the thickness ratio of the permanent magnets and pole claws on the average torque and torque ripple.</p>
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<p>Analysis of the influence of the thickness ratio of the permanent magnets and pole claws on the amplitude of the no−load back electromotive force.</p>
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<p>Analysis of the influence of the pole claw sloping shoulder distance and annular magnetic bridge length on the average torque and torque ripple.</p>
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<p>Analysis of the influence of the pole claw sloping shoulder distance and ring magnetic bridge length on the no−load back electromotive force amplitude.</p>
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<p>Schematic diagram of the position angle and radius of the auxiliary groove.</p>
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<p>Analysis of the impact of the auxiliary slot position angle and radius on the average torque and torque ripple.</p>
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<p>Analysis of the impact of the auxiliary slot position angle and radius on the no−load back electromotive force amplitude.</p>
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<p>The collaborative simulation models.</p>
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<p>Parameter sensitivity analysis.</p>
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<p>Pareto frontier diagram of the motor.</p>
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<p>Comparison before and after torque optimization.</p>
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<p>Comparison before and after no − load back EMF optimization.</p>
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<p>Comparison before and after air gap magnetic density optimization.</p>
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14 pages, 4458 KiB  
Article
Torque Ripple Suppression in the 6/4 Variable Flux Reluctance Machine with Open Winding Configuration by Using Harmonic Injection
by Xu Liu, El Moundher Aouiche, Abdelaziz Aouiche, Yang Cao and Mohammed Echarif Aguida
Energies 2024, 17(11), 2753; https://doi.org/10.3390/en17112753 - 4 Jun 2024
Viewed by 803
Abstract
High torque ripple can be observed with a 6/4 variable flux reluctance machine (VFRM). In order to minimize the torque ripple in VFRMs, this paper presents a harmonic injection method for 6/4 VFRMs with an open-winding configuration. By analyzing the impact of harmonics [...] Read more.
High torque ripple can be observed with a 6/4 variable flux reluctance machine (VFRM). In order to minimize the torque ripple in VFRMs, this paper presents a harmonic injection method for 6/4 VFRMs with an open-winding configuration. By analyzing the impact of harmonics on VFRMs, the method involves detecting the third harmonic using a first-order low-pass filter (FLPF). Subsequently, the extracted harmonics are controlled and shifted to counteract the voltage harmonics in both inverters without inducing phase imbalance or overvoltage. With the proposed method, the torque ripple can be significantly reduced by about 50% under load conditions. The effectiveness of the harmonic injection method is validated through a prototype VFRM. Full article
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<p>(<b>a</b>) Structure of VFRM with zero-sequence current excitation, (<b>b</b>) dual inverter with common DC link.</p>
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<p>(<b>a</b>) Self-inductance waveforms of the 6/4 VFRM (when <span class="html-italic">i</span><sub>0</sub> = 1 A and <span class="html-italic">ω</span><sub>e</sub> = 400 rpm). (<b>b</b>) Harmonic order of self-inductance.</p>
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<p>Third harmonic detection.</p>
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<p>Schematic of the third harmonic injection.</p>
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<p>Fundamental voltage reference and resultant third harmonic voltage.</p>
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<p>Overall harmonic-injection-based SSRFT strategy.</p>
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<p>Experimental test rig.</p>
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<p>(<b>a</b>) Extracted harmonics, (<b>b</b>) resultant voltages.</p>
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<p>Measured torque of VFRM. (<b>a</b>) Without harmonic injection, (<b>b</b>) With harmonic injection, (<b>c</b>) Comparison of torque harmonic order.</p>
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<p>Experimental current comparison: (<b>a</b>) without harmonic injection, (<b>b</b>) with harmonic injection.</p>
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<p>(<b>a</b>) Experimental results of three-phase currents: (upside left) without harmonic injection, (middle side left) with harmonic injection, (downside left) comparison of current harmonic order; (<b>b</b>) experimental results of reference voltages: (upside right) without harmonic injection, (middle side right) with harmonic injection, (downside right) comparison of voltage harmonic order.</p>
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18 pages, 9842 KiB  
Article
Design and Optimization of External Rotor Consequent Pole Permanent Magnet Motor with Low Iron Loss and Low Torque Ripple
by Liyan Guo, Hubin Yu and Huimin Wang
World Electr. Veh. J. 2024, 15(6), 232; https://doi.org/10.3390/wevj15060232 - 28 May 2024
Viewed by 890
Abstract
To reduce the iron loss and torque ripple of an external rotor consequent pole (ERCP) motor used in an electric vehicle air-conditioning compressor, the magnetic pole structure of the motor was improved, and an unequal piecewise consequent pole (CP) structure was designed. The [...] Read more.
To reduce the iron loss and torque ripple of an external rotor consequent pole (ERCP) motor used in an electric vehicle air-conditioning compressor, the magnetic pole structure of the motor was improved, and an unequal piecewise consequent pole (CP) structure was designed. The performance of the motor is optimized by reducing the harmonic content in the air gap flux density and reducing the iron saturation degree of the motor. The designed CP structure can significantly reduce the iron loss and torque ripple of the motor. Based on the Taguchi method, the optimal size parameters of the unequal piecewise CP structure are determined, and the final optimization design scheme is obtained. The results of finite element simulation and high-precision iron loss model show the following: compared with the original motor, the iron loss and torque ripple of the motor with the final optimized design scheme are significantly reduced. Full article
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<p>Physical model of the original motor.</p>
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<p>Physical model of the motor with unequal piecewise CP structure.</p>
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<p>The iron loss model calculation results and the test results at low frequency.</p>
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<p>The iron loss model calculation results and the test results at high frequency.</p>
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<p>The relative error between the iron loss model calculation results and the test results at low frequency.</p>
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<p>The relative error between the iron loss model calculation results and the test results at high frequency.</p>
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<p>The magnetic density distribution diagram of the original motor.</p>
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<p>The magnetic density distribution diagram of the preliminary improved motor.</p>
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<p>The flux density of the original motor and the preliminary improved motor at different positions.</p>
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<p>The unequal piecewise CP structure optimization variable diagram.</p>
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<p>Physical model of the final improved motor.</p>
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<p>FFT analysis of the no-load phase voltage of the original motor and the final improved motor.</p>
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<p>The torque diagram of the original motor and the final improved motor.</p>
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<p>The demagnetization analysis at different temperatures. (<b>a</b>) The demagnetization analysis of the motor at 100 °C. (<b>b</b>) The demagnetization analysis of the motor at 150 °C.</p>
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<p>The demagnetization analysis after 800A large current is introduced.</p>
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18 pages, 17861 KiB  
Article
Investigation of Torque and Reduction of Torque Ripples through Assisted-Poles in Low-Speed, High-Torque Density Spoke-Type PMSMs
by Sayyed Haleem Shah, Yun-Chong Wang, Dan Shi and Jian-Xin Shen
Machines 2024, 12(5), 327; https://doi.org/10.3390/machines12050327 - 10 May 2024
Cited by 1 | Viewed by 1278
Abstract
In this article, rotor designs utilizing assisted-poles are investigated for a high-torque density spoke-type permanent magnet synchronous machine (PMSM) with fractional slot concentrated winding (FSCW) to explore the rich air-gap magnetic field harmonics and torque generation mechanism. Due to their higher average torque [...] Read more.
In this article, rotor designs utilizing assisted-poles are investigated for a high-torque density spoke-type permanent magnet synchronous machine (PMSM) with fractional slot concentrated winding (FSCW) to explore the rich air-gap magnetic field harmonics and torque generation mechanism. Due to their higher average torque output, spoke-type PMSMs with FSCW are increasingly used in high-torque density applications. However, slot harmonics generate torque ripples that are difficult to eliminate in FSCW spoke-type PMSMs. Removing slot harmonics from the stator or winding results in a large drop in torque since their winding factors are identical to those of the main harmonic. Therefore, rotor designs having assisted-poles (symmetrical and asymmetrical) are investigated in this work to mitigate slot harmonics and minimize torque ripples. Firstly, the air-gap flux density is analyzed for the machines having assisted-poles, and a model of interaction between the stator and rotor-MMF harmonics is created and validated through Finite element analysis (FEA) to analyze the torque production mechanism. In addition, an analytical relationship between the assisted-poles’ dimensions and the generated torque harmonics is proposed. Furthermore, a generalized torque ripple reduction concept for the FSCW spoke-type PMSM having asymmetrically designed assisted-poles is presented. The proposed design and optimization method are validated through analytical calculations and FEA simulations, and a brief comparative analysis is presented for the analyzed machine prototypes. It has been established that the machine designed by applying the proposed asymmetrical assisted-poles can achieve a reduction in torque ripples while also significantly lowering cogging torque in comparison to the conventional spoke-type PMSMs and other spoke-type PMSMs with rotor having symmetrical assisted-poles. Full article
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<p>Analyzed designs of the prototype machine: (<b>a</b>) Assisted-poles symmetrical designs; (<b>b</b>) Assisted-poles asymmetrical design types.</p>
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<p>Harmonics in the air-gap flux density for the analyzed machine designs: (<b>a</b>) Radial harmonic orders; (<b>b</b>) Tangential harmonic orders.</p>
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<p>Air-gap flux density harmonic orders and torque contributions from symmetrical assisted-poles design cases.</p>
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<p>Back-EMF of the analyzed machine designs: (<b>a</b>) Waveforms; (<b>b</b>) Harmonic orders.</p>
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<p>Cogging torque waveforms for the analyzed machine designs.</p>
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<p>Generated torque for the analyzed machine designs: (<b>a</b>) waveform; (<b>b</b>) FFT analysis of the generated torque.</p>
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<p>Analyzed designs of the prototype machine with rotors having asymmetrical assisted-poles: (<b>a</b>) Type-I; (<b>b</b>) Type-II; (<b>c</b>) Type-III.</p>
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<p>Air-gap flux density for the analyzed machine designs: (<b>a</b>) Radial harmonic orders; (<b>b</b>) Tangential harmonic orders.</p>
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<p>Air-gap flux density harmonic orders and torque contributions for all the design cases.</p>
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<p>Machines back-EMF response: (<b>a</b>) Waveforms; (<b>b</b>) Harmonic orders.</p>
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<p>Cogging torque response for the machine prototypes.</p>
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<p>Generated torque response for the machine prototypes.</p>
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<p>Generated torque FFT for the machine prototypes.</p>
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<p>Machine designs torque response at different current angles: (<b>a</b>) Average torque; (<b>b</b>) Torque ripples.</p>
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