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12 pages, 6235 KiB  
Article
Hepatic Steatosis Analysis in Metabolic Dysfunction-Associated Steatotic Liver Disease Based on Artificial Intelligence
by Xiao-Xiao Wang, Yu-Yun Song, Rui Jin, Zi-Long Wang, Xiao-He Li, Qiang Yang, Xiao Teng, Fang-Fang Liu, Nan Wu, Yan-Di Xie, Hui-Ying Rao and Feng Liu
Diagnostics 2024, 14(24), 2889; https://doi.org/10.3390/diagnostics14242889 - 23 Dec 2024
Abstract
Background: Metabolic dysfunction-associated steatotic liver disease (MASLD) is characterized by the accumulation of fat in the liver, excluding excessive alcohol consumption and other known causes of liver injury. Animal models are often used to explore different pathogenic mechanisms and therapeutic targets of MASLD. [...] Read more.
Background: Metabolic dysfunction-associated steatotic liver disease (MASLD) is characterized by the accumulation of fat in the liver, excluding excessive alcohol consumption and other known causes of liver injury. Animal models are often used to explore different pathogenic mechanisms and therapeutic targets of MASLD. The aim of this study is to apply an artificial intelligence (AI) system based on second-harmonic generation (SHG)/two-photon-excited fluorescence (TPEF) technology to automatically assess the dynamic patterns of hepatic steatosis in MASLD mouse models. Methods: We evaluated the characteristics of hepatic steatosis in mouse models of MASLD using AI analysis based on SHG/TPEF images. Six different models of MASLD were induced in C57BL/6 mice by feeding with a western or high-fat diet, with or without fructose in their drinking water, and/or by weekly injections of carbon tetrachloride. Results: Body weight, serum lipids, and liver enzyme markers increased at 8 and 16 weeks in each model compared to baseline. Steatosis grade showed a steady upward trend. However, the non-alcoholic steatohepatitis (NASH) Clinical Research Network (CRN) histological scoring method detected no significant difference between 8 and 16 weeks. In contrast, AI analysis was able to quantify dynamic changes in the area, number, and size of hepatic steatosis automatically and objectively, making it more suitable for preclinical MASLD animal experiments. Conclusions: AI recognition technology may be a new tool for the accurate diagnosis of steatosis in MASLD, providing a more precise and objective method for evaluating steatosis in preclinical murine MASLD models under various experimental and treatment conditions. Full article
(This article belongs to the Special Issue Artificial Intelligence in Metabolic Diseases)
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<p>Flowchart of the imaging process and detection of fat vacuoles. (<b>A</b>) Images of unstained liver tissue samples were obtained using an SHG/TPEF imaging device (Genesis <sup>®</sup> 200). (<b>B</b>) All holes in the input images were detected in the TPE channel and classified using a pre-trained decision tree.</p>
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<p>Average body weight (<b>A</b>) and liver weight-to-body weight ratio (<b>B</b>) of the control group and six MASLD mouse models at different time points (0, 8, and 16 weeks; <span class="html-italic">n</span> = 5 at each time point). Note: *, <span class="html-italic">p</span> &lt; 0.05; **, <span class="html-italic">p</span> &lt; 0.01; ***, <span class="html-italic">p</span> &lt; 0.001; ****, <span class="html-italic">p</span> &lt; 0.0001; w, week; CCl4, Carbon tetrachloride; WD, Western diet; WDF, WD with high-fructose drinking water; WDF + CCl<sub>4</sub>, WDF plus intraperitoneal injection of CCl<sub>4</sub>; HFD, high-fat diet; HFDF, HFD with high-fructose drinking water; HFDF + CCl<sub>4</sub>, HFD plus intraperitoneal injection of CCl<sub>4</sub>.</p>
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<p>Serum levels of ALT (<b>A</b>), AST (<b>B</b>), cholesterol (CHO) (<b>C</b>), and low-density lipoprotein (LDL) (<b>D</b>) at different time points (0, 8, and 16 weeks) in the control group and six MASLD mouse models (<span class="html-italic">n</span> = 5 at each time point). Note: *, <span class="html-italic">p</span> &lt; 0.05; **, <span class="html-italic">p</span> &lt; 0.01; ****, <span class="html-italic">p</span> &lt; 0.0001; w, week; CCl<sub>4</sub>, Carbon tetrachloride; WD, Western diet; WDF, WD with high-fructose drinking water; WDF + CCl<sub>4</sub>, WDF plus intraperitoneal injection of CCl<sub>4</sub>; HFD, high-fat diet; HFDF, HFD with high-fructose drinking water; HFDF + CCl<sub>4</sub>, HFD plus intraperitoneal injection of CCl<sub>4</sub>.</p>
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<p>Representative images of H and E staining and SHG/TPEF at 8 and 16 weeks in the control group and six MASLD mouse models. In the H and E staining image, the percentages of vacuole area were shown as the percentages of steatosis, while in the SHG/TPEF image, the red channel represents TPEF, and the green channel represents SHG (collagen structure); the percentages of black fat vacuoles and surrounding affected areas were identified as the percentages of steatosis. H and E, Hematoxylin and eosin; SHG/TPEF, second-harmonic generation/two-photon-excited fluorescence; w, week; CCl<sub>4</sub>, Carbon tetrachloride; WD, Western diet; WDF, WD with high-fructose drinking water; WDF + CCl<sub>4</sub>, WDF plus intraperitoneal injection of CCl<sub>4</sub>; HFD, high-fat diet; HFDF, HFD with high-fructose drinking water; HFDF + CCl<sub>4</sub>, HFD plus intraperitoneal injection of CCl<sub>4</sub>; Bar: 200 μm.</p>
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<p>Steatosis quantification in the control group and six MASLD mouse model groups at different time points (0, 8, and 16 weeks). Quantitative parameters of steatosis (fat vacuoles and affected cell area) based on SHG/TPEF images. Note: *, <span class="html-italic">p</span> &lt; 0.05; **, <span class="html-italic">p</span> &lt; 0.01; ***, <span class="html-italic">p</span> &lt; 0.001; ****, <span class="html-italic">p</span> &lt; 0.0001; the number of samples in each group was 5; w, week; CCl<sub>4</sub>, Carbon tetrachloride; WD, Western diet; WDF, WD with high-fructose drinking water; WDF + CCl<sub>4</sub>, WDF plus intraperitoneal injection of CCl<sub>4</sub>; HFD, high-fat diet; HFDF, HFD with high-fructose drinking water; HFDF + CCl<sub>4</sub>, HFD plus intraperitoneal injection of CCl<sub>4</sub>.</p>
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<p>Fat vacuole distribution at different time points (0, 8, and 16 weeks) among the control group and six MASLD mouse models. The x-axis represents the diameter of the fat vacuoles (µm), whereas the y-axis represents the number of fat vacuoles per unit area (mm<sup>2</sup>), corresponding to the diameter of the fat vacuoles. Note: The comparison between different weeks of the same model is based on the difference in fat vacuole distribution according to their diameter per unit area. The <span class="html-italic">p</span>-value of the KS test is shown in the figure. w, week; CCl<sub>4</sub>, Carbon tetrachloride; WD, Western diet; WDF, WD with high-fructose drinking water; WDF + CCl<sub>4</sub>, WDF plus intraperitoneal injection of CCl<sub>4</sub>; HFD, high-fat diet; HFDF, HFD with high-fructose drinking water; HFDF + CCl<sub>4</sub>, HFD plus intraperitoneal injection of CCl<sub>4</sub>.</p>
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15 pages, 8380 KiB  
Article
Design and Analysis of a Low Torque Ripple Permanent Magnet Synchronous Machine for Flywheel Energy Storage Systems
by Yubo Sun, Zhenghui Zhao and Qian Zhang
Energies 2024, 17(24), 6337; https://doi.org/10.3390/en17246337 - 16 Dec 2024
Viewed by 381
Abstract
Flywheel energy storage systems (FESS) are technologies that use a rotating flywheel to store and release energy. Permanent magnet synchronous machines (PMSMs) are commonly used in FESS due to their high torque and power densities. One of the critical requirements for PMSMs in [...] Read more.
Flywheel energy storage systems (FESS) are technologies that use a rotating flywheel to store and release energy. Permanent magnet synchronous machines (PMSMs) are commonly used in FESS due to their high torque and power densities. One of the critical requirements for PMSMs in FESS is low torque ripple. Therefore, a PMSM with eccentric permanent magnets is proposed and analyzed in this article to reduce torque ripple. Cogging torque, a significant contributor to torque ripple, is investigated by a combination of finite element analysis and the analytical method. An integer-slot distribution winding structure is adopted to reduce vibration and noise. Moreover, the effects of eccentric permanent magnets and harmonic injection on the cogging torque are analyzed and compared. In addition, the electromagnetic performance is analyzed, and the torque ripple is found to be 3.1%. Finally, a prototype is built and tested, yielding a torque ripple of 3.9%, to verify the theoretical analysis. Full article
(This article belongs to the Special Issue Energy, Electrical and Power Engineering: 3rd Edition)
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<p>Topology of proposed PMSM.</p>
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<p>Winding connection.</p>
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<p>Analysis model of surface-mounted PMSM.</p>
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<p>Bread-type eccentric permanent magnet.</p>
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<p>Influence of eccentricity on torque performance.</p>
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<p>Cogging torque of PMSM with different permanent magnets.</p>
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<p>Air gap magnetic densities of PMSM with different permanent magnets. (<b>a</b>) Radial air gap magnetic densities. (<b>b</b>) Tangential air gap magnetic densities. (<b>c</b>) Harmonic order.</p>
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<p>Cogging torque contribution of different harmonics. (<b>a</b>) PMSM with original permanent magnets. (<b>b</b>) PMSM with eccentric permanent magnets.</p>
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<p>Permanent magnet with third harmonic injection.</p>
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<p>Cogging torque of PMSM with harmonic injection. (<b>a</b>) Effect of harmonic injection. (<b>b</b>) Contribution of harmonics.</p>
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<p>Load electromagnetic performance. (<b>a</b>) Magnetic field line. (<b>b</b>) Magnetic flux density.</p>
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<p>Back electromotive force of PMSM.</p>
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<p>Torque performance of PMSM. (<b>a</b>) Cogging torque. (<b>b</b>) Torque.</p>
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<p>Vibration acceleration of PMSM with different permanent magnets.</p>
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<p>Prototype.</p>
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<p>Experimental platform.</p>
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<p>Vibration and noise test platform.</p>
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<p>Comparison of experimental and simulated results. (<b>a</b>) Back electromotive force of prototype. (<b>b</b>) Comparison of back electromotive force coefficient.</p>
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<p>Experimental results. (<b>a</b>) Torque. (<b>b</b>) Vibration acceleration.</p>
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14 pages, 51619 KiB  
Article
Current Harmonics Suppression of Six-Phase Permanent-Magnet Synchronous Motor Drives Using Back-Electromotive Force Harmonics Compensation
by Po-Sheng Huang, Cheng-Ting Tsai, Jonq-Chin Hwang, Cheng-Tsung Lin and Yu-Ting Lin
Energies 2024, 17(24), 6280; https://doi.org/10.3390/en17246280 - 12 Dec 2024
Viewed by 471
Abstract
This paper investigates a back-electromotive force (EMF) harmonic compensation strategy for six-phase permanent-magnet synchronous motors (PMSMs) to reduce current harmonics and improve system performance. Ideally, the back-EMF waveform should be perfectly sinusoidal. However, manufacturing imperfections such as suboptimal magnetic circuit design, uneven winding [...] Read more.
This paper investigates a back-electromotive force (EMF) harmonic compensation strategy for six-phase permanent-magnet synchronous motors (PMSMs) to reduce current harmonics and improve system performance. Ideally, the back-EMF waveform should be perfectly sinusoidal. However, manufacturing imperfections such as suboptimal magnetic circuit design, uneven winding distribution, and mechanical eccentricity introduce low-order spatial harmonics, particularly the 5th, 7th, 11th, and 13th orders, which distort the back-EMF, increase current harmonics, complicate control, and reduce efficiency. To address these issues, this study proposes a compensation strategy utilizing common-mode and differential-mode current control. By injecting the 6th and 12th harmonics into the decoupled voltage commands along the d-axis and q-axis, the strategy significantly reduces current harmonic distortion. Experimental validation was conducted using a TMS320F28386D microcontroller, which controlled dual inverters via PWM signals and processed real-time current feedback. Rotor position feedback was provided by a resolver to ensure precise and responsive motor control. At a rotational speed of 900 rpm, with a peak phase current Im of 200 A and an IGBT switching frequency of 10 kHz, the phase-a current total harmonic distortion (THD) was reduced from 11.86% (without compensation) to 6.83% (with compensation). This study focused on mitigating harmonics below the 14th order. The experimental results demonstrate that the proposed back-EMF harmonic compensation strategy effectively minimizes current THD, highlighting its potential for improving the performance and efficiency of multi-phase motor systems. Full article
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<p>Six-phase PMSM back-EMF measurement system block diagram.</p>
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<p>Phase-<span class="html-italic">a</span> and phase-<span class="html-italic">x</span> back-EMF measurement.</p>
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<p>The waveform of the measured and reconstructed phase-<span class="html-italic">a</span> and phase-<span class="html-italic">x</span> back-EMF: (<b>a</b>) phase-<span class="html-italic">a</span> and phase-<span class="html-italic">x</span> back-EMF waveform; (<b>b</b>) zoomed-in waveform.</p>
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<p>Six-phase PMSM common-mode and differential-mode current closed-loop control block.</p>
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<p>Simulated phase-<span class="html-italic">a</span> current waveform and harmonic histogram: (<b>a</b>) Without compensation. (<b>b</b>) With compensation.</p>
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<p>Histogram of the THD reduction in simulation result.</p>
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<p>Photos of the six-phase PMSM testbench: (<b>a</b>) Setup with the dynamometer driving the six-phase PMSM. (<b>b</b>) Six-phase PMSM drive system.</p>
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<p>Actual phase-<span class="html-italic">a</span> current waveform and harmonic histogram: (<b>a</b>) Without compensation. (<b>b</b>) With compensation.</p>
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<p>Histogram of the THD reduction in actual result.</p>
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16 pages, 3829 KiB  
Article
Research on Radial Vibration Model and Low-Frequency Vibration Suppression Method in PMSM by Injecting Multiple Symmetric Harmonic Currents
by Le Kang, He Zhang, Jiakuan Xia, Meijun Qi and Yunqi Zhao
Actuators 2024, 13(11), 448; https://doi.org/10.3390/act13110448 - 8 Nov 2024
Viewed by 612
Abstract
Driven by frequency conversion, the windings of a three-phase permanent magnet synchronous motor (PMSM) contain both odd and even harmonic currents. Due to the motor’s pole–slot conductance modulation, the interaction between the magnetic fields generated by these harmonic currents and the permanent magnet [...] Read more.
Driven by frequency conversion, the windings of a three-phase permanent magnet synchronous motor (PMSM) contain both odd and even harmonic currents. Due to the motor’s pole–slot conductance modulation, the interaction between the magnetic fields generated by these harmonic currents and the permanent magnet field results in harmonic radial vibrations of the motor. This paper analyzes the three-phase currents of the prototype and derives the radial magnetomotive force (MMF) spatiotemporal models for symmetric harmonic currents. By integrating Maxwell’s magnetic force formula and vibration response formula, the radial vibration models for symmetric harmonic currents are developed. The characteristics of vibrations caused by odd and even harmonic currents, as well as positive sequence and negative sequence harmonic currents, are analyzed separately. A cyclic sequence, low-frequency vibration suppression control method incorporating multiple harmonic current injections was designed. Experimental results of this method are compared with those obtained using an ideal sinusoidal current. Except for the second harmonic vibration, all other vibrations are significantly suppressed, with a maximum suppression rate of 92.28%. The total vibration level is reduced by 12.7619 dB, and the average torque is reduced by 0.67% with the total harmonic distortion of the current at 2.89%. The experimental results show that the vibration method in this paper has little influence on the average torque of the motor, the current distortion rate is small, and the vibration suppression effect is good. Full article
(This article belongs to the Section Control Systems)
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<p>The time domain diagram of the motor radial vibration.</p>
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<p>The amplitude spectrums of radial vibration with kth harmonic current injection. (<b>a</b>) The vibration caused by no injection and injection of positive and negative sequence 6th harmonic current; (<b>b</b>) The vibration caused by no injection and injection of positive and negative sequence 7th harmonic current.</p>
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<p>Vibration amplitude variation with seventh harmonic current injection.</p>
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<p>Sixth harmonic vibration amplitude versus phase change.</p>
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<p>Sixth harmonic vibration amplitude versus amplitude change.</p>
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<p>Experimental setup.</p>
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<p>The three-phase current time domain diagram. (<b>a</b>) The three phase current before harmonic current injection; (<b>b</b>) The three phase current with the ideal sinusoidal current; (<b>c</b>) The three phase current with the vibration suppression method in this paper.</p>
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<p>The current amplitude spectrum diagram. (<b>a</b>) The spectrogram of phase current amplitude before harmonic current injection; (<b>b</b>) The spectrogram of phase current amplitude with the ideal sinusoidal current; (<b>c</b>) The spectrogram of phase current amplitude with the vibration suppression method in this paper.</p>
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<p>Radial vibration time domain diagram. (<b>a</b>) The radial vibration of the motor before harmonic current injection; (<b>b</b>) The radial vibration of the motor with the ideal sinusoidal current; (<b>c</b>) The radial vibration of the motor with the vibration suppression method in this paper.</p>
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<p>Radial vibration time domain diagram. (<b>a</b>) The radial vibration of the motor before harmonic current injection; (<b>b</b>) The radial vibration of the motor with the ideal sinusoidal current; (<b>c</b>) The radial vibration of the motor with the vibration suppression method in this paper.</p>
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<p>Radial vibration amplitude spectrum diagram. (<b>a</b>) The spectrogram of radial vibration before harmonic current injection; (<b>b</b>) The spectrogram of radial vibration with the ideal sinusoidal current; (<b>c</b>) The spectrogram of radial vibration with the vibration suppression method in this paper.</p>
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32 pages, 437 KiB  
Article
The Dirac-Dolbeault Operator Approach to the Hodge Conjecture
by Simone Farinelli
Symmetry 2024, 16(10), 1291; https://doi.org/10.3390/sym16101291 - 1 Oct 2024
Viewed by 2058
Abstract
The Dirac-Dolbeault operator for a compact Kähler manifold is a special case of Dirac operator. The Green function for the Dirac Laplacian over a Riemannian manifold with boundary allows the expression of the values of the sections of the Dirac bundle in terms [...] Read more.
The Dirac-Dolbeault operator for a compact Kähler manifold is a special case of Dirac operator. The Green function for the Dirac Laplacian over a Riemannian manifold with boundary allows the expression of the values of the sections of the Dirac bundle in terms of the values on the boundary, extending the mean value theorem of harmonic analysis. Utilizing this representation and the Nash–Moser generalized inverse function theorem, we prove the existence of complex submanifolds of a complex projective manifold satisfying globally a certain partial differential equation under a certain injectivity assumption. Thereby, internal symmetries of Dolbeault and rational Hodge cohomologies play a crucial role. Next, we show the existence of complex submanifolds whose fundamental classes span the rational Hodge classes, proving the Hodge conjecture for complex projective manifolds. Full article
(This article belongs to the Section Mathematics)
16 pages, 5512 KiB  
Article
Half-Wave Phase Shift Modulation for Hybrid Modular Multilevel Converter with Wide-Range Operation
by Junchao Ma, Yan Peng, Zimeng Su, Yilei Gu, Qiulong Ni, Ying Yang, Yi Wang and Jianing Liu
Electronics 2024, 13(17), 3556; https://doi.org/10.3390/electronics13173556 - 7 Sep 2024
Viewed by 789
Abstract
Hybrid modular multilevel converters (MMCs), which combine submodule chain links and device series switches, offer advantages such as lower costs and smaller volumes compared with MMCs. However, the hybrid MMCs only operate at a fixed modulation ratio, potentially compromising system adjustment ability. This [...] Read more.
Hybrid modular multilevel converters (MMCs), which combine submodule chain links and device series switches, offer advantages such as lower costs and smaller volumes compared with MMCs. However, the hybrid MMCs only operate at a fixed modulation ratio, potentially compromising system adjustment ability. This paper presents a half-wave phase shift modulation (HPSM) strategy aimed at extending the operation range of a hybrid MMC. First, the commutation angle is introduced as a control variable to change the fixed voltage modulation ratio. The energy balance of the converter is completed by adjusting the commutation angle. Then, the operation performance for the half-wave alternating multilevel converter (HAMC) with the proposed HPSM strategy is analyzed. Finally, the full-scale simulations are carried out to verify the theoretical analysis and the feasibility of the proposed control strategy. Compared to the third-order harmonic current injection (THCI) strategy, HPSM reduces operating losses by 50% and demonstrates superior control performance. Full article
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<p>HAMC topology.</p>
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<p>HAMC operation mode of phase a.</p>
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<p>HAMC operation mode switching principle.</p>
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<p>Principle of half-wave phase shift modulation.</p>
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<p>Variation in the commutation angle with the power factor angle and the modulation ratio.</p>
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<p>Variation in the maximal multiplexed arm voltage with power factor angle and modulation ratio.</p>
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<p>Structure of the simulated systems.</p>
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<p>Phase and sub-module voltages for HAMC.</p>
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<p>Simulation results of the multiplexed arm and switches of HAMC.</p>
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<p>Simulation results of the multiplexed arm and switches of HAMC.</p>
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<p>Dynamic simulation results of HAMC.</p>
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<p>Experimental prototype of HAMC.</p>
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<p>Experimental Ac voltage and current waveforms of HAMC.</p>
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<p>Multiplexed arm voltage, current, and capacitor voltage of phase a.</p>
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18 pages, 4381 KiB  
Article
Active Vibration Control via Current Injection in Electric Motors
by Marco Bassani, Daniel Pinardi, Andrea Toscani, Elisabetta Manconi and Carlo Concari
Electronics 2024, 13(17), 3442; https://doi.org/10.3390/electronics13173442 - 30 Aug 2024
Viewed by 1160
Abstract
This work presents a technique to actively reduce the vibrations generated by magnetic anisotropy in sinusoidal brushless motors through current injection. These vibrations are an unwanted phenomenon mainly generated by the interaction between the rotor magnets and the stator teeth. These produce vibrations [...] Read more.
This work presents a technique to actively reduce the vibrations generated by magnetic anisotropy in sinusoidal brushless motors through current injection. These vibrations are an unwanted phenomenon mainly generated by the interaction between the rotor magnets and the stator teeth. These produce vibrations which are then transmitted to the frame and other mechanical parts such as bearings, gearboxes, transmissions, and joints, thus reducing the life, performance, and reliability of these components. First, different design strategies and control algorithms to passively and actively attenuate the vibrations are reviewed. Then, a narrowband active method that attenuates a harmonic vibration through the injection of a harmonic current is presented. The effectiveness of the proposed method was demonstrated on a prototype of a Surface Permanent Magnet Synchronous Motor (SPMSM). For the motor under test, an attenuation of −13.5 dB at 650 rpm and −29 dB at 800 rpm was achieved on the main frequency component, caused by the magnetic anisotropy, which in turn corresponds to the 72nd harmonic of the rotor mechanical speed. Full article
(This article belongs to the Section Industrial Electronics)
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<p>Block scheme of the field-oriented control, where <math display="inline"><semantics> <mrow> <msubsup> <mi>i</mi> <mi>d</mi> <mo>*</mo> </msubsup> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msubsup> <mi>i</mi> <mi>q</mi> <mo>*</mo> </msubsup> </mrow> </semantics></math> represent reference values.</p>
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<p>Block scheme of the observer.</p>
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<p>Block scheme of the modified field-oriented control with current injection, where <math display="inline"><semantics> <mrow> <msubsup> <mi>i</mi> <mi>d</mi> <mo>*</mo> </msubsup> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msubsup> <mi>i</mi> <mi>q</mi> <mo>*</mo> </msubsup> </mrow> </semantics></math> represent reference values.</p>
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<p>MATLAB/Simulink model of the proposed active vibration control: scheme of the classic d–q axis control of the motor (<b>lower</b> part), compensation strategy block (<b>upper</b> part).</p>
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<p>Motor torque waveform for compensated and uncompensated control.</p>
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<p>Electric motor employed for the tests mounted on the motor test bench.</p>
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<p>Image (<b>left</b>) and schematic (<b>right</b>) of the complete acquisition system consisting of power supply unit (PSU), electric drive, electric motor (EM), DAQ system, and a personal computer (PC).</p>
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<p>Spectrum of the acceleration level along the Y direction at 650 rpm (<b>left</b>). A close-up of the acceleration level spectrum on the 71st, 72nd, and 73rd harmonics (<b>right</b>), <span class="html-italic">F</span><sub>71</sub> = 769.2 Hz, <span class="html-italic">F<sub>t</sub></span> = 780 Hz, <span class="html-italic">F</span><sub>73</sub> = 790.8 Hz, respectively.</p>
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<p>Spectrum of the acceleration level along the Y direction at 800 rpm (<b>left</b>). A close-up of the acceleration level spectrum on the 71st, 72nd, and 73rd harmonics (<b>right</b>), <span class="html-italic">F</span><sub>71</sub> = 946.7 Hz, <span class="html-italic">F<sub>t</sub></span> = 960 Hz, <span class="html-italic">F</span><sub>73</sub> = 973.3 Hz, respectively.</p>
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<p>Acceleration reduction in dB along Y direction for the 650 rpm case (<b>left</b>), <span class="html-italic">F<sub>t</sub></span> = 780 Hz, and for the 800 rpm case (<b>right</b>), <span class="html-italic">F<sub>t</sub></span> = 960 Hz.</p>
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<p>Spectra of the acceleration level along the Y direction at 650 rpm (<b>left</b>) and 800 rpm (<b>right</b>), with AVC system switched off (solid line) and on (dotted line).</p>
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20 pages, 61711 KiB  
Article
Harmonic Suppression in Permanent Magnet Synchronous Motor Currents Based on Quasi-Proportional-Resonant Sliding Mode Control
by Kelu Wu, Yongchao Zhang, Wenqi Lu, Yubao Qi and Weimin Shi
Appl. Sci. 2024, 14(16), 7206; https://doi.org/10.3390/app14167206 - 16 Aug 2024
Cited by 1 | Viewed by 967
Abstract
The output voltage of inverters is influenced by nonlinear factors such as dead time and voltage drops, injecting low-order harmonics. This results in fifth and seventh harmonic distortions in the stator current, causing periodic torque ripples and significantly affecting the control precision of [...] Read more.
The output voltage of inverters is influenced by nonlinear factors such as dead time and voltage drops, injecting low-order harmonics. This results in fifth and seventh harmonic distortions in the stator current, causing periodic torque ripples and significantly affecting the control precision of Permanent Magnet Synchronous Motors (PMSMs). To address this issue, this paper proposes a control strategy named quasi-proportional-resonant sliding mode control (QPR-SMC). Initially, sliding mode control is employed as the current controller to enhance disturbance rejection capability and provide a rapid dynamic response. Subsequently, a quasi-proportional-resonant controller is introduced to extract the sixth harmonic component from the current, which is then used as a compensation term for the sliding mode control surface. Finally, the current tracking error and the compensation term are combined as inputs to the sliding mode control law, forming a current error-proportional resonant-sliding mode control surface. This approach enhances the harmonic suppression capability of the system. The results demonstrate that the proposed method effectively reduces the fifth and seventh harmonic components in the three-phase current and mitigates motor jitter by suppressing the sixth harmonic in the d–q coordinate system. Full article
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<p>Bode plot of the ideal resonant controller and the quasi-resonant controller.</p>
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<p>Principles of harmonic suppression based on QPR.</p>
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<p>Bode plot of the quasi-proportional-resonant controller with different parameter values.</p>
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<p>Bode plot of the quasi-proportional-resonant controller with <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>k</mi> </mrow> <mrow> <mi>p</mi> </mrow> </msub> <mo> </mo> </mrow> </semantics></math>= 0.1, <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>k</mi> </mrow> <mrow> <mi>r</mi> </mrow> </msub> <mo> </mo> </mrow> </semantics></math>= 80, and <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>w</mi> </mrow> <mrow> <mi>c</mi> <mo> </mo> </mrow> </msub> </mrow> </semantics></math> = 2 rad/s.</p>
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<p>Bode plot of the system.</p>
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<p>A system control block diagram.</p>
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<p>A structural block diagram of the current error-proportional resonant-sliding mode control surface.</p>
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<p>The motor drive test platform.</p>
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<p>Phase current and load torque waveforms at low speed (450 r/min). (<b>a</b>) Phase current waveform. (<b>b</b>) Load torque waveform.</p>
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<p>Frequency spectrum of the phase current at low speed.</p>
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<p>Phase current and load torque waveforms at low speed (1125 r/min). (<b>a</b>) Phase current waveform. (<b>b</b>) Load torque waveform.</p>
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<p>Frequency spectrum of the phase current at medium speed.</p>
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<p>Phase current and load torque waveforms at low speed (2250 r/min). (<b>a</b>) Phase current waveform. (<b>b</b>) Load torque waveform.</p>
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<p>Frequency spectrum of the phase current at high speed.</p>
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<p>Phase current and torque waveforms at low speed (450 r/min) under the QPR-PI and QPR-SMC control strategies. (<b>a</b>) Phase current waveform under the QPR-PI control strategy. (<b>b</b>) Torque waveform under the QPR-PI control strategy. (<b>c</b>) Phase current waveform under the QPR-SMC control strategy. (<b>d</b>) Torque waveform under the QPR-SMC control strategy.</p>
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<p>Frequency spectrum of the phase current at low speed: (<b>a</b>) under the QPR-PI control strategy; (<b>b</b>) under the QPR-SMC control strategy.</p>
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<p>Phase current and torque waveforms at low speed (1125 r/min) under the QPR-PI and QPR-SMC control strategies. (<b>a</b>) Phase current waveform under the QPR-PI control strategy. (<b>b</b>) Torque waveform under the QPR-PI control strategy. (<b>c</b>) Phase current waveform under the QPR-SMC control strategy. (<b>d</b>) Torque waveform under the QPR-SMC control strategy.</p>
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<p>Frequency spectrum of the phase current at medium speed: (<b>a</b>) under the QPR-PI control strategy; (<b>b</b>) under the QPR-SMC control strategy.</p>
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<p>Phase current and torque waveforms at low speed (2250 r/min) under the QPR-PI and QPR-SMC control strategies. (<b>a</b>) Phase current waveform under the QPR-PI control strategy. (<b>b</b>) Torque waveform under the QPR-PI control strategy. (<b>c</b>) Phase current waveform under the QPR-SMC control strategy. (<b>d</b>) Torque waveform under the QPR-SMC control strategy.</p>
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<p>Frequency spectrum of the phase current at high speed: (<b>a</b>) under the QPR-PI control strategy; (<b>b</b>) under the QPR-SMC control strategy.</p>
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<p>Harmonic analysis results for PI, QPR-PI, and QPR-SMC control methods at different speeds: (<b>a</b>) Suppression results at low speed; (<b>b</b>) Suppression results at medium speed; (<b>c</b>) Suppression results at high speed.</p>
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16 pages, 3737 KiB  
Article
An Improved Series 36-Pulse Rectifier Based on Dual Passive Pulse-Doubling Circuit on the System DC Side
by Xiuqing Mu, Xiaoqiang Chen, Chungui Ma, Ying Wang, Tun Bai, Leijiao Ge and Xiping Ma
Electronics 2024, 13(16), 3215; https://doi.org/10.3390/electronics13163215 - 14 Aug 2024
Viewed by 687
Abstract
The series-type 12-pulse rectifier generates a large amount of harmonics in the AC side current due to the strong nonlinearity of its rectifying diodes, causing serious harmonic pollution to the power grid. This article proposes a series 36-pulse rectifier based on a DC [...] Read more.
The series-type 12-pulse rectifier generates a large amount of harmonics in the AC side current due to the strong nonlinearity of its rectifying diodes, causing serious harmonic pollution to the power grid. This article proposes a series 36-pulse rectifier based on a DC side dual passive frequency-doubling circuit to suppress the AC side current harmonics of a 12-pulse rectifier. The rectifier uses two symmetrical passive pulse multiplication circuits to regulate the circulation in the DC side circuit, increasing the output voltage and current state of the rectifier bridge, thereby increasing the number of pulses in the rectifier from 12 times to 36 times. Firstly, the working principle of the rectifier and the working mode of the dual passive frequency-doubling circuit were analyzed. Secondly, the harmonic suppression mechanism of the rectifier input current was revealed, and the frequency-doubling characteristics of the load voltage were analyzed. Finally, the correctness of the theoretical analysis was verified through a semi-physical platform. The verification and comparison results show that under the optimal conditions of the injecting transformer turns ratio, the DPPC can not only reduce the THD value of the input current by about 1/3 (from 14.87% to 4.78%) but can also increase the fluctuation frequency of the load voltage by 3 times (from 12 to 36), while improving the power quality of the AC/DC side rectifier and achieving the low harmonic operation of the rectifier. The proposed 36-pulse rectifier can effectively suppress harmonics; it has the advantages of simple structure, strong robustness, and high output voltage gain, and it is suitable for medium-voltage and high-voltage high-power rectification applications. Full article
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<p>Series 36-pulse rectification system based on DPPC on DC side.</p>
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<p>Winding structure of isolation transformer.</p>
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<p>Winding structure of injection transformer.</p>
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<p>Working modes of DPPC.</p>
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<p>Main current waveforms of the rectifier.</p>
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<p>The relation of input current THD with the turn ratio <span class="html-italic">m</span> and <span class="html-italic">ρ</span> of the injection transformer.</p>
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<p>Starsim semi-physical testing platform.</p>
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<p>Test waveforms of rectifier input current and output voltage.</p>
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<p>Harmonic comparison of rectifier input current <span class="html-italic">i</span><sub>a.</sub></p>
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<p>The main current waveforms of the rectifier.</p>
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36 pages, 28072 KiB  
Article
Four-Wire Three-Level NPC Shunt Active Power Filter Using Model Predictive Control Based on the Grid-Tied PV System for Power Quality Enhancement
by Zoubida Amrani, Abdelkader Beladel, Abdellah Kouzou, Jose Rodriguez and Mohamed Abdelrahem
Energies 2024, 17(15), 3822; https://doi.org/10.3390/en17153822 - 2 Aug 2024
Viewed by 1041
Abstract
The primary objective of this paper focuses on developing a control approach to improve the operational performance of a three-level neutral point clamped (3LNPC) shunt active power filter (SAPF) within a grid-tied PV system configuration. Indeed, this developed control approach, based on the [...] Read more.
The primary objective of this paper focuses on developing a control approach to improve the operational performance of a three-level neutral point clamped (3LNPC) shunt active power filter (SAPF) within a grid-tied PV system configuration. Indeed, this developed control approach, based on the used 3LNPC-SAPF topology, aims to ensure the seamless integration of a photovoltaic system into the three-phase four-wire grid while effectively mitigating grid harmonics, grid current unbalance, ensuring grid unit power factor by compensating the load reactive power, and allowing power sharing with the grid in case of an excess of generated power from the PV system, leading to overall high power quality at the grid side. This developed approach is based initially on the application of the four-wire instantaneous p-q theory for the identification of the reference currents that have to be injected by the 3LNPC-SAPF in the grid point of common coupling (PCC). Whereas, the 3LNPC is controlled based on using the finite control set model predictive control (FCS-MPC), which can be accomplished by determining the convenient set of switch states leading to the voltage vector, which is the most suitable to ensure the minimization of the selected cost function. Furthermore, the used topology requires a constant DC-link voltage and balanced split-capacitor voltages at the input side of the 3LNPN. Hence, the cost function is adjusted by the addition of another term with a selected weighting factor related to these voltages to ensure their precise control following the required reference values. However, due to the random changes in solar irradiance and, furthermore, to ensure efficient operation of the proposed topology, the PV system is connected to the 3LNPN-SAPF via a DC/DC boost converter to ensure the stability of the 3LNPN input voltage within the reference value, which is achieved in this paper based on the use of the maximum power point tracking (MPPT) technique. For the validation of the proposed control technique and the functionality of the used topology, a set of simulations has been presented and investigated in this paper following different irradiance profile scenarios such as a constant irradiance profile and a variables irradiance profile where the main aim is to prove the effectiveness and flexibility of the proposed approach under variable irradiance conditions. The obtained results based on the simulations carried out in this study demonstrate that the proposed control approach with the used topology under different loads such as linear, non-linear, and unbalanced can effectively reduce the harmonics, eliminating the unbalance in the currents and compensating for the reactive component contained in the grid side. The obtained results prove also that the proposed control ensures a consistent flow of power based on the sharing principle between the grid and the PV system as well as enabling the efficient satisfaction of the load demand. It can be said that the proposal presented in this paper has been proven to have many dominant features such as the ability to accurately estimate the power sharing between the grid and the PV system for ensuring the harmonics elimination, the reactive power compensation, and the elimination of the neutral current based on the zero-sequence component compensation, even under variable irradiance conditions. This feature makes the used topology and the developed control a valuable tool for power quality improvement and grid stability enhancement with low cost and under clean energy. Full article
(This article belongs to the Section A2: Solar Energy and Photovoltaic Systems)
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<p>Proposed configuration of the grid connected to two-stage photovoltaic systems using an active power filter (APF) with a control strategy that is based on a three-level NPC inverter.</p>
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<p>Single diode model of the PV module.</p>
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<p>PV array at 25 °C and specified irradiances (250, 500 and 1000 w/m<sup>2</sup>), (<b>a</b>) the out put current versu the out put voltage, (<b>b</b>) the output power versus the output voltage.</p>
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<p>Boost topology.</p>
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<p>Flowchart of the P and O algorithm.</p>
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<p>Three-level NPC multilevel converter power circuit.</p>
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<p>An analogous circuit consisting of an APF that is linked in parallel.</p>
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<p>The illustration of reference current calculation.</p>
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<p>Diagram and fundamental concepts of model predictive control.</p>
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<p>The flowchart demonstrates the implementation of the suggested FSC-MPC.</p>
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<p>Irradiance profiles. (<b>a</b>) profile of constant irradiance, (<b>b</b>) profile of variable irradiance.</p>
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<p>Three-phase load currents.</p>
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<p>Load current and voltage.</p>
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<p>Grid current and voltage.</p>
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<p>Active and reactive power of load, APF, and grid.</p>
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<p>Neutral current.</p>
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<p>DC-link voltage.</p>
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<p>Grid voltage and current.</p>
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<p>Three-phase grid currents.</p>
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<p>Neutral current.</p>
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<p>Active and reactive power of load, APF, and grid.</p>
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<p>DC-link voltage.</p>
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<p>Three-phase load currents.</p>
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<p>Three-phase grid currents.</p>
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<p>Load voltage and current.</p>
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<p>Grid voltage and current.</p>
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<p>Active and reactive power of load, APF, and grid.</p>
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<p>DC link voltage.</p>
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<p>Three-phase grid currents.</p>
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<p>Grid voltage and current.</p>
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<p>Active and reactive power of load, APF, and grid.</p>
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<p>DC link voltage.</p>
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<p>Three-phase load currents.</p>
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<p>Three-phase grid currents.</p>
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<p>Active and reactive power of load, APF, and grid.</p>
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<p>Grid voltage and current.</p>
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<p>Neutral current.</p>
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<p>DC link voltage.</p>
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<p>Three-phase grid currents.</p>
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<p>Grid voltage and current.</p>
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<p>Active and reactive power of load, APF, and grid.</p>
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<p>DC link voltage.</p>
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<p>Neutral current.</p>
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<p>Power sharing impacts on quality of grid current.</p>
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15 pages, 11771 KiB  
Essay
Harmonic Self-Compensation Control for Bidirectional Grid Tied Inverter Based on Crown Porcupine Optimization Algorithm
by Ao Tian, Fenghui Zhang and Peng Xiao
Electronics 2024, 13(13), 2607; https://doi.org/10.3390/electronics13132607 - 3 Jul 2024
Viewed by 662
Abstract
A self-compensating control strategy for harmonic parameters based on the crown porcupine optimization algorithm is proposed for the single-phase rectifier and two-phase inverter operation mode of the bidirectional converter. In order to improve the response speed of the inverter voltage, the instantaneous expressions [...] Read more.
A self-compensating control strategy for harmonic parameters based on the crown porcupine optimization algorithm is proposed for the single-phase rectifier and two-phase inverter operation mode of the bidirectional converter. In order to improve the response speed of the inverter voltage, the instantaneous expressions of the phase angle coefficient and amplitude coefficient of the dc-side voltage doubling fluctuation are derived, and the third harmonic is calculated based on the crown porcupine optimization algorithm according to the Proportional Integral (PI) + Quasi-Proportional Resonance (QPR) double closed-loop control method and injected into the input voltage of the inverter side to offset the influence of the bus-doubling fluctuation on the output voltage of the two-phase inverters of B and C so that the total harmonic content of the two-phase output voltages of the two-phase inverters of B and C can be reduced. The total harmonic content of the B and C inverter output voltages is reduced. The effective control of the control method for single-phase rectifier two-phase inverter mode is verified through simulation. Finally, the effectiveness of the control strategy is verified by experimenting with a 15 kW LCL-type bi-directional converter prototype. Full article
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<p>Single-phase rectifier two-phase inverter structure diagram.</p>
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<p>Block diagram of voltage–transient value control.</p>
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<p>Simplified block diagram of voltage–transient value control.</p>
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<p>Double closed loop control block diagram.</p>
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<p>Overall system control block diagram.</p>
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<p>Flowchart of harmonic self-compensation control based on crown porcupine optimization algorithm.</p>
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<p>Single-phase rectifier two-phase inverter steady-state waveform: (<b>a</b>) third harmonic compensation; (<b>b</b>) without third harmonic compensation.</p>
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<p>Single-phase rectifier two-phase inverter THD without third harmonic compensation: (<b>a</b>) THD of A-phase current; (<b>b</b>) THD of B-phase voltage; (<b>c</b>) THD of C-phase voltage.</p>
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<p>Single-phase rectifier two-phase inverter THD with third harmonic compensation: (<b>a</b>) THD of A-phase current; (<b>b</b>) THD of B-phase voltage; (<b>c</b>) THD of C-phase voltage.</p>
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<p>Bidirectional converter experimental platform.</p>
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<p>Analysis of single-phase rectifier two-phase inverter steady-state waveforms.</p>
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<p>Single-phase rectifier two-phase inverter THD analysis: (<b>a</b>) THD of A-phase current; (<b>b</b>) THD of B-phase voltage; (<b>c</b>) THD of C-phase voltage.</p>
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13 pages, 4221 KiB  
Article
Design, Analysis, and Comparison of Electric Vehicle Drive Motor Rotors Using Injection-Molded Carbon-Fiber-Reinforced Plastics
by Huai Cong Liu, Jang Soo Park and Il Hwan An
World Electr. Veh. J. 2024, 15(7), 283; https://doi.org/10.3390/wevj15070283 - 25 Jun 2024
Viewed by 3259
Abstract
Due to their excellent mechanical strength, corrosion resistance, and ease of processing, carbon fiber and carbon-fiber-reinforced plastics are finding wide application in diverse fields, including aerospace, industry, and automobiles. This research explores the feasibility of integrating carbon fiber solutions into the rotors of [...] Read more.
Due to their excellent mechanical strength, corrosion resistance, and ease of processing, carbon fiber and carbon-fiber-reinforced plastics are finding wide application in diverse fields, including aerospace, industry, and automobiles. This research explores the feasibility of integrating carbon fiber solutions into the rotors of 85-kilowatt electric vehicle interior permanent magnet synchronous motors. Two novel configurations are proposed: a carbon fiber wire-wound rotor and a carbon fiber injection-molded rotor. A finite element analysis compares the performance of these models against a basic designed rotor, considering factors like no-load back electromotive force, no-load voltage harmonics, cogging torque, load torque, torque ripple, efficiency, and manufacturing cost. Additionally, a comprehensive analysis of system efficiency and energy loss based on hypothetical electric vehicle parameters is presented. Finally, mechanical strength simulations assess the feasibility of the proposed carbon fiber composite rotor designs. Full article
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<p>Carbon fiber molding manufacturing process and finished product, (<b>a</b>) Filament-winding Molding (<b>b</b>) Injection Molding.</p>
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<p>Cross-sections of the IPMSM rotor (1/8 model) and stator (full model). (<b>a</b>) Basic model. (<b>b</b>) Model 2: CFRP-wrapped rotor (<b>c</b>) Model 3: rotor with injection-molded CFRP. (<b>d</b>) Forty-eight parallel slots, hair-pin stator.</p>
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<p>(<b>a</b>) Line B-EMF of the three models. (<b>b</b>) FFT analysis of the three models.</p>
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<p>Cogging torque for the three models.</p>
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<p>(<b>a</b>) FEM torque values at different current angles (phase current Ia: 250 Arms). (<b>b</b>) FEM torque waveform at rated operating point (current angle basic model, β: 38° model 2, β: 28° and model 3, β: 34°).</p>
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<p>Cross-section and flux density distributions of three IPMSM models in MPTA conditions. (<b>a</b>) Basic model, load condition (Ia: 250 Arms, β: 38°). (<b>b</b>) Model 2, load condition (Ia: 250 Arms, β: 28°). (<b>c</b>) Model 3, load condition (Ia: 250 Arms, β: 34°).</p>
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<p>(<b>a</b>) Comparison of torques according to speed. (<b>b</b>) Comparison of efficiencies according to speed.</p>
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<p>Efficiency map of three models. (<b>a</b>) Basic model, active part stack length 150 mm; (<b>b</b>) model 2, active part stack length 136 mm (9.4% reduction); (<b>c</b>) model 3, active part stack length 126 mm (16% reduction).</p>
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<p>(<b>a</b>) Motor speed, (<b>b</b>) absolute load torque, and (<b>c</b>) power over the WLTP class 3 driving cycle.</p>
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<p>(<b>a</b>) EV-propulsion motor specification for peak torque versus speed characteristics (basic model); (<b>b</b>) energy loss over the WLTP class 3 for the three models, basic model (stack length 150 mm), model 2 (stack length 136 mm), and model 3 (stack length 126 mm).</p>
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<p>Stress analysis of a candidate design model at 12,000 r/min. (<b>a</b>) Basic model. (<b>b</b>) model 2. (<b>c</b>) model 3.</p>
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19 pages, 44093 KiB  
Article
Intelligent Integration of Vehicle-to-Grid (V2G) and Vehicle-for-Grid (V4G) Systems: Leveraging Artificial Neural Networks (ANNs) for Smart Grid
by Youness Hakam, Ahmed Gaga, Mohamed Tabaa and Benachir Elhadadi
Energies 2024, 17(13), 3095; https://doi.org/10.3390/en17133095 - 23 Jun 2024
Viewed by 1566
Abstract
This paper presents a groundbreaking control strategy for a bidirectional battery charger that allows power to be injected into the smart grid while simultaneously compensating for the grid’s reactive power using an electric vehicle battery. An artificial neural network (ANN) controller is utilized [...] Read more.
This paper presents a groundbreaking control strategy for a bidirectional battery charger that allows power to be injected into the smart grid while simultaneously compensating for the grid’s reactive power using an electric vehicle battery. An artificial neural network (ANN) controller is utilized for precise design to ensure optimal performance with minimal error. The ANN technique is applied to generate sinusoidal pulse width modulation (SPWM) for a bidirectional AC–DC inverter, with the entire algorithm simulated in MATLAB Simulink.The core innovation of this study is the creation of the ANN algorithm, which supports grid compensation using electric vehicle batteries, an approach termed “vehicle-for-grid”. Additionally, the paper details the PCB circuit design of the system controlled by the DSP F28379D board, which was tested on a three-phase motor. The total harmonic distortion (THD) of the proposed ANN algorithm is approximately 1.85%, compared to the MPC algorithm’s THD of about 2.85%. This indicates that the proposed algorithm is more effective in terms of the quality of the power injected into the grid. Furthermore, it demonstrates effective grid compensation, with the reactive power effectively neutralized to 0KVAR in the vehicle-for-grid mode. Full article
(This article belongs to the Section F3: Power Electronics)
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<p>Multiple modes of V2X system.</p>
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<p>Schematic of EV charger.</p>
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<p>Internal architecture of ANN.</p>
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<p>Architecture of ANN controller.</p>
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<p>Topology design for V2X system.</p>
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<p>Architecture of DC–AC controller.</p>
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<p>Models of ANN controllers. (<b>a</b>) voltage link; (<b>b</b>) direct current; (<b>c</b>) reactive power.</p>
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<p>Controller ANN in DC–DC converter.</p>
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<p>Diagram of the proposed system architecture.</p>
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<p>Real-world apsects of the proposed system.</p>
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<p>Performance of training model algorithm.</p>
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<p>Training model algorithm.</p>
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<p>The active power for both V2G and V4G modes, comparing the PID and ANN methods.</p>
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<p>The reactive power for both V2G and V4G modes, comparing the PID and ANN methods.</p>
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<p>The voltage and current of the grid under the influence of the PID controller in the three different modes.</p>
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<p>The voltage and current profiles of the grid across the three modes under the control of the ANN controller.</p>
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<p>The voltage link (<math display="inline"><semantics> <msub> <mi>V</mi> <mrow> <mi>d</mi> <mi>c</mi> </mrow> </msub> </semantics></math>) across the three modes with both ANN and PID controllers.</p>
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<p>The battery current in all three modes under the application of both the PID and ANN methods.</p>
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<p>The active power for both V2G and V4G modes.</p>
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<p>The reactive power for both V2G and V4G modes.</p>
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<p>The voltage of the motor in modes V2G and V4G.</p>
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<p>The current of the grid in both modes, V2G and V4G.</p>
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<p>The voltage link (<math display="inline"><semantics> <msub> <mi>V</mi> <mrow> <mi>d</mi> <mi>c</mi> </mrow> </msub> </semantics></math>) in the real world.</p>
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<p>The battery current in the real world.</p>
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<p>The total harmonic distortion.</p>
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16 pages, 318 KiB  
Article
DPShield: Optimizing Differential Privacy for High-Utility Data Analysis in Sensitive Domains
by Pratik Thantharate, Shyam Bhojwani and Anurag Thantharate
Electronics 2024, 13(12), 2333; https://doi.org/10.3390/electronics13122333 - 14 Jun 2024
Cited by 1 | Viewed by 962
Abstract
The proliferation of cloud computing has amplified the need for robust privacy-preserving technologies, particularly when dealing with sensitive financial and human resources (HR) data. However, traditional differential privacy methods often struggle to balance rigorous privacy protections with maintaining data utility. This study introduces [...] Read more.
The proliferation of cloud computing has amplified the need for robust privacy-preserving technologies, particularly when dealing with sensitive financial and human resources (HR) data. However, traditional differential privacy methods often struggle to balance rigorous privacy protections with maintaining data utility. This study introduces DPShield, an optimized adaptive framework that enhances the trade-off between privacy guarantees and data utility in cloud environments. DPShield leverages advanced differential privacy techniques, including dynamic noise-injection mechanisms tailored to data sensitivity, cumulative privacy loss tracking, and domain-specific optimizations. Through comprehensive evaluations on synthetic financial and real-world HR datasets, DPShield demonstrated a remarkable 21.7% improvement in aggregate query accuracy over existing differential privacy approaches. Moreover, it maintained machine learning model accuracy within 5% of non-private benchmarks, ensuring high utility for predictive analytics. These achievements signify a major advancement in differential privacy, offering a scalable solution that harmonizes robust privacy assurances with practical data analysis needs. DPShield’s domain adaptability and seamless integration with cloud architectures underscore its potential as a versatile privacy-enhancing tool. This work bridges the gap between theoretical privacy guarantees and practical implementation demands, paving the way for more secure, ethical, and insightful data usage in cloud computing environments. Full article
(This article belongs to the Special Issue Artificial Intelligence and Applications—Responsible AI)
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<p>Evaluation of differentially private frameworks.</p>
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<p>Aggregate query accuracy.</p>
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<p>ML model quality.</p>
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<p>Impact of privacy budget on privacy guarantee level.</p>
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<p>Impact of privacy budget on utility level.</p>
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27 pages, 13538 KiB  
Article
A New LCL Filter Design Method for Single-Phase Photovoltaic Systems Connected to the Grid via Micro-Inverters
by Heriberto Adamas-Pérez, Mario Ponce-Silva, Jesús Darío Mina-Antonio, Abraham Claudio-Sánchez, Omar Rodríguez-Benítez and Oscar Miguel Rodríguez-Benítez
Technologies 2024, 12(6), 89; https://doi.org/10.3390/technologies12060089 - 12 Jun 2024
Cited by 1 | Viewed by 2037
Abstract
This paper aims to propose a new sizing approach to reduce the footprint and optimize the performance of an LCL filter implemented in photovoltaic systems using grid-connected single-phase microinverters. In particular, the analysis is carried out on a single-phase full-bridge inverter, assuming the [...] Read more.
This paper aims to propose a new sizing approach to reduce the footprint and optimize the performance of an LCL filter implemented in photovoltaic systems using grid-connected single-phase microinverters. In particular, the analysis is carried out on a single-phase full-bridge inverter, assuming the following two conditions: (1) a unit power factor at the connection point between the AC grid and the LCL filter; (2) a control circuit based on unipolar sinusoidal pulse width modulation (SPWM). In particular, the ripple and harmonics of the LCL filter input current and the current injected into the grid are analyzed. The results of the Simulink simulation and the experimental tests carried out confirm that it is possible to considerably reduce filter volume by optimizing each passive component compared with what is already available in the literature while guaranteeing excellent filtering performance. Specifically, the inductance values were reduced by almost 40% and the capacitor value by almost 100%. The main applications of this new design methodology are for use in single-phase microinverters connected to the grid and for research purposes in power electronics and optimization. Full article
(This article belongs to the Topic Advances in Solar Technologies)
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Figure 1

Figure 1
<p>Photovoltaic system with LCL filter.</p>
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<p>Grid-connected full bridge inverter with an LCL filter.</p>
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<p>General diagram of mathematical analysis using harmonics.</p>
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<p>Step-by-step diagram for LCL filter calculation and proposed parameters.</p>
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<p>LCL filter connected to the grid for the fundamental harmonic.</p>
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<p>LCL filter divided by superposition theorem.</p>
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<p>LCL filter for any harmonic <span class="html-italic">n</span>.</p>
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<p>Attenuation factor (<span class="html-italic">K<sub>a</sub></span>) versus <span class="html-italic">r</span>.</p>
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<p>The voltage on the DC bus as a function of alpha.</p>
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<p><span class="html-italic">V<sub>in</sub></span> as a function of alpha.</p>
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<p>Proposed value for <span class="html-italic">L</span><sub>1</sub>.</p>
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<p>Proposed value for <span class="html-italic">C<sub>f</sub></span>.</p>
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<p>LCL filter control diagram connected to the grid.</p>
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<p>Full bridge inverter with LCL filter connected to the grid.</p>
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<p>Schematic of control implemented in Simulink.</p>
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<p>Schematic of control implemented in Simulink.</p>
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<p>Results of simulation.</p>
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<p>Results of simulation.</p>
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<p>Current in <span class="html-italic">L</span><sub>1</sub>.</p>
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<p>FFT of the inverter side current signal.</p>
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<p>FFT of harmonics near harmonic n for the inverter side current.</p>
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<p>Grid side current.</p>
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<p>FFT of the grid side current signal.</p>
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<p>FFT of <span class="html-italic">I<sub>g</sub></span> (harmonics near harmonic <span class="html-italic">n</span>).</p>
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<p>Prototype implemented.</p>
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<p>Measured inverter-side current and grid voltage.</p>
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<p>Experimental FFT of the <span class="html-italic">L</span><sub>1</sub> current.</p>
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<p>Measured grid current with a spectrum analyzer.</p>
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<p>Experimental FFT of grid current.</p>
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