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Keywords = brushed DC motor

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15 pages, 4980 KiB  
Article
Sensorless Design and Analysis of a Brushed DC Motor Speed Regulation System for Branches Sawing
by Shangshang Cheng, Huijun Zeng, Zhen Li, Qingting Jin, Shilei Lv, Jingyuan Zeng and Zhou Yang
Agriculture 2024, 14(11), 2078; https://doi.org/10.3390/agriculture14112078 - 19 Nov 2024
Viewed by 747
Abstract
Saw rotational speed critically influences cutting force and surface quality yet is often destabilized by variable cutting resistance. The sensorless detection method for calculating rotational speed based on current ripple can prevent the contact of wood chips and dust with Hall sensors. This [...] Read more.
Saw rotational speed critically influences cutting force and surface quality yet is often destabilized by variable cutting resistance. The sensorless detection method for calculating rotational speed based on current ripple can prevent the contact of wood chips and dust with Hall sensors. This paper introduces a speed control system for brushed DC motors that capitalizes on the linear relationship between current ripple frequency and rotational speed. The system achieves speed regulation through indirect speed measurement and PID control. It utilizes an H-bridge circuit controlled by the EG2014S driver chip to regulate the motor direction and braking. Current ripple detection is accomplished through a 0.02 Ω sampling resistor and AMC1200SDUBR signal amplifier, followed by a wavelet transform and Savitzky–Golay filtering for refined signal extraction. Experimental results indicate that the system maintains stable speeds across the 2000–6000 RPM range, with a maximum error of 2.32% at 6000 RPM. The improved ripple detection algorithm effectively preserves critical signals while reducing noise. This enables the motor to quickly regain speed when resistance is encountered, ensuring a smooth cutting surface. Compared to traditional Hall sensor systems, this sensorless design enhances adaptability in agricultural applications. Full article
(This article belongs to the Special Issue New Energy-Powered Agricultural Machinery and Equipment)
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Figure 1
<p>Structural model of brushed DC motor.</p>
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<p>Original ripple signal of brushed DC motor.</p>
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<p>Noise reduction process for motor current ripple.</p>
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<p>Brushed DC motor speed stabilisation system design.</p>
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<p>H-bridge drive circuit for brushed DC motor.</p>
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<p>Ripple current detection circuit.</p>
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<p>Improved wavelet denoising of ripple signals.</p>
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<p>Sawing experimental platform.</p>
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<p>Variation of voltage, current, and speed during resistance and stabilization.</p>
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<p>Performance comparison of steady-speed system.</p>
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18 pages, 14599 KiB  
Article
Designing a Brushed DC Motor Driver with a Novel Adaptive Learning Algorithm for the Automotive Industry
by Hudaverdi Emin Elp, Hüseyin Altug and Remzi İnan
Electronics 2024, 13(22), 4344; https://doi.org/10.3390/electronics13224344 - 6 Nov 2024
Cited by 1 | Viewed by 836
Abstract
In this study, a stepper driver, which is suitable for use in the automotive industry, designed for general use, capable of adaptive learning in the systems in which it is used, and with CAN and universal asynchronous receiver–transmitter (UART) communication options, was designed. [...] Read more.
In this study, a stepper driver, which is suitable for use in the automotive industry, designed for general use, capable of adaptive learning in the systems in which it is used, and with CAN and universal asynchronous receiver–transmitter (UART) communication options, was designed. This design was made with a PIC18F25K22 microcontroller unit (MCU). Rotor speed, armature current, and terminal voltage can be measured on the proposed brushed DC motor drive system. It gives the desired response by evaluating obstacles and other situations in which high currents are drawn from the source. The speed measurement of the vehicle and the open and closed status of an automatic door can be monitored. The main contribution of the designed PCB is an adaptive learning algorithm (ALA) that uses the pulses of the encoder, estimates the position of the step, and manages the operation process to prevent mechanical damage at the final point of the motor. Furthermore, unexpected hitting and pinching which are defined as obstacles to the driver can be controlled by monitoring the current value drawn from the driver. The benefit of this method is that the life of the mechanical step is increased due to the management of the forward and backward step operation, preventing potential accidents. Full article
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Figure 1
<p>Brushed DC Motor.</p>
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<p>General scheme of the System.</p>
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<p>Basic electrical circuit of boost converter topology [<a href="#B30-electronics-13-04344" class="html-bibr">30</a>].</p>
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<p>Movement and position learning algorithm.</p>
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<p>Working principle of the proposed drive system.</p>
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<p>Brushed DC Motor with reducer which is used for design of the system.</p>
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<p>Mechanical setup of step.</p>
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<p>Designed motor driver PCB.</p>
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<p>General view of the system while the step is operating in reverse direction.</p>
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<p>General view of the system while the step is operating in forward direction.</p>
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<p>Input (yellow) and boosted (blue) voltage for 0% Boost.</p>
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<p>Input (yellow) and boosted (blue) voltage for 10% Boost.</p>
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<p>Input (yellow) and boosted (blue) voltage for 20% Boost.</p>
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<p>Motor response for 0% Boost.</p>
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<p>Motor response for 10% Boost.</p>
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<p>Motor response for 20% Boost.</p>
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23 pages, 15197 KiB  
Article
Current and Stray Flux Combined Analysis for Sparking Detection in DC Motors/Generators Using Shannon Entropy
by Jorge E. Salas-Robles, Vicente Biot-Monterde and Jose A. Antonino-Daviu
Entropy 2024, 26(9), 744; https://doi.org/10.3390/e26090744 - 30 Aug 2024
Viewed by 935
Abstract
Brushed DC motors and generators (DCMs) are extensively used in various industrial applications, including the automotive industry, where they are critical for electric vehicles (EVs) due to their high torque, power, and efficiency. Despite their advantages, DCMs are prone to premature failure due [...] Read more.
Brushed DC motors and generators (DCMs) are extensively used in various industrial applications, including the automotive industry, where they are critical for electric vehicles (EVs) due to their high torque, power, and efficiency. Despite their advantages, DCMs are prone to premature failure due to sparking between brushes and commutators, which can lead to significant economic losses. This study proposes two approaches for determining the temporal and frequency evolution of Shannon entropy in armature current and stray flux signals. One approach indirectly achieves this through prior analysis using the Short-Time Fourier Transform (STFT), while the other applies the Stockwell Transform (S-Transform) directly. Experimental results show that increased sparking activity generates significant low-frequency harmonics, which are more pronounced compared to mid and high-frequency ranges, leading to a substantial rise in system entropy. This finding enables the introduction of fault-severity indicators or Key Performance Indicators (KPIs) that relate the current condition of commutation quality to a baseline established under healthy conditions. The proposed technique can be used as a predictive maintenance tool to detect and assess sparking phenomena in DCMs, providing early warnings of component failure and performance degradation, thereby enhancing the reliability and availability of these machines. Full article
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Figure 1
<p>Axial and radial stray flux components [<a href="#B24-entropy-26-00744" class="html-bibr">24</a>,<a href="#B25-entropy-26-00744" class="html-bibr">25</a>,<a href="#B26-entropy-26-00744" class="html-bibr">26</a>].</p>
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<p>Time-frequency spectrogram resulting from the application of the STFT to the analyzed signal.</p>
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<p>Flow chart of the methodology proposal for armature current and stray flux signals.</p>
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<p>Flow chart of the methodology proposal for armature current and stray flux signals.</p>
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<p>Experimental testbench: induction motor, DC generator. Measurement devices for the registration of the signals: Yokogawa DL850 waveform recorder, Fluke current clamp model CA i3000s Flex [<a href="#B5-entropy-26-00744" class="html-bibr">5</a>]. Coil sensor for measuring stray flux [<a href="#B24-entropy-26-00744" class="html-bibr">24</a>,<a href="#B26-entropy-26-00744" class="html-bibr">26</a>].</p>
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<p>(LH) Typical configuration of the spiral spring [<a href="#B31-entropy-26-00744" class="html-bibr">31</a>], spiral spring pressure T0 (gap between brush and commutator), T1 (lower spring tension), T2, T3 (intermediate spring tension), T4 (maximum spring tension). (RH) Brush configuration, a–d represent brush positions.</p>
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<p>(<b>a</b>) Healthy generator (baseline), (<b>b</b>) moderate spark level, (<b>c</b>) high level of sparking activity. The yellow arrows indicate the zone of spark activity.</p>
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<p>FFT spectrum (baseline vs. current state) of the armature current at a starting transient and steady state for (<b>a</b>) healthy motor, (<b>b</b>,<b>c</b>) incipient fault condition, (<b>d</b>) moderate sparking level, and (<b>e</b>,<b>f</b>) severe sparking levels.</p>
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<p>FFT spectrum (baseline vs. current state) of the stray flux at a starting transient and steady state for (<b>a</b>) healthy motor, (<b>b</b>,<b>c</b>) incipient fault condition, (<b>d</b>) moderate sparking level, and (<b>e</b>,<b>f</b>) severe sparking levels.</p>
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<p>STFT 3D armature current at a transient state for (<b>a</b>) healthy motor, (<b>b</b>) moderate sparking fault condition, and (<b>c</b>) severe sparking fault condition.</p>
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<p>STFT 3D stray flux at a transient state for (<b>a</b>) healthy motor, (<b>b</b>) moderate sparking fault condition, and (<b>c</b>) severe sparking fault condition.</p>
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<p>Entropy-time (2D), evolution during start-up transient for armature current signals: (<b>a</b>) to 7 [A], (<b>b</b>) to 5.65 [A], and (<b>c</b>) to 3.75 [A] represent baseline and incipient failures. (<b>d</b>) to 7 [A], (<b>e</b>) to 5.65 [A], and (<b>f</b>) to 3.75 [A] are comparative incipient failures with severe states.</p>
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<p>Entropy-time (2D), evolution during start-up transient for armature current signals: (<b>a</b>) to 7 [A], (<b>b</b>) to 5.65 [A], and (<b>c</b>) to 3.75 [A] represent baseline and incipient failures. (<b>d</b>) to 7 [A], (<b>e</b>) to 5.65 [A], and (<b>f</b>) to 3.75 [A] are comparative incipient failures with severe states.</p>
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<p>Entropy-time (2D), evolution during start-up transient for stray flux signals: (<b>a</b>) to 7 [A], (<b>b</b>) to 5.65 [A], and (<b>c</b>) to 3.75 [A] represent baseline and incipient failures. (<b>d</b>) to 7 [A], (<b>e</b>) to 5.65 [A], and (<b>f</b>) to 3.75 [A] are comparative incipient failures with severe states.</p>
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<p>Entropy-frequency (2D), evolution during start-up transient for armature current signals. (<b>a</b>–<b>c</b>) Baseline and incipient failures, (<b>d</b>–<b>f</b>) comparative incipient failures with severe states.</p>
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<p>Entropy-frequency (2D), evolution during start-up transient for stray flux signals. (<b>a</b>–<b>c</b>) Baseline and incipient failures, (<b>d</b>–<b>f</b>) comparative incipient failures with severe states.</p>
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<p>Entropy-frequency (2D), evolution during start-up transient for armature current signals: (<b>a</b>) to 7 [A], (<b>b</b>) to 5.65 [A], and (<b>c</b>) to 3.75 [A] represent baseline and incipient failures. (<b>d</b>) to 7 [A], (<b>e</b>) to 5.65 [A], and (<b>f</b>) to 3.75 [A] are comparative incipient failures with severe states.</p>
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<p>Entropy-frequency (2D), evolution during start-up transient for stray flux signals: (<b>a</b>) to 7 [A], (<b>b</b>) to 5.65 [A], and (<b>c</b>) to 3.75 [A] represent baseline and incipient failures. (<b>d</b>) to 7 [A], (<b>e</b>) to 5.65 [A], and (<b>f</b>) to 3.75 [A] are comparative incipient failures with severe states.</p>
Full article ">Figure 16 Cont.
<p>Entropy-frequency (2D), evolution during start-up transient for stray flux signals: (<b>a</b>) to 7 [A], (<b>b</b>) to 5.65 [A], and (<b>c</b>) to 3.75 [A] represent baseline and incipient failures. (<b>d</b>) to 7 [A], (<b>e</b>) to 5.65 [A], and (<b>f</b>) to 3.75 [A] are comparative incipient failures with severe states.</p>
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<p>S-T, time-frequency maps obtained by analyzing the armature current signals of the DC generator for different start-up transients to 7 [A]. States 1, 2: healthy generator; states 3, 4, 5, and 6: incipient failure; states 7, 8, and 9: moderate and severe sparking activity.</p>
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<p>S-T time-frequency maps obtained by analyzing the stray flux signals of the DC generator for different start-up transients to 7 [A]. States 1, 2: healthy generator; states 3, 4, 5, and 6: incipient failure; states 7, 8, and 9: moderate and severe sparking activity.</p>
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22 pages, 5043 KiB  
Article
Design and Testing of an Intramedullary Nail Implant Enhanced with Active Feedback and Wireless Connectivity for Precise Limb Lengthening
by Chiang Liang Kok, Tat Chin Tan, Yit Yan Koh, Teck Kheng Lee and Jian Ping Chai
Electronics 2024, 13(8), 1519; https://doi.org/10.3390/electronics13081519 - 17 Apr 2024
Cited by 3 | Viewed by 1483
Abstract
This comprehensive study presents a pioneering approach to limb lengthening, leveraging the advancements in wireless technology to enhance orthopedic healthcare. Historically, limb lengthening has been a response to discrepancies caused by fractures, diseases, or congenital defects, utilizing the body’s innate ability to regenerate [...] Read more.
This comprehensive study presents a pioneering approach to limb lengthening, leveraging the advancements in wireless technology to enhance orthopedic healthcare. Historically, limb lengthening has been a response to discrepancies caused by fractures, diseases, or congenital defects, utilizing the body’s innate ability to regenerate bone and surrounding tissues. Traditionally, this involved external or internal fixation devices, such as the Ilizarov and Taylor Spatial frames or the Precice nail and Fitbone. The focal point of this research is the development and testing of a wireless intramedullary nail implant prototype, controlled remotely via a mobile application. This implant comprises a microcontroller, Bluetooth Low Energy module, a brushed DC motor controlled through an H-bridge, and a force sensor, all powered by medical-grade batteries. The integration of wireless technology facilitates patient autonomy in managing limb lengthening, reducing the need for frequent clinical visits. The methodology involves a detailed block diagram for our proposed work, outlining the process from treatment planning to the initiation of limb lengthening via the mobile application. Osteogenesis, the formation of new bone tissue, plays a crucial role in this procedure, which includes pre-surgery assessment, osteotomy, latency, distraction, consolidation, and removal phases. Key challenges addressed include custom battery design for efficient operation, size constraints, and overcoming signal interference due to the Faraday cage effect. Attenuation testing, simulating human tissue interaction, validates the implant’s connectivity. In conclusion, this research marks a significant stride in orthopedic care, demonstrating the feasibility of a wireless implant for limb lengthening. It highlights the potential benefits of reduced clinical visits, cost efficiency, and patient convenience. Despite limitations such as battery requirements and signal interference, this study opens avenues for future enhancements in patient-centered orthopedic treatments, signaling a transformative shift in managing limb length discrepancies. Full article
(This article belongs to the Section Circuit and Signal Processing)
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<p>Leg length discrepancies treated with a lengthening device.</p>
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<p>Proposed architecture.</p>
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<p>Schematic design for power configuration.</p>
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<p>Schematic design of the power configuration for the Bluetooth Low Energy module (CC2540).</p>
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<p>Schematic design for the microprocessor (ATMEGA328_QFN32).</p>
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<p>Schematic design for the H-bridge (DRV8837C).</p>
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<p>Force sensor and actuator setup.</p>
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<p>Force and power graph.</p>
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<p>Proposed design of mobile application.</p>
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<p>Airtight container submerged in saline solution for attenuation test.</p>
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<p>Meat submerged in saline solution in a glass jar.</p>
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<p>Attenuation testing results: successful connection up to 5 m and the impact of aluminum foil wrapping on signal degradation.</p>
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<p>Graph results for RSSI in <a href="#electronics-13-01519-t002" class="html-table">Table 2</a>.</p>
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24 pages, 6162 KiB  
Article
Power Signal Analysis for Early Fault Detection in Brushless DC Motor Drivers Based on the Hilbert–Huang Transform
by David Marcos-Andrade, Francisco Beltran-Carbajal, Eduardo Esquivel-Cruz, Ivan Rivas-Cambero, Hossam A. Gabbar and Alexis Castelan-Perez
World Electr. Veh. J. 2024, 15(4), 159; https://doi.org/10.3390/wevj15040159 - 10 Apr 2024
Cited by 1 | Viewed by 1768
Abstract
Brushless DC machines have demonstrated significant advantages in electrical engineering by eliminating commutators and brushes. Every year, these machines increase their presence in transportation applications. In this sense, early fault identification in these systems, specifically in the electronic speed controllers, is relevant for [...] Read more.
Brushless DC machines have demonstrated significant advantages in electrical engineering by eliminating commutators and brushes. Every year, these machines increase their presence in transportation applications. In this sense, early fault identification in these systems, specifically in the electronic speed controllers, is relevant for correct device operation. In this context, the techniques reported in the literature for fault identification based on the Hilbert–Huang transform have shown efficiency in electrical systems. This manuscript proposes a novel technique for early fault identification in electronic speed controllers based on the Hilbert–Huang transform algorithm. Initially, currents from the device are captured with non-invasive sensors in a time window during motor operation. Subsequently, the signals are processed to obtain pertinent information about amplitudes and frequencies using the Hilbert–Huang transform, focusing on fundamental components. Then, estimated parameters are evaluated by computing the error between signals. The existing electrical norms of a balanced system are used to identify a healthy or damaged driver. Through amplitude and frequency error analysis between three-phase signals, early faults caused by system imbalances such as current increasing, torque reduction, and speed reduction are detected. The proposed technique is implemented through data acquisition devices at different voltage conditions and then physical signals are evaluated offline through several simulations in the Matlab environment. The method’s robustness against signal variations is highlighted, as each intrinsic mode function serves as a component representation of the signal and instantaneous frequency computation provides resilience against these variations. Two study cases are conducted in different conditions to validate this technique. The experimental results demonstrate the effectiveness of the proposed method in identifying early faults in brushless DC motor drivers. This study provides data from each power line within the electronic speed controller to detect early faults and extend different approaches, contributing to addressing early failures in speed controllers while expanding beyond the conventional focus on motor failure analysis. Full article
(This article belongs to the Special Issue Dynamic Control of Traction Motors for EVs)
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Figure 1
<p>Comparative of fault detection methods based on the Hilbert–Huang transform, fast Fourier transform, and wavelet analysis.</p>
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<p>Simulation of a three–phase current system with four unknown harmonic components for the illustrative case study.</p>
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<p>Schematic representation of the proposed method for early fault identification in electronic speed controllers based on the Hilbert–Huang transform.</p>
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<p>Oscillating components of the estimated current signals extracted by performing adaptive empirical mode decomposition. (<b>a</b>) Component <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo>^</mo> </mover> <mrow> <mi>a</mi> <mi>i</mi> <mi>m</mi> <mi>f</mi> <mn>1</mn> </mrow> </msub> </semantics></math> at 500 Hz frequency. (<b>b</b>) Component <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo>^</mo> </mover> <mrow> <mi>a</mi> <mi>i</mi> <mi>m</mi> <mi>f</mi> <mn>2</mn> </mrow> </msub> </semantics></math> at 200 Hz frequency. (<b>c</b>) Component <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo>^</mo> </mover> <mrow> <mi>a</mi> <mi>i</mi> <mi>m</mi> <mi>f</mi> <mn>3</mn> </mrow> </msub> </semantics></math> at 100 Hz frequency.</p>
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<p>Oscillating components of the estimated current signals extracted by performing adaptive empirical mode decomposition. (<b>a</b>) Component <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo>^</mo> </mover> <mrow> <mi>b</mi> <mi>i</mi> <mi>m</mi> <mi>f</mi> <mn>1</mn> </mrow> </msub> </semantics></math> at 500 Hz frequency. (<b>b</b>) Component <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo>^</mo> </mover> <mrow> <mi>b</mi> <mi>i</mi> <mi>m</mi> <mi>f</mi> <mn>2</mn> </mrow> </msub> </semantics></math> at 200 Hz frequency. (<b>c</b>) Component <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo>^</mo> </mover> <mrow> <mi>b</mi> <mi>i</mi> <mi>m</mi> <mi>f</mi> <mn>3</mn> </mrow> </msub> </semantics></math> at 100 Hz frequency.</p>
Full article ">Figure 5 Cont.
<p>Oscillating components of the estimated current signals extracted by performing adaptive empirical mode decomposition. (<b>a</b>) Component <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo>^</mo> </mover> <mrow> <mi>b</mi> <mi>i</mi> <mi>m</mi> <mi>f</mi> <mn>1</mn> </mrow> </msub> </semantics></math> at 500 Hz frequency. (<b>b</b>) Component <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo>^</mo> </mover> <mrow> <mi>b</mi> <mi>i</mi> <mi>m</mi> <mi>f</mi> <mn>2</mn> </mrow> </msub> </semantics></math> at 200 Hz frequency. (<b>c</b>) Component <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo>^</mo> </mover> <mrow> <mi>b</mi> <mi>i</mi> <mi>m</mi> <mi>f</mi> <mn>3</mn> </mrow> </msub> </semantics></math> at 100 Hz frequency.</p>
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<p>Oscillating components of the estimated current signals extracted by performing adaptive empirical mode decomposition. (<b>a</b>) Component <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo>^</mo> </mover> <mrow> <mi>c</mi> <mi>i</mi> <mi>m</mi> <mi>f</mi> <mn>1</mn> </mrow> </msub> </semantics></math> at 500 Hz frequency. (<b>b</b>) Component <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo>^</mo> </mover> <mrow> <mi>c</mi> <mi>i</mi> <mi>m</mi> <mi>f</mi> <mn>2</mn> </mrow> </msub> </semantics></math> at 200 Hz frequency. (<b>c</b>) Component <math display="inline"><semantics> <msub> <mover accent="true"> <mi>i</mi> <mo>^</mo> </mover> <mrow> <mi>c</mi> <mi>i</mi> <mi>m</mi> <mi>f</mi> <mn>3</mn> </mrow> </msub> </semantics></math> at 100 Hz frequency.</p>
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<p>Primary signals representing the balanced three–phase system. (<b>a</b>) Current of Winding a. (<b>b</b>) Current of Winding b. (<b>c</b>) Current of Winding c.</p>
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<p>Frequency parameters calculated by applying the Hilbert transform to the extracted oscillatory components from the signal <math display="inline"><semantics> <mover accent="true"> <msub> <mi>i</mi> <mrow> <mi>a</mi> <mi>b</mi> <mi>c</mi> </mrow> </msub> <mo>^</mo> </mover> </semantics></math> are compared with the original reference signals. (<b>a</b>) First component frequencies <math display="inline"><semantics> <msub> <mi>i</mi> <mi>a</mi> </msub> </semantics></math>. (<b>b</b>) Second component frequencies <math display="inline"><semantics> <msub> <mi>i</mi> <mi>b</mi> </msub> </semantics></math>. (<b>c</b>) Last component frequencies <math display="inline"><semantics> <msub> <mi>i</mi> <mi>c</mi> </msub> </semantics></math>.</p>
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<p>Amplitude parameters calculated by applying the Hilbert Transform to the extracted oscillatory components from the signal <math display="inline"><semantics> <mover accent="true"> <msub> <mi>i</mi> <mrow> <mi>a</mi> <mi>b</mi> <mi>c</mi> </mrow> </msub> <mo>^</mo> </mover> </semantics></math> are compared with the original reference signals. (<b>a</b>) First component amplitude <math display="inline"><semantics> <msub> <mi>i</mi> <mi>a</mi> </msub> </semantics></math>. (<b>b</b>) Second component amplitude <math display="inline"><semantics> <msub> <mi>i</mi> <mi>b</mi> </msub> </semantics></math>. (<b>c</b>) Last component amplitude <math display="inline"><semantics> <msub> <mi>i</mi> <mi>c</mi> </msub> </semantics></math>.</p>
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<p>Block diagram for current signal extraction in a complete permanent magnet brushless DC motor drive system.</p>
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<p>Experimental 6-pulse electronic speed controller for brushless DC motor evaluation.</p>
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<p>Test bench for current data acquisition in brushless motors used for ESC fault diagnosis.</p>
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<p>Fundamental currents extracted from the first ESC obtained using the empirical mode decomposition (EMD). (<b>a</b>) Phase–A current signal processed with EMD. (<math display="inline"><semantics> <msub> <mi>i</mi> <mi>a</mi> </msub> </semantics></math>) (<b>b</b>) Phase–B current signal processed with EMD. (<math display="inline"><semantics> <msub> <mi>i</mi> <mi>b</mi> </msub> </semantics></math>) (<b>c</b>) Phase–C current signal processed with EMD. (<math display="inline"><semantics> <msub> <mi>i</mi> <mi>c</mi> </msub> </semantics></math>).</p>
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<p>Amplitude parameters calculated by applying the Hilbert Transform to the extracted oscillatory components from the healthy ESC signals. (<b>a</b>) Estimated amplitude of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>a</mi> </msub> </semantics></math>. (<b>b</b>) Estimated amplitude of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>b</mi> </msub> </semantics></math>. (<b>c</b>) Estimated amplitude of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>c</mi> </msub> </semantics></math>.</p>
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<p>Frequency parameters calculated by applying the Hilbert Transform to the extracted oscillatory components from the healthy ESC signals. (<b>a</b>) Estimated frequency of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>a</mi> </msub> </semantics></math>. (<b>b</b>) Estimated frequency of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>b</mi> </msub> </semantics></math>. (<b>c</b>) Estimated frequency of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>c</mi> </msub> </semantics></math>.</p>
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<p>Estimated principal currents using the empirical mode decomposition method extracted from the damaged ESC line power supply. (<b>a</b>) Signal of Phase–A Current extracted from damaged ESC and processed using the empirical mode decomposition method <math display="inline"><semantics> <msub> <mi>i</mi> <mi>a</mi> </msub> </semantics></math>. (<b>b</b>) Signal of Phase–B Current extracted from damaged ESC and processed using the empirical mode decomposition method <math display="inline"><semantics> <msub> <mi>i</mi> <mi>b</mi> </msub> </semantics></math>. (<b>c</b>) Signal of Phase–C Current extracted from damaged ESC and processed using the empirical mode decomposition method <math display="inline"><semantics> <msub> <mi>i</mi> <mi>c</mi> </msub> </semantics></math>.</p>
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<p>Amplitude parameters calculated by applying the Hilbert Transform to the extracted oscillatory components from the damaged ESC signals. (<b>a</b>) Estimated amplitude of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>a</mi> </msub> </semantics></math>. (<b>b</b>) Estimated amplitude of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>b</mi> </msub> </semantics></math>. (<b>c</b>) Estimated amplitude of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>c</mi> </msub> </semantics></math>.</p>
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<p>Frequency parameters calculated by applying the Hilbert Transform to the extracted oscillatory components from the healthy ESC Signals. (<b>a</b>) Estimated frequency of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>a</mi> </msub> </semantics></math>. (<b>b</b>) Estimated frequency of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>b</mi> </msub> </semantics></math>. (<b>c</b>) Estimated frequency of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>c</mi> </msub> </semantics></math>.</p>
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<p>Frequency parameters calculated by applying the Hilbert Transform to the extracted oscillatory components from the healthy ESC Signals. (<b>a</b>) Estimated frequency of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>a</mi> </msub> </semantics></math>. (<b>b</b>) Estimated frequency of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>b</mi> </msub> </semantics></math>. (<b>c</b>) Estimated frequency of the oscillating component <math display="inline"><semantics> <msub> <mi>i</mi> <mi>c</mi> </msub> </semantics></math>.</p>
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17 pages, 6448 KiB  
Article
Design of Electronic Filter for Noise and Vibration Reduction in Brushed DC Motor
by Jiman Kim and Hyunsu Kim
Machines 2024, 12(3), 148; https://doi.org/10.3390/machines12030148 - 20 Feb 2024
Cited by 2 | Viewed by 1980
Abstract
With the recent conversion of internal combustion engines to electric vehicles, new noise issues have arisen, and among them, the noise generated by internal vehicle auxiliary systems is being considered. This study introduces an electronic filter designed with a motor model featuring vibration [...] Read more.
With the recent conversion of internal combustion engines to electric vehicles, new noise issues have arisen, and among them, the noise generated by internal vehicle auxiliary systems is being considered. This study introduces an electronic filter designed with a motor model featuring vibration components, aiming to minimize the noise and vibrations generated by a Brushed DC (BDC) motor commonly employed in vehicle internal systems. It introduces a method to identify the connectors and internal parameters used in the motor for the matching of the model and experimental motor, and to measure and estimate these parameters. The model is separated and executed to ensure convergence, and it is validated by comparing the analysis results with the measured values. A filter is designed using the model to reduce current oscillations in the motor, confirming a subsequent reduction in noise and vibration. This research suggests the potential to attenuate noise and vibration in already produced motors by attaching only a filter without modifying the internal motor structure. Moreover, it is anticipated that a filter can be designed to predict and mitigate the noise and vibration components of the motor based on changes in load. Full article
(This article belongs to the Section Electrical Machines and Drives)
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Figure 1
<p>Schematic diagram of Brushed DC motor including filter and connector.</p>
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<p>Brushed DC motor modeling including motor and connector.</p>
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<p>Structure and modeling of the motor connectors.</p>
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<p>The result of measuring and performing FFT on the back EMF of the experimental motor. The numbers above the points indicate the RPM, and the dashed line represents the linear interpolation result; (<b>a</b>) 8th order component and (<b>b</b>) DC component.</p>
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<p>Variations in RPM and current vibration components according to changes in the torque constant and armature inductance: (<b>a</b>) Changes in motor RPM according to variations in the torque constant; (<b>b</b>–<b>d</b>) Changes in current variation components according to variations in the armature inductance.</p>
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<p>The back EMF varies over time. It indicates that the model does not converge: (<b>a</b>) Time graph of back EMF from 20.01 to 20.02 s; (<b>b</b>) FFT results of (<b>a</b>); (<b>c</b>) Time graph of back EMF from 100.01 to 100.02 s; (<b>d</b>) FFT results of (<b>c</b>).</p>
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<p>The back EMF varies over time. It indicates that the model does not converge: (<b>a</b>) Time graph of back EMF from 20.01 to 20.02 s; (<b>b</b>) FFT results of (<b>a</b>); (<b>c</b>) Time graph of back EMF from 100.01 to 100.02 s; (<b>d</b>) FFT results of (<b>c</b>).</p>
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<p>Comparison of simulated and experimental results for current vibration components.</p>
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<p>Six case studies for verifying the effect of current vibration reduction.</p>
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<p>Comparison of current oscillation components with varying L values: (<b>a</b>) Current oscillation magnitude; (<b>b</b>) Current oscillation frequency.</p>
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<p>Experimental environment for model validation: (<b>a</b>) Experiment schematic diagram; (<b>b</b>) Experimental environment.</p>
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<p>Comparison of experimental and simulation results for current oscillation when a series L filter is added: (<b>a</b>) Comparison of simulation results with ideal inductor and measured values; (<b>b</b>) Comparison of simulation with consideration of the internal resistance of the inductor and measured values.</p>
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<p>Comparison of current oscillation components with and without a filter. “W/O” denotes “without filter” and “W/” denotes “with filter”.</p>
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<p>Comparison of measurement results with and without filters. “W/O” stands for “without”, and “W/” stands for “with”: (<b>a</b>) Current vibration; (<b>b</b>) Vibration of body of the motor; (<b>c</b>) Motor acoustic noise.</p>
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<p>Diagram explaining the experimental method and theory for measuring motor inertia: (<b>a</b>) Figure of an object rotating on an inclined plane passing between two points on the incline. At <span class="html-italic">t</span> = 0, the rotating body is stationary, and at <span class="html-italic">t</span> = <span class="html-italic">t</span><sub>1</sub>, it denotes the time taken to pass through the inclined plane; (<b>b</b>) Displacement in the case of uniform acceleration; (<b>c</b>) The case of a rotating body rolling without slipping.</p>
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<p>Schematic diagram of motor friction measurement method.</p>
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24 pages, 7021 KiB  
Article
Increasing the Efficiency of Diagnostics in the Brush-Commutator Assembly of a Direct Current Electric Motor
by Olga A. Filina, Nikita V. Martyushev, Boris V. Malozyomov, Vadim Sergeevich Tynchenko, Viktor Alekseevich Kukartsev, Kirill Aleksandrovich Bashmur, Pavel P. Pavlov and Tatyana Aleksandrovna Panfilova
Energies 2024, 17(1), 17; https://doi.org/10.3390/en17010017 - 19 Dec 2023
Cited by 52 | Viewed by 1744
Abstract
Increasing the productivity and reliability of mining infrastructure facilities is an important task in achieving future goals. Mining dump trucks are an important part of coal mine infrastructure. In this article, to determine the reliability indicators in a brush–commutator unit and the residual [...] Read more.
Increasing the productivity and reliability of mining infrastructure facilities is an important task in achieving future goals. Mining dump trucks are an important part of coal mine infrastructure. In this article, to determine the reliability indicators in a brush–commutator unit and the residual life of electric motor brushes, a mathematical model for processing statistical data has been developed, which allows for the classification of types of failures and, unlike existing models, the determination of the life of the brushes according to the maximum extent of their wear. A method for predicting the residual life of an electric brush in a DC electric motor is presented, which contains a list of controlled reliability indicators, included a mathematical model. The described model improves the accuracy of the prediction and detection of DC motor failures. The derivation of the general formula for calculating the residual life of electric brushes is given. Based on the proposed mathematical model, we studied and calculated the reliability of the brush–commutator unit, the minimum height of the brush during operation, the average rate of its wear, the standard deviation and the mathematical expectation of brush wear. A nomogram of the failure-free operation time of the brush–commutator unit in a DC electric motor was modeled using the height of the brush during operation. Output parameters after the implementation of this monitoring system include the reliability of the electric motor operation. At the same time, diagnostic characteristics are improved twofold, and the residual life of the brush-switching unit is increased by 28–30%. Full article
(This article belongs to the Special Issue Electric Machinery and Transformers II)
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<p>Electrical scheme of the experimental setup: <span class="html-italic">IM</span> is a PN-45 type test generator with sectionalized DP winding; <span class="html-italic">D</span> is a drive motor with tachogenerator; <span class="html-italic">PG</span> generates additional poles’ make-up; <span class="html-italic">AD</span> is a drive motor of <span class="html-italic">PG</span>; <span class="html-italic">OVPG</span> and <span class="html-italic">OVIM</span> are windings for the independent excitation of <span class="html-italic">PG</span> and <span class="html-italic">IM</span>; <span class="html-italic">R<sub>H</sub></span> is a loading rheostat for <span class="html-italic">IM</span>; <span class="html-italic">SA2</span> is a polarity switch for <span class="html-italic">DP</span> make-up current; <span class="html-italic">DI</span> is a spark sensor connected to a device fora spark level estimation; <span class="html-italic">PA1–PA6</span> are ammeters; <span class="html-italic">PV1</span> is a voltmeter; <span class="html-italic">K1–K3</span> are keys; <span class="html-italic">SA1–SA2</span> are switches.</p>
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<p>Probability density distribution of voltage drop probability for brushes: (<b>a</b>)—EG-841; (<b>b</b>)—EG-14; (<b>c</b>)—EG-61A; Green line—composite detachable brushes; Red line—serial brushes.</p>
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<p>VACs of monolithic (<b>a</b>) and split (<b>b</b>) brushes (at <span class="html-italic">n</span> = 500 min<sup>−1</sup>): 1 is an ascending branch, which is obtained by increasing the armature current at a fixed value of the number of turns of additional poles; 2 is a descending branch when the armature current decreases.</p>
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<p>Schematic diagram of the switched circuit (<b>a</b>) and its substitution diagram: (<b>b</b>)—standard brush, (<b>c</b>)—composite split brush.</p>
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<p>Graph for determining the coefficient of goodness of fit <span class="html-italic">k<sub>d</sub></span>.</p>
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<p>Piecewise linear approximation of the volt-ampere characteristic.</p>
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<p>Assembly of a system for monitoring the vibrations in brush–commutators: 1—DC motor; 2—vibrometer; 3—computer.</p>
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<p>Block-functional monitoring scheme.</p>
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<p>Mnemonic diagram of the controlled units of the dump truck TEM.</p>
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<p>Frequency characteristics of the electric motor vibration spectrum: the orange line shows defects in the BCA; blue is a damage to the bearings.</p>
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<p>Diagram of the vibration spectrum of developing defects on the TEM: the blue line shows defects in the BCA; orange line is a damage to the bearings.</p>
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<p>Analogue shape of the electric motor vibration spectrum signal.</p>
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<p>Spectrum of the vibration signal registered on the motor bearing.</p>
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<p>Overall picture of the TEM vibration spectrum with the selected BCA diagnostic range.</p>
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<p>Diagram for determining brush wear depending on the diagnosable vibration frequency TEM.</p>
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<p>Program to identify defects in TEM: 1—BCA, 2—a brush, 3—commutator runout, 4—reference TEM, 5—bearings.</p>
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<p>Frequency-spectral diagram of comprehensive vibration diagnosis.</p>
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19 pages, 6445 KiB  
Article
Stochastic Models and Processing Probabilistic Data for Solving the Problem of Improving the Electric Freight Transport Reliability
by Nikita V. Martyushev, Boris V. Malozyomov, Olga A. Filina, Svetlana N. Sorokova, Egor A. Efremenkov, Denis V. Valuev and Mengxu Qi
Mathematics 2023, 11(23), 4836; https://doi.org/10.3390/math11234836 - 30 Nov 2023
Cited by 13 | Viewed by 1084
Abstract
Improving the productivity and reliability of mining infrastructure is an important task contributing to the mining performance enhancement of any enterprise. Open-pit dump trucks that move rock masses from the mining site to unloading points are an important part of the infrastructure of [...] Read more.
Improving the productivity and reliability of mining infrastructure is an important task contributing to the mining performance enhancement of any enterprise. Open-pit dump trucks that move rock masses from the mining site to unloading points are an important part of the infrastructure of coal mines, and they are the main transport unit used in the technological cycle during open-pit mining. The failure of any of the mining truck systems causes unscheduled downtime and leads to significant economic losses, which are associated with the need to immediately restore the working state and lost profits due to decreased site productivity and a disruption of the production cycle. Therefore, minimizing the number and duration of unscheduled repairs is a necessity. The most time-consuming operations are the replacement of the diesel engine, traction generator, and traction motors, which requires additional disassembly of the dump truck equipment; therefore, special reliability requirements are imposed on these units. In this article, a mathematical model intended for processing the statistical data was developed to determine the reliability indicators of the brush collector assembly and the residual life of brushes of electric motors, which, unlike existing models, allow the determination of the refined life of the brushes based on the limiting height of their wear. A method to predict the residual life of an electric brush of a DC electric motor is presented, containing a list of controlled reliability indicators that are part of the mathematical model. Using the proposed mathematical model, the reliability of the brush-collector assembly, the minimum height of the brush during operation, and the average rate of its wear were studied and calculated. Full article
(This article belongs to the Special Issue Statistical Methods for Reliability and Survival Analysis)
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<p>Exterior view of BELAZ KT30 B-240.</p>
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<p>Distribution of failures by mining truck systems.</p>
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<p>Diagram of traction motor malfunctions: 1—breakdown of insulation and interturn short circuits of the armature; 2—melting of solder from collector cockerels; 3—lubricant ingress into the skeleton; 4—beating the collector; 5—damage caused to anchor bearings; 6—low insulation of the windings; 7—breakdown of insulation and interturn short circuits; 8—other malfunctions.</p>
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<p>Three-dimensional image of the components of the AC-DC BELAZ traction electric drive (1—traction generator; 2—converter cabinet with the control equipment; 3—traction motor; 4—installation of ventilated braking resistors).</p>
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<p>Data on the BELAZ 75306 dump truck operation depending on the trip number.</p>
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<p>Algorithm for determining the technical condition of the brush.</p>
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<p>Dependence of the wear value of the brush <span class="html-italic">h<sub>av</sub></span> on time <span class="html-italic">t</span>, days per month.</p>
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<p>Algorithm intended for analyzing the experiments on identifying defects.</p>
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<p>Interval change of the BCC failure rate: I—brush lapping period, II—operation; III—brush emergency wear.</p>
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<p>(<b>a</b>) polygon: 1—empirical frequencies, 2—theoretical frequencies of BCA failures; (<b>b</b>) plot of the calculated normal law distribution function of BCA failures.</p>
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<p>Nomogram of the brush uptime (brush height during operation).</p>
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<p>Nomogram of the approximated research results.</p>
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<p>Probability of the trouble-free operation of the EG61AK brushes with a height of 40 mm (curve 1) and advanced brush holders equipped with composite brushes (curve 2).</p>
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12 pages, 1999 KiB  
Communication
Combination of a DC Motor Controller and Telemetry System to Optimize Energy Consumption
by Paweł Żur
Sensors 2023, 23(15), 6923; https://doi.org/10.3390/s23156923 - 3 Aug 2023
Cited by 1 | Viewed by 1324
Abstract
The paper introduces the development stages of a MOSFET-based controller for a DC brush motor. The main objective was to design a controller that could be integrated with the existing telemetry system, offering full configurability through an Android application. This controller aims to [...] Read more.
The paper introduces the development stages of a MOSFET-based controller for a DC brush motor. The main objective was to design a controller that could be integrated with the existing telemetry system, offering full configurability through an Android application. This controller aims to provide real-time analysis of data collected from the measurement system, including motor revolutions and current draw. Based on the analyzed data and the conditions set in the Android application, the controller adjusts the motor’s operational characteristics accordingly. The paper provides a comprehensive description of the controller system’s functioning. The proposed control system is particularly relevant in applications where minimizing energy consumption for driving a DC motor is of utmost importance. Full article
(This article belongs to the Collection Artificial Intelligence in Sensors Technology)
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<p>Wiring diagram of the motor controller.</p>
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<p>The circuit of the motor controller.</p>
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<p>Sample of the code implementation.</p>
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<p>Simplified drawing of the dyno test stand.</p>
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<p>Picture of the dyno test stand.</p>
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<p>LABView application view.</p>
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<p>Performance graph from the Fracmo 24-65-112 motor datasheet [<a href="#B14-sensors-23-06923" class="html-bibr">14</a>].</p>
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<p>Current measurements over time.</p>
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<p>RPM measurements over time.</p>
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<p>Current and PWM correlation.</p>
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18 pages, 4493 KiB  
Article
Hybrid Gray Wolf Optimization–Proportional Integral Based Speed Controllers for Brush-Less DC Motor
by Shukri Mahmood Younus Younus, Uğurhan Kutbay, Javad Rahebi and Fırat Hardalaç
Energies 2023, 16(4), 1640; https://doi.org/10.3390/en16041640 - 7 Feb 2023
Cited by 12 | Viewed by 2086
Abstract
For Brush-less DC motors to function better under various operating settings, such as constant load situations, variable loading situations, and variable set speed situations, speed controller design is essential. Conventional controllers including proportional integral controllers, frequently fall short of efficiency expectations and this [...] Read more.
For Brush-less DC motors to function better under various operating settings, such as constant load situations, variable loading situations, and variable set speed situations, speed controller design is essential. Conventional controllers including proportional integral controllers, frequently fall short of efficiency expectations and this is mostly because the characteristics of a Brush-less DC motor drive exhibit non linearity. This work proposes a hybrid gray wolf optimization and proportional integral controller for management of the speed in Brush-less DC motors to address this issue. For constant load conditions, varying load situations and varying set speed situations, the proposed controller’s efficiency is evaluated and contrasted with that of PID controller, PSO-PI controller, and ANFIS. In this study, two PI controller are used to get the more stability of the system based on tuning of their coefficients with meta heuristic method. The simulation findings show that Hybrid GWO-PI-based controllers are in every way superior to other controllers under consideration. In this study, four case studies are presented, and the best-case study was obtained 0.18619, 0.01928, 0.00030, and 0.01233 for RMSE, IAE, ITAE, and ISE respectively. Full article
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<p>(<b>a</b>) Typical inverter systems for a BLDC motor, (<b>b</b>) Brushless DC motor’s speed control system.</p>
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<p>Formation of a conventional PID controller.</p>
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<p>Simulink model of a conventional PID controller.</p>
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<p>Hierarchies of the gray wolf [<a href="#B27-energies-16-01640" class="html-bibr">27</a>].</p>
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<p>Gray wolf’s structures to get prey, (<b>a</b>) 2D and (<b>b</b>) 3D position vectors [<a href="#B27-energies-16-01640" class="html-bibr">27</a>].</p>
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<p>Search steps [<a href="#B27-energies-16-01640" class="html-bibr">27</a>].</p>
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<p>Flowchart of Gray Wolf Algorithm.</p>
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<p>Simulink model for H-GWO-PI controller.</p>
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<p>The speed response of a brushless DC motor for No-load.</p>
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<p>Speed response of the brushless dc motor under full load condition.</p>
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<p>Response of the Brush-less DC motor in terms of speed under Case A.</p>
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<p>Response of the Brushless DC motor in terms of speed under Case B.</p>
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<p>Response of the Brushless DC motor in terms of speed under Case C.</p>
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<p>Response of the Brushless DC motor in terms of speed under Case D.</p>
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14 pages, 4628 KiB  
Article
1D Modeling Considering Noise and Vibration of Vehicle Window Brushed DC Motor
by Hyunsu Kim, Jiman Kim, Kwangkyu Han and Dongkyu Won
Appl. Sci. 2022, 12(22), 11405; https://doi.org/10.3390/app122211405 - 10 Nov 2022
Cited by 3 | Viewed by 2788
Abstract
This study proposes 1D modeling that considers the noise and vibration of a vehicle window-brushed DC motor. The electrical and mechanical components of the brush DC motor are included, creating a model that considers noise and vibration. The model has a back electromagnetic [...] Read more.
This study proposes 1D modeling that considers the noise and vibration of a vehicle window-brushed DC motor. The electrical and mechanical components of the brush DC motor are included, creating a model that considers noise and vibration. The model has a back electromagnetic force (EMF) including vibration components and is constructed based on an electric circuit and transfer functions. To ensure the reliability of the model, the back EMF, noise, and vibration experiment environment of the brushed DC motor were configured. The measured back EMF was applied to the model, and it was confirmed that the simulation results of the model were consistent with the measured noise and vibrations. Full article
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<p>Schematic of a simplified equivalent representation of the brushed DC motor’s electromechanical components.</p>
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<p>Block diagram of brushed dc motor with added vibration components.</p>
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<p>The motor and measurement method used in the experiment: (<b>a</b>) Vehicle window brushed DC motor used in the experiment; (<b>b</b>) equipment used in the experiment: Microphone, power supply, accelerometer, brushed DC motor.</p>
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<p>Experimental environment for back EMF measurement: (<b>a</b>) Vehicle window brushed DC motor without housing; (<b>b</b>) connecting the drive motor and the test motor and installing the measuring equipment.</p>
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<p>FFT results of noise and vibration of the sample motor. The values measured by the microphone and accelerometer were acquired as raw data in SQUADRIGA II, and FFT was performed in MATLAB: (<b>a</b>) Noise experiment results including motor housing; (<b>b</b>) vibration experiment results including motor housing; (<b>c</b>) noise experiment result with motor housing removed; (<b>d</b>) vibration experiment result with motor housing removed.</p>
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<p>Comparison of CW (clockwise) and CCW (counterclockwise) of the sample motor. The figure shows that even if the same voltage is applied, the noise and vibration of CW and CCW differ in magnitude and frequency. The direction of rotation is shown in (<b>a</b>), and in the graph, red is CCW and blue is CW: (<b>a</b>) Results of FFT of CCW and CW noise components; (<b>b</b>) results of FFT of CCW and CW vibration components.</p>
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<p>The result of measuring the back EMF of the sample motor with an oscilloscope. Red is CCW, blue is CW, and numbers in graphs (<b>b</b>,<b>c</b>) represent motor RPM. The contents of each Figure are as follows: (<b>a</b>) Back EMF time data measured with an oscilloscope at 1500 RPM; (<b>b</b>) magnitude of the eighth-order vibration component at 1500 RPM to 3500 RPM; (<b>c</b>) magnitude of the DC component at 20 RPS to 60 RPS.</p>
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<p>The result of measuring the back EMF of the sample motor with an oscilloscope. Red is CCW, blue is CW, and numbers in graphs (<b>b</b>,<b>c</b>) represent motor RPM. The contents of each Figure are as follows: (<b>a</b>) Back EMF time data measured with an oscilloscope at 1500 RPM; (<b>b</b>) magnitude of the eighth-order vibration component at 1500 RPM to 3500 RPM; (<b>c</b>) magnitude of the DC component at 20 RPS to 60 RPS.</p>
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<p>MATLAB Simulink modeling based on transfer functions and electrical circuits.</p>
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<p>Results of simulation with back EMF including vibration in the CW: (<b>a</b>) Back EMF time data; (<b>b</b>) back EMF FFT data; (<b>c</b>) current time data; (<b>d</b>) current FFT data; (<b>e</b>) torque time data; (<b>f</b>) torque FFT data.</p>
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<p>Results of simulation with back EMF including vibration in the CCW: (<b>a</b>) Back EMF time data; (<b>b</b>) back EMF FFT data; (<b>c</b>) current time data; (<b>d</b>) current FFT data; (<b>e</b>) torque time data; (<b>f</b>) torque FFT data.</p>
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<p>Classic block diagram of brushed DC motor.</p>
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24 pages, 9064 KiB  
Article
Optimal PID Control of a Brushed DC Motor with an Embedded Low-Cost Magnetic Quadrature Encoder for Improved Step Overshoot and Undershoot Responses in a Mobile Robot Application
by Ricard Bitriá and Jordi Palacín
Sensors 2022, 22(20), 7817; https://doi.org/10.3390/s22207817 - 14 Oct 2022
Cited by 15 | Viewed by 6507
Abstract
The development of a proportional–integral–derivative (PID) control system is a simple, practical, highly effective method used to control the angular rotational velocity of electric motors. This paper describes the optimization of the PID control of a brushed DC motor (BDCM) with an embedded [...] Read more.
The development of a proportional–integral–derivative (PID) control system is a simple, practical, highly effective method used to control the angular rotational velocity of electric motors. This paper describes the optimization of the PID control of a brushed DC motor (BDCM) with an embedded low-cost magnetic quadrature encoder. This paper demonstrates empirically that the feedback provided by low-cost magnetic encoders produces some inaccuracies and control artifacts that are not usually considered in simulations, proposing a practical optimization approach in order to improve the step overshoot and undershoot controller response. This optimization approach is responsible for the motion performances of a human-sized omnidirectional mobile robot using three motorized omnidirectional wheels. Full article
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<p>(<b>a</b>) Image of the APR-02 mobile robot. (<b>b</b>) Details of the internal structure supporting the three BDCMs that drive the three omnidirectional wheels of the mobile robot.</p>
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<p>Image of the BDCM used in the APR-02 mobile robot, which includes a 64:1 planetary gearbox and a low-cost magnetic encoder attached to the motor shaft. The motor is supported by an aluminum support structure that has some (red) support elements made of flexible rubber in order to reduce the transmission of vibrations.</p>
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<p>Electronic control board implementing the PID controller.</p>
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<p>PID block diagram.</p>
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<p>Representation of all steps and modules required to practically implement the PID controller of one motor of the APR-02 mobile robot.</p>
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<p>(<b>a</b>) Representation of the six-pole magnet of the encoder that is attached to the motor shaft and the two fixed hall-effect sensors, HA and HB, placed at a 90° phase offset. (<b>b</b>) Logical quadrature output signals generated by the rotation of the encoder and the edges detected by the microcontroller using the input capture module.</p>
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<p>Open-loop wheel speed measurement deduced from the raw time-elapsed edge measurements gathered from the magnetic encoder of the BDCM for the different PWM duty cycles applied: (<b>a</b>) 20% or low-speed example; (<b>b</b>) 50% or medium-speed example; (<b>c</b>) 100% or full-speed example.</p>
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<p>Corrected open-loop wheel speed measurement deduced from the raw time-elapsed edge measurements gathered from the magnetic encoder of the BDCM for the different PWM duty cycles applied and the correction coefficients displayed in <a href="#sensors-22-07817-t001" class="html-table">Table 1</a>: (<b>a</b>) 20% PWM case; (<b>b</b>) 50% PWM case; (<b>c</b>) 100% PWM case.</p>
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<p>(<b>a</b>) PWM and RPM relationship in different load scenarios. (<b>b</b>) Motor current consumption depending on the applied PWM duty cycle in different load scenarios.</p>
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<p>Motor step response for different PWM cycles.</p>
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<p>Acceleration curve and inverted deceleration curve moved to <span class="html-italic">t</span> = 0.0 s.</p>
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<p>Calibration data required for model calculation: (<b>a</b>) PWM duty cycle sequence applied to the motor; (<b>b</b>) measured angular rotational velocity of the output shaft (gray line) and generated by the continuous-time (blue dotted line) and discrete-time (red dotted) models found by the SIT Toolbox.</p>
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<p>(<b>a</b>) Real motor setup. (<b>b</b>) Simulation of the motor model.</p>
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<p>Open-loop motor step response comparison: real motor speed gathered from the encoder (blue line), continuous-time (red line) model simulation, and discrete-time (brown line) model simulation.</p>
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<p>Histogram of the encoder’s time-elapsed (<math display="inline"><semantics> <mrow> <mo>Δ</mo> <msub> <mi>t</mi> <mi>k</mi> </msub> </mrow> </semantics></math>) values obtained with different PWM duty cycles (cases represented in <a href="#sensors-22-07817-f009" class="html-fig">Figure 9</a>a with no load), colored in order to differentiate the cases analyzed.</p>
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<p>Simulink<sup>®</sup> continuous control loop model used by the FRB PID tuner.</p>
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<p>Simulink<sup>®</sup> discrete control loop model used by the FRB PID tuner.</p>
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<p>BDCM output in a closed-loop PID control: real evolution of the angular rotational velocity measured from the information gathered by the magnetic quadrature encoder (blue line) and simulated motor velocity (yellow line). Response to steps with target speeds of 5, 10, 20, 40, and 60 rpm.</p>
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<p>Evaluation of the NIAE values for different sampling periods (<math display="inline"><semantics> <mrow> <msub> <mi>T</mi> <mi>s</mi> </msub> </mrow> </semantics></math>) and different target speeds: 10 (blue line), 30 (green line), and 60 (yellow line) rpm.</p>
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<p>A 3D representation of the NIAE of the PID controller according the planes defined by the <math display="inline"><semantics> <mrow> <msub> <mi>K</mi> <mi>p</mi> </msub> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <msub> <mi>K</mi> <mi>i</mi> </msub> </mrow> </semantics></math> and <math display="inline"><semantics> <mrow> <msub> <mi>K</mi> <mi>d</mi> </msub> </mrow> </semantics></math> parameters. The white point depicts the location of the baseline values proposed by the FRB PID Tuner procedure. The leftmost plane is for <math display="inline"><semantics> <mrow> <msub> <mi>K</mi> <mi>i</mi> </msub> <mo>=</mo> <mn>0</mn> <mo> </mo> <msup> <mi mathvariant="normal">s</mi> <mrow> <mo>−</mo> <mn>1</mn> </mrow> </msup> </mrow> </semantics></math> and the bottom plane is for <math display="inline"><semantics> <mrow> <msub> <mi>K</mi> <mi>d</mi> </msub> <mo>=</mo> <mn>0</mn> <mo> </mo> <mi mathvariant="normal">s</mi> </mrow> </semantics></math>.</p>
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<p>Details of the two horizontal planes defined in <a href="#sensors-22-07817-f020" class="html-fig">Figure 20</a>. The white point depicts the location or projection of the NIAE baseline values obtained with the FRB PID tuner procedure while the red point depicts the location of the minimum NIAE in each plane. The values of the NIAE are also displayed for reference: (<b>a</b>) plane with <math display="inline"><semantics> <mrow> <msub> <mi>K</mi> <mi>d</mi> </msub> <mo>=</mo> <mn>0.0182</mn> <mrow> <mo> </mo> <mi mathvariant="normal">s</mi> </mrow> </mrow> </semantics></math>; (<b>b</b>) plane with <math display="inline"><semantics> <mrow> <msub> <mi>K</mi> <mi>d</mi> </msub> <mo>=</mo> <mn>0</mn> <mo> </mo> <mi mathvariant="normal">s</mi> </mrow> </semantics></math>.</p>
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<p>Step overshoot results measured in the real motor using the reference PID parameters obtained with the FRB PID tuner procedure (yellow line) and the best PID parameters, which minimize the NIAE. The target speed is 30 rpm.</p>
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21 pages, 6812 KiB  
Article
Mobile Robots—AHP-Based Actuation Solution Selection and Comparison between Mecanum Wheel Drive and Differential Drive with Regard to Dynamic Loads
by Sever-Gabriel Racz, Mihai Crenganiș, Radu-Eugen Breaz, Adrian Maroșan, Alexandru Bârsan, Claudia-Emilia Gîrjob, Cristina-Maria Biriș and Melania Tera
Machines 2022, 10(10), 886; https://doi.org/10.3390/machines10100886 - 1 Oct 2022
Cited by 6 | Viewed by 2704
Abstract
Mobile robots are increasingly used in industrial applications. There are many constructive solutions for mobile robots using various variants of actuation and control. The proposed work presents a low-cost variant of a mobile robot equipped with Mecanum wheels, which uses brushed DC motors, [...] Read more.
Mobile robots are increasingly used in industrial applications. There are many constructive solutions for mobile robots using various variants of actuation and control. The proposed work presents a low-cost variant of a mobile robot equipped with Mecanum wheels, which uses brushed DC motors, controlled by the PWM method as the actuation solution. In the first part, a multicriteria analysis based on the AHP method was performed for the selection of the actuation solution. Then, using the software tools Simscape Multibody, Matlab, and Simulink, models were developed that allowed the simulation of the operation of the proposed robot, based both on its kinematics and dynamics. Using these models, both the Mecanum wheel drive version and the differential drive version were studied by means of simulation. The simulations mainly aimed at identifying the way the currents vary through the wheel drive motors, in order to find methods to reduce them. The values obtained by the simulation were later compared with those obtained experimentally, and the corresponding conclusions with regard to the accuracy of the models were drawn. Full article
(This article belongs to the Special Issue Design and Control of Industrial Robots)
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<p>The mobile robot with Mecanum wheels: (<b>a</b>) first view; (<b>b</b>) second view.</p>
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<p>Schematic diagram of the four-wheel Mecanum mobile robot.</p>
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<p>Schematic diagram of the differential drive mobile robot.</p>
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<p>The 3D CAD model of the mobile robot: (<b>a</b>) first view; (<b>b</b>) second view.</p>
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<p>Simulation diagram for the four-wheel Mecanum kinematic solution.</p>
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<p>Simulation diagram for the differential drive kinematic solution.</p>
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<p>Generating corners—differential drive kinematic solution: (<b>a</b>) without generating a loop; (<b>b</b>) generating a loop.</p>
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<p>Inputs for the four-wheel Mecanum kinematic solution (speed of the wheels).</p>
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<p>Inputs for the differential drive no-loop kinematic solution (speed of the wheels).</p>
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<p>Inputs for the differential drive with loop kinematic solution (speed of the wheels).</p>
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<p>Simulation results: (<b>a</b>) trajectory for four-wheel Mecanum; (<b>b</b>) trajectory for differential drive, no-loop; (<b>c</b>) trajectory for differential drive with loop; (<b>d</b>) screenshot from Mechanics Explorer–Simscape.</p>
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<p>Comparison between simulated (<b>a</b>,<b>c</b>,<b>e</b>,<b>g</b>) and measured (<b>b</b>,<b>d</b>,<b>f</b>,<b>h</b>) currents through the wheel motors for the four-wheel Mecanum kinematic solution: (<b>a</b>,<b>b</b>) wheel 1; (<b>c</b>,<b>d</b>) wheel 2; (<b>e</b>,<b>f</b>) wheel 3; (<b>g</b>,<b>h</b>) wheel 4.</p>
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<p>Comparison between simulated (<b>a</b>,<b>c</b>,<b>e</b>,<b>g</b>) and measured (<b>b</b>,<b>d</b>,<b>f</b>,<b>h</b>) currents through the wheel motors for the differential drive no-loop kinematic solution: (<b>a</b>,<b>b</b>) wheel 1; (<b>c</b>,<b>d</b>) wheel 2; (<b>e</b>,<b>f</b>) wheel 3; (<b>g</b>,<b>h</b>) wheel 4.</p>
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<p>Comparison between simulated (<b>a</b>,<b>c</b>,<b>e</b>,<b>g</b>) and measured (<b>b</b>,<b>d</b>,<b>f</b>,<b>h</b>) currents through the wheel motors for the differential drive with loop kinematic solution: (<b>a</b>,<b>b</b>) wheel 1; (<b>c</b>,<b>d</b>) wheel 2; (<b>e</b>,<b>f</b>) wheel 3; (<b>g</b>,<b>h</b>) wheel 4.</p>
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21 pages, 1718 KiB  
Article
Auto-Regression Model-Based Off-Line PID Controller Tuning: An Adaptive Strategy for DC Motor Control
by José A. Niembro-Ceceña, Roberto A. Gómez-Loenzo, Juvenal Rodríguez-Reséndiz, Omar Rodríguez-Abreo and Ákos Odry
Micromachines 2022, 13(8), 1264; https://doi.org/10.3390/mi13081264 - 6 Aug 2022
Cited by 8 | Viewed by 3260
Abstract
Brushed (B) and Brushless (BL) DC motors constitute the cornerstone of mechatronic systems regardless their sizes (including miniaturized), in which both position and speed control tasks require the application of sophisticated algorithms. This manuscript addresses the initial step using time series analysis to [...] Read more.
Brushed (B) and Brushless (BL) DC motors constitute the cornerstone of mechatronic systems regardless their sizes (including miniaturized), in which both position and speed control tasks require the application of sophisticated algorithms. This manuscript addresses the initial step using time series analysis to forecast Back EMF values, thereby enabling the elaboration of real-time adaptive fine-tuning strategies for PID controllers in such a control system design problem. An Auto-Regressive Moving Average (ARMA) model is developed to estimate the DC motor parameter, which evolves in time due to the system’s imperfection (i.e., unpredictable duty cycle) and influences the closed-loop performance. The methodology is executed offline; thus, it highlights the applicability of collected BDC motor measurements in time series analysis. The proposed method updates the PID controller gains based on the Simulink ™ controller tuning toolbox. The contribution of this approach is shown in a comparative study that indicates an opportunity to use time series analysis to forecast DC motor parameters, to re-tune PID controller gains, and to obtain similar performance under the same perturbation conditions. The research demonstrates the practical applicability of the proposed method for fine-tuning/re-tuning controllers in real-time. The results show the inclusion of the time series analysis to recalculate controller gains as an alternative for adaptive control. Full article
(This article belongs to the Section E:Engineering and Technology)
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<p>DC motor electro-mechanical schematic; <math display="inline"><semantics> <mrow> <mi>w</mi> <mo>=</mo> <mi>ω</mi> </mrow> </semantics></math> is the angular speed generated by an input voltage <math display="inline"><semantics> <msub> <mi>V</mi> <mi>a</mi> </msub> </semantics></math>.</p>
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<p>The DC motor block diagram represents the electrical and mechanical components of the device. The electrical component is related to the mechanical component through the torque constant <math display="inline"><semantics> <msub> <mi>K</mi> <mi>t</mi> </msub> </semantics></math>. The angular speed and voltage input are related through the Back EMF constant <math display="inline"><semantics> <msub> <mi>K</mi> <mi>b</mi> </msub> </semantics></math>.</p>
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<p>Simplified transfer function in open loop. The Back EMF <math display="inline"><semantics> <msub> <mi>K</mi> <mi>b</mi> </msub> </semantics></math> is disconnected from the loop.</p>
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<p>Open-loop system response to a voltage input of 12 volts. The angular speed produced is proportional to the input voltage and is equal to 314.16 rad/s. The dynamic response of the system achieves 63% of the reference angular velocity at 0.025 s, the steady state error at 0% is achieved after 0.15 s.</p>
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<p>The open-loop simulation produces different Back EMFs considering changes in electrical resistance and electrical inductance values.</p>
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<p>Data collection from simulation for Back EMF. This data collection is presented in time.</p>
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<p>Block diagram representation for the closed-loop system including the PID controller.</p>
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<p>System response to a 9 volts step input in a closed-loop configuration. The system exhibits an under-damped response achieving 63% of reference angular velocity at 0.025 s. This is consistent with experimental open-loop data. The steady estate 0% error is achieved at 0.2 s at approximately 240 rad/s.</p>
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<p>Mean and Standard deviation chart of simulated Back EMF data. The data is displayed in 10 sets of 7 elements each.</p>
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<p>Lag analysis of the time series determines <span class="html-italic">p</span>th and <span class="html-italic">q</span>th elements depending on statistical significance. The model is AR(1)I(0)MA(1).</p>
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<p>Regressed data displayed with current data to show regression fitting accuracy. Regression was produced using an ARMA model. The current ARMA Model is not fitting the current data; there are some causes for this: first, the data mean is not zero, the proposed model is not adding an integrated (<span class="html-italic">I</span>) part, the time series analysis using Ljung–Box concluded the data values are independent.</p>
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<p>Analysis of residuals between the current data and regressed data. The residuals do not show normal distribution, but a relatively high error.</p>
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<p>Regression produced with the ARMA model and forecast for the next 3 consecutive values (blue dots shown with CI).</p>
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<p>System response to a Back EMF change (<math display="inline"><semantics> <mrow> <msub> <mi>K</mi> <mi>b</mi> </msub> <mo>=</mo> <mn>0.0385</mn> </mrow> </semantics></math>)—sample 1. The dynamic response at initial conditions and load accepts and load rejects reaches 63% of the reference at approximately 0.025 sec, the steady-state error is 0% at the stable point after 0.15 s. In terms of performance, the proposed gains have room for improvement to reduce overshoot and increase speed response.</p>
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<p>System response to a Back EMF change (<math display="inline"><semantics> <mrow> <msub> <mi>K</mi> <mi>b</mi> </msub> <mo>=</mo> <mn>0.0342</mn> </mrow> </semantics></math>)—sample 2. The dynamic response at initial conditions and load accepts and load rejects reaches 63% of the reference approximately at 0.025 s, the steady-state error is 0% at the stable point after 0.15 s. In terms of performance, the proposed gains have room for improvement to reduce overshoot and increase speed response.</p>
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<p>System response to a Back EMF change (<math display="inline"><semantics> <mrow> <msub> <mi>K</mi> <mi>b</mi> </msub> <mo>=</mo> <mn>0.045</mn> </mrow> </semantics></math>)—sample 5. The dynamic response at initial conditions and load accepts and load rejects achieves 63% of the reference at approximately 0.025 s, the steady-state error is 0% at the stable point after 0.15 sec. In terms of performance, the proposed gains have room for improvement to reduce overshoot and increase speed response.</p>
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20 pages, 3421 KiB  
Article
A Cooperative ADRC-Based Approach for Angular Velocity Synchronization and Load-Sharing in Servomechanisms
by W. Fermin Guerrero-Sánchez, Jésus Linares-Flores, Arturo Hernández-Méndez, Victor R. Gonzalez-Diaz, Gerardo Mino Aguilar, German A. Munoz-Hernandez and J. Fermi Guerrero-Castellanos
Energies 2022, 15(14), 5121; https://doi.org/10.3390/en15145121 - 14 Jul 2022
Cited by 1 | Viewed by 1818
Abstract
This paper is concerned with designing a dynamical synchronization (via a robust cooperative control) of an electromechanical system network (EMSN), consisting of nonidentical brushed DC motors, where only the motors’ angular velocity measurements are available. The challenge of the proposed approach is that [...] Read more.
This paper is concerned with designing a dynamical synchronization (via a robust cooperative control) of an electromechanical system network (EMSN), consisting of nonidentical brushed DC motors, where only the motors’ angular velocity measurements are available. The challenge of the proposed approach is that the actuation provided by the motor needs to handle external disturbances to achieve the velocity tracking task and handle the interaction between both motors cooperatively to share the load and the disturbance rejection. The control’s basis involves differential flatness and an active disturbance rejection control (ADRC) framework augmented using ideas from the graph theory analysis and multi-agent networks. Experimental results verify the theoretical developments and show the effectiveness of the proposed control strategy despite unexpectedly changing load disturbance and parameters uncertainties. The proposed algorithm is suitable for embedded use due to its simplicity. It can be applied to a broad spectrum of mechatronic systems where dual-motor drive arrangements are necessary. Full article
(This article belongs to the Special Issue Active Disturbance Rejection Control in Power Electronics)
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<p>Servomechanism driven cooperatively.</p>
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<p>(<b>a</b>) Electromechanical system network (EMSN) and (<b>b</b>) its interconnection topology.</p>
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<p>Interconnection topology of the EMSN depicting energy flow (solid edges) and information flow (dotted edges).</p>
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<p>General block diagram of the proposed control scheme.</p>
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<p>Experimental setup scheme.</p>
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<p>Servomechanism drives by two brushed DC motors.</p>
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<p>Angular speed tracking responses: (<b>a</b>) in each subsystem M1 and M2, and (<b>b</b>) in the common stiff shaft.</p>
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<p>Angular speed tracking error responses.</p>
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<p>(<b>a</b>) Load torque applied on the common stiff shaft, (<b>b</b>) internal developed torque on each brushed DC motor, input voltage response (<b>c</b>) with and (<b>d</b>) without digital torque coupling.</p>
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<p>Angular velocity response and its corresponding armature current responses: (<b>a</b>) with digital torque coupling and (<b>b</b>) without digital torque coupling.</p>
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<p>Load torque applied in the dynamic model parameter variation tests.</p>
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<p>Variation of <math display="inline"><semantics> <msub> <mi>L</mi> <mrow> <mi>a</mi> <mn>2</mn> </mrow> </msub> </semantics></math>: (<b>a</b>) <math display="inline"><semantics> <mrow> <msub> <mi>ω</mi> <mi>L</mi> </msub> <mo>−</mo> <msubsup> <mi>ω</mi> <mi>L</mi> <mo>*</mo> </msubsup> </mrow> </semantics></math>, (<b>b</b>) <math display="inline"><semantics> <mrow> <msub> <mover accent="true"> <mi>T</mi> <mo>^</mo> </mover> <mrow> <mi>d</mi> <mn>1</mn> </mrow> </msub> <mo>−</mo> <msub> <mover accent="true"> <mi>T</mi> <mo>^</mo> </mover> <mrow> <mi>d</mi> <mn>2</mn> </mrow> </msub> </mrow> </semantics></math>; variation of <math display="inline"><semantics> <msub> <mi>J</mi> <mrow> <mi>e</mi> <mi>q</mi> <mn>2</mn> </mrow> </msub> </semantics></math>: (<b>c</b>) <math display="inline"><semantics> <mrow> <msub> <mi>ω</mi> <mi>L</mi> </msub> <mo>−</mo> <msubsup> <mi>ω</mi> <mi>L</mi> <mo>*</mo> </msubsup> </mrow> </semantics></math>, (<b>d</b>) <math display="inline"><semantics> <mrow> <msub> <mover accent="true"> <mi>T</mi> <mo>^</mo> </mover> <mrow> <mi>d</mi> <mn>1</mn> </mrow> </msub> <mo>−</mo> <msub> <mover accent="true"> <mi>T</mi> <mo>^</mo> </mover> <mrow> <mi>d</mi> <mn>2</mn> </mrow> </msub> </mrow> </semantics></math>.</p>
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<p>Variation of <math display="inline"><semantics> <msub> <mi>R</mi> <mrow> <mi>a</mi> <mn>2</mn> </mrow> </msub> </semantics></math>: (<b>a</b>) <math display="inline"><semantics> <mrow> <msub> <mi>ω</mi> <mi>L</mi> </msub> <mo>−</mo> <msubsup> <mi>ω</mi> <mi>L</mi> <mo>*</mo> </msubsup> </mrow> </semantics></math>, (<b>b</b>) <math display="inline"><semantics> <mrow> <msub> <mover accent="true"> <mi>T</mi> <mo>^</mo> </mover> <mrow> <mi>d</mi> <mn>1</mn> </mrow> </msub> <mo>−</mo> <msub> <mover accent="true"> <mi>T</mi> <mo>^</mo> </mover> <mrow> <mi>d</mi> <mn>2</mn> </mrow> </msub> </mrow> </semantics></math>.</p>
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