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18 pages, 6346 KiB  
Article
Novel Single-Stage Electrolytic Capacitor-Less Buck-Boost Inverter
by Youn-Ok Choi and Khai M. Nguyen
Energies 2024, 17(23), 6191; https://doi.org/10.3390/en17236191 - 8 Dec 2024
Viewed by 620
Abstract
Nowadays, single-phase, single-stage, buck-boost power inverters are mostly considered to be used for renewable energy source applications due to their wide range of capabilities. This article introduces a novel, single-phase, single-stage, buck-boost inverter with a wide range of input DC voltage. In addition, [...] Read more.
Nowadays, single-phase, single-stage, buck-boost power inverters are mostly considered to be used for renewable energy source applications due to their wide range of capabilities. This article introduces a novel, single-phase, single-stage, buck-boost inverter with a wide range of input DC voltage. In addition, the introduced inverter does not use the electrolytic capacitor, which enhances the lifetime and volume reduction in the inverter, avoids the high equivalent series resistance, and reduces the inrush current of electrolytic capacitors in the introduced inverter. Moreover, the introduced inverter exhibits a reduced switch voltage rating, and the novel PWM control strategy with the half-cycle of the sinusoidal is derived to reduce the switching loss of power switches, thus improving the inverter’s efficiency. The operation states, theoretical analysis, and design of components are fully discussed. A comparative study of the introduced inverter with other buck-boost inverter topologies is also reported. Finally, the 500 W laboratory prototype is set up for simulation and experimental verification. The experimental results verify the correctness of operating analysis and simulation. Full article
(This article belongs to the Special Issue Power Electronics and Power Quality 2024)
Show Figures

Figure 1

Figure 1
<p>Proposed S<sup>2</sup>B<sup>2</sup>I.</p>
Full article ">Figure 2
<p>Derived PWM switching scheme of the proposed S<sup>2</sup>B<sup>2</sup>I.</p>
Full article ">Figure 3
<p>Operational modes of the proposed S<sup>2</sup>B<sup>2</sup>I. (<b>a</b>) Mode 1. (<b>b</b>) Mode 2. (<b>c</b>) Mode 3. (<b>d</b>) Mode 4. (<b>e</b>) Mode 5. (<b>f</b>) Mode 6.</p>
Full article ">Figure 4
<p>Power loss distribution of the proposed the proposed S<sup>2</sup>B<sup>2</sup>I.</p>
Full article ">Figure 5
<p>Simulation circuit of the proposed S<sup>2</sup>B<sup>2</sup>I.</p>
Full article ">Figure 6
<p>The waveforms of simulation results in boost operation when <span class="html-italic">G</span> = 3.1. (<b>a</b>) Input and output voltages, capacitor <span class="html-italic">C</span><sub>1</sub> and <span class="html-italic">C</span><sub>2</sub> voltage, and currents of inductors <span class="html-italic">L</span><sub>1</sub> and <span class="html-italic">L</span><sub>2</sub>. (<b>b</b>) Voltage stress on switches <span class="html-italic">S</span><sub>1</sub>–<span class="html-italic">S</span><sub>4</sub>.</p>
Full article ">Figure 6 Cont.
<p>The waveforms of simulation results in boost operation when <span class="html-italic">G</span> = 3.1. (<b>a</b>) Input and output voltages, capacitor <span class="html-italic">C</span><sub>1</sub> and <span class="html-italic">C</span><sub>2</sub> voltage, and currents of inductors <span class="html-italic">L</span><sub>1</sub> and <span class="html-italic">L</span><sub>2</sub>. (<b>b</b>) Voltage stress on switches <span class="html-italic">S</span><sub>1</sub>–<span class="html-italic">S</span><sub>4</sub>.</p>
Full article ">Figure 7
<p>The waveforms of simulation results in buck operation when <span class="html-italic">G</span> = 0.78. (<b>a</b>) Input and output voltages, capacitor <span class="html-italic">C</span><sub>1</sub> and <span class="html-italic">C</span><sub>2</sub> voltage, and currents of inductors <span class="html-italic">L</span><sub>1</sub> and <span class="html-italic">L</span><sub>2</sub>. (<b>b</b>) Voltage stress on switches <span class="html-italic">S</span><sub>1</sub>–<span class="html-italic">S</span><sub>4</sub>.</p>
Full article ">Figure 7 Cont.
<p>The waveforms of simulation results in buck operation when <span class="html-italic">G</span> = 0.78. (<b>a</b>) Input and output voltages, capacitor <span class="html-italic">C</span><sub>1</sub> and <span class="html-italic">C</span><sub>2</sub> voltage, and currents of inductors <span class="html-italic">L</span><sub>1</sub> and <span class="html-italic">L</span><sub>2</sub>. (<b>b</b>) Voltage stress on switches <span class="html-italic">S</span><sub>1</sub>–<span class="html-italic">S</span><sub>4</sub>.</p>
Full article ">Figure 8
<p>A photo of the S<sup>2</sup>B<sup>2</sup>I prototype.</p>
Full article ">Figure 9
<p>The waveforms of experimental results in boost operation when <span class="html-italic">G</span> = 3.1. (<b>a</b>) Output voltage, current of inductor <span class="html-italic">L</span><sub>1</sub>, and voltages of capacitors <span class="html-italic">C</span><sub>1</sub> and <span class="html-italic">C</span><sub>2</sub>. (<b>b</b>) PWM signals of switches <span class="html-italic">S</span><sub>1</sub>, <span class="html-italic">S</span><sub>3</sub>, and <span class="html-italic">S</span><sub>4</sub>. (<b>c</b>) Voltage stress on switches <span class="html-italic">S</span><sub>1</sub>, <span class="html-italic">S</span><sub>3</sub>, and <span class="html-italic">S</span><sub>4</sub>.</p>
Full article ">Figure 9 Cont.
<p>The waveforms of experimental results in boost operation when <span class="html-italic">G</span> = 3.1. (<b>a</b>) Output voltage, current of inductor <span class="html-italic">L</span><sub>1</sub>, and voltages of capacitors <span class="html-italic">C</span><sub>1</sub> and <span class="html-italic">C</span><sub>2</sub>. (<b>b</b>) PWM signals of switches <span class="html-italic">S</span><sub>1</sub>, <span class="html-italic">S</span><sub>3</sub>, and <span class="html-italic">S</span><sub>4</sub>. (<b>c</b>) Voltage stress on switches <span class="html-italic">S</span><sub>1</sub>, <span class="html-italic">S</span><sub>3</sub>, and <span class="html-italic">S</span><sub>4</sub>.</p>
Full article ">Figure 10
<p>The waveforms of experimental results in buck operation when <span class="html-italic">G</span> = 0.78. (<b>a</b>) Output voltage, current of inductor <span class="html-italic">L</span><sub>1</sub><span class="html-italic">,</span> and voltages of capacitors <span class="html-italic">C</span><sub>1</sub> and <span class="html-italic">C</span><sub>2</sub>. (<b>b</b>) PWM signals of switches <span class="html-italic">S</span><sub>1</sub>, <span class="html-italic">S</span><sub>3</sub>, and <span class="html-italic">S</span><sub>4</sub>. (<b>c</b>) Voltage stress on switches <span class="html-italic">S</span><sub>1</sub>, <span class="html-italic">S</span><sub>3</sub>, and <span class="html-italic">S</span><sub>4</sub>.</p>
Full article ">Figure 10 Cont.
<p>The waveforms of experimental results in buck operation when <span class="html-italic">G</span> = 0.78. (<b>a</b>) Output voltage, current of inductor <span class="html-italic">L</span><sub>1</sub><span class="html-italic">,</span> and voltages of capacitors <span class="html-italic">C</span><sub>1</sub> and <span class="html-italic">C</span><sub>2</sub>. (<b>b</b>) PWM signals of switches <span class="html-italic">S</span><sub>1</sub>, <span class="html-italic">S</span><sub>3</sub>, and <span class="html-italic">S</span><sub>4</sub>. (<b>c</b>) Voltage stress on switches <span class="html-italic">S</span><sub>1</sub>, <span class="html-italic">S</span><sub>3</sub>, and <span class="html-italic">S</span><sub>4</sub>.</p>
Full article ">Figure 11
<p>Measurements of the proposed S<sup>2</sup>B<sup>2</sup>I. (<b>a</b>) THD of output current; (<b>b</b>) efficiency.</p>
Full article ">
18 pages, 8093 KiB  
Article
Quadratic Boost Converter with Optimized Switching Ripple Based on the Selection of Passive Components
by Edgar D. Silva-Vera, Julio C. Rosas-Caro, Jesus E. Valdez-Resendiz, Avelina Alejo-Reyes, Omar F. Ruiz-Martinez, Johnny Posada Contreras and Pedro Martín García-Vite
Electricity 2024, 5(4), 877-894; https://doi.org/10.3390/electricity5040044 - 9 Nov 2024
Viewed by 850
Abstract
This work introduces a boost converter with quadratic gain. Its main advantage compared to well-known similar quadratic boost converters is that it requires capacitors with a relatively small capacitance and inductors with small inductance, leading to a reduction in the size or stored [...] Read more.
This work introduces a boost converter with quadratic gain. Its main advantage compared to well-known similar quadratic boost converters is that it requires capacitors with a relatively small capacitance and inductors with small inductance, leading to a reduction in the size or stored energy while performing a power conversion of similar power rating and the same switching ripples in both the input current and the output voltage. It is inspired by the recently introduced ISB converter and uses a specific PWM method. This results in achieving switching ripple constraints while using smaller energy storage elements (capacitors and inductors). The updated converter offers the same voltage gain compared to the conventional quadratic boost topology with the benefit of compact component sizes. While it has more passive elements, they are of reduced size. An analysis of energy storage revealed that this new converter uses only half the energy in inductors and 14% in capacitors when compared to specific design parameters. Full article
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Figure 1

Figure 1
<p>The family of second-order converters: (<b>a</b>) buck, (<b>b</b>) boost, and (<b>c</b>) buck–boost.</p>
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<p>The basic family of fourth-order converters: (<b>a</b>) Cuk, (<b>b</b>) SEPIC, and (<b>c</b>) ZETA.</p>
Full article ">Figure 3
<p>(<b>a</b>) Two cascaded boost converters; (<b>b</b>) the quadratic boost topology.</p>
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<p>Quadratic boost converter’s equivalent circuits corresponding to the operation of the switch: (<b>a</b>) when the switch is on; (<b>b</b>) when the switch is off.</p>
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<p>The proposed quadratic boost converter.</p>
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<p>Depiction of the single power stage’s switching phases: (<b>a</b>) transistor activated; (<b>b</b>) transistor deactivated.</p>
Full article ">Figure 7
<p>PWM method for the standard quadratic boost topology (<a href="#electricity-05-00044-f003" class="html-fig">Figure 3</a>).</p>
Full article ">Figure 8
<p>PWM method in the proposed topology (<a href="#electricity-05-00044-f005" class="html-fig">Figure 5</a>).</p>
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<p>Equivalent circuits according to the switching state for the proposed topology.</p>
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<p>Time distribution of switching signals in the proposed converter.</p>
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<p>The standard quadratic boost topology design.</p>
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<p>The proposed topology design.</p>
Full article ">Figure 13
<p>Voltage at the output port of both the standard quadratic boost and the proposed converter.</p>
Full article ">Figure 14
<p>Current at the input port of both the traditional quadratic boost and the proposed converter.</p>
Full article ">Figure 15
<p>Input current and currents through the inductors of the input stage, <span class="html-italic">L<sub>a</sub></span> and <span class="html-italic">L<sub>b</sub></span>.</p>
Full article ">Figure 16
<p>The input current and the currents through the inductors of the output stage, <span class="html-italic">L<sub>c</sub></span> and <span class="html-italic">L<sub>d</sub></span>.</p>
Full article ">Figure 17
<p>Input and output stage inductor currents.</p>
Full article ">Figure 18
<p>Important waveforms of the converter input stage.</p>
Full article ">Figure 19
<p>Important waveforms of the converter output stage.</p>
Full article ">Figure 20
<p>Output voltage waveform and voltage across capacitors of input and output stages.</p>
Full article ">
25 pages, 12723 KiB  
Article
A Dynamic Simulation of a Piezoelectric Energy-Harvesting System Integrated with a Closed-Loop Voltage Source Converter for Sustainable Power Generation
by Ahmed K. Ali, Ali Abdulwahhab Abdulrazzaq and Ali H. Mohsin
Processes 2024, 12(10), 2198; https://doi.org/10.3390/pr12102198 - 10 Oct 2024
Viewed by 1331
Abstract
Numerous recent studies address the concept of energy harvesting from natural wind excitation vibration to piezoelectric surfaces, aerodynamic losses, and electromagnetic dampers. All these techniques require a connection to an energy-management circuit. However, the simulation model for energy conversion and management dedicated to [...] Read more.
Numerous recent studies address the concept of energy harvesting from natural wind excitation vibration to piezoelectric surfaces, aerodynamic losses, and electromagnetic dampers. All these techniques require a connection to an energy-management circuit. However, the simulation model for energy conversion and management dedicated to this task has not yet been described. This paper presents a model-based simulation for an energy conversion system using piezoelectric energy-harvester system (PEHS) technology. A controlled pulse width modulation (PWM) rectifier, a closed-loop buck-boost converter, and a piezoelectric transducer comprise a dynamic mathematical model of a PEHS. The control blocks of the closed-loop buck-boost converter use the perturbation and observation (P&O) algorithm based on maximum power point tracking (MPPT), which adapts the operational voltage of the piezoelectric source to deliver the maximum power to load. A simulation program is employed to perform mathematical analysis on various wind vibration scenarios, piezoelectric sources without PWM converters, and piezoelectric vibration sources connected to a closed-loop P&O converter. The crucial results of this paper demonstrated that the proposed dynamic PEHS model effectively fed low-power electronic loads by directly adjusting the output voltage level to the set voltage, even under different vibration severity levels. As a result, the proposed PEHS dynamic model serves as a guideline for researchers in the development of self-powered sensors, which contributes to understanding sustainable energy alternatives. Full article
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Figure 1

Figure 1
<p>Diagram of the piezoelectric energy harvester for wind-generated vibrations.</p>
Full article ">Figure 2
<p>Essential circuit layout of a single-phase voltage source PWM converter featuring an RC-IGBT.</p>
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<p>A traditional buck-boost converter circuit.</p>
Full article ">Figure 4
<p>The flowchart of the perturb and observe (P&amp;O) MPPT algorithm system.</p>
Full article ">Figure 5
<p>Implementation of the perturb and observe (P&amp;O) MPPT algorithm with a closed-loop controller for a DC-to-DC converter.</p>
Full article ">Figure 6
<p>Piezoelectric wind-energy-harvesting simulation blocks.</p>
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<p>Simulation blocks of the AC–DC converter.</p>
Full article ">Figure 8
<p>Rectifier voltage, current, and vibration force at a vibration frequency of 0.5 Hz.</p>
Full article ">Figure 9
<p>Rectifier voltage, current, and vibration force at a vibration frequency of 1 Hz.</p>
Full article ">Figure 10
<p>Rectifier voltage, current, and vibration force at a vibration frequency of 15 Hz.</p>
Full article ">Figure 11
<p>Rectifier voltage, current, and vibration force at a vibration frequency of 50 Hz.</p>
Full article ">Figure 12
<p>Rectifier voltage, current, and vibration force at a vibration frequency of 150 Hz.</p>
Full article ">Figure 13
<p>Closed-loop buck-boost converter.</p>
Full article ">Figure 14
<p>The performance of the DC-to-DC converter controller with a reference voltage set at 24 V.</p>
Full article ">Figure 15
<p>Wind vibration energy harvester with closed-loop controllers in buck-boost converters (P&amp;O MPPT).</p>
Full article ">Figure 16
<p>DC output voltage of PEHS with a closed-loop P&amp;O MPPT buck-boost converter.</p>
Full article ">Figure 17
<p>Comprehensive diagram of the recommended design for the proposed PEHS.</p>
Full article ">Figure 18
<p>Performance comparison of the suggested PEHS circuit diagram with systems available in the literature from the point of view of real power and open-circuit voltage.</p>
Full article ">Figure 18 Cont.
<p>Performance comparison of the suggested PEHS circuit diagram with systems available in the literature from the point of view of real power and open-circuit voltage.</p>
Full article ">
16 pages, 7481 KiB  
Article
Research on the Control and Modulation Scheme for a Novel Five-Switch Current Source Inverter
by Tao Fu, Jihao Gao, Haiyan Liu and Bo Xia
Energies 2024, 17(15), 3640; https://doi.org/10.3390/en17153640 - 24 Jul 2024
Cited by 1 | Viewed by 751
Abstract
Different from the voltage source inverter (VSI), the current source inverter (CSI) can boost the voltage and eliminate the additional passive filter and dead time. However, the DC-side inductor current is not a real current source and is generated by a DC voltage [...] Read more.
Different from the voltage source inverter (VSI), the current source inverter (CSI) can boost the voltage and eliminate the additional passive filter and dead time. However, the DC-side inductor current is not a real current source and is generated by a DC voltage supply and an inductor. Under different switching states, the DC-side inductor will be charged or discharged, which leads to the DC-side inductor current being discontinuous or increasing. To solve the control problem of the DC-side inductor current of the CSI, a novel single-phase CSI topology with five switching tubes for grid-connected applications is proposed. Firstly, the reference calculation method and the hysteresis loop control scheme for the DC-side inductor current are proposed, and the adjustable and constant DC-side inductor current are obtained. Since the PWM signals cannot be directly implemented to the switching tubes, the modulation strategy for the single-phase CSI is proposed in this paper. Then, an active damping method based on the feedback capacitor voltage is presented to suppress the resonance peak caused by the LC filter on the grid side. Finally, the math model of the AC-side structure is established, and the optimal proportional-resonant controller parameters’ design method is explored by the amplitude–frequency characteristic curves. The simulation and experiment are implemented for the proposed CSI topology. The results show that a high-quality power with a good control performance can be obtained with the proposed CSI topology. Full article
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Figure 1

Figure 1
<p>The topology of the traditional single-phase CSI.</p>
Full article ">Figure 2
<p>Simulation waveforms of DC-side inductor current and load current for traditional CSI. (<b>a</b>) Initial value of <span class="html-italic">i</span><sub>dc</sub> is zero; (<b>b</b>) initial value of <span class="html-italic">i</span><sub>dc</sub> is 20 A.</p>
Full article ">Figure 2 Cont.
<p>Simulation waveforms of DC-side inductor current and load current for traditional CSI. (<b>a</b>) Initial value of <span class="html-italic">i</span><sub>dc</sub> is zero; (<b>b</b>) initial value of <span class="html-italic">i</span><sub>dc</sub> is 20 A.</p>
Full article ">Figure 3
<p>Several improved topologies of CSI. (<b>a</b>) Quasi-Z source, (<b>b</b>) additional switching tube parallel with inductor, (<b>c</b>) buck–boost, (<b>d</b>) two-transistor forward voltage–current converter.</p>
Full article ">Figure 4
<p>Topology of the proposed single-phase grid-connected CSI with five switching tubes.</p>
Full article ">Figure 5
<p>Vector diagram of the AC side in CSI.</p>
Full article ">Figure 6
<p>Hysteresis control block diagram of <span class="html-italic">i</span><sub>dc</sub>.</p>
Full article ">Figure 7
<p>Diagram of switching signals. (<b>a</b>) X = 1; (<b>b</b>) X = 0.</p>
Full article ">Figure 8
<p>Closed-loop control diagram of grid current.</p>
Full article ">Figure 9
<p>Bode plots of <span class="html-italic">G</span><sub>io2is</sub>(<span class="html-italic">s</span>) under different <span class="html-italic">K</span><sub>c</sub>.</p>
Full article ">Figure 10
<p>Bode plots of <span class="html-italic">G</span><sub>close</sub>(<span class="html-italic">s</span>) and <span class="html-italic">G</span><sub>idis2is</sub>(<span class="html-italic">s</span>) under different <span class="html-italic">k</span><sub>r</sub>. (<b>a</b>) <span class="html-italic">G</span><sub>close</sub>(<span class="html-italic">s</span>); (<b>b</b>) <span class="html-italic">G</span><sub>idis2is</sub>(<span class="html-italic">s</span>).</p>
Full article ">Figure 11
<p>Bode plots of <span class="html-italic">G</span><sub>close</sub>(<span class="html-italic">s</span>) and <span class="html-italic">G</span><sub>idis2is</sub>(<span class="html-italic">s</span>) under different <span class="html-italic">k</span><sub>p</sub>. (<b>a</b>) <span class="html-italic">G</span><sub>close</sub>(<span class="html-italic">s</span>); (<b>b</b>) <span class="html-italic">G</span><sub>idis2is</sub>(<span class="html-italic">s</span>).</p>
Full article ">Figure 12
<p>Simulation results under different references of DC-side inductor current. (<b>a</b>) <math display="inline"><semantics> <mrow> <msubsup> <mi>i</mi> <mrow> <mi>dc</mi> </mrow> <mo>*</mo> </msubsup> </mrow> </semantics></math> = 14 A; (<b>b</b>) <math display="inline"><semantics> <mrow> <msubsup> <mi>i</mi> <mrow> <mi>dc</mi> </mrow> <mo>*</mo> </msubsup> </mrow> </semantics></math> = 12.5 A; (<b>c</b>) <math display="inline"><semantics> <mrow> <msubsup> <mi>i</mi> <mrow> <mi>dc</mi> </mrow> <mo>*</mo> </msubsup> </mrow> </semantics></math> = 15.5 A.</p>
Full article ">Figure 13
<p>Simulation results under different capacitor voltage feedback coefficients. (<b>a</b>) <span class="html-italic">K</span><sub>c</sub> = 0; (<b>b</b>) <span class="html-italic">K</span><sub>c</sub> = 0.5.</p>
Full article ">Figure 14
<p>The experimental platform of grid-connected CSI.</p>
Full article ">Figure 15
<p>Experimental results in boost mode. (<b>a</b>) Waveforms; (<b>b</b>) FFT analysis results.</p>
Full article ">Figure 16
<p>Experimental results in buck mode. (<b>a</b>) Waveforms; (<b>b</b>) FFT analysis results.</p>
Full article ">Figure 17
<p>Dynamic experimental waveforms under the change in the reference amplitude for grid current.</p>
Full article ">Figure 18
<p>Dynamic experimental waveforms under the change in the operating mode.</p>
Full article ">
14 pages, 1236 KiB  
Article
Utilizing Aerobic Capacity Data for EDSS Score Estimation in Multiple Sclerosis: A Machine Learning Approach
by Seda Arslan Tuncer, Cagla Danacı, Furkan Bilek, Caner Feyzi Demir and Taner Tuncer
Diagnostics 2024, 14(12), 1249; https://doi.org/10.3390/diagnostics14121249 - 13 Jun 2024
Viewed by 910
Abstract
The Expanded Disability Status Scale (EDSS) is the most popular method to assess disease progression and treatment effectiveness in patients with multiple sclerosis (PwMS). One of the main problems with the EDSS method is that different results can be determined by different physicians [...] Read more.
The Expanded Disability Status Scale (EDSS) is the most popular method to assess disease progression and treatment effectiveness in patients with multiple sclerosis (PwMS). One of the main problems with the EDSS method is that different results can be determined by different physicians for the same patient. In this case, it is necessary to produce autonomous solutions that will increase the reliability of the EDSS, which has a decision-making role. This study proposes a machine learning approach to predict EDSS scores using aerobic capacity data from PwMS. The primary goal is to reduce potential complications resulting from incorrect scoring procedures. Cardiovascular and aerobic capacity parameters of individuals, including aerobic capacity, ventilation, respiratory frequency, heart rate, average oxygen density, load, and energy expenditure, were evaluated. These parameters were given as input to CatBoost, gradient boosting (GBM), extreme gradient boosting (XGBoost), and decision tree (DT) machine learning methods. The most significant EDSS results were determined with the XGBoost algorithm. Mean absolute error, root mean square error, mean square error, mean absolute percent error, and R square values were obtained as 0.26, 0.4, 0.26, 16, and 0.68, respectively. The XGBoost based machine learning technique was shown to be effective in predicting EDSS based on aerobic capacity and cardiovascular data in PwMS. Full article
(This article belongs to the Section Machine Learning and Artificial Intelligence in Diagnostics)
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Figure 1
<p>The process design of the study.</p>
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<p>EEPeak distribution.</p>
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<p>Actual and prediction value comparison chart.</p>
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17 pages, 14190 KiB  
Article
The Impact of Grid Distortion on the Power Conversion Harmonics of AC/DC Converters in the Supraharmonic Range
by Marwa S. Osheba, Abdellatif M. Aboutaleb, Jan Desmet and Jos Knockaert
Electronics 2024, 13(12), 2244; https://doi.org/10.3390/electronics13122244 - 7 Jun 2024
Cited by 1 | Viewed by 810
Abstract
AC/DC converters, controlled by pulse width modulation (PWM) and used as power factor correction (PFC), is considered one of the main contributors to emissions in the range 2 kHz–150 kHz, recently known as the supraharmonic (SH) range. This study looks at the impact [...] Read more.
AC/DC converters, controlled by pulse width modulation (PWM) and used as power factor correction (PFC), is considered one of the main contributors to emissions in the range 2 kHz–150 kHz, recently known as the supraharmonic (SH) range. This study looks at the impact of SH grid distortion on the LF (<2 kHz) and HF (>2 kHz) emission of an AC/DC converter. The PFC boost converter is used as a particular case for validation of the results. It is observed that the AC/DC converters emit additional LF interharmonics and subharmonics when the grid voltage contains interharmonic components in the SH range. A mathematical analysis is provided to study and assess the interference between the SH in the background distortion and the AC/DC converters. Experimental studies are then performed for a PFC boost setup based on dSPACE MicroLabBox for the purposes of validating the mathematical analysis. Full article
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Figure 1

Figure 1
<p>DBR with SH current component flowing from the AC side to the DC side. (<b>a</b>) Schematic of the circuit. (<b>b</b>) The SH current is in the frequency domain on both the AC and DC sides.</p>
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<p>DBR with SH current component flowing from the DC side to the AC side. (<b>a</b>) Schematic of the circuit. (<b>b</b>) The SH current is in the frequency domain on both the AC and DC sides.</p>
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<p>The AC/DC converter DBR is subjected to a SH current component, and the main emission of the AC/DC converter on the AC side contains a SH current from the background.</p>
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<p>The PFC boosts the main emission and the reflection of the main <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>i</mi> </mrow> <mrow> <mi>g</mi> </mrow> </msub> <mfenced separators="|"> <mrow> <msub> <mrow> <mi>f</mi> </mrow> <mrow> <mi>S</mi> <mi>W</mi> </mrow> </msub> </mrow> </mfenced> </mrow> </semantics></math> at the DC side of the DBR.</p>
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<p>The DC side added emissions in the LF range of the PFC to boost DBR reflection on the AC side of the DBR.</p>
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<p>PFC boost. (<b>a</b>) power circuit, (<b>b</b>) control algorithm.</p>
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<p>Experimental setup.</p>
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<p>The simulated output voltage of the PFC boost at <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>R</mi> </mrow> <mrow> <mi>o</mi> </mrow> </msub> <mo>=</mo> <mn>600</mn> <mo> </mo> <mi mathvariant="normal">Ω</mi> </mrow> </semantics></math>.</p>
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<p>The simulated output voltage of the PFC boost <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>R</mi> </mrow> <mrow> <mi>o</mi> </mrow> </msub> <mo>=</mo> <mn>100</mn> <mo> </mo> <mi mathvariant="normal">Ω</mi> </mrow> </semantics></math>.</p>
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<p>Simulated PFC boost inductor current at <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>R</mi> </mrow> <mrow> <mi>o</mi> </mrow> </msub> <mo>=</mo> <mn>600</mn> <mo> </mo> <mi mathvariant="normal">Ω</mi> </mrow> </semantics></math>.</p>
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<p>Simulated PFC boost inductor current <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>R</mi> </mrow> <mrow> <mi>o</mi> </mrow> </msub> <mo>=</mo> <mn>100</mn> <mo> </mo> <mi mathvariant="normal">Ω</mi> </mrow> </semantics></math>.</p>
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<p>Simulated grid voltage and current at the PFC boost input terminals <math display="inline"><semantics> <mrow> <mi>t</mi> <mi>h</mi> <mi>a</mi> <mi>t</mi> <mo>=</mo> <mn>600</mn> <mo> </mo> <mi mathvariant="normal">Ω</mi> </mrow> </semantics></math>.</p>
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<p>Simulated grid voltage and current at the PFC boost input terminals <math display="inline"><semantics> <mrow> <mi>t</mi> <mi>h</mi> <mi>a</mi> <mi>t</mi> <mo>=</mo> <mn>100</mn> <mo> </mo> <mi mathvariant="normal">Ω</mi> </mrow> </semantics></math>.</p>
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<p>Simulation results of case study 1 at <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>R</mi> </mrow> <mrow> <mi>o</mi> </mrow> </msub> <mo>=</mo> <mn>600</mn> <mo> </mo> <mi mathvariant="normal">Ω</mi> </mrow> </semantics></math>, a comparison between a PFC boost converter exposed to a SH free grid voltage and the same PFC boost exposed to a distortion in the grid voltage at 5029 Hz. (<b>a</b>) The grid current, and (<b>b</b>) the inductor current.</p>
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<p>A comparison between a PFC boost converter exposed a SH free grid voltage under different loading conditions. (<b>a</b>) The grid current, and (<b>b</b>) the inductor current.</p>
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<p>A comparison between a PFC boost converter exposed to a distortion in the grid voltage at 5029 Hz under different loading conditions. (<b>a</b>) The grid current, and (<b>b</b>) the inductor current.</p>
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<p>Simulation results of case study 2 at <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>R</mi> </mrow> <mrow> <mi>o</mi> </mrow> </msub> <mo>=</mo> <mn>600</mn> <mo> </mo> <mi mathvariant="normal">Ω</mi> </mrow> </semantics></math>, a comparison between a PFC boost converter exposed to a SH free grid voltage and the same PFC boost exposed to a distortion in the grid voltage at 5038.6 Hz. (<b>a</b>) The grid current, and (<b>b</b>) the inductor current.</p>
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<p>A comparison between a PFC boost converter exposed to a distortion in the grid voltage at 5038.6 Hz under different loading conditions. (<b>a</b>) The grid current, and (<b>b</b>) the inductor current.</p>
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<p>Experimental data of the output voltage of the PFC boost.</p>
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<p>Experimental data of the PFC boost inductor current.</p>
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<p>Experimental data of grid voltage and current at the PFC boost input terminals.</p>
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<p>Case study 1 is a comparison between a PFC boost converter exposed to a SH free grid voltage and the same PFC boost exposed to a distortion in the grid voltage at 5029 Hz. (<b>a</b>) The grid current, and (<b>b</b>) the inductor current.</p>
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<p>Case study 2 is a comparison between a PFC boost exposed to a SH free grid voltage and the same PFC boost exposed to a distortion in the grid voltage at 5038.6 Hz. (<b>a</b>) The grid current, and (<b>b</b>) the inductor current.</p>
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20 pages, 8084 KiB  
Article
Current-Prediction-Controlled Quasi-Z-Source Cascaded Multilevel Photovoltaic Inverter
by Shanshan Lei, Ningzhi Jin and Jiaxin Jiang
Electronics 2024, 13(10), 1824; https://doi.org/10.3390/electronics13101824 - 8 May 2024
Viewed by 983
Abstract
To address problems that traditional two-stage inverters suffer such as high cost, low efficiency, and complex control, this study adopts a quasi-Z-source cascaded multilevel inverter. Firstly, the quasi-Z-source inverter utilizes a unique impedance network to achieve single-stage boost and inversion without requiring a [...] Read more.
To address problems that traditional two-stage inverters suffer such as high cost, low efficiency, and complex control, this study adopts a quasi-Z-source cascaded multilevel inverter. Firstly, the quasi-Z-source inverter utilizes a unique impedance network to achieve single-stage boost and inversion without requiring a dead zone setting. Additionally, its cascaded multilevel structure enables independent control of each power unit structure without capacitor voltage sharing problems. Secondly, this study proposes a current-predictive control strategy to reduce current harmonics on the grid side. Moreover, the feedback model of current and system state is established, and the fast control of grid-connected current is realized with the deadbeat control weighted by the predicted current deviation. And a grid-side inductance parameter identification is added to improve control accuracy. Also, an improved multi-carrier phase-shifted sinusoidal PWM method is adopted to address the issue of switching frequency doubling, which is caused by the shoot-through zero vector in quasi-Z-source inverters. Finally, the problems of switching frequency doubling and high harmonics on the grid side are solved by the improved deadbeat control strategy with an improved MPSPWM method. And a seven-level simulation model is built in MATLAB (2022b) to verify the correctness and superiority of the above theory. Full article
(This article belongs to the Special Issue Power Electronics in Renewable Systems)
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<p>Diagram of the quasi-Z-source cascaded multilevel inverter.</p>
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<p>Equivalent circuit diagram of quasi-Z-source inverter.</p>
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<p>Quasi-Z-source cascaded multilevel inverter topology.</p>
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<p>CMI working states: (<b>a</b>) forward conduction, (<b>b</b>) reverse conduction, (<b>c</b>) forward bypass, (<b>d</b>) reverse bypass.</p>
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<p>System control block diagram.</p>
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<p>Simulation results of the enhanced deadbeat algorithm: (<b>a</b>) <span class="html-italic">K</span> = 0.5; (<b>b</b>) <span class="html-italic">K</span> = 1.0; (<b>c</b>) <span class="html-italic">K</span> = 1.0 and 1.5.</p>
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<p>(<b>a</b>) Simple boost modulation and PS-PWM, (<b>b</b>) multi-carrier phase-shifted SPWM.</p>
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<p>Multi-carrier phase-shifted SPWM modulation schematic.</p>
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<p>Block diagram of the qZS-CMI control strategy.</p>
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<p>Seven-level qZS-CMI system simulation model.</p>
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<p>Inverter output voltage.</p>
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<p>DC link voltage.</p>
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<p>Drive signals.</p>
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<p>Grid current waveform.</p>
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<p>Grid voltage and grid current waveforms.</p>
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<p>Harmonic distortion rate of grid-connected current: (<b>a</b>) traditional control; (<b>b</b>) improved control.</p>
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<p>Filtering inductance estimation.</p>
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<p>Predicted voltage waveform.</p>
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<p>Current waveform when the grid-side inductance changes: (<b>a</b>) grid-connected current; (<b>b</b>) local amplification of current dynamic error.</p>
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<p>Network-side inductance parameter identification waveform: (<b>a</b>) 10 mH; (<b>b</b>) 5 mH; (<b>c</b>) 15 mH.</p>
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<p>Current waveform when input voltage fluctuates: (<b>a</b>) grid-connected current; (<b>b</b>) local amplification of current dynamic error.</p>
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<p>DC link voltage when input voltage fluctuates.</p>
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<p>DC link voltage waveform: (<b>a</b>) DC link voltage waveform; (<b>b</b>) voltage waveform of the capacitor <span class="html-italic">C</span><sub>1</sub>.</p>
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<p>Driving signal waveform.</p>
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<p>Inverter output waveform: (<b>a</b>) CMI output voltage waveform; (<b>b</b>) single HBI module output voltage waveform.</p>
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<p>The grid-connected current waveform: (<b>a</b>) traditional DBC; (<b>b</b>) improved DBC.</p>
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<p>The voltage and current waveform after filtering.</p>
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26 pages, 5647 KiB  
Article
An Optimization Algorithm for Embedded Raspberry Pi Pico Controllers for Solar Tree Systems
by K. Punitha, Akhlaqur Rahman, A. S. Radhamani, Ramakrishna S. S. Nuvvula, Sk. A. Shezan, Syed Riyaz Ahammed, Polamarasetty P. Kumar and Md Fatin Ishraque
Sustainability 2024, 16(9), 3788; https://doi.org/10.3390/su16093788 - 30 Apr 2024
Cited by 5 | Viewed by 2275
Abstract
Solar photovoltaic (PV) systems stand out as a promising solution for generating clean, carbon-free energy. However, traditional solar panel installations often require extensive land resources, which could become scarce as the population grows. To address this challenge, innovative approaches are needed to maximize [...] Read more.
Solar photovoltaic (PV) systems stand out as a promising solution for generating clean, carbon-free energy. However, traditional solar panel installations often require extensive land resources, which could become scarce as the population grows. To address this challenge, innovative approaches are needed to maximize solar power generation within limited spaces. One promising concept involves the development of biological tree-like structures housing solar panels. These “solar trees” mimic the arrangement of branches and leaves found in natural trees, following patterns akin to phyllotaxy, which correlates with the Fibonacci sequence and golden ratio. By adopting an alternative 1:3 phyllotaxy pattern, three solar panels can be efficiently arranged along the stem of the solar tree structure, each rotated at a 120-degree displacement. Optimizing the performance of solar trees requires effective maximum power point tracking (MPPT), a crucial process for extracting the maximum available power from solar panels to enhance the overall efficiency. In this study, a novel metaheuristic algorithm called horse herd optimization (HHO) is employed for MPPT in solar tree applications. Moreover, to efficiently manage the generated power, a cascaded buck–boost converter is utilized. This converter is capable of adjusting the DC voltage levels to match the system requirements within a single topology. The algorithm is implemented using MATLAB and embedded within a Raspberry Pi Pico controller, which facilitates the generation of pulse-width modulation (PWM) signals to control the cascaded buck–boost converter. Through extensive validation, this study confirms the effectiveness of the proposed HHO algorithm integrated into the Raspberry Pi Pico controller for optimizing solar trees under various shading conditions. In essence, this research highlights the potential of solar tree structures coupled with advanced MPPT algorithms and power management systems to maximize solar energy utilization, offering a sustainable solution for clean energy generation within limited land resources. Full article
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<p>Circuit diagram.</p>
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<p>System block diagram.</p>
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<p>(<b>a</b>) Solar Tree front and top view; (<b>b</b>) Flowchart of Solar Tree.</p>
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<p>(<b>a</b>) Solar Tree front and top view; (<b>b</b>) Flowchart of Solar Tree.</p>
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<p>Cascaded buck-boost converter circuit diagram.</p>
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<p>Board layout of Raspberry Pi Pico Controller.</p>
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<p>Characteristics of HHOA.</p>
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<p>Flowchart of HHOA.</p>
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<p>Characteristics curves of three Solar panels connected in series.</p>
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<p>Characteristics curves of three Solar panels connected in parallel.</p>
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<p>Characteristics curve under uniform irradiation for all 3 PV modules.</p>
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<p>DC-DC boost converter’s Duty cycle.</p>
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<p>Converter’s current waveforms—input side and output side.</p>
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<p>Converter’s voltage waveforms—Input Side and Output Side.</p>
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<p>Converter’s power waveforms—Input Side and Output Side.</p>
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<p>Solar Panel’s Characteristics Curves under partial shading.</p>
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<p>Duty cycle of converter.</p>
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<p>Converter’s Current waveforms—Output side and input side.</p>
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<p>Converter’s Voltage waveforms—Output side and input side.</p>
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<p>Converter’s Power waveforms—Output side and input side.</p>
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<p>Characteristics Waveforms of solar panel under partial shading.</p>
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<p>Duty cycle of converter.</p>
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<p>Converter’s Current waveforms—Output side and input side.</p>
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<p>Converter’s Voltage waveform—Output side and input side.</p>
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<p>Converter’s Power waveforms—Output side and input side.</p>
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<p>Converter’s Power waveforms—Hardware setup.</p>
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<p>(<b>a</b>) Scope 4 V, (<b>b</b>) Scope 8 V.</p>
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22 pages, 7350 KiB  
Article
A Symmetric Sixth-Order Step-Up Converter with Asymmetric PWM Achieved with Small Energy Storage Components
by Iván Dueñas-García, Julio C. Rosas-Caro, Hector R. Robles-Campos, Johnny Posada, Jesus E. Valdez-Resendiz, Antonio Valderrabano-Gonzalez, Hossam A. Gabbar and Bhanu Babaiahgari
Symmetry 2024, 16(4), 460; https://doi.org/10.3390/sym16040460 - 10 Apr 2024
Cited by 1 | Viewed by 1137
Abstract
This research explores an improved operation of a recently studied converter, the so-called two-phase sixth-order boost converter (2P6OBC). The converter consists of a symmetric design of power stations followed by an LC filter; its improved operation incorporates an asymmetric pulse width modulation (PWM) [...] Read more.
This research explores an improved operation of a recently studied converter, the so-called two-phase sixth-order boost converter (2P6OBC). The converter consists of a symmetric design of power stations followed by an LC filter; its improved operation incorporates an asymmetric pulse width modulation (PWM) scheme for transistor switching, sometimes known as an interleaved PWM approach. The new operation leads to improved performance for the 2P6OBC. Along with studying the 2P6OBC, one of the contributions of this research is providing design equations for the converter and comparing it versus the interleaved (or multiphase) boost converter, known for its competitiveness and advantages; the single-phase boost topology was also included in the comparison. The comparison consisted of a design scenario where all converters must achieve the same power conversion with an established maximum switching ripple, and then the stored energy in passive components is compared. Although the 2P6OBC requires a greater number of components, the total amount of stored energy is smaller. It is known that the stored energy is related to the size of the passive components. Still, the article includes a discussion of this topic. The new operation of the converter offers more streamlined, cost-effective, and efficient alternatives for a range of applications within power electronics. The final design of the 2P6OBC required only 68% of the stored energy in inductors compared to the multiphase boost converter, and 60% of the stored energy in capacitors. This result is outstanding, considering that the multiphase boost converter is a very competitive topology. Experimental results are provided to validate the proposed concept. Full article
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<p>(<b>a</b>) Traditional boost converter with a single inductor, (<b>b</b>) boost converter with two interleaved phases.</p>
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<p>The two-phase sixth-order converter under study.</p>
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<p>(<b>a</b>) Comparators utilized for the PWM configuration, (<b>b</b>) significant signals associated with the PWM configuration.</p>
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<p>Equivalent circuit representations based on the switching states of the previous operation: (<b>a</b>) [0, 0], (<b>b</b>) [1, 1].</p>
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<p>Circuital average dynamic model (1)–(6).</p>
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<p>(<b>a</b>) Comparators utilized for the PWM configuration, (<b>b</b>) significant signals associated with the PWM configuration.</p>
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<p>Equivalent circuit representations based on the switching states of the new operation: (<b>a</b>) [0, 0], (<b>b</b>) [0, 1], (<b>c</b>) [1, 0], (<b>d</b>) [1, 1].</p>
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<p>Equivalent circuit representation when the switching state is [0, 0].</p>
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<p>Equivalent circuit representation when the switching state is [0, 1].</p>
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<p>Equivalent circuit representation when the switching state is [1, 0].</p>
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<p>Equivalent circuit representation when the switching state is [1, 1].</p>
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<p>A design with the traditional boost (<span class="html-italic">L</span> = 520 μH, <span class="html-italic">C</span> = 80 μF).</p>
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<p>The design solution with the interleaved boost topology features inductors of 350 μH and a capacitor of 30 μF.</p>
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<p>The studied converter with all inductors <span class="html-italic">L</span><sub>1</sub> <span class="html-italic">= L</span><sub>2</sub> <span class="html-italic">= L</span><sub>3</sub> <span class="html-italic">=</span> 275 μH and all capacitors of the same capacitance. <span class="html-italic">C</span><sub>1</sub>, <span class="html-italic">C</span><sub>2</sub>, and <span class="html-italic">C</span><sub>3</sub> are each 10 μF.</p>
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<p>Schematic diagram of the traditional boost converter used for simulation purposes.</p>
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<p>Schematic diagram of the traditional boost converter used for simulation purposes.</p>
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<p>Schematic diagram of the traditional boost converter used for simulation purposes.</p>
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<p>Schematic diagram of the 2P6OBC converter used for simulation.</p>
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<p>Input current ripple comparison for all three converters.</p>
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<p>Output voltage dynamic responses to changes in the load from 150 Ω to 75 Ω.</p>
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<p>Input current dynamic responses to changes in the load from 150 Ω to 75 Ω.</p>
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<p>The voltage across the switch s1 (pink), the inductor current (mustard color), current at the input port (green), and voltage at the output pot (blue), with <span class="html-italic">D</span> = 0.6.</p>
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<p>The voltage across the switch s1 (pink), the inductor current (mustard color), current at the input port (green), and voltage at the output pot (blue), with <span class="html-italic">D</span> = 0.55.</p>
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<p>The voltage across the switch s1 (pink), the inductor current (mustard color), current at the input port (green), and voltage at the output pot (blue), with <span class="html-italic">D</span> = 0.45.</p>
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<p>Efficiencies calculated for the three compared topologies.</p>
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17 pages, 42940 KiB  
Article
Enhancing Electric Vehicle Charger Performance with Synchronous Boost and Model Predictive Control for Vehicle-to-Grid Integration
by Youness Hakam, Ahmed Gaga, Mohamed Tabaa and Benachir El hadadi
Energies 2024, 17(7), 1787; https://doi.org/10.3390/en17071787 - 8 Apr 2024
Cited by 5 | Viewed by 1332
Abstract
This paper investigates optimizing the power exchange between electric vehicles (EVs) and the grid, with a specific focus on the DC-DC converters utilized in vehicle-to-grid (V2G) systems. It specifically explores using model predictive control (MPC) in synchronous boost converters to enhance efficiency and [...] Read more.
This paper investigates optimizing the power exchange between electric vehicles (EVs) and the grid, with a specific focus on the DC-DC converters utilized in vehicle-to-grid (V2G) systems. It specifically explores using model predictive control (MPC) in synchronous boost converters to enhance efficiency and performance. Through experiments and simulations, this paper shows that replacing diodes with SIC MOSFETs in boost converters significantly improves efficiency, particularly in synchronous mode, by minimizing the deadtime of SIC MOSFETs during switching. Additionally, this study evaluates MPC’s effectiveness in controlling boost converters, highlighting its advantages over traditional control methods. Real-world validations further validate the robustness and applicability of MPC in V2G systems. This study utilizes TMS320F28379D, one of Texas Instruments’ leading digital signal processors, enabling the implementation of MPC with a high PWM frequency of up to 200 MHz. This processor features dual 32-bit CPUs and a 16-bit ADC, allowing for high-resolution readings from sensors. Leveraging digital signal processing technologies and advanced electronic circuits, this study advances the development of high-performance boost converters, achieving power outputs of up to 48 watts and output voltages of 24 volts. Electronic circuits (PCB boards) have been devised, implemented, and evaluated to showcase their significance in advancing efficient V2G integration. Full article
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<p>V2X system.</p>
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<p>Boost synchronous converter.</p>
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<p>PID controller diagram.</p>
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<p>A boost synchronous converter with a PID controller.</p>
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<p>Plant identification for closed loop.</p>
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<p>Result of PID tuning.</p>
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<p>Simulation of boost synchronous converter in MATLAB-Smulink.</p>
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<p>Diagram of DC-DC boost synchronous converter.</p>
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<p>Schematic of boost synchronouns converter with MPC under MATLAB-Simulink.</p>
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<p>Schematic of hardware in the loop.</p>
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<p>Synoptic schema of the realized boost synchronous converter.</p>
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<p>Circuit board of boost synchronous converter.</p>
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<p>PCB circuit board of boost synchronous converter.</p>
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<p>Implemented system in real world.</p>
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<p>Acquisition program and processing data through DSPF28379D under MATLAB-Simulink for PID.</p>
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<p>Acquisition program and processing data through DSPF28379D under MATLAB-Simulink for MPC.</p>
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<p>Output voltage with PID controller.</p>
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<p>Output voltage with MPC controller.</p>
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<p>Current of inductor with PID controller.</p>
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<p>Current of inductor with MPC controller.</p>
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<p>Output voltage PWM signals for both MOSFETS used PID controller.</p>
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<p>Output voltage and PWM signals for both MOSFETs using MPC controller.</p>
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26 pages, 27856 KiB  
Article
Novel Space-Vector PWM Schemes for Enhancing Efficiency and Decoupled Control in Quasi-Z-Source Inverters
by Ivan Grgić, Mateo Bašić, Dinko Vukadinović and Ivan Marinović
Energies 2024, 17(6), 1387; https://doi.org/10.3390/en17061387 - 13 Mar 2024
Cited by 3 | Viewed by 1134
Abstract
This paper investigates the development of pulse width modulation (PWM) schemes for three-phase quasi-Z-source inverters (qZSIs). These inverters are notable for their voltage boost capability, built-in short-circuit protection, and continuous input current, making them suitable for low-voltage-fed applications like photovoltaic or fuel cell-based [...] Read more.
This paper investigates the development of pulse width modulation (PWM) schemes for three-phase quasi-Z-source inverters (qZSIs). These inverters are notable for their voltage boost capability, built-in short-circuit protection, and continuous input current, making them suitable for low-voltage-fed applications like photovoltaic or fuel cell-based systems. Despite their advantages, qZSIs confront challenges such as increased control complexity and a larger number of passive components compared to traditional voltage source inverters (VSIs). In addition, most existing PWM schemes for qZSIs lack the capability for independent control of the amplitude modulation index and duty cycle, which is essential in closed-loop applications. This study introduces innovative space-vector PWM (SVPWM) schemes, addressing issues of independent control, synchronization, and unintentional short-circuiting in qZSIs. It evaluates several established continuous and discontinuous PWM schemes, and proposes two novel decoupled SVPWM-based schemes that integrate dead time and in which the shoot-through occurrence is synchronized with the beginning of the zero switching state. These novel schemes are designed to reduce switching losses and improve qZSI controllability. Experimental validation is conducted using a custom-developed electronic circuit board that enables the implementation of a range of PWM schemes, including the newly proposed ones. The obtained results indicate that the proposed PWM schemes can offer up to 6.8% greater efficiency and up to 7.5% reduced voltage stress compared to the closest competing PWM scheme from the literature. In addition, they contribute to reducing the electromagnetic interference and thermal stress of the related semiconductor switches. Full article
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<p>Standalone configuration of the qZSI.</p>
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<p>Equivalent circuits of the qZSI: non-ST state (<b>a</b>) and ST state (<b>b</b>).</p>
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<p>Waveforms of the SBSVM (<b>a</b>) and the ZSVM6 (<b>b</b>), with <span class="html-italic">M<sub>a</sub></span> = 0.7, <span class="html-italic">M<sub>f</sub></span> = 10 (ST states are denoted by vertical stripes, with different colors denoting different phase legs).</p>
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<p>Waveforms of the SBDSV (<b>a</b>) and the SBMSV (<b>b</b>), with <span class="html-italic">M<sub>a</sub></span> = 0.7, <span class="html-italic">M<sub>f</sub></span> = 10 (ST states are denoted by vertical stripes, with different colors denoting different phase legs).</p>
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<p>Waveforms of the decoupled SBDSV (<b>a</b>) and the proposed DSV2ST (<b>b</b>), with <span class="html-italic">M<sub>a</sub></span> = 0.7, <span class="html-italic">M<sub>f</sub></span> = 10, <span class="html-italic">D</span><sub>0</sub> = 0.2 (ST states are denoted by vertical stripes).</p>
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<p>PWM pulses generation for the proposed DSV2ST scheme.</p>
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<p>Waveforms of the decoupled SBMSV (<b>a</b>) and the proposed DSV1ST (<b>b</b>), with <span class="html-italic">M<sub>a</sub></span> = 0.7, <span class="html-italic">M<sub>f</sub></span> = 10, <span class="html-italic">D</span><sub>0</sub> = 0.2 (ST states are denoted by vertical stripes, with different colors denoting different phase legs).</p>
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<p>PWM pulses generation for the proposed DSV1ST scheme.</p>
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<p>Laboratory setup of the considered qZSI system (<b>a</b>) and the qZSI bridge with the corresponding gate drivers and electronic circuit board (<b>b</b>).</p>
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<p>Logic diagram of the PWM pulses generation.</p>
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<p>Photo of the electronic circuit board utilized for PWM pulses generation.</p>
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<p>System efficiency as a function of the duty cycle for the different switching frequencies and inverter power of 1000 W (<b>a</b>), 2000 W (<b>b</b>), and 3000 W (<b>c</b>).</p>
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<p>Inverter bridge input voltage as a function of the duty cycle for the different switching frequencies and inverter power of 1000 W (<b>a</b>), 2000 W (<b>b</b>), and 3000 W (<b>c</b>).</p>
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<p>Inductor current ripple percentage as a function of the duty cycle for the different switching frequencies and inverter power of 1000 W (<b>a</b>), 2000 W (<b>b</b>), and 3000 W (<b>c</b>).</p>
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<p>Output current THD as a function of the duty cycle for the different switching frequencies and inverter power of 1000 W (<b>a</b>), 2000 W (<b>b</b>), and 3000 W (<b>c</b>).</p>
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<p>Experimental waveforms of the considered continuous PWM schemes: ZSPWM (<b>a</b>), zoomed ZSPWM (<b>b</b>), ZSVM6 (<b>c</b>), and zoomed ZSVM6 (<b>d</b>).</p>
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<p>Experimental waveforms of the considered discontinuous PWM schemes with one ST state per switching period: dec. SBMSV (<b>a</b>), zoomed dec. SBMSV (<b>b</b>), DSV1ST (<b>c</b>), and zoomed DSV1ST (<b>d</b>).</p>
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<p>Experimental waveforms of the considered discontinuous PWM schemes with two ST states per switching period: dec. SBDSV (<b>a</b>), zoomed dec. SBDSV (<b>b</b>), DSV2ST (<b>c</b>), and zoomed DSV2ST (<b>d</b>).</p>
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<p>Current stress of the considered PWM schemes: ZSPWM (<b>a</b>), ZSVM6 (<b>b</b>), dec. SBDSV (<b>c</b>), dec. SBMSV (<b>d</b>), DSV2ST (<b>e</b>), and DSV1ST (<b>f</b>).</p>
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<p>Thermal stress of the considered PWM schemes: ZSPWM (<b>a</b>), ZSVM6 (<b>b</b>), dec. SBDSV (<b>c</b>), dec. SBMSV (<b>d</b>), DSV2ST (<b>e</b>), and DSV1ST (<b>f</b>).</p>
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19 pages, 12055 KiB  
Article
A Wide-Range Negative Output DC-DC Converter with Adaptive Drive Technique for Active-Matrix OLED Microdisplays
by Yue Liu, Hong Cai and Bohua Zhao
Electronics 2024, 13(3), 564; https://doi.org/10.3390/electronics13030564 - 30 Jan 2024
Cited by 1 | Viewed by 1330
Abstract
This paper presents a DC-DC converter with wide-range negative output for active-matrix organic light-emitting diode (AMOLED). The generated negative voltage Vout is connected to the negative terminal of the organic light-emitting diode (OLED), and the luminous brightness is adjusted by [...] Read more.
This paper presents a DC-DC converter with wide-range negative output for active-matrix organic light-emitting diode (AMOLED). The generated negative voltage Vout is connected to the negative terminal of the organic light-emitting diode (OLED), and the luminous brightness is adjusted by changing the value of Vout. The negative output voltage of the DC-DC converter is regulated by a Buck–Boost topology structure with a dual-loop control (DLC) system composed of a voltage loop and a current loop. The proposed compensatory peak-current-sensing technique (PCST) and switch MOSFETs adaptive drive technique (ADT) successfully support the implementation of the converter topology and enable the converter to work in continuous conduction mode (CCM). In addition, with the DLC system, the converter can guarantee a negative output voltage that enables both a fast transient response such as excellent load/line regulation, and a small output voltage ripple of the pulse width modulation (PWM) control. The proposed chip is implemented in a 0.18 μm CMOS process that operates at an operating frequency of 2 MHz with a maximum efficiency of 85.82%. The output voltage ripple is 1.5 mV at typical loading of Vout=4 V and Iout=100 mA. Full article
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<p>Block diagram of Buck–Boost system (* represents modules powered by <math display="inline"><semantics> <mrow> <mn>1.8</mn> <mo> </mo> <mi mathvariant="normal">V</mi> </mrow> </semantics></math> power supply).</p>
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<p>Small-signal model for peak-current mode control.</p>
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<p>PI controller.</p>
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<p>Error amplifier schematic diagram.</p>
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<p>Current sensing module schematic diagram.</p>
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<p>Sawtooth wave oscillator schematic diagram: (<b>a</b>) threshold voltage generation circuit; (<b>b</b>) charge–discharge control circuit.</p>
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<p>PWM comparator schematic diagram.</p>
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<p>Power-stage switch adaptive drive technique scheme.</p>
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<p>The schematic diagram of the dead-time control circuit.</p>
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<p>Waveform diagram of dead-time control circuit.</p>
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<p>The schematic diagram of the bootstrap circuit.</p>
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<p>The waveform diagram of the bootstrap circuit.</p>
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<p>The schematic diagram of the clamp and level-down circuit.</p>
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<p>Pulse signal generation circuit schematic.</p>
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<p>Pulse signal waveform diagram.</p>
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<p>Overall chip layout.</p>
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<p>Typical loading condition post-layout simulation results: (<b>a</b>) start-up results; (<b>b</b>) output voltage ripple results.</p>
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<p>Linear regulation simulation results.</p>
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<p>Power efficiency.</p>
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<p>Maximum loading condition Monte Carlo pre-layout simulation start-up results.</p>
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<p>Maximum loading condition Monte Carlo pre-layout simulation output voltage ripple results.</p>
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<p>Typical loading condition PVT post-layout simulation results: (<b>a</b>) start-up results; (<b>b</b>) output voltage ripple results.</p>
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22 pages, 9970 KiB  
Article
Integrated Control and Optimization for Grid-Connected Photovoltaic Systems: A Model-Predictive and PSO Approach
by Chaymae Boubii, Ismail El Kafazi, Rachid Bannari, Brahim El Bhiri, Saleh Mobayen, Anton Zhilenkov and Badre Bossoufi
Energies 2023, 16(21), 7390; https://doi.org/10.3390/en16217390 - 1 Nov 2023
Cited by 4 | Viewed by 1578
Abstract
To propel us toward a greener and more resilient future, it is imperative that we adopt renewable sources and implement innovative sustainable solutions in response to the escalating energy crisis. Thus, renewable energies have emerged as a viable solution to the global energy [...] Read more.
To propel us toward a greener and more resilient future, it is imperative that we adopt renewable sources and implement innovative sustainable solutions in response to the escalating energy crisis. Thus, renewable energies have emerged as a viable solution to the global energy crisis, with photovoltaic energy being one of the prominent sources in this regard. This paper represents a significant step in the desired direction by focusing on detailed, comprehensive dynamic modeling and efficient control of photovoltaic (PV) systems as grid-connected energy sources. The ultimate goal is to enhance system reliability and ensure high power quality. The behavior of the suggested photovoltaic system is tested under varying sun radiation conditions. The PV system is complemented by a boost converter and a three-phase pulse width modulation (PWM) inverter, with MATLAB software employed for system investigation. This research paper enhances photovoltaic (PV) system performance through the integration of model-predictive control (MPC) with a high-gain DC–DC converter. It improves maximum power point tracking (MPPT) efficiency in response to the variability of solar energy by combining MPC with the traditional incremental conductance (IN-C) method. Additionally, the system incorporates a DC–AC converter for three-phase pulse width modulation, which is also controlled by predictive control technology supported by Particle Swarm Optimization (PSO) to further enhance performance. PSO was selected due to its capability to optimize complex systems and its proficiency in handling nonlinear functions and multiple variables, making it an ideal choice for improving MPC control performance. The simulation results demonstrate the system’s ability to maintain stable energy production despite variations in solar irradiation levels, thus highlighting its effectiveness. Full article
(This article belongs to the Section A2: Solar Energy and Photovoltaic Systems)
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<p>The PV system.</p>
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<p>The single-diode model of PV panel.</p>
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<p>Solar Cell I-V and P-V Curves at Various Irradiances.</p>
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<p>PV panel with Boost converter.</p>
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<p>The proposed algorithm for MPPT controller using MPC method.</p>
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<p>DC–AC inverter.</p>
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<p>DC–AC Inverter controlled by MPC&amp;PSO.</p>
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<p>The flow chart of PSO.</p>
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<p>The variation in irradiation with temperature fixed at 25 °C.</p>
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<p>Simulation of PV system in MATLAB/Simulink.</p>
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<p>The overall diagram of the proposed PV system.</p>
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<p>PV voltage.</p>
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<p>Boost voltage.</p>
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<p>Current produced by part A.</p>
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<p>Active and reactive powers produced by part A.</p>
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<p>Current and voltage produced by part A.</p>
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<p>Voltage produced after the transformer 0.26/25 kV.</p>
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<p>Voltage produced after the transformer 0.26/25 kV.</p>
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<p>Active and reactive powers produced after the transformer 0.26/25 kV.</p>
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<p>Current and voltage produced after the transformer 0.26/25 kV.</p>
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<p>Current and voltage produced after the transformer 0.26/25 kV.</p>
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<p>Voltage produced after the transformer 25/120 kV.</p>
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<p>Voltage produced after the transformer 25/120 kV.</p>
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<p>Active and reactive powers produced after the transformer 25/120 kV.</p>
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<p>Current and voltage produced after the transformer 25/120 kV.</p>
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<p>Current and voltage produced after the transformer 25/120 kV.</p>
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19 pages, 3527 KiB  
Article
An Interleaved Battery Charger Circuit for a Switched Capacitor Inverter-Based Standalone Single-Phase Photovoltaic Energy Management System
by Manesh Patel and Zhongfu Zhou
Energies 2023, 16(20), 7155; https://doi.org/10.3390/en16207155 - 19 Oct 2023
Cited by 4 | Viewed by 1408
Abstract
A single-phase bidirectional DC/DC battery charger with a P&O MPPT current control strategy for a standalone energy management system has been integrated with an interleaved switched capacitor DC/AC inverter with an RMS feedback phase-shifted unipolar sinusoidal PWM control strategy. In the published literature, [...] Read more.
A single-phase bidirectional DC/DC battery charger with a P&O MPPT current control strategy for a standalone energy management system has been integrated with an interleaved switched capacitor DC/AC inverter with an RMS feedback phase-shifted unipolar sinusoidal PWM control strategy. In the published literature, P&O MPPT control is used to drive a boost converter connected in parallel to a battery charger; this modified strategy combines a P&O MPPT algorithm with current control to drive an interleaving buck-boost battery charger. This battery charger circuit is connected in parallel to a closed loop controlled interleaved inverter that feeds the AC home load. MATLAB/Simulink based simulation circuit was developed and used to validate the successful integration of the interleaved battery charger with the global system. To do this, the system is tested with varying input conditions of irradiance and temperature. The system’s response to these variable inputs is monitored and analysed. The simulation results show the proposed method is effective for standalone battery-based PV systems. The system provides a more efficient and faster response compared with both an interleaved and non-interleaved voltage-controlled battery charger circuit that is also integrated with the global system. This battery charger control strategy is also shown to protect the battery from over-charging as well as discharging below 25%, which can improve and protect the long-term battery performance. Compared with novel industry approaches, the proposed system is simpler by nature due to the reduced number of conversions and therefore a reduced number of components which provides economic advantages. Full article
(This article belongs to the Section A2: Solar Energy and Photovoltaic Systems)
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<p>Overall system configuration.</p>
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<p>I-V and P-V characteristics of PV array.</p>
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<p>Optimal battery charging stages (Blue—Voltage, Red—Current).</p>
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<p>Bidirectional buck-boost DC/DC converter topology.</p>
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<p>(<b>a</b>) P&amp;O MPPT algorithm and current control strategy. (<b>b</b>) State of charge controller. (<b>c</b>) DC/DC battery charging circuit.</p>
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<p>P&amp;O MPPT algorithm.</p>
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<p>Control circuit gate pulse (<b>a</b>) G1 (<b>b</b>) G3 (<b>c</b>) G2 (<b>d</b>) G4.</p>
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<p>Variable input conditions (<b>a</b>) Irradiance (<b>b</b>) Temperature.</p>
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<p>Inductor current (L5—blue and L6—orange).</p>
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<p>Inductor current zoomed (L5—blue and L6—orange).</p>
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<p>Battery state of charge—percentage.</p>
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<p>Battery current (blue) and battery voltage (red).</p>
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<p>System power output (battery—red, PV—blue).</p>
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<p>DC link voltage—interleaved current control (blue), interleaved voltage control (red), non-interleaved voltage control (yellow).</p>
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18 pages, 2943 KiB  
Article
State Feedback with Integral Control Circuit Design of DC-DC Buck-Boost Converter
by Humam Al-Baidhani, Abdullah Sahib and Marian K. Kazimierczuk
Mathematics 2023, 11(9), 2139; https://doi.org/10.3390/math11092139 - 3 May 2023
Cited by 8 | Viewed by 4506
Abstract
The pulse-with modulated (PWM) dc-dc buck-boost converter is a non-minimum phase system, which requires a proper control scheme to improve the transient response and provide constant output voltage during line and load variations. The pole placement technique has been proposed in the literature [...] Read more.
The pulse-with modulated (PWM) dc-dc buck-boost converter is a non-minimum phase system, which requires a proper control scheme to improve the transient response and provide constant output voltage during line and load variations. The pole placement technique has been proposed in the literature to control this type of power converter and achieve the desired response. However, the systematic design procedure of such control law using a low-cost electronic circuit has not been discussed. In this paper, the pole placement via state-feedback with an integral control scheme of inverting the PWM dc-dc buck-boost converter is introduced. The control law is developed based on the linearized power converter model in continuous conduction mode. A detailed design procedure is given to represent the control equation using a simple electronic circuit that is suitable for low-cost commercial applications. The mathematical model of the closed-loop power converter circuit is built and simulated using SIMULINK and Simscape Electrical in MATLAB. The closed-loop dc-dc buck-boost converter is tested under various operating conditions. It is confirmed that the proposed control scheme improves the power converter dynamics, tracks the reference signal, and maintains regulated output voltage during abrupt changes in input voltage and load current. The simulation results show that the line variation of 5 V and load variation of 2 A around the nominal operating point are rejected with a maximum percentage overshoot of 3.5% and a settling time of 5.5 ms. Full article
(This article belongs to the Special Issue Dynamic Modeling and Simulation for Control Systems, 2nd Edition)
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<p>(<b>a</b>) The inverting dc-dc buck-boost converter circuit. (<b>b</b>) The equivalent circuit of the non-ideal buck-boost converter in CCM.</p>
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<p>The block diagram of the state feedback with integral control system.</p>
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<p>The unit step response of the compensated dc-dc buck-boost converter.</p>
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<p>MATLAB/SIMULINK model of state feedback with integral control system of inverting dc-dc buck-boost converter.</p>
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<p>Schematic of state-feedback with integral controlled PWM dc-dc buck-boost converter circuit.</p>
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<p>Flowchart of state-feedback with integral control design of dc-dc buck-boost converter.</p>
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<p>Steady-state waveforms of (<b>a</b>) MATLAB/SIMULINK model and (<b>b</b>) Simscape Electrical circuit of the state feedback with integral control of PWM dc-dc buck-boost converter in CCM. The figures show the control input <span class="html-italic">u</span>, ramp voltage <span class="html-italic">V<sub>T</sub></span>, gate-to-source voltage <span class="html-italic">v<sub>GS</sub></span>, inductor current <span class="html-italic">i<sub>L</sub></span>, and output voltage <span class="html-italic">v<sub>O</sub></span>.</p>
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<p>The tracking performance of the state feedback with integral control of inverting dc-dc buck-boost converter under line disturbance. (<b>a</b>) The output voltage response <span class="html-italic">v<sub>O</sub></span> when the input voltage <span class="html-italic">v<sub>I</sub></span> changes from 28 V to 33 V during the time interval 20 ≤ <span class="html-italic">t</span> ≤ 32.5 ms. (<b>b</b>) The output voltage response <span class="html-italic">v<sub>O</sub></span> when the input voltage <span class="html-italic">v<sub>I</sub></span> changes from 28 V to 23 V during the time interval 20 ≤ <span class="html-italic">t</span> ≤ 32.5 ms.</p>
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<p>The tracking performance of the state feedback with integral control of inverting dc-dc buck-boost converter under load disturbance. (<b>a</b>) The output voltage response <span class="html-italic">v<sub>O</sub></span> when the load current <span class="html-italic">i<sub>O</sub></span> changes from 4 A to 6 A during the time interval 20 ≤ <span class="html-italic">t</span> ≤ 32.5 ms. (<b>b</b>) The output voltage response <span class="html-italic">v<sub>O</sub></span> when the load current <span class="html-italic">i<sub>O</sub></span> changes from 4 A to 2.5 A during the time interval 20 ≤ <span class="html-italic">t</span> ≤ 32.5 ms.</p>
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<p>The output voltage response <span class="html-italic">v<sub>O</sub></span> of the state feedback with integral control of PWM dc-dc buck-boost converter in CCM during a time-varying reference voltage <span class="html-italic">V<sub>r</sub></span>. The upper sub-figure shows the step changes in reference voltage <span class="html-italic">V<sub>r</sub></span>. The lower sub-figure shows the tracking performance of the output voltage response <span class="html-italic">v<sub>O</sub></span> with respect to the desired trajectory <span class="html-italic">v<sub>d</sub></span>.</p>
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