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Keywords = AC/DC charger in electric vehicle

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18 pages, 4650 KiB  
Article
Integrating Battery Energy Storage Systems for Sustainable EV Charging Infrastructure
by Amanda Monteiro, A. V. M. L. Filho, N. K. L. Dantas, José Castro, Ayrlw Maynyson C. Arcanjo, Pedro A. C. Rosas, Pérolla Rodrigues, Augusto C. Venerando, Newmar Spader, Mohamed A. Mohamed, Adrian Ilinca and Manoel H. N. Marinho
World Electr. Veh. J. 2025, 16(3), 147; https://doi.org/10.3390/wevj16030147 - 4 Mar 2025
Viewed by 246
Abstract
The transition to a low-carbon energy matrix has driven the electrification of vehicles (EVs), yet charging infrastructure—particularly fast direct current (DC) chargers—can negatively impact distribution networks. This study investigates the integration of Battery Energy Storage Systems (BESSs) with the power grid, focusing on [...] Read more.
The transition to a low-carbon energy matrix has driven the electrification of vehicles (EVs), yet charging infrastructure—particularly fast direct current (DC) chargers—can negatively impact distribution networks. This study investigates the integration of Battery Energy Storage Systems (BESSs) with the power grid, focusing on the E-Lounge project in Brazil as a strategy to mitigate these impacts. The results demonstrated a 21-fold increase in charging sessions and an energy consumption growth from 0.6 MWh to 10.36 MWh between June 2023 and March 2024. Compared to previous findings, which indicated the need for more robust systems, the integration of a 100 kW/138 kWh BESS with DC fast chargers (60 kW) and AC chargers (22 kW) proved effective in reducing peak demand, optimizing energy management, and enhancing grid stability. These findings confirm the critical role of BESSs in establishing a sustainable EV charging infrastructure, demonstrating improvements in power quality and the mitigation of grid impacts. The results presented in this study stem from a project approved under the Research and Development program of the Brazilian Electricity Regulatory Agency (ANEEL) through strategic call No. 022/2018. This initiative aimed to develop a modular EV charging infrastructure for fleet vehicles in Brazil, ensuring minimal impact on the distribution network. Full article
(This article belongs to the Special Issue Battery Management System in Electric and Hybrid Vehicles)
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Figure 1
<p>Main components of the E-Lounge.</p>
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<p>E-Lounge single-line diagram.</p>
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<p>EDP E-Lounge charging stations (conceptual and deployment).</p>
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<p>Flowchart of applications.</p>
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<p>Operation data.</p>
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<p>BESS operation in demand control.</p>
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<p>BESS operation in power control of electric vehicle chargers.</p>
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<p>Operation chart, BESS recharge control.</p>
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<p>Voltage measurements at the point of connection.</p>
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<p>Voltage measurement %THD at the point of connection.</p>
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28 pages, 16912 KiB  
Article
Power Flow and Voltage Control Strategies in Hybrid AC/DC Microgrids for EV Charging and Renewable Integration
by Zaid H. Ali and David Raisz
World Electr. Veh. J. 2025, 16(2), 104; https://doi.org/10.3390/wevj16020104 - 14 Feb 2025
Viewed by 486
Abstract
This study outlines the creation and lab verification of a low-voltage direct current (LVDC) back-to-back (B2B) converter intended as a versatile connection point for low-voltage users. The converter configuration features dual inverters that regulate the power distribution to AC loads and grid connections [...] Read more.
This study outlines the creation and lab verification of a low-voltage direct current (LVDC) back-to-back (B2B) converter intended as a versatile connection point for low-voltage users. The converter configuration features dual inverters that regulate the power distribution to AC loads and grid connections through a shared DC circuit. This arrangement enables the integration of various DC generation sources, such as photovoltaic systems, as well as DC consumers, like electric vehicle chargers, supported by DC/DC converters. Significant advancements include sensorless current estimation for grid-forming inverters, which removes the necessity for conventional current sensors by employing mathematical models and established system parameters. The experimental findings validate the system’s effectiveness in grid-connected and isolated microgrid modes, demonstrating its ability to sustain energy quality and system stability under different conditions. Our results highlight the considerable potential of integrating grid-forming functionalities in inverters to improve microgrid operations. Full article
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Figure 1
<p>Grid-connected microgrid general architecture.</p>
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<p>Modes of power flow.</p>
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<p>EV and storage batteries and bidirectional DC/DC buck–boost converter.</p>
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<p>Battery charge and discharge controller.</p>
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<p>EVB charge and discharge controller.</p>
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<p>HLI control scheme.</p>
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<p>GFM standalone system configuration.</p>
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<p>Mode of operations flowchart.</p>
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<p>Mode one PV to batteries and HLI; various power values for sources and load.</p>
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<p>Mode one solar PV to batteries and HLI grid voltage and current.</p>
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<p>House load voltage and current.</p>
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<p>Mode one solar PV to grid and HLI; various power values for sources and load.</p>
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<p>Grid voltage and current during mode one solar PV to grid and HLI.</p>
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<p>Various power values for sources and load during mode two.</p>
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<p>Grid voltage and current during mode two and three.</p>
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<p>Various power values during mode two when SOC1 is higher than SOC.</p>
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<p>Various power values for sources and load during mode three.</p>
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<p>Imperix system configuration.</p>
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<p>System configuration.</p>
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<p>Only battery connected feeding to the dc-link.</p>
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<p>Excess energy is used to charge the battery.</p>
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<p>Battery and PV feeding into dc-link.</p>
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<p>Unbalanced GFM load.</p>
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<p>Balanced GFM with increased load.</p>
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<p>Increasing GFM voltage and DC-link voltage.</p>
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<p>Cinergia battery and PV emulator monitor.</p>
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<p>Cinergia battery and PV emulator monitor.</p>
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35 pages, 21470 KiB  
Article
Development of GaN-Based, 6.6 kW, 450 V, Bi-Directional On-Board Charger with Integrated 1 kW, 12 V Auxiliary DC-DC Converter with High Power Density
by Alessandro Reali, Alessio Alemanno, Fabio Ronchi, Carlo Rossi and Corrado Florian
Micromachines 2024, 15(12), 1470; https://doi.org/10.3390/mi15121470 - 2 Dec 2024
Viewed by 1888
Abstract
Automotive-grade GaN power switches have recently been made available in the market from a growing number of semiconductor suppliers. The exploitation of this technology enables the development of very efficient power converters operating at much higher switching frequencies with respect to components implemented [...] Read more.
Automotive-grade GaN power switches have recently been made available in the market from a growing number of semiconductor suppliers. The exploitation of this technology enables the development of very efficient power converters operating at much higher switching frequencies with respect to components implemented with silicon power devices. Thus, a new generation of automotive power components with an increased power density is expected to replace silicon-based products in the development of higher-performance electric and hybrid vehicles. 650 V GaN-on-silicon power switches are particularly suitable for the development of 3–7 kW on-board battery chargers (OBCs) for electric cars and motorcycles with a 400 V nominal voltage battery pack. This paper describes the design and implementation of a 6.6 kW OBC for electric vehicles using automotive-grade, 650 V, 25 mΩ, discrete GaN switches. The OBC allows bi-directional power flow, since it is composed of a bridgeless, interleaved, totem-pole PFC AC/DC active front end, followed by a dual active bridge (DAB) DC-DC converter. The OBC can operate from a single-phase 90–264 Vrms AC grid to a 200–450 V high-voltage (HV) battery and also integrates an auxiliary 1 kW DC-DC converter to connect the HV battery to the 12 V battery of the vehicle. The auxiliary DC-DC converter is a center-tapped phase-shifted full-bridge (PSFB) converter with synchronous rectification. At the low-voltage side of the auxiliary converter, 100 V GaN power switches are used. The entire OBC is liquid-cooled. The first prototype of the OBC exhibited a 96% efficiency and 2.2 kW/L power density (including the cooling system) at a 60 °C ambient temperature. Full article
(This article belongs to the Special Issue III-Nitride Materials in Electronic and Photonic Devices)
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Figure 1
<p>Physical properties of Si, GaN and SiC.</p>
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<p>Converter design FOMs exploiting Si, GaN and SiC devices, from [<a href="#B17-micromachines-15-01470" class="html-bibr">17</a>].</p>
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<p>OBC system’s topology.</p>
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<p>PFC waveforms, including, from top to bottom, line voltage, line current and its fundamental component (50 Hz), inductor L1 current and its fundamental component (50 Hz), inductor L2 current and its fundamental component (50 Hz), Q5 and Q6 (LF leg) currents.</p>
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<p>Magnification of ripple of line current (at 260 kHz) and of L1/L2 current (at 130 kHz).</p>
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<p>Q1-Q2 HF current conduction.</p>
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<p>Q1 losses, including, from top to bottom, Q1 current, conduction losses (in green), switching losses (in cyan), third-quadrant losses (in violet), total losses (in black) and case (Tc) and junction (Tj) temperatures.</p>
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<p>Contributions of Q1 power losses (@ T<sub>amb</sub> = 60 °C).</p>
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<p>PFC waveforms at the output section: V<sub>out</sub>, I<sub>out</sub>, I<sub>C_DC-LINK</sub>.</p>
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<p>FFT (0–2 kHz) of PFC waveforms at output section. Y-axis is in log scale.</p>
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<p>FFT (0–280 kHz) of PFC waveforms at output section. Y-axis is in log scale.</p>
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<p>PFC converter power loss contributions (@ T<sub>amb</sub> = 60 °C).</p>
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<p>Flux-canceling traces with top-side-cooled devices in an 8-layer PCB. Layer 2 is used as a ground return. The thickness of the entire layer stack-up is 2060 µm in our case [<a href="#B16-micromachines-15-01470" class="html-bibr">16</a>].</p>
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<p>DAB DC-DC converter schematic.</p>
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<p>DAB waveforms, including, from top to bottom, PWM signals of Q9-Q12 and Q10-Q11, PWM signals of Q13-Q16 and Q14-Q15, primary (V1) and secondary (V2) voltages, series inductor voltage V<sub>L</sub> and series inductor current I<sub>L</sub>.</p>
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<p>DAB ZVS turn-on: V<sub>DS</sub> and I<sub>DS</sub> of Q10, V<sub>DS</sub> and I<sub>DS</sub> of Q9, V<sub>DS</sub> and I<sub>DS</sub> of Q14, V<sub>DS</sub> and I<sub>DS</sub> of Q13. Y-axis of drain-source voltage is on left, and Y-axis of drain-source current is on right.</p>
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<p>Q9 losses, including, from top to bottom, Q9 current, conduction losses (in orange), third-quadrant losses (in green), switching losses (in light blue), total losses (in black) and case and junction temperatures.</p>
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<p>Contributions of Q9 power losses (@ V<sub>out</sub> = 400 V, P<sub>out</sub> = 6.6 kW, T<sub>amb</sub> = 60 °C).</p>
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<p>Contributions of DAB converter losses (@ V<sub>out</sub> = 400 V; P<sub>out</sub> = 6.6 kW; T<sub>amb</sub> = 60 °C).</p>
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<p>DAB waveforms at V<sub>out</sub> = 250 V and P<sub>out</sub> = 4.125 kW, including, from top to bottom, PWM signals of Q9-Q12 and Q10-Q11, PWM signals of Q13-Q16 and Q14-Q15, primary (V1) and secondary (V2) voltages, series inductor voltage V<sub>L</sub> and series inductor current I<sub>L</sub>.</p>
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<p>DAB Q9 and Q10 ZVS turn-on (@ V<sub>out</sub> = 250 V and P<sub>out</sub> = 4.125 kW): V<sub>DS</sub> and I<sub>DS</sub> of Q10, V<sub>DS</sub> and I<sub>DS</sub> of Q9, V<sub>DS</sub> and I<sub>DS</sub> of Q14, V<sub>DS</sub> and I<sub>DS</sub> of Q13. Y-axis of drain-source voltage is on left, and Y-axis of drain-source current is on right.</p>
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<p>Q9 losses at V<sub>out</sub> = 250 V and P<sub>out</sub> = 4.125 kW: Q9 current, conduction losses (in orange), third-quadrant losses (in green), switching losses (in light blue), total losses (in black) and case and junction temperatures.</p>
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<p>Contributions of Q9 power losses (@ V<sub>out</sub> = 250 V; P<sub>out</sub> = 4.125 kW; and T<sub>amb</sub> = 60 °C).</p>
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<p>Contributions of DAB converter losses (@ V<sub>out</sub> = 250 V; P<sub>out</sub> = 4.125 kW; and T<sub>amb</sub> = 60 °C).</p>
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<p>PSFB waveforms, including, from top to bottom, PWM signals of Q17 and Q18, PWM signals of Q19 and Q20, primary voltage, primary current, secondary voltage and Q21-Q23 and Q22-Q24 currents.</p>
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<p>PSFB Q17 and Q18 ZVS turn-on: PWM signals of Q17 and Q18, V<sub>DS</sub> and I<sub>DS</sub> of Q17 and V<sub>DS</sub> and I<sub>DS</sub> of Q18. Y-axis of drain-source voltage is on left, Y-axis of drain-source current is on right.</p>
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<p>PSFB Q19 and Q20 ZVS turn-on: PWM signals of Q19 and Q20, V<sub>DS</sub> and I<sub>DS</sub> of Q19 and V<sub>DS</sub> and I<sub>DS</sub> of Q20. Y-axis of drain-source voltage is on left, Y-axis of drain-source current is on right.</p>
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<p>Q17 losses, including, from top to bottom, Q17 current, conduction losses (in orange), third-quadrant losses (in green), switching losses (in light blue), total losses (in black) and case (T<sub>c</sub>) and junction temperatures (T<sub>j</sub>).</p>
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<p>Q21/Q23 losses, including, from top to bottom, Q21-Q23 current, conduction losses (in orange), third-quadrant losses (in green), switching losses (in light blue), total losses (in black) and case and junction temperatures. Current in first plot and losses in second plot refer to power switch formed by parallel of Q21-Q23, whereas temperatures refer to individual device.</p>
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<p>Contributions of PSFB converter losses (@ T<sub>amb</sub> = 60 °C).</p>
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<p>OBC’s simplified control architecture.</p>
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<p>OBC prototype: BTP PFC converter and thermal image.</p>
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<p>OBC prototype: DAB converter and thermal image.</p>
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<p>OBC prototype: PSFB converter.</p>
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<p>Series inductor current I<sub>L</sub> and V<sub>DS</sub> and V<sub>GS</sub> of Q10 at 3.3 kW power level from post-layout simulation and scope (MSO-56 Tektronix) acquisition.</p>
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19 pages, 44093 KiB  
Article
Intelligent Integration of Vehicle-to-Grid (V2G) and Vehicle-for-Grid (V4G) Systems: Leveraging Artificial Neural Networks (ANNs) for Smart Grid
by Youness Hakam, Ahmed Gaga, Mohamed Tabaa and Benachir Elhadadi
Energies 2024, 17(13), 3095; https://doi.org/10.3390/en17133095 - 23 Jun 2024
Cited by 4 | Viewed by 1822
Abstract
This paper presents a groundbreaking control strategy for a bidirectional battery charger that allows power to be injected into the smart grid while simultaneously compensating for the grid’s reactive power using an electric vehicle battery. An artificial neural network (ANN) controller is utilized [...] Read more.
This paper presents a groundbreaking control strategy for a bidirectional battery charger that allows power to be injected into the smart grid while simultaneously compensating for the grid’s reactive power using an electric vehicle battery. An artificial neural network (ANN) controller is utilized for precise design to ensure optimal performance with minimal error. The ANN technique is applied to generate sinusoidal pulse width modulation (SPWM) for a bidirectional AC–DC inverter, with the entire algorithm simulated in MATLAB Simulink.The core innovation of this study is the creation of the ANN algorithm, which supports grid compensation using electric vehicle batteries, an approach termed “vehicle-for-grid”. Additionally, the paper details the PCB circuit design of the system controlled by the DSP F28379D board, which was tested on a three-phase motor. The total harmonic distortion (THD) of the proposed ANN algorithm is approximately 1.85%, compared to the MPC algorithm’s THD of about 2.85%. This indicates that the proposed algorithm is more effective in terms of the quality of the power injected into the grid. Furthermore, it demonstrates effective grid compensation, with the reactive power effectively neutralized to 0KVAR in the vehicle-for-grid mode. Full article
(This article belongs to the Section F3: Power Electronics)
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<p>Multiple modes of V2X system.</p>
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<p>Schematic of EV charger.</p>
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<p>Internal architecture of ANN.</p>
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<p>Architecture of ANN controller.</p>
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<p>Topology design for V2X system.</p>
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<p>Architecture of DC–AC controller.</p>
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<p>Models of ANN controllers. (<b>a</b>) voltage link; (<b>b</b>) direct current; (<b>c</b>) reactive power.</p>
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<p>Controller ANN in DC–DC converter.</p>
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<p>Diagram of the proposed system architecture.</p>
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<p>Real-world apsects of the proposed system.</p>
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<p>Performance of training model algorithm.</p>
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<p>Training model algorithm.</p>
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<p>The active power for both V2G and V4G modes, comparing the PID and ANN methods.</p>
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<p>The reactive power for both V2G and V4G modes, comparing the PID and ANN methods.</p>
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<p>The voltage and current of the grid under the influence of the PID controller in the three different modes.</p>
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<p>The voltage and current profiles of the grid across the three modes under the control of the ANN controller.</p>
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<p>The voltage link (<math display="inline"><semantics> <msub> <mi>V</mi> <mrow> <mi>d</mi> <mi>c</mi> </mrow> </msub> </semantics></math>) across the three modes with both ANN and PID controllers.</p>
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<p>The battery current in all three modes under the application of both the PID and ANN methods.</p>
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<p>The active power for both V2G and V4G modes.</p>
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<p>The reactive power for both V2G and V4G modes.</p>
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<p>The voltage of the motor in modes V2G and V4G.</p>
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<p>The current of the grid in both modes, V2G and V4G.</p>
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<p>The voltage link (<math display="inline"><semantics> <msub> <mi>V</mi> <mrow> <mi>d</mi> <mi>c</mi> </mrow> </msub> </semantics></math>) in the real world.</p>
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<p>The battery current in the real world.</p>
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<p>The total harmonic distortion.</p>
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40 pages, 9537 KiB  
Review
Non-Integrated and Integrated On-Board Battery Chargers (iOBCs) for Electric Vehicles (EVs): A Critical Review
by Fatemeh Nasr Esfahani, Ahmed Darwish, Xiandong Ma and Peter Twigg
Energies 2024, 17(10), 2285; https://doi.org/10.3390/en17102285 - 9 May 2024
Cited by 7 | Viewed by 2581
Abstract
The rising Greenhouse Gas (GHG) emissions stemming from the extensive use of automobiles across the globe represent a critical environmental challenge, contributing significantly to phenomena such as global warming and the deterioration of air quality. To address these challenges, there is a critical [...] Read more.
The rising Greenhouse Gas (GHG) emissions stemming from the extensive use of automobiles across the globe represent a critical environmental challenge, contributing significantly to phenomena such as global warming and the deterioration of air quality. To address these challenges, there is a critical need for research and development in electric vehicles (EVs) and their associated charging infrastructure, including off-board and on-board chargers (OBCs). This paper aims to bridge the gaps in existing review literature by offering a comprehensive review of both integrated and non-integrated OBCs for EVs, based on the authors’ knowledge at the time of writing. The paper begins by outlining trends in the EV market, including voltage levels, power ratings, and relevant standards. It then provides a detailed analysis of two-level and multi-level power converter topologies, covering AC-DC power factor correction (PFC) and isolated DC-DC topologies. Subsequently, it discusses single-stage and two-stage non-integrated OBC solutions. Additionally, various categories of integrated OBCs (iOBCs) are explored, accompanied by relevant examples. The paper also includes comparison tables containing technical specifications and key characteristics for reference and analysis. Full article
(This article belongs to the Section D2: Electrochem: Batteries, Fuel Cells, Capacitors)
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Figure 1
<p>EV charging system with on-board and off-board chargers.</p>
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<p>Expected EV market share by 2040.</p>
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<p>The classification of OBC topologies for EV applications.</p>
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<p>Non-integrated OBCs: (<b>a</b>) two-stage OBC, including EMI filter, AC-DC PFC, DC link, and isolated DC-DC converter; (<b>b</b>) single-stage topology, including EMI filter and AC-DC PFC.</p>
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<p>Examples of two-level AC-DC PFCs for two-stage OBCs. (<b>a</b>) Three-phase boost PFC (full-bridge PFC) [<a href="#B96-energies-17-02285" class="html-bibr">96</a>], (<b>b</b>) totem-pole PFC [<a href="#B10-energies-17-02285" class="html-bibr">10</a>], (<b>c</b>) two-channel interleaved totem-pole PFC [<a href="#B11-energies-17-02285" class="html-bibr">11</a>] and (<b>d</b>) three- channel interleaved totem-pole PFC [<a href="#B6-energies-17-02285" class="html-bibr">6</a>].</p>
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<p>Examples of multi-level AC-DC PFCs for two-stage non-integrated OBCs: (<b>a</b>) three-level T-type boost PFC (Vienna rectifier), (<b>b</b>) active-neutral-point-clamped (ANPC) converter, (<b>c</b>) flying-capacitor (FC) topology, and (<b>d</b>) modular multi-level converter.</p>
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<p>Isolated DC-DC converter topologies for two-stage non-integrated OBCs: (<b>a</b>) dual active bridge (DAB) converter; (<b>b</b>) resonant DAB converter (CLLC).</p>
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<p>Examples of two-level and multi-level variants of DAB and resonant DAB converter topologies for two-stage non-integrated OBCs: (<b>a</b>) two-level series-input–series-output DAB converter [<a href="#B115-energies-17-02285" class="html-bibr">115</a>], (<b>b</b>) three-level ANPC dual active half-bridge topology [<a href="#B105-energies-17-02285" class="html-bibr">105</a>], (<b>c</b>) three-level DAB converter with blocking capacitors [<a href="#B102-energies-17-02285" class="html-bibr">102</a>], (<b>d</b>) three-level three-phase DAB converter [<a href="#B108-energies-17-02285" class="html-bibr">108</a>], (<b>e</b>) two-level CLLC resonant converter with three modular transformers [<a href="#B110-energies-17-02285" class="html-bibr">110</a>], (<b>f</b>) multi-level stacked-half-bridge with LCL-T network with DC blocking capacitors [<a href="#B1-energies-17-02285" class="html-bibr">1</a>].</p>
Full article ">Figure 8 Cont.
<p>Examples of two-level and multi-level variants of DAB and resonant DAB converter topologies for two-stage non-integrated OBCs: (<b>a</b>) two-level series-input–series-output DAB converter [<a href="#B115-energies-17-02285" class="html-bibr">115</a>], (<b>b</b>) three-level ANPC dual active half-bridge topology [<a href="#B105-energies-17-02285" class="html-bibr">105</a>], (<b>c</b>) three-level DAB converter with blocking capacitors [<a href="#B102-energies-17-02285" class="html-bibr">102</a>], (<b>d</b>) three-level three-phase DAB converter [<a href="#B108-energies-17-02285" class="html-bibr">108</a>], (<b>e</b>) two-level CLLC resonant converter with three modular transformers [<a href="#B110-energies-17-02285" class="html-bibr">110</a>], (<b>f</b>) multi-level stacked-half-bridge with LCL-T network with DC blocking capacitors [<a href="#B1-energies-17-02285" class="html-bibr">1</a>].</p>
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<p>Two-stage non-integrated isolated OBCs with totem-pole PFC and resonant DC-DC converters: (<b>a</b>) two-channel interleaved totem-pole PFC and single-phase CLLC resonant DAB converter [<a href="#B120-energies-17-02285" class="html-bibr">120</a>], (<b>b</b>) two-channel interleaved totem-pole PFC and CLLC resonant converter [<a href="#B10-energies-17-02285" class="html-bibr">10</a>], (<b>c</b>) four-channel interleaved totem-pole PFC with Return Path Windings and three-phase CLLC resonant converter [<a href="#B100-energies-17-02285" class="html-bibr">100</a>], (<b>d</b>) two-channel interleaved totem-pole PFC and LLC resonant converter [<a href="#B124-energies-17-02285" class="html-bibr">124</a>], (<b>e</b>) two-channel interleaved totem-pole PFC with Mode Switch Boost converter and LLC resonant converter [<a href="#B125-energies-17-02285" class="html-bibr">125</a>].</p>
Full article ">Figure 9 Cont.
<p>Two-stage non-integrated isolated OBCs with totem-pole PFC and resonant DC-DC converters: (<b>a</b>) two-channel interleaved totem-pole PFC and single-phase CLLC resonant DAB converter [<a href="#B120-energies-17-02285" class="html-bibr">120</a>], (<b>b</b>) two-channel interleaved totem-pole PFC and CLLC resonant converter [<a href="#B10-energies-17-02285" class="html-bibr">10</a>], (<b>c</b>) four-channel interleaved totem-pole PFC with Return Path Windings and three-phase CLLC resonant converter [<a href="#B100-energies-17-02285" class="html-bibr">100</a>], (<b>d</b>) two-channel interleaved totem-pole PFC and LLC resonant converter [<a href="#B124-energies-17-02285" class="html-bibr">124</a>], (<b>e</b>) two-channel interleaved totem-pole PFC with Mode Switch Boost converter and LLC resonant converter [<a href="#B125-energies-17-02285" class="html-bibr">125</a>].</p>
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<p>Two-stage non-integrated isolated OBCs with three-phase boost PFC and resonant DC-DC converters: (<b>a</b>) three-phase boost PFC and LLC resonant converter [<a href="#B126-energies-17-02285" class="html-bibr">126</a>]; (<b>b</b>) three-phase boost PFC and two parallel-connected resonant LLC converters [<a href="#B127-energies-17-02285" class="html-bibr">127</a>].</p>
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<p>Two-stage non-integrated isolated OBCs with diode bridge PFC and resonant DC-DC converters: (<b>a</b>) diode bridge and boost converter in the PFC stage and a resonant LLC DC-DC converter at the HV battery side [<a href="#B128-energies-17-02285" class="html-bibr">128</a>]; (<b>b</b>) a diode bridge with an inrush current limiter and an interleaved boost converter at the grid side and two parallel-input–parallel-output (PIPO) LLC resonant converters at the HV battery side [<a href="#B129-energies-17-02285" class="html-bibr">129</a>].</p>
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<p>Single-stage non-integrated isolated OBCs: (<b>a</b>) three-phase matrix-type DAB three-phase rectifier (IMDAB3R) [<a href="#B137-energies-17-02285" class="html-bibr">137</a>], (<b>b</b>) single-phase interleaved boost DAB converter [<a href="#B139-energies-17-02285" class="html-bibr">139</a>], (<b>c</b>) three-phase modularized FB rectifier and DAB PFC (single-phase demonstration) [<a href="#B140-energies-17-02285" class="html-bibr">140</a>], and (<b>d</b>) three-phase T-type circuits and isolated FB converter [<a href="#B141-energies-17-02285" class="html-bibr">141</a>].</p>
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<p>Single-stage non-integrated isolated OBCs: (<b>a</b>) three-phase matrix-type DAB three-phase rectifier (IMDAB3R) [<a href="#B137-energies-17-02285" class="html-bibr">137</a>], (<b>b</b>) single-phase interleaved boost DAB converter [<a href="#B139-energies-17-02285" class="html-bibr">139</a>], (<b>c</b>) three-phase modularized FB rectifier and DAB PFC (single-phase demonstration) [<a href="#B140-energies-17-02285" class="html-bibr">140</a>], and (<b>d</b>) three-phase T-type circuits and isolated FB converter [<a href="#B141-energies-17-02285" class="html-bibr">141</a>].</p>
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<p>Various categories of iOBCs: (<b>a</b>) propulsion system iOBC, (<b>b</b>) auxiliary power module (APM) iOBC, (<b>c</b>) wireless charger iOBC.</p>
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<p>Multi-winding propulsion system iOBC using a symmetrical six-phase machine [<a href="#B41-energies-17-02285" class="html-bibr">41</a>].</p>
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<p>Isolated bidirectional iOBC using reconfiguration of the motor’s winding [<a href="#B145-energies-17-02285" class="html-bibr">145</a>].</p>
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<p>A dual-motor dual-inverter topology as access to the motor’s neutral point iOBC [<a href="#B148-energies-17-02285" class="html-bibr">148</a>].</p>
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<p>Three-phase split motor windings iOBC [<a href="#B59-energies-17-02285" class="html-bibr">59</a>].</p>
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<p>Add-on interface iOBC using three-phase step-down FB converter and an EMI filter [<a href="#B63-energies-17-02285" class="html-bibr">63</a>].</p>
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<p>Bidirectional traction inverter iOBC using an FB isolated boost converter and five additional auxiliary relay switches [<a href="#B65-energies-17-02285" class="html-bibr">65</a>].</p>
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<p>Unidirectional and bidirectional converter topologies used as traction inverter iOBCs: (<b>a</b>) single-phase unidirectional [<a href="#B67-energies-17-02285" class="html-bibr">67</a>], (<b>b</b>) single-phase unidirectional [<a href="#B68-energies-17-02285" class="html-bibr">68</a>], (<b>c</b>) single-phase unidirectional [<a href="#B69-energies-17-02285" class="html-bibr">69</a>], (<b>d</b>) single-phase unidirectional [<a href="#B70-energies-17-02285" class="html-bibr">70</a>], (<b>e</b>) single-phase unidirectional [<a href="#B71-energies-17-02285" class="html-bibr">71</a>], (<b>f</b>) single-phase unidirectional [<a href="#B67-energies-17-02285" class="html-bibr">67</a>], (<b>g</b>) single-phase unidirectional [<a href="#B72-energies-17-02285" class="html-bibr">72</a>], (<b>h</b>) single-phase unidirectional [<a href="#B73-energies-17-02285" class="html-bibr">73</a>], (<b>i</b>) single-phase unidirectional [<a href="#B74-energies-17-02285" class="html-bibr">74</a>], (<b>j</b>) single-phase bidirectional [<a href="#B75-energies-17-02285" class="html-bibr">75</a>].</p>
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<p>Unidirectional and bidirectional converter topologies used as traction inverter iOBCs: (<b>a</b>) single-phase unidirectional [<a href="#B67-energies-17-02285" class="html-bibr">67</a>], (<b>b</b>) single-phase unidirectional [<a href="#B68-energies-17-02285" class="html-bibr">68</a>], (<b>c</b>) single-phase unidirectional [<a href="#B69-energies-17-02285" class="html-bibr">69</a>], (<b>d</b>) single-phase unidirectional [<a href="#B70-energies-17-02285" class="html-bibr">70</a>], (<b>e</b>) single-phase unidirectional [<a href="#B71-energies-17-02285" class="html-bibr">71</a>], (<b>f</b>) single-phase unidirectional [<a href="#B67-energies-17-02285" class="html-bibr">67</a>], (<b>g</b>) single-phase unidirectional [<a href="#B72-energies-17-02285" class="html-bibr">72</a>], (<b>h</b>) single-phase unidirectional [<a href="#B73-energies-17-02285" class="html-bibr">73</a>], (<b>i</b>) single-phase unidirectional [<a href="#B74-energies-17-02285" class="html-bibr">74</a>], (<b>j</b>) single-phase bidirectional [<a href="#B75-energies-17-02285" class="html-bibr">75</a>].</p>
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<p>Multiport converters for APM iOBCs: (<b>a</b>) single-stage bidirectional converter with bidirectional PFC converter, three-port HFT, bidirectional HB CLLC resonant converter, and FB LLC resonant [<a href="#B157-energies-17-02285" class="html-bibr">157</a>]; (<b>b</b>) two-stage bidirectional converter with interleaved totem-pole PFC converters, CLLC resonant converter, three-port HFT, and interleaved buck converter [<a href="#B158-energies-17-02285" class="html-bibr">158</a>,<a href="#B159-energies-17-02285" class="html-bibr">159</a>].</p>
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<p>Highest level of power electronics integration: APM and traction inverter iOBC [<a href="#B160-energies-17-02285" class="html-bibr">160</a>,<a href="#B161-energies-17-02285" class="html-bibr">161</a>].</p>
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<p>Wireless iOBC system [<a href="#B165-energies-17-02285" class="html-bibr">165</a>].</p>
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20 pages, 5558 KiB  
Article
Bidirectional Power Control Strategy for On-Board Charger Based on Single-Stage Three-Phase Converter
by Li Sun, Xin Wang and Chenglian Ma
Electronics 2024, 13(6), 1041; https://doi.org/10.3390/electronics13061041 - 11 Mar 2024
Viewed by 1561
Abstract
To solve the problems of large switching losses and the need for large-capacity electrolytic capacitances in three-phase DC/AC on-board chargers for vehicle-to-grid (V2G) applications, this paper proposes a single-stage bidirectional high-frequency isolated converter that eliminates the need for large-capacity capacitances. Combined with the [...] Read more.
To solve the problems of large switching losses and the need for large-capacity electrolytic capacitances in three-phase DC/AC on-board chargers for vehicle-to-grid (V2G) applications, this paper proposes a single-stage bidirectional high-frequency isolated converter that eliminates the need for large-capacity capacitances. Combined with the proposed modulation scheme, it can theoretically reduce the switching loss by about two-thirds with the three-phase converter compared with the conventional modulation scheme, improving the converter’s operating efficiency and power density. Firstly, based on the characteristics of the proposed topology, a hybrid modulation scheme is proposed, which combines a phase-shift modulation scheme based on double modulation waves and a sawtooth carrier with a 1/3 modulation scheme, and the theoretical feasibility of the hybrid modulation scheme is verified using a mathematical modeling equation. Secondly, this paper provides a detailed analysis of the four operating modes of the two full-bridge circuits and the commutation process of the three-phase converter within 1/6 of the fundamental frequency cycle (P1 modulation interval). Then, the control strategy is given for the constant-current and constant-voltage charging and constant-current discharging for electric vehicle batteries. Finally, simulation results verify the correctness of the proposed topology and modulation scheme in vehicle–grid interaction. Full article
(This article belongs to the Section Power Electronics)
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Figure 1

Figure 1
<p>The single-stage bidirectional isolated three-phase DC/AC converter topology.</p>
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<p>Full-bridge circuit-switch timing diagram.</p>
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<p>Key waveforms of 1/3 modulation scheme.</p>
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<p>Overall hybrid modulation scheme.</p>
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<p>Operating modes of the full-bridge circuit: (<b>a</b>) mode 1; (<b>b</b>) mode 2; (<b>c</b>) mode 3; (<b>d</b>) mode 4.</p>
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<p>Operating modes of the full-bridge circuit: (<b>a</b>) mode 1; (<b>b</b>) mode 2; (<b>c</b>) mode 3; (<b>d</b>) mode 4.</p>
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<p>The theoretical waveforms of the full-bridge circuit in buck mode.</p>
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<p>Case 1.</p>
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<p>Case 2.</p>
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<p>Case 3.</p>
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<p>Charging and discharging control strategy.</p>
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<p>Phase adjustment control strategy.</p>
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<p>Charging and discharging modes.</p>
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<p>Grid-side currents and voltages.</p>
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<p>Analysis of grid-side current distortion: (<b>a</b>) FFT of grid-side charging current; (<b>b</b>) FFT of grid-side discharging current.</p>
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<p>Waveforms of <span class="html-italic">i</span><sub>1</sub>, <span class="html-italic">V</span><sub>1</sub>, and <span class="html-italic">V</span><sub>link</sub>.</p>
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<p>Key waveforms during the modulation process of three-phase converter.</p>
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<p>Analysis of bidirectional power flow: (<b>a</b>) voltage and current waveforms of phase A; (<b>b</b>) three-phase output voltages; (<b>c</b>) DC-side voltage.</p>
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<p>Analysis of bidirectional power flow: (<b>a</b>) voltage and current waveforms of phase A; (<b>b</b>) three-phase output voltages; (<b>c</b>) DC-side voltage.</p>
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<p>Important verification waveforms.</p>
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<p>Variation of 18 kW converter efficiency with load.</p>
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24 pages, 6988 KiB  
Article
Considerations on Combining Unfolding Inverters with Partial Power Regulators in Battery–Grid Interface Converters
by Ilya A. Galkin, Rodions Saltanovs, Alexander Bubovich, Andrei Blinov and Dimosthenis Peftitsis
Energies 2024, 17(4), 893; https://doi.org/10.3390/en17040893 - 14 Feb 2024
Cited by 1 | Viewed by 1277
Abstract
The application of electrochemical cells as a source unit of electrical energy is rapidly growing—used in electric vehicles and other electric mobility devices, as well as in energy supply systems—as energy storage, often together with renewable energy sources. The key element of such [...] Read more.
The application of electrochemical cells as a source unit of electrical energy is rapidly growing—used in electric vehicles and other electric mobility devices, as well as in energy supply systems—as energy storage, often together with renewable energy sources. The key element of such systems is the power electronic converter used for DC energy storage and AC grid interfacing. It should be bidirectional to charge and discharge the battery when it is necessary. Two-stage battery interface converters are the most common; their DC-DC stage controls the battery current and adjusts voltage, but the DC-AC stage (inverter or frontend) controls the current in the grid. The use of unfolding inverters in two-stage battery interfaces can have some advantages. In this case, the DC-DC converter produces half-sinewave pulsating voltages and currents, but the unfolding circuit changes the polarity of the voltages and currents and produces no switching losses. Another trend of modern power electronics is the principle of partial power processing. In this case, power electronic converters deal only with a part of the total power; therefore, losses in such converters are reduced. This paper considers combining unfolding frontends with partial power DC-DC converters that enable the further reduction in losses. In this paper, it is shown that such implementation of the partial power conversion principle in semi-DC-AC systems is really possible based on the real-time matching of the voltage of the partial-power DC-DC converter, battery voltage (which depends on its state of charge) and the rectified instantaneous voltage of the AC grid. Full article
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Figure 1
<p>Structural diagrams of a two-stage converter with unfolding frontend and partial power DC/DC converter: (<b>a</b>) basic configuration, (<b>b</b>) configuration with additional unfolder, (<b>c</b>) configuration with two converters dedicated for battery charging and loading and (<b>d</b>) configuration with additional unfolder and two converters.</p>
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<p>Structural diagrams of a two-stage converter with unfolding frontend and partial power DC/DC converter: (<b>a</b>) basic configuration, (<b>b</b>) configuration with additional unfolder, (<b>c</b>) configuration with two converters dedicated for battery charging and loading and (<b>d</b>) configuration with additional unfolder and two converters.</p>
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<p>Generalized schematics of unfolding inverters (single phase, basic elements): (<b>a</b>) with inductor at AC port and (<b>b</b>) with inductor at DC port.</p>
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<p>Operation of inductance in unfolding inverter with inductor at AC port: (<b>a</b>) voltages and (<b>b</b>) current (battery loading mode); (<b>c</b>) voltages and (<b>d</b>) current (battery charging mode).</p>
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<p>Operation of inductance in unfolding inverter with inductor at DC port: (<b>a</b>) voltages and (<b>b</b>) current (battery loading mode); (<b>c</b>) voltages and (<b>d</b>) current (battery charging mode).</p>
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<p>Considered configurations of partial power converters: (<b>a</b>) with bipolar DAB; (<b>b</b>) with bipolar DAB and extra unfolder.</p>
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<p>Voltage diagrams in BESS discharge mode: (<b>a</b>) voltages, typical for DC-link (black—battery voltage, red—PPC voltage at DC-link, brown—DC-link voltage); (<b>b</b>) internal voltage of PPC before extra unfolder.</p>
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<p>Voltage diagrams in BESS charge mode: (<b>a</b>) voltages typical for DC-link (black—battery voltage, red—PPC voltage at DC-link, brown—DC-link voltage); (<b>b</b>) internal voltage of PPC before extra unfolder.</p>
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<p>Voltage diagrams in BESS discharge mode for an autonomous ohmic load: (<b>a</b>) voltages, typical for DC-link (black—battery voltage, red—PPC voltage at DC-link, brown—DC-link voltage); (<b>b</b>) internal voltage of PPC before extra unfolder.</p>
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<p>Schematic of the experimental setup with unfolding grid frontend, bipolar DAB and extra unfolder.</p>
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<p>Layout of the initial (<b>a</b>) and final (<b>b</b>) experimental setups.</p>
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<p>Test results of the proposed BESS interface: (<b>a</b>) PPC current at the battery side i<sub>ppc,bat</sub>(t); (<b>b</b>) PPC current in the transformer i<sub>ppc,tr</sub>(t); (<b>c</b>) PPC internal voltage v<sub>ppc,int</sub>(t) and current i<sub>ppc,int</sub>(t) before the extra unfolder; (<b>d</b>) PPC voltage v<sub>ppc,dc</sub>(t) and current i<sub>ppc,dc</sub>(t) at the side of the DC-link; (<b>e</b>) DC-link voltage v<sub>dc</sub>(t); and (<b>f</b>) voltage v<sub>s</sub>(t) and current i<sub>s</sub>(t) in the grid (load).</p>
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<p>Test results of the proposed BESS interface: (<b>a</b>) PPC current at the battery side i<sub>ppc,bat</sub>(t); (<b>b</b>) PPC current in the transformer i<sub>ppc,tr</sub>(t); (<b>c</b>) PPC internal voltage v<sub>ppc,int</sub>(t) and current i<sub>ppc,int</sub>(t) before the extra unfolder; (<b>d</b>) PPC voltage v<sub>ppc,dc</sub>(t) and current i<sub>ppc,dc</sub>(t) at the side of the DC-link; (<b>e</b>) DC-link voltage v<sub>dc</sub>(t); and (<b>f</b>) voltage v<sub>s</sub>(t) and current i<sub>s</sub>(t) in the grid (load).</p>
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<p>Instantaneous power at the DC port of a partial power DC-DC converter (for 1 kW of the total power): (<b>a</b>) battery discharge to autonomous load (as considered in Chapter IV); (<b>b</b>) battery discharge to the grid.</p>
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<p>Comparison of power losses in the considered systems.</p>
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26 pages, 10479 KiB  
Article
A Bidirectional Grid-Friendly Charger Design for Electric Vehicle Operated under Pulse-Current Heating and Variable-Current Charging
by Ningzhi Jin, Jianjun Wang, Yalun Li, Liangxi He, Xiaogang Wu, Hewu Wang and Languang Lu
Sustainability 2024, 16(1), 367; https://doi.org/10.3390/su16010367 - 30 Dec 2023
Cited by 2 | Viewed by 2150
Abstract
Low-temperature preheating, fast charging, and vehicle-to-grid (V2G) capabilities are important factors for the further development of electric vehicles (EVs). However, for conventional two-stage chargers, the EV charging/discharging instructions and grid instructions cannot be addressed simultaneously for specific requirements, pulse heating and variable-current charging [...] Read more.
Low-temperature preheating, fast charging, and vehicle-to-grid (V2G) capabilities are important factors for the further development of electric vehicles (EVs). However, for conventional two-stage chargers, the EV charging/discharging instructions and grid instructions cannot be addressed simultaneously for specific requirements, pulse heating and variable-current charging can cause high-frequency power fluctuations at the grid side. Therefore, it is necessary to design a bidirectional grid-friendly charger for EVs operated under pulse-current heating and variable-current charging. The DC bus, which serves as the medium connecting the bidirectional DC–DC and bidirectional DC–AC, typically employs capacitors. This paper analyzes the reasons why the use of capacitors in the DC bus cannot satisfy the grid and EV requirements, and it proposes a new DC bus configuration that utilizes energy storage batteries instead of capacitors. Due to the voltage-source characteristics of the energy storage batteries, EV instructions and grid instructions can be flexibly and smoothly scheduled by using phase-shift control and adaptive virtual synchronous generator (VSG) control, respectively. In addition, the stability of the control strategy is demonstrated using small signal modeling. Finally, typical operating conditions (such as EV pulse preheating, fast charging with variable current, and grid peak shaving and valley filling) are selected for validation. The results show that in the proposed charger, the grid scheduling instructions and EV charging/discharging instructions do not interfere with each other, and different commands between EVs also do not interfere with each other under a charging pile with dual guns. Without affecting the requirements of EVs, the grid can change the proportion of energy supply based on actual scenarios and can also obtain energy from either EVs or energy storage batteries. For the novel charger, the pulse modulation time for EVs consistently achieves a steady state within 0.1 s; thus, the pulse modulation speed is as much as two times faster than that of conventional chargers with identical parameters. Full article
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Figure 1
<p>Typical working conditions of EV: (<b>a</b>) fast-charging Mas curve of lithium-ion batteries and (<b>b</b>) low-temperature pulse preheating.</p>
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<p>Basic structure of V2G and G2V modes for fast-charging scenarios.</p>
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<p>A novel bidirectional grid-friendly EV charger.</p>
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<p>The timing diagram and ZVS range of DAB under SPS control: (<b>a</b>) timing diagram and (<b>b</b>) ZVS range.</p>
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<p>VSG grid-connected equivalent circuit.</p>
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<p>Small-signal model of active power of VSG.</p>
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<p>Active loop: (<b>a</b>) Bode diagram and (<b>b</b>) Nyquist diagram.</p>
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<p>The comparison between the theoretical and simulated values of the active power.</p>
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<p>The effect of <span class="html-italic">J</span> and <span class="html-italic">D</span> on frequency: (<b>a</b>) the effect of <span class="html-italic">J</span> on frequency, (<b>b</b>) the effect of <span class="html-italic">D</span> on frequency, (<b>c</b>) the effect of <span class="html-italic">J</span> on output power, and (<b>d</b>) the effect of <span class="html-italic">D</span> on output power.</p>
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<p>The effect of <span class="html-italic">J</span> and <span class="html-italic">D</span> on frequency: (<b>a</b>) the effect of <span class="html-italic">J</span> on frequency, (<b>b</b>) the effect of <span class="html-italic">D</span> on frequency, (<b>c</b>) the effect of <span class="html-italic">J</span> on output power, and (<b>d</b>) the effect of <span class="html-italic">D</span> on output power.</p>
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<p>Power-angle and frequency oscillation curve of synchronous generator.</p>
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<p>The relevant waveform of the charger in low-temperature pulse preheating stage: (<b>a</b>) the contrast between <span class="html-italic">P<sub>g</sub></span> and <span class="html-italic">Q<sub>g</sub></span> and the <span class="html-italic">P<sub>EVref</sub></span>, (<b>b</b>) energy storage battery, (<b>c</b>) the effect of normal VSG and adaptive VSG on frequency, (<b>d</b>) dynamic harmonic waveform, (<b>e</b>) the reference current and actual current of EV, and (<b>f</b>) EV battery.</p>
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<p>The relevant waveform of the charger in low-temperature pulse preheating stage: (<b>a</b>) the contrast between <span class="html-italic">P<sub>g</sub></span> and <span class="html-italic">Q<sub>g</sub></span> and the <span class="html-italic">P<sub>EVref</sub></span>, (<b>b</b>) energy storage battery, (<b>c</b>) the effect of normal VSG and adaptive VSG on frequency, (<b>d</b>) dynamic harmonic waveform, (<b>e</b>) the reference current and actual current of EV, and (<b>f</b>) EV battery.</p>
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<p>The ZVS of DAB under low-temperature pulse preheating stage: (<b>a</b>) MOSFET on the high-voltage side in EV discharge mode, (<b>b</b>) MOSFET on the high-voltage side in EV charging mode, (<b>c</b>) MOSFET on the low-voltage side in EV discharge mode, and (<b>d</b>) MOSFET on the low-voltage side in EV charging mode.</p>
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<p>The pulse condition of the traditional charger: (<b>a</b>) the power change of the grid, (<b>b</b>) dynamic harmonic waveform, (<b>c</b>) the inductive current of DAB for the new charger, (<b>d</b>) the inductive current of DAB for the traditional charger, and (<b>e</b>) the voltage of the DC bus.</p>
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<p>The relevant waveform of charger with initial fast charge stage: (<b>a</b>) the contrast between <span class="html-italic">P<sub>g</sub></span> and <span class="html-italic">Q<sub>g</sub></span> and the <span class="html-italic">P<sub>EVref</sub></span>, (<b>b</b>) energy storage battery, (<b>c</b>) the reference current and the actual current of EV, and (<b>d</b>) EV battery.</p>
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<p>Grid and energy storage waveforms in the later stage of fast charging: (<b>a</b>) the contrast between <span class="html-italic">P<sub>g</sub></span> and <span class="html-italic">Q<sub>g</sub></span> and the <span class="html-italic">P<sub>EVref</sub></span>, (<b>b</b>) energy storage battery, (<b>c</b>) dynamic harmonic waveform, (<b>d</b>) inverter grid-connection frequency, (<b>e</b>) the voltage and current of the inverter connected to the grid when grid discharges, and (<b>f</b>) the voltage and current of the inverter connected to the grid when grid charges.</p>
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<p>The main waveform of EV in the later fast charge stage: (<b>a</b>) EV reference current and actual current with later fast charge stage and (<b>b</b>) EV battery.</p>
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<p>The main waveform in one charging pile with dual guns: (<b>a</b>) the contrast between <span class="html-italic">P<sub>g</sub></span>, <span class="html-italic">Q<sub>g</sub></span>, and <span class="html-italic">P<sub>EV</sub></span><sub>1<span class="html-italic">ref</span></sub> and <span class="html-italic">P<sub>EV</sub></span><sub>2<span class="html-italic">ref</span></sub>; (<b>b</b>) energy storage battery; (<b>c</b>) EV1 reference current and actual current; (<b>d</b>) EV1 battery; (<b>e</b>) EV2 reference current and actual current; and (<b>f</b>) EV2 battery.</p>
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<p>The main waveform in one charging pile with dual guns: (<b>a</b>) the contrast between <span class="html-italic">P<sub>g</sub></span>, <span class="html-italic">Q<sub>g</sub></span>, and <span class="html-italic">P<sub>EV</sub></span><sub>1<span class="html-italic">ref</span></sub> and <span class="html-italic">P<sub>EV</sub></span><sub>2<span class="html-italic">ref</span></sub>; (<b>b</b>) energy storage battery; (<b>c</b>) EV1 reference current and actual current; (<b>d</b>) EV1 battery; (<b>e</b>) EV2 reference current and actual current; and (<b>f</b>) EV2 battery.</p>
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36 pages, 1556 KiB  
Review
Overview on Battery Charging Systems for Electric Vehicles
by Pierpaolo Dini, Sergio Saponara and Antonio Colicelli
Electronics 2023, 12(20), 4295; https://doi.org/10.3390/electronics12204295 - 17 Oct 2023
Cited by 18 | Viewed by 14606
Abstract
Catalyzed by the increasing interest in bi-directional electric vehicles, this paper delves into their significance and the challenges they encounter. Bi-directional electric vehicles not only serve as transportation but also function as essential electricity resources. Central to this energy revolution are On-Board Chargers [...] Read more.
Catalyzed by the increasing interest in bi-directional electric vehicles, this paper delves into their significance and the challenges they encounter. Bi-directional electric vehicles not only serve as transportation but also function as essential electricity resources. Central to this energy revolution are On-Board Chargers (OBCs), which are pivotal in converting alternating (AC) energy into direct (DC) energy and vice versa. In this context, we explore the various circuit architectures of OBCs employed in bi-directional electric vehicles. We delve into the intricacies of rectifiers, switching converters, and the application of advanced control and filtering technologies. Our analysis extends to the implications of these circuit architectures on aspects such as voltage regulation capability, energy efficiency, and thermal management. Furthermore, we address the broader significance of these developments in the integration of bidirectional systems, which are driving advances in circuit architectures to better harness the energy flexibility of electric vehicles. We emphasize the critical role of bi-directional electric vehicles in the transition toward a smart and sustainable energy grid. To enhance accessibility for a diverse readership, we will provide concise definitions or explanations for technical terms used throughout the paper, ensuring that our work is approachable even for those who may not be experts in the field. Full article
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<p>Schematic representation of differences in on-board chargers and off-board chargers (or DC-fast charging station).</p>
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<p>Type of connector and their usage in related areas.</p>
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<p>Schematic summary of power levels for OBC devices and related estimation of charging times.</p>
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<p>Typical configurations of an OBC device: (<b>a</b>) single stage with only one device that act as AC/DC; (<b>b</b>) double-stage with a rectifier to reach the DC-link voltage level and a “compact” DC/DC converter connected to the battery; and (<b>c</b>) multi-stage where typical galvanic isolation is integrated.</p>
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<p>Basic filter configurations: (<b>a</b>) C-Filter; (<b>b</b>) L-Filter; (<b>c</b>) CL-Filter; (<b>d</b>) LC-Filter; (<b>e</b>) <math display="inline"><semantics> <mo>Π</mo> </semantics></math>-Filter; and (<b>f</b>) T-Filter.</p>
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<p>Typical suitability of various device types based on voltage and switching frequency considerations.</p>
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<p>Comparison of the switching technologies with respect to the coverage of main application features.</p>
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<p>Interleaved boost PFC schematic.</p>
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<p>Bridgeless Totem-Pole PFC Schematic.</p>
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<p>Interleaved Totem-Pole PFC circuit topology.</p>
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<p>Typical circuit configuration of a three-phase active rectifier.</p>
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<p>Typical circuit configuration of a Phase-Shifting Full-Bridge converter.</p>
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<p>Typical Dual Active Bridge Single-phase Circuital configuration.</p>
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<p>Typical Dual Active Bridge three-phase circuits, highlighting galvanic isolation transformer configurations.</p>
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<p>Typical circuit of LLC converters.</p>
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<p>Typical circuit configuration of a CLLC resonant converter.</p>
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16 pages, 7831 KiB  
Article
Model Predictive Control of a PUC5-Based Dual-Output Electric Vehicle Battery Charger
by Hamza Makhamreh, Meryem Kanzari and Mohamed Trabelsi
Sustainability 2023, 15(19), 14483; https://doi.org/10.3390/su151914483 - 4 Oct 2023
Viewed by 1236
Abstract
In this study, a model predictive control (MPC) technique is applied to a packed-u-cell (PUC)-based dual-output bidirectional electric vehicle (EV) battery charger. The investigated topology is a 5-level PUC-based power factor correction (PFC) rectifier allowing the generation of two levels of DC output [...] Read more.
In this study, a model predictive control (MPC) technique is applied to a packed-u-cell (PUC)-based dual-output bidirectional electric vehicle (EV) battery charger. The investigated topology is a 5-level PUC-based power factor correction (PFC) rectifier allowing the generation of two levels of DC output voltages. The optimization of the MPC cost function is performed by reducing the errors on the capacitors’ voltages (DC output voltages) and the grid (input) current. Moreover, the desired capacitors’ voltages and peak value of the input current are considered within the designed cost function to normalize the errors. In addition, an external PI controller is used to generate the amplitude of the grid current reference based on the computed errors on the capacitors’ voltages. The presented simulation and experimental results recorded using a 1 kW laboratory prototype demonstrate the high performance of the proposed approach in rectifying the AC source at different levels (dual rectifier), while drawing a sinusoidal current from the grid with low THD (around 4%) and ensuring a unity power factor operation. Full article
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<p>The proposed PUC5-based dual-output EV battery charger.</p>
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<p>Proposed control synoptic.</p>
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<p>Flowchart of the proposed control algorithm.</p>
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<p>Simulation results of the steady-state response (<span class="html-italic">R</span><sub>1</sub> = <span class="html-italic">R</span><sub>2</sub> = 80 Ω).</p>
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<p>Simulation results of the steady-state response (<span class="html-italic">R</span><sub>1</sub> = <span class="html-italic">R</span><sub>2</sub> = 80 Ω) showing the unity power factor operation: (<b>a</b>) Grid Synchronization, (<b>b</b>) Injected active power, (<b>c</b>) Injected reactive power.</p>
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<p>FFT analysis and computed THD of the grid current during steady-state operation.</p>
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<p>Simulation results of the dynamic performance during a 50% step-down variation in load 1.</p>
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<p>Simulation results of the dynamic performance during a 100% step-up variation in load 2.</p>
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<p>Simulation results of the dynamic performance during 20% grid voltage sag.</p>
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<p>Experimental prototype of the studied PUC5 dual-output rectifier.</p>
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<p>Steady-state experimental results (<span class="html-italic">R</span><sub>1</sub> = <span class="html-italic">R</span><sub>2</sub> = 80 Ω).</p>
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<p>Experimental results of the dynamic performance during a 50% step-down variation in load 1.</p>
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<p>Experimental results of the dynamic performance during a 100% step-up variation in load 2.</p>
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<p>Experimental results of the dynamic performance during 20% grid voltage swell.</p>
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<p>Experimental results of the parameters mismatch test (+30% in the inductance value <span class="html-italic">L<sub>s</sub></span>).</p>
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18 pages, 13068 KiB  
Article
Experimental Validation of 40 kW EV Charger Based on Vienna Rectifier and Series-Resonant Dual Active Bridge
by Grzegorz Wrona, Mariusz Zdanowski, Przemysław Trochimiuk, Jacek Rąbkowski and Radosław Sobieski
Energies 2023, 16(15), 5797; https://doi.org/10.3390/en16155797 - 4 Aug 2023
Cited by 4 | Viewed by 2491
Abstract
This work presents the experimental validation of a 40 kW electric vehicle (EV) charger. The proposed system comprises two 20 kW modules connected in parallel at the input and output. Each module has two stages—as a grid converter Vienna Rectifier (VR) was chosen, [...] Read more.
This work presents the experimental validation of a 40 kW electric vehicle (EV) charger. The proposed system comprises two 20 kW modules connected in parallel at the input and output. Each module has two stages—as a grid converter Vienna Rectifier (VR) was chosen, and as an isolated DC/DC stage, two Series-Resonant Dual-Active-Bridges (SRDABs) in input-series-output-parallel (ISOP) configurations were applied. The AC/DC and DC/DC stages were enclosed in 2U rack standard housing. A bipolar DC-link with ±400 V DC voltage was employed to connect both stages of the charger module while the charger’s output is dedicated to serving 800 V batteries. VRs operated at 66 kHz switching frequency and the SRDABs operated at 100 kHz. The converters used in the charger structure were based on silicon carbide (SiC) power devices. The description and parameters of the built hardware prototypes of both—AC/DC and DC/DC—converters are provided. Moreover, the experimental validation of each stage and the whole charging system, including oscilloscope waveforms and power analyzer measurements at nominal power, are included. Such a configuration enables energy conversion with high efficiency without a negative impact on the grid and high-quality grid waveforms. Full article
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<p>Overall scheme of the 40 kW EV charging system.</p>
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<p>Schemes of the: Vienna Rectifier connected to the three-phase grid (<b>a</b>) and Series-Resonant Dual-Active-Bridge (<b>b</b>).</p>
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<p>Schemes of the: Vienna Rectifier connected to the three-phase grid (<b>a</b>) and Series-Resonant Dual-Active-Bridge (<b>b</b>).</p>
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<p>Photo of the developed 20-kVA Vienna Rectifier.</p>
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<p>Photo of the developed 2 × 10 kW Series-Resonant Dual-Active-Bridge.</p>
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<p>Block scheme of the Vienna Rectifier control method.</p>
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<p>Extended SRF-PLL algorithm.</p>
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<p>Higher harmonics compensation module.</p>
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<p>SRDAB control scheme.</p>
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<p>Steady-state operation of the Vienna Rectifier, from top: selected phase voltage (C3), selected phase current (C1), and one of the VR output DC voltage (C2).</p>
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<p>Efficiency measurement of the Vienna Rectifier at nominal power in standalone operation.</p>
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<p>Steady-state operation of the two 10 kW Series-Resonant DABs, from top: transformers secondary voltages (C2, C4) and currents (C1, C3).</p>
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<p>Efficiency measurement of the two 10 kW Series-Resonant DABs.</p>
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<p>Scheme of the laboratory setup for single Ev charger module testing.</p>
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<p>Start-up of the Vienna Rectifier: C1 (500 V/div)—one of the three-phase grid voltages; C2 (50 A/div)—one of the three-phase grid currents; C3 (100 V/div)—load voltage; C4 (5 A/div)—load current; C5 (100 V/div), C6 (100 V/div)—Vienna Rectifier DC-link capacitor voltages.</p>
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<p>Steady-state of the input and output waveforms: C1 (100 V/div)—one of the three-phase grid voltages; C2 (10 A/div)—one of the three-phase grid currents; C3 (100 V/div)—load voltage; C4 (5 A/div)—load current; C5 (100 V/div), C6 (100 V/div)—Vienna Rectifier DC-link capacitor voltages).</p>
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<p>Power quality and efficiency measurement of the EV charging system @ 20 kW.</p>
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<p>Efficiency and power losses measurement of the EV charger module.</p>
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<p>Photo of the complete EV charging system—4 × 2U rack housings.</p>
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<p>Scheme of laboratory setup for testing the entire EV charger at nominal conditions of 40 kW.</p>
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<p>Waveforms of input and output parameters during 40 kW operation of both charger modules: C2 (100 V/div)—VR output first half DC link voltage, C3 (50 A/div)—grid current, C4 (200 V/div)—VR output second half DC link voltage.</p>
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<p>Power measurement of 2 × 20 kW EV system.</p>
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19 pages, 2402 KiB  
Review
Technical Review and Survey of Future Trends of Power Converters for Fast-Charging Stations of Electric Vehicles
by Halise Kilicoglu and Pietro Tricoli
Energies 2023, 16(13), 5204; https://doi.org/10.3390/en16135204 - 6 Jul 2023
Cited by 9 | Viewed by 4564
Abstract
The development and implementation of electric vehicles have significantly increased and are profoundly reshaping the automotive sector. However, long charging times, limited driving range, and difficulties as to suitable charger converter design are the main limitations of the adoption of EV technology. DC [...] Read more.
The development and implementation of electric vehicles have significantly increased and are profoundly reshaping the automotive sector. However, long charging times, limited driving range, and difficulties as to suitable charger converter design are the main limitations of the adoption of EV technology. DC fast-chargers offer the best solution for mitigating the charging time problems of EVs. This paper provides an extensive review of the status of the technical development of fast-charging infrastructure architectures and standards, and a classification of fast-charging methods. Key power electronic converter topologies for fast-charging systems, with their advantages and comparisons, are also addressed. Full article
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<p>The basic diagrams of four types of EVs and their operation principles.</p>
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<p>The basic concept of an EV charger.</p>
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<p>Classification of EV charging methods.</p>
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<p>Conductive charging system with both AC and DC charging methods.</p>
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<p>Block diagram of DC fast-charger power conversion stages with: (<b>a</b>) LFT configuration; and (<b>b</b>) SST-based HFT configuration.</p>
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<p>The classification of DC fast-charging station architectures.</p>
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<p>Block diagrams of DC fast-charging station architectures: (<b>a</b>) AC bus configuration; (<b>b</b>) DC bus configuration; (<b>c</b>) Combination of AC and DC bus-based configurations.</p>
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<p>The most common AC/DC rectifiers: (<b>a</b>) 12-pulse diode bridge rectifier; (<b>b</b>) Vienna rectifier; (<b>c</b>) PWM rectifier; (<b>d</b>) NPC rectifier.</p>
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<p>The most common DC/DC converters: (<b>a</b>) LLC resonant converter; (<b>b</b>) DAB converter; (<b>c</b>) PSFB converter.</p>
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<p>The structure of a three-phase MMC with full and half bridges.</p>
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<p>Classification of the AC/DC and DC/DC converters covered in this paper.</p>
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16 pages, 2983 KiB  
Article
Data-Driven Modeling of Vehicle-to-Grid Flexibility in Korea
by Moon-Jong Jang, Taehoon Kim and Eunsung Oh
Sustainability 2023, 15(10), 7938; https://doi.org/10.3390/su15107938 - 12 May 2023
Cited by 3 | Viewed by 1955
Abstract
With the widespread use of electric vehicles (EVs), the potential to utilize them as flexible resources has increased. However, the existing vehicle-to-grid (V2G) studies have focused on V2G operation methods. The operational performance is limited by the amount of availability resources, which represents [...] Read more.
With the widespread use of electric vehicles (EVs), the potential to utilize them as flexible resources has increased. However, the existing vehicle-to-grid (V2G) studies have focused on V2G operation methods. The operational performance is limited by the amount of availability resources, which represents the flexibility. This study proposes a data-driven modeling method to estimate the V2G flexibility. A charging station is a control point connected to a power grid for V2G operation. Therefore, the charging stations’ statuses were analyzed by applying the basic queuing model with a dataset of 1008 chargers (785 AC chargers and 223 DC chargers) from 500 charging stations recorded in Korea. The basic queuing model obtained the long-term average status values of the stations over the entire time period. To estimate the V2G flexibility over time, a charging station status modeling method was proposed within a time interval. In the proposed method, the arrival rate and service time were modified according to the time interval, and the station status was expressed in a propagated form that considered the current and previous time slots. The simulation results showed that the proposed method effectively estimated the actual value within a 10% mean absolute percentage error. Moreover, the determination of V2G flexibility based on the charging station status is discussed herein. According to the results, the charging station status in the next time slot, as well as that in the current time slot, is affected by the V2G. Therefore, to estimate the V2G flexibility, the propagation effect must be considered. Full article
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<p>AC charger station status. (<b>a</b>) AC charger station status sorted in descending order; (<b>b</b>) CDF of AC charger station status. Note that, in <a href="#sustainability-15-07938-f001" class="html-fig">Figure 1</a>b, the CDF presented on the <span class="html-italic">y</span>-axis is the probability that the station status is less than or equal to the given station status presented on the <span class="html-italic">x</span>-axis. The maximum x-value is 2.99 in <a href="#sustainability-15-07938-f001" class="html-fig">Figure 1</a>a. However, because the case in which the station status exceeds 1 is very rare, as shown in <a href="#sustainability-15-07938-f001" class="html-fig">Figure 1</a>a, only values up to 1 are displayed in <a href="#sustainability-15-07938-f001" class="html-fig">Figure 1</a>b.</p>
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<p>Representative utilization profiles for AC charger stations. (<b>a</b>) Office building; (<b>b</b>) residential building; (<b>c</b>) supermarket; and (<b>d</b>) community service center.</p>
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<p>DC charger station status. (<b>a</b>) DC charger station status sorted in descending order; (<b>b</b>) CDF of DC charger station status.</p>
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<p>Representative utilization profiles for DC charger stations. (<b>a</b>) Supermarket; (<b>b</b>) district office.</p>
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<p>Constitution of V2G flexibility modeling method.</p>
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<p>Comparisons of the actual utilization and utilization obtained by status modeling. (<b>a</b>) PAC1; (<b>b</b>) PDC1.</p>
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<p>Station status change of PDC1 according to DR program participation of 0.5 h, <math display="inline"><semantics> <mrow> <mo>Δ</mo> <mi>C</mi> <mo>=</mo> <mn>0.5</mn> </mrow> </semantics></math>. (<b>a</b>) Utilization; (<b>b</b>) blocking probability.</p>
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<p>V2G flexibility estimation of PDC1 according to the blocking probability constraint. The dashed circles represent the high utilization region in <a href="#sustainability-15-07938-f007" class="html-fig">Figure 7</a>a. (<b>a</b>) <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>γ</mi> </mrow> <mrow> <mi>T</mi> <mi>h</mi> </mrow> </msub> <mo>=</mo> <mn>5</mn> <mo mathvariant="normal">%</mo> </mrow> </semantics></math>; (<b>b</b>) <math display="inline"><semantics> <mrow> <msub> <mrow> <mi>γ</mi> </mrow> <mrow> <mi>T</mi> <mi>h</mi> </mrow> </msub> <mo>=</mo> <mn>10</mn> <mo mathvariant="normal">%</mo> </mrow> </semantics></math>.</p>
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45 pages, 5661 KiB  
Review
A Comprehensive Review of GaN-Based Bi-directional On-Board Charger Topologies and Modulation Methods
by Olcay Bay, Manh Tuan Tran, Mohamed El Baghdadi, Sajib Chakraborty and Omar Hegazy
Energies 2023, 16(8), 3433; https://doi.org/10.3390/en16083433 - 13 Apr 2023
Cited by 13 | Viewed by 6732
Abstract
The wide-scale adoption and accelerated growth of electric vehicle (EV) use and increasing demand for faster charging necessitate the research and development of power electronic converters to achieve high-power, compact, and reliable EV charging solutions. Although the fast charging concept is often associated [...] Read more.
The wide-scale adoption and accelerated growth of electric vehicle (EV) use and increasing demand for faster charging necessitate the research and development of power electronic converters to achieve high-power, compact, and reliable EV charging solutions. Although the fast charging concept is often associated with off-board DC chargers, the importance of on-board AC fast charging is undeniable with the increasing battery capacities. This article comprehensively reviews gallium nitride (GaN) semiconductor-based bidirectional on-board charger (OBC) topologies used in both 400 V and 800 V EV applications. Moreover, comparative evaluations of GaN-based bi-directional OBC topologies regarding power conversion losses (conduction loss and soft switching capabilities), power density, implementation considerations, power quality, electromagnetic interference, and reliability aspects have been presented. The status of commercially available GaN power modules, advancements in GaN technology, applicable industry standards, and application requirements for OBCs have been also included in this study. Finally, in light of forthcoming advancements in GaN power transistor technology, this study highlights potential areas of research related to the reviewed topologies. Such research can aid researchers and designers in improving the performance and user experience of electric vehicles, ultimately supporting the widespread adoption of EVs. Full article
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<p>Illustration of AC charging modes (Mode 2 and Mode 3) as per IEC 61851-1 [<xref ref-type="bibr" rid="B32-energies-16-03433">32</xref>,<xref ref-type="bibr" rid="B38-energies-16-03433">38</xref>].</p>
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<p>Typical battery current and voltage waveforms for (<bold>a</bold>) G2V, (<bold>b</bold>) V2G.</p>
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<p>Illustration of monolithic integration of driver and half-bridge configuration on a single die [<xref ref-type="bibr" rid="B64-energies-16-03433">64</xref>,<xref ref-type="bibr" rid="B66-energies-16-03433">66</xref>,<xref ref-type="bibr" rid="B67-energies-16-03433">67</xref>].</p>
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<p>Comparison of wafer cost of GaN-on-GaN and GaN-on-Si technology with SiC wafer cost [<xref ref-type="bibr" rid="B53-energies-16-03433">53</xref>].</p>
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<p>A practical implementation of (<bold>a</bold>) bottom-side cooled (<bold>b</bold>) top-side cooled GaN devices on a 4-layer PCB (derived from [<xref ref-type="bibr" rid="B9-energies-16-03433">9</xref>,<xref ref-type="bibr" rid="B80-energies-16-03433">80</xref>]).</p>
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<p>Practical GaN transistor gate driver alternatives based on (<bold>a</bold>) bootstrap [<xref ref-type="bibr" rid="B9-energies-16-03433">9</xref>,<xref ref-type="bibr" rid="B74-energies-16-03433">74</xref>] supply (<bold>b</bold>), isolated supply [<xref ref-type="bibr" rid="B9-energies-16-03433">9</xref>,<xref ref-type="bibr" rid="B74-energies-16-03433">74</xref>]. Blue printed and green printed symbols represent optional components and parasitic circuit elements respectively.</p>
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<p>Switching loop inductances showing the priority, synthesized from [<xref ref-type="bibr" rid="B9-energies-16-03433">9</xref>,<xref ref-type="bibr" rid="B80-energies-16-03433">80</xref>].</p>
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<p>Typical on-board-charger architecture in Mode-3 AC charging configuration (derived from [<xref ref-type="bibr" rid="B31-energies-16-03433">31</xref>,<xref ref-type="bibr" rid="B32-energies-16-03433">32</xref>,<xref ref-type="bibr" rid="B89-energies-16-03433">89</xref>]).</p>
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<p>Classification of bi-directional converter topologies for the OBC.</p>
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<p>Matrix-type bi-directional three-phase AC/DC converter based on GaN transistors (derived from [<xref ref-type="bibr" rid="B102-energies-16-03433">102</xref>,<xref ref-type="bibr" rid="B104-energies-16-03433">104</xref>]).</p>
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<p>(<bold>a</bold>) Three-phase three-level active neutral point clamped ANPC converter (derived from [<xref ref-type="bibr" rid="B106-energies-16-03433">106</xref>,<xref ref-type="bibr" rid="B107-energies-16-03433">107</xref>]) and (<bold>b</bold>) three-phase flying-capacitor multi-level (FCML) converter (derived from [<xref ref-type="bibr" rid="B100-energies-16-03433">100</xref>,<xref ref-type="bibr" rid="B106-energies-16-03433">106</xref>]).</p>
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<p>T-type active-front-end rectifier using Si/SiC MOSFETs and GaN transistors [<xref ref-type="bibr" rid="B63-energies-16-03433">63</xref>].</p>
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<p>Phase modular charger architecture in a (<bold>a</bold>) three-phase (<bold>b</bold>) single-phase application.</p>
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<p>Usage of a charger module as an active power decoupling unit in single-phase operation as explained in [<xref ref-type="bibr" rid="B98-energies-16-03433">98</xref>].</p>
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<p>Single-phase single-stage (<bold>a</bold>) dual active bridge (DAB) AC/DC converter proposed by [<xref ref-type="bibr" rid="B110-energies-16-03433">110</xref>] and (<bold>b</bold>) series-resonant DAB AC/DC converter proposed by [<xref ref-type="bibr" rid="B121-energies-16-03433">121</xref>].</p>
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<p>(<bold>a</bold>) GaN-based totem-pole PFC rectifier, (<bold>b</bold>) interleaved GaN-based totem-pole PFC rectifier, (<bold>c</bold>) GaN-based T-type totem-pole rectifier proposed by [<xref ref-type="bibr" rid="B127-energies-16-03433">127</xref>].</p>
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<p>Generalized structure of single-phase N-level FCML totem-pole GaN PFC (<bold>a</bold>) with H-bridge unfolder/folder and (<bold>b</bold>) with half-bridge unfolder/folder.</p>
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<p>Generalized structure of single-phase N-level MMC-based AC/DC converter (derived from [<xref ref-type="bibr" rid="B8-energies-16-03433">8</xref>]).</p>
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<p>(<bold>a</bold>) Dual active bridge (DAB) converter, (<bold>b</bold>) dual active half-bridge (DAHB) converter proposed by [<xref ref-type="bibr" rid="B139-energies-16-03433">139</xref>].</p>
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<p>(<bold>a</bold>) Three-level ANPC dual active half-bridge converter proposed by [<xref ref-type="bibr" rid="B137-energies-16-03433">137</xref>]. (<bold>b</bold>) series-input series-output (SISO) DAB converter (derived from [<xref ref-type="bibr" rid="B99-energies-16-03433">99</xref>]) for 800 V EV applications.</p>
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<p>(<bold>a</bold>) Full-bridge and (<bold>b</bold>) half-bridge CLLC (derived from [<xref ref-type="bibr" rid="B153-energies-16-03433">153</xref>]) converter topologies.</p>
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<p>Multi-level DC/DC resonant converters proposed in the literature. (<bold>a</bold>) LCL-T resonant converter (edited from [<xref ref-type="bibr" rid="B94-energies-16-03433">94</xref>]) and conceptual (<bold>b</bold>) DAB converter with series stacked half-bridge secondary, (<bold>c</bold>) Stacked half-bridge (<bold>d</bold>) and its symmetrical full-bridge variant for 800 V EV charging applications (edited from [<xref ref-type="bibr" rid="B106-energies-16-03433">106</xref>]).</p>
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<p>Bi-directional (<bold>a</bold>) hybrid resonant input-series output-parallel (ISOP) isolated resonant converter (derived from [<xref ref-type="bibr" rid="B90-energies-16-03433">90</xref>]), (<bold>b</bold>) input-parallel output-series (IPOS) isolated resonant partial power (PP) converter (derived from [<xref ref-type="bibr" rid="B156-energies-16-03433">156</xref>]), (<bold>c</bold>) LCL-T resonant converter [<xref ref-type="bibr" rid="B94-energies-16-03433">94</xref>], (<bold>d</bold>) (conceptual) SIPO resonant converter (edited from [<xref ref-type="bibr" rid="B106-energies-16-03433">106</xref>]) for 400 V EV charging applications.</p>
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15 pages, 413 KiB  
Article
Statistical Analysis of Electric Vehicle Charging Based on AC Slow Chargers
by Dong Sik Kim, Young Mo Chung and Beom Jin Chung
Energies 2023, 16(6), 2735; https://doi.org/10.3390/en16062735 - 15 Mar 2023
Cited by 7 | Viewed by 2140
Abstract
Regarding DC fast chargers, various studies, such as the charge scheduling, have been conducted. On the other hand, research on AC slow chargers has rarely been conducted due to the predictable and simple usage pattern. Despite the long charging times of AC slow [...] Read more.
Regarding DC fast chargers, various studies, such as the charge scheduling, have been conducted. On the other hand, research on AC slow chargers has rarely been conducted due to the predictable and simple usage pattern. Despite the long charging times of AC slow chargers, which use the existing electric outlets with relatively low supplied power, these chargers are suitable for daily home charging of electric vehicles (EVs) during the night. Due to their low installation costs, they are likely to be the dominant type of charging equipment. In this paper, the EV charging process based on AC slow chargers, which supply a maximum power of 3 kW from an AC 220 V outlet, is analyzed by constructing a simple charging model. The charging time and fees are statistically derived and investigated. Furthermore, power load curves for charging EVs with the 3 kW charger are observed. From the statistical analyses, we conclude that daily charging of EVs can be an appropriate scenario in using the AC slow chargers, and the power load can be spread without employing any demand response schemes. Full article
Show Figures

Figure 1

Figure 1
<p>EV charging model for the AC slow charger. The AC power is supplied from a regular AC 220 V outlet a the maximum current of 16 A to the OBC, which converts the AC power to DC power and charges the battery.</p>
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<p>Distribution example of the driving distance <span class="html-italic">x</span> (KEPRI, 2022). Average driving distance per month is 1889 km (<math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>60.9</mn> </mrow> </semantics></math> km).</p>
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<p>Examples of the slow-rate plan <math display="inline"><semantics> <mrow> <mi>r</mi> <mo>(</mo> <mi>t</mi> <mo>)</mo> </mrow> </semantics></math> (KRW 1000 is USD 0.83).</p>
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<p>Charging fee <math display="inline"><semantics> <mrow> <mi>B</mi> <mo>(</mo> <mi>s</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> </mrow> </semantics></math> of (<a href="#FD6-energies-16-02735" class="html-disp-formula">6</a>) when charging with the rate plans of <a href="#energies-16-02735-f003" class="html-fig">Figure 3</a> (<math display="inline"><semantics> <mrow> <mi>α</mi> <mo>=</mo> <mn>5.2</mn> </mrow> </semantics></math> km/kWh, <math display="inline"><semantics> <mrow> <mi>η</mi> <mo>=</mo> <mn>0.95</mn> </mrow> </semantics></math>, <math display="inline"><semantics> <mrow> <mover accent="true"> <mi>ρ</mi> <mo>¯</mo> </mover> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math> kW, and KRW 1000 is USD 0.83).</p>
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<p>Example of the charging start time distribution <math display="inline"><semantics> <msub> <mi>f</mi> <mi>S</mi> </msub> </semantics></math>: slow charger usage over the time interval (KPX, June 2021).</p>
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<p>Charging fee example for Plan 1 of <a href="#energies-16-02735-f003" class="html-fig">Figure 3</a> and the distribution <math display="inline"><semantics> <msub> <mi>f</mi> <mi>S</mi> </msub> </semantics></math> of <a href="#energies-16-02735-f005" class="html-fig">Figure 5</a>, when the supplied power is <math display="inline"><semantics> <mrow> <mover accent="true"> <mi>ρ</mi> <mo>¯</mo> </mover> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math> kW (KRW 1000 is USD 0.83). (<b>a</b>) Conditional mean charging fee <math display="inline"><semantics> <mrow> <mi>E</mi> <mfenced separators="" open="{" close="}"> <mi>B</mi> <mo>(</mo> <mi>S</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> </mfenced> </mrow> </semantics></math> of (<a href="#FD8-energies-16-02735" class="html-disp-formula">8</a>). (<b>b</b>) Normalized conditional charging fee <math display="inline"><semantics> <mrow> <mi>E</mi> <mfenced separators="" open="{" close="}"> <mi>B</mi> <mo>(</mo> <mi>S</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> </mfenced> <mo>/</mo> <mi>x</mi> </mrow> </semantics></math>.</p>
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<p>Power load curves <math display="inline"><semantics> <mrow> <mi>p</mi> <mo>(</mo> <mi>t</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> </mrow> </semantics></math> for each time interval of <a href="#energies-16-02735-t007" class="html-table">Table 7</a> with the upper mean fuel efficiency of <math display="inline"><semantics> <mrow> <mi>α</mi> <mo>=</mo> <mn>5.44</mn> </mrow> </semantics></math> km/kWh. The charging start time distribution of <a href="#energies-16-02735-f005" class="html-fig">Figure 5</a> is used, and the charging efficiency is <math display="inline"><semantics> <mrow> <mi>η</mi> <mo>=</mo> <mn>0.95</mn> </mrow> </semantics></math>. (<b>a</b>) The charging power is <math display="inline"><semantics> <mrow> <mover accent="true"> <mi>ρ</mi> <mo>¯</mo> </mover> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math> kW. The maximum power of <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>80</mn> </mrow> </semantics></math> km is 0.966 kW at 2:00 a.m. (<b>b</b>) The charging power is <math display="inline"><semantics> <mrow> <mover accent="true"> <mi>ρ</mi> <mo>¯</mo> </mover> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math> kW. The maximum power of <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>80</mn> </mrow> </semantics></math> km is 0.923 kW at 3:00 a.m.</p>
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<p>Power load curves <math display="inline"><semantics> <mrow> <mi>p</mi> <mo>(</mo> <mi>t</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> </mrow> </semantics></math> for each time interval of <a href="#energies-16-02735-t008" class="html-table">Table 8</a> with the lower mean fuel efficiency of <math display="inline"><semantics> <mrow> <mi>α</mi> <mo>=</mo> <mn>4.04</mn> </mrow> </semantics></math> km/kWh. The charging start time distribution of <a href="#energies-16-02735-f005" class="html-fig">Figure 5</a> is used and the charging efficiency is <math display="inline"><semantics> <mrow> <mi>η</mi> <mo>=</mo> <mn>0.95</mn> </mrow> </semantics></math>. (<b>a</b>) The charging power is <math display="inline"><semantics> <mrow> <mover accent="true"> <mi>ρ</mi> <mo>¯</mo> </mover> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math> kW. The maximum power of <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>80</mn> </mrow> </semantics></math> km is 1.26 kW at 3:00 a.m. (<b>b</b>) The charging power is <math display="inline"><semantics> <mrow> <mover accent="true"> <mi>ρ</mi> <mo>¯</mo> </mover> <mo>=</mo> <mn>2</mn> </mrow> </semantics></math> kW. The maximum power of <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>80</mn> </mrow> </semantics></math> km is 1.17 kW at 5:00 a.m.</p>
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<p>Peak load and time with respect to the charging mean power (<math display="inline"><semantics> <mrow> <mi>α</mi> <mo>=</mo> <mn>5.2</mn> </mrow> </semantics></math> km/kWh, <math display="inline"><semantics> <mrow> <mi>η</mi> <mo>=</mo> <mn>0.95</mn> </mrow> </semantics></math>, and <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>39.6</mn> </mrow> </semantics></math> km). (<b>a</b>) Peak load <math display="inline"><semantics> <mrow> <msub> <mo movablelimits="true" form="prefix">max</mo> <mi>t</mi> </msub> <mi>p</mi> <mrow> <mo>(</mo> <mi>t</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> </mrow> </mrow> </semantics></math> with respect to <math display="inline"><semantics> <mover accent="true"> <mi>ρ</mi> <mo>¯</mo> </mover> </semantics></math>. (<b>b</b>) Peak load time <math display="inline"><semantics> <mrow> <mo form="prefix">arg</mo> <msub> <mo movablelimits="true" form="prefix">max</mo> <mi>t</mi> </msub> <mi>p</mi> <mrow> <mo>(</mo> <mi>t</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> </mrow> </mrow> </semantics></math> with respect to <math display="inline"><semantics> <mover accent="true"> <mi>ρ</mi> <mo>¯</mo> </mover> </semantics></math>.</p>
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<p>Charging fee <math display="inline"><semantics> <mrow> <mi>E</mi> <mfenced separators="" open="{" close="}"> <mi>B</mi> <mo>(</mo> <mi>S</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> </mfenced> </mrow> </semantics></math> with respect to the supplied power <math display="inline"><semantics> <mover accent="true"> <mi>ρ</mi> <mo>¯</mo> </mover> </semantics></math> for the slow-rate plans and the charging start time distribution <math display="inline"><semantics> <msub> <mi>f</mi> <mi>S</mi> </msub> </semantics></math> of <a href="#energies-16-02735-f005" class="html-fig">Figure 5</a> (<math display="inline"><semantics> <mrow> <mi>α</mi> <mo>=</mo> <mn>5.2</mn> </mrow> </semantics></math> km/kWh, <math display="inline"><semantics> <mrow> <mi>η</mi> <mo>=</mo> <mn>0.95</mn> </mrow> </semantics></math>, and KRW 1000 is USD 0.83). (<b>a</b>) Charging fee curve for the driving distance of <math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>39.6</mn> </mrow> </semantics></math> km. The minimum charging fee is KRW 1682 at <math display="inline"><semantics> <mrow> <mover accent="true"> <mi>ρ</mi> <mo>¯</mo> </mover> <mo>=</mo> <mn>1.61</mn> </mrow> </semantics></math> kW. (<b>b</b>) Optimal supplied mean power with respect to the driving distance.</p>
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<p>Peak loads from <math display="inline"><semantics> <mrow> <msub> <mo movablelimits="true" form="prefix">max</mo> <mi>t</mi> </msub> <mi>p</mi> <mrow> <mo>(</mo> <mi>t</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> </mrow> </mrow> </semantics></math> (<math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>39.6</mn> </mrow> </semantics></math> km and <math display="inline"><semantics> <mrow> <mover accent="true"> <mi>ρ</mi> <mo>¯</mo> </mover> <mo>=</mo> <mn>3</mn> </mrow> </semantics></math> kW). (<b>a</b>) Peak load with respect to the fuel efficiency <math display="inline"><semantics> <mi>α</mi> </semantics></math> for <math display="inline"><semantics> <mrow> <mi>η</mi> <mo>=</mo> <mn>0.95</mn> </mrow> </semantics></math>. (<b>b</b>) Peak load with respect to the charging efficiency <math display="inline"><semantics> <mi>η</mi> </semantics></math> for <math display="inline"><semantics> <mrow> <mi>α</mi> <mo>=</mo> <mn>5.2</mn> </mrow> </semantics></math> km/kWh.</p>
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<p>Comparison of the slow chargers of Class 3 kW and Class 7–11 kW for Plan 1 of <a href="#energies-16-02735-f003" class="html-fig">Figure 3</a> (<math display="inline"><semantics> <mrow> <mi>x</mi> <mo>=</mo> <mn>39.6</mn> </mrow> </semantics></math> km, <math display="inline"><semantics> <mrow> <mi>α</mi> <mo>=</mo> <mn>5.44</mn> </mrow> </semantics></math> km/kWh, <math display="inline"><semantics> <mrow> <mi>η</mi> <mo>=</mo> <mn>0.95</mn> </mrow> </semantics></math>, and KRW 1000 is USD 0.83). (<b>a</b>) Charging fee <math display="inline"><semantics> <mrow> <mi>B</mi> <mo>(</mo> <mi>s</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> </mrow> </semantics></math> and <math display="inline"><semantics> <mrow> <mi>E</mi> <mo>{</mo> <mi>B</mi> <mo>(</mo> <mi>S</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> <mo>}</mo> </mrow> </semantics></math>. (<b>b</b>) Load power <math display="inline"><semantics> <mrow> <mi>p</mi> <mo>(</mo> <mi>t</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> </mrow> </semantics></math> and the peak load <math display="inline"><semantics> <mrow> <msub> <mo movablelimits="true" form="prefix">max</mo> <mi>t</mi> </msub> <mi>p</mi> <mrow> <mo>(</mo> <mi>t</mi> <mo>,</mo> <mi>x</mi> <mo>)</mo> </mrow> </mrow> </semantics></math>.</p>
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